CARNEGIEINSTITUTE
OF TECHNOLOGY
LI Bit All Y
PRESENTED BY
i.. Williams
Electrical
Engineering Papers
By Benjamin Q. Lamme
This volume contains a collection of the author's
more important engineering papers presented
before various technical societies and
published in engineering journals
and elsewhere from
time to time
79/9
Published by
Westinghouse Electric & Mfg. Co.
East Pittsburgh, Pa.
Permission to reprint these papers has been granted
by the owners of the copyrights and individual
credit is given in the foreword of each papei
PREFACE
The papcis of Beniamm G. Lamme have always interested American
engineers Distributed in many publications, some quite macessible to
readers, it is indeed a fortunate circumstance which now makes available a
collection of these papers for engineers, prcfessors, instructors, and students
and all those interested in, and able to understand, the progress of electrical
engineering.
Besides his achievements in the art of engineering, Mr. Lamme has been
gifted with the faculty for clear expression and explanation, which is one of the
rarest to be found in the engineering profession The collection begins with
his early paper on the Polyphase Induction Motor, which, in its time, was a
pnmer of the characteristics and operation of such motois in the hands of the
numerous users of these machines. Then follows a period in which he prepared
few papers, but which was one of great personal activity Then comes his
epoch-making paper, in 1902, before the Ameiican Institute of Electrical
Engineers in New York on the Single-Phase System of the Washington
Baltimore and Annapolis Railway. Up to this time, the development of the
electric railway systems, as a whole, was at a point of complete stagnation,
in the utilization of 600 volts direct current, and this paper represented the
first great and successful attempt to break away from established practice
toward materially higher trolley voltages. Its advent gave an impulse to
the entire subject of the electrification of railroads greater than any other it
had ever received, leading to the complete abandonment of old and apparently
well established standards, as well as to later attempts to meet the new con-
ditions with higher direct-current voltages.
In 1904, there are two papers, one on a 10,000 Cycle Alternator, and
another on the Synchronous Motor for Regulation of Power Factor. In the
same year, he contnbuted a discussion to the subject of Single-Phase Motors
which ranks as one of the clearest and most suggestive descriptions of this type
of motor, which owes to him its development and use.
Recognizing the importance of closer relations with the American Insti-
tute of Electrical Engineers, we find him contributing, from time to time,
papers on Commutation, on the Homopolar Dynamo, on Rotary Converters,
on Turbo Generators, on Losses in Electrical Machinery, and on Engineering
Education, etc. It is safe to say that these papers will be read in their present
form by many who enjoyed them when they came out originally, and their
contents will perhaps be more appreciated today than at the time when they
were written.
To all those who have followed the development of electrical engineering
in America during the past thirty years, and to all those who would like to
know the histoncal development of electrical apparatus, the senes of papers
which appeared in the Electric Journal, on the History of the Railway Motor,
of the Direct-Current Generator and of the Alternating-Current Generator.
and the History of the Frequencies, now collected for the first time, will form
most interesting reading Here Mr, Lamme had an opportunity to recount
the work of himself and of his associates, adding to it the clarity and lucidity
which have always marked his style.
I think those who have known Mr. Lamme 's interest in education and in
his instruction of young engineers will be glad to find reprinted in this volume
two of his contributions on the subject of engineering education. The whole-
some, sound sense which permeates these papers cannot fail to appeal tc all,
and to impress the reader with the sound judgment of their author.
Although these papers represent a work of thirty years, during which
time Mr. Lamme has been continuously associated with the great company
which bears the name of Mr. Westinghouse, yet I believe they do not com-
plete his whole life work Those of us who have had the good fortune to have
known him for a score of years, or more, well know that many contributions
will yet be made by him to the art and science of electrical engineering The
publication by the Westinghouse Company of this collection of Mr. Lammc's
engineering papers on the anniversary of his first connection with this com-
pany, thirty years ago, represents a most dignified appreciation of his services
to the entire engineering profession.
Boston Mass,
April 2, 1919.
CONTENTS
THE POLYPHASE^MOTOR . 1
WASHINGTON, BALTIMORE & ANNAPOLIS SINGLE-PHASE RAILWAY 37
SYNCHRONOUS MOTORS FOR REGULATION OF POWER FACTOR AND LINE
PRESSURE. . .. . .. . S3
DATA AND TESTS ON 10,000 CYCLE PER SECOND ALTERNATOR 65
THE SINGLE-PHASE COMMUTATOR TYPE RAILWAY MOTOR 77
COMPARISON OF SERIES AND REPULSION TYPE A.C. COMMUTATOR MOTORS . .97
COMPARATIVE CAPACITIES OF ALTERNATORS FOR SINGLE AND POLYPHASE
CURRENTS . . . . . .... Ill
DAMPERS ON LARGE SINGLE-PHASE GENERATORS 139
DEVELOPMENT OF A SUCCESSFUL DIRECT- CURRENT 2000 Kw UNIPOLAR
GENERATOR 145
COMMUTATING POLES IN SYNCHRONOUS CONVERTERS . . . . 171
THEORY OF COMMUTATION AND ITS APPLICATION TO COMMUTATING POLE
MACHINES . 201
PHYSICAL LIMITATIONS IN DIRECT-CURRENT COMMUTATING MACHINERY . .247
REGULATION CHARACTERISTICS OF COMMUTATING POLE MACHINES AND
PARALLEL OPERATION WITH OTHER MACHINES 303
HIGH SPEED TURBO ALTERNATORS — DssiGNa AND LIMITATIONS 313
TEMPERATURE AND ELECTRICAL INSULATION 353
TEMPERATURE DISTRIBUTION IN ELECTRICAL MACHINERY . , 365
SOME PRACTICAL CONSIDERATIONS IN ARTIFICIAL VENTILATION FOR ELEC-
TRICAL MACHINERY. . 387
SOME ELECTRICAL PROBLEMS PRACTICALLY CONSIDERED 393
SOME CONTROLLING CONDITIONS IN THE DESIGN AND OPERATION OF RO-
TARY CONVERTERS 441
SIXTY-CYCLE ROTARY CONVERTER 469
IRON LOSSES IN DIRECT-CURRENT MACHINES 487
IRON COMMUTATORS .... 513
POLYPHASE INDUCTION MOTOR WITH SINGLE-PHASE SECONDARY 519
A PHYSICAL CONCEPTION OF THE OPERATION OF THE SINGLE- PHASE IN-
DUCTION MOTOR 525
SINGLE-PHASE LOADS FROM POLYPHASE SYSTEMS -559
THE TECHNICAL STORY OF THE FREQUENCIES 569
THE DEVELOPMENT OF THE ALTERNATING- CURRENT GENERATOR IN AM-
ERICA 591
THE DEVELOPMENT OF THE DIRECT-CURRENT GENERATOR IN AMERICA. . . 645
THE DEVELOPMENT OF THE STREET RAILWAY MOTOR IN AMERICA 721
TECHNICAL TRAINING FOR ENGINEERS 755
ENGINEERING BY ANALYSIS . ...765
THE POLYPHASE MOTOR
FOREWORD— This paper was prepared in the early part of 1897,
or over twenty-two years ago. It was presented at the twentieth
convention of the National Electnc Light Association at Niagara
Falls on June 10, 1897, and was prepared for the purpose of
illustrating the characteristics and properties of the Westing-
house Type C motor which, at that time, was beginning to at-
tract much attention. This motor was radically new in that
it had a "cage" type secondary winding for large, as well as
small, sizes, whereas, it was generally believed that the cage
type was only suitable for small power machines, due to lack
of starting torque. — (ED.)
INTRODUCTION
THE polyphase motor is usually treated from the theoretical
standpoint, and the results obtained are of interest mainly to
designers and investigators. Such treatment has been principally
of a mathematical nature, the object being to show how the
various characteristics of the motor may be predetermined. In
the following treatment of the subject, the general operation of the
motor will be explained in a non-mathematical way by the use
of diagrams which illustrate its characteristics under different
conditions. Only the non-synchronous type of motors will be
considered, and no distinction will be made between two-and
three-phase motors ; for, if properly designed, they are practically
alike in operation.
It is necessary to understand the characteristics of the poly-
phase motor in order to consider properly its application to the
different classes of work to be met with in practice. These
characteristics can be presented in the most intelligible manner by
means of curves, which represent the relations between the speed,
torque or turning effort, horse power expended and developed,
amperes, etc. The speed-torque curve, which represents the
speed in terms of the torque, is the most important one, as upon
this depends the adaptability of the motor to the various kinds of
work. The starting conditions also depend upon the speed-torque
characteristics. The other curves that are of importance in prac-
tice are the current, efficiency aad power factor. As these are
dependent, to some extent, upon the speed-torque curve, this will
be considered first. Before treating of its characteristics a short
description of the motor itself will be given.
2 ELECTRICAL ENGINEERING PAPERS
CONSTRUCTION AND WINDING
The polyphase motor, like a direct-current motor, consists
primarily of two parts, one stationary and the other rotating, each
of which carries windings. The inside bore, or face, of the sta-
tionery part is generally slotted, and carries windings that resemble
those of the rotating part, or armature of an ordinary direct-current
motor without commutator. The rotating part is also slotted on
its outside face, and there are windings in the slots. Both cores,
or bodies, are built up of thin iron or steel plates. The general
arrangement is shown in Fig. 1. One of these windings, generally
FIG. 1— ARRANGEMENT OP WINDINGS OF THE POLYPHASE MOTOR
AND THE MAGNETIC FIELDS WHICH ARE PRODUCED.
that on the stationary part, receives current from a two or three-
phase supply circuit. The coils of this winding, although dis-
tributed symmetrically over the entire face of the core, are really
connected to form distinct groups which overlap each other. These
windings form the two or three circuits in the motor. When al-
ternating electro-motive forces are applied to these circuits, currents
will flow which set up magnetic fields in the motor. These alter-
nating fields in turn generate electro-motive forces in the windings.
Part of the current flowing in the windings represents energy ex-
pended usefully, or in heating, and part serves merely as magnetiz-
ing current. The latter, like the magnetizing current of a direct-
current machine, is dependent upon the dimensions of the mag-
netic circuit and upon the magnetic density in the various parts.
Even when the motor is running with no load the magnetizing cur-
rent is required.
THE POLYPHASE MOTOR 3
The second part of the motor, generally the rotating part,
receives no current from the supply circuit. The magnetic fields
set up by the first set of windings pass through the second windings,
and, tinder certain conditions, generate electro-motive forces in
them. If the second windings are arranged to form closed circuits,
currents will flow in them. These currents are entirely separate
from those of the supoly circuits.
SPEED AND SLIP
When running, the motor has a maximum speed that is ap-
proximately equal to the alternations of the supply circuit divided
by the number of motor poles in each circuit. This is the no-load
speed. As the motor is loaded, the speed falls off almost in pro-
portion to the load. The drop in speed is sometimes called the
FIG.2— DIAGRAM OF TWO-PHASE ALTERNATING-CURRENT GEN-
ERATOR. ROTATING-FIELD TYPE.
"slip." This is usually expressed in percent of the maximum
speed. If, for instance, a motor has a maximum speed of 1000
revolutions and drops fifty revolutions below this at full load,
it has then a slip of five percent.
TORQUE AND ARMATURE CURRENT
With this type of motor, a drop in speed is necessary for de-
veloping torque. A fairly simple illustration of this action may be
obtained by considering the operating of an alternating current
generator tinder certain conditions. We will take a type of alter-
nator having a stationary armature and a rotatable field magnet,
which can be driven at various speeds. Leads are carried out from
the armature to adjustable resistances. To avoid complexity, the
armature circuits and the resistances are considered as non-induc-
tive. The field coils are excited by direct current. Fig. 2 shows
this arrangement.
4 ELECTRICAL ENGINEERING PAPERS
When the field is rotated at a certain speed, with the field coils
charged, there is an alternating electro-motive force set up in the
armature winding. When the armature circuit is closed through
a resistance a current will flow and the armature will develop
power. The power developed by the armature is slightly less
than the power expended on the field shaft, which is proportional
to the product of the speed and the turning or driving effort — i. e ,
torque on the shaft. Consequently, at a given speed, a driving
effort is required at the field shaft, corresponding to the power de-
veloped by the armature If the armature current is increased or
decreased, the power developed is increased or decreased also, and
the driving effort will vary in proportion.
Let the field now be rotated at one-half the above speed. The
armature electro-motive force becomes what it was before Re-
ducing the resistance in the armature circuit also to one-half, the
same current as before will flow. The power developed by the
armature is now one-half and the speed of the field is one-half, con-
sequently, the driving effort or torque is the same as before. Re-
ducing the speed further, and decreasing the resistance in the ar-
mature circuit in proportion, to keep the armature current con-
stant, we find the driving effort on the field remains constant.
Finally, if we reduce the speed so much that the external armature
resistance is all cut out, and the armature is short circuited on itself
with the same current as before, the same driving effort is still
required.
The field is now rotating very slowly, and the alternations in
the armature are very low, being just sufficient to generate the
electro-motive force required to drive the armature current against
the resistance of the windings. Any further reduction in speed
will diminish the armature electro-motive force, and hence the
armature current must fall, the power developed be dimmivshed
and the driving effort also fall in proportion. An increase in
speed will increase the armature current, and thus increase the
driving effort required.
If but one armature circuit is closed, the power developed will
pulsate as the armature current varies, from zero to a maximum
value, and the driving effort will also vary, But if the armature
has two or more circuits having different phase relations, it may
develop power continuously and the driving effort will then be
continuous.
THE POLYPHASE MOTOR 5
ILLUSTRATION OF "SLIP"
The armature has been considered as stationary and develop-
ing power while a certain driving effort was applied to the field.
According to the well known law that any force is met by an op-
posing force, the armature must have a certain resisting effort.
The armature really tends to rotate with the field, and the resist-
ing effort is exerted to prevent this.
Assume the armature to be arranged for rotation, but locked,
in the above operations. Release the armature, attach a brake,
and adjust for a torque equal to the resisting effort of the armature.
The armature just remains stationary. Speed up the field, and the
armature will speed up also, keeping a certain number of revolu-
tions behind the field. This difference in speed is that required
for generating the electro-motive force necessary for sending the
current through the armature. The alternations in the arma-
ture will remain constant for a given armature current, indepen-
dent of the speed at which the armature is running.
If the brake be tightened, the armature must drive more cur-
rent through its windings to develop the required effort, the
armature alternations must hence increase, and the armature will
therefore lag behind its field more than before, or the "slip" is
increased. If the brake be loosened, the armature will* run
nearer the speed of the field. If the field be driven at a constant
speed and the brake be released, the armature will run at practic-
ally the same speed as the field.
If the winding consist of but one closed circuit, the torque
developed by the armature varies periodically, and that developed
by the brake will vary also, but to a less extent, as it is steadied
by the inertia of the rotating armature. But with two or more
circuits having different phase relations, arranged for constant
power developed in the armature windings, the torque developed
is also constant at all times. Consequently, for constant torque
at the brake, there should be two or more phases in the armature
windings.
DIFFERENCE BETWEEN ILLUSTRATION AND ACTUAL CASE
This explanation of the development of torque in the short-
circuited armature is merely an attempt to illustrate certain of the
actions in the polyphase motor armature by a comparison with the
operations of other apparatus, that is, in general, much better
understood. We cannot infer, from the above illustration, that an
alternating-current generator would run as a motor tinder" the
ELECTRICAL ENGINEERING PAPERS
assumed conditions, for, in the above operations, mechanical
power is supplied to the field shaft, and mechanical power is de-
livered by the rotating armature to the brake. There is no true
electro-motor action; that is, there is no transformation of elec-
trical power supplied to mechanical power developed.
No I
Circuit 1 at Maximum
Current
Circuit 2 at Zero Current
Circuit 1 Decreasing
Current
Circuit 2 with Increasing Current
Circuit l at Zero
Current
Circuit 2 at Maximum Current
No 4
Circuit 1 Increasing m
Reverse Direction
Circuit 2 Decreasing
HP'S
Circuit 1 at Maximum In
Reverse Direction
Circuit 2 at Zero
Circuit 1 Decreasing
Circuit 2 Increasing in Reverse
Direction
PIG 3— DIAGRAM SHOWING PRODUCTION OF ROTATING MAGNETIC
FIELD BY TWO-PHASE CURRENTS
The action of the short-circuited armature of the above gen-
erator and that of the polyphase motor are very similar in regard
to drop in speed for developing torque But in the polyphase
motor, instead of the mechanically rotated field magnet, there is
a stationary core provided with two or more windings which cany
currents having different phase relation. These windings are
placed progressively around the core, either overlapping or on
separate poles. When the currents flow in the windings, resultant
magnetic poles or fields are formed, which are progressively shift-
ing around the axis of the motor. The closed or short-circuited
armature, rotating in this field, develops torque by dropping in
THE POLYPHASE MOTOR 7
speed, in the same way that It developed torque with mechanically
rotated field magnets. But electrical power, instead of mechanical,
is now supplied to produce the shifting of rotating field, and the
conversion from electrical power supplied to the field windings, to
mechanical power developed by the armature shaft is a trans-
former action which does not appear in the above illustration.
ROTATING MAGNETIC FIELD ELECTRICALLY PRODUCED
Fig. 3 shows diagrammatically a progressively shifting field,
with two overlapping windings arranged for two-phase currents.
Coils 1-1, etc., form one circuit, while coils 2-2, etc., form the other.
Starting with the instant when the current in 1 is at its maximum
value, the magnetizing force of this set of coils must be at its maxi-
mum. The current and magnetizing force of circuit 2 are at zero
value. Four poles or magnetic fields, alternating N-S-N-S around
the core, are formed directly over coils 1. As the current in one
begins to decrease, that in 2 rises. We then have the combined
magnetizing forces of the two overlapping windings. These two
magnetizing forces act together at some points and oppose at
others. The resultant magnetic field shifts to one side of the
former position. As the current in 1 gradually falls to zero and
2 rises to its maximum value the magnetic field shifts around until
it is directly over coils 2. If the current in 1 should next increase
in the same direction as before, while 2 diminished, the magnetic
poles would shift back again to their former position. But the
current in 1, after reaching zero value, rises in the opposite direc-
tion, while that in 2 falls. This shifts the resultant poles forward
instead of backward, and they gradually shift ahead until they
are again directly over coils 1. But the "N" poles have shifted
around until they now occupy the former position of the "s"
poles. Thus, with the current in 1 passing from a maximum in
one direction to a maximum in the opposite, the poles have shifted
forward the width of one polar space. Current in 2 next rises in a
reversed direction and the poles shift forward until, when the cur-
rent in 2 is a maximum, they are over coils 2.
In the diagrams, Nos. 1, 2, 3, etc , show the positions of the
shifting field under certain conditions of current in the two circuits.
In No. 2, the position shown is an arbitrary one, for it depends upon
the relative values of the currents in the two circuits. With the
two currents equal, the position of the line N-N would be half-way
between coils 1 and 2.
8 ELECTRICAL ENGINEERING PAPERS
These diagrams show that the magnetic field due to two-phase
currents in properly arranged windings shifts progressively around
the axis, just as if the field were rotated mechanically.
SPEED-TORQUE CURVE
In polyphase motors, the part that resembles the field in the
above description and which receives the current from the line, is
usually called the primary, on account of its electrical resemblance
to the primary of a transformer. The equivalent of the armature
in the preceding description is called the secondary. If the alter-
nations of the supply circuit are constant, the reversals of the cur-
rents in the field or primary will occur at a uniform rate and the
magnetic field will shift around its center at a definite speed, de-
pending upon the rate of alternation of the supply circuit and the
number of poles in each circuit of the motor. If the armature or
secondary rotates at the same speed as the field shifts, there will be
no reversals or alternations in its magnetism, and there will be no
currents and consequently, no torque. If a load is thrown on, the
speed will drop and the resultant alternations in the secondary
will generate electro-motive forces which will drive currents
through the windings, and thus develop torque. The speed will
continue to fall, and the secondary electro-motive forces will con-
tinue to increase until a torque sufficient for the load is developed.
TORQUE
PIG. 4— SPEED TORQUE OF POLYPHASE MOTOR
Increasing the load on the motor, the speed should fall and the
torque increase until zero speed is reached. The speed-torque
curve would then be of the form shown in Pig. 4, curve "A." But
the shape of this curve is modified to a great extent in actual
motors by certain effects which cannot be entirely eliminated.
PRIMARY RESISTANCE REDUCES MAGNETIZATION AT HEAVY LOADS
In the case of the revolving field, the magnetization was sup-
posed to remain constant under different conditions. But in the
motor primary, the magnetism of the primary is not constant
under all conditions and it does not all pass through the secondary
THE POLYPHASE MOTOR 9
circuits. y The primary windings necessarily have some resistance,
and a certain electro-motive force is required to drive the primary
current through the windings. With a constant applied electro-
motive force, the primary counter-electro-motive force will dimin-
ish as the drop in primary resistance increases, and the magnetic
field required will diminish also. Consequently, to develop the
required secondary electro-motive force for driving the secondary
current through the windings the speed must drop more than
shown by curve "A" in Pig 4. This gives a speed-torque curve
as shown by curve "B," in Fig. 4. Instead of being a straight line
it is somewhat curved.
MAGNETIC LEAKAGE LIMITS MAXIMUM TORQUE
But there is a still more important effect in the motor. The
primary and secondary currents, and their consequent magnetizing
forces, are opposed to each other. The result is that part of the pri-
mary magnetism threads across between the primary and second-
ary windings without passing into the secondary. Thus, the
electro-motive force of the secondary is reduced, or, for a required
secondary electro-motive force, the secondary alternations must be
increased. This means a further drop in speed.
The secondary currents also tend to form local magnetic fields
around their own coils. These local fields are alternating and set up
electro-motive forces in the secondary circuits. In consequence,
the electro-motive forces generated by the magnetism from the
primary have to drive currents, not only against the resistance of
the secondary windings, but also against these local electro-motive
forces. This necessitates a further drop in speed for the required
torque. These local electro-motive forces depend upon the
secondary alternations and, therefore, vary with the drop in speed,
and are greatest at zero speed. This introduces a very complicated
condition in the secondary circuits. These magnetic fields which
thread around only the primary or secondary windings are called
the magnetic leakages, or stray fields, or the magnetic dispersion.
If the magnetic leakage is relatively large, that is, twenty to
twenty-five percent of the total induction, and the secondary re-
sistance is low, the speed-torque curve will have the peculiar shape
shown in Fig. 5, This curve shows the torque increasing as the
speed falls, until a certain maximum is reached. Beyond this
point the torque diminishes with further drop in speed. If the
motor is loaded to the maximum torque, a slight increase in load
causes a further drop in speed, the torque diminishes and the motor
10
ELECTRICAL ENGINEERING PAPERS
stops. As a consequence, the normal rating of the motor must be
considerably below this "pulling-out point.7' The margin neces-
sary depends upon the nature of the load to be carried.
TORQUE
PIG. 5— SPEED TORQUE OP POLYPHASE MOTOR, SHOWING EFFECT OP
MAGNETIC LEAKAGE
The starting torque, speed regulation, etc., of the polyphase
motor depend upon the form of the speed-torque curves. The
different methods of varying the form of these curves will be
considered next.
EFFECT OF SECONDARY RESISTANCE ON SPEED CURVE
As the secondary electro-motive force is that necessary to
drive the secondary currents through the windings, it follows that
the electro-motive force required must depend upon the resistance
of these windings. A larger resistance means a larger electro-
motive force for the required current, and, therefore, a greater
number of secondary alternations, or a greater drop in speed.
The torque being held constant, any variation of the secondary
resistance requires a proportionate variation in the slip. If the
slip with a given torque is 10 percent, for instance, it will be 20
percent with double the secondary resistance, or 50 percent with
five times the resistance. This is true only with the primary con-
ditions of constant applied electro-motive force and constant alter-
nations. The secondary resistance may be in the windings them-
selves, or may be external to the windings but part of the secondary
body, or it may be entirely separate from the machine and con-
nected to the windings by the proper leads.
Fig. 6 shows the speed-torque curves for a motor with different
resistances in the secondary circuit. In curve " A" the secondary
resistance is small In curve "B" the secondary resistance is
doubled. The maximttm torque remains the same but the slip
for any given torque is doubled. This motor starts much better
THE POLYPHASE MOTOR
11
than that in curve "A." In curve "c," the resistance is again
doubled and the slip is also doubled. The starting torque is in-
creased but the slip is rather large at the rated torque, "x." In
curve "D," the slip is again doubled. In this case the torque is
high at start and falls rapidly as the speed increases. In curve
"E," the maximum torque is not yet reached at zero speed. Con-
tinuing these curves below the zero-speed line, that is, running the
motor in the reverse direction, we get the general form of these
different speed-torque curves. They are all of the same general
shape, and all have the same maximum torque.
PIG. 6— SPEED-TORQUE AND CURRENT-TORQUE CURVES OF POLYPHASE
MOTOR WITH SECONDARIES OF DIFFERENT RESISTANCE
12
ELECTRICAL ENGINEERING PAPERS
So far as torque is concerned, curve * ' D ' ' is the best for starting.
But for running, curve "A" gives the least drop in speed. Con-
sequently, if a resistance is introduced at start that will give the
speed-torque curve "D," it should be cut out or short-circuited for
the running condition. This is one method of operation that has
been much used.
CURRENT CURVE
In determining the best starting condition, the current sup-
plied to the primary must be considered in connection with the
speed-torque curves. This current is plotted with the series of
speed-torque curves shown in Fig, 6. Referring to this figure,
curve "A*' represents the primary amperes in terms of torque.
Starting at the point "B," of no-load, or zero torque, it rises at
a nearly uniform rate until maximum torque is approached; that
is, below the point of maximum torque the current is nearly pro-
portional to the torque, but beyond this point the current continues
to increase and reaches a maximum at the torque represented by
zero speed. At reversed speed this current is further increased.
This one current curve holds true for all the speed-torque curves,
1 A
A,
'c," "D," etc.
P f
Fig. 7— STARTING CONDITIONS WITH VARIABLE SECONDARY RESISTANCE
THE POLYPHASE MOTOR 13
Comparing the different curves, we see that "A" takes the
most current at start, and gives low torque; "B" takes less cur-
rent than " A, ' ' and gives more torque ; " c " takes less current than
"B"; "D" takes less current than "c" and gives the maximum
torque at start ; " E " takes less current than " D, ' ' and develops less
torque; but the current and torque are very nearly in proportion
over the whole range. From this we see that a speed-torque curve
of the form of ' ' D " or ' ' E " is decidedly better for starting than ' ' A ' '
or "B." But for running at less than the maximum torque there
is no advantage, so far as current is concerned, in curve "D" over
curve "A," and the speed regulation of "D" is poor.
STARTING WITH VARIABLE SECONDARY RESISTANCE
Fig. 7 represents the conditions of speed, current, etc., when
a variable secondary resistance is used at start. The motor
starts at "F" on curve "D," and takes a current "G." The cur-
rent falls to "H," while the speed rises to "i," which corresponds
to the normal torque "T" at which the motor will run under the
given conditions as long as the motor operates on curve "D."
The speed will remain at this point. If the resistance in the
secondary is now short-circuited, and the load thus shifted to the
speed-torque curve "A," the torque at the speed "i," increases to
"K" on torque curve "A." The current corresponding to this is
"L." As the torque at "K" is greater than the normal torque
"T," the motor speed will increase until normal torque is reached
again at "M," while the current falls from "L" to "H."
At the moment of cutting out the secondary resistance there
was a very considerable increase in the current. By arranging the
starting resistance in the secondary so that the motor will start at
some curve intermediate between "A" and "D" and thus take
more current at start, somewhat less would be required upon
switching to curve "A." If curve "E" is used for starting, and if
the torque required when speeding up is greater than that at the
point where curves "A" and "E" cross each other, the motor will
not pull up because in switching from "E " to "A," the torque falls,
and the motor will stop. The current on switching over increases
to " N," and then rises to " o " as the motor stops. In this case the
resistance that gives curve "E" is too great, and a lower starting
resistance is required; with a large number of resistance steps
small variation of current is secured.
By making several steps of the secondary resistance, so that
it may be cut out gradually, the motor may be made to pass
14
ELECTRICAL ENGINEERING PAPERS
through a series of speed-torque curves with much smaller varia-
tions of current than shown in the preceding diagrams. This
method has been used to some extent, but requires collector rings
or a complicated switching arrangement in connection with the
motor secondary.
PIG, 8— STARTING CONDITIONS WITH FIVE SECONDARY RESISTANCE STEPS,
Fig. 8 shows the conditions for starting and speeding up with
five speed-torque curves. The motor starts on curve " E " at "p."
The speed rises to "G." The motor is then switched to curve
"D," the torque rising to "H." The speed then rises to "i." In
this way the motor passes successively from "D" to "c," "B" and
"A," until the full speed is reached. The currents at no time reach
very high values.
Plotting the current in, terms of speed, the use of a large
number of steps is shown to better advantage. This is shown in
Pigs. 9 and 10. Fig. 9 shows the same starting conditions as Fig.
7 with curves "D" and "A." The current starts at "A" and falls
to "B." The resistance is then short-circuited and the current
rises to " c " and then falls to "D," which is the same as "B," If
THE POLYPHASE MOTOR
15
"A" had been higher at start, "c" would have been lowered
slightly. But as the time required for passing from "A" to "B"
is generally greater than that from "c" to "D," "c" may be
higher than "A." If the motor is not required to develop such a
SPEED
FIG. 9— CURRENT SPEED CURVE FOR MOTOR STARTING, AS IN FIG. 7.
large torque when pulling up, then " c " may be lowered while "A "
is left unchanged.
In Fig 10, the currents in terms of speed are shown for five
steps with the five speed-torque curves of Fig 8. The starting
current "A" is low, and none of the currents, when switching from
SPEED
FIG. 10— CURRENT SPEED CURVE FOR MOTOR STARTING, AS IN FIG. 8
DOTTED LINES SHOW SAME CURVE AS FIG 9
one curve to another, is large. The dotted lines show the cor-
responding currents for two steps, as in Fig. 9.
MOTORS FOR VARIABLE SPEED WORK
For variable speed work, such as cranes, elevators, etc., the
series of curves in Fig. 6 shows one method of regulating the speed
By varying the secondary resistance over a wide range, any speed
from zero to maximum may be obtained with any torque up to
10
ELECTRICAL ENGINEERING PAPERS
the maximum. This requires the use of collector rings and ad-
justable rheostats. The vanations in speed are obtained by
wasting energy in resistance. For a given torque the same power
is expended on the motor whether the speed is zero or maximum.
To obtain a certain torque at start requires as much power as
when running at full speed.
An analysis of the motor shows another way in which the speed-
torque curves may be varied. In Fig. 6, all the curves show a
certain maximum torque which is the same in all cases; but this
is with the condition of constant primary electro-motive force.
By varying the electro-motive force applied to the primary we
may obtain a quite different series of curves. Taking, for ex-
TORQUE
PIG 11— SPEED-TORQUE AND CURRENT-TORQUE CURVES FOR POLYPHASE
MOTOR WITH DIFFERENT VOLTAGES APPLIED
ample, a speed-torque curve of the form "A" in Fig. 11, and
applying a higher electro-motive force to the primary, a curve is
obtained of the same shape as "A," but with a much higher point
of maximum torque. Lowering the applied electro-motive force,
the maximum torque is lowered. The torques at any given speed
are raised or lowered in the same proportion as the maxima are
varied. At any given speed the torques are proportional to the
square of the electro-motive forces applied. This relation holds
good for any form of the torque curve, whether of the shape "A,"
"D," or "B," shown in Fig. 6.
The current curves are also shown in Fig. 11. They all have
the same general shape, but have different maximum values, these
being proportional to the electro-motive forces applied. The
speed-torque curve "A" in Fig. 11 has the same shape as "D" in
Fig. 6, which gave too great a drop in speed. In Fig. 11, curve
"B," which is the same form as "A," gives less speed drop for the
same torque. Curve "c" gives less than "B," and has fairly
good speed regulation from no-load up to normal torque "T." But
THE POLYPHASE MOTOR 17
this result is obtained at the expense of increased induction in the
iron, and large no-load or magnetizing current due to the higher
electro-motive force, is required. If it is possible to obtain a
speed-torque curve like "c" in Fig 11 with the normal electro-
motive force applied, we can obtain good speed regulation from
no-load up to the rated torque, and shall be able to start the motor
with the maximum torque it can develop. Then, by lowering the
applied electro-motive force, the same form of speed-torque curve
will be retained, but the starting torque and starting current may
be lowered to any extent desired.
VARIABLE SPEED BY VARYING VOLTAGE
Returning to Fig 5, it was stated that the peculiar shape of
this curve, with the torque falling rapidly after reaching a maxi-
mum value, was due mainly to magnetic leakage between the
primary and secondary windings. But if the motor is so pro-
portioned that the leakage is very small compared with the useful
field, the speed-torque curve takes a quite different shape. The
maximum torque is increased directly as the magnetic leakage is
diminished. This is shown in Fig. 12. Here "A" is similar in
shape to curve "A" in Fig. 6; "B" represents the speed-torque
curve with the magnetic leakage reduced one-half; "c" repre-
sents it with about one-half the leakage of "B," and "D" with one-
half that of "c."
In comparing Figs 6 and 12, it may be noted that "A" in one
is the same form as "A" in the other, although drawn to a dif-
ferent scale. In Fig. 12, "B " has the same shape as in Fig. 6, but
has a different maximum value. The same is true of curves "c"
and "D" in the two figures. By lowering the applied electro-
motive forces for curves "D," " c " and " B " of Fig. 12, so that the
maximum torques are equal to that of "A," as shown by the dot-
ted curves, we get practically the same curves as in Fig. 6.
Curve "D," in Fig. 12, gives as good running conditions as
curve "A" in Fig. 6, having about the same drop in speed at the
normal torque "T." We have, then, in "D" a curve which starts
at the point of maximum torque, and which also has a small drop
in speed at the normal load. The objection to this curve is that
the starting current and starting torque, although in the proper
proportion to each other, are both much greater than is necessary
or desirable. By reducing the applied electro-motive force at
start, however, lower torques and currents are obtainable. In this
way we may combine good starting and running conditions in one
18
ELECTRICAL ENGINEERING PAPERS
motor without the use of starting resistances, and with a secondary
that has no resistance except that of its own windings. Fig. 13
shows the speed-torque and current curves of such a motor with
the applied electro-motive force varied over a considerable range.
PIG. 12— SPEED-TORQUE CURVES OP POLYPHASE MOTOR SHOWING EF-
FECT OF MAGNETIC LEAKAGE. DOTTED LINES SHOW CURVES b, c, d
WITH REDUCED VOLTAGE
If but one electro-motive force is desired for starting and
speeding up, and the motor is then to be transferred to the work-
ing electro-motive force, the speed-torque curves should preferably
TORQUE
FIG 13— SPEED-TORQUE AND CURRENT-TORQUE CURVES FOR POLY-
PHASE MOTOR WITH ELECTRO-MOTIVE FORCE VARIED OVER A
WIDE RANGE.
have the shape shown in Fig. 14. The motor starts with the de-
sired torque at reduced e. m. 1, and comes up to almost rated
speed before switching over. This is suitable for constant speed
work. In Fig. 14 are shown both the starting and running speed-
torque curves, and the currents both in the motor and the line.
The line currents are smaller than the motor currents in the ratio
of reduction of electro-motive force in the regulating transformers.
THE POLYPHASE MOTOR
19
SPEED-TORQUE CURVES FOR VARIABLE SPEED WORK
For cranes, elevators, and variable speed work in general,
curves of the form shown in Fig. 15 are preferable. The line cur-
sents are also shown in this figure. This series of speed-torque
TORQUE
FIG. 14— B EST SHAPE OP SPEED-TORQUE CURVE FOR MOTOR STARTED
AND SPEEDED UP WITH A SINGLE REDUCED VOLTAGE, BEFORE
BEING TRANSFERRED TO WORKING VOLTAGE.
curves shows that a wide range of speed may be obtained by proper
variations of the applied electro-motive force. The line currents
"A," "B," etc., practically overlap each other. This means that
the line current required with this method of control is very nearly
TOHQUE
FIG. IS— SPEED-TORQUE AND CURRENT-TORQUE CURVES OF MOTOR FOR
CRANES, ELEVATORS AND SIMILAR VARIABLE SPEED WORK WITH VOL
TAGE CONTROL. CURVES a, b, c, d, er f, ARE SPEED-TORQUE CURVES WITH
VARIABLE VOLTAGE. CURVES A, B, C, D, E, F. SHOW CORRESPONDING
LINE CURRENT.
constant for any given torque, independent of the speed. The
same is true of the method of control by varying the secondary
resistance. It may be noted that the current for starting, as on
curve "c," for instance, is slightly greater than that required for
running at the same torque on "B" or "A." This is due to the
speed-torque curve being somewhat curved at its outer end. With
a somewhat higher resistance of the secondary the curves are more
20 ELECTRICAL ENGINEERING PAPERS
nearly straight, but the drop in speed is somewhat increased on the
speed torque for any given electro-motive force In practice, a
compromise is made between the best possible starting condition
and a condition of less speed drop.
A comparison of the methods of control by varying the
secondary resistance and by varying the applied electro-motive
force shows that they give practically the same results in regard
to starting, speed regulation, etc. But a motor that has been
designed for regulation by varying its secondary resistance, will
generally give very poor results when an attempt is made to
operate it by the variable electro-motive force method A motor
must be especially proportioned for small magnetic leakage when
this method of control is to be used. The proportions and the ar-
rangement of the parts are such as may class this as a practically
distinct type of motor.
EFFICIENCY AND POWER FACTOR
We come now to the other characteristics of the polyphase
motor, the most important of which are the efficiency and the
power factor. The importance of efficiency is generally apprec-
iated, but the question of power factor in most cases appears to be
not thoroughly understood or else is entirely overlooked.
The efficiency of a polyphase motor is the ratio of the power
developed to the true power expended, as in any other kind of a
machine. The power developed may be obtained from the speed-
torque curves. If the torques are given for one foot radius, and
the speed in revolutions per minute, then the product of any given
torque by the corresponding speed, divided by 5,250, will give the
power developed in horse-power; or torque multiplied by speed,
divided by seven, gives the power developed in watts. This
power, plus the iron, copper and friction losses, gives the true
power expended.
The power factor is the ratio of the true power to the apparent
power expected. This apparent power is proportional to the
products of the primary currents by the electro-motive forces.
If there is magnetizing current, and if the motor has magnetic
leakage, the primary currents are not in phase with their electro-
motive forces and their products represent an apparent power
which is greater than the true energy expended. The current of
each circuit can be considered as made up of two currents, one of
which is in phase with the applied electro-motive force, represent-
ing true energy, and the other at right angles to the electro-motive
force, representing no energy. The right-angled component is" the
THE POLYPHASE MOTOR 21
one that has an injurious effect on the regulation of the generator,
transmission lines, transformers, etc.
The size of this component, compared with the useful current,
may be shown by a table :
Useful 90 Degree
Power Factor Total Current Component Component
100 100 100 0.
99 100 99 14.2
98 100 98 19.9
95 100 95 31.2
90 100 90 43 6
80 100 80 60.0
70 100 70 71 4
60 100 60 80 0
50 100 50 86 6
40 100 40 91 6
EFFECTS OF LAGGING CURRENT
At 90 percent power factor, for instance, the current that is
lagging 90 degrees behind the electro-motive force is equal to 43 6
percent of the total current flowing. This lagging current reacts
on the generator, affecting the regulation. In an alternating-
current generator, a 90-degree lagging current in the armature
coils directly opposes the field magnetization. When delivering
a current at 90 percent power factor there is over 43 percent of this
current opposing the field, and at 80 percent power factor 60 percent
is opposing the field. If the armature ampere turns are normally
20 percent as great as the field ampere turns, then a load of 80
percent power factor will give an opposing magnetization in the
armature of about 60 percent of the total armature ampere turns,
or about 12 percent of the total field, and the armature electro-
motive force will be lowered approximately that percent more than
with a load of 100 percent power factor.
The inductive effects of the lagging current in the transmission
circuits and transformers are much more serious than those from
a current that is in phase with the electro-motive force. The
generator, transformers, lines and motors also have increased
losses, due to the large current required when the power factor is
low. An 80 percent power factor in a system means losses due to
heating of conductors more than 50 percent greater than those
with 100 percent power factor. These figures indicate the im-
portance of good power factors in an alternating-current system.
22 ELECTRICAL ENGINEERING PAPERS
MAGNETIZING CURRENT AND MAGNETIC LEAKAGE DETERMINE POWER FACTOR
The lagging, or 90-degree component, of the current in a
motor depends upon the amount of the no-load, or magnetizing,
current and upon the magnetic leakage Let this lagging com-
ponent be expressed in percent of the total current Also express
the magnetizing current in percent of the total current, and the
total magnetic leakage in percent of the total primary induction.
Then the sum of the percents of magnetizing current and magnetic
leakage represents very closely the percent of the lagging com-
ponent of the primary current. If, for example, the magnetizing
current is 30 percent and the leakage is 14 percent, the resulting
lagging component is about 44 percent. From the preceding
table, this indicates about 90 percent power factor A low leakage
and a high magnetizing current may give the same power factor at
full load as a high leakage and low magnetizing current; but at
half load, the percent magnetizing current is practically doubled,
while the percent magnetic leakage is halved. Hence, a low mag-
netizing current is of great importance in maintaining a high power
factor If a high value of power factor over a wide range is de-
sired, then both the leakage and the magnetizing current must be
low.
VOLTAGE CONTROL VERSUS RIIEOSTATIC CONTROL
The method of control by varying the primary electro-motive
force is dependent upon the fact that the motor has a low magnetic
leakage. By using certain proportions and arrangements of the
windings on the primary and secondary, the magnetizing current
may be made comparatively low. Thus both conditions for good
power factor are obtained.
With the method of control by varying the secondary resist-
ance, good power factors may be obtained. But the form of
secondary winding required when variable resistances are used
tends to reduce both the power factor and the maximum torque.
BEST FORM OF SECONDARY WINDING
An elaborate series of tests was made to determine the best
type of winding for the secondary of a polyphase motor. First,
two circuits were arranged to give secondary phases ninety degrees
apart. The starting, running and maximum load conditions were
determined. Then a three-phase secondary winding was used.
This gave a higher pulling-out torque and better power factor than
the two-phase Pour phases were tried and were bottcr than
three; and six were better than four. Then twelve phases were
THE POLYPHASE MOTOR 23
tried, with a gain over six in maximum torque, but not much gain
in efficiency. The power factor was somewhat improved. Finally
the winding was completely short-circuited on itself, all coils being
connected to a common ring. This gave a further increase in -
maximum torque and power factor over the preceding arrange-
ment, but there was very little gain in efficiency. The same
primary was used in all these tests. Each time the number of
secondary circuits was increased the power factor was somewhat
improved. This was due to the fact that the secondary currents
were able to so distribute themselves that the local electro-motive
forces in the coils, due to leakage, were diminished; or, the mag-
netic leakage may be considered to have been diminished. This
would necessarily give higher pulling-out torques and higher-power
factors.
BEST FORM OF PRIMARY WINDINGS
Very complete tests were also made to determine the best
form of primary winding, and a certain method of distribution of
the coils was found to diminish the primary magnetic leakage very
considerably. This somewhat increased the maximum torque
and the power factor. Utilizing the arrangements of the primary
and the secondary windings just described, and otherwise pro-
portioning for small magnetic leakage, a motor may be obtained
that has a comparatively low total induction, and yet has a mag-
netic leakage of but a few percent. The low induction allows a
small magnetizing current and comparatively low iron losses. The
low leakage gives a high pulling-out torque, and thus allows a good
speed regulation, and also good starting conditions, by varying the
applied electro-motive force.
TYPE C MOTORS
Motors that are adapted for operation under the conditions of
variable applied electro-motive forces with constant secondary
resistance must have the special forms of speed-torque curves
shown in Figs. 12 to 15, and they may therefore be considered as
forming a distinct type. This type has received the name Type C.
The Type C motor is always characterized by low magnetic leak-
age and consequent high pulling-out torque. The secondary has
no adjustable resistance and all regulation is obtained by varying
the adjustable electro-motive force. The secondary is made the
rotating part, on account of the type of winding used, which con-
sists of copper bars placed in tunnels or slots in the core and
bolted to two end rings. There are no bands, and the question of
24 ELECTRICAL ENGINEERING PAPERS
insulation is of very little importance for the maximum secondary
electro-motive force does not exceed three volts in a 500 horse-
power motor and is less with smaller sizes.
ADVANTAGES OF TYPE C MOTORS
This type of motor possesses several distinct advantages over
other forms of polyphase motors. The method of control, by
varying the electro-motive forces applied to the motor, leads to
WESTINGHOUSE
75 H.P.TYPE C MOTOR
3000 ALTS.. POLES
FIG. 16— PERFORMANCE CURVE OF 75 H, P. TYPE C MOTOR
two very important advantages, one of which is mechanical and
the other electrical. With this method of control there are no
regulating appliances on the motor and, in consequence, it may be
of the simplest possible form. The electrical advantage is that
the motor may be started and controlled from a distance. Thus
it may be placed entirely out of reach of the operator. On travel-
ing cranes, for example, this is of special advantage, for in this case
only the primary wires need be run from the operator's cage to the
motor. If there are several motors on the crane, there may be one
wire common to all the motors and but two additional wires per
THE POLYPHASE MOTOR
25
motor are required. Thus for the three motors, a minimum of
eleven trolley wires may be used.
If the variable electro-motive forces are obtained from trans-
formers, the switches for operating several motors may be wired
to one set of transformers and the motors may be started and
regulated independently. For traveling cranes, only one set of
transformers is used for the hoisting, bridge and traveling motors,
WESTINGHOUSE
400 H.P.TYPEC MOTOR
3COO ALTS., 8 POLES
3000
4000 5000 COCO 7000 8000 0000 10000 11000 1200^
Pqunds Torque at i Foot Radius.
FIG. 17— PERFORMANCE CURVES OF 400 H P. TYPE C MOTOR
and this set may supply currents at different electro-motive forces
to all the motors at the same time. A further advantage possessed
by this motor lies in the high pulling-out torque. If a heavy over-
load, or a load having great inertia, is suddenly thrown on a motor
that has a speed-torque curve like "A" in Fig. 6, the point of
maximum torque may be passed for an instant, and the motor will
be stopped unless the load is quickly removed. A Type C motor
in this case would have its speed pulled down for a moment, but
this reduction in speed gives an increased torque, thus enabling
the motor to carry the overload.
26 ELECTRICAL ENGINEERING PAPERS
If the electro-motive force of the system Is suddenly lowered,
the pulling-out torque of the motors is lowered very materially.
A reduction of twenty percent in the electro-motive force will
lower the pulling-out torque to about two-thirds of its former value.
Even with a temporary drop in the electro-motive force, such as
would be caused by a momentary short-circuit on the lines, this
may be sufficient to stop the motor But a motor that has a
pulling-out point several times as large as its normal running
torque is very rarely in danger of being shut down from this cause.
This type of motor has a starting torque from two to four times
as large as the full-load running torque and it is thus able to start
any kind of load. In practice the starting torque is adjusted to the
load to be started by applying a suitable electro-motive force, as
will be explained below.
A last, but not least, advantage of the Type C motor is its
adaptability for large sizes. The larger the motor of this type, the
lower in proportion can be its magnetic leakage and its magnet-
izing current. In consequence, the power factors are very high.
The efficiencies are also very good over a wide range of load The
curves for a seventy-five horse-power, six-pole, 3,000-altcrnntion
motor are given in Fig. 16, also the curves for a 400-horsc-power,
2,300-volt, eight-pole, 3,000-alternation motor in Pig. 17 The
power factors of these motors are good examples of what can be
obtained on large motors of this type.
SPEED VARIATION WITH POLYPHASE MOTORS
There are six methods of varying the speed of polyphase
motors, but some of them are applicable only in special cases.
These methods are:
(1) — Varying the number of poles.
(2) — Varying the alternations applied.
(3) — Motors in tandem, or series-parallel.
(4) — Secondary run as single-phase.
(5) — Varying the resistance of the secondary.
(6) — Varying the electro-motive force of the primary,
with constant secondary resistance.
Some of these methods are efficient, while some are very in-
efficient if the speed is to be varied over a wide range.
VARYING THE NUMBER OF POLES
The first method, varying the number of poles, is efficient to a
certain extent, but is limited in the number of combinations of
THE POLYPHASE MOTOR 27
poles obtainable. But if combined with some of the other methods
it may be made fairly effective over a wide range. It consists in
varying the arrangement of the primary coils in such a way that
the number of resulting poles is varied. This may be accom-
plished by having two or more separate windings on the primary;
or one winding may be used, it being rearranged for different speed.
With this method of varying the speed, a secondary of the "cage "
type is the only practical one. With a "grouped" or "polar"
winding on the secondary, this would need rearranging for the dif-
ferent speeds, just as in the case of the primary. But the cage
winding, being short-circuited on itself at all points, is adapted to
any number of poles. In general, this method of regulation will
allow for only two speeds without great complications, and the
ratio of the two speeds is preferably two to one, although three to
one may be obtained. The simplest arrangement of winding con-
sists of two separate primary windings; one for one number of
poles, and the second for the other. In combination with a var-
iable primary electro-motive force, the speed-torque curves being
of such shape that this method may be used, the variable-pole
method of regulation may be made fairly efficient over a wide
range of speed. But the two windings considerably increase the
size of the motor, while the one-winding arrangements are rather
complicated. Consequently, we may consider that this method
of speed variation will be used only in special cases.
VARYING THE NUMBER OF ALTERNATIONS
The second method, variable alternations, is theoretically the
ideal method; but it is practically limited to a few special applica-
tions, for we have as yet no commercial alternation transformer.
In a few cases, where but one motor is operated, the generator
speed may be varied. If the generator is driven by a water-wheel,
its speed may be varied over a wide range, and the motor speed will
also vary. If the generator field be held at practically constant
strength, then the motor speed may be varied from zero to a
maximum at constant torque with a practically constant current.
This is a convenient method of operating a motor at a distance
from the generator. The speed of the motor may be completely
controlled by an attendant at the generating station.
Fig. 18 shows the speed-torque and other curves of a motor
when operated at 7200, 3600, 1800 and 720 alternations per minute,
or^at 100, SO, 25 and 10 percent of the normal alternations. The
speed-torque curves, corresponding to the above alternations are,
28
ELECTRICAL ENGINEERING PAPERS
"a," "b," "c" and "d." The current curves are "A," "&>" "c"
and "D." This figure shows that for the rated torque "T," the
current is practically constant for all speeds, but the electro-motive
force varies with the alternations. Consequently, the apparent
power supplied, represented by the product of the current by
FIG 18— PERFORMANCE CURVES OF POLYPHASE MOTOR WITH DIF-
FERENT ALTERNATIONS AND ELECTRO-MOTIVE FORCES.
electro-motive force, varies with the speed of the motor, and is
practically proportionate to the power developed
MOTORS IN TANDEM OR SERIES-PARALLEL
The third method is to run motors in tandem or series-parallel-
In this arrangement, the secondary of one motor is wound with a
grouped or polar winding to give approximately the same electro-
motive force and number of phases as the primary. The secondary-
is connected to the primary of a second motor, The secondary
of the second motor may be closed on itself, with or without a
resistance, or may be connected to the primary of a third motor,
etc. The arrangement with two motors is shown in Fig. 19. At
start, motor No. 1 receives the full number of alternations on its
primary, and its secondary -delivers the same number to the prim-
ary of motor No. 2. Both motors will start. As motor No, 1
speeds up, its secondary alternations fall. At about one-half
speed, its secondary alternations are about one-half its primary,
and motor No. 2 receives one-half the alternations of motor No. 1 ;
it also tends to run at half-speed, Therefore, if both motors ate
THE POLYPHASE MOTOR 29
coupled to the same load, this half speed is a position where the
two motors tend to operate together. By connecting both
primaries across the line, both motors will be run at full speed.
Thus, with two motors, two working speeds may be obtained.
This method always requires at least two motors. Its application
is limited to a few special cases.
SECONDARY WITH ONLY A SINGLE CIRCUIT CLOSED
The fourth method — the secondary run with a single circuit
closed — will give a half-speed, and with two or more circuits
closed, will give full speed. But the power factor at the half -speed
is very low, and the efficiency is not nearly so good as when run
at full speed. This may have a few special applications. Fig 20
shows this arrangement.
FIG. 19— DIAGRAMMATIC ARRANGEMENT OF THE TWO POLYPHASE
MOTORS CONNECTED IN TANDEM OR SERIES PARALLEL
VARYING THE RESISTANCE OF THE SECONDARY
The fifth arrangement is by varying the resistance in the
secondary. This method was considered before when the speed-
torque characteristics were shown. This will not give constant
speed except with constant load, as the speed-torque curve, with a
relatively large resistance is a falling curve. At heavy torques, the
motor will run at very low speeds, while with light loads it will run
at almost full speed. The speed regulation will be similar to that
of a direct-current shunt motor with a resistance in circuit with the
armature. To hold constant speed with variable load, this resis-
tance requires continual adjustment.
VARYING PRIMARY VOLTAGE
The sixth method — that in which the primary electro motive
force is varied while the secondary resistance is held constant —
gives the same results as the fifth method, as the speed-torque
curves axe similar. To hold a constant low speed, the electro-
motive force must be varied continually if the load is changing.
30 ELECTRICAL ENGINEERING PAPERS
Like the fifth method, it is not efficient at low speeds, as the reduc-
tion in speed is obtained by means of a corresponding loss of energy
in the secondary circuits. /
PIG 20— POLYPHASE MOTOR WITH ONLY ONE SECONDARY CURRENT
CLOSED
For crane work, hoisting, etc , where it is necessary to run at
reduced speed for but a portion of the time, either of the methods
five or six is satisfactory, but method five requires the use of a vari-
able secondary resistance, and there must be a set of secondary
leads earned out to a rheostat if the speed changes are to be
gradual. This introduces complication, especially on a crane where
several motors are to be controlled In this case there must be
trolley wires for both the primary and the secondary circuits of each
motor. But by method six, the control is effected in the primary
circuit and only primary trolley wires are needed, and these may
be controlled from one pair of transformers, as explained before.
The sixth method is therefore the simplest and most practical one
to use for hoisting, etc , and will be found to present many advan-
tages for all classes of work, whether speed regulation is important
or not.
METHOD OP VARYING PRIMARY ELECTRO-MOTIVE FORCE
There are several methods of varying the electro-motive force
applied for starting and varying the speed on the Type C motor.
These may be classified under three headings :
(1) — Varying the electro-motive force from the genera-
tor.
(2) — Varying the electro-motive force by transformers.
(3) — Varying the motor connections.
VARYING ELECTRO-MOTIVE FORCE FROM THE GENERATOR
A variable electro-motive force may be obtained from the
generator in several ways. The generator may be run at low
THE POLYPHASE MOTOR
31
speed, with the field charged. This gives lower electro-motive
force and lower alternations at the same time. This is adapted
only to places where all the motors are to be started at once.
The generator may be run at normal speed and its field charge
lowered. This gives the normal alternations with lower electro-
motive force. This is practicable only where all the motors are to
be started at once.
A third method is to so arrange the generator windings that
two or more electro-motive forces for each phase may be obtained.
A lower electro-motive force may be used at start, and a higher
for running.
The different arrangements of the generator windings for this
purpose are as follows:
If the armature has but one winding closed on itself, like a
direct-current machine, two or three phases may be taken off. For
two phases four leads are used, Pig. 21 illustrates this Between
MOTOR
STARTING WITH
REDUCED VOLTAGE
RUNNING WITH
FULL VOLTAGE
FIG. 21— CONNECTIONS FOR TWO-PHASE MOTORS STARTING ON SIDE
CIRCUITS.
1-3 and 2-4 is the maximum electro-motive force, and between 1-2,
2-3, 3-4 and 4-1 there is 0.7 the electro-motive force of 1-3. The
electro-motive force 1-2 is at quarter phase to that of 4-1 and 2-3,
and the electro-motive force 3-4 is at quarter phase to that of 2-3
and 4-1. Therefore, across any two adjacent side circuits we have
quarter phase circuits of 0.7 the electro-motive force of the main
circuit. A motor may thus be started on any adjacent side cir-
cuit and then switched to the main circuit. This method is wdl
adapted for local plants where the generator electro-motive force
is 200 or 400 volts. If there are many motors to be started, and
32 ELECTRICAL ENGINEERING PAPERS
the starts are numerous, it is advisable to wire the starting switches
so that the various motors are started on different side circuits.
If the generator winding is of the " open coil" type, a similar
arrangement may be obtained for two phases The two windings
may be connected to the middle point, thus giving side circuits of
0.7 electro-motive force This is shown in Fig 22.
PIG 22— WINDINGS OP ' 'OPEN COIL," TWO-PHASE GENERATORS CONNECTED
TOGETHER AT MIDDLE POINT TO ALLOW STARTING OP MOTORS FROM
"SIDE CIRCUITS'1,
Three-phase connections do not allow any convenient com-
binations with the generator winding. A fourth wire may be run,
however, which will give about 0 58 electro-motive force for
starting.
FIG 23— CONNECTIONS OF TRANSFORMERS ON TWO-PHASE CIRCUITS
TO GIVE .7 AND .5 NORMAL VOLTAGE FOR STARTING MOTORS
VARIABLE ELECTRO-MOTIVE FORCE FROM TRANSFORMERS
The method of varying the electro-motive force by means of
transformers admits of many different combinations. Several of
the simpler forms will be given.
(1) The transformers may be so connected that two or more
electro-motive forces may be obtained.
For two-phase circuits, the secondaries may be connected
together at the centre, as shown in Fig. 23 This gives two main
circuits, and four side circuits of lower electro-motive force If an
extra wire be carried out from the point 5, then 1-5, 2-5, will form
a two-phase combination for 0 5 voltage, while 1-2, 2-3 form a
THE POLYPHASE MOTOR 3S
two-phase combination for 0.7 voltage, and 1-3 and 2-4 give full
voltage.
Another method is to connect the secondaries at one side of
the centre, as shown in Fig. 24. Then 3-5 and 4-5 give one electro-
motive force; 1-5 and 2-5 give a higher electro-motive force, and
1-3 and 2-4 give full electro-motive force.
l
S
PIG. 24-CONNECTIONS OP SECONDARIES OP TRANSFORMERS ON TWO-PHASE
CIRCUIT AT A POINT ONE SIDE OP THE CENTER, TO OBTAIN LOWER
ELECTRO-MOTIVE FORCES FOR STARTING MOTORS.
These combinations are useful in certain cases, but are not as
general in their application as the following method .
(2) Auto-transformers with loops brought out for lower
electro-motive forces.
FIG. 25— DIAGRAMMATIC ARRANGEMENT OF AUTO-TRANSFORMERS AND
CONTROLLERS FOR REGULATING SPEED OF TWO-PHASE MOTOR BY VAR-
IANCES OF VOLTAGE.
In this method, no special combinations of the lines, lowering
transformers or generators are made, but, in connection with each
motor, a small pair of auto, or one-coil transformers, is used for
34 ELECTRICAL ENGINEERING PAPERS
auto-transformers are made larger From these auto- transformers
several loops or connections are brought out. For regulating the
speed these are connected to the contact plates or dials of a con-
troller, as shown in Figs 25 and 26 But for starting purposes only,
when but one loop from each transformer is used, a pair of switches
8
vvwvwT
vwvwd
FIG 26— DIAGRAMMATIC ARRANGEMENT OP AUTO-TRANSFORMERS AND
CONTROLLER FOR REGULATING SPEED OF THREE-PHASE MOTOR BY
VARYING THE VOLTAGE
are used in connection with the transformers. With the switches
open, the motor is disconnected. Throwing one direction starts
the motor at reduced voltage and brings it up to almost full speed.
The switches are then thrown over to full electro-motive force.
Two small transformers in a case with one four- jaw, throw-
over switch, form what is called an "auto-starter." This is
readily arranged for either two or three-phase circuits and motors.
This makes a most flexible arrangement for starting, as the motor
may be put at any location, and the auto-starter may be put in the
most convenient position. It also loads all the line wires equally
at start, and each motor and starter really form a unit separate
from all the others One pair of transformers may be connected
to several sets of switches and thus be used for starting several
motors.
Where motors are close to reducing transformers, the second-
aries of the transformers may have loops brought out, to which
one or more switches are connected. The primaries of the trans-
formers may have loops connected to proper switches, and the
number of primary turns in the circuit may be varied instead of
the secondary. This is applicable when the transformers supply
only one motor, or when several motors are started at the same
time. A regulator with secondary movable with respect to the
primary may be used Regulators of this type vary the electro-
THE POLYPHASE MOTOR 35
motive forces without any "make" or "break" devices, and con-
sequently have no sparking tendency. But they are in general
too complicated and costly to compete with the transformer with
loops.
VARYING THE MOTOR CONNECTIONS
This is not a method for changing the electro-motive force
applied, but for varying the number of turns in series with a given
electro-motive force, and the effect is the same as varying the ap-
plied electro-motive force. This method is rather limited in its
application owing to the complication involved. The simplest
case for two-phase motors is a series-parallel combination of the
windings of each phase. This is equivalent to using 0.5 electro-
motive force at start. For three-phase motors, series-parallel may
be used or the winding may be thrown from the star system of
connection at start to the delta system for running. This is equiv-
alent to using about 0.6 electro-motive force for start. But, as
the star connection is preferred for the running condition, this com-
bination is not advisable.
CHOKE COILS OR RESISTANCE IN THE PRIMARY
There is a fourth method of regulation which may be men-
tioned, but which is not advisable in general practice. This is the
use of choke coils or resistance in the primary circuits of the motor,
to reduce the electro-motive force. These really give varying
electro-motive forces. With choke coils, the power factor at start
is lowered, with correspondingly bad effect on the generator and
system. With ohmic resistance in the primary circuit, the reduc-
tion of electro-motive force is accompanied by a consumption of
energy in the primary circuit which in no way represents torque.
WASHINGTON, BALTIMORE & ANNAPOLIS SINGLE-
PHASE RAILWAY
FOREWORD — This paper was presented before the American Insti-
tute of Electrical Engineers, September, 1902. It was the very
first information given out for publication regarding the single-
phase alternating-current railway system as developed and in-
stalled so extensively since that time.
Before the publication of this paper, it was generally as-
sumed that the difficulties in the commutation of alternating
current were so great that only motors of relatively small capac-
ity could be built. Following its publication, many, of the larger
companies throughout the world began work on such motors
and produced operating railway equipments with more or less
success — (ED.)
THE Washington, Baltimore and Annapolis Railway is a new
high-speed electric line extending from the suburbs of Wash-
ington to Baltimore, a distance of about 31 miles, with a branch
from Annapolis Junction to Annapolis, a distance of about 15
miles. The overhead trolley will be used, and schedule speeds
of over 40 miles per hour are to be attained. This road is to be
the scene of the first commercial operation of an entirely new
system of electric traction.
The special feature of this system is the use of single-phase alter-
nating current in generators, transmission lines, trolley car equip-
ment and motors It constitutes a wide departure from present
types of railway apparatus. The standard D. c. railway equipment
possesses several characteristics which fit it especially for railway
service. These characteristics have been of sufficient importance to
overbalance many defects in the system. In fact, a far greater
ambunt of effort and engineering skill has been required for over-
coming or neutralizing the defects, than for developing the good
features possessed by the system. By far the most important
characteristic possessed by the D. c. system is found in the type
of motor used on the car. The D. c. railway motor is in all cases
a series-wound machine. The series motor is normally a variable
field machine and it is this feature which has adapted the motor
especially to railway service. Shunt-wound motors have been
tried and abandoned. All manner of combinations of shunt,
37
3S ELECTRICAL ENGINEERING PAPERS
series and separate excitation have been devised and found want-
ing, and in many casesthe real cause of failure was not recognized
by those responsible for the various combinations. They all
missed to a greater or less extent the variable-field feature of
the straight series motor. It is true that a variable field can be
obtained with shunt or separate excitation, but not without con-
trolling or regulating devices, and the variation is not inherently
automatic, as in the series motor Polyphase and single-phase
induction motors do not possess the variable field feature at all,
as they are essentially constant-field machines They are
equivalent to direct current shunt or separately excited motors
with constant field strength, which have been unable to compete
successfully with the series motor The variable field of the
series motor makes it automatically adjustable for load and
speed conditions. It also enables the series motor to develop
large torques without proportionately increased currents The
automatically varying field is accompanied by corresponding
variations in the counter e.m f. of the armature, until the speed
can adjust itself to the new field conditions This feature is of
great assistance in reducing current fluctuations, with a small
number of steps in the regulating rheostat Any increase in
current, as resistance is cut out, is accompanied by a momentary
increase in the counter e.rn f , thus limiting the current increase
to a less value than in the case of constant field motor
Next to the type of motor, the greatest advantage possessed by
the D, c. system lies in the use of a single current or circuit, thus
permitting the use of one trolley wire The advantages of the
single trolley are so well-known that it is unnecessary to discuss
them For third rail construction, the use of single current is of
even greater importance than in the case of overhead trolley
It is seen, therefore, that it is not to the direct current that
credit should be given for the great success of the present railway
system, but to the series type of motor and the fact that up to
the present time no suitable single-phase A c. motor has been
presented
Some of the undesirable features of the D c railway system
should also be considered. The speed control is inefficient. A
nominally constant voltage is supplied to the car, and speed con-
trol is obtained by applying variable voltage at the motor ter-
minals This variation is produced by the use of resistance in
series with the motors, with a loss proportional to the voltage
taken up by the resistance By means of the series-parallel
SINGLE-PHASE RAILWAY 39
arrangement, the equivalent of two voltages is obtainable at the
motor terminals without the use of resistance. Therefore, with
•series-parallel control, there are two efficient speeds with any
given torque, and with multiple control there is but one efficient
speed with a given torque All other speeds are obtained
through rheostatic loss, and the greater the reduction from
either of the two speeds, series or parallel, the lower will be the
efficiency of the equipment. At start, the rheostatic losses' are
always relatively large, as practically all the voltage of the line
is taken up in the rheostat For heavy railroad service, where
operation for long periods at other than full and half speeds may
be necessary, the rheostatic loss will be a very serious matter.
The controlling devices themselves are also a source of trouble.
An extraordinary amount of time and skill has been expended'
on the perfection of this apparatus The difficulties increase
with the power to be handled The controller is a part of the
equipment which is subjected to much more than ordinary
mechanical wear and tear, and it can go wrong at any one of
many points. The larger the equipment to be controlled, the
more places are to be found in the controller which can give
trouble. The best that can be said of the railway controller is
that it is a necessarv evil.
Another limitation of the D. c. system is the trolley voltage
Five hundred volts is common at the car and 650 volts is very
unusual. By far the larger number of the railway equipments
in service to-day are unsuited for operation at 600 volts, and 700
volts in normal operation would be unsafe for practically all
The maximum permissible trolley voltage is dependent upon
inherent limitations in the design of motors and controllers
The disadvantages of low voltage appear in the extra cost of cop-
per and in the difficulty of collecting current. In heavy railroad
work the current to be handled becomes enormous at usual
voltages. A 2400 h p. electric locomotive, for example, will
require between 3000 and 4000 amperes at normal rated power
and probably 6000 to 8000 amperes at times. With the
overhead trolley these currents are too heavy to be collected in
the ordinary manner, and it is a serious problem with any form
of trolley or third rail system which can be used. It is evident
that for heavy service, comparable with that of large steam rail-
ways, a much higher voltage than used in our present D. c. sys-
tem is essential, and the use of higher voltage is destined to come,
provided it is not attended by complications which more than
40 ELECTRICAL ENGINEERING PAPERS
overbalance the benefits obtained. A £111 1 her disadvantage of
the D. c. system is the destructive action known as electrolysis
This may not be of great importance in interurban lines, chiefly
because there is nothing to be injured by it. In city work its
dangers are well-known, and very expensive constructions are
now used to eliminate or minimize its effects.
From the above statements it is evident that an A c railway
system, to equal the D. c., should possess the two principal
features of the D. c. system, viz A single supply circuit and the
variable field motor, and to be an improvement upon the D. c.
system, the A. c. should avoid some of the more important dis-
advantages incident to the present D. c. railway apparatus,
The system must, therefore, be single- phase. The importance
of using single-phase for railway work is well known The diffi-
culties and complications of the trolley construction are such
that several A. c. systems have been planned on the basis of
single-phase supplied to the car, with converting apparatus on
the car to transform to direct current, in order that the standard
type of railway motors may be used Such plans are attempts
to obtain the two most valuable features of the present D c.
system. The polyphase railway system, used on a few European
roads, employs three currents, and therefore does not meet the
above requirement. The motor for the A c railway service
should have the variable speed characteristics of the series D. c.
motor. The polyphase motor is not suitable, as it is essentially
a constant field machine, and rloes not possess any true variable
speed characteristics. Therefore it lacks both of the good fea-
tures of the D. c. railway system. A new type of motor must,
therefore be furnished, as none of the alternating current motors
in commercial use is adapted for the speed and torque require-
ments of first-class railway service. Assuming that such a
motor is obtainable for operation on a single-phase circuit, the
next step to consider is whether the use of alternating instead
of direct current on the car, will allow some of the disadvan-
tageous features of the D. c. system to be avoided. The D. c.
limits of voltage are at once removed, as transformers can be
used for changing from any desired trolley voltage to any con-
venient motor voltage. Electrolysis troubles practically disap-
pear. As transformers can be used, variations in supply voltage
are easily obtainable. As the motor is assumed to have the
characteristics of the direct-current series motor, speed control
without rheostatic loss is practicable when voltage control is
SINGLE-PHA SR RAILWAY 41
obtained. This combination, therefore, allows the motor to
operate at relatively good efficiency at any speed within the
range of voltage obtained If the voltage be varied over
a sufficiently wide range, the speed range may be car-
ried from the maximum desired down to zero, and there-
fore, down to starting conditions. With such an arrange-
ment no rheostat need be used under any conditions, and the
lower the speed at which the motor is operated, the less the power
required from the line. The least power is required at start, as
the motor is doing no work and there is no rheostatic loss. The
losses at start are only these in the motor and transforming
apparatus, which are less than when running at full speed with
an equal torque. Such a system, therefore, permits maximum
economy in power consumed by motor and control. This
economy in control is not possible with the polyphase railway
motor, as this motor is the equivalent of the D. c. shunt motor,
with which the rheostatic loss is even greater than with the
series motor.
The use of alternating current on the car allows voltage control
to be obtained in several ways. In one method a transformer
is wound with a large number of leads carried to a dial or con-
troller drum. The Stillwell regulator is a well-known example
of this type of voltage control. This method of regulation is
suitable for small equipments with moderate currents to be
handled. The controller will be subject to some sparking, as in
the case of D. c. apparatus, and therefore becomes less satisfactory
as the car equipment is increased in capacity. Another method
of control available with alternating current is entirely non-
sparking, there being no make-and-break contacts. This con-
troller is the so-called " induction regulator," which is a trans-
former with the primary and secondary windings on separate
cores. The voltage in the secondary winding is varied by shift-
ing its angular position in relation to the primary. With this
type of voltage controller, very large currents can be handled,
and it is especially suitable for heavy equipments,such as loco-
motives It is thus seen that there is o^ie method of control,
available with alternating current, which avoids the troubles
inherent to the D. c. controller. The induction regulator is
primarily a transformer, and all wear and tear is confined to the
supports which carry the rotor. Therefore the objectionable
controller of the standard D. c. system can be eliminated, pro-
vided a suitable A. c. motor can be obtained. This ideal type
42 ELECTRICAL ENGINEERING PAPERS
of controller is not applicable to the polyphase railway motor, in
which speed control can be obtained only through rhcostatic
loss. The polyphase control system is even more complicated
than the D. c , as there must be a rheostat for each motor, and
two or three circuits in each rheostat It is thus apparent that
by the use of single-phase alternating current with an A. c
motor having the characteristics of the D c. series motor, the
best features of the D c. system can* be obtained, and at the
same time many of its disadvantages can be avoided.
This portion of the problem therefore resolves itself into the
construction of a single-phase motor having the characteristics
of the D c. series motor There are several types of single phase
A. c. motors which have the series characteristics. One
type is similar in general construction to a D. c. motor, but with
its magnetic circuit laminated throughout, and with such pro-
portions that it can successfully commutate alternating current
Such a motor is a plain series motor, and can be operated on
either alternating or direct current and will have the same torque
characteristics in either case. Another type of motor is similar
in general construction to the above, but the circuits are ar-
ranged in a different manner. The field is connected directly
across the supply circuit, with proper control appliances in series
with it. The armature is short-circuited on itself across the
brushes, and the brushes are set at an angle of approximately
45° from the ordinary neutral point The first of these two types
of motors is the one best adapted for operation in large units.
This is the type of motor which is to be used on the Washington
Baltimore and Annapolis Railway. Several motors have been
built and tested with very satisfactory results, both on the test-
ing stand and under a car. The results were so favorable that
the system was proposed to the Cleveland Engineering Company,
representing the Washington, Baltimore and Annapolis Railway,
and after investigation by their engineers, the system was
adopted. A description of the apparatus to be used on this road
will illustrate the system to good advantage.
Single-phase alternating current will bo suppled to the car at
a frequency of 16 J cycles per second, or 2T000 alternations per
minute. The current from the overhead trolley wire is normally
fed in by one trolley at approximately 1,000 volts. Within
the limits of the District of Columbia two trolleys are employed,
as by Act of Congress the use of rails as conductors is prohibited
in this District, presumably on account of electrolysis. In this
SINGLE-PHA SE RAIL WA Y 43
case the trouble, of course, will not exist, but the contracting
company has been unable to obtain permission for the grounded
circuit.
The alternating current to the car is carried through a main
switch or circuit breaker on the car, to an auto-transformer
connected between the trolley and the return circuit. At
approximately 300 volts from the ground terminal, a lead is
brought out from the auto-transformer and passes through the
regulator to one terminal of the motors. For starting and con-
trolling the speed, an induction regulator is used with its second-
ary winding in series with the motors. This secondary circuit
of the regulator can be made either to add to, or substract from
the transformer voltage, thus raising or lowering the voltage
VVWVW^ 1
<v*wvw> — I j
rOflO
Fio. 1 — a Auto-Transformer b. Induction Regulator c Reversing Switch, d Fta d
of Motors e Armature of Motors f Equalizing Transformer.
supplied to the motors. The regulator therefore does double
duty. The controller for D. c. motors merely lowers the voltage
supplied to the motors but cannot raise it, but an A. c. regulator
can be connected for an intermediate voltage, and can either
raise or lower the motor voltage. In this way the regulator can
be made relatively small, as it handles only the variable element
of the voltage and the maximum voltage in the secondary wind-
ing is but half of the total variation required.
In the equipments in question, the range of voltage at the
motor is to be varied from approximately 200 volts up to 400
volts or slightly higher. The transformer on the car will supply
315 volts, and the secondary circuit of the regulator will be
44 ELECTRICAL ENGINEERING PAPERS
wound to generate slightly more than 100 volts when turned to
the position of its maximum voltage. This voltage of the regu-
lator is about one-fourth of that of the motors at full voltage.
The regulator can consequently be made relatively small, in
comparison with the motor capacity of the equipment. It has
been found unnecessary to use much lower than 200 volts in this
installation, as this voltage allows a comparatively low running
speed, and approximately 200 volts will be necessary to start
with the required torque The greater part of this voltage 5s
required to overcoine the e m 1. of self-induction in the motor
windings, which is dependent upon the current through the
motor and is independent of the speed ot the armature.
There will be four motors of 100 h.p. on each car The full
rated voltage of each motor is approximately 220 volts The
motors are arranged in two pairs, each consisting of two arma-
tures in series, and two fields in series, and the two pairs are
connected in parallel The motors are connected permanently
in this manner As voltage control is used, there is no necessity
for series parallel operation, as with D. c. motors. To ensure
equal voltage to the armatures in scries, a balancing or equalizing
action is obtained by the use of a small auto-transformer con-
nected permanently across the two armatures in series with its
middle point connected between them. The fields are arranged
m two pairs, with two fields in scries and two pairs in multiple
This parallels the fields independently of the armatures, which
was formerly the practice with D c motors. It was a defective
arrangement with such motors, as equal currents in the field did
not ensure equal field strengths in the motors, and the armatures
connected in parallel would be operating m fields of unequal
strength, with unequal armature currents as a direct result.
With alternating currents in the fields, the case is different
The voltage across the fields is dependent upon the field strengths,
and the current supplied to the fields naturally divides itself for
equal magnetic strengths The chief advantage m paralleling
the fields and armatures independently is, that one reversing
switch may serve for the four motors and one balancing trans-
former may be used across the two pairs of armatures The
usual D. c. arrangement of armatures m series with their own
fields can be used, with a greater number of switches and con-
nections.
The general arrangement of the auto-transformer, regulator,
jnotors, etc , is shown in Fig. 1
SINGLE-PHA SE RAILWAY 45
The induction regulator or controller, resembles an induction
motor in general appearance and construction. The primary
winding is placed on the rotor, and the secondary or low voltage
winding on the stator. The rotor also has a second winding
which is permanently short-circuited on itself. This function
of this short-circuited winding is to neutralize the self-induction
of the secondary winding as it passes from the magnetic influ-
ence of the primary. The regulator is wound for two poles, and
therefore is operated through 180° for producing the full range
of variation of voltage for the motors. One end of the primary
winding of the regulator is connected to the trolley, and the
other to a point between the regulator and the motors. It thus
receives a variable voltage as the controller is rotated. There
are several advantages in this arrangement of the primary in
this particular case. First, the regulator is worked at a higher
induction at start, and at lower induction when running, the
running position being used in these equipments for much longer
periods than required for starting Second, when the motors
are operating at full voltage the current in the primary of the
•regulator passes through the motors but not through the auto-
transformer or the secondary of the regulator. This allows con-
siderable reduction m the size of auto-transformer and regulator.
The motors on the car are all of the straight series type. The
armature and fields being connected in series, the entire current
of the field passes through the armature as in ordinary series
D c. motors. The motor has eight poles, and the speed is
approximately 700 revolutions at 220 volts. The general con-
struction is similar to that of a D. c. motor, but the field core is
laminated throughout, this being necessary on account of the
alternating magnetic field. There are eight field-coils wound
with copper strap, and all connected permanently in parallel.
The parallel arrangement of field-coils assists in the equalizing
of the field strength in the different poles, due to the balancing
action of alternating circuits in parallel. This arrangement is
not really necessary, but it possesses some advantages and
therefore has been used. With equal magnetic strength in the
poles, the magnetic pull is equalized even with the armature out
of center. The armature is similar in general construction to
that of a D. c. motor. The fundamental difficulty in the opera-
tion of a commutator type of motor, on single-phase alternating
current lies in the sparking at the brushes. The working current
passing through the motor should be practically no more difficult
46 ELECTRICAL ENGINEERING PAPERS
to commutate than an equal direct current, and it is not this cur-
rent which gives trouble. The real source of trouble is found in
a local or secondary current set up in any coil, the two ends of
which are momentarily short-circuited by a brush. This coil
encloses the alternating magnetic field, and thus becomes a
secondary circuit of which the field-coil forms the primary. In
40 ,10 00 TO 80 UO 300 110 130 130 140
HORSE POWER
PIG 2 — 'Westinghouse Alternating Current Railway Motor No, 91, — Single-Phase — 220
Volts.
the motors of the Washington, Baltimore and Annapolis Rail-
way, this commutation difficulty has been overcome by so con-
structing the motor that the secondary -or short-circuit current in
the armature coil is small, and the commutating conditions so
SINGLE-PHASE RAILWA Y 47
perfect that the combined working and secondary currents can
be commutated without sparking. This condition being ob-
tained, the motor operates like a D. c, machine and will give no
more trouble at the commutator than ordinary D. c. railway
motors. Experience covering a considerable period in the opera-
tion of motors of 100 h.p. capacity indicates that no trouble need
be feared at the commutator.
An extended series of tests were made at the Westinghouse
shops at East Pittsburg, both in the testing room and under a
car. Fig. 2 shows curves of the speed, torque, efficiency and
power factor plotted from data from brake tests.
It should be noted that »the efficiency is good, being very
nearly equal to that of high-class D. c. motors. The power
factor, as shown in these curves, is highest at light loads and
decreases with the load. This is due to the fact that the power
developed increases approximately in proportion to the current,
while the wattless component of the input increases practically
as the square of the current. The curve indicates that the
average power factor should be very good. The calculations
for the W. B. and A. Railway show that the average power factor
of the motors will be approximately 96 per cent.
The average efficiency of these equipments will be much
higher during starting and acceleration than that of correspond-
ing D. c. equipments, and rheostatic losses are avoided. When
running at normal full speed, however, the efficiency will be
slightly less than with D. c. This is due to the fact that the A. c.
motor efficiency is slightly lower than the D. c., and in addition
there are small losses in the transformer and the regulator. The
A. c equipments are somewhat heavier than the D. c., thus re-
quiring some extra power, both in accelerating and at full speed.
Therefore, for infrequent stops the D. c, car equipment is more
efficient than the A. c., but for frequent stops the A. c. shows the
better efficiency. Tests on the East Pittsburg track verified
this conclusion. But the better efficiency of the D. c. equipment
with infrequent stops is offset with the A. c. by decreased loss in
the trolley wire, by reason of the higher voltage used, and the
elimination of the rotary converter losses.. The resultant effi-
ciency for the system will therefore be equal to or better than
that of the D. c.
In the W. B. and A Railway contract the guarantee given by
the Westinghouse Electric and Mfg. Co. states that the efficiency
of the system shall be equal to that of the D. c. system with rotary
converter substations
48 ELECTRICAL ENGINEERING PAPERS
There is one loss in the A. c. system which is relatively much
higher than in the o c This is the loss in the rail return. Tests
have shown that at 2,000 alternations this is three to four times
as great as with an equal direct current This would be a
Serious matter in cases where the D. c rail loss is high. But the
higher A. c trolley voltage reduces the current so much, that
the A. c. rail loss is practically the same as with direct current
at usual voltages In many city railways the D. c. rail loss is
made very low, not to lessen waste of power, but in order to
reduce electrolysis. In such cases the A. c. rail loss could be
higher than D. c , thus decreasing the cost of return conductors.
More frequent transformer substations, with copper feeders
connected to the rails at frequent intervals will enable the rail
loss to be reduced to any extent desired. As a frequency of
2,000 alternations per minute is used, the lighting of the cars and
the substations was at first considered to be a serious difficulty,
due to the very disagreeable winking of ordinary incandescent
lamps at this frequency. Two methods of overcoming the
winking were tried, both of which were successful. One method
was by the use of split phase. A two-phase induction motor
(was run on a single-phase 2,000 alternating circuit, and current
was taken from the unconnected primary circuit of the motor,
This current was, of course, at approximately 90° from the cur-
rent of the supply circuit. A two-phase circuit was thus obtained
on the car. Currents from the two phases wore put through
ordinary incandescent lamps, placed close together. The
resulting illumination a few feet distant from the lamps showed
about the same winking as is noticed with 3,000 alts. With two
filaments in one lamp the winking disappears entirely. A three-
phase arrangement would work in the same way.
A muoh simpler method was tried which worked equally well.
This consisted in the use of very low-voltage lamps. I^ow volt-
age at the lamp terminals allows the use of a thick filament with
considerable heat inertia. Tests were made on lamps of this
type at a frequency of 2,000 alts., and the light appeared to be as
steady as that from the ordinary high-frequency incandescent
lamp. The low voltage is not objectionable in this case, as a
number of lamps can be run in a series, as in ordinary street
railway practice, and any voltage desired can readily be obtained.
as alternating current is used on the car.
There will be an air compressor, driven by a series A. c. motor,
on each car, for supplying air to the brakes and for operating
SINGLE-PHASE RAILWAY 49
the driving mechanism of the controller. The details of this
mechanism are not near enough to completion to permit a de-
scription of it The method used will be one which readily
allows operation on the multiple-unit system.
The generating station contains some interesting electrical
features, but there is no great departure from usual A. c, prac-
tice. There will be three 1,500 k w. single-phase alternators.
These are 24-pole machines operating at 83 revolutions and
wound for 15,000 volts at the terminals. They are o,f the
rotating field type, with laminated magnetic circuits aftd field-
coils of strap on edge. The field-coils are held on the pole-tips
by copper supports, which serve also as dampers to assist in the
parallel running The armatures are of the usual slotted type.
The armature coils are placed in partially closed slots. There
are four coils per pole The proportions of these machines are
such that good inherent regulation is obtained without saturation
of the magnetic circuit. The rise in potential with non-inductive
load thrown off will be approximately 4 per cent. An alterna-
tive estimate was furnished for the generators proposing 20,000
volts instead of 15,000. The simplicity of the type of winding
used, and the low frequency, are both favorable for the use of
very high voltage on the generator. As 15,000 volts was con-
sidered amply high for the service, the engineers for the railway
considered it unadvisable to adopt a higher voltage.
There are to be two exciters, each of 100 k w. capacity at 250
revolutions The exciters are wound for 125 volts normal. The
armature of each exciter has, in addition to the commutator,
two collector rings, so that single-phase alternating current can
be delivered It is the intention to use the exciters as alter-
nators for .supplying current to the system for lighting when the
large generators are shut down at night. The main station
switchboard comprises three generator panels, one load panel,
and three feeder panels. High-tension oil-break switches are to
be provided, operated by means of controlling apparatus on the
panels. The switches, bus-bars and all high-tension apparatus
will be in brick compartments separate from the board. In
each generator circuit there are two non-automatic oil-break
switches in series; and on each feeder circuit there are two over-
load time-limit oil-break switches in series. The two oil-break
switches in series on the same circuit can be closed separately
and then opened to test the switches without closing the circuit.
With the switches in the closed position they are both operated"
50 ELECTRICAL ENGINEERING PAPERS
at the same time by the controller, to ensure opening of the cir-
cuit, and to put less strain on the switches, although either one
is capable of opening the load There will be nine transformer
substations distributed along the railway line. Each station
will contain two 250 k.w. oil-cooled lowering transformers,
supplying approximately 1 ,000 volts to the trolley system. The
transformers are used in each station so that in case of accident
to one transformer the station will not be entirely crippled. It
is the intention of the railway company to operate a n, c. road
already equipped with the direct-current system The present
D. c car equipments arc to be retained, but the current will be
supplied from a rotary converter substation fed from the main
system of the W B and A. Railway. As this system is single-
phase, it is necessary that single-phase rotarics be used in the
substations. There are to be two k.w. 550-volt rotary con-
verters. These are 4-pole, 500-rcvolution machines. The
general construction of these machines is very similar to that of
the Westmghouse polyphase rotary converters. The armature
resembles that of a polyphase rotary except in the number of
collector rings, and in certain details of the proportions made
necessary by reason of the use of single-phase. The commutat-
ing proportions are so perfect that any reactions due to the use
of single-phase will result in no injurious effect. The field con-
struction is similar to that of a polyphase rotary. . The lamin-
ated field-poles are provided with dampers of the " grid " or
11 cage " type, a form used at present in the Westinghouse poly-
phase rotary converters. This damper serves to prevent hunt-
ing, as in the polyphase machines, and also to damp out pulsa-
tions due to single-phase currents in the armature. The damper
acts to a certain extent as a second phase. Each rotary con-
verter is started and brought to synchronous speed by a small
series A. c. motor on the end of the shaft. The voltage at the
motor terminals can be adjusted either by loops from the lower-
ing transformer or by resistance in series with the motor, so that
true synchronous speed can be given to the rotary converter,
before throwing it on the A. c. line.
From the preceding description of this system and the appar-
atus used on it, some conclusions may be drawn as to the various
fields where it can be applied to advantage. It is evident that ?i
good field for it will be on intcrurban long-distance lines such as
the W B. and A, Railway. On such railways, high trolley
voltage and the absence of converter substations are very
important factors.
SINGLE-PHASE RAILWAY 51
For heavy railroading also, this system possesses many ideal
features.. It allows efficient operation of large equipments at
practically any speed and any torque, and also avoids the con-
troller troubles- which are ever present with large direct current
equipments. It. also permits the use of high trolley voltage,
thus reducing the current to be collected Tn this class of serv-
ice the .advantages of this A c system are so great that is it
possible that heavy railroading will prove to be the special field
for it.
For general city work, this system may not find a field for some
time to come, as the limitations m the present system are not so
great that there, will be any great necessity for making a change.
It is probable that at first this system will be applied to new
railways, or in changing over steam roads rather than in replac-
ing existing city equipments. One difficulty with which the
new system will have to contend, is due to the fact that the
A. c equipments cannot conveniently operate on existing city
lines, as is the present practice where interurban lines run into
the cities. It will be preferable for the A. c. system to have its
own lines throughout, unless very considerable complication is
permitted. When the A. c. system applied to interurban and
steam railway systems finally becomes of predominant import-
ance, it is probable that the existing D. c. railways will gradually
be changed to A. c. as a matter of convenience in tying the vari-
ous railway systems together
As was stated above, A. c equipments cannot conveniently be
operated on direct current lines. It does not follow that the
motor will not operate on direct current. On the contrary, the
motor is a first-class direct current machine, and if supplied with
suitable control apparatus and proper voltage it will operate
very well on the D. c. lines. This would require that the motors
be connected formally in series, as the voltage per motor is low.
A complete set of D. c. control apparatus would be needed when
the A. c. equipment is to be run on direct current, and con-
siderable switching apparatus would be necessary for disconnect-
ing all the A. c. control system and connecting in the D. c. The
complication of such a system may be sufficient to prevent its
use, at least for some time to come
In some cities, very strict laws are in force in regard to the
voltage variations in various parts of the track system. The
permissible variations are so small in some cases, that an enor-
mous amount of copper is used for return conductors; and in
52 ELECTRICAL ENGINEERING PAPERS
some cases special boosters are used in the return circuits to
avoid large differences of potential between the various parts
of the track system. The object in limiting the conditions in
this manner is to avoid troubles from electrolysis. The A. c.
system will, of course, remedy this.
For city work, it is probable that voltages of 500 or 600 would
be employed instead of 1,000 or higher. The transformers and
controllers can be designed to be readily changed from full to
half voltage, so that low voltage can be used on one part of the
line and high voltage on another As the car equipments of
such railways arc usually of small capacity, it is probable that
speed control will be obtained by means of a transformer with a
large number of leads carried out to a control drum, rather than
by means of the induction regulator, as the latter device is much
more expensive in small units. This is chiefly a question of cost,
and if the advantages of the induction regulator are found to
over-weigh the objection of high first cost, then it will be used
even on small equipments.
In the W. B. and A. Railway, the generators are wound for
single-phase, In the case of large power-stations with many
feeders, the generators may be wound for three-phase, with
single-phase circuits carried out to the transformer substation,
or three-phase transmission may be used, with the transformers
connected in such a -manner as will give a fairly well-balanced
three-phase load.
There are many arrangements and combinations of apparatus
made possible by the use of alternating current in the car equip-
ments, which have not been mentioned, as it is impracticable
to give a full description of all that can be done. But enough
has been presented to outline the apparatus and to indicate the
possibilities of this new system which is soon to see the test -of
commercial service.
SYNCHRONOUS MOTORS FOR REGULATION OF
POWER FACTOR AND LINE PRESSURE
FOREWORD— In 1890, the author discovered, during certain ex-
periments in the Westinghouse testing room, that a synchronous
motor could affect the power factor of the supply system, by
variations in^its field strength. Later, he proposed the use of
such a machine for regulating the pressure of a supply system
and for changing the relation between e.m.f. and current in
alternating-current systems. However, even as late as 1904,
when the paper was presented, the value of this method of
operation was but little appreciated.
This paper should be read from the viewpoint of the time
when it was written. Hand regulation was the ordinary prac-
tice. Consequently, alternators with inherently good regula-
tion, that is, which would give three to four times full load
current on sustained short circuit, were preferred, in order that
much hand regulation would not be needed. This paper was pre-
sented at a meeting of the American Institute of Electrical
Engineers in June, 1904. — (ED.)
IT is well known that the synchronous motor, running on an
alternating-current circuit, can have its armature current
varied by varying its field strength. A certain adjustment of field
strength will give a minimum armature current. Either stronger
or weaker fields will give increased current. These increased cur-
rents are to a great extent wattless. If the field is weaker than
the normal (or field for minimum armature current), the increased
armature current is leading with respect to the e.m.f. waves in the
motor and lagging with respect to the line e.m.f. For stronger than
the normal field, the current is to a great extent lagging and
tends to lessen the flux in the motor and the current is leading
with respect to the line e m f A synchronous motor therefore
has an inherent tendency to correct conditions set up by im-
proper adjustment of its field strength The correcting current
in the motor being drawn from the supply system has a correct-
ing effect on sucli system, tending to produce equalization between
generated pressures in the motor and the supply pressure. This
characteristic of the synchronous motor can readily be utilized
for two purposes; namely, for varying the amount of leading
or lagging current in a system for producing changes in the
power-factor of the system (including transmission line, trans-
formers, and generators), or a synchronous motor can be utilized
for pressure regulation in a system.
53
54 ELECTRICAL ENGINEERING PAPERS
As the synchronous motor can be made to impress a leading
current upon the system, and as the amount of this leading
current will depend upon the field adjustment of the synchronous
motor, it is evident that this property can be used for neutral-
izing the effects of lagging current due to other apparatus on
the system. The resultant leading or lagging current can be
varied and the power-factor controlled over a fairly wide range
depending upon the location of the synchronous motor or motors,
and upon the current capacity of the motor, etc.
As the wattless current in the motor is primarily a corrective
current, it is evident that for most effective purposes for ad-
justing power-factor on the system the corrective action of
this current on the motor should not be too great. When
used for such purpose the synchronous motor should therefore
be one which would give a comparatively large current if short-
circuited as a generator Also the motor should preferably be
one in which the magnetic circuit is not highly saturated, for
in the saturated machine the limits of adjustment in the field
strength are rather narrow.
As has been noted above, if the field strength bf the motor
be varied, a leading or lagging current can be made to flow in
its armature circuit, this current being one which tends to
adjust the pressure of the armature and that of the supply
system. It is evident that if the armature pressure is held con-
stant and the supply pressure varied, a leading or lagging
current would also flow. If for instance the line pressure were
dropped below that of the motor, then a lagging current would
flow in the motor tending to weaken its field, and a leading
current would flow in. the line, tending to raise the pressure, on
the line.1 If the line pressure should be higher than that of
the synchronous motor, then the current in the motor woftld
be leading, tending to raise its pressure; while it would be lag-
ging with respect to the line, tending to lower it§ pressure.
The resultant effect would be to equalize the pressures of the
line and motor, and there would thus be a teadency to regulate
the line pressure to a nioro nearly constant value, It is evident
that the less the synchronous motor is affectecL by the <correc-'
tive current and the more sensitive the line is Jo such corrective
action, the greater the tendency will be toward constant pres-
sure on the line It is therefore evident that the synchronous
motor Which gives the largest current on short circuit as n gen-
erator would be the one which gives the greatest corrective
action as regards pressure regulation of the system.
POWER-FA CTOR REG ULA TION 55
For such regulation, the synchronous motor which gives a com-
paratively large leading or lagging current with small change to
the pressure of the system is the most suitable one. Or, the
motor which gives the greatest change in the leading or lagging
current is the one which gives best regulation. It is the change
in the amount of wattless current which produces the regulation.
This current could vary from zero to 100 leading, for example,
or could change from 50 leading to 50 lagging, or could change
from 100 lagging to zero lagging. Any of these conditions
could produce the desired regulating tendency, but all would1
not be equally good as regards the synchronous motor capacity.
If in addition to the regulating tendency it is desired to correct
for lower power-factor due to other apparatus on the circuit,
it would probably be advisable to run a comparatively large
leading current on the line due to the synchronous motor, and
the regulating tendency would be in the variations in the
amount of leading current, and not from leading to lagging,
or vice versa. A larger synchronous motor for the same regu-
lating range would be required than if the motor were used
for pressure regulation alone. It is evident that the current
capacity of a -motor regulating from 50 leading to 50 lagging
need be much less than for current regulating from 100 leading
to zero. It is evident therefore that if there is to be compensa-
tion for power-factor as well as regulation of pressure, that
'additional normal current capacity is required.
In case such synchronous motors are required for regulation
purely, it may be suggested that such machines be operated
at very high speeds compared with ordinary practice. At first
glance it would appear that such a synchronous motor could
be operated at the highest speed that mechanical conditions
would allow, but there are other conditions than mechanical
ones which enter into this problem. For instance, it is now
possible to build machines of relatively large capacity for two-
poles for 60-cycle circuits, and for very large capacities — say
1500 kilowatts — having four poles. Therefore mechanical con-
ditions permit the high speeds, and the electrical conditions
should be looked into carefully to see whether they are suitable
for such service. As such synchronous motors should give rela-
tively large currents on short circuit the effect of high speeds
and a small number of poles on short-circuit current should be
considered.
In order to give full-load current on short circuit, the field
56 ELECTRICAL ENGINEERING PAPERS
ampere-rums of such a machine should be practically equal to
the armature ampere-turns, taking the distribution of windings,
etc., into account By armature turns in this case is not meant
the ampere wires on the armature, but the magnetizing effect
due to these wires Therefore to give, for instance, five or six
times full-load current on short circuit, the field ampere-turns
should be relatively high compared with the armature
This means that the field ampere-turns per pole should be very
high, or the armature ampere-turns per pole very low Ex-
perience shows that for very high speed machines, such as used
for turbo-generators, there is considerable difficulty m finding
room for a large number of field ampere-turns, and therefore
in such machines it is necessary to reduce the armature ampere-
turns very considerably for good inherent regulating charac-
teristics This in turn means rather massive construction, as
the magnetic circuit m both the armature and field must have
comparatively large section and the inductions must be rather
high. This in turn means high iron losses in a relatively small
amount of material compared with an ordinary low-speed ma-
chine, and abnormal designs are required for ventilation, etc ,
and for mechanical strength
An increase in the number of poles usually allows increased
number of field ampere-turns without a proportionate increase
in the number of armature ampere-turns This condition is
true until a large number of poles is obtained when the leakage
between poles may become so high that the effective induction
per pole is decreased so that there is no further gain by increas-
ing the number of poles, unless the machine is made of abnormal
dimensions as regards diameter, etc. Experience has indi-
cated that in the case of very high-speed and very low-speed
alternators, it is more difficult to obtain a large current on short
circuit than with machines with an intermediate number of
poles For example, it is rather difficult to make a 600 kilovolt-
ampere, 3600-rev. per min., 2-pole machine which will give
three times full-load current on short circuit A 4-pole, 1800
rev. per min. machine can more easily be made to give three
times full-load current on short circuit and with comparatively
small additional weight of material The material in the ro-
tating part of the four-pole machine, while of greater weight,
may be of considerably lower cost per pound. The stationary
part of the four-pole machine may have a sorhewhat larger in-
ternal diameter, but the radial depth of sheet -steel will be less
POWER- FACTOR REGULATION 57
than in a two-pole machine. The total weight of material in
the armature of a four-pole machine may be practically no
greater than in a two-pole machine. Therefore a two-pole
machine of this capacity should cost more than a four-pole
machine, if designed to give the same current on short circuit.
A six-pole machine would show possibly a slight gain over the
one with four poles, but not nearly as much as the four-pole
machine would over the one with two poles The real gain of
the six-pole over the four-pole construction would be in ob-
taining a machine which would give more than three times
full-load current on short circuit. It would possibly be as
easy to obtain four, times full load current on short circuit
with a six-pole machine as to obtain three times full load cur-
rent on four7pole machine. An eight-pole machine would be
in the same way somewhat better than the six-pole machine
Therefore if a 600 kilovolt-ampere machine giving six times
full-load current on short circuit is desired, it would be advan-
tageous to make the machine with possibly eight to twelve
poles. The question of which would be the cheaper would de-
pend upon a number of features in design.
If very large short-circuit currents are desired, then, as in-
dicated above, the number of poles for a given capacity should
be increased, or the normal rating of the high-speed machine
should be decreased. If, for example, the 600 kilovolt-ampere,
3600 rev. per min. machine, mentioned above, should be rated
at 200 kilovolt-amperes, then it could give nine times full-load
current on short circuit ; but such a method of rating is merely
dodging the question.
In general, the following approximate Umits for speeds and
short circuit currents for 40-cycle apparatus can be given.
These limits are necessarily arbitrary, and are intended to rep-
resent machines which could probably be made without using
too abnormal dimensions,
600 kilovolt-amperes, 3600 rev. per min., two to three times
full-load current on short circuit.
1000 kilovolt-amperes, 1800 rev. per min., three to four
times full-load current on short circuit.
1500 kilovolt-amperes, 1200 rev. per min., four to five times
full-load current on short circuit.
2500 kilovolt-amperes, 900 rev. per min , four to five times
full-load current on short circuit.
For 25 cycles it is more difficult to give limiting conditions,
58 ELECTRICAL ENGINEERING PAPERS
as the choice of speeds is very narrow. If, for example, a 1500
kilovolt-ampere, 2-pole, 1500 rev per min. machine can be
made to give three times full-load current on short circuit,
then as machines of smaller rating cannot run at higher speed,
the limiting condition of such machines must be the amount
of current which they will give on short circuit In the same
way a 4-pole machine running at 750 rev per min. may be
made for 5000 kilovolt-amperes for three times full-load current
as the limiting rating, and there is no choice of speeds for
ratings between 1500 kilovolt-amperes and 5000 kilovolt-amperes.
It should be noted that the above speeds are very high com-
pared with ordinary alternator practice and are up to high-
speed turbo -generator practice, but machines with the above
short-circuit ratings and speeds are probably more costly to
build than machines of corresponding ratings at somewhat
lower speeds It will probably be found therefore that for
the above maximum current on short circuit the cheapest
synchronous motors for the given ratings will have somewhat
lower speeds than those indicated above It is certain that
tae lower-speed machines will be easier to design and will be
slightly quieter in operation Probably best all-round condi-
tions will be found at about half the above speeds.
The above limiting conditions are given as only approxi-
mate and are based upon machines having ventiliation as is
usually found on rotating field generators for high speed. Arti-
ficial cooling, such as obtained with an air-blast or blowers
could modify the above figures somewhat; but in general it
has been found that high-speed alternators can be worked up
to the limit imposed by saturation before the limit imposed
by temperature is attained. Therefore if higher saturation is
not permissible, then there may be relatively small gain by
using artificial cooling.
One of the principal applications of such regulating syn-
chronous motors would be for controlling or regulating the
pressure at the end of a long transmission line for maintaining-
constant pressure at the end of the line, independent of fluc-
tuations of load or change of power-factor. In this case, in-
creased output of the transmission line may more than con-
pensate for the cost of the regulating synchronous motor. In
such a case the synchronous motor not only acts as a regulator
on the system but costs nothing in the end. In general, the
more current that such a synchronous motor will give on short-
POWER-FA CTOR REG ULA TION 50
circuit, the better suited it will be for its purpose at the end
of a long transmission line
Where a number of such synchronous motors are installed
in the same station, the field adjustment must be rather care-
fully made, to avoid cross-currents between machines, and the
saturation characteristics of the various machines should be
very similar. The better such machines are for regulating
purposes, the poorer they are for equalizing each other by
means of cross-currents
As to the use of dampers with such synchronous motors,
it is difficult to say just what is required A synchronous
motor on a line with considerable ohmic drop is liable to hunt
to some extent, especially if the prime mover driving the gen-
erator has periodic variations in speed If the synchronous
motor gives very large current on short circuit, then its syn-
chronizing power is high , this will tend to steady the operation
of the motor and decrease the hunting. The writer believes
that such motors in practice will be found to operate better
and have better regulating power for constant pressure if pro-
vided with rather heavy copper dampers effectively placed on
the field poles. With such heavy dampers reaction of the
armature on the field is retarded, and therefore the armature
may give a larger momentary current than would flow it there
were no damping effect; in other words, the motor is more
sluggish than one without dampers Therefore the addition
of heavy dampers on such a machine may produce the same
regulating effect which would be obtained by a machine without
dampers which gives a larger current on short circuit. Also
a machine with heavy dampers will usually be the one with
the least hunting tendency and therefore will have the least
effect on the transmission line due to hunting currents.
In the above, the synchronous motor has been considered
only as a regulator and not as a motor. It may be worth
considering what would be the effect if the synchronous motor
can do useful work at the same time that it regulates the
system. In this case, with a given rated output, one com-
ponent of the input will be wattless, and the other part will
be energy. The ratio of these two components could be varied
as desired. For example, considering the input as 100, the
wattless component could be 60 when the energy component
is 80; or the synchronous motor could carry a load of 80%
of its rated capacity, this load including its own losses, and could
60 ELECTRICAL ENGINEERING PAPERS
have a regulating component of 60% of its rated capacity.
If the motor is used as a regulating machine only, then its
wattless component caa be practically 100 It appears there-
fore" that the machine could be used more economically as both
motor and regulator than as a regulator alone, but in such case
it would probably be advisable to run the motor at somewhat
lower speed than if operated entirely as a regulator. This
reduction in speed may practically offset the gain in apparent
capacity by using the machine for a double purpose, Also
there is comparatively limited use for large synchronous motors
for power purposes, as better results are usually obtained by
subdividing the units and locating each unit nearest to its-
load. If a load could be provided which would permit very
high-speed driving, then it would probably be of advantage
to utilize the synchronous motor for driving
As the synchronous converter is one form of synchronous
motor, the question of utilizing such machines for regulators-
should be mentioned* Upon looking into the question of dis-
tribution of losses in the converter, it will be noted that the
losses in the armature winding are not uniform Investigations
show that at 100% power-factor, the lowest heating in copper
is obtained, and that any departure from this power-factor
shows considerably increased loss in the copper, such loss being
very high in certain portions of the winding Next to the
taps which lead* to the collector there are strips of winding
which at times are worked at a very high loss. Experience
shows that it is not advantageous to operate converters at a
low power-factor, and that if so operated continuously, or
for any considerable periods > the winding should he made much
heavier than for higher power-factors, Also in the usual de-
sign of converters the field is not made as strong compared
with the armature as in alternator practice, and therefore the
regulating tendency of the converter compared with a generator
or ordinary synchronous motor, is low. Synchronous con-
verters can and do act as regulators of pressure for sudden
changes of the supply pressure, but such correcting or regu-
lating action should not be continual; that is, the pressure
supplied to a converter from a line should nominally be that
required by the converter for best operation as a synchronous
converter. Unless designed for the purpose, a synchronous
converter should not be used to correct low powgr-factors.
due to other apparatus on the circuit.
PO WER-FA CTOR REG ULA TION 61
In the above considerations only general reference has been
made to the cost of synchronous motors for regulating pres-
sure and power-factors It is difficult to give even approxi-
mate figures for relative costs of such apparatus As inti-
mated before, there is some mean speed or number of poles
which will be the most suitable for giving a certain maximum
current on short circuit. For speeds slightly above or below
such mean speed, the cost of the synchronous motor should
vary almost in proportion to the speed, provided the maximum
short-circuit current can be diminished somewhat at the same
time If the speed is further increased or further decreased,
the cost will tend to approach a constant figure As the ex-
treme conditions are approached, the cost will begin to rise.
The above assumptions are on the basis of continuous opera-
tion at a given current capacity, this being the same in all cases.
The above assumption is on the basis of decrease in the max-
imum short-circuit current, as the machine departs from the
mean, or best speed. If the same maximum current is re-
quired, then the lowest cost should be at the mean or best
speed, while at either side the cost should rise.
It is evident that it would be difficult to give any figures on
relative costs of such apparatus. The machine for the best
or mean condition, should cost practically the same as an alter-
nating-current generator of the same speed, output, and short-
circuit characteristics. As this speed would probably be some-
what higher than usual generator speeds, the cost of such
machine would therefore be somewhat lower. This cost would
be to a considerable extent, a function of the current on short
circuit for a given rated capacity of machine. As mentioned
before, in giving a table of limiting speeds and short circuits,
it is probable that one-half this limiting speed would be near
the best condition. Such machines would probably cost from
60% to 80% as much as similar machines for usual commercial
high-speed conditions, neglecting turbo-generator practice. The
frequency has considerable effect on this, as, for example, there
is small choice of speed as regards high-speed 25-cycle machines.
Taking very general figures only, it is probable that in the
case of a given capacity of machine for say three or four times
full-load current on short circuit the cost cannot be expected
to be lower than one-half that of machines of similar rating at
ordinary commercial speeds, turbo-generator practice being ex-
cluded. The costs in general should approximate more nearly
62 ELECTRICAL ENGINEERING PAPERS
those of turbo -generators, but again, an exact comparison
cannot be made because in usual practice the turbo-generators
do not give three to four times full-load current on short circuit.
There are a number of other conditions in this general problem,
such as advantage or disadvantage of placing synchronous
motors in the main power-house, or distnbuting them m a
number of sub-stations Also there is the question of the eSect
of the cost on the generating plant when used with such regu-
lating synchronous motors. If higher power-factors are main-
tained on the transmission system and generator, a cheaper
form of generator can probably be used. The high power-
factor permits a larger output from the transmission system
and thus represents a gam. If the synchronous motor can be
operated at its best speed and also do work, then there is a
further gam If the synchronous motor should be located * at
the center of power distribution, and the power is" distributed
through induction motors, then there is a possibility of re-
ducing the cost of such motors by lowering the power-factor,
this being compensated for by the synchronous motor deliver-
ing leading currents As the cost per horse power of small
motors will be much greater than the cost per horse power of
a large regulating motor, there is a possibility of gain from this
source. If the induction motors are distributed over wide
territory, this gain would "be lessened and might disappear.
It should be mentioned that the powers-factor of a system
as influenced by difference in wave form has not been con-
sidered in the preceding discussion. It is obviously impossible
to neutralize by a synchronous motor the effect of currents
in a system due to difference in wave form. Such currents will
in general be of higher frequency than the fundamental wave
of the system, and the synchronous motor obviously could not
correct for them, unless it impressed upon the system opposite
waves of the same frequency. This would mean a synchronous
motor with a different wave form from that of the system.
The power-factor of a system will also be affected by any
hunting of the apparatus on the system. It is evident that
the synchronous motor could not correct or neutralize such
•effects, except through exerting a damping effect on the system
And other apparatus on the system. A synchronous motor
with heavy dampers can reduce the hunting in a system, but
such hunting can also be damped by induction motors with
low -resistance secondaries, especially if of 'the cage type. This
POWER- FACTOR REGULATION 63
correcting effect should therefore be credited to the damper
rather than to synchronous -motor action. There are a number
of other questions which arise in connection with this regu-
lating feature of the synchronous motor, but the subject is too
broad to permit even mention of them.
The substance of the preceding statements can be summarized
as follows:
1. A synchronous motor can be-used to establish leading or
lagging currents in its supply system by suitable field adjust-
ment, and can thus affect or control power-factor or phase
relations of the current in the alternating current system
2. A synchronous motor will set up leading or lagging cur-
rents in its supply system if its field strength is held constant,
and the pressure of the supply system is varied above or below
that generated by the synchronous motor Such leading or
lagging currents in the supply system will tend to vary the
pressure of the system A synchronous motor can thus act
as a regulator of the pressure of its supply system.
3. This regulating action is greatest with synchronous motors
which have the closest true inherent regulation (as indicated by
high field magnetomotive force compared with the armature
magnetomotive force) in distinction from machines which have
close apparent regulation obtained by saturation of the mag-
netic circuit.
•4. If the synchronous motor is used both for regulating the
power-factor for neutralizing the effect of other apparatus on
the circuit, and for regulating or steadying the pressure of
the supply system, its normal capacity for regulating will be
diminished.
5. The most suitable speeds for best electrical conditions
will in general be considerably below highest possible speeds
as limited by mechanical conditions.
6. Heavy dampers will increase the effectiveness of the reg-
ulating tendency.
7. If the synchronous motor can be used for power purposes
as well as for regulation, its apparent capacity is increased.
This is due to the fact that the regulation is obtained by means
of a wattless component and the power from the energy com-
ponent, and the algebraic sum of these two is greater than their
resultant which fixes the current capacity of the machine.
8. Synchronous converters in general are not suited for reg-
ulating the pressure or controlling the power-factor of an alter-
t svstem.
64 ELECTRICAL ENGINEERING PAPERS
9. The costs of synchronous motors for regulating purposes
will in general be lower than for alternating-current motors
or generators of customary speeds, and will approach more
nearly -to turbo-generator practice
DATA AND TESTS ON 10 000 CYCLE PER SECOND
ALTERNATOR
FOREWORD — In 1902, the author undertook the construction of
10 000 cycle per second alternator. This problem was a very
new and radical one at that time and it was considered worth
while to put the record of results m permanent form. There-
fore, this paper was prepared on the subject and presented before
the American Institute of Electrical Engineers in May, 1904.
This is interesting merely as a record of a relatively early
construction. — (ED )
IN the early part of 1902, M. Leblanc, the eminent French
engineer, was in this country, and spent considerable time at
the Westinghouse Electric & Manufacturing Company's works at
East Pittsburg. M. Leblanc was very much interested in cer-
tain special telephone work, and in connection with such work
he desired for experimentation a current of very high frequency.
He took up with the writer the question of building a successful
alternator for generating current at frequencies between 5000
and 10 000 cycles per second. He was informed that the ma-
chine would necessarily be of very special construction, but that
it was not an impossible machine. Later he took up the
matter with Mr. Westinghouse, who, upon receiving satisfactory
assurance that such a machine was possible, advised that the
generator be built. A preliminary description of the general
design was given M. Leblanc before he returned to Paris. He
was somewhat surprised at certain of the features proposed,
especially at the fact that an iron-cored armature was consid-
ered feasible for a frequency of 10 000 cycles per second.
The machine was designed and built on practically the lines
of the preliminary description furnished M. Leblanc. The fre-
quency being so abnormal, the writer believes that many features
in the machine, with the results obtained, will be of scientific
interest, and therefore the data of the machine, and the tests
obtained are presented herewith
The starting point in this machine was the sheet-steel to be
used in the armature. No direct data were at hand showing
losses in sheet-steel at such high frequencies, nor was there 'at
65
66 ELECTRICAL ENGINEERING PAPERS
hand any suitable apparatus for determining such losses. As
preliminary data, tests at frequencies up to about 140 cycles
per second were used and results plotted in the form of curves;
these results were plotted for different thicknesses of sheet-steel.
Also, tests were obtained showing the relative losses due to
eddy currents and hysteresis, and these were plotted, taking
into account the thickness of the sheets. These data were not
consistent throughout; but the general shape of the curves was
indicated, and in this way the probable loss at the frequency
of 10 000 cycles per second was estimated for the thinnest
sheet-steel which could be obtained. The steel finally obtained
for this machine was in the form of a ribbon about 2 in. wide,
and about 0.003 in. thick, which was very much thinner than
any steel used in commercial dynamos or transformers, which
varies from 0,125 to 0.0280 inch. Therefore the machine had to
be designed with the intention of using this narrow ribbon of
steel for the armature segments.
A second consideration of great importance in the construc-
tion of such a machine is the number of poles permissible for
good mechanical construction. For instance, at 3000 revolu-
tions— which was adopted as normal speed — the number of
poles required is 400 for 10 000 cycles per second. The fre-
quency, expressed in terms of alternations per minute, multi-
plied by the pole-pitch in inches, gives the peripheral speed in
inches. At 1 200 000 alternations per minute (or 10 000 cycles
per second) and a pole pitch of 0.25 in., for example, the peri-
pheral speed of the field will be 25 000 feet per minute. It
was therefore evident that either a pole construction should be
10000 CYCLE ALTERNATOR 67.
adopted which would stand this high peripheral speed, or the
pole-pitch should be less than 0.25 in. It was finally decided
that an inductor type of alternator would be the most convenient
construction for this high frequency; with the inductor type
alternate poles could be omitted, thus allowing 200 pole projec-
tions, instead of 400. The field winding could also be made
stationary instead of rotating, which is important for such a
high speed. This construction required a somewhat larger ma-
chine for a givan output than if the usual rotating type of
machine were adopted; but in a machine of this type where
everything was special, the weight of material was of compara-
tively little importance, and no attempts were made to cut the
weight or cost of the machine down to the lowest possible limits.
The following covers a general description of the electrical
and magnetic features of the machine.
Armature. — The armature was built up in two laminated
rings dovetailed into a cast-iron yoke, as indicated in Fig. 1.
^" Ffe-B
The laminations were made in the form of segments dovetailed
to the cast-iron yoke (Fig. 2). Special care was taken that the
laminations made good contact with the cast-iron yoke, as the
magnetic circuit is completed through the yoke.
The armature sheet-steel consisted of plates of 0.003 in.
thickness. The sheet-steel was not annealed after being re-
ceived from the manufacturer; it was so thin that to attempt
annealing was considered inadvisable. To avoid eddy currents
between plates each segment was coated with a thin paint of
good insulating quality. This painting was a feature requiring
considerable care and investigation, as it was necessary to obtain
a paint or varnish which was very thin, and which would adhere
properly to the unannealed laminations. These laminations
had a bright polished appearance quite different from that of
ordinary steel. They were so thin that the ordinary paint or
varnish used on sheet-steel made a relatively thick coating,
possibly almost as thick as the plates themselves. A very thin
varnish was finally obtained which gave a much thinner coating
than the plate itself, so that a relatively small part of the arma-
ture space was taken up by the insulation between plates.
ELECTRICAL ENGINEERING PAPERS
Each armature ring or crown has 400 slots. Each slot is
circular and 0 0625 inch diameter "(Fig 3) There is 0.03125
inch opening at the top of the slot into the air-gap, and the
thickness of the overhanging tip at the thinnest point is 0 03125
inch
g. 4
The armature winding consists of No 22 wire, B. & S gauge,
and there is one wire per slot. The entire winding is con-
nected in series (Fig 4) The measured resistance of the wind-
ing is 1.84 ohms at 25° cent.
After the sheet-steel was built up in the frame, it was ground
out carefully. The laminations were then removed, all burred
edges taken off and the laminations again built up in the frame.
The object of this was to remove all chances of eddy currents
10000 CYCLE ALTERNATOR 69
between the plates due to any filing or grinding. The finished
bore of the armature is 25.0625 inch.
Field or Inductor. — This was made of a forged-steel disc
25 in. diameter turned into the proper shape, and the poles
were formed on the outside by slotting the periphery of the ring.
The general construction is indicated in Figs, 1 and 5. The
poles were 0 125 in wide and about 0 75 in. long radially and
were round at the pole-face. Fig. 6 shows the general dimen-
sions of a pole.
The field winding consisted of No 21 wire, B. & S. gauge.
There were 600 turns total arranged in 30 layers of 20 turns per
layer. The field coil after being wound was attached to a light
brass supporting ring. The general arrangement of the field or
inductor, armature yoke, and bearings, is as indicated in Fig 1.
The measured resistance of the field winding is 53 8 ohms at
25° cent.
Tests. — The machine was designed primarily for only a small
output, but was operated on temporary test up to 2 kw. A
series of curves were taken at 500, 1000, 1500, 2000, 2500, and
3000 revolutions, giving frequencies from 1667 to 10 000 per
second. At each of the above speeds, saturation curves, iron
losses, and short-circuit tests were made. Friction and wind-
age were also measured at each speed.
On account of the high frequency, the machine was worked
at a very low induction; consequently there is an extremely
wide range in pressure, the normal operating pressure being
taken at approximately 150 volts.
On curve sheet No. 1, the saturation curves for the various
speeds are given. These curves check fairly well, the pressure
being practically proportional to the speed with a given field
charge. This is to be expected at the lower speeds, but it was
considered possible that at 3000 revolutions the air-gap might
be slightly lessened, due to the expansion of the rotor under
centrifugal action; and it was also thought that eddy-current
loss due to the high frequency might affect the distribution of
magnetism at the armature face, but the armature iron losses
were comparatively small, and there appeared to be no such
effect. Also there appears to be no effect due to expansion at
high speed. The air-gap specified for this machine is 0 03125 in/
on each side or 0.0625 in total gap. A very small varia-
tion in the diameter of the inductor or the bore of the armature
70
ELECTRICAL ENGINEERING PAPERS
would make a relatively large per cent, in the effective air-gap,
Therefore no reliable calculations can be made on the saturation
curves of this machine based upon the specified air-gap.
Curve sheet No. 2 shows the iron losses at various speeds
from 500 to 3000 rev. per min. — 1667 to 10 000 cycles per second.
These losses are plotted in terms of watts for a given exciting
400
37
LO 1.2 1.4
Field Amperes
current. These curves show a rather unexpected condition as
regards the losses. According to the original data showing the
• relative losses due to eddy currents and hysteresis, the eddy-
current loss even with these thin plates should have been much
higher than the hysteresis loss, but these iron-loss curves sho^v
10000 CYCLE ALTERNATOR
71
losses with a given field charge almost proportional to the fre-
quency, which is the ratio that the hysteresis loss alone should
show. As the eddy-current loss varies as the square of the
frequency, the writer expected this to be a large element in
the total iron loss, especially at the higher inductions.
The six curves shown on this test-sheet are fairly consistent
1
1400
1300
1200
1100
1000
900
800
700
000
000
400
300
SJOO
IOC
HIGH- FREQUENCY ALTERNATOR
10000 Cycles per Second
Iron-Loss Tests
0.2 0.4
0.8 LO lj> 1.4
Field Amperes
1.8
with each other, but it should be remembered that in making
measurements of such abnormal apparatus little discrepancies
in the curves could easily creep in. For instance, in the satu-
ration curve a series of experiments were first made to find
whether usual types of voltmeters were satisfactory, and a num-
72
H&IELECTRICAL ENGINEERING PAPERS
ber of different methods for checking these readings were used;
In determining the iron losses in curve sheet No. 2, the machine
was driven by a small motor and the losses measured with difn
ferent field charges. Under most conditions of test the iron los$
was a small element of the total loss, and therefore slight varia-.
tions in the friction loss would apparently show large variations
HIGH-FREQUENCY ALTERNATOR
10000 Cycles per Second
Short-Circuit Tests
<U
Field Amperes
in the iron losses. Also the fly-wheel capacity of the rotating
part of the alternator was comparatively high. Therefore, if
there are any variations in the circuits supplying the driving
motor, there would tend to be considerable fluctuations in the
power supplied. Considering all the conditions of test, the
curves appear to be remarkably consistent.
10000 CYCLE ALTERNATOR
73
Curve sheet No. 3 shows the short-circuit curves at speeds
of 1000, 2000, and 3000 rev. per min., or frequencies of 3333,
6667, and 10 000 cycles per second, respectively. It should be
noted that at a given frequency the short-circuit current is pro-
portional to the field current over the entire range measured
1000
1500
rev. permia.
2000
2500
9000
tut that the short-circuit current is not the same for the same
field current at the various frequencies. According to these
curves the current on short circuit increases somewhat with the
given field charge as the frequency is increased.
Curve sheet No. 4 shows the measured windage and friction
losses plotted at speeds from 500*to 3000 rev. per min. This
ELECTRICAL ENGINEERING PAPERS
curve indicates clearly that the windage is the principal friction
loss at the higher speeds. The writer has added two curves,
one showing the estimated bearing friction loss, and the other
the estimated windage, based upon the assumption that the
bearing friction varies directly as the revolutions and the wind-
age loss with the third power of the revolutions. The small
circles lying close to the measured loss curve show the sum of
these estimated losses, and the agreement with the measured
loss is fairly close over the entire range.
II
0,8150
117 11*?
HIGH-FHEQUENCr ALTERNATOR
10000 Cycles per Second
Regulation Test artOOOO Cycles per Second
No 2
Joostac
t eiiLf
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0.^140
in —
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Ampei-es Load
Curve sheet No. 5 shows regulation tests made at ISO volts.
The power-factor of the load on this test was not determined,
and it was extremely difficult to make accurate measurements.
The load consisted of incandescent lamps and the wiring from
the machine to the lamps was non-inductive for the usual fre-
quencies; but at the abnormal frequency of 10 000 cycles per
second it is more difficult to obtain a true non-inductive load
with ordinary apparatus. The tested regulation indicates that
the load was practically non-inductive.
In first undertaking tests on this machine there was consid-
10000 CYCLE ALTERNATOR 75
erable difficulty in measuring the pressures. It was found that
at a frequency of 10 000 cycles per second the Weston voltmeter
did not work satisfactorily. Practically the same deflection
was obtained on the high and low scales of a 60-120 volt Weston
alternating-current direct-current voltmeter with the same
pressure.
Very good results were obtained by the use of a form of
static voltmeter devised by Mr. Miles Walker. This voltmeter
is of the same form as the static wattmeter described by Mr.
Walker before the AMERICAN INSTITUTE OF ELECTRICAL EN-
GINEERS, May 1902,* Tests were also made with the Cardew
hot-wire voltmeter with the high frequencies, and the results
checked very satisfactorily with the static voltmeter.
For measuring the current a current dynamometer was used
which had wood upright supports and a celluloid dial. The
only metal parts outside of the copper coils were brass screws.
It was found that the current dynamometer is not affected by
frequency, unless there are adjacent metal parts in which eddy
currents can be generated which react upon the moving element.
The dynamometer used had but a few turns in order to reduce
the pressure drop across it. This dynamometer "was checked
very carefully at different frequencies and apparently gave
similar results for any frequency between 25 and 10 000 cycles.
Several temperature tests were made on this machine. The
heaviest load on any test was 13.3 amperes at 150 volts, or
2-kw. output. This test was of two hours' duration, and at the
end the armature iron showed a rise of 16° cent.; the armature
copper 21° cent, by resistance, and the field copper 17.3° cent.
Air temperature 19° cent. The machine showed a relatively
small increase in temperature at this load over the temperature
rise with one-third this load. This was probably due to the
fact that the windage loss was so much higher than the other
losses of the machine that the temperature was but little affected
by the small additional loss with increase in load.
Attempts were made to utilize the current from this machine
for various experiments, but difficulty was at once found in
transforming it. At this high frequency no suitable iron-cored
transformer was available. Transformers with open magnetic
circuits were tried and operated better than those with iron cores
but were still rather unsatisfactory. It was decided that nothing
could be done in this line without building special transformers.
[TRANSACTIONS of the A. I. E. E^ Vol. xix. p. 1035J
76 ELECTRICAL ENGINEERING PAPERS
Among the few experiments made was that of forming an arc
with current at this high frequency. This arc appeared to be
like an ordinary arc so far as the light was concerned, but had
a very high-pitched note corresponding to the high frequency.
This note was very distressing to the ears.
This machine is in reality of the nature of a piece of labora-
tory apparatus; and at present it has no commercial value. It.
was designed primarily for scientific investigation, and appears*
to be a very good machine for that purpose.
THE SINGLE-PHASE COMMUTATOR TYPE RAILWAY
MOTOR
FOREWORD — This paper was presented before the Philadelphia
Section of the American Institute of Electrical Engineers in
February, 1908. It describes, as simply as possible, the general
construction and characteristics of compensated series single-
phase motors — (ED.)
THE broad statement may be made that it is no more difficult
to commutate an alternating current than an equal direct
current Such a statement would appear to be entirely contrary
to the usual experience, but a little study of the matter will show
where the apparent discrepancy lies. In commutator type alter-
nating-current motors, as usually built, a relatively large number
of commutator bars pass off under the brush during one alternation
of the supply current. While the current supplied is varying
from zero to maximum value and back to zero, possibly 50 bars
have been passed under the brush, and therefore 50 coils in
the armature have been reversed or commutated. Some of
these reversals occur at the top of the current wave which has
a value of about 40% higher than the mean or effective value
which is read by the ammeter. The motor is therefore at times
commutating 40% higher current than that indicated by the
instruments. It is thus evident that in comparing the com-
mutation of 100 amperes direct-current with 100 amperes
alternating-current we should actually compare the direct-
current with 141 amperes alternating. In other words, for com-
mutating equal currents alternating-current or direct-current,
the alternating-current ammeter should register only 71% as
much current as the direct-current. Another way of expressing
it is that we have to commutate the top or maximum of the
alternating-current wave, while our instruments only record
the mean value.
If the above represented the only difference between the
alternating current and direct current the problem to be solved
in commutation of alternating current would not be serious.
77
78
ELECTRICAL ENGINEERING PAPERS
However, the current to be commutated by an alternating-
current motor is not merely the working current supplied tc
the motor and measured by the ammeter, but there is, in addi-
tion, a current which is generated m the motor itself, both a1
standstill and during rotation, which has to be reversed or com-
mutated along with the working current. It is this latter cur-
rent, usually called the local or short-circuit current, which has
been the source of greatest trouble in commutating alternating
current; for this short-circuit current may have a value any-
where from three to ten times the working current, depending
on the design of the machine. Therefore in comparing the com-
mutation of an alternating current, as indicated by an ammeter,
/
0
\
1
0
\
I
1
0
o
r
f
1 * ! f ;
O
o
1
1
FIG. 1
with an equal direct current, we should, in reality, consider
that the alternating-current motor is commutating a maximum
current from five to ten times the value of the indicated current
Furthermore, it would not do to reduce the ammeter current to
one-fifth or one-tenth value in order to compare commutation
with direct current, because by so doing we would simply be
reducing the small applied component of the total current
commutated by the brushes, the local or short-circuit current
still retaining a rather high value. In order to compare with
direct-current commutation, it would be necessary for the
total maximum of the combined supply and the short-circuit
current to be reduced to the same value asr direct current.
SINGLE-PHASE RAILWAY IfOTOR 79
It is the local current in the armature turn short-circuited
by the brush which is the source of practically all the trouble in
commutating alternating currents Fig 1 illustrates a portion
of the field and armature structure of a commutator type
alternating-current motor. It will be noted that the armature
conductor, which is in the neutral position between poles, sur-
rounds the magnetic flux from the field pole, just as the field
turns themselves surround it. The field flux being alternating,
this armature turn will have set up in it an electromotive force
of the same value as one of the field turns. Short-circuiting
the two ends of this armature turn should have the same effect
as short-circuiting one of the field turns, which is the same
thing as short-circuiting a turn on a transformer. Such a short-
circuited turn, if of sufficiently low resistance, should have as
many ampere-turns set up in it as there are field ampere-turns
In single-phase motors of good design the field ampere-turns
per pole are about twelve to fifteen times the normal ampere-
turns in any one armature coil. Therefore, if the armature coil
in the position shown in this Fig. 1 should have its ends closed
on themselves the current in this coil would rise to a value of
twelve to fifteen times normal In reality, it would not rise
quite this much, because this armature turn is placed on a
separate core from the field or magnetizing turns with an air-
gap between, so that the magnetic leakage between the primary
(or field winding) and this armature (or secondary winding)
would tend to protect this coil somewhat, just as leakage between
the primary and secondary windings of a transformer tends to
reduce the secondary electromotive force and current. Also,
this armature coil is embedded in slots, thus adding somewhat
to its self-induction, and tending further to reduce the short-
circuit current. In consequence, with its ends closed together
the current in this armature coil would probably not rise more
than ten to twelve* times above normal value under any con-
dition. It is evident, therefore, that if the brush shown in
Fig. 1 as bridging across two commutator bars to which the
ends of this coil are connected is of copper or other low-resistance
material, then there could be an enormous local current set up
in the coil when thus short-circuited by the brush. This local
current of about ten times the normal working current would
have to be commutated as the brush moves from bar to bar,
and therefore the operation of the machine would be similar to
that of a direct-current motor if overloaded about ten times
in^ current. In other words, there would be vicious sparking.
80 ELECTRICAL ENGINEERING PAPERS
Even if the low-resistance brush were replaced by one of
ordinary carbon, the short-circuiting current would still be rela-
tively high, due to the fact that it is not possible to make the
brush contact of very high resistance by reducing the size or
number of the brushes, because these -same brushes must carry
the working current supplied to the motor, and there must be
brush capacity sufficient to handle this current. This brush
capacity will, in practice, be of such amount that the resistance
in bridging from one bar to the next is still rather low, although
much higher than if a copper brush were used. Experience
shows that with not more than four or five volts generated in
this short-circuited coil by the field flux, the resistance of the
carbons at the contact with the commutator would be such that
a short-circuit current of three to fouf times the normal working
current in the coil can still flow. Therefore, if the motor were
equipped with carbon brushes and had but four or five volts
generated in the short-circuit coil, the motor would have to-
comrnutate the main or working current and also a short-circuit
current of possibly three times the amount. This short-circuit
current would also have a maximum or top of its current wave.
Assuming 100 amperes as the current supplied to the motor,
the machine therefore actually commutates a supply current of
141 amperes and an additional short-circuit current of possibly
three times this value, or from 400 to 500 amperes; therefore,
the motor actually comtoutates the equivalent of about 600'
amperes direct current when the alternating-current ammeter
is reading 100, It is evident from this that any one who tries
to commutate alternating current with an ordinary type of
commutating machine would at once draw the conclusion that
alternating current in itself is very difficult to commutate,
naturally overlooking the fact that it is the excessive "current
handled by the brush that is back of the trouble, and not the
current indicated by the ammeter.
From what has been stated, it is evident that the excessive
local current is back of the difficulty in commutating alternating
current. All efforts of designers of alternating-current com-
mutator motors have been in the direction of reducing or elimina-
ting this local current. The present success of the motor, in
the various forms brought out, is largely due to the fact that
this current has been successfully reduced to so low a value that
it does not materially add to the difficulties of commutating the
main current. No successful method has yet been practically
SINGLE-PHA SE RA IL WA Y MOTOR S 1
developed for entirely overcoming the effects of this short-circuit
current under all conditions from standstill to highest speed.
Some of the corrective methods developed almost eliminate this
current at a certain speed or speeds, but have little or no cor-
rective effect under other conditions; other methods do not effect
a complete correction at any speed, but have a relatively good
effect at all speeds and under all conditions. The former
methods would appear to be applicable to motors which run at,
or near, a certain speed for a large part of the time; the latter
method would be more applicable to those cases where the motor
is liable to be operated for considerable periods with practically
any speed from standstill to the highest. While several methods
have been brought forward for correcting local current when
the motor has obtained speed, yet up to the present time but
one successful method has been developed for materially re-
ducing this current at standstill or very low speeds. It may
be suggested that the short-circuit voltage per coil be reduced
to so low a value, say four or five volts, that the local current
is not excessive and does not produce undue sparking. This
would certainly reduce the sparking difficulty, but is open to the
very great objection that the capacity of the motor is directly
affected by a reduction in the short-circuit voltage. This voltage
per turn in the armature coil is a direct function of the value of
the alternating field-flux and its frequency. Assuming a given
frequency, then the short-circuit voltage is a direct function of
the induction per field pole, and the lower the short-circuit volt-
age the lower must be the field flux. But the output of the
machine, or the torque with a given speed, is proportional to
the product of the field flux per pole by the armature ampere-
turns. In a given size of armature the maximum permissible
number of ampere-turns is pretty well fixed by mechanical and
heating considerations, and therefore with a given armature
the torque of the motor is a direct function of the field flux.
Using the maximum permissible armature ampere-turns, the
output of a given motor would be very low if the field flux were
so low that the short-circuit voltage would not be more than
three or four volts. Increasing the field induction, and there-
fore increasing the short-circuit voltage, increases the output.
Experience shows that on large motors, such as required for
railway work, the induction per pole must necessarily be so high
that the electromotive force in the short-circuit coil must be
about double the figure just given; therefore, with such heavy
82
ELECTRICAL ENGINEERING PAPERS
flux the short-circuited current will necessarily be excessive
unless some corrective means is used for reducing it.
I will consider the standstill or low-speed conditions first
For this condition only one practical arrangement has so far
been suggested for reducing the local current to a reasonably
low value compared with the working current. This method
involves the use of preventive leads, or, as they are sometimes
called, resistance leads These consist of resistances connected
between the commutator bars and the armature conductors.
Fig. 2 illustrates the arrangement. The armature is wound
like a direct-current machine, except that the end of one arma-
ture coil is connected directly to the beginning of the next
o'
8
O
0
0
FIG 2
without being placed m the commutator Between these con-
nections separate leads are carried to the commutator bars, and
in these leads sufficient resistance is placed to cut down the
short-circuit current. The arrangement is very similar in effect
to the preventive coils used in connection with step-by-step
voltage regulators which have been in use for many years. In
passing from one step to the next on such regulators, it is common
practice to introduce a preventive coil or resistance in such a
way that the two contact bars are bridged only through this
preventive device.
In. an armature winding arranged in this way, the working
current is introduced through the brushes and the leads to the
armature winding proper. After entering the winding, the
SINGLE-PHASE RAILWA Y MOTOR S3
current does not pass through the resistance leads because the
connections between coils are made beyond these leads. In
consequence, only a very small number of these leads are in
circuit at any one time, when the armature is in motion all the
leads carry current in turn so that the average loss in any one
lead is very small. As the brush generally bridges across two
or more commutator bars, there is usually more than one lead
in circuit, but generally not more than three. When the brush
is bridging across two bars, there is not only the working cur-
rent passing into the two leads connected ta these two bars,
but there is the local current, before" described, which passes in
through one lead, through an armature turn, then back through
the next lead to the brush. There are losses in these two leads
due to these two currents. By increasing the resistance, the loss
due to the working current is increased, but at the same time
the short-circuit current is decreased. As the Toss due to this
latter is equal to the square of the current multiplied by the
resistance, it is evident that increasing this resistance will cut
down the loss due to the local current in direct proportion as the
resistance is increased. When the working current is much
smaller in value than the short-circuit current, an increase in
the resistance of the leads does not increase the loss due to the
working current as much as it decreases the loss due to the
short-circuit current. Both theory and practice show that
when the resistance in the leads is so proportioned that the
short-circuit current in the coil is equal to the normal working
current, the total losses are u minimum. Calculation, as well
as experience, indicates that a variation of 20% to 30% at either
side of this theoretically best resistance gives but a very slight
increase in loss, so there is considerable flexibility in the adjust-
ment of this resistance. The resistance of the brush contacts
and of the coil itself must be included with the resistance of the
leads in determining the best value. In practice it is found that
with ordinary medium-resistance brushes, the resistance in the
leads themselves should be about four or five times as great as
the resistance in the brush contact and the coil; that is, we
usually calculate the total necessary resistance required and
then place about 70% or 80% of it in the leads themselves.
When leads of the proper proportion are added to the motor, it
is found that practically twice as high field flux can be used as
before with the same sparking and burning tendency as when
the lower flux is used without such leads. But even with six
84 ELECTRICAL ENGINEERING PAPERS
to eight volts per commutator bar as a limit, we are greatly
handicapped in the design of the motors, especially when the
frequency is taken into account. This limited voltage between
bars also indicates at once why single-phase railway motors are
wound for such relatively low armature voltages. Direct-
current railway motors commonly use from 12 to 20 volts per
commutator bar, or from 2 to 2.5 times the usual practice on
alternating-current motors. With this low voltage between
bars in alternating-current machines, with the largest practic-
able number of bars, the armature voltages become 200 to 250,.
or about 40% of the usual direct voltages. The choice of low
voltage should, therefore, not be considered as simply a whim
of the designers; it is a necessity which they would gladly
avoid if possible.
Assuming preventive leads of the best proportions, let us
again compare the current to be commutated in an alternating-
current motor with that of the direct-current. Considering
the ammeter reading as 100, the working alternating current
has a maximum value of 140 and in addition there is a short-
circuit current of same value. Even under this best condition,
the alternating-current mo tor must commutate a current several
times as large as in. the corresponding direct-current motor.
The design of such a motor, therefore, is a rather difficult prob-
lem, even under the best conditions. .
While resistance leads theoretically appear to give the most
satisfactory method for 'obtaining good starting and slow-
speed running conditions, yet other methods have been pro-
posed. The only one of any practical importance is that in
which the short-circuit voltage is reduced at start and at slow
speed by sufficiently reducing the field induction. As this
reduced field induction would give a proportionately reduced
torque, it is necessary at the same time to increase the armature
ampere-turns a corresponding amount above normal. This is
only a part solution of the problem, however, for the decrease
in short-circuit current by this means is partly offset by the
increase in the working current, so that the total current to be
commutated is not reduced in proportion to the field flux.
Where the period of starting and slow running is very short>
this method is fairly successful in practice. However, with this
arrangement it is rather dangerous to hold the motor at stand-
still for any appreciable length of time, for in such a case the
large short-circuit current is confined to a single coil and the
SINGLE-PHASE RAILWAY MOTOR So
effect is liable to be disastrous if continued for more than a very
short period. With this method of starting, the total current
handled by the brushes will usually be at least two to three
times as great as when preventive leads are used.
The preceding statements refer mainly to starting or slow-
speed conditions. When it comes to full-speed conditions,
however, there are various ways of taking care of the commuta-
tion. One of these methods is based on the use of preventive
leads, as described ; the other methods depend upon the use of
commutating poles or commutating fields in one form or another.
It is evident, from what has been said, that at start the pre-
ventive leads which reduce the short-circuit current to low
values will also be effective in a similar manner when running
at normal speed Such a motor with proper proportion of
leads will, in general, commutate very well at full speed when
the starting conditions have been suitably taken care of Nothing
further need be.said of this method except that the tests show
that the short-circuit current has considerably less value at
high speed than at start.
The other methods of commutation at speed, involving corn-
mutating poles and commutating fields, necessarily depend upon
the armature rotation for setting up a suitable electromotive
force in the short-circuit coil to oppose the flow of the short-
circuit current. As the electromotive force in the short-cir-
cuited coil is a direct function of the field flux, and is inde-
pendent of speed, while the correcting electromotive force is a
function of the armature speed, it is evident that either the
commutating pole can produce the proper correction only at
one particular speed, or the strength of this commutating pole
must be varied as some function of the speed Usually the
strength of these poles is made adjustable with a limited number
of adjustments and approximate compensation only is obtained
on the average. In the Siemens-Schuckert motor the corn-
mutating poles are of small size and placed between the main
poles. These are for the purpose of obtaining commutation
when running. In addition the armature is provided with pre-
ventive leads for improving the operation at start and at slow
speed. In the Alexanderson motor, according to published
description, no separate commutating poles are provided, but
the edges of the main poles are used as commutating poles,
the armature coil having its throw shortened until its two sides
come under the edges of the main poles. In this motor the field
S6 ELECTRICAL ENGINEERING PAPERS
'is weakened and the armature ampere -turns are increased
while starting The commutating-pole scheme in this motor is,
m some ways, not as economical as in the Siemens-Schuckert
arrangement, as the motor requires a somewhat higher mag-
netization with a consequent reduction in power-factor The
Winter-Eichberg motor is quite different in arrangement from
any of those which I have mentioned I will not attempt to
describe this motor in full, but will say that it has two sets of
brushes in the armature, one of which is short-circuited on
itself, and carries the equivalent of the working current in the
types I have described, while the other carries the magnetizing
or exciting current which is supplied to the armature winding
instead of the field. The arrangement is such as to give prac-
tically the same effect as a commutating pole or commutating
field. When starting, the field flux is decreased and the arma-
ture ampere-turns increased
All of the above motors are nominally of low armature voltage
and all of them appear to comrnutate reasonably well at speed.
Two of them use the full-speed induction at start, while the
other two use reduced induction and increased armature ampere-
turns at start.
There has been considerable discussion during the last year
or two regarding the most suitable frequency for single-phase
commutator type motors It may therefore be of interest to
consider what effect reduction in frequency would have on the
commutation, output, and other characteristics of the motor.
The short-circuit voltage, as I have stated before, is a function
of the amount of field flux and of the frequency. For a given
short-circuit voltage the induction per pole can be increased
directly as the frequency is decreased If a certain maximum
induction per pole is permissible at 25 cycles, then with 12.5
cycles, for example, the induction per pole may be double, with
the same short-circuit voltage, This would at once permit
double output if the saturation of the magnetic circuit would
permit the doubling of the induction. But on 25-cycle motors,
as usually built, we work the magnetic flux up to a point just
on the verge of saturation, so to speak, as indicated in Fig. 3.
It is evident that double induction, under such conditions,
would not be practicable unless the 25-cycle motor had been
worked at an uneconomically low point. However, an increase
of 30% to 40% in the induction would appear to be obtainable,
but a large increase in excitation is required. With but 30%
SINGLE-PHASE RAILWAY MOTOR
87
to 40% higher induction, and with the frequency halved, the
short-circuit voltage would be but 65% to 70% of that with
25 cycles or, in other words, the voltage per turn in the field
coil is but 65% to 70%. As the higher induction raises the
armature counter electromotive force the field electromotive
force can be increased in proportion for the same power-factor,
or can be 30% to 40% higher than with 25 cycles. As the total
field voltage, therefore, can be 30% to 40% higher, and the
voltage per field turn is but 65% to 70%, it is evident that the
number of field turns can be doubled without changing the
<u
S-l
c
o
I
FIG. 3
ratio of the field inductive volts to the armature electromotive
force. In other words, the field turns can be doubled if the
frequency is halved. With the double field turns the field
excitation can therefore be doubled, which is the requirement
for the increased induction shown in Pig. 3., It is thus evident
that halving the frequency will permit higher pole inductions,
and therefore higher torque and output, with lower short-circuit
voltage and better commutatmg conditions throughout. Also,
this higher field induction is not necessarily accompanied by an
increased iron loss, for the lower frequency of the alternating
88 ELECTRICAL ENGINEERING PAPERS
flux compensates for this. On the above basis it may be asked
why a reduction to 15 cycles is proposed instead of to 12 5, or
even to 10 cycles. There are several reasons for the choice of
15 cycles.
1. The motor can be worked up to so high a saturation at 15
cycles that there is relatively small gain with a reduction to
12 5 cycles, which would be about the lowest frequency to con-
sider when the transformers and other apparatus is taken into
account
2 As the torque of the single-phase motor is pulsating in-
stead of being constant, as in a direct- current machine, there
is liability of vibration as the frequency of the pulsation is de-
creased. This effect becomes more pronounced the larger the
torque of the motor, and is, therefore, of most importance in the
case of a large locomotive Expenence shows that this ten-
dency to vibrate can be damped out effectively in very large
motors with a frequency of 15 cycles, but becomes more difficult
to suppress as the frequency is further reduced. This is, in
reality, one of the fundamental reasons for keepmg up to 15
cycles instead of reducing to 12 5 or lower.
3. The lower the frequency the heavier the transforming
apparatus on the car or locomotive. It is probable that with
12^ cycles instead of 15 cycles, the increase in weight and cost
of the transforming apparatus would about counter-balance
the decrease in the same items in the motors themselves, al-
though the efficiency and power factor of the equipment would
be slightly better with the lower frequency.
4. As synchronous converters will be used to some extent m
connection with the generating plants for single-phase systems
in order to feed existing direct current railways, the frequency
of 15 cycles will be slightly more favorable than 12.5 as regards
cost of the converters and the step-down transformers The
same will be true if motor-generators are used for transforming
to direct current, also for induction motors.
Against the choice of 15 cycles may be cited the fact that
there are other frequencies which represent a better ratio to
25 cycles when frequency-changers are to be taken into account.
A low-frequency railway generating plant may require to tie
up with some existing 25-cycle or 60-cycle plant; this can be
done by interposing frequency-changers. Or it may be desired
to obtain a lower frequency with a single-phase current from
some existing higher frequency^ polyphase plant, By inter-
SINGLE-PHASE RAILWAY MOTOR 89
posing the frequency-changer the single-phase railway load will
not exert any unbalancing effect on the polyphase supply
circuit, and at the same time the railway circuit can be regulated
up or down independently of the three-phase generator circuit.
In case the three-phase plant is operated at 25 cycles, then a
two-to-one ratio of frequencies; that is, 12.5 cycles on the rail-
Way circuit, would give the best conditions as regards choice
of poles and speeds in the frequency-changer sets A five-to-
three relation is given by 15 cycles, which is not nearly as good
as the two-to-one ratio. A frequency of 16| cycles would give
a three-to-two ratio, which represents considerable improve-
ment over the five-to-three ratio Therefore, this slightly
higher frequency may prove of advantage in some cases. The
choice of this frequency, however, does not mean a new line
of apparatus; for a well designed line of 15-oycle motors tran-
formers, etc, should operate very well on a 16§-cycle circuit
without any change whatever
When transforming from 60 cycles, however, the 15 cycle
gives a four-to-one ratio which is very good, and neither 12,5
nor 16f cycles is very satisfactory. Therefore this 15-cycle
frequency represents the best condition in transforming from
60 cycles, and fairly good conditions for transforming from 25
cycles; and by operation of 15-cycle apparatus at 16$ cycles a
very good transformation ratio is obtained from 25 cycles. It
may be of interest to recall that the old Washington, Baltimore
and Annapolis Railway, which was the first road contracting
for single-phase commutator motors, was laid out for 16-J
cycles. There was considerable criticisms at that time of the
use of this frequency, but the statement which I have just made
shows one very good reason for this frequency A second rea-
son is that 16f cycles per second is 2000 alternations per minute,
which permits a steam turbine driving a two-pole generator to
use a speed of 1000 rev. per min., which is a very good one for
large turbo-generators.
I have gone into the question of induction and frequency
as affecting the commutation and torque. I will now take up
the question of power-factor in the single-phase commutator
motor In a direct-current motor we have two electromotive
forces which add up equal to the applied electromotive force ,
namely, the counter electromotive force due to rotation of the
armature winding in. the magnetic field, and the electromotive
force absorbed in the resistance of the windings and rheostat.
90 ELECTRICAL ENGINEERING PAPERS
In the alternating-current motor there are these two electro-
motive forces, and there is also another one not found in the
direct-current machine, namely, the electromotive force of self-
induction of the armature and field windings due to the alter-
nating magnetic flux m the motor This inductive electro-
motive force exerts a far greater influence than the ohmic
electromotive force for it has much higher values
The inductive electromotive force lies principally in the main
field or exciting winding of the alternating- current motor
There is a certain voltage per turn generated in the field coils,
depending upon the amount of the field flux and its frequency,
as stated before. This electromotive force per field turn is
practically of the same value as the short-circuit electromotive
force generated in the armature coil, as already referred to. I
have stated that a short-circuit voltage of three or four volts
per armature turn gave prohibitive designs and that it was
necessary practically to double this This means that the field
coils also have six to eight volts per turn generated in them
The total number of field turns must, therefore, be very small
in order to keep down the field electromotive force, for this
represents simply a choke-coil in series with the armature. If
the armature counter electromotive force should be 200 volts,
for instance, which is rather high m practice with 25-cycle
motors, then a field self-induction of half this value would allow
about 14 turns total in the field winding. Compare this with
direct-current motors with 150 to 200 field turns for 550 volts,
or 60 to 80 turns for 220 volts The alternating-current 25-cycle
motor, therefore, can have only about 20% to 25% as many
field turns as the ordinary direct-current motor. This fact
makes it particularly hard to design large motors where there
must be many poles. In the single-phase motor the induction
per pole being limited by the permissible short-circuit voltage,
it is necessary to use a large number of poles for heavy torques;
but the total number of field turns must remain practically
constant on account of the self induction, while in reality the
number of turns should be increased as the number of poles is
increased. With a given number of poles we may have just
sufficient field turns to magnetize the motor up to the required
point; but if a large number of poles should be required, then we
at once lack field turns and must either reduce the field induc-
tion, and thus reduce the output, or must add more field turns
and thus get a higher self-induction or choking action in the
SINGLE-PHASE RAILWA Y MOTOR 91
field, with a consequent reduction in power- factor Here is
where a lower frequency comes in to advantage, fdr, as I showed
before, with the same relative inductive effect, the field turns
can be increased directly as the frequency is decreased The
use of 15 cycles thus permits 67% more field turns than 25
cycles and raises our permissible magnetizing limits enormously
This problem is encountered particularly in gearless locomotive
motors of large capacity. For increased capacity the driving
wheels are made larger, thus permitting a larger diameter of
motor, the length, axlewise, being fixed. But with increased
diameter of drivers, the number of revolutions is decreased for a
given number of miles per hour. With 25-cycle motors we
soon encounter the above mentioned limiting condition in field
turns; beyond this point the characteristics of the motor must
be sacrificed, and even doing this we soon reach prohibitive
limits By dropping the frequency to 15 cycles, for instance,
we change the whole situation. The induction per pole can be
increased and the number of poles, if desired, can also be in-
creased. The practical result is that, in the case of a high-speed
passenger locomotive with gearless motors, a 700-h p. 15-cycle
motor can be got in on the same diameter of drivers as required
for a 500-h.p. 25-cycle motor. Also a 500-h.p. 15-cycle motor
goes in on the same drivers a.s a 360-h.p., 25-cycle motor. At
the same time these 15-cycle motors have better all round
characteristics than the 25-cycle machines as regards efficiency,
power-factor, starting, over-load commutation, etc.
Returning to the design of the motor, there is one other
electromotive force of self induction which may be considered;
namely, that generated in the armature winding and in the
opposing winding in the pole face, usually called the neutralizing
or compensating winding
Fig. 4 shows a section of the field and armature corresponding
to the usual direct-current motor, or an alternating-current
motor without compensating winding. In the direct-current
motor the armature ampere-turns lying under the pole face
tend to set up a local field around themselves, producing what
is known as cross-induction. This produces no harmful effect
except in crowding the field induction to one edge of the pole,
thus shifting the magnetic field slightly and possibly affecting
the commutation in a small degree. But if the armature is
carrying alternating current this cross flux will generate an
electromotive force in the armature winding, and this will be
92
ELECTRICAL ENGINEERING PAPERS
added to the field self-induction, thus increasing the self-induc-
tion or choking action of the machine. As the armature turns
on such motors are much greater, in proportion, than the field
turns, it is evident that the ampere-turns under the pole face
can exert a relatively great cross-magnetizing effect. This high
cross-magnetization generates a high armature self-induction
which may be almost as much as the field self-induction. Further,
this great cross-induction would tend to shift the magnetic
field quite appreciably, thus affecting the commutation to some
extent.
To overcome this serious objection, the neutralizing winding
is added. This is a winding embedded in the pole face and so
o \o\o\o\o\o \o V p IQI ooj o IO/QI o
/
FIG. 4
arranged that it opposes the armature cross-magnetizing action.
The arrangement is shown in Fig. 5. As it opposes and thus
neutralizes the cross-induction set up by the armature winding,
it eliminates the self-induction due to the cross-magnetization.
It also prevents shifting of the magnetic field and thus eliminates
its injurious effect on commutation. As the cross-flux is
practically cut out the armature winding becomes relatively
non-inductive. There is, however, a small self-induction in
the armature and neutralizing windings, due to the small flux
which can be set up in the space between the two windings,
they being on separate cores with an air-gap between.
I have stated that the field turns of the alternating-current
motor can be only 20% to 25% as many as in ordinary direct-
SINGLE-PHASE RAILWAY MOTOR
93
current practice. It may be questioned how the field caa be
magnetized with so few field turns. This has been one of the
most difficult problems in the motor. Obviously, one solution
would be the use of a very small air-gap, but in railway practice
there are objections to making the air-gap unduly small. Furth-
ermore, if the armature has large open slots, as shown in Fig. 6,
experience shows that a reduction in the clearance between the
armature and field iron does not represent a corresponding de-
crease in the effective length of the air-gap, due to the fact that
the fringing of the magnetic flux from the tooth tip of the pole
face changes as the air-gap is varied. The most effective con-
struction yet used consists in making the armature slots of the
partially closed type as in the secondary of an induction motor.
This is shown in Fig. 7.
jf
'—
-^c
^"-vV
'
s
'SS>
^
L^^M
^>xX;
\
\
\
1
o /o fo /o /b't o\ o\ o\ o^
'O^
[ 1
I 1 I • 1 i . \
0 \0 \0 \ 0 \ 0 \0 \0 \pl O/' Oy' O/ O/O / O/ 0
\ \ \ \ \ ^_^y v X / / /
FIG. 5
With this construction practically the whole armature surface
under the pole becomes effective, and the true length of air-gap
is practically the same as the distance from iron to iron. With
the increased effective surface, due to this construction, the
length of air-gap need npt be unduly decreased, which is of con-
siderable importance in railway work.
A further assistance in reducing the required field turns is
the field construction used in the single-phase motor. The
magnetic circuit consists of laminations of high permeability
and usually without joints across the magnetic path. The iron
is also worked either below the bend in the saturation curve or,
at most, only slightly up on the bend, except in the case of very
low frequency motors where more field turns are permissible.
ELECTRICAL ENGINEERING PAPERS
Taking the whole magnetic circuit into account, on 25-cycle
motors about 80% of the whole field excitation is expended in
the air-gap, while in direct-current motors, even with a much
larger air-gap, as much as 40% to 50% of the magnetization
may be expended in the iron and In the joints,
This armature construction with the partly closed slots has
been found very effective in large, slow-speed, single-phase
motors in which a relatively large number of poles is required.
This construction is used on the New Haven 250-h p., 25-cycle
/> / > vj
FIG. C
motors; also on the 500 h.p., 15-cycle motor on the Pennsylvania
locomotive exhibited at Altantic City at the Street Railway
convention, last October. Geared motors for interurban service
can be constructed with ordinary open slots with bands, and
many have been built that way. The semi-closed slot, however,
allows more economical field excitation.
It may be asked what the objection is to low power-factors
on single-phase railway motors, aside from the increased watt-
less load on the generating station and transmission circuits.
There is an objection to the low power-factor in such motors,
SINGLE-PHASE RAILWAY MOTOR
95
a very serious one. This lies in the greatly reduced margin for
overload torque in case the supply voltage is lowered. In
railway work it is generally the requirement of abnormal loads
or torques which causes a reduction in the line voltage ; that is,
the overload pulls down the trolley voltage just when a good
voltage condition is most necessary. This is true of direct cur-
rent as well as alternating current. In the direct current
motor, however, such reduction in voltage simply means reduced
speed but in the alternating current motor the effect may be
more serious.
To illustrate, assume a motor with a power-factor of 90% at
full load. The energy component of the input being 90%,
FIG. 7
the inductive component is about 44% or, putting it in terms of
electromotive force the inductive volts of the motor are 44%
of the terminal voltage, Neglecting the resistance of the motor,
a supplied electromotive force of 44% of the rated voltage
would just drive full-load current through it and develop full-
load torque. With full voltage applied the motor could develop
from five to six times full-lgad torque. Under abnormal con-
ditions a drop of 30% in the line voltage would still give suffi-
cient voltage at the motor terminals to develop two and one half
to three times full-load torque. Let us next take a motor of
80% power-factor at full load. The inductive voltage would
then become 60% of the terminal voltage, and therefore 60%
Of the rated voltage must be applied to send full-load current
96 ELECTRICAL ENGINEERING PAPERS
through the motor. This neglects the resistance of the motor,
which, if included, means that- slightly more than 60% of the
voltage is required. With full voltage applied, this motor
would develop about three or four times the rated torque.
With 30% drop in the line voltage the motor could develop
from one and one half to two times rated torque, which is hardly
enough for an emergency condition
Taking, next, a motor with 70% power-factor at full load it
would require 70% of.the rated voltage to send full-load current
through the motor; with 30% drop in line voltage the motor
could just develop full-load torque, and even with 15% drop it
would develop only about one and one half times torque. As
15% drop is liable to occur on any ordinary system", this latter
motor would be a very unsafe one.
It is evident from the above that it would be bad practice in
railway work to install motors with very low full-load power-
factors. In general, the higher the power-factor the more
satisfactory will be the service, other things being equal.
I have endeavored to explain some of the problems which have
been encountered in the design of single-phase commutator
railway motors of sizes suitable for all classes of railway service.
Here is a type of machine which has been known for a great
many years, but which, until the last few years, has been con-
sidered utterly bad. In a comparatively short time it has been
changed from what was considered an unworkable machine to
a highly satisfactory one and this has been accomplished, not
by any radically new discoveries, but by the common-sense
application of well known principles to overcome the apparently
inherent defects of the type. As an indication that the motor
is making progress in the railway field, I will mention that the
first commercial single-phase railway motors have not been in
use more than four or five years, and yet at the present time
there have been sold by the various manufacturers in this
country and Europe, a total capacity of approximately 200,000
to 250,000 h.p., a very considerable part of which has been put
in operation. Considering that the motor was a newcomer in a
well established field, the above record is astonishing. How-
ever, it may be safely predicted that what has been done in the
last five years will hardly make a showing compared with what
will be done during the next five years, for the real field for such
motors, namely, heavy railway work, has hardly been touched.
COMPARISON OF SERIES AND REPULSION TYPE
A. C. COMMUTATOR MOTORS
FOREWORD — This is part of a discussion by the author, of papers by
Dr. Steinmetz and Mr. Slichter before the American Institute
of Electrical Engineers, January 2d, 1904. The major part of
the author's discussion covered the comparison between the
series and repulsion type motors, in which, he showed that the
repulsion type was simply a series type motor with a trans-
former added. The several references to Mr. Shchter's paper
given in the discussion have but little bearing on the technical
matter contained but could not be eliminated without consider-
able remodeling of the paper. — (ED.)
DISCUSSION OF STEINMETZ AND SLIGHTER PAPERS n
IN the paper presented before the American Institute of Elec-
trical Engineers, in September, 1902, the speaker called atten-
tion to the fact that there were but two types of single-phase al-
ternating-current motors having suitable characteristics for rail-
way service; viz., that called the "Series Type/* and the "Repul-
sion Type." Attention was called to the fact that both
motors have suitable characteristics for railway service, as
both automatically give variable-speed characteristics with
changes in load. That paper primarily described a single-
phase railway system, and the motor formed but an ele-
ment in the general system. It was a very general opinion
at that time that, the success of the commutator type of motor for
large sizes was doubtful, and the sparking feature was considered
a fundamental source of trouble. It was generally conceded that
if a motor with series characteristics could be made to operate suc-
cessfully, it would be a great step in advance in the railway field.
Since that time single-phase railway systems have been more
fully developed. Practically, no departures from the general
system then indicated have been furnished, and the types of
motors developed have been along the lines of the two motors
indicated in that paper.
Up to the present time the only suitable motors suggested
for this work have been of the commutator type, and have been
those having series characteristics. The speaker has suggested
that all these motors can be considered broadly under the one
class of series motors, as they all have the series characteristics
97
98 ELECTRICAL ENGINEERING PAPERS
of the direct-current series motor. The speaker further sug-
gested that they be sub-divided into the "Straight-Series" type
and the "Transformer-Series" type. The transformer-series
could also be arranged in two classes; viz., one in which the
armature or field is supplied by an external transformer, and
one in which the transformer is placed in the motor itself, this
latter is the repulsion type of motor.
Figs 1, 2, and 3 illustrate the three classes. Fig 1 being the
straight-series, Fig 2 the transformer-series and Fig. 3 the repul-
sion motor Fig 2 would be considered as a true series motor,
although the armature and field are not directly in series, yet most
of the characteristics described as belonging in the repulsion
FIG 1.
PIG 2
FIG 3
motor apply directly to the transformer motor shown in the
figure. Comparing the relations of these motors, viz., the
straight-series and the repulsion motor, we will first take up the
straight-series.
In this motor, if properly designed, two pressures can be con-
sidered; viz,, that across the field circuit, and that across the
armature circuit. The armature pressure can be made practi-
cally non-inductive so that the input of the armature will repre-
sent practically true energy. The pressure across the field
is practically at right angles to the armature pressure, and repre-
sents very closely the wattless component supplied by the motor.
The resultant of these two pressures will then be the line pressure.
The power-factor of the motor when running is represented prac-
SERIES AND REPULSION MOTORS 99
ticaUy by the pressure across the armature winding, increased
slightly by the losses in the field-core and winding. Therefore,
for high power-factors it is important that the pressure across
the armature circuit be made as high as possible, relatively to
the applied pressure, and that across the field as low as possible.
There are three ways in which to increase the pressure across
the armature; viz., by increase in speed, by increase in the
number of wires in series on the armature, and by increase in flux
through the armature.
By increase in speed and increase of the wires in series, the
armature pressure will be increased without affecting the field
pressure, and therefore the ratio of the armature pressure to the
line pressure is increased. Increasing the flux in the armature also
increases the flux in the magnetizing-coil in the field, and the
pressures of both are increased. Therefore this increase does not
improve the power-factor of the machine.
Instead of increasing the armature pressure, the pressure
across the field winding may be decreased ; this can be done in two
ways; viz., by reducing the turns in the field coil, or by reducing
flux through the coil. Reducing the flux through the field re-
duces the flux in the armature winding also, and therefore repre-
sents no gain; reduction in field-turns, therefore, is the feasible
means of reducing the field pressure. Reduction in field-turns
can be accomplished in two ways; viz., by decreasing the effec-
tive length of air-gap in the motor, and by increasing the cross-
section of gap. By making the gap very small the pressure
across the field could be made very small compared with the
line pressure, and extremely high power-factors could be ob-
tained, whether the motor is of the straight-series or the repul-
sion type. Also by increasing the section of the air-gap the
turns of the field can be decreased with a given total flux through
the coil, and the power-factor can thus be very considerably
increased. The first method, viz., decrease in gap, is limited by
practical conditions which have been determined from long ex-
perience with direct-current work. It should be borne in mind
when published descriptions of such motors are given, that the
results, as regards power-factor, generally depend upon data
which are not given in the description; such as the magnetic
dimensions of the armature and field, the length of gap, etc.
Therefore, a machine may be described as showing an extremely
high power-factor, which may in practice not be a commercial
machine, from the standpoint of American railway experience.
100 ELECTRICAL ENGINEERING PAPERS
Increasing the section of air-gap without decreasing the
length of gap also improves the power-factor, but makes a larger
and heavier machine, as a rule.
Both these modifications reduce the ampere-turns in the field.
The direction of the improvement in the armature was shown
to be in increased armature ampere-turns with a given speed.
It therefore follows that almost any result desired can be ob-
tained as regards power-factor by increasing the armature am-
pere-turns and decreasing the field, or exciting ampere-turns.
Reference will be made to this point in considering the repulsion
motor.
It should be noted that in all these motors there should be but
little saturation in the magnetic circuit and but few ampere-
turns expended in saturation of the iron under normal conditions.
This consequent low saturation in such motors leads to certain
characteristics in the torque curves which have been cited this
evening as an indication of superiority of alternating-current
motors over direct-current motors; namely, a torque increasing
approximately as the square of the current. In fact, this superi-
ority of torque should be charged to the low flux-density of the
motor rather than to the alternating current. If direct-current
motors were worked normally at as low density as the alternating-
current motor, then the direct-current motor would show better
torque characteristics, and would be comparable with the alter-
nating-current motor. This claim for a better torque in the
alternating-current motor compared with the direct-current
motor seems to be making a virtue of a necessity.
It is evident from what has been said that the power-factor of
the straight-series motor can be made anything desired, it being
a question of proportion between armature and field, length of
air-gap, amount of material used, etc. In practice a compromise
would naturally be made among the various characteristics, and
a slight reduction in power-factor is probably of less importance
than a corresponding reduction in size and weight. Also large
clearance is probably of more importance than an extremely high
power-factor at normal load. In practice it will be found that
the armatures of such motors have a large number of ampere-
turns compared with the fields, in order to obtain comparatively
high power-factors with large air-gaps. The number of poles
need not be made such that the product of the poles by the normal
speed represents the frequency of the supply circuit; good series
SERIES AND REPULSION MOTORS 101
motors can be made, and have been made, in which the number
of poles were very much larger or much smaller than represented
by this relation.
Taking up next the transformer type of motors — Fig. 2; the
field is in series with the primary of the transformer, the second-
ary of which is connected to the terminals of the motor. I would
call this a true series motor, although it is not a straight-series
motor. In this motor the pressure across the armature can be
made practically non-inductive and the pressure across the
primary of the transformer will be practically non-inductive.
The voltage across the field winding will have practically 90°
phase relation to that across the primary of the transformers, and
the magnetic field, set up by the field winding, will have a 90°
relation in time to the magnetic field in the transformer, as in
the repulsion motor. In this motor the voltage across the trans-
former will be highest at light loads and will decrease with load
until zero speed is reached. At start there is lowest flux in the
transformer and highest flux in the field winding. Such a motor
will have speed-torque characteristics very similar to those of a
straight-series motor, except as affected by the actions taking
place in the transformer itself. If the transformer possesses no
reactance, then at start the current in the armature should be
the same as if connected as straight-series motor, and the condi-
tions of torque at start should be the same. If the transformer
has reactance, then at start the current in the armature will not be
quite equal to the current which the armature will receive if
coupled as a straight-series motor, assuming the transformer to
have a 1 to 1 ratio. Neither will the armature current be ex-
actly in phase with the field current; therefore the starting
torque of a motor connected in this way will be slightly less than
the torque of the same motor if connected in straight-series.
This is on the assumption that the transformer is one propor-
tioned for small reactance; but if the primary and secondary
windings of the transformer should be on separate cores with
air-gap between, then the reactances of the windings are con-
siderably greater than in the above case. Therefore, we should
expect a motor with such a transformer to give still lower torque
than the straight-series with the same current supplied from
the line.
In a repulsion motor the transformer is combined with the
motor itself and the primary and secondary windings are upon
102
ELECTRICAL ENGINEERING PAPERS
different cores with an air-gap between. The starting condi-
tions of such a motor as indicated above should be poorer than
the straight-series motor, or for the same starting torque some-
what greater apparent energy should be required. It stands to
reason that applying the current directly to the armature wind-
ing should give greater ampere-turns and better phase relations
than generating this current in a secondary circuit, and not
under ideal transformer conditions. The tests which have been
made, as well as the results shown in the curves of the papers
given tonight indicate this. It is to be noted that the torque
curve is not the same shape near the zero speed point as the
torque curve of the series motor.
PIG 4.
FIG 5.
Series motors and repulsion motors may be indicated in the
simple form shown in Figs. 4 and 5. In the diagrams of the
repulsion motor (Fig. 5), two field-poles FF, are shown, and two
transformer-poles, TT. To obtain high power-factors on such a
motoi the ampere-turns in T must be very much greater than in
F, which means that the ampere-turns in the secondary or arma-
ture are much greater than in the exciting field, as in the series
motor. The high power-factor obtained with these motors is
therefore due principally to the small ampere-turns in the field
and the small pressure across the field.
For instance, with brushes set at an angle of 16°, from the
primary or resultant field, the ratio of armature to exciting field-
turns would be almost 5 to 1, a ratio which will also permit of
extremely high power-factors in well-designed straight-series
SERIES ASD REPULSION MOTORS 103
motors over wide ranges of speed. To this feature should be
credited the good power-factors claimed for the repulsion motor.
In either the series or repulsion type of motors, high power
factors, especially at low speeds, are directly dependent upon this
fact of high ratio of armature to field, and with a high ratio, high
power-factors should be obtained without crediting the result to
leading currents in the armature. In the diagram of the repul-
sion motor, the line current indicated flows through both the
field winding and the transformer winding. The primary cur-
rent sets up a magnetic field in the exciting windings in phase
with the line current. If it also set up a field in the transformer
in phase with the line current, then the electromotive force gen-
erated in the armature winding due to rotation would have a 90°
relation to the electromotive force set up by the transformer, and
a correcting or magnetizing current would flow. This flow is
in such direction that it corrects the relation between the two
pressures in the armature by shifting the transformer magnetism
one-quarter phase later than the exciting field magnetism. This
armature corrective current may thus be considered as mag-
netizing the transformer, making the primary input to the trans-
former practically non-inductive; but this magnetizing or cor-
recting current may be considered as flowing in a circuit at right
angles to the field magnetic circuit, and having practically no
effect on the field circuit. Therefore as a rough approximation,
the exciting field may be considered to represent the wattless
component of the input, and the transformer field the energy
component, as in the series motor. As to the statement that the
magnetizing current in the armature reduces the wattless com-
ponent of the exciting field, the speaker does not accept it broadly.
If this component is reduced, then another component of practi-
cally equal value is introduced somewhere else, for the power-
factors obtained with such motors can be accounted for by the high
ampere-turns in the armature winding, compared with the field
or exciting ampere-turns. If the armature current improves the
power-factor by diminishing the magnetizing or exciting field,
then the curves in Figs. 1 and 4 of Mr. Slichter's paper should
show it. The speaker has gone over both sets of curves calculat-
ing the wattless components from the power-factors. From this
and other data in these curves, he finds that beginning near
synchronous speed the wattless component in the motor goes tip
.slightly faster than would be represented by the field excitation,
104 ELECTRICAL ENGINEERING PAPERS
assuming it to be entirely wattless. Therefore, according to
these curves, the power-factors at lower speeds are not quite as
good as would be obtained by a field entirely inductive and the
armature entirely non-inductive, in a straight series motor.
These calculations are rather approximate, as the curves do not
check at all well with each other. For instance, the output of
the motor as represented by the input multiplied by the power-
factor and by the efficiency, does not check with the output as
represented by the product of speed by torque, in either set of
curves, the discrepancies being as high as 10 percent. In Fig. 4,
for instance, either the torque or the speed is too high for the
lower speeds. Checking back on this curve, using either the
speed and torque or the power-factor and efficiency for deter-
mining the output, the speaker finds that the wattless component
in the motor at 190 revolutions is approximately 20 percent
higher than it would be if the field excitation alone were wattless,
assuming at 440 revolutions the wattless component is represented
purely by field excitation; that is, from 440 to 190 revolutions the
wattless component is increased 20 percent over that which
would be represented by field excitation alone. This indicates
that not only should the field excitation be considered as practi-
cally wattless, but that in addition there is a wattless component
due to reactances in the armature windings.
The armature current can be split into two components, one
of which is partly magnetizing and represents no torque. The
other component is in phase with the field magnetism and there-
fore represents torque. The magnetizing or wattless element
may be comparatively small, as the number of turns in the arma-
ture is relatively large, but the armature thus carries at times a
slightly larger current than the straight-series motor.
A further inspection of the diagram (Fig. 5) indicates how the
power-factor of the motor can be made very high at synchronous
speed. At all speeds the pressure generated in the armature due
to rotation in the field of F, is practically equal to the pressure
generated by the transformer T, thus making zero pressure
across the terminals. But also at synchronous speed the pressure
generated by the exciting field acting as a transformer, between
the points a b, will be practically equal to the pressure generated
in the winding by rotation of the winding in the transformer
field. Therefore across a b the pressure is practically zero with
these conditions, but the frequency remains the same as that in
SERIES AND REPULSION MOTROS 105
the field. If now the magnetizing current be supplied across the
points a 6, then the required ampere-turns for magnetizing the
motor can be supplied at practically zero pressure, and the turns
of the external magnetizing field can be omitted. Therefore,
under this condition the wattless component is practically zero
and the power-factor becomes practically 100 per cent. This
is the method of excitation used on certain European single-phase
motors in which high power-factors are claimed for full-load
running. But this method of excitation does not improve con-
ditions at start, as the same excitation will be required at stand-
still, whether the excitation be supplied to the armature or to the
field. Therefore this method of excitation does not help the
motor at that condition of load which is the severest on the
generating and transmission system. It has the advantage of
omitting the field exciting winding, but has the great disadvan-
tage of requiring a double set of brushes on the commutator,
with but half the distance between the brushes found in the
straight-series or the ordinary repulsion motor. I do not believe
that such methods of compensation are of sufficient advantage to
overcome the complications attendant upon them.
At zero speed, both the straight-series and the repulsion
motors have low power-factors and with equal losses in the
motors, the repulsion should have slightly lower power-factor
than the series. This question of power-factor at start is largely
a question of internal losses in the motor at rest, ajid the repul-
sion motor in individual cases may show higher than the series
motor, because it may be designed with higher internal losses.
The real measure of effectiveness is not the power-factor at start,
but the apparent input or kilovolt-amperes at start required for a
given starting torque. With equally good designs of motors, the
speaker's experience is that the kilovolt-amperes will be found to
be considerably less with the straight-series than with the repul-
sion motor, due to the fact that the current is fed directly into
the armature and not by transformer action, and therefore the
conditions of phase-relation and amount of current in the arma-
ture windings are more favorable. Therefore it follows that in
order to have the same kUovolt-ampere input for the same start-
ing torque, the repulsion motor should have a smaller length
of air-gap tira-n the corresponding straight-series motor, or should
have a greater section of air-gap, which means greater weight
of motor. This is one of the conditions which has led the speaker
106
ELECTRICAL ENGINEERING PAPERS
to the advocacy of the series motor rather than the repulsion
motor, as he has considered this condition of starting of more
importance than running; although he is satisfied that many of
the running conditions of a well-designed series motor will be
found in practice to be superior to those of an equally well-de-
signed repulsion motor.
Referring again to Fig. 5, it will be noted that two fields are
set up in such a motor, and that at synchronous speed these two
fields are equal. In the straight-series motor there is but one
field set up, the other being omitted. It is evident that the
straight-series motor with the current supplied directly to the
brushes can have a smaller section in certain parts of the mag-
netic circuit than is required for the repulsion motor, and that
therefore the weight of material would be less, and the external
PIG. 1.
dimensions can be less. In Pig. 7 the heavy line represents
outlines of series and the dotted line those of repulsion motor;
therefore, it follows that for equally good designs and same fre-
quency, the straight-series motor should be more compact, and
should weigh less than the repulsion motor. It is reasonable
to expect this, as the repulsion motor contains a transformer in
addition to the other parts found in the straight-series motor.
Futherrnore, the transformer found in such a motor is one with
an air-gap, and with the windings on two separate elements, and
therefore cannot be so well proportioned as a separate trans-
former could be. Also, there is a transformer for each motor,
and in a 4-motor railway equipment, for instance, there would be
four transformers of smaller size against one largfer transformer
used with the series motor, this larger transformer having a
SERIES AND REPULSION MOTORS
107
closed magnetic circuit, and of a highly efficient design com-
pared with the transformers in the motors themselves.
A further point should be taken up in the comparison of these
motors ; viz , the current in the coil short-circuited by the brushes.
This coil is a secondary to the field and the current in it is neces-
sarily greatest at the period of strongest field. Therefore, this
current will be greatest at the time of starting. If the repulsion
motor and the straight series motor have the same field strength
at start, then the short-circuited current should be the same in
each But as the current is fed into the armature in the repulsion
motor through transformer action, it will as a rule be found that
CURRENT
STRAIGHT SERIES MOTOR
REPULSION MOTOR
the starting field strength of such a motor is slightly greater
and the starting armature strength slightly less for a given torque
than is found in the straight-series motor having same ratio of
armature to field windings. Therefore the short-circuit current
at start will be somewhat larger for the repulsion motor than for
the corresponding straight-series motor. This short-circuit cur-
rent may be somewhat less near full speed than in the straight-
series motor, but it is not the full-speed condition which is the
serious one. The short-circuit current at start is one of the
most serious conditions which confronts us in alterrating-cur-
rent motors, and is also of great importance where there is any
considerable operation on low speeds. The speaker advocates
10S ELECTRICAL ENGINEERING PAPERS
a type wHch he considers gives the easiest condition in this regard.
This short-circuiting cannot be entirely avoided in any of the
motors brought out without adopting abnormal and question-
able constructions, although devices like narrow brushes, sand-
wich windings, etc., have been proposed. In certain foreign
motors the brushes used are so narrow that they cover practically
the width of one commutator-bar. As such motors are gener-
ally built with a veiy large number of bars, the brushes used are
extremely narrow, being approximately 0.2 inch thick at the tip.
This will undoubtedly lessen the short-circuiting, but simply
transfers trouble to another point; a brush 0.2 inch thick is not
practicable for commercial railway service; at high speeds,
with only a moderately rough commutator, such brushes will
be liable to chip and break; further, the brush on a street-car
motor should bridge at least two bars to give good, smooth,
brush operation; in practice, a 0 5 inch brush on motors of 100 h.p.
should be used.
The sandwich winding, which consists of two or more wind*
ings side by side7 will prevent short-circuiting at the brushes, but
is only another way of transferring trouble to another point; it
has been found in practice that it is difficult to run a sandwich
winding without trouble at the commutator with direct current,
without a tendency to blackening and pitting the commutator,
and with alternating current this tendency to pitting and burn-
ing of the bars would be equally great.
As a rule, there is little difference between the operation of
repulsion and straight-series motors as regards sparking, except
that the repulsion motors generally have greater current in the
short-circuited coil near zero speed, and therefore show greater
tendency to heat and spark. At or near synchronous speed,
there appears to be very Httle difference in the commutation,
although the speaker has never given the repulsion motor the
same test of long-continued setvicfe as lie has in the case of the
series motor. These series motors have never shown any tend-
ency to give trouble on the commutator, and on an exhibition
car equipped with four 100-h.p. motors, the commutator nave
never been sandpapered since the equipment has been put into
service. This exhibition car is used principally for showing the
accelerating properties of the motors; therefore, the speaker
does not hesitate to say that the commutation of the straight-
series motor will prove to be equal to that of the direct-current
SERIES AND REPULSION MOTORS 109
motor. Wide brushes axe used with it, such as have been used
in street-railway motors.
It is well known that with large direct-current motors, espe-
cially when operated at very high speeds, there is a tendency to
flash across the commutator, or to the frame of the motor, if the
field circuit be opened for a period long enough to allow magnet-
ism to drop to zero, and then the field be closed again. In this
case there is a rush of current before the field has had time to
build up, and this rush of current, together with field distortion,
may cause serious flashing. In the alternating-current motor,
whether of the straight-series or the repulsion type, this ten-
dency should be entirely absent. In the straight-series motor the
magnetism falls to zero once in each alternation, and therefore
if this tendency existed, flashing would occur continuously.
Furthermore, a properly designed straight-series motor can be
short-circuited across the brushes without injury to the motor,
and can continue to operate in this way; therefore, if the ma-
chine can be short-circuited in this way, there is evidently no
tendency to maintain an arc.
Returning to the subject of power-factors it should be noted
that high-power-factors are very frequently found in motors of
low or only moderately good efficiency. This low efficiency to a
slight extent explains the high power-factor in some motors, both
polyphase and single-phase. Low efficiency means higher true
energy expended, and with a given wattless component it means
higher power-factor. It is the old problem of increasing the
power-factor by wasting energy in a circuit instead of reducing
the wattless component. The power-factor of any alternating-
current motor can be very considerably increased by putting
resistance in series with it. Instead of this resistance the internal
losses of the motor may be made higher, which will accomplish
the same results. The motor will therefore appear to have a
higher power-factor than it really deserves, if efficiency of the
motor is taken into account. If, for instance, the efficiency at
300 rev. shown in Mr. Slichter's Fig. 4 would be made as high as
on direct-current motors, then the power-factors with the same
magnetizing and other conditions, would have been approxi-
mately four percent lower. This lower power-factor would not
have made any harder condition on the supply circuit, but actually
would have made a somewhat easier condition, as the supply sys-
tem would have furnished about eight percent less Mlovolt-
110 ELECTRICAL ENGINEERING PAPERS
amperes. For lower speeds this difference in power-factor will
be greater, and less for higher speeds A high power-factor at
start, obtained by the use of resistance in series with the motor
by high internal losses which do not represent torque, is there-
fore a detrimental condition rather than a good one, as it means
increased kilo volt-ampere expenditure for a given torque. This
is merely given as an illustration showing that power-factor in
itself is not a true indication of conditions, but must be accom-
panied by other data; this is not a criticism of these motors,
but is a general condition, found to a greater or less extent in all
alternating-current motors.
COMPARATIVE CAPACITIES OF ALTERNATORS FOR
SINGLE AND POLYPHASE CURRENTS
FOREWORD — This article was prepared many years ago for the
information of the younger technical men of the Westinghouse
Company. It was considered of sufficient value by the Com-
pany to publish in pamphlet form, of which there were several
editions from time to time. It should be considered as purely
educational. Only the types of windings which were in use up
to the time the paper was prepared, are included. — (ED.)
THERE are a number of popular misconceptions regarding the
relative polyphase and single-phase capacities which can be
obtained from a given winding. For instance, there appears to be
a half -formed opinion that a given winding connected for two-
phase will give a slightly less output than when connected for three-
phase; but, on the other hand, it seems to be generally assumed
that the various three-phase windings all give the same rating.
Also, it is a widespread idea that when any polyphase machine
carries a single-phase load the permissible rating, with the same
temperature, is approximately 71 percent of the polyphase rating.
While there are a few cases where this may be true, yet, in general,
it is far from being the fact, as will be explained below.
This fallacy regarding single-phase ratings arose partly from
early practice with polyphase machines, which were ofttimes
designed with a view to carrying single-phase load almost exclu-
sively. In consequence, the type of armature winding chosen was,
in many cases, that which gave a high output on the single-phase,
with some sacrifice in the polyphase rating, and the single-phase
rating in many cases was a relatively large percent of the polyphase
rating simply because the polyphase rating was less than could
have been obtained with a different type of winding.
The 71 percent (or 70.71 percent) ratio of single-phase to poly-
phase ratings in a given armature arose partly from tho fact that
at these relative loads the total armature losses were practically
equal. On old designs of machines, in many cases it could be as-
sumed safely that with equal armature losses the temperature of
the armature parts would be practically equal. This assumption
ill
112
ELECTRICAL ENGINEERING PAPERS
does not hold, in general, on modern designs of machines in which
each individual part is proportioned for a specified result. The
distribution of the armature losses is just as important as the total
losses. If the temperature drop between the inside of the arma-
ture coil and the armature core is small compared with the tem-
perature drop from the core to the air, then the temperature of the
armature, or its rating, will depend largely upon its total losses,
equal ventilation being assumed in all such comparisons If, how-
ever,the temperature drop from the coil to the iron, or from the in-
side of the coil to the outside, is relatively high, then the temper-
ature limit may be fixed by the loss in an individual coil rather
than by the total loss. This is particularly the case in high voltage
machines where there is a considerable amount of insulation over
the individual armature coils. Also, in many of the later designs
of machines (especially turbo-generators) each armature coil is
practically separated from all other coils, so that one coil can have
but little direct influence on the temperature of its neighboring coils.
In such an armature it is possible to completely roast out an indi-
vidual coil or group of coils without seriously heating any other
coils or groups of coils. It is obvious that in such a machine the
loss in the individual coils is what fixes the rating of the machine,
and not the armature loss as a whole. It is evident, therefore, that
when a polyphase machine, with such a winding, is loaded single-
phase, the maximum current which can be carried in any single
coil must be the same for either polyphase or single-phase rating.
As this type of winding is used in the majority of large capacity
machines of the present day, the following comparison will show
CAPACITIES OF ALTERNATORS
113
the relative rating of such machines on polyphase and single-
phase loading. Three-phase ratings will be considered first,
because the great majority of modern machines are wound for
three-phase.
THREE-PHASE WINDINGS
All the various types of commercial three-phase windings
with their current and voltage relations can be derived in a very
simple manner from the consideration of a ring armature with
its windings arranged in six symmetrical groups, each covering
60 degrees of the ring, which may all be closed together to form
the ordinary closed winding, or which may be separated into either
three or six groups and connected to form various delta and star
types of windings.
Let Fig. 1 represent such a ring armature closed on itself and
with six taps brought out, these being designated as A, at B, b, C, c.
By connecting together the points Aa, aB, Bb, etc., as shown
in Fig. 2, a six-sided figure is obtained, which represents the
various voltage and phase relations which can be obtained with
all commercial three-phase (and six-phase) windings. It will be
noted that Aa and bC are of equal length and are parallel in di-
rection. The length represents e. m. f . and the direction re-
presents phase relation. Therefore, these two groups or legs are of
equal e. m f.'s and of the same phase. The same holds true of aB
and Cct and of Bb and cA. Beginning at Aa, these groups have
also been numbered consecutively from 1 to 6, so that in the
following diagrams a given leg or group can be identified by
number.
114
ELECTRICAL ENGINEERING PAPERS
Fig. 3 is the same as Pig. 2 with three leads carried out from
A, B and C to form the three terminals of a three-phase winding
The dotted lines from A to B, B to C, and C to A represent the
voltage and phase relations obtained from this combination
This is known as a closed coil type of winding and is the standard
arrangement of winding on a three-phase rotary converter. The
comparative e m. f . values for this and other combinations will be
given later
By opening the closed arrangement of Fig 2 at the points A, B
and C, as shown in Fig. 4, then an open coil arrangement is obtained
and the three parts resulting can be recombined in several ways,
keeping the same voltage and phase relations of the individual
parts.
•Fig. 6
However, only one of these combinations, — that shown in Fig.
5 — has been used to any extent. This is one form of star winding
which is sometimes used to give certain voltage combinations, as
will be explained later.
By splitting Fig. 2 at six points instead of three, as shown in
Fig. 6, various other open coil combinations of windings can be
obtained while keeping each group or leg in its proper phase and
voltage relations.
One of these combinations is shown in Fig. 7, in which the
groups which are similar in e. m. f . and phase are connected in
parallel and the three resulting combinations are connected to form
a delta winding.
In Fig. 8 the two groups of similar phase are shown in series
instead of parallel and connected to form a delta. Obviously
CAPACITIES OF ALTERNATORS
115
Pig. 7 and 8 are equivalent, except that the terminal e. m. f of one
is double that of the other
By reconnecting the three components of Fig 7 in the manner
shown in Fig. 9, a parallel star winding is obtained. Two arrang-
ments are shown, one with all the legs connected together at the
middle point, and the other with the two stars not connected at the
middle.
Fig 10 is equivalent to Fig. 9 except that the two e. m. f.'s of
\C
fig.IO
equal phase are in series instead of in parallel, thus giving just twice
the voltage of Fig. 9.
SIX-PHASE WINDINGS
The foregoing covers all of the usual combinations for three-
phase windings, open and closed coil types. The same general
scheme may be used to illustrate the usual six-phase combinations
of windings which are frequently used in connection with rotary
converters.
116
ELECTRICAL ENGINEERING PAPERS
In Fig. 3, a three-phase winding is shown with terminals at
A, B and C. If three other terminals be formed by a, b and c,
then a second three-phase winding is obtained. The dotted lines
in Pig. 11 illustrate the voltage and phase relation of these two
windiags. This is the so-called double delta arrangement some-
times used with six-phase rotaries, the dotted lines representing
the voltage and phase relations of the transformers which supply
the rotary converters.
c
r"
-/-— y--?
/ ^ '
Fig. II
It is evident that the voltage represented by ac is equal in
value and phase to that represented by BC. Therefore, one
transformer with, two secondaries of equal value could be tapped
across these two circuits. Similar arrangements can be applied to
the other two-phase relations in this diagram.
In Pig. 2 it is evident that, if six terminals are used, a voltage
can be obtained across Ab Similar voltages can be obtained
across aC and Be. These three voltages axe equal in value but
have the 60-degree relation to each other. It is evident therefore
that three transformers connected to a three-phase circuit can have
their secondaries connected to this winding across the indicated
CAP A CITIES OF ALTERNA TORS 1 17
points. This arrangement is indicated in Fig. 12, and is the
so-called diametral connection of six-phase rotaries. The middle
points of the transformer winding from these three circuits can be
connected together, if desired.
RELATIVE E. M. F. OBTAINED FROM THE FOREGOING
COMBINATIONS
From an inspection of the above diagrams, and the application
of but very little mathematics, all the e. m. f. relations of these
various combinations can be readily obtained. In the following
comparisons the magnetic field is assumed to be of such distribu-
tion that the e. m. f. waves will be of sine shape, as this greatly
simplifies the various relations.
Let E represent the effective e. m. f . of any one of the six legs
or groups in Fig. 2. Then, combining the various groups geo-
metrically, taking into account the angular relation between the
legs in the diagram, the various e. m. f.'s can be readily derived.
The results are as follows:
In Fig. 3, the e. m. f . across AB, BC, etc., = VT x E = 1 .732
E.
In Fig. 5, the e. m.f . Ad is the same as AB in Fig. 3 and is
therefore equal to -x/lT x E, but the e. m. f . AB in Fig. 5 is equal
to VlfxAd. Therefore, the e.m.f. of AB — VlTx VlTxS^
3E.
In Fig. 7, AB is evidently equal to one group or side of Fig. 2
and therefore the e. m. f . of AB = E.
In the same way the e. m. f . of Fig. 8 = 2E.
In Fig. 9 the e. m. f . Ad is evidently equal to E and the e. m. f .
AB= VTxe. m. f. of Ad. Therefore the e. m. f. of AB= i/lT*
E = 1.732 E, or same as Fig. 3.
In the same way the e. m. f. of ABinFig. 10= 2times V 3
x£ = 3.464E.
For the six-phase combinations the following e. m. f.'s are
obtained:
In Fig. 11 each of the deltas is the same as in Fig. 3 and
therefore the e. m. f.'s are the same and are equal to 1.732 E.
In Fig. 12, Ab is geometrically equal to twice aB and the
e. m. f . Ab is therefore equal to 2E.
THREE-PHASE CAPACITIES
It might be assumed from casual inspection that all of the
different combinations of three-phase and six-phase would give
118 ELECTRICAL ENGINEERING PAPERS
the same capacities when cajrrying the same limiting current per
armature coil, or per leg. This however, is not correct, as will be
shown by the following:
Let A equal the limiting current which can be carried by one
coil or by one group of windings. This is not necessarily the
current per terminal, but it is the current permissible in an indi-
vidual coil without exceeding a certain prescribed temperature.
Then the following ratings are obtainable with the above combina-
tions of windings.
In Pig. 3 the rating = 3A x y"~T x E =* 5.196 AE.
In Pig. 5 the current per coil and per terminal = A. The
e. m. f . becomes A x \/ir x 3E = 5.196 AE. Therefore the three-
phase ratings of the windings in Pigs. 3 and 5 are equal.
In Fig, 7 the current in each leg of the delta is 2A, as there
are two groups in parallel, each carrying current A . As the e. m. f.
across terminals is E, the rating becomes 3 x 2A x E *= 6 AE.
In Fig. 8 the current per side or leg of the delta is equal to A
and the e. m, f . is 2E. The capacity therefore becomes the same as
for Fig. 7 or = 6 AE.
In Fig. 9 the current per terminal is 2A as there are two
groups in parallel for each terminal. The e. m. f . across the term-
inals is V1T x E. The capacity is therefore 2A V~ x V1T E =
6AE.
The rating of Pig. 10 is also 6 AE, the same as Fig. 9.
In Figs. 11 and 12 the ratings can be determined by direct
inspection from the following method of considering the problem:
In a closed coil, polyphase machine, for example, such as
shown in Pig. 2, one circuit can be taken off from A and a, a
second circuit from a and B, etc., and the total number of circuits
which can be taken off corresponds to the number of armature taps.
Each circuit can be considered as having its own rating. There-
fore, the effective voltage of each of such circuits times the current
per circuit, times the number of circuits, equals the rating. In
Figs. 11 and 12 six circuits can be taJsen off, each with voltage
E and carrying current A. The rating therefore becomes 6 AE.
The same method could be applied to any other number of phases
from closed coil windings,
It is evident from the foregoing that the same rating can not be
obtained from the armature winding with all methods of con-
nection. In those three-phase arrangements in which two groups
of similar phase relations are thrown in series or parallel, the high-
CAPACITIES OF ALTERNATORS 119
est output is obtained. In those cases where two e m f.'s out of
phase with each other are combined to form one leg of the three-
phase circuit, it is evident that the resultant e. m. f. is at once
reduced by such combinations and that the capacity of the ma-
chine is therefore reduced, simply because the most effective use of
the windings is not obtained. The three-phase closed coil winding
is therefore not as effective as the true delta or star type of winding.
For this reason the closed coil winding is used in only those cases
where some condition other than the current capacity itself is of
greater importance. Otherwise, delta and star windings are
always used, the star being preferred as it gives a higher voltage
with a given number of conductors, or a smaller number of conduc-
tors for a given voltage, and is therefore somewhat more effective
in the amount of copper which can be gotten into a given space
SINGLE-PHASE RATING — Any three-phase machine with one of
the above windings can be used to carry single-phase load by using
two of the three terminals. The single-phase e. m f.'s obtained will
therefore be the same, in each case, as the three-phase. The
current capacity per coil, or group, on single-phase can be no
greater than on three-phase. On this basis, therefore, the following
single-phase ratings are obtained with the above combinations:
Fig. 3, calling A and B the single-phase terminals, then with
the limiting current A per coil, the windings 1 and 2 in the diagram
will carry current A, and 3, 4, 5 and 6 will carry %A. The total
current at the terminals will therefore be 1}^A and the e. m. f . per
terminal will be V~3~ E. The single-phase rating then becomes 1 .5
A x V1T E = 2.598 AE. The corresponding three-phase rating is
3A x V1TE = 5.196 AE. The single-phase rating is therefore just
50 percent of the three-phase for this combination.
In Fig. 5, the current per leg is A> while the e. m. f. is 3E.
The single-phase rating therefore becomes 3 AE. The correspond-
ing polyphase rating is .A x V1T x 3E = 5.196 AE. The single-
phase rating is therefore 57.7 percent of the polyphase rating
In Fig. 7 the total current in two legs is 2At while in the
other four legs of the delta the total current is A. The total
current at the terminals therefore becomes 3 A. The e. rn. f . is E
and therefore the single-phase rating becomes 3 AE. The corres-
ponding three-phase rating is 6 AE. The single-phase rating is
therefore 50 percent of the polyphase for a true delta winding.
The same holds true for Fig. 8.
120 ELECTRICAL ENGINEERING PAPERS
In Fig. 9 the current per group Is A and with two groups in
parallel the current per terminal is 2A. The e. m. f. across the
terminals is VT E. The single-phase rating therefore becomes
2A x VT E or 3 464 AE. The three-phase rating for the same
combination is 6 AE. The single-phase rating therefore becomes
57.7 percent of the three-phase when a true star winding is used.
Pig. 10 gives the same results as Fig. 9.
It may be noted that in the three-phase star arrangement
two legs are carrying all of the current, while the third leg is idle
and could be omitted. This means that the active winding covers
two-thirds of the armature surf ace, while an idle space of one-third
the surface lies in the middle of the winding.
In the delta winding it may be noted that one leg, covering
one-third the surface, is directly in phase with the single-phase
e. m. f . and is therefore in its most effective position The other
two legs carry current also, but are relatively ineffective as the
e. m f.'s generated in these two legs are displaced 60 degrees in
phase from the single-phase e. m. f . delivered. The delta arrange-
ment therefore has two-thirds of its winding acting in a very
ineffective manner. One-third of the winding is very effective.
In the star arrangement, two-thirds of the winding is almost in
phase with the terminal e. m. f . (being 86 6 percent effective), while
one leg is entirely idle. The star arrangement is about 15 percent
more effective than the delta arrangement.
The single-phase rating which can be obtained from the two
six-phase combinations shown in Figs. 1 1 and 12 should also be con-
sidered. In either of these diagrams, if two opposite terminals,
such as AB, be taken as the single-phase terminals, then the e. m f .
will be 2E. As each half of the winding can carry the current A,
the total which can be handled is 2A. The single-phase rating
therefore becomes 4AE. The corresponding polyphase rating is
6 AE. The single-phase rating is therefore 66.7 percent of the
polyphase, or is higher than in any of the other three-phase com-
binations shown. It should be noted, however, that in order to
obtain three-phase from this combination, transformers are neces-
sary in order to transform from six-phase at the winding to three-
phase on the line. Therefore, while this combination gives the
highest single-phase and polyphase ratings, yet if three-phase is
used on the transmission circuit, transformers must be interposed.
Therefore, the highest obtainable rating of single-phase and three-
phase from the same winding implies the use of transformers.
CAP A CITIES OF ALTERNA TORS 121
The high single-phase rating obtained in this case is due to the
fact that the arrangement is equivalent to the star arrangement
•with the idle leg added, as illustrated in Fig. 13. The addition of
this extra leg increases the terminal e. m. f . in the ratio of 100 : 86.6,
while the current per terminal remains the same. This arrange-
ment, when used for both single-phase and three-phase, implies
the use of a closed coil type of winding which, as shown before,
cannot give the maximum three-phase rating unless six terminals
axe used.
It should be noted that the three legs shown in Fig. 13 have
the same phase relations as a delta winding when used on single-
phase; that is, one of the three legs is in phase with the terminal
voltage, while the other two legs have a 60-degree relation, How-
ever, these two legs, with the 60-degree relation, carry the full cur-
rent A; while in the delta arrangement they carry one-half current.
Therefore, although the voltage relations are the same, the current
relations are quite different; which accounts for the increased
capacity with the groups connected as in Fig. 13 or Fig. 12.
Fig. 13, like Fig. 12, is equivalent to covering the entire arma-
ture surface with copper which is equally active in carrying current
when the machine is operated single-phase. However, compared
with the three-phase star arrangement where two legs only are
active, it may be seen that the voltage and the output have been
increased in the ratio of 100: 86.6, or about 15 percent, by the
addition of 33 1-3 percent in copper, and 33 1-3 percent in total
armature copper loss. It is evident, therefore, that the addition
of a third leg when operating single-phase does not give results in
proportion to the material used.
122 ELECTRICAL ENGINEERING PAPERS
COMPARISON OF SINGLE-PHASE AND THREE-PHASE RATINGS ON
THE BASIS OF EQUAL TOTAL ARMATURE COPPER Loss
All the foregoing comparisons have been on the basis of equal
losses in a given coil or group; but it has been shown that with
some of the windings, when operated on single-phase, the currents
are not divided equally. In consequence, in such cases the total
copper loss in the windings must be less than where the current is
divided equally. In the following comparisons the total copper
losses for three-phase and single-phase are given, and the possible
increase in single-phase rating for the same total copper loss is
indicated
Let r = the resistance of one group.
Let A = the limiting current per group, which has been used
in the above comparisons.
Then in Fig 3, for three-phase, 6Azr = the armature copper
loss. For single-phase { — jx4r + 2A2r = 3AV = total armature
copper loss.
The three-phase loss is therefore twice the single-phase on the
basis of equal limiting current For equal total loss the single-
phase current could therefore be increased as the V~2^ as the loss
varies as the square of the current. As the former single-phase
output was 50 percent of the three-phase, then for equal losses the
single-phase output "becomes 50 x V~T = 70.7 percent of the
corresponding polyphase rating.
In Fig. 5, the three-phase loss = 6AV. The single-phase loss
with the same limiting current = 4AV, as there are but four legs in
circuit instead of six, each leg carrying the same current as when
operating three-phase. The three-phase loss is thus 6/4 single-
phase, and for equal losses the single-phase current can be in-
creased in the ratio of -v/6/4- The former single-phase rating was
57.7 percent. This therefore can be increased to 57.7 x Vs/4 =
70.7 percent of the corresponding three-phase rating.
In Figs. 7 and 8, the three-phase loss = 6AV. The single-phase
loss = 3A*r, as determined by direct inspection of currents and
resistances, For equal losses, therefore, the single-phase current
can be increased as the VT- The output then becomes 50 x \/~ir
= 70.7 percent of the corresponding three-phase rating.
In Figs. 9 and 10, the three-phase loss = 6A2r. Single-phase
loss = 4A2r. The single-phase output - 57 7 percent and for
CAPACITIES OF ALTERNATORS 123
equal loss this can be increased in the ratio of VoTI- The output
then becomes 70.7 percent of the corresponding three-phase output.
In Fig. 12, the six-phase loss = 6AV. The single-phase
loss = 6A2r, as all the groups carry equal currents and all are in
circuit. Therefore the single-phase current cannot be further
increased and the single-phase output remains at 66.7 percent of
the six-phase output (or three-phase beyond the transformers.)
From this it would appear that most of the above wind-
ings would give, for equal armature copper loss, 70.7 percent of the
three-phase rating. However, it should be taken into account that
the three-phase ratings are not all equal on the basis of equal
copper loss.
In Figs. 3 and 5, for instance, the three-phase ratings are
equal to 5.196 AE. The three-phase ratings with the arrangement
shown in Figs. 7, 8, 9 and 10, are equal to £ 4£. Therefore Figs. 3
and 5 have only 86.6 percent of the three-phase ratings of 7, 8, 9
and 10. The single-phase ratings of Figs. 3 and 5 therefore are
70.7 percent of 86.6 percent, or 61.2 percent of the best three-phase
rating which can be obtained. Therefore, on the basis of 6AE
being the best three-phase output, then with equal copper loss, the
arrangements in Figs. 3 and 5 give 61.2 x 6AE = 3.792AE as the
single-phase rating with equal copper loss, while Figs. 7, 8, 9 and 10
give 4 243AE as the single-phase ratings with equal copper loss,
and Fig. 12 gives 4AE as the single-phase rating with the same
copper loss. Therefore, the arrangements in Figs. 7, 8, 9 and 10 are
better than any of the others for single-phase rating, if total copper
loss is the limit rather than the loss in an individual coil or group.
However, if total copper loss is the limit, then there is still a
difference between the true delta and star windings. With the
delta winding the current A is increased 41 percent, which means
that one of the groups will have double the copper loss which it has
on three-phase, while with the star winding the current A will be
increased slightly over 22 percent, which means that two groups of
the winding will have their copper losses increased SO percent. The
star arrangement, even with the same total copper loss, works the
individual coils on single-phase easier than in the delta arrange-
ment,
The following table summarizes the above relationships,
124
ELECTRICAL ENGINEERING PAPERS
Haas
AM
LIMITI
PER COJ
i
^ ^ •*
*%al
w
leo
s
ftj W
CO<J
'5?
fe?
7
1
g
5x2AxE
«3AE
5xAx2E
«=3AE
JJfl
M <
t-00
^7
w w
,«|«S
FH
B
S
CAPACITIES OF ALTERNA TORS 125
TWO-PHASE WINDINGS
w
The two-phase windings may be analyzed in a manner similar
to the preceding. Starting with a closed-ring arrangement, just as
in the three-phase, the various relations may be readily determined.
Assuming a ring, as in Fig. 14, with four taps brought out at 90
degrees apart and assuming that this winding is the same in every
way as that in Fig. 1, then the following e. m. f.'s and capacities
are obtained.
Fig. 14
Fig. 15 represents a closed coil two-phase winding correspond-
ing to the three-phase winding in Fig. 3. Calling E the e. m. f. of
the groups of legs, then the e. m. f.'s AC and BD = V1T x E.
Opening Fig. 15 at two opposite points as in Fig. 16, the two
parts may be rearranged to give Fig. 17. This is an interconnected
open coil two-phase winding; that is, the central points are con-
nected together so that there are fixed e. m. f . relations between all
four terminals. The e. m. f . Ad is equal to E, and the e. m. f . across
AB, BC, etc. = V!T x Ei, while the e. m. L across AC and BD =
Splitting the winding of Fig. 16 at four points, then the ar-
rangements shown in Figs. 18 and 19 are obtained. These two
windings are equivalent, except that in Fig. 18 the two legs which
are in phase are connected in parallel, while in Fig. 19 they are in
series. If the middle points in. Fig. 19 are connected together tie
arrangement becomes equivalent to Fig. 17. In Fig. 18, e. m. f.'s
AC and BD are equal to EI, while there is no fixed e. m. f . relation
between AB, BC, etc.
In Fig. 19 the e. m, f.'s ACaad BD are equal to 2Ei and there
is no fixed relation between AB, BC, eta, unless the middle points
126
ELECTRICAL ENGINEERING PAPERS
are interconnected, in which case the e.m.f.'s become the same as
in Fig. 17.
In Figs. 20 and 21 the usual two-phase, three-wire arrange-
ment is shown. In Fig. 20, AB = EI and AC = \/~2~ x EI. In
Fig. 21 AB = 2Ei and AC = 2 x V 2 EI.
Fig .17
CAPACITIES OF TWO-PHASE WINDINGS : Let A equal the cur-
rent per coil, this current being the same as for the three-phase
winding. Then —
In Fig. 15 the capacity equals 4
" "
" "
18
19
20
21
It is obvious therefore that the two-phase capacities are equal for
all the various windings which have been commonly used.
COMPARISON OF TWO-PHASE CAPACITIES WITH THREE-PHASE
As the same winding has been assumed for both two-phase and
three-phase, it is of interest to compare their ratings. Comparing
E and EI in Fig. 22, it may be seen that EI — -\f~2~ x E. Therefore
the two-phase capacities given above, when put in terms of three-
phase e.m.f.'s become, in all cases, 4A x V1T x E = 5.656 AE.
The closed coil three-phase capacity = 5 196 AE. The closed coij
six-phase capacity = 6 AE. The open coil (star or delta) three^
phase capacity = 6 AE. Therefore, the three-phase closed coij
arrangement gives the least output, while the two-phase, (which i$
CAPACITIES OF ALTERNATORS
127
in reality, four-phase with a closed coil winding) gives somewhat
better results and the six-phase closed coil gives still better results.
SINGLE-PHASE RATING FROM TWO-PHASE WINDING
Two of the terminals of the two-phase windings may be used
for single-phase. Assuming the same current A per coil as in
Fig, 19
two-phase or three-phase, then the single-phase capacity
In Fig. 15 = 2A x VT Ei = 2.828 AEi
In Fig. 17 = A x 2El = 2
In Figs 18 and 19 = 2 AEl
In Figs 20 and 21 = 2
becomes
Fig. 2 i
Fig. 22
Comparing the best single-phase obtained from the two-
phase with the best single-phase from the three-phase windings, EI
being equal to V^IT E, the following is obtained •
128 ELECTRICAL ENGINEERING PAPERS
Then 2,828 EiA = 4 AE, or same as obtained from the
six-phase closed coil winding.
Comparing the three-phase closed coil winding with the two-
phase closed coil winding for both polyphase and single-phase
ratings, the following is obtained on the basis of same loss per coil:
The 3-phase closed coil winding gives 3-phase rating of 5 196 AE.
" 3 " " " " " single" " " 2.596
« 2 " " " " " 2 " " " 5. 656 AE
« 2 " " " " " single" " " 4 AE.
It is therefore apparent that with the closed coil winding the
two-phase arrangement (or four-phase in reality) gives higher out-
puts, for both polyphase and single-phase, than the three-phase
closed coil arrangement will give.
It may be of interest to note that in the earlier Westinghouse
polyphase machines, when the single-phase rating of a polyphase
generator was frequently of more importance than the polyphase
rating, the closed coil two-phase winding shown above was gener-
ally used. One reason for the selection of this type of winding was
the high single-phase rating which could be obtained without un-
due sacrifice in the polyphase rating.
SPECIAL CONNECTIONS FOR SINGLE-PHASE
All of the preceding comparisons have had to do with sym-
metrical arrangement of windings. However, by putting on one
or more additional connections, which are used for single-phase
operation purely, the windings can sometimes be made to give
larger single-phase ratings than where the straight polyphase con-
nections are used for single-phase operation. Two such arrange-
ments will be shown below: —
It is shown in Pig. 12 that by taking off single-phase at -A 6, a
high single-phase rating can be obtained. For supplying three-
phase circuits, however, it was stated that transformers would have
to be interposed to transform from six-phase to three-phase.
However, by using A and b as the single-phase terminals and
using A, B and C as the three-phase terminals, thus having four
terminals total on the winding, as shown in Pig. 23, the machine
can supply three-phase directly to the circuit and can also deliver
single-phase with the best utilization of winding. In this case the
three-phase rating equals 5.196 AE and the single-phase rating
-equals 4 AE. The single-phase thus becomes approximately
77 percent of the polyphase. This high relative rating, however,
CAPACITIES OF ALTERNATORS
129
is due to the fact that the three-phase rating is only 86.6 percent
of the maximum three-phase which could be obtained.
In a similar way, with the delta winding shown in Fig. 8, an
improved single-phase rating can be obtained by putting an
additional terminal at the middle of one of the legs, as shown in Fig.
24. The single-phase is then taken off at A and 6, while A, B and C
are the three-phase terminals. In this case two of the delta legs are
almost in phase with the single-phase, while the third leg is prac-
tically idle as far as voltage is concerned, although it carries the
full current. If the e. m. f . of AB is 2E then the e. m f . of AB is
v"~3~ E. The total single-phase current is 2A, Therefore, the
Fig. 24
single-phase rating becomes 3.464 AE. The single-phase rating in
this case is therefore 57.7 percent of the three-phase, instead of 50
percent where the single-phase was taken off at the terminals AB.
The above two arrangements are therefore more effective than
the usual single-phase from the same types of windings. However,
as will be shown later, the true delta and the closed coil three-
phase windings are seldom used on alternating-current generators
and therefore the above special arrangements are of no particular
commercial advantage.
COMPARISON OF ALTERNATING AND DIRECT-CURRENT RATINGS
FROM SAME ARMATURE WINDING
If direct current be taken from the same winding as described,
the limiting current per coil should be the same as the effective
(or square root mean square) current when delivering alternating
130 ELECTRICAL ENGINEERING PAPERS
current. This is the value A used in the preceding comparisons.
The direct-current e. m. f . is taken off from two opposite points of
the armature, This e. m. f . therefore corresponds to the two op-
posite terminals of either the two-phase closed coil or six-phase
closed coil winding shown in the preceding diagrams. The direct-
current e. m. f . will be equal to the maximum or peak value of the
alternating-current e. m f . taken off from these two points This
will be \J~~z times the effective value used in the preceding
comparison.
For the six-phase diametral arrangement, it was shown that
the effective alternating-current e m. f . = IE. Therefore the peak
value of direct-current e. m. f . will be equal to VIT x IE. As the
limiting current is A, and as there are two direct-current branches,
the total direct current will be 2£. The direct-current output
therefore becomes 4 x \/~2~ AE = 5.656 AE.
The following interesting comparisons can therefore be made:
Direct-current capacity = 5 656 AE
1-Phase closed coil capacity =4 AE =70.7% of D C.
3-Phase " " " =5.192 AE =91 8% " "
2 " (4-phase) " " =5656AE =100% " "
6 " " " " =6 AE =1061%u "
3 " open " " =6 AE =1061%" "
From the above it appears that the two-phase closed coil (and
two-phase open coil) capacity is equal to the direct-current capacity
from the same armature winding. The three-phase closed coil is
less than the direct current, while the six-phase is greater than the
direct current. The three-phase true star or delta winding and the
six-phase closed coil winding are all slightly more effective than
when the same winding is used for direct-current.
The question may be raised whether still higher ratings could
not be obtained from a given winding by taking off more phases.
An examination will show that higher ratings can be obtained with
the number of phases increased, with the dosed coil winding; but
it can be shown that the possible increase over the six-phase
arrangement is very small.
An easy way of comparing the ratings of closed cofl windings,
with different numbers of phases, is to compare the number of
circuits which can be taken off between adjacent taps or terminals
all around the winding, as referred to in first paragraph of page 120.
This is equivalent to comparing the perimeters of the poly-
CAPACITIES OF ALTERXATORS
131
gonal figures shown in the diagrams for the various closed coil
combinations and is illustrated in Figs. 25, 26, 27 and 28.
In Fig. 25, calling one side E, than the perimeter = 6E
In Fig.^26, the perimeter = 5.656 E. In Fig 27 the perimeter
= 3 V 3 E = 5,196 E. In Fig. 28, which represents single-
phase, the two sides of the polygon coincide, making a straight line
Therefore, double the length of this line should represent the
perimeter, which = 4E. A comparison of these values shows that
they are exactly in proportion to the alternating-current capacities
given above
\
Fig. 25
Fig. 26
It is evident that the greater the number of phases obtained
from the closed coil winding, the more nearly the perimeter of the
polygon approaches the circumference of the circle. With an infinite
number of phases a true circle would be obtained and in this case
the perimeter becomes 2irE = 6 283 E. Therefore, the maximum
/\ 983
possible polyphase rating is ——== 1.047, or 4.7 percent greater
6.0
than the six-phase closed coil rating or the true star and delta rat-
ing. Also, the greatest possible polyphase rating is greater than the
direct-current rating in the proportion of 6.283: 5.656, or approx-
imately 11 per cent.
FIELD HEATING
In the above comparisons of the relative ratings of the three-
phase, two-phase and single-phase windings, only the armature
copper losses have been taken into account: but if the problem is
to be considered in its completeness, other armature conditions and
the field conditions must also be taken into account.
132
ELECTRICAL ENGINEERING PAPERS
A comparison of the three-phase and two-phase ratings shows
that they are usually so close^together that the field conditions
would probably not exert a controlling influence on the relative
capacities In general, it may be taken that those combinations
of polyphase windings which give lower ratings at the same time
give lower armature reactions.
In comparing single-phase with polyphase ratings, however,
the field conditions, both as regards the field winding and field core,
must be taken into account The armature reaction of the single-
phase winding is pulsating and tends to produce magnetic disturb-
/
\
X
\
1
, 1
\ 2
t
Fig. 2 7
Fig. 28
ances in the field poles or core which may result in very considerable
iron losses, both eddy and hysteretic. In general, these disturb-
ances are relatively much greater on larger capacity machines, so
that provision must be made on such machines for suppressing or
avoiding the ill effects of the armature reaction. This can be
accomplished to some extent, by completely laminating the field
poles. Another method which has been used on very large ma-
chines is the employment of heavy cage damper in the pole faces,
similar to that of the secondary of an induction motor. This damper
must have current capacity such that when developing ampere
turns sufficient to completely neutralize the armature pulsations,
the heating effect in the damper winding, due to the current in it,
is relatively low.
Field copper heating, in most cases, is not a controlling con-
dition, owing to the fact that the single-phase rating, defined by the
armature heating, as indicated above, is so much lower than the
polyphase rating that the field copper is usually worked some-
what easier than on the polyphase loading. This is particularly
CAP A CITIES OF ALTERNA TORS 133
true when the rating is fixed by the heating of individual armature
coils.' However, if the single-phase rating is determined by the
total armature loss and not by the loss in individual coils, then the
permissible armature capacity on single-phase may be such that in
some instances the field copper is worked harder than on polyphase.
In such cases, if the field copper is the limiting condition, then the
single-phase rating cannot be as high as the armature would
permit. It may be assumed, however, that in large machines the
armature conditions, as fixed by the loss in individual coils,
determine the safe single-phase rating; and under this assumption
the field conditions, except in regard to the use of dampers or the
elimination of the effects of armature reaction, need not be con-
sidered.
APPLICATION OF VARIOUS TYPES OF ALTERNATING-CURRENT
WINDINGS
The three-phase true star type of winding is the one which, in
general, lends itself to best advantage to the various types of
alternating-current machinery. It may be a question then as to
why any other types of windings are used. However, it was
intimated , before that where other than the true star winding is
used, there is usually some condition other than the output which
is of first importance. In the following will be given some of the
principal applications of the different types of windings: —
CLOSED COIL TYPES
The closed coil type of winding is always used with rotary
converters. The controlling feature in this case is that the rotary
converter carries a commutator, which naturally requires a closed
coil type of winding. Rotary converters are, in practice, wound
for three-phase as in Fig. 3, four-phase (usually called two-phase) as
in Fig. IS and six-phase as in Figs. 11 and 12; and the number of
collector rings is 3, 4 and 6 respectively. The three-phase winding
is generally used in small capacity rotaries. While the three-phase
winding allows less output than the fofttr-phase or six-phase, on
small rotaries the capacity is usually not limited by the armature
copper loss, while the use of three rings somewhat simplifies the
machines.
Four-phase rotaries are used to a very considerable extent in
connection with two-phase circuits. However, where the supply
134 ELECTRICAL ENGINEERING PAPERS
circuit is three-phase it is rare that the transformation is from three-
phase on the supply circuit to the two-phase on the rotary, as there
are certain disadvantages in such transformation which more than
offset the slight advantage of the four-phase rotary over the three-
phase Moreover, where a higher number of phases is of advantage
in a rotary converter, it is practicable to transform from the three-
phase supply circuit to six-phase for the rotary Two arrange-
ments of such six-phase transformation are in use, as illustrated in
Figs 11 and 12
One of these is the so-called " Double Delta" arrangement, in
which each of the step-down transformer circuits is equipped with
two secondaries, as indicated in Fig 11 These are connected to
form two separate deltas, one being inverted with respect to the
other.
The other arrangement is the so-called "Diametral" arrange-
ment, as shown in Fig 12 This has advantages over the double
delta in that only one secondary circuit is required for each phase
and the middle points of these secondary circuits may be connected
together for a neutral or middle wire between the direct-current
leads from the rotary converter.
In a rotary converter the armature copper loss is generally so
small, compared with that of the straight direct-current or straight
alternating-current machine with the same winding, that all con-
siderations of the comparative heating of three-phase, four-phase
and six-phase windings, as on alternating-current generators, has
practically no bearing on the rotary converter rating. In a rotary
converter, an increase in the number of phases over six represents
a considerable reduction in the armature copper loss, — much more
so than in the closed coil alternating-current generator This is
due, in the rotary converter, to the fact that one armature winding
carries both the direct and the alternating currents, which are to a
certain extent, flowing oppositely.
Closed coil windings are also occasionally used on the second-
aries of induction motors in order to give a better choice in the
number of slots than would be allowed otherwise Such windings
when used on induction motors are usually of the two-circuit or
series type, for the purpose of increasing the voltage as much as
possible and at the same time keeping the number of conductors
as small as possible, while retaining the closed coil arrangement.
A two-circuit closed coil winding will close upon itself symmetrical-
ly if the ntonber of turns or coils is one more or less than a multiple
CAPACITIES OF ALTERNATORS 135
of the number of pairs of poles. This sometimes allows the use
in the secondary of an induction motor, of a number of coils or slots
which has no close numerical relation to the number of primary
slots. For instance, if the primary of a four-pole induction motor
has 48 slots with an open coil, star or delta winding, then with
39 coils and slots in the secondary, a symmetrical closed coil three-
phase winding could be obtained, while if an open coil secondary
were used, the number of slots should preferably be 36 or 42, which
might not be as desirable as 39 in some cases. This simply illus-
trates an occasional use of the closed coil winding.
Closed coil windings were at one time used very extensively on
low voltage, rotating armature, two-phase generators. Such genera-
tors were very satisfactory for delivering a relatively large percent-
age of their rating as single-phase. Furthermore, with one conduc-
tor per slot and with bolted-on end connectors, the potential bet-
ween adjacent end connectors was at all points relatively low. The
symmetrical arrangement of such windings also rendered them
very suitable for use with supporting bands or end bells over the
end winding. However, with the advent of the rotating field ma-
chines, and particularly with the use of higher voltages, the open
coil star winding has entirely superseded the closed coil type of
generator winding.
THREE-PHASE STAR WINDINGS
Two types of star windings have been shown, namely, those in
Figs. 5 and 10. That of Fig. 5 gives less output than that of Fig. 10
in the ratio of 86 6: 100. There would appear therefore to be no
use for the Fig. 5 arrangement; but, in certain cases, in using a
given winding it may be desired to reduce the voltage from 12
percent to 15 percent while retaining normal conditions otherwise.
In such a case the lower voltage could be obtained, if a new winding
were used, by simply chording the winding one-third the pitch.
On the other hand, if an existing winding is to be used, the same
result could be obtained by coupling as in Fig. 5.
In induction motors the arrangement shown in Fig. 5 may be
used occasionally where the windings are arranged for coupling for
two different speeds. In some cases this type of winding may give
better average field distribution for the two numbers of poles
than the one shown in Fig, 10. In this case therefore it is the dis-
tribution of the magnetic field, and not the capacity of the winding,
which is the important feature.
136 ELECTRICAL ENGINEERING PAPERS
The arrangement shown in Fig. 10 is the true star winding
which is used almost universally on three-phase machines. For a
given voltage it requires fewer conductors than any other type of
winding, This is of very material advantage in allowing, with a
given number of slots, a smaller number of conductors per slot,
which, as a rule, allows a better utilization of the star space: —
That is, more copper can be gotten into a given slot. Furthermore,
in relatively high voltage machines where the conductors may be
very large in number and small in size, the star winding with its
smaller number of conductors, each of much larger size, gives more
substantial coils than any other arrangement. Another advantage
of the three-phase winding is its fairly good utilization of copper
when operated on single-phase. When operated on purely single-
phase load, one leg of the star could, of course, be omitted, but if
it is retained it becomes a reserve winding which may be used in
case of an accident to one of the active legs of the winding By
opening any defective coils in an active leg and connecting in the
reserve leg in place of the defective one, the machine can still
develop its specified rating on single-phase.
Another advantage of the star type of winding is the readiness
with which the central or neutral point can be grounded, which is
a very considerable advantage in some high voltage systems.
DELTA TYPE WINDINGS
The true delta type winding, as illustrated in Figs. 7 and 8,
is not used to any great extent in either alternating-current
generators or induction motors. For a given voltage it requires
73 percent more conductors, each of 58 percent of the capacity of
those of the true star type of winding. As the terminals of all three
legs are connected in a closed circuit it is necessary that the e. m. f .'s
generated in the three legs should balance each other at all instants
or there is liable to be circulating current around the windings.
This means that the winding must be applied only where the
conditions are favorable, or the conditions in the design must be
made to suit the type of winding. This winding is occasionally
used on low voltage turbo generators of fairly large capacity, due
to the fact that the delta type winding requires more conductors
than the star type. For example, in a large capacity two-pole
turbo-generator, wound for relatively low voltage, the number^of
conductors for the star winding may be so small that a satisfactory
number of slots is not obtained, even with only one conductor per
CAP A CITIES OF ALTERNA TORS 137
slot and even using the double-star winding, shown in Fig. 9. In
such case a double delta winding will allow 73 percent more con-
ductors and slots than the double star will give. Also, each
conductor will be much smaller than in the star arrangement,
which may be of considerable advantage in the case of low voltages
and very heavy current per conductor.
Delta windings are occasionally used on machines which are
arranged for connection for two different voltages, such as 6600
volts and 11,000 volts. If an armature is wound for star connection
at 11,000 volts, then it can be coupled in delta for 6600 volts with
practically the same inductions, losses, field currents, etc. The
delta type of winding is also used occasionally in the primaries
of induction motors for special purposes, such as multi-speed
combinations where the winding is changed from one number of
poles to another. In general, however, the star type winding is
used on induction motors.
The delta winding is not well adapted for single-phase opera-
tion on account of its low capacity. Also, it does not admit of
grounding of the neutral or central point of the system. Taking
everything into account, the true delta winding is only used where
some special condition is imposed upon the winding which puts
the star arrangement at a disadvantage.
SINGLE-PHASE ALTERNATORS
All the foregoing comparisons have been made on the basis of
the same armature winding being vised for three-phase, two-phase
or single-phase The relations shown do not hold true in general for
machines which are wound initially for single-phase service, such
as for single-phase railway or electro-chemical or electro-fusion
work. In such cases the amount of armature copper used and its
distribution are such that the armature coils, either individually or
as a whole, do not determine the true Emits of output; but the
armature as a rule can carry anything that the field winding will
stand, so that the field temperature becomes the true limit in such
machines. Also, very massive, well distributed cage dampers are
used with such machines when they are of large capacity and these,
in turn, have a certain effect on the characteristics, such as the
regulation, and thus have an indirect influence on the permissible
capacity. It is well known that if the inherent regulation of an al-
ternator is made poorer, the capacity can usually be increased with
the same limiting field temperature. In large single-phase gener-
138 ELECTRICAL ENGINEERING PAPERS
ators, especially for railway service, the capacity is increased by
sacrifice in the inherent regulation of the machine. However, the
massive dampers greatly improve the regulation for quick changes
in load; while the poorer inherent regulation only affects the
regulation over considerable intervals of time, and automatic
regulators, acting on the alternator excitation, readily take care of
the slow fluctuations. In consequence, single-phase generators of
large capacities may be built for ratings which bear no definite
relation to any of those given above.
The armature windings of single-phase generators, when ar-
ranged for single-phase purely, are frequently distributed over
only part of the surface. Usually they cover considerably more
than half the surface, and in extreme cases they cover 80 percent
or more. Of course, when spaced like a true three-phase winding
they cover two-thirds the surface. This arrangement admits of an
extra leg being added to the winding, which is normally idle, if the
winding is connected in star, this leg being a reserve in case of
accident, as mentioned before. However, when such a leg is not
added, the winding generally covers more than two-thirds the
surface, rather than less, but rarely covers the whole surface.
DAMPERS ON LARGE SINGLE-PHASE GENERATORS
FOREWORD — This formed part of the discussion of a paper presented
before the Institute of Electrical Engineers, December, 1908,
by Mr. Murray, describing the operation of the New Haven
single-phase railway. The effect of the addition of the massive
dampers on the rotors of the New Haven generators was so
pronounced, and the results were so beneficial, as a whole, that
it was considered advisable to publish it as new and interesting
material, in the form of a discussion of Mr. Murray's paper.
Immediately after the publication of this, heavy dampers were
adopted very generally by manufacturers of large single-phase
generators, throughout the world, who had encountered more or
less trouble of the same nature as found in the New Haven
generators. Practically all large single-phase generators since
then have been built with such dampers as part of their con-
struction.— (ED.)
WHEN the New Haven single-phase generators were put on.
load test, the first, and most pronounced, difficulty was in
heating, not in the winding, but in the field or rotor structure, due
to the pulsating reaction of the armature winding when carrying a
heavy load in single-phase current. This reaction was known
previously to building these machines, but on machines of smaller
capacity it had not developed destructive tendencies. It was
proved later that this was simply because it had not been tried out
under the conditions which would develop its most harmful
effects. This pulsating armature reaction may be analyzed in the
following manner :
Consider the armature winding as a magnetizing coil fixed
in (Space and carrying an alternating current. This coil may
be considered as setting up an alternating field fixed in space.
For analysis, this alternating-current field, fixed in space, may be
considered as made up of two constant fields of half value, rota-
ting in opposite directions at the synchronous speed of the machine.
One of these fields therefore rotates at the same speed and in the
same direction as the rotor. The other field is traveling round the
rotor core in the direction opposite to its rotation. This field may
therefore be considered as equivalent to one fixed in space with
the rotor running in it at double speed. This core thus becomes
an armature core subject to a heavy induction at a high frequency*
139
140 IELECTRICAL ENGINEERING PAPERS
When the first rotor was built, the structure was laminated as
completely as mechanical conditions would permit. However, in
the case of high-speed turbine-generators of very large capacity, it
is almost impossible completely to laminate everything, due to the
fact that the mechanical requirements call for rigidity in some of
the structural features. Upon testing the first machine it was
found that there was local heating, with heavy load, sufficient to
create hot spots in the core; and in a comparatively short time in
turn these hot spots damaged the insulation on the coils from the
outside, thus causing grounds on the winding. As soon as this was
noticed, an effort was made to eliminate these hot spots ; but it was
found, after several attempts, that as soon as one was eliminated
others would show up in some different place as soon as a higher
load condition was reached. It was evident, after considerable
work had been done, that the correct remedy was not being applied
to this trouble It was then decided to take a bold step by at-
tempting to eliminate all pulsating reactions from the armature by
putting a short-circuited winding on the rotor, of such value that
a very large current could flow in it with but very little loss. It
was the idea to damp out the field in very much the same way that
the armature of a polyphase alternator will demagnetize, or kill its
magnetic field, if the armature terminals are all short-circuited
together. It is known that under this condition the armature
current will rise to such a value that the field flux is practically
eliminated. In order to maintain this condition indefinitely
without overheating, it is only necessary to put enough copper on
the armature so that the PR losses in it under this condition are
within the temperature capacity of the windings. Working on
this theory, a complete cage winding was placed on one of the
rotors of the New Haven generators. This rotor had not been
designed originally for this purpose, and it was therefore difficult
to adopt the most suitable proportions in this winding, but what
was put on, immediately showed in practice that a practicable
remedy had been applied for this trouble Meanwhile the new
rotors designed for the application of heavy cage windings were
under construction, and upon the installation of these, the field or
rotor trouble all disappeared. It is interesting to note that the
fourth machine installed, which has a 4260 kilovolt-ampere single-
phase rating, has a solid steel core, in the surface of which the
copper cage winding is embedded. As this winding completely
eliminated the pulsating armature reaction, there was no further
DAMPERS ON SINGLE-PHASE GENERATORS 141
occasion for laminating the field as a protection from magnetic
pulsations.
I might add that a number of the earlier tests, leading up to
the design of the first New Haven rotors, were misleading, in the
fact that turbine-generators were used for obtaining the prelimin-
ary data for single-phase operation and, in all cases, the machines
had solid steel cores. These cores acted as dampers to a certain
extent, and this in itself eliminated part of the pulsation. It thus
developed afterwards, that in the very act of lamination to avoid the
trouble, we had gotten into it deeper.
Practically all this work on the generators was done before
the full electric service was established, and while only one or two
generators were required to be operated at one time. With one
generator running, there was apparently but little or no disturb-
ance due to short-circuits on the system. As the service was in-
creased and two generators put in operation, the effect of short-
circuits became more pronounced. When, in June, 1908, the entire
electric service was established, and three generators were con-
nected to the system, it soon became evident that there was some
serious condition existing in the system, as indicated by the ex-
tremely violent shocks to everything in case of a short-circuit.
This was particularly noticeable in the switching system, and, as
Mr. Murray intimates, in the case of a short-circuit, all the
switches in the system felt it their duty to jump in and open the
circuit. This indicated an abnormal current condition. It was
calculated that these machines would give possibly six or seven
times full-load current on the first rush, in the case of a dead short-
circuit, this excess current dying down to possibly two or three
times normal full-load current. All indications were, however,
that this current was being greatly exceeded, and therefore a
series of oscillograph tests were made to determine the current
rush when the lines were purposely short-circuited tinder various
conditions. These tests indicated that under certain conditions
each machine could give, at the moment of short-circuit, almost
5000 amperes on one phase, the normal full-load current being 340.
With three machines in parallel, this would therefore mean that
approximately 15,000 amperes could be delivered momentarily.
This enormous current rush was sufficient to explain many of the
difficulties, but this was not all the explanation. The oscillo-
graph tests also showed that this short-circuit current would be
maintained at almost its maximum value for a very considerable
142 ELECTRICAL ENGINEERING PAPERS
period, due to the cage winding on the rotors of the generators.
Apparently this current at the first rush, was not appreciably
greater than that on the machine before the dampers were added,
but without the dampers the field was killed more quickly by this
enormous current, so quickly that apparently the breakers did not
open until the current had fallen somewhat. However, with the
heavy cage winding on the field structure, secondary currents were
set up in this winding, tending to maintain the field strength, and
thus the current rush was maintained at almost full value for
possibly 20 to 30 alternations. These oscillograph tests indicated
very clearly that the armatures of these generators did not have
nearly so great internal self-induction as our calculations indicated.
Meanwhile, the generators in the power house had been suf-
fering from the tremendous shocks which accompanied short-
circuits on the line. There is necessarily considerable local field
around the end-windings of all these machines, and this stray
field is especially large on machines with a small number of poles,
and, in consequence, high ampere-turns per pole. These stray
fields at the ends tend to exert a bending or distorting effect on the
end-windings. In any given machine the distorting force varies
as the square of the current carried by the coils. Our experience
with the windings on these machines indicated that they were
being subjected to enormous forces in the end-windings. The
oscillograph tests gave an indication as to the amount of this
force. As the machines could give about IS times full-load cur-
rent momentarily on short-circuit, the force acting on these end-
windings would be 225 times normal; in this case, therefore, these
forces were so great that it became a serious problem to devise a
type of bracing on the end-windings sufficient to withstand such a
force. It should also be borne in mind that probably as many
short-circuits came, in one day, on these generators, as the or-
dinary high-voltage power-house generator is called upon to
sustain in one year. While ninety-nine shocks out of a hundred
might not be sufficient to do damage, yet if the shocks occur fre-
quently enough, the hundredth one will soon be reached. In our
endeavors to support these windings against movement, probably
the most complete system of bracing ever applied to alternating-
current generators was developed and used on these machines.
But in spite of this there was evidence of movement at times,'
It thus became evident that some method of limiting this short-
circuit current to the value originally intended; namely, about
DAMPERS ON SINGLE-PHASE GENERATORS 143
six times full-load current, would have to be applied. This was
done by placing an unsaturated choke-coil, or impedance coil, on
the trolley side of each machine This coil takes up a comparatively
small voltage tinder normal operation, but in case of a short-
circuit, the electromotive force generated in it is sufficient to limit
the current rush to less than half the value it would attain without
this coil Thus as the shock on the end-windings of the generators
varies as the square of the current, it is evident that cutting this
current in half would cut the shock to one-quarter of its former
value, which, with the method of bracing used on these machines,
would mean the difference between good and bad.
When these choke-coils were installed, the results on the
power house were evident The shocks on the machines were very
greatly reduced, so reduced that we do not fear future trouble
from this source. It is interesting to note that No. 4 machine;
that is, the 4260 kilovolt-ampere generator, referred to before,
was put in service a considerable time before the choke-coils were
installed, and it went through the most severe short-circuits ever
encountered on this system. Its armature winding has never
shown any distress. This is partly because, in the design of this
machine, the difficulties to be overcome were known, and the
remedies could be applied in the most suitable manner.
An interesting point in connection with the use of the cage
windings on these generators, is that the apparent regulation of the
system has been improved. This was anticipated, but the actual
result in practice was more pronounced than was expected. In
installing new rotors for these machines with the heavier cage
dampers, the inherent regulation of the generators was made
somewhat poorer than before, partly in order to accommodate
certain structural features in the rotor. It was anticipated that
the cage winding with its damping effect would, to a certain
extent, mask this poor regulation by making the machine sluggish
as regards fluctuation in voltage with sudden variations in load.
In practice it was found that, with the later rotors with their
poorer inherent regulation, the average regulation of the system
was considerably better than before, thus indicating that most of
the disturbances in the voltage, when the old rotors were used,
were due to sudden changes in load, while the slow variations
were taken care of by the automatic regulators. With the new
rotors the voltage changes are so slow, that the Tirrill regulator
144 ELECTRICAL ENGINEERING PAPERS
has plenty of time to act before any serious disturbance can take
place.
It must be borne in mind that in one way this New Haven
power-house installation was more difficult than anything under-
taken heretofore, and that is, in the use of 11,000 volt generators
with one terminal connected directly to ground Taking this
condition into account, together with the enormous current
rushes with consequent shocks on the winding, and the single-
phase operation of units of such large capacity, it may reasonably
be claimed that this was the most difficult case of alternating-
current generation ever undertaken.
DEVELOPMENT OF A SUCCESSFUL DIRECT-CURRENT
2000 KW UNI-POLAR GENERATOR
FOREWORD— In 1906, the Westinghouse Company contracted to
build a 2000 kw uni-polar type generator direct coupled to a
1200, revolution steam turbine. Many difficulties were en-
countered in shop tests on this machine, winch were apparently
corrected, but upon installation and operation on the customer's
premises, many new and totally unexpected difficulties arose.
This paper illustrates how a responsible manufacturing com-
pany will throw its whole engineering and manufacturing en-
deavors into correcting serious difficulties. It also serves to give
student engineers a good idea of the practical side of manufac-
turing engineering. Fearing the results of the engineering
efforts expended on this machine would eventually be lost, the
author prepared them for presentation at the twenty-ninth
annual convention of the American Institute of Electrical
Engineers at Boston, June, 1912. — (ED.)
THIS paper is not intended to be a theoretical discussion of
the principles of unipolar machines; neither is it a purely
descriptive article. It is a record of engineering experiences
obtained, and difficulties overcome, in the practical development
of a large machine of the unipolar type. Some of the conditions
of operation, with their attendant difficulties, proved to be so
unusual that it is believed that a straightforward story of these
troubles, and the methods for correcting them, will be of some
value.
Two theoretical questions of unipolar design have come up
frequently; (1) whether the magnetic flux rotates or travels
with respect to the rotor of the stator; and (2) whether it is
possible to generate e.m.fs. in two or more conductors in series
in such a way that they can be combined in one direction, with-
out the aid of a corresponding number of pairs of collector rings,
to give higher e.m.fs. than a single conductor.
To the first question the answer may be made that in the
machine in question, it makes no difference whether the flux
rotates or is stationary; the result is the same on either assump-
tion. To the second it may be said that when the theory of inter-
linkages of the electric and magnetic circuits is properly con-
sidered, it is obvious that the resultant e.m.f . is always equivalent
to that of one effective conductor. It has been proposed in the
145
146
ELECTRICAL ENGINEERING PAPERS
past, by means of certain arrangements of liquid conductors in
insulating tubes, to add the e m fs of several conductors in series
but such a scheme does not appear to be a practical device There-
fore, the theoretical considerations being largely eliminated, the
author confines himself to the practical side only.
In 1896 the writer designed a small unipolai generator of
approximately three volts and 6000 amperes capacity at a
speed of 1500 rev. per mm. This machine was built for meter test-
ing and the occasion for its design lay in the continued trouble
encountered with former machines of the commutator type
designed for very heavy currents at low voltages.
The general construction of this early machine is shown in
Fig. 1. The rotating part of this machine consisted of a brass
casting, cylindrical shaped, with a central web, very similar
to a cast metal pulley. The two
outer edges of this pulley or ring
served as collector rings for col-
lecting the current as indicated
in the figure, while the body of the
same ring served as the single
conductor. The object of this
construction of rotor was to obtain
a form which could be very quickly
renewed in case of rapid wear, as
this arrangement would allow a
small casting to he made and simply turned up to form a new-
rotor. However, this renewal feature has not been of very
great importance for the rotor of the first machine was replaced
only after 12 years' service. This period of course did not
represent continuous service, for this particular machine was
used for meter testing purposes or where large currents were
required only occasionally,
A number of peculiar conditions were found in this machine.
In the initial design the leads for carrying the current away
from the brushes were purposely carried part way around the
shaft in order to obtain the effect of a series winding by means
of the leads themselves. In practice, they were found to act in.
this manner and, in fact, they over-compounded the machine
possibly 30 to 40 per cent. In consequence, it was necessary
to shunt them by means of copper shunts around the shaft in
ihe opposite direction.
FIG. 1
UNI-POLA R GENERA TOR 147
Shortly after this machine was put in operation there was con-
siderable cutting of the brushes and rings, especially at very
heavy currents. It was found that block graphite, used as a
lubricant, gave satisfactory results. This machine was operated
up to 10,000 to 12,000 amperes for short periods.
The description of the above machine has been gone into rather
fully, as it was a forerunner of the 2000-kw. machine which will
be described in the following pages. The general principle of
construction and the general arrangement of the two parts, or
paths, of the magnetic circuit are practically the same in the two
machines, as will be shown.
In 1904, due to the rapidly increasing use of steam turbines,
the question of building a turbo-generator of the unipolar type
was brought up, and an investigation was made by the writer
to determine the possibilities. This study indicated that a
commercial machine for direct connection to a steam turbine
could be constructed, provided a very high peripheral speed was
allowable at the collector rings or current collecting surfaces. It
appeared that the velocity at such collector surfaces would have
to be at least 200 to 250 feet per second, in order to keep the
machine down to permissible proportions of the magnetic
circuit, and to allow a reasonably high turbine speed. Con-
trary to the usual idea, the very high speeds obtainable with
steam turbines are not advantageous for unipolar machines.
For example, while maintaining a given peripheral speed at the
current collecting surface, if the revolutions per minute of the
rotor are doubled, then the diameter of the rotor collecting
rings is halved, and the diameter of the magnetic core surrounded
by the collector rings is more than halved, and the effective
section of core is reduced to less than one-fourth. The e.m.f.
generated per ring or conductor, therefore, on the basis of flux
alone, would be reduced to less than one-fourth, but allowing
for the doubled revolutions per minute, it becomes practically
one-half.
On the other hand, if the revolutions are reduced, while the
speed of the collector ring is kept constant, then the e m.f .
per ring can be increased, as the cross section of the magnetic
circuit increases rapidly with reduction in the number of revo-
lutions. But-at a materially reduced speed, the total material
in the magnetic circuit becomes unduly heavy. In consequence,
if the speed is reduced too much, then the machine becomes too
large and expensive, while with too great an increase in speed,
148
ELECTRICAL ENGINEERING PAPERS
the e,m.f. per ring becomes low or the peripheral speed of the
rings must be very high. It is desirable to keep the number
of collector rings as small as possible, for each pair of rings handles
the full current of the machine, and therefore any increase
in the number of rings means that the full current must be col-
lected a correspondingly large number of times. Therefore,
it works out that the range of speeds, within which the unipolar
machine becomes commercially practicable, is rather narrow.
In 1906, an order was taken for a2000-kw. 1200-rev.permin.,
260-volt, 7700-arnpere unipolar generator to be installed in a
Portland cement works near Easton, Pa. The fact that it is
a cement works should be emphazised, as having a considerable
bearing on the history of the operation of this machine, as will
be shown later*
jnnnnnn nn
PIG. 2
This 2000-kw. machine does not represent any theoretically
radical features, being similar in type to the smaller machine
already described, but modified Somewhat in arrangement to
allow the use of a large number of current paths and collector
rings. The general construction of this machine is indicated
in Fig. 2.
The stator core and the rotor body are made of solid steel,
the stator being cast, while the rotor is a forging. There are
eight collector rings at each end of the rotor, the corresponding
rings of the two ends being connected together by solid round
conductors, there being six conductors per ring, or 48 con-
ductors total. In each conductor is generated a normal
e.m.f. of 32.5 volts, and with all the rings connected in series,
the total voltage is 260.
The stator core, at what might be called the pole face, is built
UNI-POLAR GENERATOR
149
up of laminated iron, forming a ring around the rotor. This
was laminated in order to furnish an easy method for obtaining
the stator slots in which the conductors lie which connect to-
gether the brushes or brush holders for throwing the pairs of
rings in series. The slots in the stator laminations were made
open, as-indicated in Fig. 3, in order to readily insert the stator
conductors. There are 16 slots in this ring, and in each slot
there is placed one large solid conductor.
As first assembled, non-metallic wedges were used to close
these slots, but later these were changed to cast iron for reasons
which will be explained later.
The rotor core consists of one large forging, as indicated in
Fig. 2. Lengthwise of this rotor are 12 holes for ventilating
FIG. 3
FIG. 4
purposes originally 2f in. diameter. Each of these holes con-
nected to the external surface by means of nine If in. radial
holes at each end of the rotor, these holes corresponding to mid-
positions between the collector rings. It was intended to take
air in at each end of the rotor and feed it out between the collec-
tor rings for cooling. In addition, as originally constructed,
there was a large enclosed fan at each end, as indicated in Fig.
4. These fans took air in along the shaft and directed it over
the collector rings parallel to the shaft. The object of this was
to furnish an extra amount of air for cooling the surfaces of the
rings, and the brushes and brush holders, as it was estimated
that the brushes and brush holders themselves could conduct
away a considerable amount of heat from the rings by direct
150
ELECTRICAL ENGINEERING PAPERS
contact, and that the cooling air from the fans, circulating among
the brush holders, would carry away this heat. These fans
were removed duriag the preliminary tests, for reasons which will
be given later.
The rotor collector rings consisted of eight large rings at each
end, insulated from the core by sheet mica, and from each other
by air spaces between them. Each ring has 48 holes parallel
to the shaft. These holes are of slightly larger diameter than
FIG. 5
the rotor conductors outside their insulation. Six holes in
each ring were threaded to contain the ends of six of the conduc-
tors which were joined to each ring. The six conductors con-
nected to each ring were spaced symmetrically around the core.
Fig. 5 shows this construction.
The rotor conductors, 48 in number, consist of one in. copper
rods, outside of which is placed an insulating tube of hard ma-
terial. Each conductor, in fact,- consists of two lengths arranged
for joining in the middle. The outer end of each conductor
is upset to give a diameter
larger than the insulating tubes, ,
and a thread is cut on this ex- ~~
panded part. After th^ rings
were installed on the core, the
rods were inserted through the E
holes to the threaded part of a
ring and were then screwed pIG. 5
home.
At the middle part of the rotor core, a groove is cut as shown
in Fig. 6. Into this groove the two halves of each conductor
project. These two ends are then connected together by strap
conductors in such a way as to giye flexibility in case of expan-
sion of the conductors lengthwise. This arrangement is also
shown in Fig. 6.
With this arrangement there is no possibility whatever of
the conductors turning after once being connected. There is
U SI-POLAR GENERATOR
151
a series of holes from the axial holes through the shaft to this
central groove, for the purpose of allowing some ventilating air
to flow over the central connections.
As originally constructed, the conductors passed through com-
pletely enclosed holes near the surface of the rotor core, as in-
dicated in Fig. 7. This construction was afterwards modified
to a certain extent. The face of the rotor at this point was also
solid, as originally constructed. This was afterwards changed,
as will be described later.
The collector rings, as originally constructed, consisted of
a base ring with a wearing ring on the outside, as shown in Fig.
8. Both rings were made of a special bronze, with high elastic
limit and ultimate strength. On the preliminary tests these
rings showed certain difficulties and required very considerable
modifications, and several different designs were developed
during the preliminary operation, as will be described.
FIG. 7
iffiSSizzrXTA
FIG. 9
FIG. 8
The eight sets of brush holders at each end are carried by
eight copper supporting rings. These supporting rings are
insulated from the frame of the machine but are connected in
series by means of the conductors through the stator slots.
There are 16 brush holders studs per ring and two brush holders
per stud, each capable of taking a copper leaf brush f in. wide
by If in. thick. These. brush holders are spaced practically
uniformly around the supporting rings. The supporting copper
rings are continuous or complete circles, so that the current
collected from the brushes are carried in both directions
around the ring. There are two conductors carried from each
ring through the stator slots to a ring on the opposite side of the
machine, in order to connect the various brush holders in series.
The arrangement is illustrated in Fig. 9,
The above description represents the machine as originally
152 ELECTRICAL ENGINEERING PAPERS
constructed and put on shop test. From this point on, the
real story begins. Various unexpected troubles developed, each
of which required some minor modification in the construction of
the machine and, moreover, these troubles occurred in series*
that is, each trouble required a certain length of time to de-
velop, and each one was serious enough to require an immediate
modification in the machine. In consequence, the machine
would be operated until a certain -difficulty would develop; that
is, that trouble would appear which took the least time to de-
velop. After it was remedied, a continuation pf the test would
show a second trouble which required a remedy, and so on.
Some of these troubles were of a more or less startling nature
as will be described later.
This machine, after being assembled according to its original
design, was operated over a period of several weeks in the testing
room of the manufacturing company. It was operated both
at no load and at full load, and a careful study was made of all
the phenomena which were in evidence during these tests.
The machine was first run at no-load without field charge
to note the ventilation, balance, and general running conditions
of the machine. The ventilation seemed to be extremely good,
especially that due to the fans on the ends o£ the shaft. The
noise, however, was excessive — so much so that anyone working
around the machine had to keep his «ars padded. At first it
was difficult to locate the exact source of this noisfe, but it was
determined that the end fans were responsible for a considerable
part of it.
On taking the saturation curve of the machine, it was found
to be extremely sluggish in following any changes in the field
current. The reason for this sluggishness is obvious from the
construction of the machine, each magnetic circuit of the rotor
core being surrounded by eight continuous collector rings of
very heavy section, and also by eight brush holder supporting
rings of copper of very low resistance. These rings, of course,
formed heavy secondaries or dampers which opposed any change
in the main flux. The total effective section of these rings was
equivalent in resistance to a pure copper ring having a section
of 49 sq. in. One can readily imagine that such a ring would be
very effective in damping any sudden flux changes. This slug-
gishness of the machine to changes in flux, however, was not
an entirely unexpected result*
The saturation curve showed that the machine could be carried
UNI-POLAR GENERATOR 153
considerably higher in voltage than originally contemplated, for
apparently the magnetic properties of the heavy steel parts
were very good, and it was possible to force the inductions in
these parts to much higher density than was considered prac-
ticable in working out the design. This gave considerable lee-
way for changes which later were found to be necessary.
In taking the saturation curve, the power for driving the
machine was measured and it was found that there were prac-
tically no iron losses in the machine; that is, at full voltage
at no-load the total measured losses were practically the same
as without field charge. This apparently eliminated one pos-
sible source of loss which was anticipated, namely, that due to
the large open slots in the stator pole face, these slots being very
wide compared with the clearance between the stator and rotor
After completion of this test the machine was then run on
short circuit Apparently, as there was no iron loss shown in
the no-load full voltage condition, the short circuit test with full
load current should cover all the losses in the rotor which would
be found with full" load current at full voltage. Experience
afterward proved this assumption to be correct, for in its final
form the machine would operate under practically the same
condition as regards temperature, etc., at full voltage as it would
show at short circuit, carrying the same current, the principal
difference being the temperature of the field coil.
It was in this short circuit temperature run that the real
troubles with the machine began. The measured losses, when
running on short circuit, were somewhat higher than indicated
by the resistance between terminals times the square of the
current. These extra losses were a function of the load and
increased more rapidly with heavy currents. The measured
power indicated that these excess losses were principally due to
eddy currents. However, the total losses indicated in these
preliminary tests, although somewhat higher than calculated,
were still within allowable limits, as considerable margin had been
allowed in the original proportions to take care of a certain
amount of loss. It was therefore considered satisfactory to go
ahead with the short circuit tests, and in making these it was
the intention to operate long enough to determine the neces-
sary running conditions as regards lubrication, heating, etc.
As mentioned before, the original collector rings of the machine
each consisted of a base ring upon which was mounted a second-
ary or wearing ring, it being the intention to have this latter
154 ELECTRICAL ENGINEERING PAPERS
ring replaceable after it was down to the lowest permissible
thickness, as it would be rather expensive and difficult to replace
the base ring which carried the rotor conductors. As the inner
*ing was shrunk on the core and the outer ring was shrunk on
over the base ring, with a very small shrinkage allowance, it
was considered that the outer ring was in no danger of loosening
on the inner ring, especially as both rings, being of bronze, and
in good contact, should heat each other at about the same rate.
This assumption, however, was wrong. The machine was put
on short circuit load of about 8000 amperes early one evening
and an experienced engineer was left in charge of it until about
midnight. Up to that time the machine was working perfectly,
with no under heating in the rings and no brush trouble, although
vaseline lubrication was used. About midnight the engineer
left the machine in charge of a night operator, and at about three
o'clock in the morning this operator saw the brushes beginning
to spark and this very rapidly grew worse, so that in a very few
minutes he found it necessary to shut
the machine down. An examination
then showed that several of the outer
rings had shifted sideways on the base
ring, as indicated in Fig. 10. One of
these rings had even moved into contact
with a neighboring ring so as to make FIG. 10
a dead short circuit on the machine. It
was also noted that all the rings which loosened were on one side
of the machine, and that the surfaces of the rings exposed to
the brushes were very badly blistered. The brushes also were
in bad shape, indicating that there had been excessive burning
for a short time. An investigation of the loose rings showed
that they had loosened on their seats on the inner or base rings.
Investigation then showed that a temperature rise of 70 to 80
deg. cent., combined with the high centrifugal stresses, would
allow the rings to loosen very materially. It was then assumed
that as the ring had heated up, bad contact had resulted be-
tween the inner and outer rings and this, in turn, had caused
additional heating, so that the temperature rose rather suddenly
after bad contact once formed. It developed later that this
was probably not the true cause of the trouble, but at the time
it was considered that the remedy for the trouble was in the
tise of rings which could be shrunk on with a greater tension.
It was then decided to try steel outer rings instead of bronze
UNI-POLAR GENERATOR 155
on the end where the bronze rings had loosened. However, upon
loading the machine, after applying the steel rings, a new diffi-
culty was encountered. It was found that the loss was very
greatly increased over that with the bronze rings. This loss
was so excessive as to be prohibitive, as far as efficiency was
concerned, and also the tests showed excessive heating of the
rings and of the machine as a whole. Also, there were continual
small sparks from the tips of the brushes, these sparks being
from the iron itself, as indicated by their color and appearance.
However, during the time these rings were operated there did
not seem to be any undue wear of either the brushes or the rings,
but obviously there was continued burning, as indicated by the
sparks. With thes,e steel rings it was found to be impossible
to operate continuously at a current of 8000 amperes, due to
the heating of the steel rings in particular and everything in
general. At a load of 6000 amperes the loss was materially re-
duced and it was possible to operate continuously but with very
high temperatures. The tests showed that,
with the steel rings, at full rated current, the
loss was approximately 200 kw. greater than
with the bronze rings, or about 10 per cent
of the output. With both ends equipped
_ with steel rings, this would have been prac-
FIG 11 tically doubled.
While this was recognized as an entirely
unsatisfactory operating condition, yet it allowed the machine to
be run for a long enough period to determine a number of other
defects which did not develop in the former test. One of these
defects was an undue heating of the rotor pole face. This was
obviously not due directly to bunching of the flux in the air gap
on account of the open stator slots, for this heating did not appear
when running with normal voltage without load. Further investi-
gation showed that this was apparently due to some flux dis-
torting effect of the stationary conductors in the stator slots,
which carried about 4000 amperes each at rated load. On
account of ample margin in the magnetizing coils the air gap
was then materially increased, with some benefit. A further
improvement resulted in the use of magnetic wedges, made of
cast iron, in place of the non-magnetic wedges used before.
These wedges are illustrated in Fig. 1 1 . This produced a further
beneficial effect, but there was still some extra heating in the
pole face. Cylindrical grooves alternating $ in. and 1 in. deep
156
ELECTRICAL EXGIXEERIXG PAPERS
and about J in. wide, with a J ia. web of steel between, were
then turned in the pole face. The resultant pole face was there-
fore crudely laminated, as shown in Fig. 12. Also, on account
of an apparent local heating of the metal bridge over the rotor
slots, a narrow groove was cut in the closed bridge above each
rotor slot, thus changing it to a partially open slot, as shown in the
figure. This effectively eliminated the excess loss in the rotor
pole face. This, however, led to another unexpected difficulty,
which will be described later.
After this trouble was cured, the short circuit test was con-
tinued with a current of about 6000 amperes. After a con-
siderable period of operation, a very serious difficulty in the
operation of the machine began to show up? namely, trouble
with lubrication. At first the lubrication was vaseline fed on
to the rings by lubricating pads. This was apparently very
effective for awhile, but eventually it was noted that slight
sparking began, which, in some cases, would increase very
rapidly and, in a comparatively
short time, became so bad that
the rings or brushes would be-
come badly scored or blistered.
Examination of the sparking
brushes showed a coating of black
" smudge " over the surface which
seemed to have more or less in-
sulating qualities, A series of tests then showed that when-
ever sparking began, the contact drop between a brush and the
collector ring was fairly high and this drop increased as the spark-
ing increased. For instance, it was found that on good, clean
surfaces, the voltage drop between the brushes and the ring
might be 0.3 to 0.5 volt. As each brush carried about 250
amperes at full load, this represented 75 to 125 watts per
brush. When this contact resistance rose to about one volt,
noticeable sparking would begin-, the watts being, of course,
proportionally higher, afid when the contact drop became as high
as two volts, representing about 500 watts per brush, very bad
burning of the brushes and rings was liable to occur. A series
of tests then showed that vaseline, or any other lubricating oil,
would tend to form a coating over the brush contact and this
coating would gradually burn, or be acted upon otherwise by
the current, so that its resistance increased and the black
smudge was formed which had more or less insulating qualities.
FIG. 12
VXI-POLAR GENERATOR 157
A great number of tests were then carried out with various
kinds of lubricants and it was found that anything of an dil
or grease nature was troublesome sooner or later, as the smudge
was formed on the brush contact. Then graphite, formed into
cakes or brushes by means of high pessure, was tried on the rings
and the results were very favorable compared with anything
used before. In fact, the tests indicated that soft graphite
blocks or brushes could furnish proper lubrication for the rings.
The graphite is a conducting material, and a coating of it on
the brush contact does not materially increase the resistance
of the contact. This was supposed to have practically settled
the question of lubrication and brush contact trouble, but ex-
perience later gave an entirely new turn to this matter.
While these tests were being carried on, a study of the ventila-
tion of the machine was being made. Tha tests indicated that
the end rings, that is, those next to the exciting coils, were con-
siderably cooler than those near the center of the machine.
However, as there were excessive losses and heating in the steel
rings themselves, it was not possible to make any material im-
provement until the rings were changed.
The steel rings at one end of the rotor, and the bronze rings
at the other end, were then removed and a second set of bronze
rings was tried. These rings were specially treated in the manu-
facture so that the elastic limit was very high, and they were
put on much tighter than in the former case. The load tests
were then continued and the excess losses were agaia measured
at various loads. It was found that the losses were very small
compared with those of the steel rings, thus verifying the former
results. The temperatures of the rings were much lower than
with the steel, but it was found that the heating of the rings war
unequal. It was finally determined that this unequal heating was
due to the large external blowers which were driving the air over
the rings in such a way as to heat those next to the center of the
rotor to a much higher temperature than those at the outer
ends. It was assumed at first that the air entering the axial
holes through the core and blowing out between the rings as
shown in Fig. 4, was more effective on the outer rings, and that
this possibly caused the difference in temperatures. However,
the radial holes at the outer ends were dosed, and this made
but little difference. The axial holes were then closed, and
while the temperattires of the rings, as a whole, were increased,
about the same difference as before was found between the end
rings and the center ones.
158 ELECTRICAL EXGIXEERIXG PAPERS
It was then decided to remove the two large bloxvers to de-
termine whether some other method of ventilation would be
more effective. \Vhen this change was made the windage of
the machine was greatly reduced and there was greater uni-
formity in the temperatures and the average temperature of
the rings wasonly about 10 deg. higher than with the fans. More-
over, the windage loss was only about one-seventh as great as
before, although the average temperature rise was not much
higher, which indicated that the ventilation through the rotor
holes was much more effective than that due to the blowers.
In consequence, it was decided to increase the size of the axial
holes through the rotor core from 2f in. to 3f in. diameter, and
to " bell-mouth " them at their openings at the ends, in order
to give a freer admission of air to the holes. When this was done
it was found that the temperatures of the rings were lower than
in any of the preceding tests, and moreover, they were fairly
uniform. Also after the removal of the blowers, the objection-
able noise, already referred to, was largely eliminated, so that it
was not disagreeable to work around the machine. The graphite
lubrication was continued "with the bronze rings, on this test,
and no difficulty was encountered, although the machine was
operated for very considerable periods at approximately 8000
amperes.
On the basis of these tests, the machine was shipped to its
destination and put in service. Then the real difficulties began —
difficulties which were not encountered in the shop tests, princi-
pally because the conditions under which the machine operated
in service were radically different from those at the shop, and
also, because the shop test had not been continued long enough.
This machine was operated in service, although not regularly,
for a period of about two months, being shut down at times due
to difficulties outside of the generating unit itself. However,
this period of operation of the generator was suddenly ended
by the stretching of one of the outer collector rings, which
loosened it to such an extent that it ceased to rotate with the
inner ring. This required the return of the rotor to the manu-
facturer. ,
This two months' operation gave data of great practical
value, and in consequence, a number of minor difficulties were
eliminated in the repaired rotor.
Upon the return of the rotor to the shop, an examination of the
collector rings showed that the separate shrtmk-on type of ring
USI-POLAR GENERATOR
150
was not practicable with any design of nng then at hand. There-
fore, it \vas decided to make the collector rings in one solid piece
with a very considerable wearing depth. This necessitated
the removal of all the base rings and, in fact, it required a com-
plete dismantling of the entire rotor winding. As the outer ring
had loosened, there was a possibility of the base nngs loosening
in the same way, and therefore it was considered necessary to
apply some scheme for preventing this loosening in case of sudden
heating and expansion of any of the collector rings. It was then
decided to apply some form of spnng support underneath these
nngs, which could follow up any expansion in such a way as to
keep the rings tight under any temperature conditions liable to
be met with in practice. The spnng support used consisted of
a number of flat steel plates arranged around the rotor core, as
indicated in Fig. 13. These plates were of such length and stiff-
ness that a very high pressure was required to bend them down to
conform with the rotor surface.
These plates were arranged
around the rotor core and drawn
down with clamp rings until
they fitted tightly against the
mica. The collector ring was
highly heated and slipped over
the springs, the clamps being
removed as the ring was slipped
on. Tests were made to find
at what temperature such a ring would loosen. While the best
arrangement without springs would loosen at about 100 to 125
deg. cent., it was found that a ring supported, in the above
manner, was still fairly tight at 180 deg. cent., which was far
above any temperature which the machine would attain under
any condition. It may be said here that, after several years'
operation, this construction still appears to be first class, and
no loosening of any sort has occurred.
In removing the winding from the rotor, it w£s discovered
that the insulating tubes over the rotor conductors had traveled
back and forth along the rods a certain amount* This travel,
if continued for a long enough period, would apparently have
injured the insulation, although no trouble had yet developed.
Apparently, during heating and cooling, the expansion and con-
traction of the rods would carry the tubes with them lengthwise
a very small amount. The tubes would then seat themselves in
FIG. 13
160 ELECTRICAL EXGIXEERIXG PAPERS
the supporting rings or core and would not return to their original
positions. It was found that in the slotted pole face already
described, the webs or laminations of metal overhanging the
rotor slots would hold the tube when the rod was traveEng in
one direction, but would sometimes allow the tube to move
slightly when the rod traveled in the other direction, so that
there was a sort of extremely slow ratchet action taking place.
It was evidently necessary to have the tubes fit rather tightly
in the retaining or supporting holes in the rings and the core, and
to have the rods fit rather loosely in the tubes. Also, it ap-
peared that shellac or other " gummy " material on the inner
surface of the insulating tubes, was harmful, for wherever shellac
was, present the insulating tube always stuck to the rod and
would tear at either side of such place. In consequence, the
new set of tubes was made with a dry, hard finish on both the
outside and the inside, and the inside surface was also paraf-
FIG.
fined. This, when carried out properly, served to remedy this
trouble.
The reconstructed rotor, with the solid collector rings, was
shipped to the customer and the service was continued. After
operation for a considerable time, certain extremely serious dif-
ficulties appeared. One of these was brush trouble, and another
was undue wear of the rings.
The brush trouble was a most discouraging one. The machine
was located in an engine room adjacent to a rock-crushing build-
ing. Fine dust was always floating around the machine and,
this dust continuously passing through the machine tended to
form a deposit immediately behind the brushes as shown in Fig.
14. This dust packed in rather solidly behind the brush, due to
the high speed of the rings, and eventually it tended to lift the
brushes away from the rings. It also showed a tendency to get
Tinder the brush contact, with consequent increased resistance
of contact. Frequent removal and cleaning of the brushes
UXI-POLAR GENERATOR Uil
impracticable, as they were not sufficiently accessible to do
this readily. This rock dust, packed behind the brushes,
also had a scouring or grinding action on the rings themselves.
Accompanying this was an undue rate of wear of the rings. This,
however, was not entirely mechanical wear, as it appeared also
to be dependent upon the current carried and was, to some ex-
tent, due to a burning action under the brush which tended to
eat away the surface of the rings. However, while the undue
wear was not altogether due to dust back of the brushes, yet
this accumulation of dust appeared to have a very harmful
action on the machine. Various methods were considered for
overcoming this collection of dust, one of which consisted of
enclosed air inlets to the machine, fitted with screens for sifting
out the dust. This lessened the trouble to some extent, but
it was evident that it would not cure it entirely, as the entire
machine was so located that dust could come in around the brush
holders without going through the ventilating channels.
The method finally adopted for overcoming the difficulty of
accumulation of dirt was rather startling. It was casually sug-
gested that the copper leaf brushes be turned around so that
the rings would run against the brushes, so that the dirt or dust
over the rings would be " skimmed off " by the forward edge of
the brushes. This obviously would prevent the collection of
dirty but the question of running thin leaf copper brushes on
a collector ring operated at a speed of about 220 feet per second
(or 13,200 feet per minute) looked like an absurdity to any one
with experience in electrical machinery, so that we all hesitated
at first to consider the possibility of it. However, as something
had to be done, the writer suggested to the engineer in charge,
that he change the brushes on one of the rings so that they would
be inclined against the direction of rotation. This gave no
trouble and the other brushes were then changed to the same
direction and the operation ever since has been carried on with
this arrangement. To the writer this has always seemed an
almost unbelievable condition of operation, but as there has
not been a single case of trouble from this arrangement during
several years of operation, one is forced to believe that it is all
right. This change entirely overcame the trouble from accumu-
lation of dirt. However, it did not entirely cure the burning of
the brushes and rings above described, but rendered the matter
of lubrication somewhat easier than at first.
As to the other serious trouble, it was mentioned that there
162 ELECTRICAL ENGINEERING PAPERS
was a burning action under the brushes which tended to " eat "
or " wear " away the surface of the rings. This also tended to
burn away the brush surfaces, the amount of burning in either
case depending, to a considerable extent , upon the direction
of the current. At one side of the machine the brushes
would wear more rapidly, while at the other side the rings
would wear faster. The polarity of the current was influential
in this action. Particles of the metal appeared to travel in
the direction of the current; that is, where the current was from
the ring to the brushes, the ring would wear more rapidly,
while the brush would show but little wear, while at the other
end of the machine, the opposite effect would be found. How-
ever, the particles of metal taken from the ring did not deposit,
or " build up," on the brushes.
During all this operation, graphite had been used for lubri-
cation. In the earlier stages, powdered graphite compressed
into blocks, had been used. Later it was found that very soft
graphite brushes in insulated holders would give ample lubri-
cation for the rings. However, even with this lubrication and
the removal of the dirt trouble, there was still an appreciable
burning of the brushes and rings as indicated by the more rapid
wear of the rings at one end of the rotor, and of the brushes at
the other end. Extended tests showed that this burning was
a function of the contact drop between the brushes and the rings.
Neither the nngs nor the brushes would burn appreciably if
the contact drop between the brushes and the ring could be kept
very low. When this drop became relatively high (about one
volt), the rings or brushes would show an undue rate of wear. It
was found also that, after a considerable period of operation,
it was very difficult to obtain a low brush contact drop, as the
brush wearing surface became coated with a sort of " smudge,"
which seemed to have resisting qualities. An analysis of this
coating showed a very considerable amount of zinc in it, and
it was determined that the zinc in the collector rings was burning
out and forming an insulating coating on the brush contacts.
The remedy for this condition was the application of some clean-
ing agent which would chemically act on the smudge and dis-
solve it or destroy its insulating qualities. The right material for
this purpose was found to be a weak solution of muriatic acid —
about 4 per cent in water. When this was applied to the rings by
means of a " wiper," at intervals, the brush contact drop could be
reduced to a very low figure— frequently to 0.1 or 0.2 of a volt,
UXI-POLA R GENERA TOR 1 63
and the rings would take on a very bright polish. Also, while
this low contact drop was maintained it was found that the rings
showed an almost inappreciable rate of wear. However, one
set of rings continued to wear somewhat faster than the other.
This difficulty of unequal wear of the two sets of rings was over-
come by arranging a switch so that the polarity of the two ends
of the machine could be changed occasionally.
The temperature of the machine was reduced by the above
treatment of the rings. Obviously, part of the heat was due to
the loss at the brush contacts, which, of course, was reduced
directly as the contact drop was reduced.
The machine was now running quite decently with compara
tively heavy loads, from 7000 to 10,000 amperes, and the only
trouble was in several minor difficulties which were then taken
up, one at a time, in order to ascertain a suitable remedy.
These difficulties, however, were not interfering with the regular
operation of the machine.
One of the difficulties which finally developed was due to
stray magnetic fluxes through the bearings. These fluxes, pass-
ing out through the shaft to the shell of the bearing, consti-
tuted, in themselves, the elements of a small unipolar machine,
of which the bearing metal served as collecting brushes. The
e.m.f . generated in the shaft was a maximum across the two ends
of the bearing. Consequently the current collected from the
shaft by the bearing metal -should have been greatest near the
ends of the bearing, and least at the center. This was the case
as. indicated by the appearance of the bearing itself, which
showed evidence of pitting near the ends but none at the center.
To remedy this trouble, a small demagnetizing coil was placed
outside the stator frame, at each end of the rotor, between the
rotor core and the bearings. These coils were excited by direct
current which was adjusted in value until practically zero e.m.f .
was indicated on the shaft at the two ends of each bearing. This
indicated that the unipolar action was practically eliminated.
This arrangement has been in use ever since it was installed, and
no more trouble of any sort has been encountered from local
currents in the bearings or elsewhere.
Some of the brushes did not show as good wearing qualities
as desired and various experiments were made with different
combinations of materials and various thicknesses and arrange-
ment of the brush laminae. Brass leaf brushes were tried; also,
mixtures of copper, brass, aluminum and various other leaf metals
164 ELECTRICAL ENGINEERING PAPERS
in combination. None of these showed any better than the thin
copper leaf brush. The tests finally showed that such a brush,
very soft and flexible, with a suitable spring tension, would
give very satisfactory results. Also instead, of two brushes
side by side, a. single brush, covering the full width of a ring, was
found to be more satisfactory. Some tests were also made with
carbon brushes, consisting of a combination of carbon or graphite
combined with some metal, such as copper, in a finely divided
state. These brushes were claimed to have a very high carrying
capacity and also to have a certain amount of self -lubrication.
A set of these brushes was tried on one of the rings, but lasted
only for a very short time. The apparent wear was rapid, but
it is not known whether this was due to the very high speed of the
collector rings, or rapid burning away of the brush or4;he inability
of this type of brush to quickly follow any inequalities of the
collector rings. This test was abandoned in a comparatively
short time.
After getting rid of the old troubles, a new and unexpected one
had to appear. For some unknown reason, the insulating tubes
on the rotor conductors began to break down j also grounds oc-
curred between the collector rings and the core.
On account of the delay required in making any changes in
the rings or rotor winding, the customer arranged with the
manufacturer to have a new rotor built as a reserve, as it was
obvious that sooner or later there would have to be considerable
reconstruction of the insulation on the first rotor due to unex-
plained short circuits and grounds. A new rotor was at once
constructed, embodying all the good features of the first rotor,
with some supposedly minor improvements. The old rotor'was
then removed for investigation and repairs. The cause of the
breakdowns of the insulation on the tubes was then discovered.
The air entering through the axial rotor holes and passing out
through the radial holes between the rings, carried fine particles
of cement or Crushed stone dust and this had " sand-blasted M
the under side of the tubes. When the rotor had been operated
during the preliminary two months* period, previously described,
before the replacement of the rings, no evidence of thfe sand-
blasting had been visible. Investigation showed that the in-
sulating tubes in the former winding had been made with a fuller-
board base, which is rather soft and fibrous in its construction.
The tubes on the second winding had been made with " fish "
paper instead of fullerboard, in order to give a hard finish on the
UNI-POLAR GENERATOR
165
inside and outside. It was due to this hard material that the
troubles from sand blasting occurred. However, fish paper
tubes were superior to the fullerboard in strength and other
qualities, and as they were inferior only, in this one character-
istic, they were used again in rewinding the rotor, but where-
ever the tubes were exposed in passing from one ring to the next,
they were taped over with several layers of soft tape whch was
also sewed. This gave a soft finish which would resist sand-
blasting, and no trouble from this source has occurred for several
years.
From the breakdowns to ground, it was evident that an entire
replacement of the rings was necessary in order to repair the
mica bush or sleeve lying beneath the rings. This required
the removal of the entire rotor winding and rings. It was found
that cement dust coming up through the radial holes had sifted
in through various crevices- or openings
around the holes and that, finally, con-
ducting surfaces and paths were formed
which allowed the current to leak to
ground sufficient - to eventually burn the
insulation. Therefore, when replacing
the mica sleeve over the rotor, extra care
was taken to fit insulating bushings at
the top of the radial holes in such a
way as to seal or -close all joints, thus
allowing no leakage paths between
collector rings and the body of the cote. This is shown in Fig. 15.
No further trouble has occurred at this point.
In removing the collector rings for these repairs, it was found
that the flat spring supports shown in Fig. 13 had been entirely
effective and there was no evidence whatever of any disturbance
of the rings on the core, and there was no injury to the mica,
such as would be shown by any slight movement. The rings
were also very tight so that it took a very considerable temper-
ature to loosen them sufficiently for removal.
In view of the delay and expense of repairing one of these
rotors when the collector rings had to be removed, with the pos-
sibility of damaging the insulating tubes over the conductors,
and the insulating bush over the core, it was then decided that
a movable wearing ring was practically necessary in order to
make this mgdhine a permanent success. Therefore, the
problem of a separate outside wearing ring, as originally con-'
FIG. 15
166
ELECTRICAL ENGINEERING PAPERS
templated, was again taken up. The difficulty, already de-
scribed, of the zinc burning from the rings and forming a coating
on the brushes, indicated that some other material, without
such a large percentage of zinc, should give better results. The
difficulty was to obtain such a material, with suitable charac-
teristics otherwise. All data at hand showed that rings, with
desirable characteristics electrically, did not have the proper
elastic limits, or proper expansion properties when heated. In
other words, when such rings were shrunk on the base or sup-
porting ring they would stretch to such an extent, when cooled,
that they would become loose again with very moderate in-
crease in temperature. The solution of this problem of a separate
ring construction was found in the use of some spring arrange-
ment -underneath the outer ring which would still keep it tight
on the inner ring even when hot. The spring arrangement
PIG. 16
used under the inner rings, as shown in Fig. 13 was then applied
with certain modifications. In order to get good contact be-
tween the inner and outer rings for carrying the current, each
of these steel springs or plates was covered by a thin sheet of
copper as shown in Pig, 16. While each copper shest was of
comparatively small section, the large number of springs used
gave sufficient total copper to carry the current from the outer
to the inner or base ring without any danger of current passing
through the spring plates themselves. This arrangement was
used in reconstructing this rotor and has proven entirely
successful.
In order to determine the effects of various materials without
zinc, or with but a small quantity of it, a number of rings were
fitted up on a test rig and were operated for long periods with
currents, up to 12,000 amperes in some cases. In these tests,
UNI-POLAR GENERATOR 167
four different kinds of material were used, all of them representing
different mixtures of copper with a small percentage of other
materials but with little zinc in any of them. It was feared
that copper brushes on the copper rings would not work satisfac-
torily, but while there was apparently some difference between
the action of the different rings, it was found that copper brushes
running on copper were, in general, satisfactory. The brushes
were in-clined against the rings, as in the actual machine,
during this series of tests.
These tests were carried through with various numbers of
brushes, etc. It was found that the number of brushes could
be reduced to about one-third the full number, and still collect
the total rated current, but that any great reduction from the full
number of brushes made the operation of the rings and brushes
more sensitive, and more attention was required to keep them
in perfect condition. It was also found that any hardness or
undue "springiness" in the brushes, or brush material, would
tend to give increased wear. Brushes of very thin leaf copper,
eventually gave best results. It was also shown by these tests
that if a very good polish could be maintained on the rings,
the rate of wear from day to day was practically unmeasurable
on account of its smallness.
As a result of these ring tests, the rotor undergoing repair
was equipped with outside copper wearing rings, spring sup-
ported. The material in the rings was about 92 per cent pure
copper, 2 per cent zinc and 6 per cent tin.
The rotor was then installed in service and has been operating
steadily for several years, with entire success. The other rotor,
which had been operating while this rotor was being repaired,
was then thoroughly examined after removal, to determine any
possible defects. It was noted that the insulating tubes over
the rotor conductors were badly cracked or buckled in a number
of places. Upon removal of the rods or conductors it was found
that the insulating tubes were stuck so tightly to the copper
rods that they would be torn in pieces in trying to remove them.
As it had been intended that these tubes should move freely
on the rods or conductors, as previously described, it was evident
that there was something radically wrong. The true cause
of the "trouble was then discovered. In first fitting this set of
tubes over the rods, they had been too tight, and, in
order to make them fit easily, the men who assembled
the machine had reamed them* on the inside to enlarge
168 ELECTRICAL ENGINEERING PAPERS
them, and, in doing so, had cut away the inner hard sheet of
fish paper which had formed the lining, thus exposing a shellaced
surface. As soon as heated, this shellac stuck the tube to the
rod so that there could be no possible movement between the
two. In consequence, when the rods expanded or contracted,
the tubes moved backward and forward in the supporting holes,
and wherever they stuck fast in the outer holes, something had
to give, so that eventually the tubes buckled or cracked or pulled
open. This was readily remedied by putting on new tubes prop-
erly constructed. As the rings on this rotor were in very good
condition with but little worn away, the removable type of
ring was not added, as this would require turning off a large
amount of effective material on the existing rings and replacing
it with new outer rings. It was decided that as there was several
years' wear in the old rings, it would be of no material advantage
to throw this away when it could be worn away in service,
just as well as it could be turned off in a lathe. After the rings
in this machine are worn down the permissible depth, they will
be refilled by the addition of the removable type.
This unipolar generator has now been in service for quits
a long period, with no difficulty whatever, and with an average
ring wear of less than 0.001 in. per day, or less than f in. per
year. This may seem like an undue rate of wear; but in reality
it is an extremely low rate, if the high peripheral speed, and the
number of brushes, are considered. This machine operates
day and night, seven days in the week, and practically contin-
uously during the entire year. Taking the peripheral speed
into account, the above rate of Wear represents a total travel
of each, ring of about 3.6 million miles for each inch depth of wear,
or about 150 times around the earth along a great circle. Con-
sidering that there are brushes bearing on each ring at intervals
of about eight in., a wear of one in., for every 3.6 million miles
traveled, does not seem unduly large. If, at the same time, it
is considered that the brushes are collecting from 7500 to 10,000
amperes from each ring on a total ring surface of about 3£ in.
wide by 42 in. diameter, it is not surprising that there should
be more or less " wear " due to the collection of this current.
In fact, the current collected averages from 16 to 20 amperes
per square inch of the total ring wearing surface. This may be
compared with standard practice with large d-c. commutators,
in which H to 2 amperes per square inch of commutator face
is usual and 3 amperes is extreme.
UNI-POLAR GENERATOR 169
On account of the final success of this machine, the story of
its development is a more pleasant one to tell than is the case
in some instances where entirely new types of apparatus are
undertaken. It might be said, after reviewing the foregoing
description, that many of the troubles encountered with this
machine could have been foreseen; but such a statement would
be open to question, for the engineers of the manufacturing
company were in frequent session on all the various phases and
difficulties which developed. The writer knows that in many
cases, after any individual trouble was known, suggestion for
remedies were not readily forthcoming. The writer does not
know of any individual machine where more engineering and
manufacturing skill was expended in endeavoring to bring about
success, than was the case with this machine. As an example
of engineering pertinacity, this machine is possibly without a
rival. A mere telling of the story cannot give more than a
slight idea of the actual fight to overcome the various difficulties
encountered in the development of this machine.
The results obtained were valuable in many ways. Many
data were obtained which have since been of great use, both from
a theoretical as well as a practical standpoint, in other classes
of apparatus. Certain fundamental conditions encountered in
this machine have led to the study of other allied principles
which point toward possibilities in other lines of endeavor.
Therefore this machine, which was very costly in its develop-
ment, may eventually pay for itself through improvements and
developments in other lines of design.
The writer wishes to say a good word for the purchaser of this
new apparatus. He was long-suffering, and was undoubtedly
put to more or less trouble and inconvenience, but nevertheless
he gave opportunity to correct difficulties. He recognized that
the engineers were confronted with a new problem in this ma-
:hine and he gave them an opportunity to cany it through to
success. Apparatus of this type could only be developed to
full success in commerical operation, as all the difficulties en-
countered would never have been found on shop test. There-
fore, the attitude of the customer was of prime importance in
the development of such a machine.
COMMUTATING POLES IN SYNCHRONOUS
CONVERTERS
FOREWORD — About 1909, the use of commutating poles in syn-
chronous converters was being studied. Suggestions were made
from time to time that our usual slow speed rotary converters
shoiild have interpoles. The author, therefore, prepared a short
article, explaining wherein commutating poles would be of less
value to rotary converters, of the then usual speeds and con-
structions, than they would be on direct-current generators.
11 Late in September, 1910, the Chairman of the Papers Com-
mittee of the American Institute of Electrical Engineers asked
the author whether he had any material which could be pre-
pared for the Institute on very short notice, A rough draft
of this article was submitted and was at once accepted, with
instructions to complete it for the following November meeting.
The author called to his aid, Mr. F. D. Newbury, who added
about one-half more, covering principally material on existing
types of rotaries. Most of this latter part has been omitted from
this reprint, but the author's discussion at the Institute meeting
has been incorporated as it forms a technical continuation of the
first part of the paper and brings out that the real need for
commutating poles in rotary converters would come with higher
This paper states that the short-circuiting effect of the
dampers surrounding the commutating poles is considered
harmful. However later experience has shown that the in-
creased damping effect of this arrangement more than compen-
sates for the harmful effects.
As this paper was written before the term "commutating
pole" was adopted as standard, the term "interpole" has been
used throughout. — (ED.)
SYNCHRONOUS converters with interpoles have been used
^ but little in this country up to the present time (1910). Con-
sidering that interpole generators and motors have come into
extensive use in this country, the question will naturally be raised
why interpole converters have not come into similarly extensive
use. The reply might be that the introduction of any new type of
apparatus is a relatively slow process; but, on the other hand,
interpoles on direct current generators and motors came into
general use in a relatively short time, especially so in railway
motors. This indicates that there has been a more or less pressing
need for interpoles in certain classes of apparatus and the greater
the need for the change the quicker was the change made.
Any important change in design or type must be justified
171
172
ELECTRICAL ENGINEERING PAPERS
by engineering and commercial reasons, such as improved per-
formance greater economy, or lower cost. In the railway motor,
placed under the car, and more or less inaccessible, improved
operation at the brushes and commutator, when equipped with
interpoles, represented a pressing reason for the change in type,
although the cost and efficiency were not appreciably changed.
In the direct-current generator with the modern tendency toward
higher speeds with lower cost, the interpoles represented a
practical necessity. This has been recognized for several years
and the change to the interpole type has been made as rapidly
as circumstances will permit. Also, in variable-speed direct-
curretit motors interpoles have been in general use for a number
of years, simply because the interpoles represent a very definite
improvement in a number of ways.
New types of apparatus should only be introduced where they
represent some distinct improvement or advance over existing
types. Where a new type does not represent such improvement
and is simply introduced to gratify a personal whim of the
purchaser, or desire on the part of a manuf acturing company to
produce something different from other companies, the new
apparatus, as a rule, will not advance quickly into public favor
since there is no real necessity for it.
It is therefore a question
whether the slowness in the
introduction of interpoles in
synchronous converters is due
to lack of sufficient advan-
tages, or American engineers
do not sufficiently appreciate
their advantages. There ap-
pears to be room for wide
differences in opinion on this
subject. The synchronous
converter and the direct-
current generator are two
qttite different machines, in
their characteristics, and no
one can say off hand, that interpoles will give the same results
in both. In the following is given a partial analysis of the condi-
tions occurring in the two classes of machines, which will indicate
wherein interpoles are of greater advantage on direct-current
generators than on converters.
FIG. 1
COMMUTATING POLES ON ROTARIES 173
Taking up first, the direct current generator, it may be
considered as containing two sets of magnetizing coils, namely,
the armature and the field windings. Considering the armatiire
winding alone, the magnetomotive force of the armature winding
has zero values at poirxts midway between two adjacent brush
arms or points of collection of current and rises at a uniform rate
to the point of the winding which is in contact with the brushes.
This is illustrated in Fig. 1. Therefore the armature winding
has Its maximum magnetizing affect or magnetomotive foi<~-
at that part of the core surface where the winding is directly
in contact with the brushes. However, the magnetic flux- set
up by the armature winding will not necessarily be a maximum
at this point, as this depends upon the arrangement of the mag-
netic or other material surrounding the armature. If this point
occurs midway between two field poles, then, while the mag-
netizing effect is greatest at this point, the presence of a large
air-gap at this same point may mean a relatively small magnetic
flux, while a much higher flux may be set up by the armature
winding at the edges of the adjacent field poles. In the usual
direct-current generator construction without interpoles, the
position of commutation is almost midway between two adjacent
poles and therefore the point .of maximum magnetomotive
force of the armature is also practically midway between poles.
The absence of good magnetic material over the armature at
this point serves to lessen the magnetic flux due to the armature
magnetizing effect, but even with the best possible proportions
there will necessarily be a slight magnetic flux set up at this
point. While this field is usually of small value, yet unfor-
tunately it is of such a polarity as to have a harmful effect on the
commutation of the machine. During the operation of comma*
tation, the coil which is being commutated has its two terminals
short-circuited by the brushes. If this short circuited coil at
this moment is moving across a magnetic flux or field, it will
have an e.m.f . set up in it which will tend to cause a lo£al or
short circuit current to flow. Such a current is set up by the
flux due to the armature magnetomotive force described above
and unfortunately this current flows in such a way as to give the
same effect as an increased external or working current to be re-
versed as the coil passes from under the brush. In other words,
the e.m.f. set up in the short circuited coil by the above field
adds to the e.m.f. of self induction in the coil due to the reversal
of the working current.
174= ELECTRICAL ENGINEERING PAPERS
Another cause of difficulty in the commutation of a direct
current machine is the self induction of the armature coils as they
individually have the current reversed in them in passing from
one side of the brush to the other. Each coil has a local magnetic
field around itself, set up by current in itself and its c-sighboring
coils. The value of this local magnetic field depends upon the
arrangement of the winding, the disposition of the magnetic
structure around the coil, the ampere turns, etc. During the
act of commutation, that part of the local field due to the coil
which is being commutated must be reversed in direction. It is
therefore desirable to make the local field due to any individual
coil as small as possible. This means that the number of tisms
per coil should be as low as possible, the amperes per coil aiso
should be as small as possible, while the magnetic conditions sur-
rounding the coil should be such as to give the highest reluctance.
By the proper arrangement of the various parts, it is usually
found that the e.m.f- of self induction, due to the reversal of the
coil passing under the brush, can be made of comparatively small
value so that, if no other conditions interfere, good commutation
could be obtained under practically all commercial operating
conditions. t However, the magnetic field between the poles set
up by the armature magnetomotive force as a whole, as described
above, adds very greatly to the difficulties of commutation. If
the armature magnetomotive force, or the field due to it, could
be suppressed, then one of the principal limitations in the design
and operation of direct-current generators would be removed,
and the commutation limits would be greatly extended. Or,
better still, if a magnetic flux in the reverse direction were estab-
lished at the point of commutation, then the e.m.f. set up by this
would be in opposition to the e-.m.f. of self induction of the
commutated coil and would actually assist in the commutation!
This latter is what is accomplished by interpoles. When these
are used the brushes on the commutator are so placed that the
short circuited or commutated coils are directly under the inter-
pole. Consequently, the maximum magnetomotive force of the
armature is in exact opposition to that of the interpoles. There-
fore, the total ampere turns on the interpoles should be equal to
the total ampere turns on the armature in order to produce zero
magnetic flux under the interpole or at the point of commutation
But, for best conditions there should not be zero field, but a
slight, field in the opposite direction from that which the arma-
ture winding alone would produce. Therefore, the magneto*
COMMUTATING POLES ON ROTARIES 175
motive force of the interpole must be greater than that of the
armature by an amount sufficient to set up a local field under
the interpole which will establish an e.m.f . in the short circuited
coils opposite to that set up by the commutated coils themselves
and practically "equal to it. The excess ampere turns required
on the commutated poles is therefore for magnetizing purposes
only and the amount of extra ampere turns will depend upon the
value of the commutating field required, depth of air-gap under
the commutating pole, etc. The commutating field required is
obviously a function of the self induction of the commutated coil
and evidently the lower the self induction the less commutating
field will be required. It is evident therefore that the commu-
tating field under the commutating pole bears no fixed relation
to the armature ampere turns or to the main field ampere turns,
but is, to a certain extent, dependent upon the proportions of
each individual machine.
It is evident that the magnetomotive force of a given arma-
ture varies directly with the current delivered, regardless of the
voltage. Therefore, that part of the interpole magnetomotive
force which neutralizes that of the armature should also vary
directly in proportion to the armature current. Also, the self
induction of the commutated coils will vary in proportion to the
armature current carried, and therefore the magnetic field under
the interpole for neutralizing this self induction should also
vary in proportion to the armature current. It is therefore
obvious that if the main armature current be put through the
interpole winding, the magnetomotive force of this winding will
vary in the proper proportion to give correct commutating con-
ditions as the armature current varies, regardless of the voltage
of the machine. This is on the assumption that the entire
magnetomotive force of the interpole winding is effective at the
air gap and armature, which implies an absence of saturation in
the interpole- magnetic circuit. In the usual construction, the
interpole winding always carries the main armature current
as indicated above.
One consequence of the use of the interpole is that somewhat
less regard need be paid to keeping the self induction of the
commutating coil at its lowest value. In consequence, there is
somewhat more freedom in proportioning the armature wading,
slots, etc., than in a non-interpole machine, and advantage can be
taken of this in bettering the proportions for other characteristics.
176
ELECTRICAL ENGINEERING PAPERS
The conditions of design are therefore not as rigid in the interpole
as in the non-interpole type.
The above description of the interpole generator has been gone
into rather fully, as many of the points mentioned ^vill be re-
ferred to again in connection with interpoles on synchronous
converters.
The synchronous converter differs from the direct current
generator in one very important particular, namely, it may be
considered as motor and generator combined. It receives cur-
rent from a supply system the same as a motor and it delivers
current to another system like a direct-current generator. The
magnetomotive force of the armature winding as a motor acts
in one direction, while the magnetomotive force of the armature
winding as a generator acts in the opposite direction. As the
input is practically equal to the output, it is evident that these
two armature magnetomotive forces should practically neu-
tralize each other, on the assumption that the armature mag-
netomotive force, due to the polyphase current supplied has
practically the same distribution as -that of the corresponding
direct-current winding. Assuming that the two practically
balance each other, then it is evident that one of the principal
sources of commutation difficulty in direct current generators
-45°-750-I5°
FIG, 2
FIG. 3
is absent in the converter and therefore the limits in commuta-
tion should be much higher than those of direct-current ma-
chines.
COMMUTATING POLES ON ROTARIES
177
The following diagrams show the distribution of the alternating-
current and direct-current magnetomotive forces on a six-phase
rotary converter. The magnetomotive force distribution for
the alternating-current input is plotted for several different
positions of the armature. Three different positions are shown
with the armatures displaced successively 15 electrical degrees.
The general forms of these distributions repeat themselves for
further similar displacements.
These distributions are illustrated in Figs. 2, 3 and 4. It is
evident from these three figures that the peak value of the mag-
netomotive force the armature varies as the armature is rotated,
as indicated by the heights of the center line in the three figures.
In Fig. 5, the magnetomotive force distribution of Fig. 2 and
the corresponding direct-current distribution of Fig. 1 are both
shown, but in opposition to each other. In this figure both are
shown in proper proportion to each other, taking into account
the alternating current amperes and the direct-current amperes
output. The resultant of these two distributions is also indi-
cated in these figures.
In Fig. 6 the distributions correspond to Figs. 3 and 1 combined
and the resultant is also shown.
Fig. 7 combines Figs. 4 and 1.
FIG. 4
PIG.
It is the resultant magnetomotive force in these three figures
which is important, as this is the effective magnetomotive force
which tends to produce a flux or field over the commutated
178
ELECTRICAL ENGINEERING PAPERS
coil. It is evident from these figures, which are drawn to scale,
that this resultant varies in height as the armature is rotated, but
the maximum is only a relatively small per cent of the direct-
current magnetomotive force. Therefore, it is obvious that
one of the principal sources of difficulty in the commutation of
the direct-current generator is practically absent in the converter,
and it is also evident from this that the commutating conditions
in the latter should be materially easier than in the former.
This has proved to be true by wide experience in the construction
and operation of converters.
In the above figures the magnetomotive forces have been
plotted to scale on the following basis:
The six-phase converter winding is connected to three trans-
formers with the so-called diametral arrangement; each of the
three secondaries is connected across the diameter, or across
180 deg. points on the winding, the three diameters being dis-
placed 60 deg. with respect to each other. Assuming the direct
current in the winding as A, then the maximum value of the
alternating current in- any one phase of the alternating-current
end will be equal to f A, or 0.667 A, assuming 100 per cent
efficiency. However, as the alternating-current input must be
somewhat greater than the direct-current output, due to certain
losses in the machine, it is evident that the maximum alter-
nating current in any one phase must be somewhat greater than
0.667 A. The field copper losses may be considered as part of
COMMUTATING POLES ON ROTARIES
179
the output of the rotary. The armature copper Ipsess maybe
considered as due to an ohmic drop between the counter e.m.f.
of the armature and the transformer e.m.f., and simply a higher
transformer e.m.f. must be supplied to overcome this drop and
therefore it does not effect the true current input of the rotary.
However, the losses due to rotation, such as iron loss and. the
friction and windage are excess losses which represent extra
current which must be supplied to the alternating-current end
of the rotary. These rotational losses will usually be relatively
small in a 25-cyde converter, being possibly 4 per cent or 5 per
cent in a small machine and li per cent to 3 per cent in a large
machine. In the 60-cyde converters, where the iron losses are
relatively higher and the speeds are somewhat higher, giving
greater friction and windage, the rotation losses may be con-
siderably greater than on 25-cycle machines. Assuming these
rotation losses will be 3 per cent, then the maximum alternating
rt ftftrr A
current per phase = ' y — = 0.687 A. The foregoing Figs. 5,
6 and 7 are worked out on this assumption of 97 per cent rota-
tional efficiency and on this basis of -mini-mum value of the
resultant magnetomotive force of the armature at the direct-
current brush is about 7 per cent of the direct-current magneto^
motive force of the same word-
ing, while the maximum value is
about 20 per cent. The lower the
rotational efficiency the smaller
would be these values, and with
a rotational efficiency of about
) per cent, the mfmrmini result-
ant would fall to zero, while the
maximum value would be about
13 per cent.
The resultant magnetomotive
force of a synchronous converter
might be compared with that of
a direct-current generator with
compensating windings in the
pole faces. It is generally known
that such direct-current generators have much better com-
mutatiag conditions than ordinary uncompensated machines.
If such compensating winding on the field of a direct-current
machine covered symmetrically the whole armature surface.
pIG
180 ELECTRICAL ENGINEERING PAPERS
then the armature reaction could be completely annulled, which
is not the case in the converter. But with compensating wind-
ings located only in the pole faces, then the armature magneto-
motive force midway between the poles could not be completely
annulled, unless over-compensation is used, and the resultant
would be as shown in Fig. 8, which is not quite as good as the
average resultant in the converter. The commutating con-
ditions in the converter can therefore be considered as at least
In the application of interpoles to the synchronous converter
the same principles should hold as in a direct-current generator,
namely, the interpole magnetomotive force should be sufficient
to neutralize that of the armature winding and, in addition, should
set up a small magnetic flux sufficient to overcome the self in-
duction of the commutated coil. As the magnetomotive force
the armature varies between 7 per cent and 20 per cent shown in
the above figures, it is evident that perfect compensation of this
cannot be obtained and that therefore only some average value
can be applied. Assuming that 15 per cent will be required on
the average to compensate for this, then in addition the inter-
pole winding must carry ampere turns sufficient to set up the
small magnetic field for commutation. Thus the total ampere
turns on the interpole will be equal to 15 per cent of the armature
direct-current ampere turns plus a small addition for setting up
the useful or commutating field. In the direct-current gen-
erator, the ampere turns on the interpoles must equal the total
armature ampere turns plus a corresponding addition for the
commutating field. It is therefore evident that an interpole
winding on a converter will naturally be very much smaller than
on a direct-current generator, and in general it is between 25 per
cent and 40 per cent of the direct-current.
In the pulsating resultant magnetomotive force in the con-
verter there lies one possible source of trouble with interpoles
Assume, for example, the total ampere turns on the interpoles
are equal to 30 per cent of the direct-current ampere turns on the
• rotary and that 15 per cent of this is for overcoming the average
value of the resultant magnetomotive force, then an average
of 15 per cent will be available for setting up a commutating
field; but, according to the above diagrams, the resultant mag-
netomotive force of the armature varies from 7 per cent to 20 per
cent. With a total interpole winding representing 30 per cent,
COMMUTATING POLES ON ROTARIES 181
then the effective or magnetizing part will vary from 30-7
to 30-20; that is, from 23 per cent to 10 per cent. The effective
magnetomotive force therefore tends to vary over quite a wide
range so that the commutating field would also tend to vary up
or down over a velry considerable range, which is an undesirable
thing for commutation. However, as this pulsation is at a
fairly high frequency it tends to damp itself out by setting up
eddy currents in the structure of the magnetic circuit. If a
good conducting damper or closed circuit were placed around the
interpole, it is probable that this pulsation would be almost
completely eliminated, but such a damper possesses certain dis-
advantages, as will be shown later.
In practice this pulsation of the armature reaction under
the interpoles is apparently not noticeably harmful in most
cases, as evidenced by the fact that well-proportioned interpole
converters in commercial service show no undue trouble at the
commutator or brushes,
Due to the relatively small number of ampere turns required
on the interpole of a converter compared with those required on
a direct-current generator, the design of the interpoles in the two
cases presents quite different problems. In the direct-current
generator the interpoles carry ampere turns, which in all cases
are greater than the armature ampere turns, as explained before.
As the field ampere turns on the main poles are, not infrequently,
but little greater than the armature ampere turns, it is evident
that the interpole winding may, in some cases, carry as many
ampere turns as the main field windings. While but a small
per cent of these interpole windings is effective in producing
flux under the pole tip, yet they are all effective in producing
leakage from the sides of the poles. As the interpoles are gen-
erally small in section compared with the main poles, and as
they may carry ampere turns equal to the main poles, it is
evident that the effect of leakage may be relatively great on the
interpole.
For instance, if the leakage on the main poles is 15 per cent of
the useful flux, then, with the same total leakage on the inter-
poles, this may represent a very high 'value compared with the
useful flux, due to the small section of the interpole and the
relatively low useful interpole flux. In consequence, it is con-
siderable of a problem to proportion the interpoles of a direct
current generator so that the leakage flux will aot saturate the
interpoles at some part of the circuit. If they saturate, then
182 ELECTRICAL ENGINEERING PAPERS
part of the ampere turns on the interpole are expended in such
saturation and the part thus expended must be counted off from
the extra or excess interpole ampere turns. If, for example,
the interpole winding requires 100 per cent for overcoming the
armature and there is 20 per cent extra ampere turns for setting
up a useful flux, then any saturation in the interpole circuit must
represent additional ampere turns on the field, as the above
120 per cent is necessary for useful flux and for neutralizing the
armature. With reduced current, and consequent lower satura-
tion, these additional interpole turns become effective in mag-
netizing the gap and thus the commutating flux is too strong.
At greatly increased load, more ampere turns are required for
saturation, and the commutating flux is altogether too weak.
It is thus evident that a machine with highly saturated inter-
poles will not comtnutate equally well for all loads. Herein
lies a problem in the design of interpole generators, as it is
difficult to maintain a relatively low saturation in the interpoles
due to their small section and high ampere turns which cause
leakage. It is well known that in the main poles of the generator,
a leakage flux which is higher than the useful flux is objection-
able, from the designer's standpoint; and yet in the use of inter-
poles this is a normal condition rather than an exception.
In the synchronous converter the conditions are somewhat
different due to the fact that the interpole ampere turns are
usually only 25 per cent to 40 per cent as great as on a correspond*
ing direct-current generator. The leakage at the -sides of the
poles becomes relatively much less, while the usefrjl induction
remains about the same as on the direct-current generator. In
consequence, saturation of the poles is not so difficult to avoid.
Irl some cases, due to the smaller ampere turns on the interpole
winding, the interpole coils can be located nearer the pole tip
and thus the leakage can be further reduced. However, the
placing of the interpole coil over the whole length of the pole
is not as objectionable in the converter interpole as -it is on the
direct-current generator as the ampere turns are less. It is those
ampere turns which are located close to the yoke, or furthest
away from the pole tip, which produce the highest leakage, while
those close to the pole tip usually produce much less leakage,
but in interpole generators with their high number of ampere
turns on the interpoles it is often difficult to find space for the
iaterpole winding, even if distributed over the whole pole length.
In some casess a direct-cuirent machine may be larger than
COMMUTATING POLES ON ROTARIES 183
would otherwise be zequired, simply to obtain space for the inter-
pole winding. This is not true' to the same extent in the appli-
cation of interpoles to converters.
In the above the leakage is referred to as a function of the
interpole winding as if the main winding had little or nothing
to do with it. The reason for this nxay be given as follows:
Fig. 9 represents two main poles and an interpole of a direct-
current generator or converter, with their windings in place.
The direction of current or polarity of each side of each coil is
also indicated by + or — . It is evident that between the inter-
pole and one main pole, the interpole winding and the main
field winding are of the same polarity, while on the opposite side
of the interpole, these two windings are in opposition. Let A
equal the ampere turns of the interpole and B the ampere turns
in the main coil. Then, A+B will represent the leakage ampere
turns at one side of the interpole and A - B will represent the
leakage ampere turns at the other side. Therefore, the leakage
at the two sides of the poles is represented by (A +B) -f (A - B)
= 2A; that is, the leakage could be considered as due to the
interpole winding entirely and may also be considered as due to
double the interpole turns acting as one side of the interpole
only. Another way of looking at this is to consider that the
windings on the main pole produce leakage in' the interpoles,
but the leakage due to one main pole acts radially in, one direc-
tion in the interpole, while that due to the other main pole is
in the opposite direction.
Considering therefore the interpole leakage as being due to
the interpole ampere turns only, it is evident that the syn-
chronous converter will not be
troubled with saturation of the in-
terpoles to the same extent as a
direct-current generator. With the
same size of interpole it is evident
that tke converter should be able
to carry heavier overloads than the
direct-current generator before saturation of the interpoles is
reached.
It was mentioned before that a closed conducting circuit
around the interpoles would be objectionable. This has be$n
proved by experience with irtterpole generators. It is evident
from the preceding analysis that the ampere turns on the inter-
pole of a direct-current generator should always rise or fall in
184 ELECTRICAL ENGINEERING PAPERS
proportion to the armature ampere turns in order to give best
commutation, assuming, of course, no saturation of the poles.
If the interpole turns are directly in series with the armature
winding, with no shunt across the interpole winding, it is evident
that the interpole ampere turns must vary in direct proportion
to the armature ampere turns. However, if a non-inductive
shunt, for instance, were connected across the interpole winding
in order to shunt part of the current, then in the event of a sudden
change in load, the interpole winding being inductive due to its
iron core and the shunt being non-inductive, the momentary
division of current during a change in load would not be the same
as under steady conditions. In other words, if the armature
and interpole current were suddenly increased, then a large part
of the increase would momentarily pass through the non-induc-
tive interpole shunt until steady conditions were again attained.
In consequence, the interpole ampere turns would not increase
in proportion to the armature ampere turns just at the critical
time when the proper commutating field should be obtained.
The same condition is approximated when a separate con-
ducting circuit is closed around the interpole. A sudden change
in the current in the interpole winding, causes a change in the
flux, and secondary currents are set up in the closed circuit,
which always act in such a way as to oppose any change in the
flux, whereas, the flux in reality should change directly with the
current. The above described non-inductive shunt across the
interpole winding might be considered also as completing a
closed circuit with the interpole winding, and therefore retarding
secondary currents would be set up in this closed circuit with any
change in the flux in the interpole.
In some cases it may be impracticable to get exactly the right
number of turns on the interpole winding to give the correct
interpole magnetomotive force. For example, on a heavy
current machine, 1.8 turns carrying full current might be re-
quired on each interpole. If two turns were used, with the
extra current shunted, the right interpole strength would be
obtained. A non-inductive shunt, however, is bad, as shown
above. However, if an inductive shunt is used, instead of non-
inductive, and the reactance in this shunt circuit is properly
adjusted, then it is possible to get the right interpole strength for
normal conditions and still obtain satisfactory conditions with
sudden changes in load. Also, by arranging the interpole
winding so that a very considerable percentage of the current
COMMUTATING POLES ON ROTARIES 185
is shunted normally by an inductive shunt having a relatively
high reactance compared with the interpole, it should be possible
to force an excess current through the interpole winding in case
of a sudden increase in load, in case a stronger commutating
field were needed at this instant.
On the interpole synchronous converter a non-inductive shunt
across the interpole winding should act very much as on an inter-
pole generator and therefore non-inductive shunts are inad-
visable. If any shunting is required it should be by means of an
inductive shunt in those cases where the current from the con-
verter is liable to sudden fluctuations, as in railway service.
"Where the service is practically steady, a non-inductive shunt
should prove satisfactory for the interpoles of converters or
direct-current generators.
Under extreme conditions of overload current, that is, in
case of a short circuit across the terminals, it is questionable to
what extent interpoles are effective. It is practicable to design
interpoles on direcUcurrent generators which will not unduly
saturate up to possibly three or four times normal load. How-
ever, in case of a sudden short circuit the current delivered by
the machine is liable momentarily to rise to a value anywhere
from 15 to 30 times full load current. With this excessive cur-
rent the interpoles of the direct-current generator must -neces-
sarily be more or less ineffective. On account of saturation, the
commutating flux under the interpole cannot rise in proportion
to the current. However, there should still be some commutating
field present, which condition is probably Considerably better
than no field at all, or a strong field in the opposite direction
as would be found without commutating poles. Therefore, in
direct-current generators with well-proportioned interpoles,
the conditions on short circuit are generally less severe than in
non-interpole machines.
If the pole is highly saturated by the heavy current rush on
short circuit, then it is evident that a highly inductive shunt,
as described above, which would increase the interpole current
in a greater proportion than the armature current, would simply
mean higher saturation with little or no increase in the useful
flux tinder the interpole.
In the synchronous converter at short circuit the conditions
may be somewhat different. When the converter is short cir-
cuited it can also give extremely high currents, possibly touch
greater than the corresponding direct-current generator can give.
186 ELECTRICAL ENGINEERING PAPERS
Both, the armature winding tied to an alternating-current supply
system, and the presence of the low resistance dampers on the
field magnetic circuit, tend to make the short circuit conditions
more severe in the converter. The worst condition, however,
would appear to be in the relation of the interpole ampere turns
to the armature ampere turns on short circuit. As shown before,
the normal ampere turns on the interpole winding will be only
25 per cent to 40 per cent of the direct-current ampere turns on
the armature. In the case of a sudden short circuit the armature
momentarily may deliver a very considerable current as a direct-
current generator, and the armature reaction, or the resultant
magnetomotive force, may approach that of a direct-current
generator. In such case the ampere turns on the interpole will
be very much smaller than the* armature resultant magneto-
motive force at this instant and thus there will be no commu-
tating flux under the interpole, but, on the contrary, the arma-
ture being stronger, there will be a reverse flux which may be
considerably higher than if no interpole were present, as the iron
of the interpole represents an improved magnetic path for such
flux. While the converter armature will probably never deliver
all its energy as a direct-current generator at the instant of short
circuit, yet it may be assumed that it will deliver some of its
load thus, and it does not require a very large per cent to be
generator action in order to neutralize, or even reverse the effect
of -the interpoles. In consequence, on a short circuit the con-
verter may have a reverse field under the commutating pole,
while the direct-current generator under the same condition
will have a field of the proper direction but of insufficient strength
which, however, is a much better condition than a field of the
wrong polarity.
The inductive shunt mentioned before, which normally shunts
a considerable portion of the interpole current, might be more
effective in a converter than in a direct-current generator in the
case of a short circuit. In a direct-current generator, the inter-
poles would be so highly saturated, as described before, that the
increase in current in the interpole winding due to the inductive
shunt would be relatively ineffective. In the converter, how-
ever, the saturation of the interpole can normally be very much
lower than in the direct-current generator and it might be
practicable to so proportion these interpoles that they do not
saturate highly, even on short circuit. In consequence, a
strong inductive shunt might force up the interpole ampere
COMMUTATING POLES ON ROT ARIES 187
turns so that the negative field under the interpole would be
much decreased, or might even be changed to a positive field
and thus become useful in commutation. This would be helpful
only during the short circuit. However, converters not infre-
quently flash over or " buck " when the circuit breaker is
opened on a very heavy overload or a short circuit and not
when the first rush of current occurs. If the flash tends to
occur at the opening of the circuit, then the above mentioned
inductive shunt might have just the opposite effect from what is
desired, for it would tend to develop or maintain a stronger
field under the interpole after the armature reaction is removed.
In consequence, the heavy inductive shunt might prove harmful
in such a case.
Another condition exists in a converter which does not exist
in a generator* When a short circuit occurs on a direct-current
generator, the armature reaction tends to distort the main field
very greatly — so much so that the field of the machine is very
greatly weakened. This decreases the terminal voltage and
the resultant decrease in the shunt excitation will still further
tend to weaken the field. In consequence, the machine tends
to " kill " its magnetic field and the voltage tends to drop to a
low value. Therefore, when the breaker opens on a short circuit
the direct-current voltage may be falling rapidly. When the
armature current is removed from the machine the voltage may
rise slowly, depending upon the natural rate of building up the
field. Consequently, after the breaker opens there is little or no
tendency to flash, and practically all difficulties occur dttting the
current rush, before the breaker oftens. In a converter, how-
ever, the conditions are different. The armature of the con-
verter is tied to an alternating-current supply system which
tends to maintain the voltage on the converter. The machine
cannot " kill " its field in the same way as the direct-current
generator, for the alternating-current system tends to maintain
the field by corrective currents which act in such a way as to tend
to hold up the voltage. An enormous current may be drawn from
the alternating-current system momentarily in case of a short
circuit on the direct-current side of the converter. This heavy
alternating current may cause a drop in the alternating-current
lines, step-down transformers, etc., so that the supply voltage
does fall very considerably and the direct-current voltage does
drop materially in case of a short circuit. However, the instant
the short circuit is removed by opening the breaker, then the
188 ELECTRICAL ENGINEERING PAPERS
converter at once tends to attain full voltage as the alternating-
current supply system tends to bring the armature up quickly
to normal voltage conditions. In consequence there may be a
relatively heavy current flow in the alternating-current side of
the machine, while there is no direct-current flow in the armature
Part of this alternating-current flow represents energy in bringing
the machine back to a normal condition, and part is purely mag-
netizing or wattless current. The energy component tends to
produce an armature magnetomotive ibrce giving an active field
at the point of commutation. This energy component alter-
nating-current flow, however, cannot be corrected by inter-
poles, as there is no direct current flowing.
A further difference between the synchronous converter and
the direct-current generator, in case of a short circuit, lies in the
results of field distortion. The enormous short circuit current
from the converter with the armature acting partly as a direct-
current generator, may very greatly shift or distort the field
flux. The dampers on the field poles tend to delay this distor-
tion. Also, after distortion has occurred they tend to maintain
the distorted or shifted field so that momentarily after the circuit
breaker opens the converter may be operating without direct-
current load but with a very badly distorted or shifted field.
This also tends to produce sparking or flashing after the direct-
current breaker has opened.
Another condition which may affect the action of interpoles
on converters, but which does not occur in direct-current gen-
erators, is hunting. When Jaunting occurs in a converter the
energy current delivered to the alternating-current side of the
converter pulsates, or varies up and down over a certain range,
which may be either large or small. At the same time the direct-
current flow is apparently varied but little. In consequence,
the resultant magnetizing effects of the alternating current and
direct current do not nearly neutralize each other at all times.
When the alternating-current energy input is least the converter
delivers part of its direct-current load as a generator, the stored
energy in the rotating armature being partly given up to supply-
ing the direct-current power. In this case the resultant magneto-
motive force may be a very considerable per cent, of the maxi-
mum direct-current magnetomotive force of the armature wind-
ing. Also, the magnetic field under the main poles is distorted
or shifted toward one pole edge. The armature necessarily
slows down during this operation, the field polarity of all
COMMUTATING POLES ON ROTARIES 189
the poles being shifted toward one pole edge. The position
'of maximum e.m.f . of the alternating-current end and also the
position of maximum alternating-current flow may be shifted
to a certain extent also. In consequence, the magnetomotive
force due to the alternating-current flow will be shifted cir-
cumferentially a certain amount, while the direct-current mag-
netomotive force cannot be shifted, being fixed in position by
the brushes. In consequence, the alternating-current magneto-
motive force may not be in direct opposition to the direct-current
at this instant, and the resultant magnetomotive force may be
much higher than at normal condition. A moment later the
swing may be in the opposite direction; that is, the alternating
armature current may be greater than direct current and the
energy being received from the alternating-current system is
considerably greater than is given out by the direct current*
Again, the two magnetomotive-forces will not nearly neutralize
each other and there also will be field distortion, but in the
opposite direction, and again, the two magnetomotive forces
will not be in direct opposition to each other circumferentially.
If hunting is very severe, the resultant magnetomotive force of
the armature due to the inequality of the input and output, and
to the circumferential shifting of the magnetomotive forces
with respect to each other, may vary enormously and may pass
from positive to negative values periodically. It is evident that
under such condition the presence of an interpole may give much
worse results than if no interpole were present; for, as mentioned
before, if there is a magnetomotive force in the wrong direction
at the interpole, the interpole magnetic circuit apparently makes
conditions worse. In consequence, an interpole synchronous
converter should be especially well designed to avoid hunting*
All of the above considerations have taken into account only
the energy currents delivered to the alternating-current side of
the converter. Some consideration should be given to the effect
of wattless currents in connection with interpoles.
As is well known, when a synchronous converter has its field
strength improperly adjusted for the required alternating-current
counter e.m.f., alternating currents will flow in the armature in
such a way as to correct the effect of the improper field strength;
that is, if the field is too weak wattless currents will flow in the
armature which tend to magnetize the field of the converter.
These currents will be leading in the armature, but will be lagging
with respect to the Hue. On the other hand, if the converter
190 ELECTRICAL ENGINEERING PAPERS
field is too strong, these wattless or corrective currents will tend
to weaken the field and will lag with respect to the armature, but
will lead with respect to the line. These corrective currents
will have a lead or lag of 90 deg. with respect to the energy
currents. Their magnetomotive forces also will have a lead or
lag of 90 deg. from the magnetomotive force of the energy com-
ponent of alternating-current input. As this latter practically
coincides with the direct-current magnetomotive force, which is
midway between the main poles, the corrective armatur.e cur-
rents will have a maximum magnetomotive force practically
under the middle of the main poles and therefore become purely
magnetizing or demagnetizing due to such position* Also,
being at right angles to the energy component, the magneto-
motive forces of the corrective currents will have zero value
where the energy component has maximum, and therefore
should have no direct effect upon the resultant magnetomotive
force midway between the main poles, or under the interpoles
if such are used. It might be assumed therefore that the usual
wattless or corrective currents, which the converter may carry
on account of improper field strength, will have no direct harmful
effect on the commutation- However, there ar6 apparently
some indirect effects due to this corrective current, for when a
converter is operated at a bad power-factor, either leading or
lagging, there is generally more trouble at the commutator and
brushes than when a high power-factor is maintained.
It has been shown that the maximum possible benefit to be
derived from interpoles in neutralizing armature reaction is much
less in synchronous converters than in direct-current generators.
In direct-current generators and motors interpoles have also been
oi great advantage, due to variable speed and variable voltage
requirements- In synchronous converters, however, the re-
quirement of variable speed is obviously absent and that of
variable voltage very limited. The converter has constant
voltage characteristics and variable voltage can only be obtained
through the agency of such relatively expensive devices as in-
duction regulators, synchronous boosters or split-pole construc-
tions. The advantages of interpoles in synchronous converters
are then to be looked for only in the direction of increased -outputs
and higher speeds.
COMMUTATING POLES ON ROTARIES 191
DISCUSSION
Some question has been raised this evening regarding the
statements in the paper that in case of sudden overload or short
circuit the alternating-current and direct-current magneto-
motive forces will not balance each other and that the machine
will operate momentarily as a direct-current generator, with a
correspondingly high armature reaction. The basis of the
criticism is that the converter, being a synchronous machine,
cannot change its speed except for a very short period, namely,
that occurring within a small fraction of one cycle, otherwise
the machine would fall out of step. For such a small change in
speed, it Was argued, very little energy could be given up as a
direct-current generator, as there is not enough stored energy in
the converter armature to giv0 up much energy as a direct-cur-
rent generator without falling OUT; of step.
At first thought, such an argument seemed reasonable, but
one answer to it is found in the operation of a synchronous con-
verter on a single-phase circuit. In such operation the energy
supplied to the alternating current end falls to zero twice in each
cycle, while the direct-current output remains practically constant.
The alternating-current input must therefore vary from zero
to far above the direct-current output of the machine. The
converter must therefore act as a direct-current generator, for a
brief period, twice during each cycle. When it is considered
that such a converter can operate with more or less spkrking up
to three or four times full-load current, or even much more,
depending upon the design of the machine, it is obvious that the
converter can deliver very heavy outputs momentarily as a
direct-current machine without falling out of step.
Also, a little calculation will show that with an ordinary design
of synchronous converter the stored energy in the armature is
such that, in dropping back as much as 45 electrical degrees in
position, the armature could give up an enormous energy com-
pared with its normal rated capacity. If it were not for this it
would not be possible to run the machine on heavy load on a
single-phase circuit.
That is all I will say in regard to the points brought up in the
discussion. However, there are several points I want to bring-,
out in connection with the paper itself. In the first part of the
paper it is stated that the ampere turns on the interpoles of a
direct-current generator are always greater than the ampere
192 ELECTRICAL ENGINEERING PAPERS
turns of the armature winding. This statement is not correct in
all cases but in those arrangements which depart from this rule,
direct-current generators and converters would be affected in
the same way so that for comparative purposes the statement
in the paper may be considered as correct.
When there are as many interpoles as there are main poles it is
correct to say that the ampere turns on the interpoles should
always be greater than on the armature. However, in some
cases, especially on small machines, the number of interpoles on
direct-current machines is made only half as great as the number
of main poles. There are several advantages in this arrange-
ment and they apply equally well to generators and synchronous
converters. Obviously where only half as many interpoles are
used the commutating flux or field of each interpole must be at
least twice as strong as when the full number of interpoles is used,
as the opposing e.m f . set up by the interpoles must be sufficient
to overcome the e m.f . of self-induction, regardless of the number
of interpoles. This opposing e.m.f. need not be distributed
over the whole armature coil, but could be located over either
side of the commutated coils or even along a short portion of
its length. It is only necessary that this opposing e.m f . should
have the proper value, while the distribution of it seems to be of
relatively less importance. It should be understood, however,
that the use of half the interpoles is permissible only with drum-
wound armature windings, where each armature coil spans
approximately one pole pitch. Ring-wound armatures require
the full number of interpoles.
Experience shows that when but half the number of interpoles
is used the demagnetizing ampere turns, or those which directly
oppose the armature magnetomotive force, should have about
the same value per interpole as when the full number is used.
However, the effective ampere turns which set up the commu-
tating flux must be doubled in value, as just stated. Therefore
the total ampere turns per interpole would be greater than when
the full number of interpoles is used, but the total number of
ampere turns on all the interpoles is much less than with the
full number of interpoles. In consequence, there is a very con-
siderable saving in the amount of copper required.
On account of the increased number of ampere turns per
interpole when half the number of poles is used, the interpole
leakage will be increased in proportion. This is particularly
COMMUTATING POLES ON ROTARIES 193
objectionable on large machines where the design of the inter-
pole becomes difficult on account of magnetic leakage. There-
fore this arrangement is usually confined to small machines.
A very considerable advantage in this arrangement is that
the ventilating conditions are improved due to the fact that the
interpoles and main poles do not so completely enclose the arma-
ture, for, with alternate interpoles omitted, the circulation of air
between the armature and the field poles can be materially im-
proved.
With interpole converters, with their smaller ampere turns
per interpole, the omission of alternate interpoles will not have
as much influence on the general design as in the case of direct-
current generators. As the interpole ampere turns are only
about 35 per cent, as great as on a direct-current machine, and
as about half is useful and half demagnetizing, it is evident that
the useful component would readily be doubled, thus doubling
the useful flux, while the total leakage would still be far less on a
direct-current machine. Therefore the smaller number of inter-
poles is much better adapted to the synchronous converter than
to the direct-current generator.
In the converter the use of the small number of interpoles
also possesses a further advantage. In the case of a short cir-
cuit, and assuming a negative field to be set up by the armature
reaction, as described in the paper, the use of half the number of
interpoles would cut this reverse field to half value. In conse-
quence, any flashing tendency would be proportionately re-
duced. Half the neutral spaces being without interpoles, and
the other half having interpoles, it is evident that such an
arrangement should be practically midway between a non-inter-
pole and a full interpole converter as regards any flashing
tendencies.
It is also evident that with half the number of interpoles the
ventilating conditions will be improved just as on the direct-
current generator.
The lower leakage in the interpoles of the converter allows
another material difference between the design of the converter
interpoles and those of tie direct-current generator. In ordinary
direct-current generators, especially those of large capacity,
the interpoles, as a rule, are made almost the full width of the
armature core, principally in order to maintain a lower satura-
tion of the interpole core. As the width u i the interpoles is
194 ELECTRICAL ENGINEERING PAPERS
varied the leakage flux varies practically in proportion to the
-width, but the total useful flux remains practically constant.
Therefore, with wider interpoles the flux density due to the com-
bined leakage and useful fluxes will be lower than if a narrower
pole were used, and the saturation will be correspondingly re-
duced. In the interpole converter, however, the leakage flux
being so much lower than in a direct-current generator, it is
evident that the useful flux could be correspondingly increased
while maintaining no higher saturation than on a direct-current
machine. This, therefore, permits a much narrower interpole
on the converter than on a direct-current machine. As the
interpole becomes narrower than the armature the reverse
field which may be set up on short circuit also should be pro-
portionately reduced, so that with interpoles of practically
half the width of the armature, the conditions should be practi-
cally equivalent to those where half the number of poles is used,
as far as flashing conditions are concerned The use of narrow
interpoles should also allow better ventilation than when the
full width is used. Narrower interpoles, of course, allow con-
siderably less copper for the same total number of ampere turns
However, unless the interpoles can be made less than half the
width of the armature, the amount of copper required for this
arrangement would be still greater than would be required with
only half the number of interpoles, each of full width of the
armature.
There are many other points in connection with the use of
interpoles on converters which were not mentioned in this
paper. I will describe briefly a few interesting features which
are encountered in the design of such machines, but which are
not found in direct-current machines.
One of these concerns the application of dampers to interpole
converters. It is found that the usual distributed cage type of
damper supplied with self-starting converters is not directly
applicable to the interpole converter Dampers are supplied
to synchronous converters for two purposes, namely, to prevent
hunting and to obtain good self-starting conditions. To prevent
hunting the damper should be thoroughly distributed through
and around the pole face in the form of numerous low resistance
bars or rods which are joined together at each end by low re-
sistance connectors. There may or may not be any connection
between the dampers on adjacent poles. In practice, with well
COMMUTATING POLES ON ROTARIES 195
proportioned dampers, such connection between the poles may
be of some benefit, but this is difficult to determine as far as
hunting is concerned. Those conductors embedded in the pole
and immediately surrounding it appear to give all the damping
action which is necessary if the damper is well proportioned.
However, when it comes to self-starting converters, that is,
those which are started and brought up to speed by direct
application of alternating-current to the collector rings, it is
claimed by some designers that the interconnection between
the adjacent dampers is of benefit at the moment of starting,
by reducing the tendency toward dead points or points of very
low starting torque. When started in this manner the armature
of the converter becomes the primary of an induction motor,
while the cage damper in the field poles becomes the equivalent
of a cage winding on the secondary of an induction motor. It
is claimed that the interconnection between the dampers to
form a complete cage allows better polyphase action in the
secondary winding. Any beneficial result of this should show
in more uniform torque at start, but not to any pronounced
extent in the apparent input required to start the converter
and bring it up to speed.
When hunting occurs the magnetic field in the main poles is
alternately shifted or crowded toward one pole edge or the other
and the parts of the damper embedded in and immediately
surrounding the pole face aare particularly effective in preventing
such shifting. Also, the lower the resistance and the better
distributed this damper, the more effective it appears to be in
general as regards damping.
On the other hand, for self starting, the damper, acting as a
cage secondary of an induction motor, will have the character-
istics of such secondary and therefore for best and most uniform
starting torque conditions, a relatively high resistance is de-
sirable and a continuous cage is usually preferred. In conse-
quence, the two conditions of best damping and best starting
are, to a certain extent, opposed to each other.
In the use of a continuous cage damper is found a difficulty
in the application of interpoles to the synchronous converter.
If adjacent dampers are connected together, as shown in Fig. 1
then the interpole between the two main poles is actually sur-
rounded by the low resistance damper circuit, a condition which
is very objectionable, as explained in the paper. Conse-
196
ELECTRICAL ENGINEERING PAPERS
quently, tlie usual arrangement of the cage damper for
self starting is not advisable on an interpole con-
verter which is subject to sudden fluctuations in load. In
other words, the continuous cage damper should not be used,
or its design should be modified very considerably, in the case of
self-starting converters, which are subject to considerable
fluctuations in load in service. If the continuous cage construc-
tion is desired, the individual dampers might be connected
together by high resistance connectors.
A second interesting point in the design of interpole converters,
but not found in direct-current generators, comes up in connec-
tion with the copper loss in the tap coils, that is, those armature
coils which are tapped directly to the collector rings. As is well
known to those familiar with synchronous converter design,
the copper loss in the tap coils
of a rotary is relatively high
compared with the average loss
in all the coils, the loss per coil
falling ofi to a minimum value
between the taps. The real
limit in carrying capacity of the
armature is fixed by the heating
of the tap coils and not by the armature copper as a whole.
It is possible to overload an armature so that the tap coils will
roast out while the remaining coils will show very much less
signs of heating. The heating in these tap coils also increases
rapidly as the power-factor of the alternating-current input is de-
creased, the output remaining constant. Therefore by reducing the
power-factor of a converter while keeping the direct-current
output constant it is possible to roast out the tap coils. The
true limit of heating in a converter armature therefore is found
in these coils. Herein is found a difference between the inter-
pole and the usual non-interpole converter. In the non-inter-
pole type, as usually constructed, the armature coils are of the
fractional pitch or "chorded" type in which the "throw" or
"span" of a coil is one or more slots less than the pole pitch.
The primary object of this is to improve commutation. In the
ordinary direct-current winding there are two coils in each slot
one above the other. With a full pitch winding, when the
upper coil is being commutated or reversed the lower coil in
the same slot is also being reversed so that the e.m.f. of self-
FiG. 1
COMMUTATING POLES ON ROT ARIES 197
and mutual-induction of the commutated coils is due to the
reversal of the local field of both upper and lower commutated
coils in the slot. With a fractional pitch winding, the upper
coil which is being commutated lies in a different slot from the
lower one which is being commutated at the same instant.
This same arrangement of fractional pitch winding puts the
upper tap coil in a different slot from the lower one so that the
maximum heating does not occur in the upper and lower coils
in the same slot, as would be the case if a full pitch winding were
used. Therefore, with a fractional pitch winding the heating
is somewhat better distributed than in the full pitch winding.
However, with interpoles, a full pitch winding would naturally
be used, as a fractional pitch winding would mean a relatively
wide interpole with a corresponding increase in distance between
the main poles. Therefore with the full pitch winding used with
interpole converters the heating due to the tap coils will be more
concentrated than in the non-interpole type. In other words,
the machine will have less maximum capacity unless more copper
is used in the armature coils, or an inferior type of interpole
construction is used in order to allow a fractional pitch winding.
This looks like a minor point, but when it is borne in mind that
in modern converter designs the starting point in the design of
the armature winding is the permissible copper loss in the tap
coils, and not the armature copper loss as a whole, the import-
ance of this point may be seen.
A third point, not mentioned in the paper but which concerns
design as well as operation, is found in self-starting converters.
In such machines the alternating current is applied directly to
the alternating-current end of the converter and a rotating mag-
netic field is set up, just as in the primary of an induction motor.
This field travels around the armature at a speed corresponding
to the frequency of the supply circuit and the number of field
poles and all the armature coils in turn are cut by this traveling-
field. Those coils which are short circuited at the commutator
by the brushes form closed secondary circuits and secondary
currents are set up by the alternating field just as in commu-
tating type alternating-current motors at start. As soon as the
converter gets in motion the short circuit is transferred from coil
to coil but the short circuit current must be broken as each coil
passes out from tinder the brushes and this results in more or
less sparking, depe&ding on the size and general proportions of
198 ELECTRICAL ENGINEERING PAPERS
the machine. It is a question to what extent this sparking is
dependent upon the normal commutating characteristics of
the armature winding. Other things being equal, presumably
the better these characteristics the less should be the sparking
and burning at the brushes when the converter is self started
from the alternating-current end. On this basis then, a con-
verter armature designed with poor commutating characteristics
and in which the commutation at synchronous speed is ac-
complished by interpoles, should spark considerably more when
starting than a converter which has inherently very much
better commutating characteristics. The presence of com-
mutatiag poles should in no way help commutation at start as
there is no current in the interpole winding. However, as con-
verters are started very infrequently, such increased sparking
at start would probably do but little real injury. This is simply
mentioned as one of the points in which the designer is concerned.
Some reference has been made this evening to the split pole
converter in connection with interpoles. Some distinction
should be made between the true interpole or commutating pole
arrangement referred to in this paper and what is sometimes
referred to as the interpole in the so-called "split-pole" con-
verter. In the split pole converter, as usually built, there is a
series of wide poles alternating with narrow poles, the field
construction therefore resembling somewhat the ordinary inter-
pole machine. In the split pole converter, however, the small
pole is used primarily for the purpose of obtaining variations
in the direct-current voltage and not for the purpose of ob-
taining a true commutating field. The winding on this small
pole on the split pole machine is usually in shunt with the
armature instead of in series, and its circuit is so arranged that
the polarity can be varied from maximum down to zero and to
maximum in the opposite direction regardless of the armature
current carried. In certain combinations this arrangement
can be made to have the effect of commutating poles, but under
other conditions it may have just the opposite effect.
The small pole is usually placed dose to one of the main
poles, thus allowing a fairly wide interpolar space between itself
and one of the adjacent large poles and a very narrow space to
the other large pole. Commutation occurs usually in the wider
interpolar space and not under the small pole itself as is the case
in the true interpole machine. The direct-current e,m.f. is
COMMUTATING POLES ON ROTARIES 199
generated by the resultant field due to one large pole and the
small pole which is closest to it. When these two have the
same polarity the direct-current e m.f . is highest and when they
are of opposite polarity it is lowest. However, the alternating-
current e.m f . is due to the flux of two adjacent poles, a large
and a small one of like polarity. It is evident therefore that
the maximum alternating-current e.m.f . will coincide in position
with the direct-current only at the highest direct-current e.m.f.;
that is, when both fluxes included in one direct-current circuit
are of the same polarity. At lowest direct-current e.m.f . when
one direct-current circuit includes two fluxes of opposite polarity,
it is obvious that the maximum alternating-current e.m.f.
must be shifted tircumferentially with respect to the direct-
current. The alternating-current magnetomotive force will
also be shifted in like manner with respect to the direct-current
and the resultant of the two will vary both in height and position
with variations in the strength and direction of the flux of the
small pole.
At highest direct-current e.m.f. a coil which is being corn-
mutated lies midway between poles of opposite polarity and the
conditions resemble those in an ordinary converter as regards
commutation. At the lowest direct-current e.m.f. the commu-
tated coil lies midway between two poles of like polarity and
there will be a field flux in the interpolar space in which the
armature coil must commutate. The direction of this field
may be such that it will assist in commutation; that is, it will
tend to overcome the higher magnetomotive force of the arma-
ture currents resulting from the alternating-current and direct-
current magnetomotive forces being shifted with respect to
each other, as just mentioned. Therefore this interpolar field
flux may act in a very beneficial manner tinder certain condi-
tions. However, if this flux is in the right direction for assisting
commutation when transforming from alternating-current to
direct-current, it will evidently be in the wrong direction when
operating from direct-current to alternating-current. Also,
this field flux in the interpolar space will vary with any variations
in the strength of the small pole; that is, with any change in the
direct-current voltage, although the currents in the armature
may be unchanged. Also, this interpolar field may remain of
constant strength, while wide changes may occur in the armature
currents, and thus in their resultant magnetomotive forces. It
200 ELECTRICAL ENGINEERING PAPERS
is obvious therefore that this interpolar flux can be equivalent
to a true interpole of proper strength and polarity, only under a
very limited range of operation.
In conclusion I may say that, as brought out in the paper,
the real field for interpoles in synchronous converters is found
in connection with higher speeds and large outputs per pole.
I am an advocate of the highest speeds which the public will
stand, up to the point where no further real gain in cost and
performance is obtained. If this highest speed in converters
is such that interpoles are of material benefit, then in such ma-
chines we may look forward to the use of interpoles. However,
for the relatively low speeds represented by much of our present
practice the use of interpoles can be considered as only a rela-
tively small improvement, concerning which there may be honest
differences of opinion regarding the commercial value.
THEORY OF COMMUTATION AND ITS APPLICATION
TO COMMUTATING POLE MACHINES
FOREWORD — This paper was the result of many years of the author's
work on the subject of commutation. In its presentation, it
embodies a new method of looking at the problem. In this
method, the armature winding, as a whole, is considered as
setting up a magnetic field in the so-called neutral zone; and
it is, primarily, the e.m.fs. set up by the armature conductors
cutting this field, which are dealt with in this theory of commuta-
tion. Before the completion of the paper, the commutating con-
stants of many hundreds of direct-current machines of various
kinds were checked to determine the correctness of the method.
The paper was presented at a meeting of the American Institute
of Electrical Engineers, October, 1911.
Throughout this paper, it will be noted that the term "inter-
pole" was used in place of the present accepted term ' ' commutat-
ing pole" which came later. — (ED.)
IN the usual theory of commutation it is considered that ,
when the current in a coil is commutated or reversed, the local
magnetic flux due to the current reverses also, and in so doing
sets up an e.m.f. in the coil which opposes the reversal. This is
the so-called reactance voltage referred to in commutation prob-
lems. The fact that two or more coils may be undergoing
commutation at the same time involves consideration of mutual
as well as self-induction. The relation of the mutual to the self-
induction, the probable value of each, etc,, lead to such mathe-
matical complication in the analysis of the problem, that em-
pirical methods have become the usual practice in dealing with
commutation. The usual analytical methods do not permit a
ready or easy physical conception of what actually takes place.
According to the usual theory, during the commutation of the
coil the local magnetic flux due to the coil is assumed to be
reversed. However, in the zone in which the commutation
occurs, certain of the magnetic fluxes may remain practically
constant in value and direction during the entire period of com-
mutation.
The fact of part of the flux in tbe zone of commutation
remaining practically constant in value and direction, led the
author to a method of dealing with the problem of commutation
which is based upon consideration of the armature flux as a
201
202 ELECTRICAL ENGINEERING PAPERS
whole, as set up by the armature ampere turns. The results
obtained by the method were very satisfactory, and it was ap-
parent that a much better conception could be obtained of some
of the phenomena of commutation than was possible with former
methods.
In the following pages the method is indicated in general,
and its application to interpole machines is then worked out in
greater detail. In non-interpole machines the problem is greatly
complicated by the presence of local currents under the brushes
which modify the distribution of certain of the armature magnetic
fluxes, as will be shown.
This theory of commutation, with the method of calculation,
is based upon the broad principle of the armature conductors
cutting across the magnetic field %et up by the armature "winding and
thereby generating an e.mj. in the short circuited coils which w
proportional to the product of the revolutions, the flux which is cut
and the number of turns in series. The usual " reactance "
voltage due to reversal of the local flux of an individual coil is
not considered, although its equivalent appears under another
form.
The method in general is therefore the same as that used for
determination of the main armature e.rn.f., except that the
magnetic fluxes cut by the armature conductors are those due to
the armature magnetomotive force instead of those due to the
field.
When the armature winding is carrying current its magneto-
motive force tends to set up certain magnetic fields or fluxes,
which have a definite relation to the position of the brushes.
Considered broadly, the current after entering the commutator
or armature winding, at any brush arm, divides into two paths-
of opposite direction. As the winding on each of these paths is
arranged in exactly the same way, and as the currents flow in
opposite directions, the armature windings in these two paths
have magnetomotive forces which are in opposite directions.
The resultant armature magnetomotive force rises to a maximum
at points corresponding to the brush positions. Midway between
these points the magnetomotive force is zero. Magnetic fluxes
are set up by these magnetomotive forces, which are a function
o£ the force producing them, and the proportions, dimensions,
and arrangement of the magnetic paths; and these magnetic
fluxes will be practically fixed in position corresponding to the
brush setting.
THEORY OF COMMUTATION 203
The armature conductors cutting across these fluxes set up by
the armature magnetomotive forces, will have e.m.fs. generated
in them. In those conductors which have their terminals short
circuited by the brushes, these e.m.fs. may be called the short
circuit e.m.fs.
There are three principal armature fluxes which are cut by the
short circuited armature coils. In the order of their usual
importance these are,
1. That which crosses from slot to slot. It may be called the
slot flux.
2. The interpoiar flux which passes from the armature surface
to the neighboring poles or yoke surface. It may be called the
interpoiar flux, as distinguished from interpole flux, ,which term
will be used later.
3. That flux set up in the armature end-winding in the zone of
the short circuited coil/ due to the magnetomotive force of the
end windings as a whole. It may be called the end flux.
The short circuited armature coils cutting across these three
fluxes generate the short circuit e.m.fs. The whole problem of
commutation may be considered as depending upon the prede-
termination of these three fluxes.
Consider, first, an armature conductor approaching the poini
of current reversal or commutation. Under this condition the
current carried by the coil always flows in the same direction
as the e.m.f. generated by the conductor cutting across the magnetic
field or flux set up by the armature winding is induced. When the-
terminals of an armature coil pass under the brush and are short
circuited, it is obvious that -the e.m.f. set up in the coil by the
armature flux is unchanged in direction for the coil is still cutting
a field of the same polarity. This e.m.f. tends to maintain the cur-
rent in the short circuited armature coil in the same direction as
before but the value the current attains will be dependent upon,
the short circuit e.m.f . and largely upon the resistance in the
circuit, which will usually consist of the resistance of the coil
itself and of the brush contact. As the coil passes out of short
circuit, that is, as it leaves the brush, the current must flow in
the opposite direction, but the e.m.f . set up by the armature
flux is still in the same direction as before. Therefore, after
commutation, the armature current in the coil is flowing in.
opposition to the e.m.f . set up in the coil by the armature flux.
The following is a method for calculating approximately the
three fluxes before described and the e^m-fs., generated by the
-204=
ELECTRICAL ENGINEERING PAPERS
armature conductors cutting them. The interpolar fluxes will
be considered first, the end fluxes second, and the slot fluxes
last, as these latter are greatly complicated "by the problem of
local currents produced largely by the interpolar and end fluxes.
INTERPOLAR ABMATURE FLUX
By- this is meant the flux in the interpolar space between the
armature core and the field poles and yoke, due to the magneto-
motive force of the armature winding, as shown in Fig. 1. This
magnetomotive force has its highest value at those parts of the
armature winding corresponding to the brush contacts on the
commutator and is zero midw;ay between such points. If the
brushes are set -with zero lead then the maximum magneto-
motive force of the armature lies midway between adjacent field
poles and will taper off in value from this midpoint toward the
\
FIG. 1
FIG 2
adjacent edges of the poles. The flux density between the arma-
ture surface and the sides of the poles should therefore tend to
taper off as the armature magnetomotive force is reduced but, in
most types of field construction, it tends to increase in value due
to the relatively shorter magnetic path as- the edges of the poles
are approached. Usually this increase very considerably over-
balances the decrease due to the lower magnetomotive forces
and in consequence the interpolar flux density due to the arma-
ture generally has a mini-cntrm value midway between the poles
and rises toward tte edges of the poles. This is illustrated by
Fig. 2.
The density of this fltut in the interpolar space is dependent
-upon many conditions such as the ampere turns of the armature
winding per poler distance between poles, conformation of the
poles, yoke, etc. In Fig. 2 the ordinates of the dotted lines
represent the flux densities at the armature interpolar surface
THEORY OF COMMUTATION 20o
due to each of the two adjacent poles. The resultant of these
two is the full line a c b which represents the distribution of the
armature inter polar flux. This interpolar flux might be con-
sidered as a true magnetic field fixed in space with respect to the
position of the brushes. This field being fixed and the, armature
conductors rotating it is obvious that any conductor moving
across this magnetic field must have e,m,f. generated in it, the
value of which depends upon the flux which is cut at any instant.
Therefore, the e.m.f. due to this interpolar field can be de-
termined directly, if the intensity of the field itself can be cal-
culated.
During the period of commutation the armature ooil is short
circuited and has the current reversed in it under certain por-
tions of this field. The problem is to determine the strength of
the field corresponding to this point of com-
mutation and then by direct calculation the
corresponding e.m f. can be determined.
In the following analysis two cases will be
considered, namely, pitch windings, and
" chorded " or " fractional pitch " windings.
Pitch Windings. When commutating or
reversing a coil with a pitch winding it is
evident that if there were no lead at the
brushes such a coil would commutate, on
the average, at the midpoint between two
poles. The e.m.f. generated in the coil by cutting the interpolar
field would therefore be proportional to the strength of the inter-
polar flux at the midpoint. This flux can be determined approx-
imately in a fairly simple manner in the ordinary types of machines
in which the poles are relatively long compared with the distance
between adjacent pole tips and where the distance from the arma-
ture surface to the yoke is relatively great. The following is
a method which appears to give reasonably close results:
Let Wt = total number of wires on the armature.
!<, =the current per conductor.
p = number of .poles.
Then, the armature ampere turns per pole =• — C0 * r
Ap
neglectifig any change in ampere turns due to the short circuit-
ing action of the brushes.
In Fig. 3 let b represent the length of the mean flux path
corresponding to the mid-interpolar position. This is assumed
208 ELECTRICAL ENGINEERING PAPERS
to" be a part of a circle which is poetically at right angles to the
armature surface and the side of the field pole, as indicated in
Pig. 3.
Let P = widt& of body of pole.
Let .Bt — the flux density at the midpoint between the poles.
2X3 197.X TV*
Then E^--
2pb
But 6 = 27ra QZ. . approximately, as angle (90+0) is
OOU
only approximate.
Also, a = ( 0 — — ) approximately.
\ & p £i I
Therefore
Therefore
2X3.197.
-B,—
(0.25£+0.5) (IT D-Pp)X2 p
The above gives the approximate flux density at the midpoint
tetween poles. The flux densities at points at each side of the
midpoint can be determined in a similar manner, taking into
account the lower armature magnetomotive force as the mid-
point is departed from. As the edge of the pole is approached
the effect of pole horns may complicate the flux distribution so
that the above method of calculating interpolar flux density will
not apply for points close to the pole.
E,mj. Due to Interpolar Flux.
Let Ec- The e.m.f. due to cutting the armature flux.
D = diameter of armature.
L = length of core including ventilating spaces.
Tc = turns per individual armature coil.
Rs — revolutions per second.
THEORY OF COMMUTATION 207
Then, the e,m f . induced in a coil cutting the field at c (Fig. 2)
can be represented by the formula,
TcXRs
c 10
Or,
27rDLTcRs
' (0.25^+0.5) (irD-Pp) ~ 108
Or
IcWtTcRs / ZpXirDL
L \
D-Pp) )
108 \ (0.25p+0.5) (irD-Pp)
Incidentally, with this method of dealing with the problem
the effect of the addition of an interpole can at once be seen.
The magnetomotive force of the interpole is superimposed on
that of the armature and the resultant flux is then considered.
The armature conductors cut this flux and thereby generate
e.m.f. If the interpole magnetomotive force is stronger than
that of the armature, then the flux established will be in the
opposite direction in that part of the armature face which lies
under the interpole. Therefore, the flux or field over the com-
mutated coil in the non-commutating pole machine is replaced
by flux in the opposite direction. The presence of the interpole
does not increase the reactance of the armature coil as sometimes
considered, but, on the contrary, the harmful flux is replaced by
one which is of direct assistance in commutation.
Effect of Brush Width. In cutting across the interpolar flux
it is obvious that the e.m.f. set up in the short circuited coil is
not a function of the length of time the coil is short circuited,
for this interpolar flux is set up by the armature winding as a
whole and not by individual coils. If two or more armature
•coils in series are short circuited by the brush, then their e.m.fs.
will be in series while the total resistance in the path will be very
little higher than in the case of a single coil short circuited, for
the principal part of the resistance lies in the brush contact. It
is evident therefore that considerably higher short circuit cur-
rents can be set tip by the interpolar field when more commutator
bars, and more turns, are short circuited. It can therefore be
assumed that, as far as the interpolar field is concerned, the more
208 ELECTRICAL ENGINEERING PAPERS
commutator bars the brush covers the greater will be the short
circuit current and the greater will be the difficulty in commuta-
tion, assuming there is no external field assisting commutation
Chord Winding. With a pitch winding, with no lead at the
brushes, the commutation of a coil will occur in the lowest part
of the armature interpolar flux, as a a in Fig. 4. With a chorded
winding, as indicated at b b, the commutation will occur under
somewhat higher flux than with a pitch winding. Therefore in
considering the interpolar flux a full pitch winding commutates
linder better conditions than a chorded winding.
END FLUXES
The armature winding as a whole sets up certain fluxes in the
end windings. These fluxes are fixed in position with respect
to the brushes, and the armature coils, in cutting across, them,
generate e.m.fs. The only part of these end fluxes concerned in
FIG. 4 FIG. 5
the present problem is that which, the commutating coils cu£
during the operation of commutation.
Fig. 5 illustrates an armature winding na which the heavy
lines represent two coils in contact with the brushes and there-
fore at the position of commutation. It is only the end flux
density along the shaded portion or zone of this diagram which
need be considered. If the various densities for this zone can
be determined, then the e.m.f. in the commutated coil can be
calculated. 0nly the usual cylindrical type of end windings
will he considered, as practically all direct current machines at
the present time use this type. Such windings are usually ar-
ranged iii two layers, the coils of which extend straight out from
the armature core for a short distance, usually | in. to If in.,
depending upon size and voltage of the machine, and then extend
at an angle to the core of 30 deg. to 45 deg. The conductors of
the upper and lower layers therefore usually He almost at right
angles to each other
THEORY OF COMMUTATION
209
Pitch Winding Let Fig. 6 represent a single coil of the end
winding located in the commutating zone. Both theory and
test show that the maximum flux density in this zone is at a
and tapers off slightly to 6, then tapers off more rapidly from
b until it reaches practically zero value at c. It may be assumed
with but little error that the decrease from b to c is at a practi-
cally uniform rate. The flux density along the commutating
zone of the end winding may therefore be represented by Fig. 7,
in which the ordinates represent flux density. On the above
assumption the total flux in the commutating zone of the end
winding can be determined with sufficient accuracy if the density
at b, for instance, can be determined and the distances a b and
c d in Figs. 6 and 7 are known. These latter can be determined
directly from the winding dimensions.
FIG. 6
FIG. 7
The following is an approximate formula for the flux density
at b, including allowance for proximity of iron end plater core, etc.
N — number of slots per pole.
Ic = current per conductor.
Wt — total armature wires.
D = diameter of armature.
Let a b = h, and c d = m.
Then the flux cut by one conductor at one end is
2.15-1, WtXlog 2N
Therefore the e.m.f. per single turn of the armature winding,
210
ELECTRICAL ENGINEERING PAPERS
due to the end flux, considering the end fluxes for both ends of
the core, becomes
m_ \ 2.15 lc Wt Xlog 2 AT ir D RSX2 Tc
TT D sin 6
10*
Or,
N\
X]
This formula is on the basis of non-magnetic paths around the
end windings, that is, with no bands of magnetic material and no
magnetic supports under the coils, The effect of bands over the
end winding is approximately equivalent to cutting the flux
path to half length for those parts of the
end winding covered by the bands. There-
fore, with bands, the diagram representing
flux density in the commutating zone of
the end winding would be as indicated in
Fig. 8. In this case the total flux corresponds ]\
to the total area of the curve including the
dotted portion Of course the actual flux
distribution would not be exactly as shown ^
in this diagram for there would be sonie
fringing in the neighborhood of the bands FIG. 8
The diagram simply serves to illustrate the
general effect of magnetic bands and an approximate method of
taking it into account.
The effect of a magnetic coil support will be very similar to
that of a steel band in reducing the length of path and therefore
increasing the flux in the neighborhood of the cpil support.
However, in case of magnetic bands over the winding and coil
supports under it the limit lies in saturation of the bands them-
selves. This usually represents a comparatively small total flux.
The coil support, however, would probably not saturate in any
case.
The above formula for end flux can therefore be corrected
for magnetic bands and coil supports by multiplying by a suit-
able constant to cover the increased flux".
It is obvious that the determination of the end flux is, to £
certain extent, a question of judgment and experience. No
THEORY OF COMMUTATION 211
iixed method or formula can be specified for all types of machines,
for this flux would be influenced very greatly by the bands, if of
magnetic material, and by the material, size and location of the
coil supports and their relation to the bands. Also, eddy cur-
rents may be set up in the coil supports which will influence the
•distribution of the end flux in the zone of the commutated coil.
However, in each individual case an approximation can be made
whioh will, in general, be much closer than would be obtained
from any empirical rule or by neglecting the effect of the end
flux altogether.
Chord Winding. The effect of chording the armature winding
is to slightly diminish the flux density in the commutating zone
which results in a slight reduction in the e.m.f . of the commu-
tating coil. But a relatively much greater gain is obtained
by the consequent shortening of the distance c d in Fig. 8 and
the corresponding reduction of the total end flux. Due to the
chording itself the flux density at b is reduced practically in the
ratio of i o AT ' where NI — number of slots spanned by the
coil. For example, if the full pitch is 20 slots and the coil
spans 18 slots, then the density at b will be reduced in the
t O/*
ratio of . s n =0.971 due to the chording itself; and the flux
18
along cd, Fig. 7, will be further reduced in the ratio of ^
Z\J
due to the shorter end extension. The average flux along c d
therefore will be reduced to 0.9X0.971 = 0.874, or about 87 per
cent of that of a pitch winding.
Effect of Brush Width. As in the case of the interpolar flux the
width of the brush, or the number of armature coils short cir-
cuited by the brush, has practically no influence on the e.m.f.
generated per turn. However, the total effective armature
iampere turns will be reduced slightly, if the average current in
the short circuited turns is less than the normal current. This
will have a very slight effect on the e.m.f.
SLOT FLUX
By this is meant the magnetic flux across and over the arma-
ture slots which does not extend to the yoke or field poles.
Two general cases will be considered; first, that in which no
local currents are present, which is the case in well designed
interpole machines; and second, that in which there are local
212
ELECTRICAL ENGINEERING PAPERS
currents set up in the short circuited coils, which is almost
invariably the case in machines without inter poles or some other
form of compensation. Also, pitch and chorded windings will
be considered.
SLOT FLUX WITH No LOCAL CURRENTS
Pitch Winding. Let Fig. 9 represent an upper and a lower
coil in the same slot, with, equal turns and currents. Then if
there is no saturation in the adjacent teeth the flux density across
the slot will be zero at the bottom of the lower coil and will
rise to a maximum value at the top of the upper coil. There
will also be a flux across the slot above the upper coil and also
from the top of the tooth as indicated in Fig. 9. The total slot
flux entering at the bottom of the teeth is therefore equal to the
total flux which crosses the two adjacent slots, plus the flux
crossing at the top of the slots. The interpolar fiux which ex-
D
a
d
fc
FIG 10
tends from the armature surface to the poles or yoke is not in-
cluded in this.
As this slot flux is practically fixed in position the armature
conductor in 'slot A, in passing from a to b must cut this flux.
It is obvious that the flux which crosses above the uppermost
conductor in the slot is cut equally by all the conductors in the
slot, as the coil passes from position a to position b; but the flux
crossing the slot below the uppermost conductor does not affect
all the conductors equally, and therefore, for simplicity of cal-
culation, an equivalent flux of lower value can be used which
may be considered as cutting -all the conductors equally.
Let d Fig. 10, represent the depth of the conductors of one
complete coil.
/ represent the distance between the upper and lower
coils.
a represent the distance from the upper conductor to
the core surface.
THEORY OF COMMUTATION 213
s represent the width of the slot, assuming parallel sides.
n represent the ratio of width of armature tooth to the
width of the armature slot, at the surface of the core.
Tc represent turns per single coil, or per commutator bar,
Cs represent the number of individual coils, or commu-
tator bars, per complete coil.
L represent the width of armature core, including
ventilating spaces.
Ic represent the current per armature conductor.
Then, ampere turns per upper or lower coil = /c Tc G.
~ . i fl .« 3.19 Ic TcXCs-L (2 d+f)
Total flux across coil space = - - — — - -- —*-
™ 1*1. -1
Flux across slot above coil =
Flux from tooth top across the slot is approximately,
3.19 Ic Tc C,iX2X0.54 ^n
Total flux above-upper coil=3:19 Ic Tc CSL
The sum of the two fluxes represents the total flux across one
slot which enters at the bottom of one tooth. As a similar flux
passes across the slot at the other side of the tooth the total
flux entering the tooth will be double the above and becomes
Total slot flux=2X3.19 I, Tf C. L <2 *+*+* '+L06 ' V">
5"
This total flux cannot t>e used directly in the calculations as
it does not affect all the conductors equally. It is therefore
necessary to determine equivalent fluxes for the upper and
lower coils which can be used instead of the above value.
For the lower coil the following value has been calculated:
JVM 1 J A 2X3.19 J.C TC CrS L ^., oOO J I *\
The equivalent flux= - (LSSSa+f)
And for the upper coil,
•r> - * ^ a 2X3.19Xi<T TC (*S-Lr ~ OOQ i
Equivalent flux = --- O< 0.833d
To these equivalent fluxes shotild be added the total flux
above the upper coil. This gives the total effective flux for the
upper and lower Coils. Then, for the lower coil,
214 ELECTRICAL ENGINEERING PAPERS
Total effective flux
-2X3I9A7- C,L
And for the upper coil,
Total effective flux
= 2X3197, T. C5Lxt0.833d+2a+108sVB)
The average value of the effective flux for the upper and
lower coils then becomes,
3i9/.rcc.L(2-67rf+f+4a+2-16aVir)
o
(This average effective value is approximately 80 per cent of the
total slot flux.)
On the basis of a pitch winding and the assumption that only
one armature coil is short circuited, that is, with the brush
covering the width of only one commutator bar, then the above
slot flux is cut by all the coils in the slot in passing through one
slot pitch. From this the e.m.f in the commutating coil due to
the slot flux can be calculated directly and may be expressed as
follows
& = — TTtr-^-X number of slots
But CsX number of slots = No of commutator bars
_ total number of conductors Wt
~
Therefore the above expression for e.m.f may be changed to the
form,
If it is desired to compare this expression with a certain well
known fonmda which has been much used heretofore* thea let
THEORY OF COMMUTATION 215
the quantity in the parenthesis in the above expression be repre-
sented by cx. The formula can then be changed to,,
r? /ON/Q IQVX \v^ Ic T<?^< number commutator
Xi - = (<& X o . lv X cx) X ™
It contains the same terms (except in the value of the constant)
for the expression of the e.m.f. which has been used heretofore
in determining the reactance of the commutated coil.
Effect of Brush Width or Number of Commutator Bars Covered
by Britsh. The above formulas are on the basis of the brush
covering only the width of one commutator bar. In this case
all the conductors of one slot cut across the entire slot flux in
passing, through one tooth pitch. However, if the brush covers
more than one commutator bar, then the full slot flux is not cut
in passing through one tooth pitch, and a movement greater than
one tooth pitch is required for full cutting. For example, if
there is one commutator bar per armature slot and the brush
covers a width equal to two commutator bars, then the total
cutting of the slot flux will take place in two tooth pitches.
Again, if there are three commutator bars per armature slot and
the brush covers the width of one commutator bar, then the total
cutting of the total slot flux would occur in one tooth pitch, while
if the brush covered two bars, the total cutting would occur in
1J tooth pitches; and if it covered three bars If tooth pitches
are required. In other words, the total cutting will occur in a
period corresponding to the number of commutator bars per
slot plus one less than the number of commutator bars covered
by the brush.
On this basis the correction factor for the slot e.m.f. should be
C *
expressed by the term ^ , * — — f where Cs = number of com-
~ —
mutator bars per slot, and B » = number of commutator bars
spanned by the brush. However, \*ith several coils per slot,
and with the brush spanning several bars, the rate of cutting of
the tooth flux for the entire period is not quite the same as the
rate for one tooth pitch. Taking this into account the correc-
Q
tion factor should not be equal to ~ . PJ — =-, but is slightly
- — I
greater. Up to four commutator bars per slot, and three bars
period of coeqsmtatlon is obtaitwd
factorv^ , ^ _^ t the overage slot e, m. 1 for the
216 ELECTRICAL ENGINEERING PAPERS
spanned by the brush the correction factor can be expressed by
1 1 *
the term 1-i — = — ^- — "7^~-
JJi txj L,s
Taking the lengthened period of reversal into account, it
would appear that a wide brush covering a large number of
commutator bars should be beneficial in reducing the e.m.f
generated by the slot flux. This is true where the local currents
ate very small, or are absent, as is the case in a properly designed
interpole machine. In a non-interpole machine where the local
currents in the short circuited coils may be relatively high, this
condition does not hold, as will be explained later.
The above formula for e.m.f. due to the slot flux should there-
fore be modified by multiplying by a factor which takes into
account the period of reversal as affected by brush width.
Chord Winding. The armature winding may be chorded one
or more slots and, in some instances, where there are several
coils side by side there has been chord-
ing of part of the conductors in the
slot. In Fig. 11 is illustrated the
conditions with one-slot chording
The total slot flux now occupies two
teeth instead of one. Therefore the
e.m.f. set up by cutting across this
slot flux will be approximately one-
half that which is obtained with a
full pitch winding, on the basis of the brush covering the
width of one ba/ only, for the e.m.f generated by cutting this
flux will be reduced in proportion as the period of cutting is
increased There is one slight difference from the flux distribu-
tion with a pitch winding, namely, that at the top of the teeth.
With a chorded winding this flux will be slightly greater than
with a pitch winding, but the total effect *of this difference should
be relatively so small that ordinarily the value need not be
changed. Therefore equivalent fluxes used with chord windings
can be taken the same as for pitch windings. In consequence,
the e.m.f , due -to the slot flux, with one-tooth chording, may be
taken as one-half that for a pitch winding, with the brush cover-
ing one commutator bar in both cases.
For two-slot chording the slot flux may be considered as oc-
cupying the space of two teeth only, while there will be a mag-
netically idle tooth at the center. The e.m.f . per coil actually
generated by cutting the slot flux will be, for part of the period
^General use of this factor, 1 + B^Cs C^ should, be avoided. It is not
applicable to all tyres or ccirbinaticns of vir dings Use instead the factor Divine averaee
THEORY OF COMMUTATION 217
the same as for one-slot chording, but there will be an inter-
mediate period where the slot e.m.f. is practically zero, which
does not occur with a one-slot chording or with a pitch winding.
The average results, however, should be practically the same as
if the total slot flux were actually distributed over three teeth
instead of two.
Effect of Brush Width with Chord Winding. In the chord
winding, when the brush covers two or more commutator bars,
the period of cutting the slot flux will be lengthened just as with
a pitch winding on the assumption of no local currents For
example, if there are three commutator bars per armature slot
and the winding is chorded one slot, then with the' brush covering
one .commutator bar, complete cutting of the slot flux will occur
in the space of six commutator bars. If the brush covers three
commutator bars instead of one, then complete cutting will occur
in the space of eight commutator bars, while in a corresponding
full pitch winding it would occur in ths space of five bars. There-
fore, the wide brush represents an improvement with the chorded
winding, but not to the same extent, relatively, as with the pitch
winding. This is on the assumption of absence of local currents
in the short circuited coils. *
Bands on A rmature Core. By the preceding method of analysis
the effect of bands of magnetic material on the armature core can
be readily taken into account. This effect represents simply an
addition to the total flux which can pass up the tooth and across
the top of the slots. From the ampere turns per slot, the clear-
ance between the bands and the iron core, the total section o± the
band, etc., the flux due to the band can be calculated This flux
can either be combined directly with the slot flu* already de-
scribed and the resultant e.m.f. can then be calculated; or, the
e.m.f. can be calculated independently for the baud flux alone
Magnetic bands on the 'armature introduce a complication into
the general e.m.f . formula due to the fact that in many cases the
flux into the bands Is such as to highly saturate the band material
at relatively low armature currents. This flux therefore is
usually not proportional to the armature ampere turns. If the
e.m.f. due to the band Sux is to be calculated separately, the
following formula can be used:
4& represents the total magnetic flux in the hand from the
armature core considering both directions from the tooth, then
2 <t>b N p Tc Rs .
^Considering chortling, the correction factor ^ — -:--= - = becomes
- —
-= - = -
&€ — J, *- j -f *>t — A -f «•
wheie K »» slots chorded X C*. For tie general case, where there aie Pf circuits and F
poles, the correction factor becomes - *+$ -
218 ELECTRICAL ENGINEERING PAPERS
This formula holds true for the band flux which passes throug
the one tooth in the pitch winding. Proper allowance must be
made for the effect of chord windings and brush width, which
can be done by the methods already described.
SLOT FLUX WITH LocAt CURRENT*
PitchWinding. In the prsceding analysis local currents have
not been included, as the method would be greatly complicated
by taking such currents into account. In the general method,
given below the effect of local currents in the short circuited coils
can be most easily shown.
As already explained, an armature coil, as it approaches the
short-circuit condition, has an e,m.f. generated in it by the inter-
polar and the end fluxes. After the coil is short circuited this
e.m.f , is still generated by the coil and naturally a local or short
circuit current tends to flow through the coil, brush contact
and brush. In addition, the work, or supply, current is being
furnished to the armature winding through the brushes. These
two currents are superimposed in the short circuited winding
in such a way as, to have a very pfonounced influence in the
distribution of the slot fluxes. This effect can be bast seen by
first determining the distribution of the work current in the
various parts of the short circuited winding on the assumption
of n& local current and second, determining the distribution
of the local currents on the assumption of no work current, but
with the same armature magnetomotive force as in the first assump-
tion. The two distributions can then be combined and the re-
sultant currents in the various parts of the short circuited coils
can be obtained.
Let Fig. 12 represent the first assumption in which no local
currents are present. In order to illustrate conditions to better
advantage, four commutator bars are assumed to be covered by
the brush. Uniform distribution of current over the brush con-
tact can be assumed in this case, as there are no local currents*
THEORY OF COMMUTATION
219
Tracing out the current in each short circuited coil in Fig. 12,
it will be seen that the current decreases at a uniform rate and
then rises in the opposite direction at the same rate until the
short circuit is removed The period of commutation is the
longest possible with this number of commutator bars short
circuited, and the brush conditions are ideal, as the current
density at the brush contact is uniform at all parts The above
are the conditions which the designer endeavors to obtain in the
construction of good Interpole machines, as will be shown later.
In Fig 13 the same arrangement of winding and brushes is
chosen as in Fig. 12 except that only the local currents are shown
and the values of these are assumed as proportional to the
e.m.fs. in the short circuited coils and the resistance in circuit. In
this diagram the current is a minimum
in the coils at the moment that short
circuit occurs, and rises to a maximum
value and then diminishes to zero value
again at the end of the short circuit
FIG 14
FIG 15
In Fig 14 the currents of Fig. 12 and 13 are supenmposed
The resultant currents in the various parts of the short circuited
winding are seen to rise after short circuit until a maximum value
is reached and then decrease rapidly and reverse to normal
value m the opposite direction. Therefore, the period from
normal value of the current to normal in the opposite direction
is very much shorter than when no local currents are present
It may therefore be considered that the period of reversal is
much reduced by the presence of the local currents, so that the
e rruf m the short circuited armature conductors generated by
the slot flux is proportionately increased, compared with the
value it would have in case the local currents were absent
These conditions can be shown possibly in a somewhat better
manner by curves a, b and c in Fig. 15 The curve a shows the
distribution of current in the short circuited coils without any
local currents Curve b shows the distribution of local currents
220
ELECTRICAL ENGINEERING PAPERS
while curve c shows the resultant of the two. The distance be-
tween d and/ on curve c gives the period of reversal from normal
current in one direction to normal current in the opposite direc-
tion. This period is much shorter than the full period repre-
sented by g f which would be obtained without local currents.
The period df, however, may not differ much from the period
of commutation with the brush covering the width of only one
bar, when the local current is high compared with the work cur-
rent. In such case the gain in the period of commutation which
should be obtained by means of the wider brush may be practi-
cally offset by the effect of the local currents which also increase
with the wider brush, so that over a considerable r£nge the
resultant of the two effects may be practically constant. This
is one indication why, in non-interpole machines, the brush
width may be varied over quite a range with relatively small
noticeable difference in the commutation. This may be il-
FIG. 16
FIG. 17
lustrated by Pig. 16, in which is shown the current conditions
with two to five bars spanned. In this figure a b, b c, c d, etc.,
each represent the width of one commutator bar. Therefore,
curve A, extending over the width ac, represents two bars
spanned. The period of reversal of the current from normal
value in one direction to normal in the opposite direction is
represented by g c for curve A , h d f or curve B, i e for C and
kf for D. A comparison of these values is interesting. Calling
a b the period of reversal with the brush covering one bar only,
then g c with two bars covered, is greater than a b. kdis also
greater than a &, but less than g c, while i e is slightly less than
ab, and kf is considerably less. However, the variation be-
tween g c and kf is much less than between a c and af which
would be the corresponding periods with no local currents.
It should be borne in mind that the above curves are only
relative, depending upon the comparative values of the local
and work currents and assuming a constant brush resistance'
THEORY OF COMMUTATION 221
which is not correct, but they serve. Do illustrate the general
principle This method of presentation is simply a skeleton of
the problem of commutation when local currents are present
in ths short circuited coils and it would be beyond the scope of
this paper to attempt a full solution.
Effects of Field Distortion. One of the " bugaboos " of the
designer of commutating machines has been the question of field
distortion. It has usually been considered that when the ma-
chine is loaded the magnetic field is more or less distorted or
shifted from its nprmal no-load position and that commutation
is affected by this distorted field.
To state the case plainly, the field distortion has practically
nothing to do with the problem. The distorted field magnetism
is simply a resultant of the no-load main field flux combined
with that due to the armature winding. Therefore, the two
components of the distorted full-load field are the no-load main
field, which is fixed in space and is usually practically constant,
and the armature field, which is also fixed in space but varies
with the load. If the brushes are set in a certain position with
respect to the no-load field, then, as this component of the re-
sultant full load field is practically fixed in space and in value,
It has no variable influence on the commutating conditions.
The true variable element which does affect the commutation
is the armature field, or flux, and it is in this very flux which is the
basis of the preceding theory of commutation. Therefore, the
distorted resultant field of a loaded machine does not present
any new condition in the problem of commutation. Ose ex-
ception, however, can be made to the above, namely, where
there is any considerable saturation in the armature teeth or
in the main field pole corners. The effect of the armature mag-
netomotive force is to strengthen one corner or edge of the field
pole and to weaken the other edge, but when saturation is pro-
nounced the strengthening action is much less than the weaken-
ing action. The resultant of these actions is a decrease in the
total value of the main field flux. If, now, this main field flux
be brought back to its normal total value, or higher, a very con-
siderable addition to the main field magnetomotive force will be
necessary, which wilt be effective in increasing the field flux at
the weaker pole corner to a much greater extent than at the
highly saturated pole corner. In consequence, with load, the
main field distribution, or field form, may be considered as being
changed from its no-load form A, to the fonn B, as indicated
in Fig. 17. It is, in reality, strengthened at a point b, for
222 ELECTRICAL ENGINEERING PAPERS
example. In such case the main field will have a variable in-
fluence on the commutation, if the brush is set with a lead, as
at &, and, to a slight extent, the effect of an interpole is thus
obtained.
Effect of Brush Lead. Before taking up the problem of inter-
poles on direct current machines it might be well to consider the
effect of brush lead, as this gives a result intermediate between
true intsrpole and non-interpole commutating conditions.
The precedmg formulas apply to non-commutating pole
machines without brush lead. However, except in case of re-
versing machines, such as street railway motors, or hoist motors,
etc., it is usual practice to give a forward lead to the brushes
of direct current generators or a slight backward lead to direct
current motors. The effect of giving a lead at the brushes of a
non-interpole direct current machine may be considered as
being equivalent to the effect of an interpole with the exception
FIG. 18 FIG. 19
that correct flux conditions and proper commutation, with any
given brush setting, are obtained only for one given load.
As described before, with a non-interpole machine the arma-
ture winding sets up a flux in the interpolar space. With no-
lead at the brushes this flux is usually a minimum midway be-
tween the poles and ris,es toward the polar edges. The flux
from the adjacent main poles has a zero value midway between
the poles and rises toward the polar edges, but has opposite
polarities at the two sides of the midpoint. This is illustrated in.
Fig. 18. The resultant of the armature and field fluxes is indi-
cated by the dotted line A. This resultant falls to zero at one
side of the midpoint and then rises in the direction opposite to
that of the flux due to the armature ampere turns. At the other
side of the midpoint the two fluxes add, giving an increased re-
sultant flux m the same direction as the interpolar flux due to the
armature. Prom this figure it is evident that if the point of
THEORY OF COMMUTATION 223
commutation is shifted from a to the point of zero interpolar
flux 6, then commutation will occur without any interpolar flux
to be taken into account, that is, the e.m.f. generated by the
short circuited armature conductors may be due to the slot and
end winding fluxes only. If the brushes are shifted still further
in the same direction to c, then, not only will the interpolar arma-
ture flux be annulled but a flux in the opposite direction would be
cut by the short circuited armature conductor, which will gen-
erate an e.m.f. in opposition to that due to the armature fluxes
in the slots and end windings. Consequently, the commutation
can be materially assisted by such lead at the brushes.
The difficulty in the use of this method of commutation lies
In the fact that the commutating or reversing flux at c is the
resultant of the main field flux and tha armature interpolar flux
at this point, and the latter flux varies with the load, while the
former remains practically constant. Therefore the zero point
of the resultant field shifts backwards or forwards with change in
load and the density of the commutating field beyond the zero
point will therefore change with the armature current. In con-
sequence, if the brushes are shifted into a suitable resultant field
c at a given current, then with a different load the intensity of
this field at c will be changed, and unfortunately the change will
be in the opposite direction from that desired. In other words,
the density of this resultant field will decrease with increase in
load, whsreas just ths opposite effect is desired for good commu-
tation over a wide rangs in load.
In practice, however, an average condition is found which, in
many cases, will give reasonably good commutation over a rela-
tively wide range in load. The brushes may be shifted at no-
load into an active field in such a way as to generate an e.m.f.
in the armature coils of a comparatively high value. This
e.m.f. will circulate considerable local current through the brush
contacts and the amount of lead which can be given is dependent,
to a certain extent, upon the amount of local current which can
thus be handled without undue sparking
As the load is increased the strength of the resultant field,
corresponding to this brush position, will be decreased, and with
some value of the current this field will be reversed in direction.
At this point the e.m.f due to this field is added to the e.m.f.
due to the slot and end winding fluxes. Obviously the limiting
condition of commutation will be reached at a much higher cur-
rent than, would be the case if ao load at all had been given. This
condition is represented in Fig. 19, in which curves 1, 1, 2, 2, 3, 3,
224 ELECTRICAL ENGINEERING PAPERS
etc., represent the armature and resultant flux distributions with
various loads. In this figure the brushes are given a lead so that
commutation occurs at a point corresponding to b.
It is obvious that at heavy load a still greater lead at the
brushes might give improved commutating conditions. How-
ever, if the load were suddenly removed without moving the
brushes toward a, then the short circuited coils would be cutting
the main field at such density that serious sparking or flashing
might occur.
One serious objection to this method of commutation is that
the distribution of the resultant field is practically such that
equally good commutation cannot be obtained for all the coils
in one slot when there are several coils or commutator bars per
slot. All the coils of one slot must pass under a given position
or value of the interpolar magnetic field at the same instant,
while the commutator bars to which these coils are connected
must pass under the brush Consecut-vely. If the field intensity
is just right for good commutation a$ the first coil per slot
passes under the brush, then it may be entirely too great by the
time the last coil is commutated. For good commutation with
a number of coils in one slot, the resultant interpolar flux should
have practically constant- value over the whole range repre-
sented by the period of commutation of all the coils in one slot.
This condition, however, is extremely difficult, or is frequently
impracticable, to obtain with the ordinary non-interpole ma-
chine.
The above treatment of the problem of the effect of the brush
lead has been based upon the armature interpolar magnetic
field being located in the same position with lead as when there
is no lead at the brushes. It has been assumed heretofore that
the non-interpolar flux due to the armature winding has a mini-
mum value midway between the main poles and rises uniformly
toward two adjacent pole corners. This, however, is only true
when the point of commutation, or brush setting, is midway be-
tween the poles. When the brushes are shifted toward either
pole the point of maximum armature magnetic potential is
shifted in the same way. This means that the distribution of
the armature interpolar flux will be modified directly by the
position of the brushes. Instead of rising uniformly toward th3
two pole corners, with a minimum value midway between, it
will have a minimum at one side of the midpoint, this being at
the opposite side from the point of brush contact, and will have
THEORY OF COMMUTATION * 225
an increased value on the side toward which the brushes are
shifted. This is illustrated in Fig. 20 in -which A represents the
armature .interpolar flux distribution with the brush at a, while
B represents it with the brush at b.
This increased armature interpolar flux due to the brush
shifting means that the resultant interpolar flux due to both the
armature and main field fluxes will cross the zero line at a point
further removed from the midpoint than in the case of no lead
at the brushes. Consequently, in order to obtain a given useful
commutating field the brushes must be given a greater amount of
lead and this in turn shifts the zero point still further Thus,
the act itself of shifting the brushes makes the commutating con-
ditions more difficult.
The calculation of the comrnutating conditions with any given
lead therefore resolves itself into a determination of the re-
FIG 20
sultant fluxes in which the coil is short circuited or commutated
and the e.m fs generated by such fluxes. For the slot and end
winding fluxes the calculation will be the same as for no-lead at
the brushes The resultant flux in the interpolar space is the
only condition which will introduce any variation from the pre-
ceding formulae and methods of calculation This part of the
problem resolves itself simply into the determination of the
resultant interpolar flux at the point of commutation for any
given load The corresponding e.m.f can then be calculated.
This, combined with the e.m.fs. due to the slot and end windings,
gives the total short-circuit e.m.f The method is, in principle,
exactly the same as given before, except that the determination
of the interpolar flux will be modified.
Summation of Formula In order to obtain the total voltage in
the short circuited coil a summation should be made of the four
separate voltages which have been derived for the interpolar,
226 ELECTRICAL ENGINEERING PAPERS
end, slot and band fluxes. In reality it is the resultant fluxes
which should be combined, but as the voltages to be derived
from these fluxes represent somewhat different terms, a better
procedure appears to be the summation of the voltages. Also,
in practice it is the e.m.fs. generated by the different fluxes,
rather than the fluxes themselves, which are desired.
The e.m.f. derived from the interpolar flux is
WiTcRs 2pirDL
10s (0.25 £+0.5) (jrD-Pp)
where Ci is a correcting factor for chord winding, etc.
The formula for the, end flux voltage is,
„ _ ^Ic Wt TeR>^-4.3(2h+m)
*~ -CaX HP x ihT0
where d represents the correcting factor for chord windings, etc.
The formula for the slot flux voltage is,
3.19 Ic Wt TCRSL (2.666 d+4a+t+2.16s Vn)
&c-c3X 1Q8 -
where c3 is the correcting factor for the brush width, chord
winding, etc., and,
For the bands,
where c4 is the correcting factor for chord winding, brush width,
etc.
Therefore,
<-*-i-** '* . _ 7T
total- ^ L' ((0.25/^+0.5)
2<t>NpTcRs
THEORY OF COMMUTATION 227
It is evident from this last equation that when there are no
bands over the core the total e.m.f. in the short circuited coil
is directly proportional to the current per armature coil or con-
ductor. If the bands saturate, as would usually be the case
with any considerable load, then the e.m.f. is no longer directly
proportional to the current. Attention is called to this point
as it has some bearing in the design of interpole machines.
Condensed Approximate Formula. The above formula can
be simplified very considerably by certain approximations which
introduce but little error within the range of ordinary design
First, the expression, (025/)+05f (irD_Pp} does not seem
to be capable of any general simplification. In fact, as shown
from its derivation, it is not a general term, but applies only to
certain constructions and may appear in a quite different form
for other constructions. Therefore this expression must be
used with judgment in any case. Moreover, this term appears
only in non-interpole machines or in interpole machines only
when the interpoles are narrower than the armature core or the
number of interpoles is less than that of the main poles. There-
fore this term may be neglected in many cases where interpoles
are used.
/O 7L I ft-\
Second, the expression 4.3 -W-: — ^p- log 2 N can be changed
as follows:
4-3 / • m = — - — * with reasonable accuracy within the
(sin u) p
ordinary limit of design,
And log 2 N= 0.9+0.035 N, with an error of about 4 per cent
within the range of 6 to 24 slots.
Therefore 4.3 -" log 2N=--- (0.9+0.035 N}r
(sin u) p
approximately .
This is simpler to handle, in practice, than the original term.
Third, the expression, *-™wr'T*-"* v" can ^ sim,
plified very materially.
Let the total depth of slot be represented by d*, which is equal
to 2 d+a+1.5 t, approximately.
4ds 8 a — 3 /
Then, the term, 2.666 d+± a +t can be changed tc— ^- ^ ^ —
228 ELECTRICAL ENGINEERING PAPERS
Assuming a »0.25 and J«0.15, then
Q __ O j
5 =0.52 approximately.
o
_. , 2.6Qd+4a+t id, . 0 52
Therefore, _ -37+—
This is a very close approximation within the ordinary work-
ing range of slot dimensions. Therefore, the above expression
becomes, 0 * H — '• 1-2. 16 V#, which is much simpler to use in
3 s $
practice.
Fourth, in the simplified equation TT appears in the first
and second terms, and 3.19 appears in the third term. These
are so nearly equal that TT may be used as a common factor for
the three terms.
The combined formulas for the total voltage per armature
coil thus becomes, in approximate form,
2pDL
" 10* (0.25£+0.5)(7rZ>-P/>)
4 D
+C* ^f- (0.9+0.035 N) +
P
*
(1.33 &+0.52+2.16* Vn)1 , 2 <fr> N}> Tc R,
- - - -
.
c>L
This appears to be about as simple a form as the equation can
be put into when all the factors are to be included- It will be
shortened for machines without magnetic bands on the core
and in many interpole machines the term derived from the inter-
polar flux may be omitted. For a given line of machines which
are all of similar design, etc., it is probable that the terms can
be further combined and simplified.
INTERFOLAR MACHINES
In the interpole machine a small pole is placed between two
adjacent main poles for the purpose of setting up a local magnetic
flux under which the armature coil is commutated. This local
*For ordinary working range of slot dimensions, 216 JV*— 1.07 X tooth pitch at ar-
mature surface. This formula may be further simplified by substituting 1,07 Pt for 2.16
s v/n. Pt being the tooth pitch at the armature surface.
THEORY OF COMMUTATION 229
flux, in order to assist commutation, must be opposite in direction
to the interpolar flux set up by the armature winding itself. To
set up this flux in the opposite direction the magnetomotive
force of the interpole winding obviously must be greater than
that of the armature winding in the commutating zone.
An armature coil, cutting across this interpole flux, generates
an e.m.f. proportional to the flux, the speed and the number of
conductors in series. This e.m.f. is in opposition to the e.m.f.
in the short circuited coils, generated by the slot and end winding
fluxes. For ideal commutation these e.m.fs. are not only in
opposition, but they should also be of practically equal value.
For perfect commutation the current in a short circuited coil
should die down to zero value at about a uniform rate and
should then rise to normal value in the opposite direction by the
time the coil passes out from under the brush, as was illustrated
in Fig. 12. This is the condition when no local currents are de-
veloped in the short circuited coils and this can only be obtained
when the interpole e.m.f, at all times, balances the armature
e.m.fs. in the short circuited coils.
Looking at the problem broadly, the resultant magnetic
fluxes and e.m.fs. may be assumed as made up of two com-
ponents which can be considered singly. One of these com-
ponents is that which would be obtained with the armature
magnetomotive forte alone acting through the various flux paths,
including the interpole. The other would be that which would be
obtained with the full interpole magnetomotive force alone, the
armature magnetomotive force being absent. Saturation is not
considered in. either case.
Considering the first component, due to the armature mag-
netomotive force alone, there would be the slot and the end
fluxes with their short circuit e.m.fs., as already described,
and in addition, there would be a relatively high flux, and short-
circuit e.m.f. due to the good magnetic path furnished by the
interpole core. In case the interpole does not cover the full
width of the armature, or the number of interpoles is less than
the main poles, there will also be some interpolar flux and e.m.f. ,
as already described.
Considering the second component, the entire interpole mag-
netomotive force would set up a relatively high flux through the
interpole magnetic circuit and a. correspondingly high e.m.f.
would be generated in a sfoort drcuited armature coil cutting
fhift flux.
230 ELECTRICAL ENGINEERING PAPERS
When these two components are superimposed, it is seen that
the interpole flux due to the armature magnetomotive force is
in direct opposition to that due to the interpole magneto-
motive force and therefore only the e.m.f. due to their dif-
ference need be considered. As the interpole winding has the
higher magnetomotive force, the resultant interpole e.m.f. is
in opposite direction to the armature e.m.fs., and should be
sufficient to neutralize them. This way of considering the prob-
lem avoids a number of confusing elements which would com*
plicate the explanation if given in detail.
In practice it is difficult to obtain exact equality between the
interpole and armature e.m.fs. That due to the armature
fluxes is generated in all parts of the coil including the end
winding, while the e.m.f. due to the interpole flux is generated
only in that part of the coil which lies in the. armature, slots,
However, it makes no difference in what part of the coil the e.m.f.
due to the interpole is generated provided it is of such value that
it properly opposes and neutralizes the various e.m.f s., due to
the armature fluxes. Therefore, in practice the interpoles need
not have the same width as the armature core and, where space
and magnetic conditions will permit, the number of interpoles
can be made half that of the main poles.
According to the method outlined, the whole problem of the
design of the interpole depends, first, upon the determination
of the a.m.fs. due to the armature fluxes, and, second, upon the
determination of such interpole flux as will generate an e.m.f,
in the short circuited armature coils which will equal, or slightly
exceed, the armature e.m.fs.
Interpole Calculations. Assuming that all the armature
fluxes, except the interpolar, are unaffected by the presence of
interpoles, the armature e.m.f. to be balanced by the interpole
would be represented by the formula
3
_ _
- (0,25 £+0.5)
(0.9+0.035 AO +
1.88 A +0.52+2.16 * Vn
THEORY OF COMMUTATION 231
However, the flux above the slot, from the tooth top, is very
considerably modified by the interpolar flux. In fact most of
this should be omitted It may be assumed that the flux across
the slot, above the upper coil, simply " bulges " up slightly
into the air gap, and the remainder of the usual tooth top flux
is absent, except when the interpole does not cover the full
armature width. Therefore, in the above formula, the term
LX2 16 V^ should be changed to (L-Li)X2 16 Vn and the
] .33 ck + 0.52 . ,u 1.33 & +0.7
term ! replaced by jL_L___
«s s
Then, the corrected resultant of all the armature e.m.fs.
becomes
/T T \ %DP
d (L—L^
-Pp)
4. n
+cjX-~ ^ (0.9+0.035 JV)
In this formula
L represents the width of the armature core.
Li represents the effective width of interpole at the gap
on the basis of the full number of interpoles.
L—Li is the difference between the width of the armature
core and the interpole face. This term enters when the interpoie
is narrower than the armature core. When alternate interpoles
are omitted and the remaining interpoles are of the same width,
as the armature core the conditions are practically the same as
when the full number of interpoles are used but with their width
equal to half the core width. Other combinations should be
treated in the same way so that the above formula can be taken
to represent the general conditions.
In practice it is desired that the resultant interpole e.tn.f,,
and therefore the interpole flux, vary in- proportion to the arma-
ture short-circuit e.m.f. which is to be neutralized. As shown
fcy the last ^equation, this e.m.f . is proportional to the armature
232 ELECTRICAL ENGINEERING PAPERS
current, except where there is saturation in the armature flux
path, as in the case of magnetic bands over the core* Therefore
the interpole magnetomotive force should vary in proportion
to the armature current, neglecting core bands. In consequence,
in practice the interpole winding is always connected in series
with the armature winding.
The interpole magnetomotive force can be considered as made
up of two components, one of which neutralizes the armature
magnetomotive force, and the other component represents the
ampere turns which set up the actual interpole flux. The first
component will be referred to as the neutralizing ampere turns
or neutralizing turns , and the other as the magnetizing ampere
turns or magnetizing turns.
Let T represent the total interpole turns for one interpole,
Tv represent the total magnetizing interpole turns for one
interpole.
Ta represent the total effective " armature turns per
total eff . ampere turns of armature ,
~~ number poles X total current '
/ represent the amperes per interpole coil.
Then ITt = IT-I Ta, or, r=
Let g = effective air gap per interpole.
2J»= flux density under the interpole, and
JS, = e.m.f. in an armature coil of turns Tf due to the
interpole flux
Then,
The e.mX due to one interpole is equal to
10*
Or, for two interpoles
JLxX2r.lt,
*If average slot e. rru f. is used in calculating' EC (See Note on page 215), this expression
should be multiplied by a factor Cp to obtain, average value of Ei. Cp is the ratio of the
average flux density in the commutating zone, to the marfmijTn density, J5».
THEORY OF COMMUTATION 233
This e.m.f. should be equal to the e.m.f. generated in the same
coils by the armature flux, or Ei=Ec. Therefore,
3.19 I Tt TT D LiX2 Tc Rs -IeW,.TfRsir
,r_r
gXlO8 10*
2D p
(0.25^+0.5)
(0.9+0.035
(L-i02.16 V^ T<
In the second term of this equation 7t W( = IX Ta'X2p, where
jT0' = total armature turns per pole, as distinguished from effec-
tive turns per pole Ta, and Ta' =- — ?— , where & = ^'T' as will
1 — op Wt
be shown later under the subject of " Effective Armature Am-
pere Turns." Therefore, neglecting magnetic bands on the core,
the above expression becomes,
r raj>g r
1 *~3.19 DZ-! (l-&^>) L
(0.25 ^>+0.5) (irD-Pp)
(0.9+0.035 (1'33
+c» (L-iO 2.16
2J>j>
(vD-Pp)
(0.9+0.025 .
+c» (L— LI) 2.16
234 ELECTRICAL ENGINEERING PAPERS
If the full number of interpoles is used, and each covers the
full width of the armature, then Z~Z,i = 0, and
(1.33
Therefore the total interpole turns for one pole are equal to
the effective armature turns, per pole multiplied by a constant
which is a function of the' proportions of the machine. How-
ever, this holds true only for the condition of no saturated path
for the armature flux, such as magnetic bands.
The above formula gives the interpole turns for two inter-
poles acting on each armature coil. With but one interpole
per coil the number of conductors per armature coil generating
the interpole e.m.f. is halved so that the flux density must be at
least doubled, and the effect of the armature flux in the inter-
polar space over the other half of the armature coil must also be
taken into account. This can be done in the preceding formula
by using the equivalent value of LI.
With half the number of interpoles the effective gap length, gr
will not be the same as with the full number of interpoles with
the sameinechanical gap, for the flux from the interpole maybe
considered as returning across the gap of the two adjacent main
poles and the value of g must be increased to represent the total
resultant gap.
Let ge represent the effective resultant gap,
gm represent thfc effective gap under the main poles,
A i represent the area of the interpole gap, and
Am represent the area of one main pole gap.
These areas can be derived from the field distribution or " field
form " of the main and the interpoles.
Then, the effective resultant gap g, = g-f— p gmj and this
•" ./LIT*
should be used instead of g
With half the number of interpoles and on the basis of the
interpole flux returning through the two adjacent main poles,
it may be assumed that this flux weakens the total flux in one
pole and strengthens that of the other pole a Ek^ amount. If
THEORY OF COMMUTATION ' 235
there is no saturation in the main poles or armature teeth under
them, then no additional ampere turns, other than for the
increased gap, will be required on account of the main poles
carrying the interpolar fluxes. However, where there is much
saturation of the main poles or teeth, then additional interpole
ampere turns will be required, as will be described later in con-
nection with effects of saturation.
Chord Windings with Interpoles. Chorded armature windings
can be used with interpoles with satisfactory results provided
the interpoles are suitably proportioned. There are apparently
some advantages with such an arrangement, but there are also
disadvantages of such a nature that it is questionable whether
it is advisable to use chord windings with such machines, except
possibly in special cases. When chorded windings are used with
interpoles, the e.m.f. due to the armature flux is usually much
smaller than with a pitch winding and thus fewer interpole
magnetizing turns are required. Also, the effective armature
turns which must be neutralized by the interpole are reduced
somewhat, which also means a slight reduction in interpole
tuftis. Against these advantages must be charged the disad-
vantage of a wider interpole face. This in itself would not be
objectionable where there is space for such wider pole face, but
if the space between the main poles must be increased it may lead
to sacrifice in the proportions of the main poles or changes in
the general dimensions, such that the result as a whole is less
economical than with a pitch winding.
Effective Armature Ampere Turns. The term Ta representing
the effective artnature ampere turns should be considered, as the
value of this term is influenced by a number of conditions, such
as the number of bars covered by the brush, the amount of
chording in the armature winding, etc. With a full pitch wind-
ing and neglecting the reduction in current in the short circuited
coils, the magnetomotive force of the total armature winding
is represented by the expression, — £^ L , and per pole it is,
- . However, when the brush spans several coils, so that
2p
a number of armature coils are short circuited at the same time,
the average current in these short circuit coils should be con-
siderably less than the normal value so that the effective ampere
turns per pole is correspondingly reduced. Allowance must be
236 ELECTRICAL ENGINEERING PAPERS
made for this reduction as it has considerable influence in de-
termining the correct number of interpole turns.
On the basis of no local currents, the average value of the
current in the short circuited coils is just half that of the work
currents per conductor.
Let B represent the total number of commutator bars,
BI represent the number of bars spanned by the brush,
pi represent number of current paths, and
p number of poles.
•n <TT»
Then, . ," = total number of armature turns per pole, and
Pip
7? 7"1
* c = number of turns by which the total armature turns per
& pi
pole must be reduced to obtain the effective turns per pole, or,
^.—g-, ..„,.___
Let BI Te be represented as a percentage of Wh or BI Tc «= b Wt
Then, ro= 0 * (1
Wt IWt
2p
T
Therefore, Ta/ = -rr '
Chorded windings also have an influence on the effective arma-
ture ampere turns per pole- When the winding is chorded one
slot, for example, then, in one slot per pole, the upper and lower
coils will be carrying current in opposite directions and tEeir
magnetizing effects will be neutralized. In consequence, the
total effective armature ampere turns are correspondingly re-
duced and this must be allowed for in determining the interpole
turns.
THEORY OF COMMUTATION
237
Conditions Affecting Interpole Proportions. The foregoing
formulae have been based upon the use of interpoles of such pro-
portions that the interpole flux varies directly as the magnetizing
current and its distribution over the cojnmutating zone is such
as will give the proper opposing e.m.f. at all times.
However, the proportionality of flux to current can only be
true as long as there is no saturation, in the interpole magnetic
circuit. Such saturation is liable to be found in practice and not
infrequently it is quite a problem df design to avoid it within
the working range of the machine.
Also, another difficult problem lies in so designing the interpole
face that the flux distribution in the commutating zone is such
that its e.m.f. will properly balance the armature e.m.fs. in the
short circuited coils, especially as the latter are generated by
cutting fluxes which may be distributed in a quite different man-
ner from the interpole flux.
FIG. 21
Shape and Proportion of Interpole Face. As already shown,
the effective interpole flux under the pole face is the "resultant
of the total interpole magnetomotive force and the opposing
armature magnetomotive force. As the armature windiag is
distributed over a surface and the interpole winding is of the
polar or concentrated type, the resultant magnetomotive force
would normally be such as would not tend to give a uniform flux
distribution under the interpole unless the interpole face is
properly shaped or proportioned for such distribution. The
conditions may be illustrated in Pig. 21. In this figure the lines
A A represent the armature magnetomotive force, with a full
pitch winding, and the brash covering one commutator" bar.
The heavier p&rt of the lines a b c at the peak of the magneto-
motive force diagram, represents the armature magnetomotive
fdrce which would be obtained tinder the interpole face, a#d also
the fttcc distribttfioa wMdi would be obtained, with no interpole
238 ELECTRICAL ENGINEERING PAPERS
magnetomotive force, and with, uniform gap under the pole
faces. In opposition is shown the interpole magnetomotive
force and flux distributions d ef for corresponding conditions.
The resultant magnetomotive force is represented by g h i, and
with a uniform gap under the pole, the resultant interpole flux
would have a similar distribution. Instead of this, either a
flat or, in some cases, the reverse distribution is required, that
is, with a slight " hump " in the middle instead of a depression-
By prbperly shaping the pole face so as to give an increased air
-gap toward the edges, the flux distribution can be made practi-
cally anything desired. In some cases a relatively narrow
pole tip with a very large air gap will give a close approximation
to the desired flux distribution.
However, in practice the above distribution of the armature
magnetomotive force is rarely found. The use of brushes
which cover more than one commutator bar serves to cut off
or flatten out the pointed top of the armature magnetomotive
force diagram, as shown by the dotted line B, in Fig. 21, and thus
lessen the depression at the center of the resultant magneto-
motive force distribution.
As intimated before, this problem of proportioning the inter-
pole face turns upon the determination of the armature e.m.fs.
in the short circuited coils which have to be balanced by the
interpole. If the different armature e.m.fs. are determined for
the whole period of commutation and then superimposed, the
resultant e.m.f . indicates the flux distribution required under the
interpole. Usually the e.m.fs. due to the end winding, and to
the interpolar flux, if any, will be practically constant during the
whole period of commutation. If no local currents are present
the e.m.f. due to the slot flux will also be practically constant,
although it may be slightly reduced near the beginning and end
of the commutation period. The sum of these e.m.fs. should
therefore be practically Constant over the whole commutation
period and therefore, in a well designed machine, the interpole
flux, density should be practically constant over the whole
commutation zone. As explained before, special shaping of the
poles and pole face will be necessary, in most cases, to obtain
exactly this proper flux distribution. Large interpole air gaps
are obviously advantageous in obtaining such distribution. In
fact* a very small interpole gap makes the determination of the
properjnterpole face dimensions very difficult in, many cases.
On accocrat of the interpole usually covering less than two
THEOR Y OF CO MM UTA TION 239
armature teeth, the ordinarily accepted methods of determining
the effective length of air gap under a pole will not apply, iifc
many cases, which may lead to a slight error in the results.
Practically the effective gap tinder the narrow interpole will
usually be longer than determined by the ordinary methods.
This partly explains the fact that, in some cases, an increase
in mechanical clearance between the interpole face and the
armature core does not require anything like a corresponding
increase in the interpole magnetizing ampere turns. The effec-
tive interpole air gap increases, but at a much less rate than the
mechanical gap.
The brush setting in relation to the interpole is of great im-
portance. The point of maximum armature magnetomotive
force is definitely fixed by the brush setting. With the interpole
fixed in position, any shifting of the biuishes backward or forward
will obviously change the shape of the- resultant magnetomotive
fores distribution under the interpole face and in consequence
the flux distribution will be changed. With but one armature
coil per slot and the brush covering but one commutator bar,
good commutating conditions might be found over a considerable
range of brush adjustment, by suitably varying the interpole
ampere turns. However, with two or more coils per slot and
with the brush short circuiting several bars, any marked change
in the resultant interpole magnetomotive force and flux distribu-
tion will mean improper commutation for some of the coils.
Proper brush setting is therefore of first importance.
It has been ''assumed in the foregoing treatment, that an exact
balance between the interpole and armature e.m.f s. will give the
best conditions. From certain standpoints, this is true, but in
practice usually a slight excess in the interpole strength, or
" over-compensation " of the interpole, as it is frequently called,
is advantageous. Reference to Fig. 14 shows that in a machine
without interpoles, and therefore without compensation, the
current flowing between the brush contact and the commutator
is crowded toward one brush edge, this being the edge at which
the commutation of a coil is completed, that is, at the so-called
forward brush edge. With over-compensation the opposite
effect occurs — that is, the brush current density is below the
average at the forward edge. This is, to a certain extent, a de-
sirable condition. Also, if there is any saturation of the inter-
pole circuit at overloads, the over excitation of the interpole
winding can take care of the saturation ampere turns, so that
240 ELECTRICAL ENGINEERING PAPERS
normal compensation can be obtained at considerably higher load
than in a machine with no over compensation. Furthermore,
over compensation is desirable on account of the effect of the
resistance of the coils undergoing commutation, which heretofore
has been neglected as being of minor importance. Such re-
sistance tends to lower the current density at the middle of the
brush contact, and increase it toward the brush edges. Over
compensation will oppose this at the forward edge, but increase it
at the back edge, which is less objectionable. Also, as shown in
Fig. 21, there is liable to be a depression at the center of the
interpole flux distribution, if the pole face is not properly
shaped. This depression tends to cause higher current densities
at the brush edges. Over compensation again tends to reduce
this density at the forward brush edge. Thus there are several
good reasons for slight over compensation, and practical opera-
tion bears this out, especially on high voltage machines, where
the short circuit e.m.fs. average higher than in other machines.
Balanced Circuits. It has been assumed that the armature
ampere turns per pole have been the same for all poles. This
will be true for the usual two-circuit or series type of winding,
or its allied combinations, but is not necessarily true of the
parallel type of armature winding. Ill such a winding a number
of circuits are connected in parallel at the brushes, and, unless
ample provision be made for equalizing the different circuits,
they may not carry equal currents at all times. As the re-
sultant interpole flux and e.m.f. is directly dependent upon the
opposing armature ampere turns, it is obvious that any ine-
qualities in the armature currents would lead at once to incorrect
interpole conditions. A poorly equalized parallel-wound arma-
ture might furnish conditions such that the interpoles cannot be
adjusted for satisfactory operation. Also paralleling of the
interpole windings, unless care be taken to insure equal cutrent
division among the circuits, is liable to lead to trouble,
Saturation of the Inter.pole Circuit. Heretofore the interpole
turns T, as determined, have been only those required for forcing
the resultant interpole flux across the effective interpole air gap,
and nothing has been allowed for any turns required for magnet-
izing the parts of the interpole circuit other than the gap.
Where such additional turns are required they must be added to
the turns T, already determined.
Saturation in the interpole magnetic path is the principle
cause for such additional turns, but saturation in the various
THEORY OF COMMUTATION 241
flux paths may occur in such a way as to be either harmful or
beneficial, depending upon where it is located. Beneficial
saturation may be assumed to be such as will reduce the arma-
ture short circuit e.m.fs,, while harmful saturation tends to re-
duce the interpole e.m.f.
While the useful interpole flux passing into the armature may
be relatively low — say one-fifth that required for saturation of
the interpole material — the leakage flux between the interpole
and the two adjacent main poles is often very much greater
than the useful flux so that the interpole at the part where it
carries the highest total flux may be worked up to possibly half
saturation, or higher, with normal load on the machine. The
interpole leakage flux is due to the total ampere turns on the inter-
pole, while the useful interpole flux is due only to the magne-
tizing component of the interpole ampere turns, which may be
as low as 15 per cent to 25 per cent of the total interpole ampere
turns. Ths leakage flux is thus liable to be a high percentage
of the total interpole fluxt
"While the ampere turns on the interpole will rise in direct
proportion to the current, the effective magnetizing component
will rise in direct proportion only below saturation of the inter-
pole circuit. Any ampere turns required for saturating this
circuit will be taken from the magnetizing component of the
interpole winding. Therefore, when any appreciable saturation
occurs, the effective magnetizing component will not vary in
proportion to the current, and the interpole e.m.f. will not vaiy
in proportion to the armature e.m.f s. As the magnetizing com-
ponent of the interpole winding usually represents a relatively
small number of ampere turns per pole a comparatively slight
saturation in the interpole circuit may have an appreciable effect „*
It is therefore advisable to work at as low a saturation as possible
in the interpole circuit so that practically no saturation occurs
within the ordinary working range of the machine.
Where saturation occurs in any of the armature flux paths,
as, for instance, with saturated bands over the armature core,
the result of such saturation will serve to neutralize the effect
of saturation in the interpole magnetic circuit. In other words,
the armature e.m.f. will not rise in proportion to the current
and thei*efore the opposing interpole e.m.f. does not need to
increase in proportion either.
The principal source of saturation in the interpole circuit lies
in the magnetic leakage from the interpole to the adjacent main
242 ELECTRICAL ENGINEERING PAPERS
poles. Serious trouble has often been encountered by not
making due allowance for such leakage. However, there may
be other causes for saturation. When the full number of inter-
poles is used the interpole magnetic path or circuit is independent
of the main pole magnetic circuit, except in the yoke and in
the armature core below the slots, as indicated in Fig. 22.
In the yoke it may be seen that the interpole flux is in the same
direction as the main flux at one side of the main pole and is in
opposition to the main flux at the other side. The same is true
in the armature core. Therefore the interpolar flux tends to
reduce the flux in one part of the yoke and tends to increase it in
the other part. If the saturation in these parts is relatively low,
then the magnetomotive force required for forcing the low and
the high fluxes through the yoke will be but little greater than if
these fluxes were equal. However, if the yoke is highly saturated
the increase in ampere turns required for the high part much
more than offset the decrease in ampere turns for the low part,
so that, as a result, additional am-«
pere turns are required for sending
the interpole flux through this path.
The interpole ampere turns therefore
must be increased on this account, }
^riien the saturation is high. The same F 22
condition holds for the armature core.
A similar condition occurs -where half the number of interpoles
is used and when there is much saturation of the main pole and
the armature teeth under it, as already referred to. This con-
dition requires additional interpole ampere turns.
In practice, with the ordinary compact designs of direct cur-
rent machines, it is usually difficult to keep the total interpole
flux as low as one-third that which gives any material saturation
and, not infrequently, it is much higher than this. Therefore,
by direct proportion it might be assumed that such machines
could carry only double to treble load without sparking badly. ,
However, the resistance of the brushes, etc., will be of such as-
sistance that relatively higher loads may be commutated rea-
sonably well. For instance, with the interpole worked at about
half saturation at normal load, the machine may be able to
commutate considerably more than double load without undue
sparking. It is also of material assistance, where heavy over-
loads are to be carried, to over-excite the interpolevwinding,
that is, to make the magnetizing component somewhat greater
THEORY OF COMMUTATION 243
than required at normal load, as described before. In this case,
at light loads, the interpole e.m.f. exceeds the armature e.m.f.
a certain amount which is taken care of by the brush resistance
as local currents will be less harmful when the work current is
low. As partial saturation is obtained at overload, the two
e.m.fs. become equal but at a higher load than would be the case
without ovef -excitation of the interpole.
Commutating Conditions on Short Circuit. When a direct
current generator is short circuited across its terminals, either
through a low external resistance or without such resistance, a
current rush will occur which will rise to a value represented
approximately by the generated e.m.f. divided by the resistance
in circuit. This current rush is only of short duration as the
excessive armature current will react to demagnetize or " kill "
the field. If the short circuit is without external resistance the
current rush may reach an enormous value as the internal re-
sistance on large machines is usually very low. This means that
currents from 25 to 40 times full load may be obtained on " dead "
short circuit. Experience shows that under such current rushes,
any kind of direct current machine will tend to flash viciously at
the brushes.
By the preceding theory and analysis a rough approximation
to the commutating conditions on short circuit can readily be
obtained. Assuming an interpole machine, the following con-
ditions will be found:
1. The interpole will be highly saturated so that it is of little
or no direct benefit.
2. The slot flux will rise to such a value that the armature
teeth in the commutating zone are practically saturated.
3. There may be some interpolar flux from the armature, as the
high interpole saturation may allow this.
4. The armature end flux, with the exception of that part due
to magnetic bands, will rise practically in proportion to the
current.
The following short circuit e.m.f. conditions will be obtained:
1. There will be possibly a slight e.m.f. due to the armature
interpolar flux.
2. There will be an e.m.f. due to the tooth flux which is almost
as high, per conductor, as could be obtained by a conductor
cutting the flux under the main field at no load, for saturation of
the armature teeth may be assumed to be the limit in both cases.
3. There will be an e.m.f. due to the end flux which may be
10 to 20 times larger than at normal full load.
244 ELECTRICAL ENGINEERING PAPERS
Therefore, the total e.m.£. in the short circuited coil due to
cutting the armature flux on dead short circuit may be higher
than would be obtained if the brushes were shifted at no load until
the commutated coil lies under the strongest part of the main field.
As very few machines of large capacity would stand this
latter condition without flashing, it may be assumed that they
would be no more able to stand a dead short circuit without
flashing. In fact, 8 to 10 times full load current will make an
interpolar machine of normally good design flash badly, as it is
impracticable to make an interpole of the usual type which will
not saturate highly at 8 to 10 times normal current.
If, however, the interpole is combined with compensating
windings in the main poles, the interpole leakage may be made
so small that comparatively low saturation is obtained normally
in the interpole circuit. In such case the interpole may be effec-
tive with heavier currents and the flashing load may be very
much higher than with the usual type of interpole machines.
CONCLUSION
The foregoing is a general presentation of the problem of
commutation, which is admittedly crude and incomplete in some
points. In particular may be mentioned the part describing,
the action of local currents. Also, the method of considering
the resultant action in interpole machines as the superposition
of two components does not tell the whole story, but the actual
analysis, in detail, of a number of these phenomena would be so
confusing and complicated, that a general physical conception
of what takes place during commutation would be lost. In the
ultimate analysis it will be found that a number of the methods
described are, In reality, simply illustrations of the conditions
of commutation rather than an analysis of the conditions them-
selves. However, the method as given throws light on many
things which take placie during commutation. It also includes
a number of conditions which are not -covered in the usual
methods of dealing with this problem. For example, the number
of commutator bars spanned by the brush is an important ele-
ment in this method of handling the problem, whereas, in many
former methods, this point was either omitted, or treated in an
empirical manner. In this method the results obtained would be
very greatly in error if the brush span were not included.
Any theory qr method of calculation is open to question until
ti has stood the proof of actual test. In consequence, the above
THEORY OF COMMUTATION 245
"jnethod has been tried on a very large number of direct current
machines, including high speed direct current generators,
direct current turbo-generators, direct current railway motors of
all sizes, moderate- and low-speed generators of all capacities,
industrial motors of various designs including adjustable speed
motors and machines with half the number of interpoles. In
those cases where tfce actual test data of the machines was very
accurately obtained, the agreement between the tests and the
calculated results by the above method was found to be close.
In fact, the method in som§ cas6s indicated errors or inaccuracies
in the test results. In a number of cases of early interpole
machines there was considerable disagreement between the
results of the calculation and the actual test, but, in many of
these cases, later experience showed definitely that the proper
interpole field strength or proportions had not been obtained
in the actual test or that the proper brush setting had not been
used. These cases were thus, to a certain extent, a verification
of the method, for in general the greatest discrepancies between
the calculated and the test results corresponded to the ma-
chines which eventually proved to have the poorest proportions
or adjustment.
This theory of commutation looks complicated and cumber-
some in its practical application, but it should be understood
that it is, in reality, an exposition of a general method from
which special and simpler methods may be derived -for different
types and designs of machines. It indicates plainly that the
problem is so complicated that no simple formulae or methods of
calculation can be devised which will cover more than individual
cases, and that such formulae, if applied generally, will lead
to errtfr sooner or later. If, however, tt^e general derivation
of such simplified formulae is well understood, then they may
be used with proper judgment and with much less danger of
error in the results. It is evident, from the general analysis, that
the whole problem must be handled with judgment, for new or
different conditions are encountered in almost every type of
machine.
A great many problems, closely allied to that of commutation
in interpole machines, have not been considered, because some
of them represent special cases of the general theory, while
others axe somewhat outside the subject of this paper. Of the
former class may be mentioned, commutation of synchronous
converters, niachiiies with distributed or true compensating
246 ELECTRICAL ENGINEERING PAPERS
windings, the so-called " split-pole " converter, and the commu-
tator type alternating current motors, etc. In the latter class
may be included such problems as the effect on commutation of
closed circuits around the interpoles, losses due to commutation,
current distribution at the brush contact, etc. Some of these
subjects were included in this paper as originally prepared, but
on account of its undue length they had to be omitted.
PHYSICAL LIMITATIONS IN DIRECT-CURRENT
COMMUTATING MACHINERY
FOREWORD — This paper was presented before the American Insti-
tute of Electrical Engineers in San Francisco, September 16,
1915, at the Electrical Congress at the Panama-Pacific Inter*
national Exposition. It gives the results of the author's work
on determination of commutating limits covering the period of
many years of work. As regards commutation, it is, in reality,
a supplement to the paper, "Theory of Commutation and Its
Application to Commutating Pole Machines." On the subject
of flashing, it covers some very interesting limitations, based
upon experience and special tests.
This paper is, in reality, more or less of a general summary
of the author's experience in direct-current machinery. Al-
though usually looked upon as an "alternating-current man,"
he has probably spent as much total time on direct-current
work as on alternating. Many of the limiting conditions in
direct-current machinery, as described in this paper, were de-
termined by the author himself. Many of the early more or
less radical developments and improvements in direct-current
machinery resulted directly from his work. A description of
some of these is covered in his historical papers, entitled, "The
Development of the Direct-Current Generator in America,"
and "The Development of the Street Railway Motor in Amer-
ica" which appear in the latter part of this volume. — (ED.)
IN DIRECT-current commutating machinery there are
many limitations in practical design which cannot be
exceeded without undue risk in operating characteristics.
Some of these limitations are actually physical ones, and, there-
fore, cannot be avoided or over-stepped without very considerable
departures from our present methods of construction and opera-
tion; others are not wholly physical, but are fixed largely by
practical experience, and are, in consequence, subject to modifica-
tion, as our experience is increased. Seme of them are quite defin-
ite in nature, while others axe indefinite. Some are measurable,
in a quantitative sense, while others may be considered as quali-
tative. Noise, for instance, is a distinct limitation, in many cases,
but it is difficult to fix any definite value where it is prohibitive.
247
248 ' ELECTRICAL ENGINEERING PAPERS
Many of these limits are not sharply defined in practise, due, in
many cases, to the impossibility of taking advantage of all" the
helpful conditions and of avoiding the objectionable ones. There
are many minor conditions which affect the permissible limits
of operation, which are practically beyond the scope of reliable
calculation. Usually, such conditions are recognized, and al-
lowance is made for them. It is the purpose of this paper to
treat of some of the major, as well as minor, conditions which
must be taken into account in advanced direct-current design.
These are so numerous, and are so interwoven, that it is difficult
to present them in any consecutive order.
Probably the most serious limitation encountered in direct-
current electric machinery is that of commutation. This is an
electrical problem primarily, but in carrying any design of direct-
current machine to the utmost, certain limitations are found
which are, to a certain extent, dependent upon the physical
characteristics of materials, constructions, etc
A second limitation which is usually considered as primarily
an electrical one, namely, flashing, (and bucking) is in reality
fixed as much by physical as by purely electrical conditions.
A third limitation is found in blackening and burning of com-
mutators, burning and honeycombing of brushes, etc. These
actions are, to a certain extent, electrical, but are partly physical
and "mechanical, as distinguished from purely electrical.
There are many other limiting conditions dependent upon
speed, voltage, output per pole, quality or kind of materials
used, etc. As indicated before, these cannot all be treated
separately and individually, as they are too closely related to
other characteristics and limitations.
COMMUTATION AND COMMUTATION LIMITS
In dealing with the limits of commutation, it is unnecessary
to go into the theory of commutation, except to indicate the
general idea upon which the following treatment is based. This
has been given more fully elsewhere,* and therefore the following
brief treatment will probably be sufficient for all that is required
in this paper.
In this -theory it is considered that the armature winding as a
whole tends to set up a magnetic field when carrying current,
and that the armature conductors cutting this magnetic field
*Theory of Commutation and Its Application to Comxautatxng Pole Machines, Page 201.
PHYSICAL LIMITATIONS IX D.C. MACHINES 249
generate e.m.fs. just as when cutting any magnetic field.
From consideration of the armature magnetomotive force alone,
the flux or field set up by this winding would have a maximum
value over those armature conductors which are connected to
the brushes. If the magnetic conditions or paths surrounding
the armature were equally good at all points, this would be true.
However, with the usual interpolar spaces in direct-current
machines, the magnetic paths above the commutated coils are
usually of higher reluctance than elsewhere. However, what-
ever the magnetic conditions, the tendency of the armature
•magnetomotive force is to establish magnetic fluxes, and, if
any field is established in the commutating zone by the armature
•winding, then those armature coils cutting this field will have
e.m.fs. generated in them proportional to the field which is cut.
As part of this armature flux is across the armature slots them-
selves, and part is around the end windings, both of which are
practically unaffected by the magnetic path in the interpolar
space above referred to, obviously, then no matter how poor the
•magnetic paths in the interpolar space above the core may be
made, there will always be e.m.fs. generated on account of that
part of the armature flux which is not affected by those paths.
In the coils short circuited by the brushes, these e.m.fs. will
naturally tend to set up local of short circuit currents during the
interval of short circuit.
In good commutation, as the commutator bars connected to
the two ends of an armature coil which is carrying current in a
.given direction, pass under the brush, the current in the coil
itself should die down at practically a uniform rate, to zero value
at a point corresponding to the middle of the brush, and it should
then increase at a uniform fate to its normal value in the opposite
direction by the time that the short circuit is opened as the coil
passes from under the brush. This may be considered as the
ideal or straight line reversal or commutation which, however,
is only approximated in actual practice. This gives uniform
current distribution over the brush face.
If no corrective actions are present, then the coil while under
the brush tends to carry current in the same direction as before
its terminals were short circuited. In addition, the short circuit
current in the coil, due to cutting the armature flux, tends to add
to the normal or work current before reversal occurs. The
resultant current in the coil is thus not only continued in the
same direction as before, but tends to have an increased value.
250 ELECTRICAL ENGINEERING PAPERS
Thus the conditions at the moment that the coil passes out from
tinder the short circuiting brush are much worse than if no short
circuit current were generated. The reversal of the current
would thus be almost instantaneous instead of being gradual as
called for by the ideal commutation, and the resultant current
reversed much greater than the work current alone. However,
the introduction of resistance into the local circuit will greatly
assist in the reversal as will be illustrated later. The ideal condi-
tion however, is obtained by the introduction of an opposing
e.mi . into the local short circuited path, thus neutralizing the
tendency of the work current to continue in its former direction.
As this opposing e.m.f. must be in the reverse direction to
the short circuit e.m.f. which would set up by cutting the arma-
ture magnetic field, it follows that where commutation is accomp-
lished by means of such an e.m.f. it is necessary to provide a
magnetic field opposite in direction to the armature field for
setting up the commutating current. This may be obtained in
various ways, such as shifting the brushes forward (or backward)
until the commutated coil comes under an external field of the
right direction and value, which is the usual practise in non-
commutating pole machines; or a special commutating field of
the right direction and value may be provided, this being the
practise in commutating pole and in some types of compensated
field machines. When the commutating emf. is obtained by
shifting the commutated coil under the main field, only average
conditions may be obtained for different loads; whereas, with
suitable commutating poles or compensating windings, suffi-
ciently correct commutating e.m.fs. can be obtained over a
very wide range of operation.
In practise, it is difficult to obtain magnetic conditions such
that an ideal neutralizing e.mJ. is generated. However, the use
of a relatively high resistance in the short circuited path of the
commutated coil very greatly simplifies the problem. If the
resistance of the coil itself were the only limit, then a relatively
low magnetic field cut by the short circuited coil would generate
-sufficient e.m.f. to circulate an excessively large local current.
Since such current might be from 10 to 50 times as great as the
normal work current, depending upon the size of machine,, it
would necessarily add enormously to the difficulties of commuta-
tion whether it is in the same direction as the work current or is
in opposition. To illustrate the effect of resistance, assume, for
example, a short circuit e.m.f. in the commutated coil of two
PHYSICAL LIMITATIONS IN D.C. MACHINES 251
volts, and also assume that a copper brush of negligible resist-
ance short circuits the coil, so that the resistance of the short
circuited coil itself -practically limits the current to a value 20
times as large as the work current. Now replace this copper
brush with one giving about 20 times as large a resistance (some
form of graphite or carbon brush) then the total resistance in
circuit is such that the short circuit current is cut down to a
value about equal to that of the work current. This at once
gives a much easier condition of commutation, even without any
reversing field; while with such field, it is evident that extreme
accuracy in proportioning is not necessary. Thus a relatively
high resistance brush — or brush contact, rather — is of very great
help in commutation; especially so in large capacity machines
where the coil resistance is necessarily very low. In very small
machines, the resistance of the individual armature coils has
quite an influence in litrilting the short circuit current.
It is in its high contact resistance that the carbon brush is
such an important factor in the commutating machine. Usually,
it is the resistance of the brush that is referred to as an important
factor in assisting commutation. In reality, it is the resistance
of the Contact between the brush and commutator face which
must be considered, and not that of the brush itself, which usually
is of very much lower resistance, relatively. As this contact re-
sistance or drop will be referred to very frequently in the fol-
lowing, and as the brush resistance itself will be considered
in but a few instances, the terms " brush resistance rt and
" brush drop " will mean contact resistance and contact drop
respectively, unless otherwise specified.
Short Circuit Volts per Commutator Bar. As stated before
the armature short circuit e,m.f. per coil, or per commutator
bar, is due to cutting a number of different magnetic fluxes, such
as those of the end windings-, those of the armature slots, and
those over the armature core adjacent to the commutating zone.
Each of these fluxes represent different conditions and distri-
butions, and therefore the individual e.m.fs. generated by them
may not be coincident in time phase. Therefore, the resultant
e,m.f . usually may not be represented by any simple graphical
or mathematical expression.
When an external flux or field is superimposed on the armature
in the commutating zone, it may be considered as setting up an
additional e.m.f. which may be added to, or- subtracted from,
the resultant short circuit e.nuf. due to the armature fluxes.
252 ELECTRICAL ENGINEERING PAPERS
These component e.m.fs. are not really generated separately
in the armature coils, for the external flux combines with part
of the armature flux, so that the armature coil simply generates
an e.m.f. due to the resultant flux. However, as part of the
armature short circuit e.m.f is generated by fluxes which do not
combine with any external flux, as in the end winding, for in-
stance, it follows that, to a certain extent, separate e m.fs are
actually generated in the armature winding in different parts of
the coil. For purposes of analysis, there are advantages in
considering that all the e m.fs in the short circuited armature
coil are generated separately by the various fluxes. A better
quantitative idea of the actions which are taking place is thus
obtained, and the permissible limitations are more easily seen.
In the following treatment, these component e.m.fs will be
considered separately. As that component, due to cutting the
various armature fluxes, will be referred to very frequently
hereafter, it- will be called the " apparent " armature short
circuit e.m f . per coil, or in abbreviated form, " the apparent
short circuit em.f." In practise, on account of the complexity
of the separate elements which make up the apparent short
circuit e m.f., it is very difficult, or in many cases, impossible,
to entirely neutralize or balance it at all instants by means of an
e.m.f. generated by an extraneous field or flux of a definite distri-
bution-. Therefore, it should be borne in mind that, in practise,
only an approximate or average balance between the two com-
ponent e.m.fs. is possible. With such average balance there are
liable to be all sorts of minor pulsations in e.m.f. which tend to
produce local currents and which must be taken care of by means-
of the brush resistance. Pulsations or variations in either of the
component e.m.fs. are due to various minor causes, such as the
varying magnetic conditions which result from a rotating open
slot armature, from cross jnagnetizing and other distorting effects
under the commutating poles, variations in air-gap reluctance
under the commutating pol^s, pulsations in the main field reluc-
tance causing development of- secondary e.m.fs. in the short
circuited coils, etc. Some of these conditions are liable to be
present in every machine; some which would otherwise tend to
give favorable conditions as regards commutation, are partic-
ularly liable to -set up minor pulsations in the short circuit e.m.f.
Therefore, brushes of high enough resistance to take care of the
short circuit e m.f . pulsations are a requisite of the present types
of d-c. machines, and it may be assumed that there is but little
PHYSICAL LIMITATIONS IN D C. MACHINES 253
prospect of so improving the conditions in general that relatively
high resistance brushes, or their equivalent, may be discarded.
It is only on very special types of machines that low resistance
brushes can be used.
With ideal or perfect commutation, the two component e.m.fs
in the short circuited coil should balance each other at all times
However, as stated before, this condition is never actually ob-
tained, and the brush resistance must do the rest. With ideal
commutation, the current distribution over the brush contact
face should be practically uniform, and a series of voltage read-
ings between the brush tip and commutator face should show
uniform drops over the whole brush face In most cases in
practise however, such voltage readings will be only averages
For example, instead of a contact drop of one volt at a given
point, the actual voltage may be varying from zero to two volts,
or possibly from minus one volt to plus three volts These
pulsating e.m.fs. will result in high frequency local currents,
which have only a harmful influence on the commutation and
commatator and brushes These pulsations may be assumed
to be roughly related in value to the apparent short circuit
volts generated by the. armature conductor. In other words,
the higher the apparent short circuit volts per conductor, the
larger these pulsations are liable to be As the currents set up
by these pulsations must be limited largely by the brush contact
resistance, it is obvious that there is a limit to the pulsation*
in voltage, beyond which the current set up by them may be
harmful. A very crude practise, and yet possibly, the only
fairly safe one, has been to set an upper limit to the apparent
short circuit volts per bar, this limit varying to some extent with
the conditions of service, such as high peak loads of short dura-
tion, overloads of considerable period, continuous operation, etc.
Experience has shown that in commutating pole machines, the
apparent short circuit voltages per turn may be as high as four
to four-and-one-half volts, with usually but small evidence of
local high frequency currents, as indicated by the condition of
the brush face. If this polishes brightly, and the commutator
face does not tend to " smut," then apparently the local currents
are not excessive. However, in individual cases, the above
limits have been very considerably exceeded in continuoxis opera-
tion, while, in exceptional cases, even with apparently well
proportioned comxnutating poles, there has been evidence of
considerable local current at less than fo'ur volts per bar.
254 ELECTRICAL ENGINEERING PAPERS
The contact droi> between brush and commutator with the
usual brushes is about 1 to 1.25 volts As is well known, this
drop is not directly proportional to the current, but increases
only slowly with very considerable increases in current density
at the brush contact For instance, with 20 amperes per sq in.
in a given brush » the contact drop may be one volt ; at 40 amperes
per square inch, it may be 1 25 volts, while at 100 amperes per
square inch, it may be 1 4 volts, and, with materially higher
currents, it may increase but little further. This peculiar prop-
erty of the brush contact is, in some ways, very much of a dis-
advantage For instance, if the local currents are to be limited
to a comparatively low density, then necessarily the voltages
generating such currents must be kept comparatively low With
the above brush contact characteristics, two volts would allow
a local current of 20 amperes per square inch to flow, (there being
one volt drop from brush to commutator and one volt back to
the brush) If, however, the local voltage is three volts instead
of two, or only 50 per cent higher, then a local current of possibly
150 to 200 amperes per square inch may flow, and this excessive
current density may destroy the brush contact, as will be de-
scribed later
It may be assumed in general that the lower the apparent short
circuit voltage per armature conductor, the lower the pulsations
in this voltage are liable to be. Assuming therefore, as a rough
approximation a 50 per cent pulsation as liable to occur, then,
from the standpoint of brush contact drop, the total apparent
voltage of the commutated coil in continuous service machines
should not be more than 4 to 4J volts, which accords pretty well
with practise. For intermittent services, such as railway,
materially higher voltages are not unusual
As the main advantage pf the carbon brush is that it determines
or limits the amount of short circuit current, it might be ques-
tioned whether such advantage might not be carried much fur-
ther by using higher short circuit voltages and proportionately
greater resistance. However, there are reasons why this cannot
be done The carbon brush is a resistance in the path of the
local current, but it is also in the path of the work current As
the brush resistance is increased, the greater is the short circuit
voltage which can be taken care of with a given limit in short circuit
current, but at the same time, the loss due to the work current is
increased. Decreasing the resistance of the brush contact in-
creases the loss due to the short circuit current, but decreases
PHYSICAL LIMITATIONS IN D.C. MACHINES 255
that due to the work current. Thus in each individual case,
there is some particular brush resistance which gives minimum
loss However, this may not always be the resistance desired
for best commutation, from the operating standpoint, but these
two conditions of resistance appear to lie fairly close together
Practise is a continual compromise on this question of brush con-
tact resistance In some machines, a low resistance brush is
practicable, with consequent low loss due to work current. In
other cases, which, to the layman, would appear to be exactly
similar, higher resistance brushes give better average results
Thus one grade of carbon brush is not the most suitable for dif-
ferent machines unless they have similar commutating condi-
tions However, it is impractica*ble to design all machines of
different speeds, types, or capacities so that they will have equal
commutating -characteristics In non-commutating pole ma-
chines where only average commutating fluxes are obtainable,
the resistance of the brush is usually of more importance than
m the commutating pole type, for. in the latter, a means is pro-
vided for controlling the value of the short circuit current How-
ever, advantage has been taken of this latter fact to such an
extent in modern commutating pole machines, that the critical
or best brush resistance has again become a very important
condition of design and operation
"Apparent" Short Circuit em f per Brush. The preceding
considerations lead up to another limitation, namely, the total
e m f short circuited by the brush. This again may be considered
as being made up of two components, — the apparent short
circuit e.m f per bar times the average number of bars covered
by the brush, hereafter called " The apparent short circuit
e m.f per brush *'; and the e.m.f. per bar generated by the com-
mutating field, times the average number of bars covered by
the brush
As has been shown, ordinary carbon brushes can short circuit
2 to 2^ volts without excessive local current. Obviously , if the
resultant e.m.f. generated in all the coils short circuited by the
brush, — that is, the resultant of the short circuit e.m.fs , due to
both the armature and the commutating field is much larger
than 2J volts, large local currents will flow. Therefore, in a
commutating pole machine, for instance, the strength of the
commutating pole field should always be such that it also
neutralizes the total short circuit e.m.f- across the brush within
a limit represented by the brush contact drop, in order to keep
256 ELECTRICAL ENGINEERING PAPERS
within the limits of permissible local currents. With very
low resistance brushes, the proportioning of the commutating
field for neutralization of the apparent brush e.m.f. would
have to be much closer than with higher resistance brushes.
Moreover, not only should this e.m.f. generated by the com-
mutating flux balance the total short circuit voltage across the
brush within these prescribed limits, but these limits should
not be exceeded anywhere under the brush.
It might be assumed that if there is a pulsation of t\vo volts
per coil, for instance, then the total pulsation would be equal
to this value times the average number of coils short circuited.
However, this in general is not correct, as the e.m.f. pulsations
for the different coils are not in phase, and their resultant may
be but little larger than for a single coil
Based upon the foregoing considerations, the limiting values
of the apparent brush e.m.f. may be approximated as follows:
Assume ordinary carbon brushes with 1 to li volts drop with
permissible current densities — that is, with 2 to 2| volts opposr
ing action as regards local currents. Also, assume, for example,
an apparent brush short circuit e.m f . of 5 volts, with brush
resistance sufficient to take care of 2§ volts. Then the total
e.m f. due to the commutating flux need not be closer than 50
per cent of the theoretically correct value, with permissible
local currents. This is a comparatively easy condition, for it
is a relatively poor design of machine in which the commutating
pole strength cannot be brought within 50 per cent of the right
value. Assuming next, an apparent brush e.m.f. of 10 volts,
then the commutating pole must be proportioned within 25
per cent of the right value. In practise, this also appears to
be feasible, without undue care and refinement in proportion-
ing the commutating field. If this machine never carried any
overload, this 25 per cent approximation would represent a
relatively easy condition, for experience has shown that pro-
portioning within 10 per cent is obtainable in some cases, which
should allow an apparent brush e.m.f. of 25 volts as a limit.
However, experience al<o shows that this latter is a compara-
tively sensitive condition, which, while permissible on short
peak loads, is not satisfactory for normal conditions. Where
such close adjustment is necessary to keep within the brush
correcting limits, any rapid changes in load are liable to result
in sensitive commutating conditions, for the commutating pole
flux does not always rise and fall exactly in time with the arma-
PHYSICAL LIMITATIONS IN D.C MACHINES 257
ture flux, and ihus momentary unbalanced conditions of pos-
sibly as high as 10 or 12 volts might occur with an apparent
brush e.m.f. of 25 volts Also, very slight saturation in the
commutating pole magnetic circuit may have an unduly large
influence on unbalancing the e m.f . conditions. In other words,
the apparent brush short circuit and neutralizing e.m.fs. must
not be unduly high compared with the permissible corrective
drop of the brushes Experience shows that an apparent e rn.f
of 10 volts across the brush in well designed commutating pole
machines is usually very satisfactory, while, in occasional cases,
12 to 13 volts allow fair results on large machines, and, in rare
cases, as high as io to 18 volts has been allowed on small ma-
chines at normal rating. However, overloads, in some cases,
limit this permissible apparent brush voltage. As a rule, 30
volts across the brush on extreme overload is permissible,
but, usually this is accompanied by some sparking, usually
not of a very harmful nature if not of too long duration. Under
such overload conditions, doubtless unbalancing of three volts
or more may tye permissible, and thus, with 30 volts to be
neutralized, this means about 90 per cent theoretically correct
proportioning of the commutating pole flux. Cases have been
noted where as high as 35 to 40 apparent brush volts have been
corrected by the commutating pole on heavy overloads with
practically no sparking. This, however, is an abnormally good
result, and is not often possible of attainment. Obviously, with
such high voltages to be corrected, any little discrepancies in
the balancing action between 'the various* e.m.fs. are liable to
cause excessive local current flow.-
Incidentally, the above indicates pretty ' clearly why d-c
generators are liable to -flash viciously when dead short cir-
cuited. The ordinary large capacity machine can give 20 to
30 times rated full load current'on short circuit. If this large
current flows, then, neglecting saturation, the armature short
circuit e.m.f. across the brush will be excessive. Assuming,
for instance, a 10-volt limit for normal rating, then with only
ten times full load current, the apparent short circuit e.m f
would be 100 volts. The commutating pole, in the normal con-
struction, does not have flux margin of 10 times before high
saturation is reached, and in consequence, it may neutralize
only 50 to 60 volts of the 100. Therefore a resultant actual
e.m.f of possibly 40 volts must be taken care of by the brushes
This means an enormous short circuit current in addition to
258 ELECTRICAL ENGINEERING PAPERS
the 10 times work current. Vaporization of the copper and
brushes occurs and flashing results, as will be described more
fully in the treatment of flashing limits.
Brush contact drops of 1 to 1.5 volts have been assumed
in the preceding, and certain limits in the apparent short cir-
cuit e.m.f. based on these drops, have been discussed. How-
ever, the conditions may be modifi ed to a considerable extent
by effects of temperature upon the brush contact resistance.
Usually it has been assumed that the well known decrease in
contact resistance of carbon and graphite brushes with increase
in temperature, is in some ways related to the negative tem-
perature coefficient of carbon and graphite The writer has
been among those who advanced this idea, but later experience,
based upon tests, has shown that the reduced drop with increase
in temperature does not necessarily hold any relation to the
negative temperature coefficient of the carbon brush itself, for
similar changes in the contact drop have been found with ma-
terials, other than carbon, which actually had, in themselves,
positive temperature coefficients. Moreover, in some tests,
the changes in contact resistance with increase in temperature
have proved to be much greater in proportion than occurs
in the carbons themselves. In some cases, the measured drops
with temperature increases of less than 100 deg. cent decreased
to one-half or one-third of the drops measured cold
Obviously, these decreased contact resistances or drops may
have a very considerable effect on the amount of local current
which can flo\v and, therefore, in such case the foregoing general
deductions, should be modified accordingly However, the
results are so affected by the oxidation of the copper commutator
face, and other conditions also more or less dependent upon
temperature, that, as yet. no" definite statement can be made
regarding the practical effects of increase in temperature except
the general one that the resistance is usually lowered to a con-
siderable extent Apparently, oxidation of the copper face
tends toward higher contact resistance Ofttimes, "sanding
off " the glaze tends to give poorer commutation The above
points to one explanation of this
Assuming any desired limits for the apparent e m fs , such as
4 to 4| volts per commutator bar, it is possible to approximate
by calculation the limiting capacities of generators or motors in
terms of speed, etc Appendix I shows one method of doing
this In the writer's experience, a number of machines have been
PHYSICAL LIMITATIONS IN D.C. MACHINES
259
earned up to about the limits derived in the appendix, and the
practical results were in fair accord with the calculations. In
general, it may be said that in large machines, the upper limits
of capacity in terms of speed, etc. are so high that they do not
indicate any great handicap on future practise.
In the foregoing, the limits for the apparent short circuit e m.f .
per bar and per brush have been based upon the brush contact
resistance However, it may be suggested that something other
than the brush contact resistance might be used for limiting the
local current, and thus the commutating limits might be raised.
For instance, an armature winding could be completely closed on
itself, with high resistance leads carried from the winding to the
commutator bars. Each of such leads
would be in circuit only where the
brushes touched the commutator
bars. Thus there could be very con-
siderable resistance in each lead with-
out greatly increasing the total losses;
and, unlike the brushes, each lead
would be in circuit only for a very
small proportion of the time.
About 10 years ago, the writer de-
signed a non-commutating pole d-c.
turbo-generator with such resistance
leads connected between the winding
and the commutator. The leads were
placed in the armature slots below the
main armature winding. The idea was
to have enough resistance in circuit
I I I I ITTT
FIG. 1
with the short circuited coils that the brushes at no load could be
thrown well forward into a field flux sufficient to produce good
commutation at heavy load, even if very low resistance brushes,
were used. Tests of this machine showed that the non-sparking
range, with the brushes shifted either forward or back of the
neutral point was very much greater than in an ordinary machine.
In this case, it developed that the leads were of too high resistance
for practical purposes, as the armature ran too hot, the heat-dis-
sipating conditions in a small d-c. turbo-armature not being any
too good at best. These tests however, indicate one possibility
in the way of increasing the present limits of voltage per bar and
volts across the brush. Moreover, such resistances can have a
positive temperature coefficient of resistance, instead of the
260 ELECTRICAL ENGINEERING PAPERS
negative one of the carbon brushes and contacts. Also, the
corrective action in limiting local currents would vary directly
with the current over any range, and not reach a limit, as in car-
bon brushes
Considerable experience with resistance leads in d-c operation
has also been, obtained in large a-c, commutator type railway
motors, designed for operation on both a-c and d-c. circuits.
Apparently these leads have a very appreciable balancing action
as regards division of current between brush arms in parallel.
With but few brushes per arm, it appears that very high current
densities in the brushes can be used without undue glowing or
honeycombing. Presumably the reduction in short circuit
current, when operating on d-c , also has much to do with this.
Some special tests were made along this line, and it was found that
a, very low resistance in the leads, compared with that which was
best for a-c. operation, was sufficient to exert quite a decided
balancing between the brush arms
With properly proportioned resistance leads it should be pos-
sible to use very low resistance brushes, and relatively high
current densities. Advantage of this might be taken in various
ways. There may prove to be serious mechanical objections to
such arrangements However, if the objections are not too
serious, the use of resistance leads in this manner may be prac-
tised at some future time as we approach more extreme flesigns
FLASHING
One of the limits in commtltating machinery is flashing. This
tnay be of several kinds. There may be a large arc or fla£h
from the front edge of the brush, which may increase in volume
until it becomes a flash-over to some other part of the machine.
Again, a flash may originate between two adjacent bars at some
point between the brush arms, and may not extend further, or
•it may grow into a general flashover. Different kinds of flashes
:may arise from radically different causes, some of which may be
-normally present in the machine, while others may be of an
.accidental nature.
Whatever the initial cause, the flash itself means vaporized
conducting material. If the heat developed by or in this vapor
arc is sufficient to vaporize more conducting material — that is,
generate more 'conduct ing vapor — then the arc or flash will grow
or continue. Thus, true flashing should be associated with
vaporization, ,and, in sttany cases, in order to get at the initial
PHYSICAL LIMITATIONS 7.V D C MACHINES 261
cause of flashing, it is only necessary to find the initial cause of
vaporization.
Arcs Between Adjacent Cowrmit-ator Bars. This being one of
the easiest conditions to analyze, it will be treated first, especially
as certain flashing conditions are dependent upon this.
A not uncommon condition on commutators in operation is
a belt of incandescent material around the commutator, usually
known as "ring fire" This is really incandescent material
between adjacent bars, such as carbon or graphite, scraped off
the brush faces usually by the mica between bars. As the mica
tends to stand slightly above the copper, due to less rapid "wear,"
its natural action is to scrape carbon particles off the brush.
These particles are conducting and if there is sufficient voltage,*
and current to bring them up to incandescence, this shows as a
streak of fire around the commutator In many cases, by its
different intensities around the commutator, trlis ring fire shows
plainly the density of the field flux, or e m.f . distribution around
the machine It is practically zero in the commutating or
neutral zone, and shows plainly under the main field. In loaded
machines, this often indicates roughly the flux distortion. In
machines which act alternately as motors and generators, as in
reversing mill work, the point of highest incandescence shifts
forward or backward over the "commutator, depending upon the
direction of field distortion.
In undercut commutators (those with mica cut below the cop-
per surface) this ring fire is also observable at times, due to con-
ducting particles in the slots between bars. Usually such
particles consist of carbon or graphite, as already stated, but
particles of copper may also be present. Also, oil or grease, mixed
with carbon, will carbonize under incandescence, and will thus
add to the ring fire. Often when a commutator is rubbed with
an oiled cloth or wiper, ring fire will show very plainly, and then
gradually die down. The burning oil exaggerates the action,,
and also, the oil itself may enable a conducting coating to adhere-
to the mica edges, thus starting the action, which disappears*
when the oil film is 'burned away. However, when the oil can-
penetrate the mica, the incandescence may continue in spots and
at intervals, the mica being calcined or burned away so that it
gradually disppears in spots. This is the action usually called.
"' pitting ", which experience has shown to be almost invariably
caused by conducting material in the mica, such as carbonized
•oil, carbonized binding material, copper and carbon particles
been carried in with the oil, etc.
'262
ELECTRICAL ENGINEERING PAPERS
This ring fire is not always a direct function of the voltage
between bars, although, under exactly equivalent conditions of
speed, grade of brushes, etc., it is closely allied with voltage condi-
tions. In high voltage machines, usually hard high-resistance
brushes are used, which tend to give off the least carbon in the
form of particles; while in low voltage machines, soft, low-re-
sistance brushes, with a good percentage of graphite in them, are
common, and these naturally tend to coat the mica to a greater
extent.
Under extreme conditions, this ring fire may become so intense
locally that there is an actual arc formed between two adjacent
bars, due to vaporization of the copper. This may show in the
form of minute copper beads at the edge of the bar, or minute
"pits" or "pockets" may be burned in the copper next to the
mica. In extreme cases, where the voltage between bars is
sufficient to maintain an arc, conical shaped
cavities or holes may be burned in the
copper. In such cases, the arc is usually
explosive, resembling somewhat a small ,
"buck-over." An examination of the com-
mutator will show melted-out places, as in
Pig. 2. Part of the missing copper has
been vaporized by the arc, while part may
have become so softened or fused that it is
thrown off by centrifugal force. Exper- '
ience shows that sometimes these explosive
IIITITI
FIG. 2
arcs grow into general flashes, while at other times, they are
purely local.
An extended study was made of such arcs to determine the
conditions which produced them. Also, numerous tests were
made, the results of which are given below,
i It was determined first, that these explosive arcs between
adjacent bars were dependent, in practically all cases, upon a
fairly high voltage between bars. This was reasonable to expect,
but it was found that the voltage between bars which would
produce arcs in one case, would not do so in another. Apparently
there were other limiting or controlling conditions. It developed
that the resistance of the armature winding between two adja-
cent bars has much to do with the arc. Apparently an excessive
current is necessary to melt a small chunk out of a mass of good
heat-conducting material like a large copper commutator; * and
also, a certain amount of time is required to bring it up to the
PHYSICAL LIMITATIONS IN D.C. MACHINES 263
melting point Therefore, both time and current are involved,
as \\ ell as voltage. A series of tests was made to determine some
of the limiting conditions.
The commutator of a small machine (about 20 kw., high speed)
was sprinkled with iron filings, »fme dust, etc, during several
days' operation under various conditions of load, field distortion,
etc. Such dust, whether conducting or not; apparently would not
cause arcing between bars. Graphite was finally applied with a
special "\\iper," and with this, small arcs or flashes could be
produced at 50 to 60 volts maximum between commutator bars.
It soon became evident that this was too small a machine from
which to draw conclusions. Then numerous other much larger gen-
erators were tested A slow-speed engine type generator of 200-kw.
capacity at 250 volts, was speeded up to about double speed,
in order to obtain sufficiently high e.m.f. between commutator
bars. With a clean commutator nothing was obtained at 40
volts maximum per bar. The commutator was then wiped with
a piece of oily waste which had been used to wipe off other com-
mutators. Arcs then occurred repeatedly between commutator
bars, although all such arcs were confined to adjacent bars and
there were no actual flashovers from brush holder to brush holder.
Moreover, the arcs always appeared to start about midway
between brush arms or neutral points, and lasted only until the
next neutral point was reached. Quite large pits or cavities
were burned in the bars next to the mica, as shown in Fig. 2.
some of these being possibly J inch in width, and 1/16 inch deep
or more at the center This indicated excessively large currents.
These arcs would develop at about 32 to 34 volts between bars,
and they were very vicious (explosive) above 35 volts
Still larger machines were tested with various speeds, voltage
between bars, etc It was found that, as a rule, the larger the
machine — or rather, the lower the resistance of the armature
winding per bar — the lower would be the voltage at which serious
arcing would develop In these tests, it was found that graphite
mixed with grease gave the most sensitive arcing conditions.
In these various tests, no arcing between bars was developed
in any case at less than 28 volts maximum, while 30 volts was
approximately the limit on many machines. However, the
results varied with the speed Apparently it took a certain time
to raise the incandescent material to the arcing point and to build
up a big arc. Therefore, the duration of the possible arcing
period appeared to be involved. If this were so, then a higher
264 ELECTRICAL ENGINEERING PAPERS
voltage limit for a shorter time should be possible with the same
arcing tendency. Also, if this were the case, then with 30 volts
maximum, for instance, between commutator bars with an un~
distorted field flux, the arcing should be the same as with a some-
what higher voltage with a highly distorted narrow peaked field.
In other words, the limiting voltage between bars on a loaded
machine might be somewhat higher than on an unloaded machine.
This was actually found to be the case, the, difference being from
10 per cent to 15 per cent in several instances. This, however,
depended upon various limiting conditions such as the actual
period within which the arc could build up to a destructive
point, etc.
One very interesting case developed which apparently illus-
trated very beautifully the effects of lengthening or shorten-
ing the period during which the arc could occur. A high-speed,
600-volt generator of a motor-generator set was speeded up
about 60 per cent above normal. Even at normal speed this
was a rather high-frequency machine, so that the period of
time for a commutator bar to pass from neutral point to neutral
point was very short. At the highest speed the graphite-grease
was used liberally on the commutator, but without causing arc-
ing, even when the voltage was raised considerably higher
than usually required for producing arcs between bars in other
machines of similar size. Neither was there much ring-fire
at the highest speed with normal voltage. Finally, after an
application of graphite, without forming arcs or unusual ring-
fire, the speed was reduced gradually with normal voltage
maintained. The ring-fire increased with decrease in speed, until
at about normal speed, it was so excessive that the on-lookers
expected an explosion of some sort. However, the voltage
was now below the normal arcing point and nothing happened.
At still lower speed, but with reduced voltage on account of
saturation, the ring-fire gradually decreased. Apparently at
the very high speeds, the tirrie was too short for the ring-fire to
reach its maximum; while with reduction in speed, even with
somewhat reduced voltage, the, ring-fire increased to a maxi-
mum and then decreased. This test was continued sufficiently
to be sure that it was not an accidental case. Only a certain,
combination of speed, frequency, voltage, etc. could develop
this peculiar condition, and it was purely by accident that
this combination was obtained, for the result was not foreseen
in selecting the particular machine used.
PHYSICAL LIMITATIONS IN D.C MACHINES 265
A summation of these and other tests led to th£ conclusion
that there were pretty definite limits to the maximum volts
per bar, beyond which it was not safe to go. These limits
however, involved such a number of conditions that no fixed
rule could be established, and apparently, the designer has
to use his judgment and experience to a certain extent, if he
works very close to the limits. The grades and materials of
the brushes, the thickness of the mica, flux distortion from over-
loads, etc. must be taken into account. For instance, the above
tests were made on machines with 1/32-inch mica between bars.
This thickness is fixed, to a great extent, in non-undercut
commutators, by conditions of mica wear, as will be referred
to later. But with undercut commutators, thicker mica can
be used, and, while the gain in permissible safe voltage between
bars is not at all in proportion to the mica thickness, yet it is
enough to deserve consideration.
The general conclusions were that with 1/32-inch mica,
large current machines would very rarely flash with 28 volts
maximum between bars; while with moderate capacities, 30
volts is about the lower limit; and with still smaller machines,
100 kw. for example, this might be as high as 33 to 35 volts,
the limit rising to 50 or 60 volts with very1 small machines.
Of course, the brush conditions have something to do with
the above limits, and many exceptions to these figures will be
found in actual practise. Many machines are in daily service
which are subject to more or less ring-fire, but which have never
developed trouble of any sort, and doubtless never will. Ap-
parently, ring-fire in itself is not harpiful, as a rule. It is only
where it starts some other trouble tiat it may be considered as
actually objectionable.
The above limiting figures are interesting when compared
with the voltages necessary to establish arcs in general. An
alternating arc through air will not usually maintain itself at
less than some limiting voltage such as 20 to 25 volts, corres-
ponding to peak values of 28 to 35 volts. Moreover, an arc
formed between the edges of two insulated bodies, such as ad-
jacent 'commutator bars, will naturally tend to rupture itself
due to the shape of its path. Furthermore, the resistance and
"reactance of the short circuited path, while comparatively low
in large machines, will tend to. limit the voltage which main-
tains the arc. In snr>a-11 machines with relatively high internal
drops in tlie sfoort circuited coils> the current will not reach a
266 ELECTRICAL ENGINEERING PAPERS
commutator vaporizing value unless the initial voltage between
bars is comparatively high, and usually the explosive actions
are relatively small, and, in many cases, no senous arcs will
develop at all. Obviously, the less the local current can in-
crease in the case of short circuits between adjacent bars, the
higher the voltage between bars can be, without danger. In
machines having inherent constant current characteristics, very
high voltages between adjacent commutator bars are possible
without serious flashing or burning. In consequence, from the
flashing standpoint, constant current machines can be built for
enormously high terminal voltages, compared with constant
potential machines. This is a point which is very commonly
overlooked in discussing high-voltage d-c. machines.
Cbming back to the subject of arcs between commutator
bars, these are more common than is usually supposed, for,
in ma,ny cases, the operating conditions are such that* these
arcs, if very small, or limited, will show no visible evidence.
Only very minute 'particles of copper may be vaporized. How-
ever, these minute arcs may sometimes lead directly to more-
serious flashing. If, for instance, they occur in proximity to-
some live part of the machine, such as an over-hanging brush
holder which is at a considerable difference of potential from
the arcing part of the commutator, the conducting vapor may
bridge across and start a big arc or flash. "In one instance/
which the writer has in mind, a very serious case of trouble
occurred in this way. This was a very large capacity 250-
volt, low-speed, generator, in which the maximum volts per
bar were not unduly high. When taking the saturation curve
in the shop test, this machine " bucked" viciously several
times, apparently without reason. An investigation of the
burning indicated a possible source of trouble. The brush
holder arms or supports to which the individual holders were
attached, were located over the commutator about midway
between neutral points, and, about one inch from the com-
mutator face. This was not the normal position of the brush
arms, as a temporary set of holders was being used for this test.
It was noted that just before the flashovers occurred, con-
siderable ring-fire developed. The conclusion was drawn from
all the evidence that could be obtained, that a small arc had
formed between bars that had reached to the brush arms, thus
short circuiting a high enough voltage to draw a real flash.
This happened not once but several times. The proper holders.
PHYSICAL LIMITATIONS IN D.C. MACHINES 267
were then applied, which put the brush arms in a much less
exposed position, and not a single flashover occurred in all the
subsequent tests and operation. In another case, a large syn-
chronous converter carrying full load on shop test flashed over
a number of times, apparently without sufficient cause. The
commutation was perfect, as evidenced by the fact that there
was no perceptible sparking. The maximum voltage between
bars was comparatively low. At "first the flashovers were
blamed on drops of water from the roof of the building, but
this theory was soon disproved. An examination of the brush -
holders showed that certain live parts, fairly close to the com-
mutator, were at a considerable difference of potential from the
nearest part of the commutator. There was but little ring-
fire on the commutator, and therefore, minute arcs at first were
not blamed for the trouble. A modified brush holder was tried
however, with a view to decreasing the high difference of poten-
tial between the live parts. All flashing then disappeared and
no trouble of this sort was ever encountered in a large number
of duplicate machines brought through afterwards. Both the
above cases should be considered as abnormal, and they have
been selected simply as examples of what small arcs between
bars may do. These two cases do not in themselves constitute
a proof of this action, but they serve to verify other evidences
which have been obtained. *
In view of the fact that small arcs of a non-explosive sort
may form at voltages considerably lower than the limits given
in the preceding part of this paper,- it should be considered
whether such small arcs can cause any trouble if no other live
parts of the machine are in close proximity. One case should^
be considered, namely, thai of other commutator bars adjacent
to the arc. When conducting vapor is formed by the first
minute arc, this vapor in spreading out may bridge across a
number of commutator bars having a much liigher total differ-
ence of potential across them than that which caused the initial
arc. Assume, for instance, a very crowded design of high*
voltage corrfmutator. In some cases, in order to use high rota-
tive speeds, without unduly high commutator peripheral speed*
the commutator bars are sometimes made very thin and the
volts per bar very high, possibly up almost to the limit. As-
suming a thickness of bar and mica of 0.2 inch (or 5 bars per
inch) and a maximum volts per bar of 25, then there is an e.m f .
of 125 volts per inch circumference of the commutator- In such
268 ELECTRICAL ENGINEERING PAPERS
case, a small arc between two bars may result in bridging across
a comparatively high voltage through the resulting copper
vapor Therefore, when considering the possible harmful effects
of minute arcs, the volts per inch circumference of the commuta-
tor should be taken -into consideration. The writer observed
one high-voltage commutator which flashed viciously at times,
apparently without " provocation " The only explanation he
could find was that the vapor from little arcs resulting from
ringfire was sufficient to spread all over the commutator, the
bars being very thin and the voltage per bar very high. How-,
ever, difficullies from this cause have not yet become serious,
probably because no one has yet carried such constructions to
the extreme, in practical work
High voltage between commutator bars may result in flash-
ing due to other than normal operating conditions. Excessive
overloads may give such high voltages per armature coil or per
commutator bar, immediately under the brush, that the terrific
current rush will develop conducting vapors under the brush,
which appear immediately in front of the brushes, as such vapors
naturally are carried forward by rotation of the commutator.
This short circuit condition under the brush has already been
referred to when treating of commutation limits It was shown
then that an inherent short circuit voltage of 4 to 4| volts' is
permissible in good practise Immediately under the com-
mutating pole this voltage is practically neutralized by the
commutating pole field, but immediately ahead or behind the
pole it is not neutralized usually, except to the extent of the
commutating pole flux fringe. Thus, the resultant voltage
between two bars a little distance ahead of the brush, is liable
to be considerably higher than under the brush Assuming,
for instance, 3£ volts per bar, due to cutting the resultant field
just ahead of the1 brush, then with 10 times full load current,
for example, there would be 35 volts between bars, and this is
liable to be accompanied by highly conducting vapor formed
"by the excessive current at the brush contact, this vapor being;
carried forward by rotation of the commutator. Here are the
conditions for a flash, which may or may not bridge across to
.some other live part If the current rush is not too great, this
flash will usually appear only as a momentary blaze just in
front of the brush. In many cases, if this blaze or heavy arc
were not allowed to come in contact with, or bridge between,
any parts having high difference of potential, it would not be
PHYSICAL LIMITATIONS IN D.C MACHINES 269
particularly harmful. In case of " dead short circuiting" of
large moderately high-voltage machines where the current can
rise to 25 or 30 times normal, it is astonishing how large such
arcs or flashes may become, and to what distances they will
reach. The arc will sometimes go in unanticipated directions.
The conducting vapor may be deflected by magnetic action
and by air drafts Shields or partitions will sometimes pro-
duce unexpected results, not necessarily beneficial. Unless
such shields actually touch the commutator f ac e so that con-
ducting vapor cannot pass underneath them, the vapor that
does pass underneath may produce just as harmful results as
if the shields were not used. Trying to suppress such arcs by
covers or shields is very much the case of damming a river at
the wrong end in order to prevent high water
From the preceding considerations it would appear that a
compensated direct-current machine should have some ad-
vantages over the straight commutating-pole type in case of a
severe short circuit. With the lesser saturation in the com-
mutating pole circuit due to the lower leakage, the apparent
armature short circuit e.m.f. will usually be better neutralized
under extreme load conditions, and thus there will be lower
local currents in the brush contacts In addition, the armature
flux will be practically as well neutralized behind and ahead
of the brush, as it is under the brush, so that, with ten times
current as in the former example, there may be only a low
e m.f. per bar ahead of the brush, instead of the 35 volts for
the former case Obviously, the initial flashing cause, and the
tendency to continue it ahead of the brush, will be materially
reduced. The compensating winding is -therefore particularly
advantageous in very high voltage generators, in which the
bars are usually very thin and the maximum volts per bar are
high.
There is a prevailing opinion that when a circuit breaker
opens on a very heavy overload or a short circuit, flashing is-
liable to follow from such interruption of the current In some
cases, this may be true However, when a breaker opens on.
a short circuit, it is difficult for the observer to say whether both
the opening of the breaker and the flash are due to the excessive
momentary current, or one is consequent to the other. The
short circuit, if severe, will most certainly cause more or less
of a flash at the brush contacts by the time the breaker is opened,
and if this flash is carried around the commutator, or bridges
270 ELECTRICAL ENGINEERING PAPERS
across two points of widely different potentials, then it is liable
to continue after the breaker opens, and thus ^ives the im-
pression that the flashing followed the interruption of the cir-
cuit. In railway and in mine work in particular, a great many
flashes which are credited to overloads are primarily caused by
partial short circuits on the system, or " arcing shorts," which
are extinguished as soon as the main breakers are opened, so
that but little or no evidence of any short circuit remains.
Such a partial short circuit however, may be sufficient to open
the generator circuit and to cause a flash at the same time.
Not infrequently, such flashes are simply credited to opening
of the breakers
There are other conditions, however, where a flash is liable
to result directly from opening the breaker on heavy overload.
If as referred to before, the apparent short circuit e m.f. per
brush on heavy overload is from 25 to 35 volts, then if the
armature magnetomotive force could be interrupted suddenly,
with a correspondingly rapid reduction in the armature flux,
while the commutating field flux does not die down at an equally
rapid rate, then momentarily, there will be an actual short
circuit voltage of a considerable amount under the brushes
which may be sufficient to circulate large enough local currents
to start flashing.. With commutating pole machines, this con-
dition may result from the use of solid poles and solid field
yokes Laminated commutating poles are sometimes very much
of ah improvement. However, the yokes of practically all
direct current machines are of solid material, and thus tend to
give sluggishness in flux changes. The above explains why non-
inductive shunts, or any closed circuits whatever, are usually
objectionable on commutating poles or their windings.
Iri non-commutating pole machines, where the brushes are
liable to be shifted under the main field magnetic fringe in
order to commutate heavy loads, flashing sometimes results,
when such heavy overload is interrupted.
Also, if the rupture of the current is very sudden, there \ull
be an inductive " kick " from the collapse of the armature
magnetic field. This rise in voltage sometimes is sufficient to
start a flash, especially in those cases where flashing limits are
already almost reached.
In synchronous converters, the conditions are materially
different from d-c. generators as regards flashing when the
load is suddenly broken. In such machines, the flash is liable
PHYSICAL LIMITATIONS IN D.C. MACHINES 271
to follow the opening of the breaker, if simply a heavy over-
load is interrupted. This is possibly more pronounced in the
commutating pole machine than in the non-commutating pole
type In a commutating pole converter, the commutating
pole magnetomotive force is considerably larger than the re-
sultant armature magnetomotive force, under normal opera-
ting conditions, but is much smaller than the armature magneto-
motive force considered as a straight d-c. or a-c. machine.
Normally the commutating pole establishes a commutating
field or flux in the proper direction in the armature. However,
if, for any reason, the converter becomes a motor or a generator,
even momentarily, the increased magnetomotive force of the
armature may greatly exceed that of the commutating pole,
so that the commutating pole flux will be greatly increased, or
it may be greatly reduced, or even reversed, depending upon
which armature magnetomotive force predominates.
The above is what happens when a synchronous converter
hunts, and under the accompanying condition of variable
armature magnetomotive force, the commutating pole con-
verter, with iron directly over the commutating zone, is liable
to show greater variations in the flux in the commutating zone
than is the case in the non-commutating pole converter. Ex-
perience has shown that uhen a synchronous converter carry-
ing a heavy overload has its direct-current circuit suddenly
interrupted, it is liable to hunt considerably for a very short
. period, depending upon the hunting constants of the individual
machine and circuit. Apparently, all converters hunt to some
extent \\ith such change in load. This hunting means wide
variations in the commutating pole flux with corresponding
sparking tendencies. For a " swing " or two, this sparking
may be so bad as to develop into a flash. Thus the flash follows
the interruption of the circuit.
Curiously, the most effective remedy for this condition is
one ^hich has proved most objectionable in d-c. machines,
namely, a low-resistance closed electric circuit surrounding the
commutating pole. The primary object of this remedy is" not
to form a closed circuit around the commutating field, but to
obtain a more effective damper in order to minimize hunting.
In a paper presented before the Institute several years ago,*
the writer, showed that the ideal type of cage winding for damp*
*Commtitating Poles in Synchronous Converters. PSage 171.
272 ELECTRICAL ENGINEERING PAPERS
ing synchronous converters, namely, that in which all circuits-
are tied together by common end rings, was not suitable for
commutating pole converters due to the fact that the various
sections of this cage winding form low-resistance closed circuits
around the commutating poles. This was in accord \\ith all
evidence available to that time, and no one took exception to
it However, later experience has shown that this was incor-
rect, for, in later practise, it was found that the use of a complete
cage damper of low resistance which decreases the hunting
tendency, also greatly decreases the flashing tendency, so that
today most converters of the commutating pole type are being
made with complete cage dampers. Apparently, the flashing
tendencies in converters due to hunting are much worse than
those due to flux sluggishness. Therefore, a sacrifice can be
made in one* for the benefit of the other.
In the case of a dead short circuit on the d-c side of a syn-
chronous converter, there is liable to be flashing, just as in the
d-c machine, and the flash and the breaker opening are liable
to occur so closely together that an observer cannot say which
is first.
In d-c. railway motors, flashing at the commutator is not
an uncommon occurrence One rather common cause of flash-
ing, especially at high speed, is due to jolting the brushes away
from the commutator, due to rough track, etc This is espe-
cially the case with light spring tension on the brushes. The
carbon breaks contact with the copper, forming an arc which
is carried around. Another prolific source of flashing is due
to opening and closing the motor circuit in passing over a gap
or dead section in a trolley circuit Here the motor current
is entirely interrupted, and, after a short interval, it comes oa
again, without any resistance in circuit except that of the motor
itself. If the current rush at the first moment of closing is
not too large, and if the armature and field magnetic fluxes
build up at the same rate, then there is usually but small danger
of a flash, except under very abnormal conditions. The rapidly
changing field flux however generates heavy currents under
the brushes, thus tending toward flashing. The reactance of
the motor, especially of the field windings, limits the first cur-
rent rush to a great extent. According to this, closed second-
ary circuits of low resistance around either the main poles or
the commutating poles, should be objectionable, and experience
bears this out
PHYSICAL LIMITATIONS IN D.C. MACHINES 273
In railway armatures, as a rule, fewer commutator bars per
pole are used on the average than in stationary machines of
corresponding capacity, except possibly, in large capacity
motors. This is due largely to certain design limitations in
-such apparatus, but this has doubtless been responsible for a
certain amount of flashing in such apparatus
Average em.f. and " Field Form" A rather common prac-
tise has -been to specify the average volts per bar in a given
machine. This, in itself, does not mean anything, except in a very
general way; for the lirr.it is really fixed by the maximum volts
per bar, as already shown, and there is no fixed relation between
the average and the maximum volts per bar. The ratio be-
tween these two voltages is dependent upon the field flux dis-
tribution,— that is, the "field form." In practise, this ratio
varies over a ^ide range, depending upon the preferences of
the designer, upon limitations of pole space available, etc.
Also, TTvith load, it depends upon the amount of flux distortion
of the field, which, in turn varies greatly in practise. In well
proportioned modern machines, where space and other limita-
tions permit, the average e.m.f. per bar is about 70 per cent
of the maximum at no load, and about 55 per cent to 60 per
cent with heavy load. This means that about 15 volts per
bar, average, is the maximum permissible, in large machines
with considerable field distortion, if a maximum of 28 volts
per bar is not to be exceeded. On this basis, a 600-volt machine
should therefore have not less than 40 commutator bars per
pole. However, this is with considerable field distortion. If
this distortion is reduced or eliminated, the average volts can
be considerably higher, as in machines with high saturation in
the pole faces, pole horns and armature teeth, or with com-
pensated fields. Synchronous converters are practically self-
compensated and can therefore have higher limits than the
above, if the normal rated e.m.f. is never to be exceeded. How-
ever, in 600-volt converter work, in particular, wide variations
sometimes momentarily occur, up to 700 to 750 volts, and such
machines should have some margin for such voltage swings.
The ordinary 600-volt d-c. generator also attains materially
Hgher voltages at times, which would be taken into account
in the limiting voltage per commutator bar and the total number
of commutator bars per pole.
Obviously, the " fatter * the field form, the nearer the aver-
age voltage caa apf>nwb the maximum. With an 80 per cent
274 ELECTRICAL ENGINEERING PAPERS
field form, instead of 70 per cent, for instance, the number of
bars per pole can be reduced directly as the polar percentage
is increased; and 35 bars per pole with 80 per cent would be as
good as 40 bars with 70 per cent assuming the same percentage
of field distortion in both cases. An increase in the polar arc
will tend toward increased distortion, but the reduced number
of turns per pole should practically balance this, so that, other
things being unchanged, the flux distortion should have prac-
tically the same percentage as before.
In large machines of very high speeds, large polar percentages,
— that is, large " field form constants," are very advantageous,
but are not always obtainable, due to the space required for the
commutating pole winding. In compensated field machines,
with their smaller commutating pole windings, the conditions
are probably best for high field form constants, and high aver-
age volts per bar; and thus this type often lends itself very-
well to those classes of ma-
chines where the minimum
possible number of commu-
tator bars is necessary. This
is the case with 'very high
speeds, and also for very high
voltage machines.
Usually it is considered that
the commutating conditions JG>
of a machine are practically the same with the same current,
whether it be operated as a generator or motor. However,
when it comes to flashing conditions, there is one very consider-
able difference between the two operations. In the d-c. gen-
erator, the field flux distortion by the armature is such as to
crowd the highest field density, and thus the highest volts
per bar, away from the forward edge of the brushes. In the
motor, the opposite is the case, and therefore there is a steeply
rising field, and a corresponding e.m.f. distribution in front of
the brushes. As the flash is carried in the direction of rotation
it may be seen that, in this particular, the generator and motor
are different.
BLACKENING AND BURNING — HIGH MICA — " PICKING UP "
COPPER
In the preceding, certain limitations of commutation and
flashing have been treated. There are, in addition, a number
PHYSICAL LIMITATIONS IN D.C MACHINES 275
of other conditions which are related closely to commutation,
and which have already been touched upon to a limited extent.
One of these is the permissible current density in the brushes
or brush contacts.
As brought out before, there are two currents to be con-
sidered, namely, the work current which flows to or from the
outside circuit, and the local or short circuit current which is
purely local to the short circuited coils and the brush. The
true current density is that due to the actual resultant current
in the brush tip or face, which is very seldom uniform over the
whole brush tip. The " apparent " current density is that due
to the work current alone — assumed to be uniform over the
brush tip. The current density very commonly has been as-
sumed as the total work current, in and out, divided by the
total brush section, and, moreover, this has been considered
as the true current density, the local or short circuit currents
being neglected altogether. This method of considering the
matter has been very misleading, resulting in many cases, in
a wrong or unsuitable size of brush being used just to meet
some specified current density. In many of the old, non-com-
mutating pole machines, the local currents were predominant
under certain conditions of load, for the brushes, as a rule, had
to be set at the best average position, so that at some average
load, the commutating conditions would be best. At higher
and lower loads, the short circuit currents were usually com-
paratively large. The wider the brush contact circumferen-
tially, the greater would be the short circuit currents and the
higher the actual current density at one edge of the brush,
while the apparent density would be reduced. Thus, in at-
tempting to meet a low specified current density, the true den-
sity would be gregtly increased. The fallacy of this procedure
was shown in many cases in which the brush contact was very
greatly reduced by grinding off one edge of the brush. Very
often, a reduction in circumferential width of contact to one-
half resulted in less burning of the brush face. The apparent^
density was doubled but the actual maximum density was .
actually reduced. Many of these instances showed very
conclusively that much higher true current densities were prac-
ticable, provided the true and apparent densities could be
brought more nearly together. This is what has been accom-
plished to a considerable extent in the modern well designed
commutating pole machine* In such machines, the current dis-
276 ELECTRICAL ENGINEERING PAPERS
tribution at the brush face is nearly uniform under all condi-
tions of load It is not really uniform, even in the best machines ;
but the variations from uniformity, \\hile possibly as much as.
50 per cent in good machines, is yet very small compared \vith.
the variation in some of the old non-commutating pole machines.
In consequence, it has been possible to increase the apparent
current densities in the brushes in modern commutating pole
machines very considerably above former practise, while still
retaining comparatively wide brush faces. In fact, the width
of the brush contact circumferentially is not particularly limited
if the commutating field flux can be suitably proportioned;
that is, where a suitable width and shape of commutating field
can be obtained. In many of the old time machines, an ap-
parent density of 40 amperes per square inch under normal
loads was considered as amply high, while at the present timeT
with well proportioned commutating poles, 50 per cent higher
apparent densities are not uncommon However, experience
shows that the same brushes, with perfectly uniform distribu-
tion of current at the brush face, can carry still higher currents.
Therefore, in modern commutating pole machines, the actual
upper limit of brush capacity is not yet attained. But there
are reasons \\hy this upper lirr it is not practicable. One reason
is that already given, that uniform current distribution over
the brush face is seldom found. This rreans that a certain
margin must be allowed for variations. A second reason lies-
in the unequal division of current between the various brushes-
and brush arms. This may be due initially to a number of
different causes. However, when a difference in current once
occurs, it tends to accentuate itself, due to the negative co-
efficient of resistance of the carbon brushes and brush contacts.
If one of the brushes, for instance, takes more than its share of
current for a period long enough to heat the brush more than,
the others, then "its resistance is lowered and it tends to take
still more current. If there were no other resistance in the
current path, it is presumable that the parallel operation off
xarbon brushes would be more or less unsatisfactory. In the
practical case, however, instead of the operation being im-
practicable^ it is merely somewhat unstable. Unequal division
of current between the brushes on the same brush arms, is to
some extent, dependent upon the total current per arm. Where
there are many brushes in parallel and the total current to
be carried is very large, it is obvious that one brush may take
PHYSICAL LIMITATIONS IN D.C MACHINES 277
an excessively large current without materially decreasing the
current carried by the other brushes. As a rule, the larger
the current per arm, the more difficult is the problem of prop-
erly balancing or distributing the current among all the brushes.
Schemes have been proposed, and patented, for forcing equal
division, but, as a rule, they have not proved very practicable,
although some comparatively simple expedients have been
tried out ^ith a certain degree of success.
In the same way, the division of current among brush arms
of the same polarity is not always satisfactory. 50 per cent
variation of current between different arms is not very unusual,
and the writer has seen a number of instances where the varia-
tion has been 100 per cent, or even much more. Obviously,
with such variation, it is not practicable to work the brushes up
to the maximum density possible, for some margin must be
allowed for such unbalancing.
Experience has shown that when current passes through
a moving contact, as from a brush to the commutator copper,
or vice versa, a certain action take place which resembles elec-
trolytic action to some extent, although it is not really electro-
lytic. It might also, be said to resemble some of the actions
which takes place in an arc. Minute particles appear to be
«aten or burned away from one contact surface, and these are
sometimes deposited mechanically upon the opposing surface.
The particles appear to be carried in the direction of current
flow, so that if the current is from the carbon brush to the
copper, the commutator face will tend to darken somewhat,
•evidently from depositation of carbon. If the current is from
the copper to the carbon, the brush face will sometimes tend
to take a coating of copper, while the commutator face will
take a clean, and sometimes raw, copper appearance. As the
current is in both directions on the ordinary commutator, this
action is more or less averaged, and therefore is not usually
noticed. With one polarity or direction of current, the com-
mutator face eats away, while with the other direction, the
brush face is eaten away and may lose its gloss.
The above action of the current gives rise to a number of
limiting conditions in direct-current practise. Experience shows
that this " eating away " action occurs with all kinds of brushes,
and with various materials in the commutator. It appears to
be dependent , to a considerable extent, upon the losses at the
contact surface. In other words, it is dependent upon both the
278 ELECTRICAL ENGINEERING PAPERS
current and the contact drop. With reduction in contact drop,
this burning action apparently is decreased, but in commutating
machinery, this reduction cannot be carried very far, in most
cases, on account of increase in short circuit current, which
nullifies the gain in contact drop. In fact, in each individual
machine, there is some critical resistance which gives least loss
and least burning at the contact surfaces.
Practise has shown that this burning action is very slow at
moderate current densities in carbon and graphite brushes —
so slow as usually' to Be' unnoted. However, if the actual
current density in the brush face is carried too high, the burn-
ing of the brushes may become very pronounced. With the
actual work current per brush usual in present practise, the
burning of the brush face may usually be credited to local cur-
rents in the brushes This is one pretty good indication of
the presence of excessive local currents. It also indicates the
location and direction of such currents, but is not a very exact
quantitative measure of them. It is not unconr.iron, in exam-
ining the brushes of a generator or motor, to find a dull black
area under one edge of the brush, which obviously has been
burned, while the remainder of the brush face is brightly polished.
In severe cases, practically as good results t\ill be obtained
if the burned area is entirely cut away by beveling the edge
of the brush.
This eating away of either the brush face or the commutator,
and the deposit upon the opposing face, leads to certain very
harmful conditions in direct-current machinery. As stated
before, if the true current density is kept sufficiently low in
the contact face, the burning is negligibly small m most cases.
However, where the current passes from the commutator to
the brush, it is the commutator copper which eats away, while
the mica between commutator bars doe? not eat away, but must
be worn away at the same rate that the copper is burnt, if good
contact is to be maintained. Let the burning of the copper
gain ever so little on the wear of the mica, then trouble begins.
The brush begins to " ride " on the mica edges and docs not
make true contact with the copper. This increases the burn-
ing action very rapidly, so that eventually the mica stands
well above the copper face. This is the trouble usually known
as " high mica/' It is frequently credited to unequal rates
of wear of copper and mica. This idea of unequal wear has
been partly fostered by the fact that with relatively thick
PHYSICAL LIMITATIONS IN D.C. MACHINES 279
mica, the action is greatly increased, or, with very thin com-
mutator bars, with the usual thickness of the mica, the high mica
trouble becomes more serious. In both these latter cases, it
is the higher percentage of mica, — that is, the relatively poorer
wearing characteristics of the mica itself, which is at fault.
But the commutator copper does not wear away. In fact, it
is not physically possible for it to wear below the mica. It is
" eaten away " or burned, as described above. In some special
cases, where this burning is unusually severe, the mica apparently
wears down about as fast as the copper, so that the commutator
remains fairly clean and has no particularly burnt appearance,
but grooves or ridges, showing undue wear. But this rapid
apparent wear is a pretty good indication that excessive burn-
ing action is present at times, usually due to excessive local
currents. In some cases, this burning action may be present
only during heavy or peak loads which may be so interspersed
with periods of light running that the true wear of the mica
catches up with the burning of the copper. In such cases, the
commutator may have a beautiful glossy appearance normally,
but may wear in grooves and ridges On account of this burn-
ing action, practise has changed somewhat in regard to stagger-
ing of brushes on commutators to prevent ridging between the
brushes. Formerly, it was common practise to displace all
the positive brushes one direction axially, and the negatives
in the other direction, in order to have the brushes overlap.
This, however, did not entirely prevent ridging, for the burning
of the copper occurred only under one polarity. It is now con-
sidered better practise to stagger the arms in pairs.
With commutating pole machines, the true current densities
in the brushes are carried up to. as high a point as the non-
burning requirements wall permit. Reduction in local currents
has been accompanied by increase in the work current density.
Therefore, conditions for burning and high mica are still exist-
ent, as in non-commutating pole machines. In recent years,
a new practise, or rather an extension of an old practise, has
been very generally adopted, namely, undercutting the mica
between bars. In early times, such undercutting was practised
to a certain extent, usually however, to overcome mica troubles
principally. In the newer practise, such undercutting is pri-
marily for other reasons, although the mica problem is partly
concerned in it. During the last few years, extended experi
ence ha$ shown that graphite brushes, or carbon brushes with
280 ELECTRICAL ENGINEERING PAPERS
considerable graphite m them, are extremely good for collect-
ing current, but on the other hand, are very poor when it comes
to wearing down the mica» due to their softness or lack of ab-
rasive qualities Due to the graphite constituent, such brushes
are largely self -lubricating, and therefore, "ride" more smoothly
on the commutator than the ordinary carbon brush. They are
therefore much quieter, and this is a very important point \vith
the present high speeds which are becoming very much the
practise. However, by undercutting the mica, all difficulty
from lack of abrasive qualities in the brush is overcome, and
thus the good qualities of such brushes could be utilized. The
advantage of self-lubricating brushes should be apparent to
anyone who has had difficulties from chattering and vibration
of brushes, due to lack of lubrication. Such chattering may
put a commutator " to the bad " in a short time, and the con-
ditions become cumulatively worse* Chattering means bad
contact between the brush and commutator, which in turn,
means sparking and burning, which means increased chatter-
ing or vibration.
The above refers to burning of the commutator face. But
such burning also may have a bad effect on the brushes. When
the commutator copper burns away to any extent, it may de-
posit on the brush face following the direction of the current.
This coating on the brush face sometimes leads to serious
trouble, by lowenng the resistance of the contact surf ace. This
not only allows larger short circuit current and greater heating
of the brush, but it makes the resistance of that particular
path lower than that of other parallel brush paths. In con-
sequence, the coated brush takes an undue share of the total
current, as well as an unduly large local current. The result-
ant heating may be such that the brush actually becomes red
hot or glows. This heating further reduces the resistance,
and tends to maintain the high temperatures. This glowing
or overheating very frequently causes disintegration of the bind-
ing or other material in the brush, so that it gradually honey-
combs at or near its tip. This action may keep up until the
brush makes bad contact. It may be that a similar action may
occur coincidently on other brushes, but, there is no uniformity
about it. This action of transferring copper to the brush is
sometimes known as " picking up copper/' It is not limited
to brushes of one polarity, except where the metallic coating
is caused primarily by the work current. Where it results from
PHYSICAL LIMITATIONS IN D.C. MACHINES 281
high local currents, it may be on the brushes of either polarity,
for the local currents go in and out at each brush. However,
according to the \\nterTs experience, this coating is more com-
mon on the one polarity
Glowing and honeycombing of brushes is not necessarily
dependent upon the metallic coating on the brushes, although
this latter increases the action Anything that will unduly in-
crease the amount of current m any brush contact for a period
long enough to result in heating and lower contact resistance,
with brushes in parallel, may start this gloxving and honey-
combing. It is not as common an action in modern machines
as in old time ones.
As an evidence that poor contact or high contact drop tends
to produce burning, may be cited the fact that, in many cases
of apparent rapid wear of the commutators, such wear has
been practically overcome by simply undercutting the mica
and thus allowing more intimate contact between brush and
copper. In some instances, this also lessened or eliminated
the tendency to pick up copper. Thus undercutting has been
very beneficial in quite a number of ways.
NUMBER OF SLOTS, CONDUCTORS PER SLOT, ETC.
There are certain limitations in direct-current machines, de-
pending upon the minimum number of slots per pole which can
be used. Provided satisfactory commutating conditions can
be obtained, it is in the direction of economy of design to use
a relatively low number of slots per pole, with a correspond-
ingly large number of coils per slot. This is effective in several
ways. In the first place, insulating space is saved, thus allow-
ing an increase in copper or iron sections, either of which al-
lows greater output. In the second place, \vider slots arc favor-
able to commutation. Thus the natural tendency of d-c. de-
sign is toward a minimum number of slots per pole. But if
this is carried too far, certain objections or disadvantages arise
or become more prominent, so that at some point they over-
balance the advantageous features. As the slots are widened
and the number of teeth diminished, variations in the reluct-
ance of the air gap under the main poles, with corresponding
pulsations in the main field flux become more and more pro-
nounced. These may effect commutation, as the short cir-
cuited armature coils form secondary circuits in the path of
these pulsations But before this condition becomes objec-
282 ELECTRICAL ENGINEERING PAPERS
tionable, other troubles are liable to become prominent, such
as " magnetic noises,1' etc. If the machine is of the commutat-
ing pole type, there are liable to be variations in the commutat-
ing pole air gap reluctance, so that it may be difficult to obtain
proper conditions for commutation. A relatively wide corn-
mutating zone is required if there are many coils per slot; also,
all the conductors per slot usually will not commutate under
equal conditions, which may result in blackening or spotting
| of individual commutator bars symmetrically spaced around
the commutator, corresponding to the number of slots. Innon-
commutating pole machines, it may be difficult to find a suit-
able field or magnetic fringe in which to commutate, and thus
the first and last coil in each slot will have quite different fluxes
in which to commutate.
Depending upon the relative weight of the various advant-
ages and disadvantages of a small number of slots per pole,
practise varies greatly in different apparatus. In small and
medium capacity railway motors, where maximum output in'
minimum space is of first importance, and where noise, vibra-
tions, etc. are not very objectionable, the number of slots per
pole used is probably lower than in any other line of d-c. ma-
chines, six to eight per pole being rather common. In the
smaller and medium size stationary motors, where noise must
be avoided, a somewhat larger number of slots is used in gen-
eral, depending somewhat upon the size of the machine. On
still larger apparatus, excepting possibly, small low-speed en-
gine type generators, 10 slots or more per pole are used in
most cases, and, in general, more than 12 are preferred. In
the large 600-volt machines, the number is fixed partly by the
minimum number of commutator bars per pole, and the num-
ber of coils per slot. Assuming three coils per slot, then with
a minimum number of commutator bars of about 40 per pole,
the minimum number of slots per pole will be 14, and with
two bars per slot, will be correspondingly larger. This there-
fore represents one of the limits in present practise.
Noise, Vibration, etc. Mention has been made of limita-
tions of noise and vibration being reached, in considering the
minimum number of slots. This is a very positive limitation
in design, especially so in recent years, when everything is being
carried as close as possible to all limits in economies in materials
and constructions. All the various conditions which cause
unkltte noises in electrical apparatus are not yet well known,
PHYSICAL LIMITATIONS IN D C MACHINES 283
and the application of remedies is more or less a question of
" cut-and-try."
A fundamental cause of noise in direct-current machines lies
in very rapid pulsations or fluctuations in magnetic conditions.
This has been well known for years, and many solutions of the
problem of preventing such variations in magnetic conditions
from setting up vibrations and consequent noise, have been
proposed, but many of them appear to hold only for the particu-
lar machine, or line of machines, for which they were devised.
A perfectly good remedy in one machine not infrequently
proves an utter failure on the next one. There are certain
remedies for noise in direct-current machines which apply pretty
generally to all machines, but, as a rule, such remedies mean more
expensive constructions In general, large air gaps and gradual
tapering of the flux at the pole edges tend toward quiet opera-
tion. A large number of slots per pole tends toward quietness.
However, the trend of design has been toward very small air
gaps, especially in recent designs of small and moderate size
d-c motors, also, the aim has been to use as few armature slots
as possible Moreover, newer designs with steel or wrought
iron frames, as a rule, have the magnetic material in the frames
reduced to the lowest limit that magnetic conditions will per-
mit. Also, with the general use of commutating poles, the
tendency has been toward " strong " armatures and corres-
pondingly weak fields, so that the total field fluxes and field
frames are relatively small compared with the practise of a
few years ago. With these small frames, resonant conditions
not infrequently are encountered, especially in those machines
which are designed to operate over a very wide range in speed.
There is liable to be some point in the speed range where the
poles or frame, or some other part, is properly tuned to some
pulsating torque or " magnetic pull " in the machine. In such
case, a very slight disturbance of a periodic nature may act
cumulatively to give a very considerable vibration and conse-
quent noise.
The pulsations in magnetic conditions which produce vibra-
tion may be due to various causes, but, as a rule, the slotted
armature construction is at the bottom of all of them. Open
type armature slots usually arc much worse than partially
closed slots. Such open slots produce ** tufting " or " bunch-
ing " of the magnetic flux l>etween the field and armature, and
it is this bunching of flttx which usually, in one form or another.
284 ELECTRICAL ENGINEERING PAPERS
produces a -magnetic pulsation or pull which sets up vibration.
This bunching of lines may be such as to set up pulsating mag-
netic pulls at no-load as well as full load In other cases, the
ampere turns in the armature slots tend to exaggerate or accen-
tuate the bunching so that the vibration varies with the load.
This bunching of the flux may act in various ways. The total
air gap reluctance betvi een the armature and tnain poles may
vary or pulsate, so that the radial magnetic pull between any
main pole and the armature will pulsate in value. If the re-
luctances under all the poles are varying alike, then these
pulsating radial pulls will tend to balance each other at all
instants. However, if the reluctances under the different poles
do not vary simultaneously, then there are liable to be un-
balanced * radial magnetic pulls of high frequency, depending
upon the number of armature teeth, speed of rotation, etc.
If this frequency is so nearly in tune with the natural period
of vibration of some part of the machine, such as the yoke,
poles or pole horns, armature core and shaft, that a resonant
condition is approximated, then vibration and noise are almost
sure to occur.
Radial unbalanced pulls, as described, are liable to occur when
the number of armature teeth is other than a multiple of the num-
ber of poles; and the smaller the number of teeth per pole, the
larger will be the unbalancing in general As a remedy, it
might be suggested that the number of armature slots always
be made a multiple of the number of poles However, there are
several objections to this One serious objection is that, on
small and moderate size d-c machines, the two-circuit type of
armature winding is very generally used, and, with this type of
v( hiding, the number of armature coils and commutator bars must
always be one more or less in number than some multiple of the
number of pairs of poles. Mathematically therefore, with a two-
circuit winding, the number of slots can never be a multiple of the
number of poles unless an unsymmetrioal winding is used,
that is, one vuth a " dummy " coil A second objection to using
a number of slots which is a multiple of the number of poles,
is that there are pulsating magnetic pulls "which may be exag-
gerated by this very construction There are two kinds of mag-
netic pulls, a radial, which has already been considered, and a
circumferential, due to the tendency of the armature core to
set itself where it will enclose the maximum amount of field
flux. Obviously, if the arrangement of slots is such that when
PHYSICAL LIMITATIONS IN D C MACHINES 285
one pole has a maximum flux into the teeth, another pole has
a minimum, then the circumferential puslations in torque
will be less than if all poles enclosed the maximum or the mini-
mum flux simultaneously. This latter condition will be produced
when the number of armature slots is a multiple of the number
of poles. Therefore, in dodging unbalanced radial magnetic
pulls by using a number of armature slots which is a multiple
of the number of poles, the designer is liable to exaggerate the
circumferential variations in torque or pull, so that he is no better
off than before. This circumferential pulsating magnetic pull
may act in various ways to set up vibration, and if there is any
resonant condition in the machine, vibration and noise will
result.
Several years ago, the writer made some very interesting tests
on a number of d-c. machines to discover the nature of the vi-
brations which were producing noise.
These machines had very light frames
and were noisy, although not exces-
sively so. The following results were
noted : In certain four-pole machines,
it was noted that the frames vibrated
in a radial direction, as could be
easily determined by feeling. How-
ever, upon tracing around the frame
circumferentially, nodal points were
pIG 4 noted. In some cases, there were
points of practically no vibration
midway between the poles, as at A in Fig. 4. In other cases
the point of least vibration was at Bt directly over the main
poles. Apparently, minimum vibration at A and maximum at
B occurred when the pulsating magnetic pulls were in a radial
direction, while, with circumferential pulls, the maximum vibra-
tion was at A . It was also noted in some instances that a varia-
tion in the width of the contact face of the pole against the yoke
produced vibrations and noise, and nodal points in the yoke,
the vibrations being a iBaximum at A .
In still other cases in commutating pole machines, vibrations
and noise were apparently set up by either radial or circumferen-
tial magnetic pulsations under the cominutating poles themselves,
as indicated by 'tfoe-f^cfc tbat mnoval of the comirrutating poles,
or a cdnsideraMe mcr-ease m their air gaps, tended to overcome
the noise. la s&cfo «ases, tlie noise usually increased with the
load, m ooiastant speed imchines.
286 ELECTRICAL ENGINEERING PAPERS
Skewing of the armature slots, or of the pole faces, has proven
quite effective in some cases of vibration and noise. Tapered
air gaps at the pole edges have also proven effective in many
individual cases However, the causes of the trouble and the
remedies to be applied in specific cases are so numerous and so
varied that at present it is useless to attempt to give any limita-
tions in design as fixed by noise and vibration due to magnetic
conditions.
" FLICKERING" OF VOLTAGE, AND " WINKING " OF LIGHTS
From time to time, cases have come up where noticeable
11 winking " of incandescent lights occur, this being either of a
periodic or non-periodic character, the two actions being due to
quite different causes In either case, the primary cause of the
difficulty may be in the generator itself, or it may be 'in the
prime mover. The characteristics of the incandescent lamp
itself tends, in some cases, to exaggerate this winking To be
observable when periodic, the period must be rather long, cor-
responding to a very low frequency Periodic flickering of
voltage may be considered as equivalent to a constant d-c
voltage with a low-frequency small-amplitude alternating e m f .
superimposed upon it In view of the fact that incandescent
lamps of practically all kinds give satisfactory service without
flicker at 40 cycles uith the impressed e m f varying from zero
to 40 per cent above the effective value, one would think that a
relatively small variation of voltage, of 3 per cent or 4 per cent
for instance, would not be noticeable at frequencies of 5 to
10 cycles per second. However, careful tests have shown
that commercial incandescent lamps do show pronounced
flicker at much lower percentage variations in voltage, de-
pending upon the thermal capacity of the lamp filament. Based
on such thermal capacity, low candle power 110-volt lamps, for
example, should show more flicker than high candle power lamps.
Also, tungsten lamps for same candle power should be more sen-
sitive than carbon lamps, due to their less massive films. In
fact, trouble from winking of lights has become much more pro-
nounced since the general introduction of the lower-candle power,
higher-efficiency incandescent lamps.
In view of the fact that winking has been encountered with
machines in which no pronounced pulsations in voltage appear
to be possible, a series of tests was made some years ago to
determine what periodic variation was noticeable on ordinary
PHYSICAL LIMITATIONS IN D.C. MACHINES 287
low-candle power Tungsten and carbon lamps A lamp circuit
\vas connected across a source of constant direct e m f , and in
series with this circuit was placed a small resistance which could
be varied at different rates and over varying range The
results were rather surprising in the very low pulsations in volt-
age which showeda flickering of the light when reflected from a
white surface With the ordinary frequencies corresponding to
small engine type generators — that is, from 5 to 10 cycles — peri-
odic variations in voltage of \ per cent above or below the mean
value were sufficient to produce a visible wink, with 16-candle
power carbon lamps; while 1 per cent variation above and below
was quite pronounced With corresponding tungsten lamps,
only about half this variation is sufficient to produce a similar
wink. These tests were continued sufficiently to show that such
periodic fluctuations in voltage must be limited to extremely
small and unsuspected limits This condition therefore imposes
upon the designer of such apparatus a degree of refinement in
his designs which is almost a limitation in some cases.
It is probable that non-periodic fluctuations in voltage do
not have as pronounced an effect in regard to winking of lights
as is the case with periodic fluctuations, if they do not follow
each other at too frequent intervals, unless each individual
pulsation is of greater amplitude, or is of longer duration
Possibly a momentary variation in voltage of several per cent
will not be noted, except by the trained observer, unless such
variation .has an appreciable duration
A brief discussion of the two classes of voltage variations
may be of interest, and is given below.
Periodic Fluctuations. As stated before, these may be due
to conditions inside the machine itself, or may be caused by
speed conditions in the prime mover. Not infrequently, the
two act together. Variations in prime mover speed can act in
two ways; first, by varying the voltage directly in proportion
to the speed, and secpnd, by varying the voltage indirectly
through the excitation, the action being more or less cumulative
in some cases. Such sp^ed variations usually set up pulsations
corresponding directly to tthe revolutions per jraiimte and in-
dependent of tbe number of pok§ #a th&?machine$,
In the machine itself, p^o^y^^i^ pf frequency lower
than normal Creque^v^fSte !&*£%* Hw*fj may be caused
by magnetic <fes5p^^fe^|*^^^ s^j, ®r> by unsymmetrical
windings, Ustt^$?3fl|^ fluctua^
288 ELECTRICAL ENGINEERING PAPERS
lions at a frequency corresponding to the normal frequency of
the machine, and therefore will have no visible effect unless
such normal frequency is comparatively low, which is usually
the case in engine type d-c. generators. In other cases, these
dissymmetries may give pulsations corresponding to the rev-
olutions, and not the poles For instance, if the armature
periphery and the field bore are both eccentric to the shaft,
then magnetic conditions are presented which vary directly
with the revolutions.
However, there have been cases where no dissymmetry could
be found, and yet which produced enough variations to wink
the lights Usually in such cases, the number of armature
slots per pole was comparatively small, and the trouble was
overcome by materially increasing the number of slots per pole.
A second source of winking has been encountered in some three-
wire machines in which the neutral tap is not a true central
point In such case, the neutral travels in a circle around the
central point and impresses upon the d-c voltage a pulsation
corresponding to the diameter of the circle Its frequency how-
ever, is that of the machine itself and is therefore more notice-
able on low frequency machines, such as engine type generators.
Non-Periodic Pulsations or Voltage " Dips." In all d-c.
generators, there is a momentary drop or " dip" in voltage with
sudden applications of load, the degree of drop depending upon
the character and amount of load, etc The effects of this
have been noted most frequently in connection with electric
elevator operation, in which the action is liable to be repeated
with sufficient frequency to cause complaint. Various claims
have been made that certain types of machines did not have
such voltage dips, and that others were subject to it In con-
sequence, the writer and his associates made various tests in
order to verify an analysis of this action which is given below,
The explanation of this dip in voltage is as follows. Assume,
ior instance, a 100-volt generator supplying a load of 100 am-
peres— that is, with one ohm resistance in circuit. The drop
across the resistance is, of course, 100 volts. Now, assume
that a resistance of one ohm is thrown in parallel across the
circuit. The resultant resistance in circuit is then one-half
ohm However, at the first instant of closing the circuit through
the second resistance, the total current in the circuit is only
100 amperes, and therefore the line voltage at the first instant
momentarily must drop to 50 volts. However, the em.f.
PHYSICAL LIMITATIONS IN D.C. MACHINES 289
generated in the machine is 100 volts, and the discrepancy of
50 volts between the generated and the line volts results in a
very rapid rise in the generator current to 200 amperes. If
the current rise could be instantaneous, the voltage dip would
be represented diagrammatically by a line only, that is, no
time element would be involved. However, the current can-
not rise instantaneously in any machine, due to its self-induction,
and therefore, the voltage dip is not of zero duration, but has
a more or less time interval. The current rises according to an
exponential law, which could be calculated for any given ma-
chine if all the necessary constants were known. However,
such a great number of conditions enter into this that is it usually
impracticable to predetermine the rate of current rise in de-
signing a machine, and it would not change the fundamental
conditions if the rate could be predetermined, as will be shown
later.
A rough check on the above theory could be obtained in the
following manner, by means of oscillograph tests. For example,
it was assumed in the above illustration that with one ohm
resistance in circuit, an equal resistance was thrown in parallel,
which dropped the voltage to one-half. In practise, the actual
drop which can be measured might not be as low as one-half
voltage, as the first increase in current might be so rapid as to
prevent the full theoretical dip from being obtained. However,
an oscillograph would show a certain amount of voltage drop.
If now, after the current has risen to 200 amperes and the con-
ditions become stable, the second resistance of one ohm is
thrown in parallel with the other two resistances of one ohm
each, then in this latter case, the resultant resistance is re-
duced to two-thirds the preceding value, instead of one-lialf,
as was the case in the former instance. Therefore, the dip
, would be less than in the former case. Again, if "one ohm re-
sistance is thrown in parallel ^ith three resistances of one ohm
each, the restdtant resistance becomes three-fourths of the
preceding value, — that is, the voltage dip is still less. There-
fore, according to the above analysis, if a given load is thrown
on a machine, the dips will be relatively less the higher the load
the machine is carrying. Also, if the same percentage of load
is thrown on each time, then the dips should be practically the
same, regardless of the load the xnadiine is already carrying.
For example, if the machine is carrying 100 amperes, and 100
amperes additional is tha^cmii o% ike dip shotild be the same as
290
ELECTRICAL ENGINEERING PAPERS
if the machine were carrying 300 amperes and 300 amperes
additional were thrown on.
Also, according to the above theory, a fully compensated
field machine, (that is, one with a distributed winding in the
pole faces proportioned to correctly neutralize the armature
magnetomotive force) should also show voltage dips with load
thrown on. To determine if this is so, several series of tests were
made on a carefully proportioned compensated field machine. Two
series of tests were made primarily. In the first, equal in-
crements of currents were thrown on, (1) at half load, (2) at full
load, and (3) at 1J load on the armature. In the second series
of tests, a constant percentage of load was thrown on; that is~7
at half load the same current was thrown on as in the first test,
while at full load, twice this current, and at If load, three
times this current was thrown on.
According to the above theory, all these should show voltage
dips, although the machine was very completely compensated.
Also, in the first series of tests, the dips should be smaller with
the heavier loads on the machine, while in the second series
they should be the same in all tests. This is what the tests
indicated. In the first series, the dips in voltage varied, while
in the second series, they were practically constant. The re-
sults of these tests are shown in the following table. (The
oscillograph prints were so faint that it was not considered
practicable to produce them in this paper.)
NORMAL E.M F— 1200 VOLTS.
Load on generator
Increase in load.
Dip in voltage
Test.
(Appro*).
A
0 Amps
417 Amps
700 Volts
B
208
80
300 «
C
417
80
200 *
D
625
80
150
B
417
160
300 *
F
625
240
300 •
Tests, B C and D in the table show the dips for the first
series of tests, while B, E and F show results for second series.
The time for recovery to practically normal voltage was very
short in all cases, varying from 0.002 to 0.004 seconds accord-
ing to the oscillograph curves, but even with this extremely
PHYSICAL LIMITATIONS IN D C. MACHINES 291
short time, there was very noticeable winking of tungsten
lamps, in practically all tests The oscillograph curves showed
practically no change in field current, except in test A.
The machine used in these tests was a special one in some
ways. It was a 500-kw., 1200- volt, railway generator with
compensating windings and commutating poles, In order to
keep the peripheral speed of the commutator within approved
practise, it was necessary in the design to reduce the number
of commutator bars per pole, and consequently the number
of armature ampere turns, to the lowest practical limit. This
resulted in an armature of very low self induction, which was
very quick in building up the armature current with increase
in load, This machine therefore did not show quite as severe
variations as would be expected from a normal low-voltage
machine of this same construction. However, these two series
of tests did show pronounced voltage dips which were sufficient
to produce noticeable winking of incandescent lamps. Presum-
ably, therefore, all normal types of generators will wink the
lights under similar conditions.
Data obtained on non-compensated machines of 125 and 250
volts indicate the same character of voltage dips as were found
in the above tests. This should be the case, for, by the fore-
going explanation, the compensating winding has no direct re-
lation to the cause of the dip.
It will be noted in these curves that the voltage recovers to
normal value very quickly. However, incandescent lamps
will wink, even with this quick recovery, if the dip is great
enough. There is some critical condition of voltage dip in
each machine which would produce visible winking of lights.
Any increments of load up to this critical point will apparently
allow satisfactory operation. If larger loads are to be thrown
on, then these should be made up of smaller increments, each
below the critical value, which may follow each other in fairly
rapid succession. In other words, the rate of application of
the load is of great importance, if winking of lights is to be
avoided Therefore, the type of control for motor loads, for
instance, should be given careful consideration in those cases
where steadiness of the light is of first importance, and where
motors and lights are on the same circuit.
An extended series of tests has shown that, in most cases,
10 per cent to 15 per cent of the rated capacity of the generator
can be thrown on in a single step without materially affecting
292 ELCETRICAL ENGINEERING PAPERS
the lighting on the same circuit, and provided the prime mover
holds sufficiently constant speed. However, judging from the
quickness of the voltage recovery, the prime mover, if equipped
with any reasonable flywheel capacity, cannot drop off materially
during the period of the voltage dip as shown in the curves.
The dip in voltage due to the flywheel is thus apparently some-
thing distinct frdm the voltage dip due to the load. However,
if the load is thrown on in successive increments at a very
rapid rate, the result will be a dip in voltage due to the prime
mover regulation, although the voltage dips due to the load
itself may not be noticeable.
Thejabove gives a rough outline of this interesting but little
understood subject of voltage variations. Going a step farther,
a similar, explanation could be given for voltage rises when the
load is suddenly interrupted, in whole or in part. This is
usually known as the inductive kick of the armature when the
circuit is opened This may give rise to momentarily increased
voltages which tend to produce flashing, as has already been
referred to under the subject of flashing when the circuit breaker
is opened.
PERIPHERAL SPEED OF COMMUTATOR
This presents two separate limitations in d-c. design, one
being largely mechanical and the other being related to voltage
conditions. As regards operation, the higher the commutator
speed, as a rule, the more difficult it is to maintain good contact
between brushes and commutator face. This is not merely a
function of speed, but rather of commutator diameter and speed
together. Apparently it is easier to maintain good brush con-
tact at 5000 ft per minute with a commutator 50 in. in di-
ameter than with one of 10 in. in diameter. Very slight un-
evenness of the commutator surface will make the brushes
" jump " at high peripheral speeds, and the larger the dia-
meter of the commutator with a given peripheral speed, the
less this is.
The peripheral speed of the commutators is also limited by
constructive conditions. With the usual V-supported com-
mutators, the longer the commutator, the more difficult it is
to keep true, especially at very high speeds and the higher
temperatures which are liable to accompany such speeds.
Therefore, the allowable peripheral speeds are, to some extent,
dependent upon the current capacity per brush arm, for the
ength of the commutator is dependent upon this. The per-
PHYSICAL LIMITATIONS IN D C MACHINES 293
missible speed limits, as fixed by mechanical constructions-
have been rising gradually as such constructions are improved,
At the present time, peripheral speeds of about 4500 ft. per
minute are not uncommon with commutators carrying 800 to
1000 amperes per brush arm. In the case of 60-cycle, 600-
volt synchronous converters, 5200- to 5500-ft. speeds are usual
with currents sometimes as high as 500 to 600 amperes per arm,
In the case of certain special 750-volt, 60-cycle converters, oper-
ated two in series, commutator speeds of about 6400 ft. have
proved satisfactory. These latter, however, had comparatively
short commutators.
For the small diameter commutators used in d-c. turbo-
generator work, peripheral speeds of 5500 to 6000 ft. have been
common. However, such machines usually have very long com-
mutators and of the so-called " shrink-ring " construction. The
brushes may not maintain good contact with the commutator
at all times, and in a number of machines in actual service, the
writer, in looking at the brush operation, could distinctly see
objects beyond the brush contacts; that is, one could see
" through " the contact, and curiously, in some of these cases,
the machines seemed to have operated fairly well. One ex-
planation of this is that the gaps between brushes and com-
mutator were intermittent,, and, with one or more brush arms in
parallel, one arm would be making good contact, while another
showed a gap between brushes and commutator. Appar-
ently, the commutators were not rough or irregular, but
were simply eccentric when running at full speed and the
brushes could not rise and fall rapidly enough to follow
the commutator face all the time. Incidentally, it may be men-
tioned at this point, that with the higher commutator speeds
now in use, there has come the practise of " truing " commutators
at full speed. This is one of the improvements which has al-
lowed higher commutator speeds.
The other limitation fixed by peripheral speed, namely, that
of the voltage, is a more or less indirect one. It is dependent
upon the number of commutator bars that are practicable be-
tween two adjacent neutral points; or, in other words, it is
dependent upon the distance between neutral paints. The
product of the distance between adjacent neutral points and the
frequency, in Alternations, gives the peripheral speed of the
commutator, (distance between neiitcal points in feet times
per &&&^]&$^ peripheral speed in feet per
294 ELECTRICAL ENGINEERING PAPERS
minute). With a given number of poles and revolutions per
minute, the alternations are fixed Then, with an assumed
limiting speed of commutator, the distance between neutral
points is thus fixed. This then limits the maximum number of
commutator bars, and therefore the maximum voltage which
is possible, assuming a safe limiting voltage per bar From
this it may be seen that the higher the penpheral speed, the
higher the permissible voltage with a given frequency In the
same way, if the frequency can be lowered (either the speed or
the number of poles be reduced) the permissible voltage can
be increased with a given peripheral speed. Where the speed
and the number of poles are definitely fixed and the diameter
of commutator is limited by peripheral speed and other con-
ditions, the maximum practicable d-c voltage is thus very defi-
nitely fixed. This ^s a point which apparently has been mis-
understood frequently It explains why, in railway motors, for
high voltages, it is usual practise to connect two armatures per-
manently m series, also, why two 60-cycle synchronous conver-
ters are connected in series for 1200- or 1500- volt service. In
synchronous converter work, the frequency being fixed once for
all, the maximum d-c. voltage is directly dependent upon the
peripheral speed of the commutator
CONCLUSION
The principal intent, in this paper has been to show that cer-
tain limitations encountered in d-c. practise are just what should
be expected from the known properties of materials and electric
circuits. The writer has endeavored to explain, in a simple,
non-mathematical manner, how some of the apparently com-
plicated actions which take place in commutating machinery
are really very similar to better understood actions found in
various other apparatus An endeavor has also been made to
show that a number of the present limitations in direct current
design and operation are not based merely upon lack of ex-
perience, but are really dependent upon pretty definite condi-
tions, such as the characteristics of carbon brushes and brush
contacts, etc Possibly a better understanding of the character-
istics and functions of carbon brushes will result from this paper.
The writer makes no claims to priority for many of the ideas
and suggestions brought out in this paper However, much of
the material is a direct result of his own investigations and those
of his associates during many years of experience with direct-
currcnt apparatus
PHYSICAL LIMITATIONS IN D.C. MACHINES 295
APPENDIX
The following method of determining the maximum capacity
which can be obtained with given dimensions and for assumed
limitations as fixed by commutation, flashing and other con-
ditions, is based upon certain formulas which the writer de-
veloped several years ago, and which appeared in a paper before
the Institute.*
On page 2389 of the 1911 TRANSACTIONS of the Institute,
the following general equation is given :
„ Ic WtRs TC-K r _ _ 2 Dp _
10* 1C] (L L}) (025^+05) (D+PP)
9 + °-035 N) + c*- (JL33 ds + °-52 + 2-16 s
"•
Where Ic = Current per armature conductor.
Wt = Total number of armature conductors
Tc = Turns per armature coil or commutator bar.
L & Li \= Width of armature core and commutating pole
faces respectively.
D = Diameter of armature.
p = No. of poles.
N = No. of slots per pole.
d9 = Depth of armature slot.
5 = Width of armature slot.
n = Ratio of width of armature tooth to slot 'at
surface of core.
Ci, Cz, £3, £4 are design constants.
In order to simplify the above equation, the following as-
sumptions are made;
(a) No bands are used on armature core, thus eliminating
the last term in the above equation. •
(b) Li = L, thus eliminating the first expression inside tha
bracket in the above equation,
B&th the above assumptions are in the direction of increased
capacity with a given short circuit voltage, Ec.
Equation (1) then becomes,
*Theory of Commutatang and Its Application to Commutating-Pole Machines, Page 201.
296 ELECTRICAL ENGINEERING PAPERS
[Sept. 16
+ c3 — (1 33rfs + 0.52 + 2 16 s Vn) 1 (2)
The various terms in equation (2) should be put in such form
that limiting values can be assigned to them as far as possible.
In order to do this the equation can be condensed and simplified
as follows, for large machines:
(a) Assuming parallel type windings, —
7" 2 to F
\yt — " r — ^ where F& = Average volts per commutator
l/&
bar or coil.
where It = Total current.
'
c
P
IE = Kilowatts X 10* = Kw 103
Also, Ra p = 2/, where/ = Frequency in cycles per second.
_, , Ic Wt Rs T, TT Kwp X 4/ rcV „ u . ,....-
Therefore, - j^ - = - V& X 10s - ' p g
watts per pole.
(6) Let P< = Armature tooth pitch,
Then D
and c2 - (09 + 0.035 N) = c2 -- (0.9 + .035 .Vj Pt
p 7T
In case of a chorded winding, the term 0.035 N should be
0.035 Nit where NI represents the number of teeth or tooth pitches
spanned by the coil.
(c) In the second tenn inside the bracket in equation (2),
the ratio •=- can be transformed into an expression containing
o
Pif as follows:
E =BtStCPR,Wa
10*
PHYSICAL LIMITATIONS IN D.C MACHINES 297
Bt = Flux density in armature teeth.
St — Section of iron in armature teeth.
Cp = Field form constant (percentage polar area).
Rs = Revolutions per second.
Ws = Wires in series.
St = N T p L c^ where T = Width of tooth, and c* = the
ratio of actual iron to the core width L.
P 2
As an approximation, TX9 = -£• (This is a fairly close ap-
proximation within practical limits in the usual armature con-
structions) .
Then, S,=
4X10*E
°r -S =1
This can further be condensed as follows.
W.= Tc-22-,*rLARtp-2f
™ t L 1QS v*>
Therefore, — = •=— ^
(d) The expression (1.33 d, + 0.52 + 2.16 $ Vn) can be
modified as follows,
Vw" = ^1 T = ^(^ = ^ on the basis that Txs = ^~
approx.
Then, 2.16 sVn « 1.08 Pt approx.
and, (1.33 d, + 0.52 + 2.16 sVnj = (1 33 ds + 0.52 + 1.08 Pt)
Substituting all the above transformations in equation (2)
we get,
4 (°-9 + ° °35 Nl} NPt
298 ELECTRICAL ENGINEERING PAPERS
„ Ec Vb 105
Kwp = — ^ ^.,
P£ (4)
4c2 (0.9 +0 035tfi)jyyP<a + ~^^r (1 33d. + 0.52+ 1 08 P t\
ntLpL\ C51 c [
Maximum Kilowatts per Pole. Differentiating (4) to obtain
Pt for maximum Kwpt
c» Nf (0.9 + 0.035 tf 0 * '6 (1 33 <fs + 0 52)
* c •#* Cp J\ C$
TT Ci Vb 10s
If Pi in equation (5) could be derived and then substituted
in equation (4), then for any assumed value of Ec and with the
other terms given limiting values, an expression for the maximum
kilowatts per pole could be obtained. The writer has not been
able to solve this directly in any sufficiently simple manner,
although a complicated approximate expression can be obtained.
However, for practical purposes, the solution for an3r given con-
ditions can be obtained by trial methods and the results plotted
in curves.
For instance, in equations (4) and (5), the following terms
may be given limiting values for a given class of machines and
for a specified voltage
Tr - Turns per coil
c<i = End flux constant.
Af = Number of slots per pole Ari = No. of teeth spanned
by coil.
GZ = Brush short circuit constant.
Vi = Average volts per bar.
Cp = Field form constant With max. volts per bar fixed,
then V max. X Cp = Vb.
Bt = Flux density in teeth.
£& = Ratio of actual iron width to core width L.
Also, type of armature winding can be fixed and departure
from full pitch winding, or amount of chording can be given.
PHYSICAL LIMITATIONS IN D C. MACHINES 299
There will then remain for any assumed value of Ec, the terms,
Kwp = Kilowatts per pole.
Pt = Tooth pitch.
/ = Cycles per second.
ds = Depth of armature slot.
All four of these latter terms are in equation (4), and the last
three in equation (5). Therefore, assuming the depth of slot,
equation (5), the values of Pt for different frequencies may be
determined by trial methods. The corresponding values of
Pt, f and d3 can then be substituted in equation (4), and the
kilowatts per pole thus determined. Tables or curves can then
be prepared giving the kilowatts per pole for different frequencies
and for different assumed slot depths.
A series of such tables have been worked out for a specified
set of Conditions as given below. The assumed limiting con-
ditions were as follows:
Ec = 4.5, — that is, one turn per coil parallel type winding
is assumed,
e m f =600 volts.
Cp = 0.68
Vb = 14.3. No of commutator bars per pole = 42. No
compensating winding is used. Therefore, Vb.
600
" 42
14.3 =
0.68
and max. volts per bar at no load =
21. Allowing 25 per cent increase for
flux distortion, and increased voltages at times,
gives 26 3 at full load.
r.> = 1,25 for average constructions.
<-, = Vanes with the number of coils per slot and the aver-
age number of bars covered by the brush, but as-
suming 2 bars covered, then Cz = 0.4 approx,
with 1 slot chording, and with either 2 or 3 coils
per slot.
Bt - 150,000 lines per sq. in. on the basis of actual iron
and all flux confined to the iron.
r& = 0.75. This allows for 90 per cent solid iron and j
of the total width taken up by air ducts (aboul
|" duct for each 2" of laminations).
300
ELECTRICAL ENGINEERING PAPERS
N
14 f
(Two cases have been assumed, one with 3 coils
per slot and 14 slots per pole, and the other with
2 coils per slot and 21 slots per pole.
14 Slots per Pole. — Substituting the above values in equations
(4) and (5), then for 14 slots per pole equation (4) becomes,
Kw, = 3767 Ec [
and equation (5) becomes
jP? = 18 36 (2.5 d, + 1) + 19 Pt
(6)
(7)
Incidentally, equation (6) can be simplified to a certain extent
by partially combining with equation (7), giving the following
equation :
p?
Kiuf = 99 EC
3.725 (2.5 d. + 1) -
Equation (8), of course, can only be used with the values of
Pt determined from equation (7).
Three values for ds were chosen, 1 in., 1.5 in., and 2 in., which
cover the practical range of design for large d.-c. generators.
Frequencies from 5 to 60 cycles were also chosen. The corres-
ponding values for Pt and Kwp are tabulated below,
TABLE I.
f—
Cycles
J, =1*
d = 15"
d -o*
per sec.
/>! K~>
Pt K»p
Pi *«,
5
2 85 in. 670
3 08 m 647
3 255 in 620
10
2 20 453
2 362 428
2 504 407
20
1 685 2Q9
1 828 282
1 945 266
30
1 455 235
1,575 219
1 680 208
40
1 302 197
1 417 183 5
1 515 173
50
1.20 173 5
1 305 160
1 398 151 5
60
1 I2o 153
1 226 143 5
1 310 135
21 Slots Per Pole. Substituting the proper values in equations
(4) and (6) for 21 slots per pole, and, one slot chording, and then
solving for Pt and Kwp for the same slot depths and frequencies,
the following table is obtained:
PHYSICAL LIMITATIONS IN D C. MACHINES 301
TABLE II.
/—
Cycles
ds = 1 in.
<f <r =* 1 5 in.
ds = 2 in
per sec.
Pt Kwp
Pt Kwp
Pt Kwp
5
1 985 in. 576
2 14 in 542
2 27 in 515
10
1 53 380
1 56 333
1 77 338
20
1 185 249
1 29 J,52
1 36 214
30
1 022 195
1 12 181
1 192 368
40
0 922 16,i
1 003 130
1 077 141
50
0 830 142
0 932 131
0 997 123
60
0 796 126
0 874 117
0 936 110
SYNCHRONOUS CONVERTERS
Two cases only need be considered, namely 25 and 60 cycles.
For these two cases, more definite limits can be given than for
the above rather general solution for d-c. machines.
25 Cycles. Let N ~ 21, and NI = 20; also, assume two
coils per slot for 600 volt machines.
ri = 1.0.
cz = 0.37
ft = 165,000
Cp = 0.7
Then for assumed values for depth of slot of 1 in., 1.5 in ,
and 2 in., and for Ec = 4.5, the following values of Pt and
Kwp are obtained:
«
TABLE III.
Depth of
Tooth
Kilowatts
slot.
pitch.
*
per pole.
1 in
1.09
278
1 5
1 19
257
2
1 275
243
60 Cycles. Let N = 15, and
per slot for 600 volts.
c3 = 0.4
Bt = 150.000
Cp = 0.66
14, Also, assume 3 coils
302
ELECTRICAL ENGINEERING PAPERS
Then assuming s bt depth of 1 in , 1.25 in., and 1 5 in., and
EC = 4.0, the following values of Pt and Kwp result:
TABLE IV.
Depth of
Tooth
Kilowatts
slot
pitch.
per pole.
1 in
1 14
143
1 25
1 195
137 5
1 5
1 24
132
The above tabulated results agree pretty well with practical
results obtained in large generators and converters. There are
so many possible variations in the limits assumed that only
general results can be shown For instance, in Table I, a
constant limiting induction in the armature teeth of 150,000
lines per sq. in. is assumed. With low frequencies this can be
increased, while with frequencies of 50 to 60 cycles, somewhat
lower inductions will be used. Also, the commutation con-
stant C\ which is dependent upon the number of bars covered
by the brush is naturally subject to considerable variation.
The results obtained are predicated upon parallel types of
windings and a minimum of one turn per armature coil. If
types of windings having the equivalent of a fractional number
of turns per coil less than one, prove to be thoroughly satis-
factory for large capacity machines, then the above maximum
capacities can be materially increased. However, accepting
the results as they stand, the limits of capacity as fixed by
commutation are in general about as high as other limitations
will allow
REGULATION CHARACTERISTICS OF COMMUTATING
POLE MACHINES AND PARALLEL OPERATION
WITH OTHER MACHINES
FOREWORD— About ten years ago, the author found that there was
considerable misunderstanding regarding the regulating charac-
teristics of commutating-pole machines, and the conditions
which were to be met in parallel operation. In consequence, he
prepared this brief article for the use of the engineers of the
Westinghouse Electric & Manufacturing Company. It has
proved so satisfactory that it has been kept in publication ever
since.
This paper was written before the term " comrnutating
pole" was adopted to replace the term "interpole" which is
found throughout the article. — (Eo.)
THE inherent regulation characteristics of the armature of a
direct-current machine has much to do with its parallel
operation with other machines. When two direct-current ar-
matures are coupled in parallel and delivering load to the same
external circuit, it is necessary, in order to obtain stable conditions,
for each armature to tend to "shirk" its load; that is, it must
naturally tend to transfer load to the other machine. This
tendency to shirk may be either in bad speed regulation due to the
prime mover which drives the armature, or in the drooping voltage
characteristics of the armature itself. A drooping speed character-
istic indirectly produces a drooping voltage characteristic in the
armature and therefore both causes lead to the one characteristic,
namely, drooping voltage, as the condition for stable parallel
operation. This drooping voltage characteristic must be the in-
herent condition. In practice, the voltage at the armature
terminals frequently rises with increase in load, but its rise is due
to some external condition, such as increased field strength.
Direct-current machines, as hitherto ordinarily constructed,
naturally give drooping voltage characteristics in the armature
windings. If two such armatures are paralleled they tend to
divide the load in a fairly satisfactory manner provided then-
prime movers regulate similarly in speed. If means are applied
for giving a rising voltage characteristic to the machines, such as
series coils in the field, then the armature terminals must be
paralleled directly in order to maintain stability. If, for instance,
the armatures are not paralleled directly, but the paralleling is
303
304 ELECTRICAL ENGINEERING PAPERS
done outside the series coils, then the operation will be unstable
unless the machines still have drooping voltage characteristics
If they have rising characteristics, then parallel operation is im-
practicable. If either machine should take an excess of load, its
voltage would rise, while that of the other machine would fall due
to decreased load. This condition would naturally force the first
machine to take still more load and the second one to take still less
This condition would continue until the first machine actually fed
current back through the other machine and it would be necessary
to cut them apart to avoid injury. However, by paralleling the
two armatures inside the series coils, that is, between the series
coils and the armature terminals, this unstable condition is avoided
due to two reasons, first, the inherent drooping voltage character-
istics of the armatures, and, second, the fact that the series coils
are paralleled at both terminals, thus forcing them to take pro-
portional currents at all times and thus compounding both ma-
chines equally.
If direct current machines are so designed or operated as to
give rising instead of drooping armature characteristics, then
parallel operation is liable to be unstable. This condition could
be obtained in ordinary machines by prime movers which tend to
speed up with increasing load, thus producing rising voltage on the
armature. Ordinarily, such speeding up of the prime mover would
have to be rather large, as the normal drooping characteristics of
the ordinary armature is fairly large. However, prime movers of
this character are comparatively rare.
A second condition which can give a rising voltage is found
not infrequently in the interpole type of direct-current machine. The
interpole generator is similar to the ordinary type of generator,
except that midway between the main poles small poles are
placed which carry windings or coils which are connected directly
in series with the armature. The winding on the interpoles is
connected directly in opposition to the winding in the armature.
The maxirnurn magnetizing effect of the armature winding is found
at the points on the armature corresponding to the coils which are
being commutated. The interpole is intended to be placed
directly over these points and the interpole winding normally has
such a value that it not only neutralizes the magnetizing effect to
the armature winding at these points, but it also sets up a small
magnetic field in the opposite direction whicl^ assists in the com-
mutation of the armature coil. Therefore the interpole winding
PARALLEL OPERATION OF D.C MACHINES 305
must have a number of ampere turns equal to the maximum ampere
turns in the armature winding, plus the excess ampere turns
necessary to produce the required commutating field strength.
When this interpole winding is placed directly over the com-
mutating position of the armature winding it should have prac-
tically no effect on the armature characteristics. If, however, the
interpole winding is not placed over these positions it will have an
effect on the voltage characteristics of the machine, tending to
either raise or lower the voltage, depending upon the position of
the interpole with respect to the commutating position. The
commutating points on the armature depend directly upon the
brush position If the brushes are rocked backward or forward
from the point corresponding to the mid position between the poles
then the position of the commutated armature coils moves back-
ward or forward with the brushes. As the commutating pole is
fixed in position it is evident that the relation of the commutating
pole to the coils undergoing commutation can be changed by the
different brush settings. Herein lies a possible trouble in parallel
running, for the commutating points can be so shifted, with
respect to the commutating pole, that the armature winding
voltage characteristics can be made to rise instead of droop. As
explained before, this is an unstable condition for parallel operation.
This condition can be illustrated in the following manner:
PIG.
Let Pig. 1 represent two main poles, and interpoles, with the
brushes set in a position corresponding to the middle point of the
interpole. The polarity of the interpoles and main poles is in-
dicated in this figure. The polarity of any interpole, when the
machine is running as a generator, is always the same as the
polarity of the main pole immediately in front of the interpole.
When the brush is placed in a position corresponding to an exact
intermediate point in the interpole it is evident that the aramture
306 ELECTRICAL ENGINEERING PAPERS
coils lying between two commutating points, that is, the winding
between a and b in Fig. 1, is acted upon by induction from the
main pole and by half the induction from the interpoles adjacent to
the main pole. However, as these two interpoles are of opposite
polarity, and the induction is the same from each, it is evident that
they have equal and opposite effects on the armature winding
between a and b, and therefore do not affect its voltage
In Fig. 2 the brushes are given a slight back lead so that the
commutation is under the trailing magnetic flux from the inter-
pole. It is now evident that between a and b the induction is
from the main pole and from one interpole principally. With the
back lead at the brushes, this interpole is the one immediately
behind the main pole and therefore of the same polarity. This
interpole therefore becomes a magnetizing pole and adds to the
e. m. f . generated between a and b As the strength of this inter-
pole is zero at no load and rises with load, it is evident that it tends
to give an increased voltage between a and b as the load increases
and thus tends to produce a rising voltage characteristic instead
of a drooping one. The ampere turns in the interpole, as stated
before is considerably greater than in the armature, but ordinarily
the effect of these ampere turns is almost neutralized by the
opposing effect of the armature winding However, with the
*"•
OG00OO©
%2
->
H \-
FIG. 2
back lead, as indicated in Fig. 2, the opposing effect of the armature
winding is shifted to one side of the interpole and thus the inter-
pole ampere turns become more effective in actually magnetizing
the armature, but become less effective in creating a commutating
field for the coils which are now being reversed by the brushes. On
account of this less effective field it may be necessary in practice
to still further increase the ampere turns on the commutating poles
in order to bring the trailing magnetic fringe up to a suitable
value for producing proper commutation. It is evident, that this
PARALLEL OPERATION OF D C MACHINES 307
increased ampere turns on the commutating pole increases the
induction under other parts of the commutating pole as well as
under the trailing tip, and this increase under the other parts of
the pole still further increases the voltage between a and b.
With a back lead therefore the interpole may have the same
effect as the series winding on the main field; that is, it may
compound the machine so that the voltage at the terminals is rising
instead of falling, even without any true series winding on the
main poles. The machine therefore becomes an equivalent of a
compound wound machine and if there is no equalizer between the
interpole winding and the armature terminal, the generator may
be unstable when paralleled with other machines.
Take the case, next, where the brushes are given a forward
lead, as shown in Fig. 3. Comparing this with Fig. 2, by the same
reasoning it is evident that the interpole is now opposing the
effect of the main pole, in the winding between a and b. The
interpole therefore tends to produce a drooping voltage charac-
teristic and has just the opposite effect of the series winding. In
this position of the brushes the interpole winding tends to give
good characteristics for parallel operation, but as the effect of the
interpole is in opposition to the main pole it is evident that more
series winding is required on the main field in order to over-
compound the machine as a whole. Also, with the brushes in this
position the interpole is not as effective in producing gpod com-
mutation and therefore more ampere turns are required on their
interpole winding. Therefore, both the interpole winding and the
main series winding must be increased when the brushes are given
this forward postion. However, parallel operation should be
stable.
It is evident, therefore, from the above considerations, that
for best results the brushes should be so set that the true point of
commutation comes midway under the interpole. If this position
'FIG. 3
308 ELECTRICAL ENGINEERING PAPERS
is found exactly, then the interpole should have practically no
effect on the voltage characteristics of the armature, and parallel
operation with other generators should be practicable A very
slight forward lead is favorable to paralleling, but lessens the
compounding.
As a back lead at the brushes, when the machine is acting as a
generator, tends to improve the compounding and lessens the
series winding required on the main field, it might be suggested
that this gives a cheaper and more efficient machine and that
therefore this arrangement should be used, with some means added
for overcoming the unstable conditions of paralleling. One
means proposed for this is an additional equalizer connected
between the interpoles and the armature terminals. This has
been used in one or two instances, but in principle the arrange-
ment is inherently wrong. When the interpole windings are
paralleled, then the currents in them must divide according to
their resistances. This condition would not be objectionable
provided the armature currents also always varied in the same
proportion. With slow changes in load this condition might be
obtained. However, there are conditions of operation where the
armature currents will not rise and fall in proportion and there-
fore the interpole windings, with this arrangement, would not
always have the right value to produce the desired commutating
fields. By rights, each armature should be connected directly
in series with its own interpoles and the currents in the two should
rise and fall together for best results. This condition will not be
obtained when an equalizer is connected between the armatures
and interpoles. This solution of the problem should therefore be
avoided in general.
All the above leads to the fact that very accurate brush set-
ting is required on interpole types of machines, and furthermore,
when such setting is once obtained it should not be capable of
ready adjustment or change. For this reason interpole machines
should not have any brush rocking gear. In machines where such
gear is present it would be better, in general, if the brush rocking
mechanism were removed after the proper setting of the brushes is
once obtained, and means should be employed for locking the
brushes in this correct position.
The correct setting of the brushes is rather difficult to obtain
in many cases. Where the armature conductors can be traced
from the commutator bars back under the poles, it is feasible in
PARALLEL OPERATION OF D.C MACHINES 309
general to locate the correct setting by the position of the com-
mutated coil with respect to the interpoles. In standard practice
the throw or span of the coil is made, as nearly as possible, equal to
the pole pitch. In a parallel type of winding where the number of
slots is an exact multiple of the number of poles, the space of the
coil can be made exactly equal to the pole pitch. In this case if
the winding can be traced through, the brushes can be so set that a
coil or turn exactly under the middle of the commutating poles
has its two ends connected to the two adjacent commutator bars
which are symmetrically short-circuited by the brush; that is, the
insulating strip between these two bars should be under the
middle of the brush. To carry this out properly it is necessary to
trace the conductor, with absolute exactness, through the slots
When there are several separate turns side by side in one slot, it is
advisable to select a middle, or approximately middle, turn for
determining the brush setting.
In the case of a 2-circuit or series winding, it is more difficult
to determine the brush setting by tracing out the coils, for the
number of slots in such windings is usually not an exact multiple
of the number of poles and therefore the span of the coil is not
exactly equal to the pole pitch. In this case the position of the
coil must be averaged; that is, one edge or half of the coil may be
slightly ahead of the middle point of its interpole, while the other
half is slightly behind the middle of the interpole. Even if the
position of the coil is properly fixed it is not easy to fix exactly
the corresponding brush setting, as the two commutator bars to
which the coil is connected do not lie adjacent to each other, as in
a parallel type of winding, but are two neutral" points apart. Also,
the number of commutator bars is not an exact multiple of the
number of poles (except in some rare cases where there is an idle
bar) and therefore they do not have a symmetrical relation to the
brushes. The best that can be done therefore is to average the
brush position as well as possible.
If the winding is chorded; that is, if it has a span considerably
shorter than the pole tip, then its position will have to be averaged
in the manner described above.
In some cases it is not practicable to trace out the coils in the
above manner, as the end windings may be so covered that it is
not possible to trace an individual coil from the commutator to the
dot.
310 ELECTRICAL ENGINEERING PAPERS
On later machines it is the practice to put a mark or "cross"
on the tops of two adjacent armature teeth The top conductors
which lie in the slot between these two teeth are connected to
commutator bars which are also marked with a cross at their
outer ends. In this way it is possible to trace from the commut-
ator to the slots.
When an interpole generator is running alone, or where it is
operating properly with other machines, and the commutation is
satisfactory, it is unnecessary, of course, to look into this question
of locating the best brush setting. In those cases, however, where
the machine does not parallel properly with others, and it is
evident that the brush setting is wrong, then if the above procedure
cannot be followed, a better brush setting can be found by deter-
mining the voltage characteristics of the armature This can be
done by operating the machine with various loads with the series
winding cut out of circuit. If, under this condition, the voltage
either rises with increase in load, or droops but very little, then it
is evident that a greater forward lead would improve the opera-
tion. The brushes could then be shifted slightly forward and the
regulation noted. After a brush setting has been obtained which
gives a considerably larger drop in the voltage, then parallel oper-
ation should again be tried with this brush setting, the series coils,
of course, being connected in circuit. After proper paralleling is
obtained, then it may be necessary to re-adjust the strength of the
commutating field. If the machine has had a considerable back-
lead before and is shifted to the no-lead condition, then it may be
necessary to weaken the interpole winding somewhat. If the new
brush setting however, should correspond to as much forward
lead as it had back lead before, then the interpole strength may not
require readjustment and the commutation may be just as good
as before. After the proper conditions have been obtained, the
brush holder position should be marked so that it can be readily
found again if necessary.
There is another feature wherein an interpole machine is
different from the non-interpole type, namely, in the amount of
series winding. In the non-interpole type the brushes are usually
given a very considerable forward lead. In consequence of this
forward lead a part of the armature ampere turns are actually
effective in demagnetizing the field, and extra series turns are
necessary simply to overcome this demagnetizing effect, without
accomplishing any useful result.
PARALLEL OPERATION OF D C, MACHINES 311
On the interpole type, however, with the brushes set property
there is no lead at the brushes and therefore none of the armature
turns are tending to directly oppose the main field. In conse-
quence of this the number of series turns may be reduced and the
resistance of the series coils is correspondingly reduced. When
operating interpole machines in parallel with other types it may
be necessary to increase the resistance of the series circuit in order
that the interpole machine may take its proper share of the current
through the series coils. This result is obtained best, in general,
by a resistance connected in series with the series coil and not by a
shunt connected across the series coils of the other machines. A
shunt across a series coil of one machine is, in reality, a shunt
across all the machines which are operating in parallel, and it may
be more effective, in one machine simply because of the resistancr
of the leads connecting the various machines. These statements
apply to other types of machines as well as the interpole.
HIGH SPEED TURBO-ALTERNATORS—DESIGNS AND
LIMITATIONS
FOREWORD — This paper was prepared for the American Institute
of Electrical Engineers at the request of the Power Station
Committee of the Institute. It was presented in January, 1913
It contains a quite complete description of the two principal
types of turbo alternator rotors up to that time. In the latter
part of the paper, it takes up the problems of ventilation, tem-
perature and insulation from the turbo-generator standpoint.
Attention was called to the high temperature liable to be en-
countered in very wide core machines, such as turbo-generators,
due, to a certain extent, to mechanical limitations. The neces-
sity for the use of mica in such windings was also brought out. —
(ED.)
THE real problems in the design of turbo-alternators did not
really develop until the high-speed, large capacity units came
into demand. In the earlier work, the difficulties in design were
mostly those due to lack of experience and to insufficient knowl-
edge of the possibilities of materials, etc. As more data were
obtained, the speeds and capacities were gradually increased
until with the present large capacities and high speeds, a number
of conditions are encountered which may be considered as true
physical limitations.
The principal difficulties in the design of the earlier machines
were found in the permissible weight on bearings, undue noise
due to the open construction of the machines, and the troubles
incident to the through-shaft construction of the rotor.
The bearing problem was eliminated by securing more complete
data, which showed that the possibilities in this feature had
hardly been touched upon.
The solution of the noise problem was largely one of enclosing
the machine. The noise was practically eliminated, but the
greater problem of ventilation then developed.
In overcoming the difficulties of the through-shaft construc-
tion, the first great advance was made in the direction of larger
outputs at higher speeds. In very high-speed machinesr the
diameter of the shaft in the rotor core is necessarily small. As
the overall diameter of the core is comparatively small, it fol-
lows that, after allowing for the slot depth, and the metal in the
313
314
ELECTRICAL ENGINEERING PAPERS
core necessary to withstand the high rotative stresses, there is
left but little available space for the shaft. About 600 kv-a.
capacity at 3600 rev. per min. was the limit with this construction.
The first great advance in this problem was made by the intro-
duction of rotors without the through-shaft. By this means,
the parts of the shaft adjacent to the rotor core proper, could
be very much heavier1 than with the through-shaft type,
and this combined, with the solid rotor core, gave great stiffness
or rigidity compared with the former through-shaft type. This
allowed much larger cores, with correspondingly increased out-
puts. The two-pole parallel slot type of rotor with bolted-on
shaft construction, as described later, was apparently a leader
in this respect, due t6 mechanical, rather than electrical, char-
acteristics, WKen this type had proved to be a successful one,
the possible capacities of two-pole .3600-revolution, 60-cycle
machines at once jumped from 600 to 1000 kv-a., and this was
FIG. 1
quickly followed by 1500, 2000 and 3000 kv-a. units at 3600
revolutions. Since then, the increase in capacity at this speed
has been more gradual, but has been carried up to 5000 kv-a.
at present, with possibilities of a 6250 kv-a. unit:
The radial slot type of rotor, also described later, when con-
structed with its core and shaft in one piece, quickly, followed the
parallel-slot type in the above growth, and may eventually catch
up with its only rival in the two-pole, 60-cycle field of construc-
tion.
About the same timfe that the through-shaft type was super-
seded in the two-pole, 60-cycle machine, a corresponding change
was made in the two-pole, 25-cyde, and in four-pole .rotors for
both frequencies, so that, at the present time, practically no-
designs for the highest speed machines use the through-shaft
type of construction. This latter, however, has been retained
in some of the more moderate speed large capacity units.
TURBO-GENERA TORS
315
On account of the high, rotative and peripheral speeds, the
general design of large capacity turbo-generators turns upon the
type and construction of the rotor, rather than the stator.
Various designs and types of rotors have been developed but,
with rare exceptions, only two general types are now built in
this country. These may be designated as the radial-slot and
the parallel-slot types. Each has a number of advantages over
its rival and each has given good results in practice.
RADIAL SLOT TYPE OF ROTOR
In the radial slot type, as usually constructed for high-speed
machines, the core and shaft are forged in one piece in the Smaller
and more moderate sizes, but may be built up of a number of
separate plates or disks bolted rigidly together in the larger sizes.
In this type, the core is cylindrical in all cases, and in the outside
surfaces are radial slots, usually arranged in groups, in which the
FIG. 2
exciting windings are placed. While all radial slot types of
rotors bear a general resemblance to each other, yet there are
marked differences in the method of forming the slots and teeth
which constitute the outer surface. In some types the solid
rotor core has radial slots milled or slotted in the main body of
the core. In other cases the slots are formed outside the main
core by inserted teeth, usually with overhanging tips, between
which the exciting coils lie. These two general constructions
are illustrated in Fig. 3. Examples of the inserted-tooth con-
struction are found in the large moderate speed rotors of one
American company, and in somewhat higher speed machines of
a German company. However, with the advent of the high-
speed, high-capacity machines, the milled-in construction of
the radial slots appears to be taking the lead, due to certain
mechanical limitations in the inserted-tooth types.
On account' of the radial slots and the usual concentric arrange-
316
ELECTRICAL ENGINEERING PAPERS
men! of the exciting coils, the field or exciting turns cannot be
assembled and insulated before placing on the core, except in
the inserted-tooth type of construction. With the milled-in-slot
type, the field conductors, usually of flat strap, are dropped into
the slot one at a time, with insulation between individual turns.
For ease of winding, the ends are usually allowed to overhang
the core, and require a very ample outside support in the very
high speed machines This is illustrated in Fig. 4. The com-
pleted coils are usually held in place by strong non-magnetic
wedges in the tops of the slots. These wedges are usually carried
by overhanging pole tips, in the inserted-tooth type, or by grooves
in the sides of the slots in the milled-slot type The design of
the supports for the overhanging end windings has furnished one
of the difficult problems in this type of construction Examples
FIG. 3
FIG. 4
of radial slot end windings, and of the rotor complete, are shown
in Figs. 5 and 6.
This general construction of the radial slot type of rotor is
obviously applicable to machines of any number of poles. With
a two-pole machine there will be only two groups of coil slots and
two groups of concentric coils, while with four poles or six poles
there will be four or six groups respectively. It is evident that,
with this construction, a cylindrical rotor is obtained, regardless
of the number of poles. It is also evident that the problem of
supporting the end windings becomes an increasingly difficult
one, as the number of poles is decreased and the span of the
end windings is correspondingly increased.
The support over the end ^findings usually consists of a heavy
ring which, in very high-spefed machines, must consist of material
TURBO-GENERA TORS
317
FIG. 5
318 ELECTRICAL ENGINEERING PAPERS
having extra good physical characteristics, for this ring must
not only be able to carry itself, but must also carry the weight
of the underlying end windings which it supports. In the German
inserted-tooth rotor, the end windings are supported by steel
bands of many layers, instead of the solid steel ring. In some of
the lower speed radial slot machines, such as one American type
with inserted teeth, the end supports are of ring form usually
made in a number of sections, which are bolted to an inner shelf
by numerous bolts extending from the outer ring between the
coils of the end windings to the inner shelf. While this construc-
tion is satisfactory for the more moderate peripheral speeds, yet
with the much higher speeds in some of the later practise, this
construction has been superseded by a solid ring type of support.
PARALLEL-SLOT TYPE OP ROTOR
In the parallel-slot type of rotor, the slots for the exciting coils,
for any number of field poles, lie in planes parallel to one another
and to the rotor axis. The arrangement is illustrated by Fig 7.
As usually constructed, the slots are cut across the ends of the
poles, as well as in the sides, so that the exciting coils are em-
bedded in metal throughout their length. The object of this
general arrangement of parallel slots is to facilitate the winding
of the exciting coils. The rotor can be placed upon a turn-table,
or similar device, and rotated, to wind the coils in place under
tension. Two or more coils can be wound at the same time, as
is actually done in practice. As the coils can be wound under
tension, and as the conductors usually consist of thin flat strap,
which can be wound in very tightly, the resultant winding is a
very substantial piece of work. The finished winding is sup-
ported by metal wedges over the coils.
It is obvious that, with this construction, no external support
is required for the end windings, as the field core proper furnishes
the necessary support. It is largely on account of this feature
of well supported end windings that the parallel-slot type took
a leading position during the growth of .the larger two-pole,
60-cycle alternators. With the radial-slot type, the support
of the end windings presented a more difficult problem in the
large capacity, high-speed, two-pole machines, which, however,
is being gradually solved.
In the two-pole, parallel-slot construction, in order to utilize
the available winding space to advantage, it is necessary for the
windings to cover the central portion of the core end where the
TURBO-GENERA TORS
319
FIG. 7
FIG. 8
320 ELECTRICAL ENGINEERING PAPERS
shaft is usually attached, as shown before m Figs 7 and 8 There-
fore, with this construction, a separate " head " or driving flange
must be bolted to the core- at each end, this head carrying the
shaft, as shown in Fig 8. To avoid magnetic 'shunting of the
field flux, this driving head must be made of non-magnetic
material, usually of some high grade bronze, to which the shaft
is attached in such a way as to keep the magnetic leakage as
low as possible. This makes a good strong construction, but is
necessarily rather expensive, due tp the bronze driving heads.
As these cost but little more for a long rotor than for a short one,
the construction therefore tends toward relatively long, small
diameter cores in order to lessen the relative dimensions of the
bronze heads.
In two-pole, single phase machines of this construction, the
copper cage damper for suppressing the armature pulsating re-
action on the field, is comprised partly of these bronze heads,
which form the " end rings " for the copper bar& embedded in
the slots in the rotor face.
In the four-pole, parallel-slot machine, no bolted-on driving
leads are necessary, for the core proper and the shaft may be
:ast, or forged, in one piece, or in two or more pieces, which are
Doited or " linked " together to form a solid core. The principal
lifference between the, two-pole and the four-pole parallel slot
Constructions, is that the latter must have salient or projecting
Doles, in order to utilize the parallel construction for the slots,
vhile the two-pole machine is preferably made cylindrical. Fig.
illustrates this feature.
It is evident that there is considerable available space lost by
fie openings between the projecting poles, while the sections of
he poles themselves are cut down very materially by the slots
Dr the exciting winding. The limitations therefore in such a
otor are in the magnetic section of the field poles and in the
vailable copper space, and in these features the four-pole parallel
!ot rotor is inferior to the radial slot type. In the two-pole
lachine, however, the difference between the radial slot and the
arallel slot is not nearly so pronounced,' as is indicated in Fig. 10
here the two arrangements are shown on one core for compari-
)n. It may be seen from this that, in the iwo-pole form, the
*o constructions approach each other, to a certain extent,
>me of the slots in the parallel construction being radial, while
,hers depart but little from the radial. One disadvantage in the
ro-pole, parallel-slot type, however, lies in the smaller amount of
TURBO-GENERA TORS
321
copper space which is obtained, for the slot space must necessarily
cover a less proportion of the total circumference than is permis-
able with the radial slot type. This winding space is limited by
the physical requirements as regards bending and breaking
strains in the overhanging tip a
in Fig. 10. In the radial slot
type, the slot space has no such
limitation. Also, on account of
the grouping of the field copper
into a narrower zone in the
parallel-slot type, the heat con-
duction from the copper presents
a more difficult problem than in
the radial type.
At first glance, it would appear
that the effective length of the
field core in the parallel-slot type
is very considerably diminished by the slots across the ends
of the core. However, this is only an apparent effect, for the
true length of the core should be taken as that inside of the
winding slots, and it should be considered that the additional
FIG. 10
PIG. 11
length of the core at the pole face is in the nature of a coil
support which takes the place of the separate support in the
racial slot type. Therefore, if over-all lengths, including
rotor coil supports, are compared in the two types, there
is but little difference, as indicated by Kg. 11. However,
322 ELECTRICAL ENGINEERING PAPERS
if the armature core is made of the same width as the pole face
in both types of rotors, then in the parallel-slot type it will b
materially greater than in the radial, for the over-hanging pol
tips of the parallel-slot machine are also eifective magneticall
in furnishing flux to the armature. Therefore, as regards th
stator, this tends toward ?i wider core in the axial direction, an<
a shallower depth of iron back of the armature slots, as indicatfe*
in Fig. 12. Also, on account of the relatively larger polar sur
face, in the parallel slot type of rotor, the magnetic flux densit;
in the air gap is usually rela tively smaller than in the radial slo
type, which conduces towards a larger depth of air gap. Alsc
on account of the larger polar surface, the available space fo
armature slots and teeth is correspondingly increased. There
fore, this type of construction is better adapted for the straigh
air gap method of ventilation, as will -be described later. Th
greater section available for slots and teeth at the stator pol
face permits a large number of ventilating ducts. The relatively
large depth of gap allows a large amount of air to be fed througl
the air gap to the ducts. Therefore, the " radial " type of stato
core ventilation has been used very largely with this type o
rotor construction. In the parallel-slot type of rotor, it is obviou
that, due to the large polar surface compared with the minimun
section of the field core, a limit in design is found in the magneti<
saturation in the field core itself.
In the four-pole parallel-slot rotor, the field section is mor<
limited than in the two-pole machine, due to the fact that con
siderable magnetic space is lost by the notches between the pro
jecting poles. However, in this type of construction, the aii
gap method of ventilation is relatively easy, due to the fact thai
these interpolar spaces furnish easy access of the ventilating aii
to the stator ventilating ducts. In consequence, the problerr
of ventilation is usually not a serious one in this type of rotor
Due to the polar projections, however, the tendency to noise is
obviously greater than in either the radial-slot type or the two
pole parallel type, which are always cylindrical.
Nothing has yet been said as to the peripheral speeds obtained
in some of the actual designs of th;* higher speed generators.
These, in themselves, indicate some of the limitations which now
confront the designer.
In the 5000 kv-a., two-pole, 3600-rev. per rnin., 60-cycle
generator already referred to, which is of the parallel-slot rotor
construction, the rotor diameter is 26 in. (66 cm.) This gives a
TURBO-GENERA TORS
323
FIG. 12
FiO. 21
324 ELECTRICAL ENGINEERING PAPERS
peripheral speed of 408 ft. (124.3 m ) per second, or approximately
24,500 ft (7468m) per minute The core is designed for .a
very considerable margin of safety, and is actually tested at
overspecds which give practically 30,000 ft. (9144 m ) peripheral
speed at the surface pf the core
In certain 19,000 kv-a , 62J-cycle, four-pole, 1875-rev per min.
machines now being built, which are of the radial-slot rotor
construction, the rotor diameter is 49 in. (124 4 cm ) This gives
a peripheral speed of 24,000 ft. (7315 m.) per minute. This
compares with a speed of 21,600 ft. (6583 m.) in a 21,000 kv-a.
two-pole, 1500-rev per min., 25-cycle, radial-slot machine also
being built, the rotor core of which is shown in Fig. 12. Obviously
the mechanical limitations are being more closely approached in
the 60-cycle machines, up to the present capacities.
If, a comparison is made between the above 5000 and 19,-
QOO kv-a. rotors, with their parallel and radial type construc-
tions, it is found that their limitations lie in quite different
features. In the radial-slot type, the core stresses are much
lower than in the rother, but the supporting end ring is an im-
portant problem, requiring for its solution, a very high grade
steel for the material of the ring. In the parallel-slot rotor, the
maximum stresses are in the core itself, principally in the parts
which overhang the slots at the sides and ends of the core. In
the radial slot core, there are no such overhanging masses. In
both construction's, the core material is purposely made of re-
latively soft steel, having a high percentage elongation, the ob-
ject being to obtain a material which can yield sufficiently to
transfer the strains from local higher points, to adjacent lower
parts, and thus equalize them, to a great extent.
The smaller diameter rotor cores are made of steel forgings,
in one piece. The larger cores are made up of thick steel plates
assembled and bolted together to form a solid jnass comprising
the core and shaft extensions. By this disk construction, com-
mercial material is used which is of uniform quality clear to the
center of the disks. The fiber of the material is in a direction
best suited to the directions of stress. With corresponding sise
disks made in one piece, the outside, to a certain depth, can be
given fair physical characteristics, but the center is liable to be*
glass-hard, as found by experience. However, this may not
be a prohibitive condition in machines of more moderate per-
ipheral speeds. Herein lies one great difference between American
and European limitations. In American practice, 60-cycles,
T URBO-GENERA TORS 325
calling for 3600 and 1800-rev. per mm machines, is the standard
frequency, while in Europe, 50-cycles is standard, giving 3000
and 1500-rev. per min. machines. These lower speeds make
an enormous difference in the possibilities of design and construc-
tion
PRESENT LIMITATIONS IN DESIGN
On account of th§ very great capacities, at high speeds, now
being obtained in turbo-generator practice, a number of problems
are being encountered, the solutions of which are producing
more or less radical changes, both in design alid in practise.
Softie of the limitations now encountered are in the relatively
high temperatures in certain parts, high losses in a relatively
small space, the difficulty of ventilation, due to the requirement
of endrmous volumes of cooling air through limited openings
or- passages, the type of insulation, fire risks, regulation and
short circuit conditions, etc.
A number of these limiting conditions, such as the temperature,
ventilation, losses, and insulation, are so closely related to each
othfer, that ft is difficult to describe any one of them in detail,
without including the others to a considerable extent.
THE PROBLEM OF VENTILATION
Ip the general problem of ventilation, four conditions must
be considered, namely, the total loss, or heat, developed, the
surface exposed for dissipating this heat to the &ir, the quantity
of air required to carry away the heat, and the temperature
of the cooling air.
In the conduction of heat from the surface of a body into the
air, the quantity of heat per unit $rea which can be dissipated
depends upon the difference in temperature maintained between
the surface of the body and the body of air to which the heat is
conducted. The heat dissipated raises the temperature of
the adjacent air a certain amount, and thus tends to reduce
the temperature difference, utoless the air is renewed with suffi-
cient tapidity. On the other hand, if the quantity of air is so
great, in proportion to the heat dissipated, that there is but
little rise in the air temperature, then any increased amount
of air over the surface will represent practically no gain in
ventilation. In other words, when the amount of air passed
oyar a surface is sufficient to take up the heat dissipated from
the surface without an undue rise, then a. further quantity of
air is wasteful, and it may even be considered as indirectly
326 ELECTRICAL ENGINEERING PAPERS
harmful, in those cases where the total quantity of air is limited
This has a direct bearing on the size of ventilating ducts or
passages in a machine. If the air path through a duct is relatively
long, then a considerable width of duct may be required in order
to get the necessary quantity of air through it. On the other
hand, if the air path is very short, then a very narrow duct
may be most effective, for a wider duct may allow more air to
pass through than can be utilized in taking up the heat.
No matter how thoroughly the ventilating air is distributed
through the heat-generating body, or however effective the
heat-dissipating surfaces may be, the total air supplied must be
ample in quantity, or its temperature will be raised an undue
amount. As the surfaces to be cooled must always have a
higher temperature than the cooling air, any considerable rise
in the latter will have a direct influence on the ultimate tempera-
ture which may" be attained by the body to be cooled. Con-
versely, if an ample quantity of cooling air is supplied, but the
heat-dissipating surfaces are insufficient, the ultimate tempera-
ture of the body will also be affected.
In large capacity, high-speed turbo-generators, the problem
of ventilation is one of the most difficult ones encountered, The
trouble lies principally in the large total loss expended in a very
limited space. The difficulties of the problem may be illustrated
by the following example :
Assume, in a 1500-rcv. per min , 25-cycle, 15,000-kv-a
machine, a total efficiency of 96 5 per cent, including air friction
loss inside of the machine. This means a total loss in the machine
of 565 kw., which is not excessive for this capacity, but is very
large for the limited space in which it is developed A very
large volume of cooling air is required for carrying away the
heat due to this loss. A simple approximate rule for determining
the quantity of air required is that an expenditure of one kw,
in one minute will raise the temperature of 100 cu. ft (2.8 cu.
m.) of air 18 deg. cent. Therefore, 565 kw. loss would require a
supply of ventilating air of approximately 50,000 cu.'ft. (1416
cu. m.) per minute for a rise of the out-going air of 20 deg. above
that of the incoming air. Assuming a velocity of 3000 ft (914 m,)
per minute, this would mean, with a cylindrical ventilating
channel, a diameter of 56 in, (142.2 cm ), which is greater than
the rotor diameter itself. However, as the cooling air ordinarily
\vould be supplied to both sides of the machine, the ventilating
passage need only be half the above section for each side.
TURBO-GENERATORS 327
Obviously, such passages arc prohibitively large, and much
greater air velocities through the machine proper are necessary
Velocities as high as 5000 to 6000 ft. (1524 to 1828 m ) per
minute are common, while, in some cases, more than 10,000
ft. (3048 m.) per minute has been required m certain constricted
sections of the air path inside the machines Therefore, no
matter how the problem is considered, it may be seen that
the above condition of the enormous volume of air required,
makes the problem, of ventilation a difficult one
There are several methods of ventilating large turbo generators,
depending upon the system of applying the air. There is, first,
the radial system, in which practically all the cooling air passes
out radially through ventilating ducts in the stator core. This
radial system of ventilating can be subdivided into two alterna-
tive methods, depending upon whether the air is partly or
wholly supplied through passages in the rotor, or through the
air gap alone. These two methods are illustrated m Fig 13
The straight air gap arrangement may require a relatively large
air gap, combined with very high velocity of the air along the
gap, while the other method permits a considerably shorter gap.
The straight air gap method of ventilation is used, to a
considerable extent, in all 60-oycle machines of two-pole con-
struction, while it is practically the only one that has been used
with the parallel-slot type of machine with either two or four
poles In this parallel-slot type of rotor, however, the air gap can
be relatively larger than the radial-slot type of rotor, as explained
before, which compensates, to some extent, for the necessity of
depending upon this method entirely. In the four-pole parallel-
slot rotors, the interpolar spaces are also effective. Moreover,
with parallel-slot rotors in general, the openings from the air
gap into the stator ventilating ducts can usually be somewhat
larger in total section than with the radial type of rotor, as also
described before. However, the relatively greater axial length
of the core of the parallel slot type of rotor increases the length
of the constricted air passages along the air gap in the two-pole
machines, which is a material disadvantage
The straight air gap type of ventilation has proven astonish-
ingly effective in cooling the rotor in both the radial and parallel-
slot types of rotors, and with either type there is usually no
great difficulty in forcing through enough air to cool the rotor
core in a fairly effective manner. It must be considered, however,,
that the total rotor loss in large turbo-generators is possibly
328
ELECTRICAL ENGINEERING PAPERS
only 10 per cent of the total loss which must be taken care of, and
a relatively small proportion of the total ventilating air may
suffice to cool it. According to actual measurements, corrobor-
ated by general experience, the cylindrical surface of the rotor
core can give off four or five watts per square inch (6 45 sq.
cm.) to the cooling air, with a temperature rise of the rotor
surface of about 35 to 40 deg. cent, above the cooling air. To
those who have had experience with dissipating heat from electric
apparatus, this result will appear to be extremely good.
The real difficulty with the air gap method of ventilation,
is not so much in getting enough air through for cooling the
FIG. 13
FIG. 14
rotor itself, but it is in the much larger quantity required for
the stator. For instance, a one-inch (2.54 cm.) depth of gap
from iron to iron) with a 50-in. (127-cm.) diameter of rotor,
means a total section of air path into the gap (counting both
ends of rotor) of 314 sq. in. or 2.18 sq. ft, (0.19 sq. m.)- At a
velocity of 10 000 ft. (3048 m ) per minute, this allows a flow
of only 21 800 cu. ft. (617 cu. m) per minute, which will not
take care of a large machine, from the present standpoint of
possible capacities with the above diameter of rotor. By
additional openings in the rotor core, this might be increased to
30000 cu. ft. (849 cu. m.) per minute, but even this is still
T URBO-GENERA TORS 329
much less than a machine, with a 50-in. (127-cm.) diameter of
rotor, would require if built for capacities otherwise possible.
Therefore, on account of this limitation in the amount of cooling
air, other means of ventilation have received much considera-
tion. Two other general systems of ventilation, in addition to
the gap method, have been used, namely, the circumferential
method, and the axial The former has been developed and
applied more extensively in the past, but the latter contains
possibilities which are bringing it rapidly to the front.
In the circumferential method of ventilation, air is supplied
to-one or more points on the outside circumference of the stator,
and is forced circumferentially around through the air ducts to
suitable outlets, also on the outside surface. Air gap ventilation
is usually combined with this circumferential method, partly to
cool the rotor. The general arrangement is indicated diagram-
matically in Fig. 14, in its simplest form, namely, with one inlet
and one outlet diametrically opposite. A serious objection to
this method of ventilation is found in the limited section of the
ventilating path. Assuming, for example, a depth of stator
core of 20 in. (50.8 cm.) outside the armature slots and a total
of 40 f-in. (9.5 mm.) ventilating ducts, or a total effective duct
space of 15 in. (37.1 cm.) width then this gives a total section
of ventilating path of 20 X 15 X 2 = 600 sq. in., or 4. 16 sq. ft.
(0.386 sq. in.). On account of the relatively great length of the
ventilating path, air velocities of more than 6000 to 7000 ft.
(1828 to 2133 m.) are not desirable or economical, but even
with 10,000 ft. (3048 m.) velocity, the total quantity of air
would be only 41,600 cu. ft, (1166 cu. m.) per minute. Further-
more, this method is handicapped in machines with very high-
speed rotors, by interference between the radial and the cir-
cumferential systems of ventilation, so that the full benefit of
either is not obtained. Below a certain rotor velocity, apparently
the circumferential action can predominate, and the method is
fairly effective up to the permissible air capacity of the stator
ducts ; but at very high speeds the radial ventilation may very
seriously interfere with the other, so much so, that the radial
ventilation alone, even with its very restricted gap section, may
give as good results as the two methods acting together.
To avoid this interference, various methods have been devised,
such as closing part, or all, of the radial ventilating ducts at the
air gap to keep the radial effect from interfering with the other.
One arrangement which has been used in Europe to a considerable
3£0 ELECTRICAL ENGINEERING PAPERS
extent is indicated in Fig 15. In this, the alternate radial air
ducts are closed at the outside surface, while all are closed at
the air gap- The air enters by the ducts open at the back of
the machine, flows both circumferentially and toward the' gap,
and crosses over to the immediate ducts by axial opeiiings back
of the armature teeth, and then along these ducts to the outlet.
This scheme is effective in principle, but is uneconomical in the
sense that less than the total section of stator duqts is useful,
as regards the quantity of air which can be carried. There is
usually one large central duct to allow an outlet for the rotor
ventilating air. This particular arrangement of the stator also
uses axial ventilation in crossing over from oiie«set of ducts to
the other, which is an effective arrangement.
A modification of the simple circumferential method of
J
pnrnonnn
v
FIG. J5
ventilation is to admit air to the back of the stator at two oppo-
site sides of the machine, and deliver it at two outlets at inter-
mediate points on thej surface, as shown diagrammatically in
Fig. 16. By this means, the cross section of the ventilating
path is doubled and the length is .halved. Also, the interference
of the radial ventilation with the circumferential will be less
harmful. A serious disadvantage in the Circumferential venti-
lation in general is that the ventilating path is relatively long,
especially where there is but one inlet and outlet, and therefore
the cooling air at the outlet of the channel may be considerably
hotter than at the inlet, with consequent less effective cooling
action. This means points of local higher temperature in the
core, due to the method ,of ventilation. In the radial type of
ventilation, the coolest air is applied near the seat of the highest
losses, namely, at the armature teeth, and immediately back of
TURBO-GENERA TORS
331
them, and the air, as it becomes heated, passes over the outer
part of the iron which has a diminished loss, and therefore
normally less heat to dissipate. Therefore, the effect of the in-
creased temperature of the cooling medium is offset by the lower
Loss and .consequent less necessity for ventilation, in the part
where the air is hottest. The radial system of cooling is therefore
theoretically the most effective, but practically, the difficulty
•s in applying it, due to the limited air passages available.
BoUk the circumferential and the radial methods of cooling
arre subject to one serious defect, namely, most of the generated
heat in the stator iron must be conducted across the lamina-
tions to the air ducts. The rate of conduction across the" lamina-
FIG. 16
tions is only from 1 per cent to 10 per cent as 'great as along the
laminations themselves, according to various authorities.
Therefore, if the heat could all be conducted along the lamina-
tions to the ventilating surfaces, apparently much more effective
heat dissipation could be obtained, provided sufficient surface
is exposed to the air, and an ample quantity of air supplied.
This has led to the development of the axial system of ventila-
tion, as distinguished from the radial and circumferential.
In this method, a large number of axial holes are provided in
the stator core which may extend uninterruptedly from one
side of the core to the other, or they may extend from each side
to one or more large central radial channels which form the outlet.
The usual numerous radial ducts are omitted, or may be con-
332 ELECTRICAL ENGINEERING PAPERS
sidered as combined in one central channel. This general
arrangement is illustrated in Fig. 17. The rotor cooling is
accomplished by air along the air gap, and through the rotor
core to the large central duct. In this method of ventilation
therefore, there is a combination of two types, namely, the axial
and the air gapy but there is not the interference between the
two, that is sometimes found where the circumferential method is
used.
From the preceding, it may be seen that the problem of
putting a sufficient quantity of air through the machine is an
extremely difficult one. In addition, in very large machines,
the problem -of supplying the required quantity of air from a
suitable blower forms another serious problem. In smaller
capacities, and in slower speed machines, it has been the usual
practise to attach blowing fans to the rotor shaft or core, as
nonnnn
FIG. 17
part of the outfit. There is no particular difficulty in this
arrangement, except, possibly, in the high-speed construction
of the fans required for 60-cycle, two-pole machines. Such
fans can supply an amount of air whieh is limited by the diameter
and other dimensions of the fan itself.
Assume, for example, that by lengthening the rotor core, or
by other modifications in the construction, the capacity of the
machine can be doubled, and therefore double the quantity of
air is required for cooling. If the limit of the fan design or
operation was reached before, then obviously some radical
change is required with the new capacity of the machine. This
condition apparently has been reached in some of the later
practise in large, high-speed turbo-alternators. One ot>vious
solution of this difficulty lies in the use of separate slower speed,
large diameter, fans or blowers. This may appear to be a step
backward, but when the above conditions and limitations are
T URBO-GENERA TORS 333
taken into account, it is not so. The " tail " must not be
allowed to '"wag the dog;" the blower, which is an adjunct,
must not be>allowed to dominate the construction of the machine
itself. Moreover, there are a number of meritorious features in
the use of a separate blower. In the first place, it can be made
somewhat more efficient than the high-speed, rotor-driven fans.
Again, with a suitable means to drive, variable speeds, and
therefore different air pressures, can be obtained. This feature
may prove to be very desirable or advantageous under peak,
or overload, or emergency conditions.
One further condition keeps cropping out in the general
problem of ventilation, -namely, that of filtering or washing, or
otherwise cleaning the ventilating air With 50,000 to 75,000
cu. ft. (1415 to 2122 cu. m.) of air per minute passing through
a large machine, obviously in a year's time, an enormous quan-
tity of foreign matter is carried through the machine with the
ventilating air. A deposit of a very small per cent of this in the
machine will probably be disastrous. In fact, however, the
high velocity of the air through the machine serves to keep the
air passages clear if no oil or moisture is allowed to enter. That
a large amount of foreign matter does go through the machine
is very soon shown in case a little oil is allowed to get into the
ventilating passages. This oil catches the dirt and in a short
time the ventilating passages may be very materially obstructed.
On account of the deposit of dust, etc. in the ventilating
passages, it is necessary to clean certain types of machines at
more or less frequent intervals, and it is advisable to clean all
types occasionally. With some systems of ventilation, where
such cleaning is difficult, or almost impossible, such as that
shown in Fig. '16, provision must be made for cleaning the air
before it enters the machine. With the particular construction
shown in Fig. 16, air filters are almost always supplied. In the
American types of construction, however, such filters have not
yet been used, except in a< more or less experimental manner,
due probably to the greater accessibility of these machines as
regards cleaning. But such filtering processes possess consider-
able merit in general. One modification which is being agitated
at present i? that of washing, instead of filtering, the air. This
serves the double purpose of cleaning and cooling the air, and
in very hot weather, when the available capacity of the machine
is at its minimum, this cooling effect may mean a reduction of
6 to 10 deg. in the tetnperatuxe 6f the machine.
334 ELECTRICAL ENGINEERING PAPERS
THE TEMPERATURE PROBLEM
In the general problem of temperatures in electrical apparatus,
it is not the rises, but rather the ultimate or limiting temperatures
which are of first importance. Furthermore, the real limitation
in ultimate temperature does riot lie in the copper and iron,
but in insulating materials used; and only insofar as the tem-
peratures of the former affect the latter do they concern the
general problem. However, as insulating materials in themselves
are not usually sources of heat, but as they receive most of their
heat from adjacent media, such as iron or copper which may be
generating loss, the real temperature problem, as regards insula-
tion, resolves itself into the consideration of that of the adjacent
materials. Therefore, it is one which, for its full analysis,
requires a knowledge of the sources and amounts of heat gener-
ated, and its conduction and distribution to other parts
Broadly speaking, there is always a flow of heat from points
of higher to those of lower heat potential and the amount of
flow is also a function of the quantity of heat generated, the
section and length of the paths through which it can flow, and
the specific heat resistance of the various materials which con-
duct the heat. In an electric generator, for example, heat is
generated in large quantities in the armature teeth and in the
armature core It is also generated in the armature coils when
the machine is carrying load Part of the armature copper is
buried in the armature slots where it is almost surrounded by
iron, which, in itself, develops a loss, while another part, such
as the end windings, may be surrounded by, and thoroughly
exposed to, the ventilating or cooling air In such end portions,
the flow of heat will usually be from the inside copper, directly
through the insulation to the cooling air The amount of heat
which will flow from the copper through the insulation, depends
upon the temperature differences between the copper and the
outside surface of the insulation, upon the cross section of the
path of flow, upon the thickness and 4' make-up " of the material,
and upon the heat-conducting properties of the insulation itself
There is also a considerable temperature gradient from the
outside surface to the air. If the surrounding air is not renewed
with sufficient rapidity, the flow of heat from the insulation to
the air may raise the temperature of the adjacent air, so that
the total temperature drop is decreased, and the amount of heat
dissipated is correspondingly reduced.
In the armature core, the problem is much more complex
r URBO-GENERA TORS 335
In the copper buried in the armature slots, there are usually
three paths along which the heat can flow. First, it may flow
from the copper directly through the insulation to the fron,
-provided the adjacent iron temperature is lower than that of
the copper. Second, it may flow lengthwise of the copper to
the end windings to be dissipated directly into the air from that
portion ot the winding, as described above Third, in the case
of open-slot machines, one edge of the coil may be exposed to
the air in the air gap, and there may thus be a direct conduction
of the heat through the insulation to the air in the air gap. This
latter case, however, only holds for the upper coil, or that next
to the gap, in the case of two coils per slot, which is the most
common construction In the bottom coil, the only means of
conduction in the buried portion of the coil, are to the adjacent
iron or lengthwise to the end windings, or to the adjacent upper
coil, which, however, would normally have at least as high
temperature as the lower coil Therefore, the two effective
paths should be considered as through to the iron and thence
to the air, and lengthwise of the copper to the end windings and
to the air. It is the relation of the various factors of these two
paths that control the actual temperatures.
It has usually been considered that, in the buried copper, the
greater portion of the heat is conducted directly into the sur-
rounding iron. This, however, is only partially true, depending
upon many features in the construction and type of apparatus,
The heat conductivity of copper is, roughly, about six times that
of laminated iron lengthwise of the sheet, which is possibly ten
to twenty times as great across the laminations. In an armature
which is comparatively narrow and which has very open, well
ventilated end windings, a relatively small difference in tempera-
ture between the copper at the center of the core and that in the
end windings, may cause a relatively large flow of heat from the
buried copper to the end copper. Therefore, in certain design?,
a great part of the armature copper heat may be dissipated
through the end windings, and not through the armature core,
especially in those cases where the armature core in itself has a
considerable temperature rise. There even might be no con-
duction of heat from the copper to the iron, or there may be
conduction from the iron to the copper; for it the copper is at
the same temperature as the iron at the center of the core, for
instance, then at each side of the center, or as the edges of the
core are approached, the copper temperatures will be relatively
336
ELECTRICAL ENGINEERING PAPERS
lower than at the center, and therefore lower than the adjacent
iron, on the assumption that the iron temperatures would be
practically constant over the full width of the core The con-
ditions would therefore be as represented in Fig. 18. The solid
line a in this figure represents the iron temperature at uniformly
40 deg. cent, rise, and the dotted line b represents the copper
temperatures ir6m the center of the core to the edges. Th* tem-
peratures at tne center being assumed the same for copper and
iron, obviously there will be a flow for heat from the iron to the
copper near the edges or the core. The effect of this additional
heat carried out by the copper would be such as to tend to increase
the temperature of the copper at the center of the core by " bank-
ing up f ' the copper heat.
Again, if the temperature of the copper at the center is materi-
10°
FIG. 18
FIG 19
ally higher than that of the surrounding core, the conditions
may be as represented in Fig. 19 In this case, assuming the
core at constant temperature, there will be heat flow from the
copper to the iron at the center of the core, and from the iron to
the copper at the edges
This study of the problem leads to certain very curious con-
ditions which are sometimes found in large machines. At no-
load, for instance, with practically no copper loss present, and
with high iron loss, there may be a very considerable flow of
heat from the armature teeth through the insulation into the
copper, and thence to the end windings and to the air. In this
way the temperature -of the armature teeth at no-load, and with
normal voltage generated, may be considerably reduced by con-
duction of the iron heat into the copper, while the copper itself
TURBO-GENERATORS 337
may show a very considerable temperature rise. When load is
placed upon such a machine, sufficient to raise the temperature
of the copper up to that of the iron in the armature teeth, the
latter is actually increased in temperature, due to the prevention
of the heat conduction into the copper. In this way, therefore,
the copper may apparently heat the iron, although there is no
direct flow of heat from the copper to the iron, but the reverse
flow is prevented.
In high-voltage windings requiring thick insulation, the temp-
erature drop from the copper to the outside may be relatively
large; that is, with a given difference of temperature between
the copper and the surrounding air," a relatively small amount
of heat may be conducted through the insulation. Experience
shows that the amount which can be conducted is a function of
the quality of the material, the way it is built up, its thickness,
and also the pressure upon it. It is almost impossible, in a
machine in service, to calculate exactly the flow of heat, even if
all the temperature conditions are known, for the insulating
material itself is one of the variables in the problem The ability
of the insulation to conduct heat will change with operating
conditions, to some extent, as, for instance, it may tend to ex-
pand somewhat under heat, and thus change its heat conducting
qualities.
In the armature iron, the problem of heat conduction is just
as complicated as in the armature conductor. The principal
sources of heat lie in the armature teeth and in the armature
core back of the teeth. As a rule, the loss in the portion of the
core immediately back of the teeth is relatively greater than at
a greater depth, for the magnetic fluxes which cause the tempera-
ture rise, generally crowd close to the teeth, so that the density
is higher at such parts.
The heat from the armature teeth can be dissipated along
several paths. It can flow lengthwise of the laminations to the
end of the tooth and into the air gap, where the ventilation is
usually fairly good, but the tooth surface exposed is relatively
small. In the second place, it can flow back along the lamina-
tions to the armature core where it can spread out through a path
of much greater cross section and be conducted partly to the back
part of the laminations, and partly transversely to the ventilating
ducts. A third path from the armature teeth is across the
laminations of the teeth, to the neighboring ventilating ducts.
This latter path, however, must necessarily be relatively poor
338 ELECTRICAL ENGINEERING PAPERS
in conductivity per unit section of path, compared with the
others, but offsetting this, it is frequently of much greater cross
section and of relatively small length. In passing from plate
to plate, the heat must pass through the insulating varnish,
or other material used, which is of relatively high heat resistance
compared with the iron itself. Nevertheless, in machines with
radial ventilation, a very considerable portion of the heat due
to the tooth loss is carried transversely thrpugh the plates to
the air in the ventilating ducts, simply because that is the path
of lowest total heat resistance, everything considered. In mariy
cases, the temperature in the core back of the teeth may be as
high as that of the teeth, themselves, so that the only flow
possible is across the laminations to the air ducts, or lengthwise
to the tip of the teeth in the air gap. Therefore, the question
whether the armature teeth may be hotter than the armature
core, or whether the flow of heat is from the teeth to the core,
or from the core to the teeth, is a very involved one; and yet
upon this question depends, to a great extent, the temperature
rise in the buried armature copper. If the armature core is
normally hotter, than the teeth, and a considerable amount of
heat in the teeth is carried away by the buried copper at no
load, then it may happen that when carrying heavy load, the
heat in the teeth will rise very considerably above the no-load
condition, and it may actually so " bank-up " that there is still
more or less flow from the iron to the copper, eVen with load.
With such a condition, therefore, the outside of the insulation
may reach a higher temperature than the inside, while in those
cases where the temperature of the copper rises above that $f
the iron of the armature teeth, the inside of the insulation
will be hotter. Therefore, the temperature to which the insula-
tion is liable to be subjected appears to be largely a problem
for the designer to determine from his- calculations, based upon
accumulated data and experience. This is especially the case
with very wide armature cores and large, heavily insulated
armature coils, such as found in large capacity, high speed
turbo generators. In such machines, experience has shown
that various temperature conditions may be found, depending
upon the location and relative values of the losses in the different
parts and the means for conducting away the heat. Tests
have shown that, rq. some cases, the armature iron at the center
of the core is considerably warmer than the armature copper,
while in other cases the opposite is found to be true.
T URBO-GENERA TORS 339
In such apparatus, the temperatures actually obtained are
liable to be materially higher than the usual methods of measure-
ment will indicate. These temperatures are inherent to the
conditions of design and cannot be avoided economically, in
certain types of apparatus, such as turbo-generators. In such
machines, the limitations in speed, strength of material, etc.
force the designer to certain proportions which preclude larger
dimensions, or lower inductions in the iron, or lower densities
in the copper, or increased ventilation. In such apparatus
therefore, the development apparently lies in the direction of
insulations which will stand the higher temperatures which may
be' obtained.
These conditions of higher temperatures in some parts of
the machine, than indicated by the usual tests, have been
recognized for years by designers and manufacturers of large
electric machinery. A rough indication of these temperatures
can be obtained by exploring coils or thermo-couples suitably
located. However, it is evident that such coils, if located next
to the copper, will not give the correct temperature measurement
if the flow of heat is from the iron to the copper, while a coil
next to the iron will not give the correct result .with the flow
from the copper to the iron. Experience has shown that the
temperatures, in corresponding positions around the core, may
not be uniform, due to local conditions. In consequence, it is
not practicable to actually determine the true temperatures of
all parts of the insulation on commercial machines, except by
measurements of a laboratory nature, which wtould involve such
a number of separate readings as to be commercially prohibitive.'
On account of the higher temperatures which may be found
in such apparatus, and the difficulty of making exact measure-
jmcnts, except by laboratory methods, manufacturers very
generally have adopted the use of mica as an insulating material
on the buried part of the coils. Experience has shown that such
material, when properly applied, can safely stand temperatures
of at least 125 deg. cent. How much more has riot yet been
determined.
Of such machines it may be said that the manufacturer, with
his 'guarantee of 40 deg. cent, by thermometer, actually builds
for possible temperatures of 70 to 90 deg, cent, in some parts of
the machine, for he expects to find fairly high temperatures in
some cases with exploring devices. The usual guarantee trf 40
deg. cent, therefore should be considered as only a relative indi-
cation of a safe temperature in such apparatus.
340 ELECTRICAL ENGINEERING PAPERS
If, for instance, the exploring coils should show 70 deg. cent,
maximum rise under running conditions, and the permissible
ultimate temperature of fibrous or tape insulation is assumed
as 90 deg. cent, for continuous operation, then obviously, with
air at 40 deg. cent, the insulation would be considered as insuffi-
cient from point of durability, except for intermittent service,
such as overloads, and such limited conditions. Plainly, the
insulation, for such temperatures, should be of mica, or equiva-
lent material, for which 125 deg. cent, has been found to be safe.
Furthermore, it may be stated that with such mica insulation,
a turbo generator which shows 75 deg. cent, rise by exploring
coils, or thermo-couples, has, in fact, more margin of safety
than the ordinary varnished-tape-insulated low-voltage machines
of any type, which show 40 deg. cent, rise by thermometer or
SO deg. cent, rise by resistance.
The foregoing aims to bring out clearly that the temperature
problem is a most complex one, in all electrical apparatus, and
especially so in turbo-generators. It indicates that no simple
temperature test can show all the facts, and that all commercial
methods must be considered as approximations. It also shows
the absurdity of classifying a piece of apparatus as good or bad,
respectively, according to whether it tests possibly one or two-
degrees below or above a specified thermometer guarantee.
Also, following out the above principles on heat flow, various
fallacies in temperature measurements might be noted. For
example, it is usually assumed that, after shutdown, if a grad-
ually rising temperature is shown, this is a more accurate indica-
tion of the true temperature. But this may be entirely wrong as
regards windings. If, for instance, the core back of the armature
slots is materially hotter than the armature teeth while carrying
load, then, upon shut-down, with the air circulation stoppedr
the teeth will rise to approximately the same temperature as the
core back of the teeth, and there may be a flow of heat into the
coils, which condition may not have existed while carrying load.
A thermo couple on the coil or in the teeth would thus indicate
a false temperature rise after shut-down. This is cited simply
as one of many instances, to show the possibilities of entirely
wrong conclusions which may be reached in the problem of
temperature.
THE INSULATION PROBLEM
The one fundamental condition which must be considered in
the insulation problem, is the durability of the material itself, and
T URBO-GENERA TORS 34 1
this must be viewed from two standpoints, — the mechanical, and
the electrical. From the mechanical standpoint, the material
may have its insulating qualities impaired by the action of
mechanical forces which tend to crack, or crush, or disrupt the
material itself, or it may be affected by being permeated by
foreign materials or substances, or it may be injured by such
overheating as will partially or wholly carbonize it, or render it
brittle or otherwise unsuitable for the desired purpose.
From the electrical standpoint, it may be weakened by 'deter-
ioration of the quality of the insulating material itself or some
of its component parts, which may be due to heating; or oxida-
tion, or many other causes.
The effect of mechanical injury, such as cracking crushing
or overheating, on the insulating qualities, will depend upon
many conditions. In some cases, with relatively low voltage,
any effective mechanical separation of the parts is sufficient for
electrical purposes. For higher voltages, continuity of the separ-
ating insulating medium is necessary.
Experience has shown that, for moderate voltages, tempera-
tures which may injure, or even ruin, the insulating material,
from a mechanical standpoint, may not seriously affect its
insulating qualities. Many insuhating materials of a cellulose
nature will still retain good insulating qualities if maintained
at temperatures as high as 150 deg. cent, for such long periods
that the material itself semi-carbonizes. Under such high
temperature conditions, however, it becomes structurally bad, —
that is, it may become so brittle that it tends to crumble, or
powder, or flake off, and thus its value as an insulation is im-
paired by displacement of the material itself. In low voltages,
therefore, it is not a deterioration in the insulating qualities,
but rather a mechanical breakdown of the material itself, which
is liable to cause trouble. With high voltages, however, the
conditions may be quite different. With some insulating mater-
ials, the dielectric strength may be so affected by long continued
high temperatures that the insulating quality becomes insufficient.
This has a direct bearing on large capacity, high-voltage turbo-
generators.
In the problem of insulation, certain difficulties have been
encountered in large turbo-generators, which, while they would
have developed eventually in other large machines, yet became
apparent more quickly and preeminently in the turbo type, due
to the abnormal conditions in its design. The two most promi-
342 ELECTRICAL ENGINEERING PAPERS
nent difficulties were, first, that of relatively high temperature
in the buried copper, already described, and second, the destruc-
tion of the insulation by reason of static discharges between the
coils and the armature iron
Due to the fact that the ultimate temperature reached in such
machines not infrequently exceeds the safe limits for insulation
of the fibrous or cellulose type, such insulations will show
deterioration eventually in their insulating qualities and their
durability. In consequence, with the advent of the larger
machines, it became necessary to return to the use of mica for
insulating purposes on the buned part of the coil This type
of insulation in the form of mica wrappers, had been used
extensively on some of the earlier large capacity, slow-speed
generators, but it had not been adopted on large turbo-generators,
due principally to the difficulty in applying the very long
wrappers for the straight part of the coil. However, when the
gradual deterioration of the fibrous type of insulation was noted
in large turbo-generators, the mica wrapper type of insulation
was again taken up and, after considerable experiment, was
applied successfully for the outside insulation on the straight
parts of the coils This use of mica overcame the deterioration
in the insulating qualities of the outside insulation, but for
a while it was considered that a fibrous type of insulation was
still effective between turns in those coils where there were
two or more turns in series per coil. As stated before, the
insulating qualities of many fibrous materials will stand up
astonishingly well under low voltages, when the material is
apparently so greatly heated that it is practically carbonized,
Therefore, temperatures which did not carbonize, but simply
browned, or darkened, the material, had not been considered
dangerous, and undoubtedly many thousands of electrical
machines of all kinds are today in operation, in which the
insulation is in this condition, and in which no trouble need be
expected. For this reason, little or no trouble was expected
between turns on the turbo-generators. However, a new con-
dition was encountered in large capacity machines, namely, the
insulation between turns, when it became dry and brittle at the
higher temperatures, was liable to be injured by the terrific
shocks to which the coils were subjected in such machines, in
case of a short circuit across the terminals. The insulation would
be cracked, or so distributed that short circuits would occur later,
without apparent cause. These short circuits on large machines,
T URBO-GENERA TORS 343
most often appeared as breakdowns to ground, even with the
mica wrapper insulation on the outside of the coil Incidentally,
several cases were discovered where arcs had occurred inside
the coils between adjacent turns, and where they had not yet
broken through the outer insulation to ground. For many
months the writer, with his associates, followed up this matter,
examining all available coils and windings. Eventually the
conclusion was reached that many of the breakdowns to ground
had actually started between turns on the inside of the coil.
Moreover, as a corroboration, it was noted that in machines
with one conductor per coil, the breakdowns were practically
negligible. This investigation led to the practise of insulating
the individual turns, in each coil, from end to end, with mica
tape. After the adoption of this practice, it is noteworthy that
the breakdowns to ground practically disappeared, although
the outside insulation to ground had not been changed in type
or thickness.
Many improvements have been made in recent times in the
application of this mica insulation. One of these is the Haefely
process, developed in Europe, but now being used extensively
in this country. By this process, the mica wrappers are s'o
tightly rolled on the cofl that practically a solid mass of insula-
tion, of minimum thickness and greatest heat conductivity is
obtained.
By means of the mica insulation, the temperature difficulties
in general have been entirely overcome, and a durable and non-
deteriorating construction, from an insulation standpoint, has
been obtained with the temperatures which appear to be more
or less inherent in the large, high-speed turbo-generators.
The second trouble, namely, that due to static discharges
between the annature copper and the iron, was also encountered
to a certain extent, on some of the earlier machines. It was found
that these discharges were apparently " eating " holes, or even
grooves, through the outside insulation of the armature coils.
This effect was most pronounced at the edges of the air ducts
and at the ends of the armature core, where edges were presented
by the iron. After a long period, the holes or grooves would
become so deep that the insulation was weakened or ruined.
This was a very disturbing condition, when it was once fully
recognized and appreciated. Again, a comprehensive investi-
gation was made to discover a cure for this difficulty. Various
types of machines and windings were examined. It was noted
344 ELECTRICAL ENGINEERING PAPERS
"that the action was a function of the voltage of the machine,
"but was noticeable, in some cases, at relatively low voltages.
During the course of the investigations, it was noted that where
mica, wrappers were used with an outside layer of tape, the " eat-
ing away " extended only through the outside wrapping in as
far &s the mica, and that no 'apparent effect at the tnica was
visible. Even when examined , with a very powerful microscope,
no evidence of any puncture of the mica was found, in any case
These investigations naturally led to th,e- conclusion that the
#iost suitable remedy for the trouble was the use of mica insula-
fton, which was also a remecly for the temperature conditions
This is one of the rare cases in large turbogenerators where two
•desirable conditions do not conflict With feach other. The rnica
insulations on the buried part of the coil has now been very
generally adopted in this country on high-voltage ipachines,
whether of- the turbine-driven, or aiiy other type
This, static trouble was considered so serious at one time that
low voltage practice with step-up transformers was adopted
by some manufacturers as the safest course, until something
positive in the way of a femedy was proved out. This trouble
promised to be one of the most serious encountered in high-
voltage generator work, and even threatened to revolutionize
practise in winding generators for the higher voltages. However,
as consistently advocated by the writer, the us£ of mica, suit-
ably applied, appears to have entirely overcome this trouble, as
evidenced by several year's experience, and 'all indications now
are that there need be no fear from static discharges on windings
of 11,000 and 13,000 volts, Even in the 11, 000- volt New Hatfejn
generators with one terminal grounded, which gives the equiva-
lent of a I9tOOO-voltT three-phase winding with the jieutral
grouiided, the mica insulation appears to-be successful and dur-
able.
ROTOR INSULATION
In most of the early turbo-generators, the rotor winding
in the slots was insulated with fibrous material!'" fish paper "
and " horn M fiber having the ^reference. 'One of the difficulties
in the rotor is, that the insulation between the winding and the
slot is liable to be crushed or cracked by the higlji •centrifugal
forces. In the earlier insulatibns, before fish paper was used, it
was found that even at very moderate temperatures, the insula-
tion got dry and brittle, and cracked readily. Fish paper, or
horn fiber, was then adopted pretty generally. Such material
T URBO-GENERA TORS 345
apparently stood much higher temperatures than the ordinary
fibrous insulations. However, experience also showed that
eventually this also became brittle, arid was liable to be cracked,
and then displaced, due to the centrifugal forces. There is
always the possibility of a sinaH amount of movement in the
field coils when a machine is being brought up to speed, and this
movement, in itself, may eventually damage the insulation if
it is at all brittle.
As the capacities and speeds of turbo-generators were increased
and the space limitations for the rotor windings became more
pronounced, the resulting higher normal temperatures led to
the adoption of mica for the insulating material in the slots with
either mica or asbestos for the insulation between turns. As
the voltage between adjacent turns is always extremely low,
what is needed -is really a durable separating medium, rather
tharf an insulation, this medium being one which will not become
crisp or brittle at fairly high temperatures. Asbestos has
served for this purpose very effectively, and even has some
advantages over mica, as the latter must be applied in relatively
small pieces in the form of strap or tape, and the individual
pieces are more readily displaced or shifted than is the case
with asbestos. Some very severe tests have been made in
order to determine the possibilities of such rotor insulation
In one case, a turbo rotor thus insulated was run at full speed for
over 40 hours, with such a current that the rise by resistance
in the rotor copper was about 250 deg. cent It was the in-
tention to continue this test very much longer, but the conduc-
tion of heat from the winding to the core, and thence through
the shaft to the bearings, was such that finally the bearings
became overheated and gave out. After this test, the winding was
carefully dismantled, and no evidence of any injury^ to the
insulation could be discovered. Of course, such temperatures
a*e not recommended in turbo rotor practice, but this was
simply an attempt to find' a temperature limitation. If a
designer wants to find the facts in any apparatus, he will obtain
the most valuable information if he operates the apparatus
up to the point of destruction. He thus fixes a limit which
•he must keep below.
The use of thica, or mica and asbestos, on turbo rotors has
been very .generally adopted in this country at the present time,
and it may fee said that, within the writers experience, no case
of .destruction ot.one of these windings through heating, has
346 ELECTRICAL ENGINEERING PAPERS
come to his notice, although a great number of them have
been in service for a relatively long time. In many of the older
machines with fish paper insulation in the rotors, the conditions
of ventilation and the normal ratings of the machines were
such that the maximum temperatures in the rotor windings
were relatively much less than in present practise It may there-
fore be said that the use of mica in the rotor has been largely
due to the introduction of the larger capacities and higher speeds.
LOSSES IN TURBO ALTERNATORS
The total iron and copper losses in a large, high-speed turbo-
alternator are in general no higher than in a corresponding
capacity low-speed machine
As far as the iron losses are concerned, no further comment
need be made than that the magnetic flux densities in general
are somewhat lower than in lower speed machines of same
frequency, and therefore the losses per unit volume of material
are no larger.
The total armature copper losses in turbo-alternators, as a
rule, are considerably smaller than in corresponding capacity
machines of the moderate or low-speed types. This is due partly
to the use of a smaller total number of conductors, and partly
to a lower current density in the armature conductors. As
brought out before, in a narrow core machine, a considerable
portion of the buried copper heat may be conducted lengthwise
of the conductor into the end winding, and there dissipated
into the air In the turbo-generator, with its much wider
core and greater distance from the buried copper to the end
windings, a smaller percentage of the buried copper heat will
be conducted into the end windings. To partly compensate
for this, it is usual to work the armature copper in the turbo-gen-
erators at a lower current density, and therefore at a relatively
lower total copper loss. This is somewhat of a handicap in the
economical design of the generator, as extra space is thus required
for the armature winding. In some of the earlier machines, the
armature conductors were made of solid copper bars of relatively
large section, partly for stiffening or bracing the end windings,
as will be referred to later With these solid conductors there
was a very considerable loss in the buried copper due to eddy
currents. To compensate for this, the armature conductors
were made very large in section, so that the current density,
due to the work current alone, was very low compared with
TURBO-GENERA TORS 347
practise in other types of machines. On account of the com-
paratively large section of armature conductors, the conduction
of heat from the buried copper to the end windings was relatively
large. In some of these earlier, large capacity machines,
the nominal current density in the armature conductors was
so low, and the section of conductors so great, that the total
buried copper loss, due to the work current, could be carried
from the buried paft of the coils into the end windings with a
comparatively small (drop -in temperature, so that,t if there had
been no eddy currents present, the buried copper would have
shown less rise .than the iron. Any considerable rise which
occurred was thtis chargeable to eddy currents in the buried
conductors, rather than to the work current. While such con-
struction was fairly effective for the purpose, yet it was decid-
edly uneconomical in design, as indicated before. In fact,
with later proportions and methods of design, the safe oiitputs
of some of the earlier machines could easily be 50 to 75 per cent
greater, largely on account of elimination of eddy currents and
improvement in methods of dissipating heat from the end wind-
ings. In many of the older machine's, the ventilation of the
end windings was not nearly as effective as in modeni types,
due principally to the form and arrangement of the end con-
nectors, tlsually $ir spaces were allowed between adjacent
coils although, in some instances, these were so small as to
give but little benefit. Moreover, in many cases, the type of
fend winding employed rendered these air spaces between coils
rather ineffective, unless special means were taken td deflect
the air between the coils. With later constructions, the end
windings lie more or less agross the path of the ventilating air,
and there are ample openings between the coils, so that a very
considerate part of the ventilating air will actually pass between
the cO^ls of thfe end windings in such a way as to give the niaxi-
nuih possible ventilation. When it is considered that the total
armature copper loss may be only 20 per cent of the total stator
loss, it will be seen that an excessive amount of air is Hot re-
quired when the end windings are properly arranged for most
effective ventilation.
Much effort has been expended in eliminating or reducing
th£ eddy current, losses in the buried copper of large turbo-
generators, as well as in othef types of large capacity alternators.
These eddy currents aare due to two sources, namely, the alter-
nating magnetic flux across the slots djie to ttte armature ampere
348 ELECTRICAL ENGINEERING PAPERS
turns per slot, and secondly, the magnetic fringing from the
rotor pole face into the open armature slots. In some instances,
tests have indicated that the local e.m.fs. set up in the armature
conductors by the flux through the slot opening is very consider
ably greater than those due to the flux across the slot. Obviously
with partially closed slots, this fringing into the top of the slot
should be practically absent.
The simplest remedy for the eddy currents set up by these
local e.m.fs. is to sub-divide the conductors into a number of
wires or conductors in parallel, so arranged or connected that
the local e.m.fs. oppose and, to a great extent, balance each
other. This opposition may be obtained by special arrangement
of the conductors in each Individual slot, 6r parallel conductors*
in the two halves of a complete coil may be connected in oppo-
sition to each other. Some of these arrangements do not com-
pletely balance the opposing e.m.fs., but they include the resist-
ance of the complete coil in the eddy current circuit, so that the
eddy losses are not only very materially reduced, but they are
distributed over the entire coil, including the end windings, which
condition, in itself, represents a very material improvement.
PROTECTION AGAINST FIRE
An important problem connected with the insulation of
large turbo-generators, is found in the fire risk, or danger of
destruction of th3 end windings due to starting an arc at some
point. On account of the tremendous ventilation in such
machines, a fire, if once started, may quickly ruin the entire end
winding. An extended investigation was made, with a view
to providing an insulation which would not burn rapidly.
Among other tests, the end windings were finished on the out-
side with an asbestos covering or tape However, such tape
requires some sort of sealing varnish, or material to fill its pores,
to keep it from absorbing moisture or oil. The tests showed that
if a fire was once started, combustion would be maintained by
the gases liberated by the u gasification " of the varnishes and
other material in the end windings, whether the coil was covered
with asbestos or not. No covering which was tested appeared
to be very effective. Although some outside covering might be
found which would be slightly effective in preventing fire from
starting so readily* yet, if once started, it appears that a fire
can very easily maintain itself in such machines. Eventually,
the conclusion was reached that the safest course would be to
T URBO-GENERA TORS 349
provide suitable closing doors or valves in the air inlets to com-
pletely shut off the incoming air to the machine. In addition,
suitable doors on the air outlets, where they can be applied,
should also be helpful, by retaining the smoke and burnt gases
inside the machine, which thus assist in smothering the flames.
The uSe of fire extinguishers of the gaseous type will usually
be rather ineffective, unless the incoming air and ventilation is
practically cut off. For instance, with 60,000 cu. ft, (1698 cu.
m.) of air per minute passing through a large machine, the
addition of a little gas for extinguishing the fire would hardly
make any impression. In one instance, in attempting to extin-
guish a fire, an effort was made to feed the gas in against the
ventilating pressure of the fans. Obviously, this would not
work, and then a hose was used in order to get enough pressure
to counteract the fan action. Although the fire was extinguished,
the resultant effect of fife and the high pressure water was that
new insulation was required.
REGULATION AND SHORT CIRCUIT CHARACTERISTICS
It has been known for many years to designers, that alterna-
ting current generators can give, at the instant of short circuit,
a much greater current than that which they will give on con-
tinued short circuit. The first emphatic evidence of this, in the
writer's experience, was in connection with the first Niagara
generators in 1894. Upon short circuiting one of these machines
at 'full speed and normal voltage, the results indicated a current
tush so great that it was apparent that it was limited only by
the anhature self-induction, and not by the so-called synchronous
reactance. Later, after being put into actual commercial
service, it was found necessary to brace the end windings on these
machines. However, at that time, no suitable instrument,
such as the oscillograph, was available for determining the
conditions on short circuit, and the phenomena did not permit
of fjuich 6*p'erimental investigation.
Similar evidence was found from time to time, as in the first
Manhattan Elevated engine type generators, which bent their
$nd windings out of shape on a dead short circuit. But the real"
possibilities for trouble in this matter did -not develop until
the large capacity turbo-generators came into use. In these
^machines, the armature ampere turiis per pole are so high,
Compared with moderate speed alternators, that the stresses
due to the stray magnetic fields oo^xort circuit are much greater
350
ELECTRICAL ENGINEERING PAPERS
than the natural rigidity of the end windings will withstand.
The manufacturer of such apparatus, without data of any
quantitative value at hand, did not fully recognize the Veal
•weakness in the end windings until disaster overtook them. Even
then it was a long and difficult undertaking to overcome the
trouble. All kinds of designs of etid supports, and various ar-
rangements of end windings were tried, with more or less success.
But each new -step in the increase in capacity opened up the
problem a&ain. It was soon noted that those armature windings
which were made up of cable or small wires, suffered most on
'short circuit, and for awhile therq was a tendency on the part
of some manufacturers to .use heavy, solid conductors to give
rigidity in the end windings. This was effective within certain
limits, but was very expensive from the design standpoint, as
on account of eddy currents in the buried copper It was neces-
sary to work at a very low current density, which was not
economical in winding space.
FIG. 20
In this country, the types of armature windings finally
narrowed down to the open-slot construction, usually with an
upper and lower coil per slot, with the end winding arranged
in two layers, similar to d-c. armature windings, or the common
induction motor primary windings. This turbo end winding
was extended at various angles to the axis of the machine froih
almost parallel up to 90 deg., as shown in Fig. 20. The principal
survivor of these types, is one which extends at some angle
between 30 and 60 deg. to the axis. There are several reasons for
this, — first, it allows a very 'substantial bracing to be applied to
the end windings. Second, the stray fields around the end
windings do not, to any extent, cut the adjacent solid parts,
such as the end housings, stator and end-plates, etc. An angular
position of approximately 45 deg. seems to be a good compromise
on these points. Ample supports, as shown in Pig. 21 can be
applied for bracing the windings against movement in any
T URBO-GENERA TORS 35 1
direction. Such end windings are usually braced against metal
supports attached to the stator end-plates. The coils are so
clamped to the racks, and are so braced against each other that
the windings will sustain a dead short circuit across the terminals,
even in the largest capacity machines, without injury.
On some recent large turbo-generators the end windings have
been further strengthened by double metal racks between the
two layers of windings, so arranged as to securely key these two
layers to one another at certain points. Moulded mica troughs
are placed around the coils as an extra insulation from the metal
racks. By this keying of the two layers to one another, the
winding as a whole is stiffened, quite irrespective of any other
clamping arrangement. In fact, this is practically equivalent to
putting the end windings in rigidly held slots, thus approaching
the conditions which obtain in the buried part of the coil.
In order to limit the momentary short circuit current, the
armature reactance is now usually made as large as the condition
of the design will permit. This naturally means high ampere
turns per pole, which in turn means high synchronous reactance,
and consequently poor inherent regulation of the machine,
especially on inductive loads. This can be illustrated by the
following example: Assume a 5000-kw. unit of an earlier design,
which can give 25 times full load current on momentary short
circuit. By certain improvements in the design of the armature
coils, such as the use of deeper slots, better subdivision of the
copper to eliminate eddy currents, improved ventilation and
'conduction of heat, etc., the capacity of the machine is assumed
to be increased to 10,000 kv-a., the number of armature turns
remaining the same as before. It is evident that when short
circuited, the revised machine will give the same total current
as on the former rating, which, however, is only 12£ times
the rated current on the new capacity basis. Obviously, the
end winding stresses are no greater than before, although the
nominal capacity has been doubled, and if it -were possible to
satisfactorily brace the end windings with the former rating,
the same bracing should be effective on the new rating. This
illustrates, roughly, what is taking place in later designs, although
the steps in the change may not be just those mentioned. Again,
in the above example, it is obvious that, with the now rating,
the inherent regulation at full load is the same as at 100 per
cent overload on the old rating, which means that it is relatively
poor. Another way to express this is, that the old fating might
352 ELECTRICAL ENGINEERING PAPERS
give 2| times full load current on steady short circuit, while the
new rating gives 1 \ times.
This condition of poorer regulation is inherent in the newer
practise, bttt is apparently acceptable to the users of such
apparatus, for a variety >of reasons wliich do not come within
the province of this paper.
CONCLUSION
The foregoing covers, in a general way, fnany of the problems
encountered in large turbo-generators, and defines the situation
as it stands at present.
It anay be suggested, in connection with the temperature
problem, that the high temperatures obtained are due to forcing
the construction too far; but, in answer, it may be stated that
it is forced no further in this feature than in many others. The
whole design has been carried far beyond the most economical
construction, from the generator standpoint alone. In fact, the
whole machine is more or less a compromise between desirable
conditions as a generator, and most economical conditions as
part of a combined turbine and generator unit. It may £e
added that the ultimate limits in construction and capacity will
be obtained only when the steam turbine conditions are satis-
fied, and there are indications that possibly this result is being
approached now with the present high speeds.
There is one small consolation in all the confusion of develop-
ment which has attended > the turbo-generator work, in the few
years it has been with us, namely, the question of choice of
speed has been practically eliminated. For 25 cycles, there
remains only one speed, namely 1500 revolutions, with two
poles, from the smallest unit up to 251000 kv-a. as a possible
upper limit. For 60 cycles, up to 5000 kv-a , two-pole machines
at 3600 revolutions are being furnished, while from this
capacity up to 20,000 kv-a. four poles may be used.
It will be evident to any reader of this paper, that the designers
of large turbo-alternators 'have had a strenuous time during the
past few years — very much more so than is indicated herein, for
their successes, rather than their failures have been discussed.
In fact, much of the time they have been working ahead of their
data and experience. In presenting this situation from the
design point of view, it is hoped that a better and clearer under-
standing of the turbo-generator ^problem will be obtained by all
who are interested in such apparatus.
TEMPERATURE AND ELECTRICAL INSULATION
FOREWORD— In 1911 and 1912, a revision of the standardization
rules of the American Institute of Electrical Engineers was being
made. The problem of temperature guarantees was referred to
a sub-committee, consisting of Dr. Steinmetz and Mr. Lamme.
It was decided by the Standards Committee to hold a mid-
winter convention of the Institute in February, 1913. In order
to furnish a basis for discussion of the temperature problem at
this convention, the sub-committee on temperature collaborated
in the preparation of this paper.
It may be noted that later information has modified some
of the figures for temperature limits. — (ED.)
THE problem of permissible temperature limits in electric
apparatus is largely that of the durability of the insulation
used. As this may consist of materials of widely varying heat-
resisting qualities, the probem resolves itself into one of con-
sideration of the properties of the materials themselves.
The durability of insulation may be considered from two stand-
points, the mechanical and the electrical. Temperatures which may
ruin the insulation, from a mechanical standpoint, may not radi-
cally effect its dielectric strength. This is particularly true with
moderate voltages where the insulation serves largely as a separat-
ing medium. The purpose of the insulation usually is two-fold:
First, it must serve to separate, mechanically, the electric conduc-
tors from each other, and from other conducting structures, and
second, it must withstand the voltage between the electric con-
ductors and between the electric circuits, and other con-
ducting parts. In lower voltage apparatus, usually only the
former function applies, as the mechanical separation is more
than sufficient to withstand the voltage used. The dielectric
strength of the material is, however, of first importance in high
voltage apparatus.
A great majority of the electrical "breakdowns" on low
voltage apparatus is due to mechanical weaknesses, as far as the
temperature problem is concerned; that is, high temperatures
may make the insulation brittle, or crisp, so that it may flake off,
or powder, or crack, or be crushed by mechanical action, thus
allowing the conductors to make contact with each other or with
adjacent conducting material.
354 ELECTRICAL ENGINEERING PAPERS
The " life of insulation " is an indefinite term and must bo de-
fined in time, mechanical strength, absence of foreign materials
of a conducting nature, etc. Almost all insulating materials
will be somewhat affected in time, and many of them tend to be-
come dry and brittle. The rate at which deterioration occurs
\\ith any given material, is some complex function of the tem-
perature and of other conditions.
CLASSES OF INSULATIONS
Insulations may be classified under three headings, depend-
ing upon their heat-resisting properties. However, all such
classifications must be relative, for no absolute limit can be fixed,
as there is no definite point at which injury or destruction can be
said to take place.
The usual insulating materials can be considered as included
m three general classes:
Class A. This includes most of the fibrous materials, as
paper, cotton, etc., most of the natural oil resins and gums, etc.
As a rule, such materials become dry and brittle, or lose their
fibrous strength under long continued moderately high tempera-
ture, or under very high temperature for a short time.
Class B, This includes what may be designated as heat-re-
sisting materials, which consist of mica, asbestos, or equivalent
refractory materials, frequently used in combination with other
supporting or binding materials, the deterioration of which, by
heat, will not interfere with the insulating properties of the final
product. However, where such supporting or binding materials
arc in such quantity, or of such nature, that their deterioration
by heat will greatly impair the final product, the material should
be considered as belonging to class A
Class C. This is represented by fireproof, or heat-proof
materials, such as mica, so assembled that very high tempera-
tures do not produce rapid deterioration. Such materials are
used m rheostats and in the heating elements of heating
appliances, etc
All the above are relative terms. The first class, for instance,
represents materials which are really more or less heat-resist-
ing, but which deteriorate at lower temperatures than those in
the second class, which are defined as heat-resisting. Also, the
fireproof materials of the third class are not strictly heat-proof
or fireproof, but will simply withstand very high temperatures
for rclativelv long pcnods without undue deterioration
TEMPERATURE AND INSULATION
355
In class A, the materials appear to have a very long life (or an
almost indefinitely long life, aside from mechanical conditions)
if subjected to ultimate temperatures which never exceed 90
deg, cent. Also, they appear to have a comparatively long life,
even at ultimate temperatures as high as 100 deg. cent. At
materially higher temperatures than 100-deg. cent., the life is
very greatly shortened, and temperatures of 125 deg. cent, will
apparently ruin the insulation, from a mechanical standpoint, in
possibly a few weeks, if such temperature is maintained steadily
However, for low voltages, the insulating qualities may still be
very satisfactory, even at this temperature, and therefore the de-
struction of the insulation is purely one of injury or breakdown
from the mechanical standpoint, as stated before. Tempera-
10
8
W6
flC
*.
2
o.
—
—
—
\
\
\
^^
ft 75 100 125 130
DEGREES C
FIG. 1
tures as high as 160 deg. cent, on such insulations for a con-
siderable period may not entirely destroy their insulating qual-
ities, althoiigh, mechanically, such temperature? appear to be
impracticable, except for very short periods.
In order to illustrate the relation between the possible life
and temperature of class A insulation, Fig. 1 is shown. This
must not be taken as representing actual results, but is simply in-
tended to illustrate, in a very approximate manner, the very great
shortening of the Kfe of insulation by increase in temperature.
It may be assumed that at very high temperatures, the insu-
lation will have practically the same life, in actual hours of high
temperature operation, whether the temperature is applied con-
tinuously or intermittently. For example, if an insulation has
10,000 hours Kfe with a certain high temperature continuously
356
ELECTRICAL ENGINEERING PAPERS
applied, it is assumed that it will also stand the same tempera-
ture for 10,000 hours in short periods, provided the intermediate
temperatures are low enough to represent an indefinitely long
life. It is probable that under the intermittent condition, the
life will really be slightly greater, due to the fact that depre-
elation will be largely mechanical, and the insulation may " re-
cover/* in some of its mechanical characteristics after each period
of high heating.
If 3 therefore, higji temperatures 'are reached intermittently,
with intermediate periods of lower value but still high enough
to shorten the life of the insulation, it may be assumed that the
total life o£ the insulation is the resultant of the life under the
two temperature conditions.
10
3
t-~i—
-b
5
j
U
r
j
V
0
"x
*--,
50 100 150 200 250
DEGREES C.
FIG. 2
In heat-resisting materials, such as those of class B tempera-
tures of 125 deg cent are comparable with 85 deg. cent or 90
deg cent in class A, and 150 deg cent in the tormer is comparable
with 100 deg. cent in the Utter Pig 2 illustrates very approxi-
mately the life-temperature curve of such insulations As in Fig
1 , this should not be taken as an exact representation of the actual
life Due to the greater heat-resisting qualities of such materials,
it appears that relatively higher temperatures'are not as quickly
harmful as in the first class
In class C materials, it is difficult to give any reasonable indi-
cation as to the limits of temperature, except that very 'high
temperatures, (practically up to the point of incandescence) are
found in some heating appliances.
TEMPERATURE AND INSULATION
357
TEMPERATURES AND FLOW OF HEAT
As the insulation, in itself, is not usually the seat' of generation
of loss or heat, it is the temperature of adjacent materials which
must be considered in defining the conditions in the insulation.
The temperatures of the adjacent materials should therefore be
considered only in so far as they affect the insulation itself, and
where such temperatures do not affect the insulation, or the life
of the apparatus, or its normal perfomance, they are immaterial
Considering the influence of the temperatures of the adjacent
media, the direction and amount of heat flow must be taken into
account, as the maximum temperature in the insulatiori is de-
pendent upon these. In the case of armature windings, for
instance, the heat flow may be from the buried portion of. the
coils toward the end windings. It also may be from the buried
copper through the insulation to the armature teeth, or there may
be a reverse heat flow from the iron to the copper, depending
upon the various factors of construction, heat conductivity of
the materials, amount of heat generated in the various parts,
ventilation, heat dissipation etc.
Depending upon conditions of heat flow and distribution,
various methods of temperature determination may be used.
No method is accurate, unless all the conditions of heat flow are
accurately known, which is never the case in commercial ma-
chines.
The difficulties in the problem of commercial temperature
determination are illustrated by Fig. 3.
358 ELECTRICAL ENGINEERING PAPERS
In the figure, a represents the temperature inside an armature
coil, b the temperature between the insulation and the iron of an
armature tooth, c that in the body of the tooth, and d that in the
body of the core at some point back of the coils and teeth. "Lei
the temperatures at no load be represented on the ordinate A
Then, at some load, represented by ordinate B, the relations
of the various temperatures have changed. At C, D and E,
there are still greater changes, depending upon the heat genera-
tion and distribution. If the rated capacity of the machine is
at E, for instance, then the armature copper is hotter than the
iron, while if rated at B, the reverse would be true. Obviously,
no rule can be formulated to cover these various conditions in
different machines, nor even in a given machine, unless all the
heat generation, distribution, and dissipation characteristics are
known. Obviously, as far as the insulation is concerned, the
temperatures of a and b are the only ones which need be consid-
ered.
All temperature determinations of a commercial nature, are
necessarily approximations, or relative indications, upon which
proper margins must be allowed for the ultimate temperature
possibly attained. Therefore, in apparatus where there are
liable to be discrepancies of 10 dcg. between the measurable and
the actual idtimate temperatures, a limit of 90 deg cent, should
be allowed by conventional temperature measurement on insu
lations in which 100 deg. is set as the maximum temperature with
a reasonable length of life.
The conventional methods of temperature measurement, as
by resistance, and by thermometer, do not usually give the maxi-
mum temperature, but give either the average, or the outside sur-
face, values, and, when measuring the temperature by these
methods, which are the only ones generally applicable, an allou -
ance must be made m windings for possible local higher
temperatures. These methods apply especially to those ma-
chines of moderate or low voltages in which the insulation is
relatively thin, so that the heat gradient from the inside copper
to the outside surface is small. Also, they apply particularly to
those machines m which the conditions of ventilation are not nor-
mally difficult, and in which a fairly thorough distribution and
dissipation of heat occurs among the various parts, such as in
ordinary direct-current armatures, induction motors primaries,
stators and rotors of moderate, speed alternators m which the
width is relativelv small compared with the diameter, etc
TEMPERATURE AND INSULATION 359
As the ultimate temperatures obtained by the apparatus de-
pend upon its rise above the room temperature, or that of the
cooling medium, and as such temperatures may vary over a wide
range, it is not practicable to specify or guarantee ultimate tem-
perature of apparatus without also specifying the. elements upon
which it depends This, therefore, results in specifying the
temperature rise in relation to that of the cooling medium.
While most apparatus operates at materially lower cooling
temperature than 35 deg. cent, to 40 deg cent,, yet such tem-
peratures are sometimes reached for considerable periods of time
in steam stations, and it appears therefore as justifiable to choose
the permissible temperature rise, such that, at room temperature
of 35 deg. cent, to 40 deg. cent , an ultimate temperature of 85
deg. cent to 90 deg. cent, by conventional methods of measure-
ment, is not exceeded This means, therefore, a temperature
rise of 50 deg. cent, with conventional methods of testing, such
as by increase of resistance, or by thermometer, in those insula-
tions which can stand a continuous ultimate temperature of
100 deg cent with a comparatively long life. This allows an
excess of 10 deg. cent, to 15 deg. cent, for local spots, or for the
temperature gradient through the insulation. A less allowance
should be made for this difference when methods of temperature
measurement other than the conventional are used, and which
approach more closely to the highest temperature actuallv at-
tained
When the above temperatures are liable to be materially
exceeded for long periods, heat-resisting insulation of class B is
recommended With such materials, a temperature of 125 deg.
cent is comparable with 85 deg cent to 90 deg. cent, in the
materials of class A Therefore, on this basis of a room tem-
perature at 40 deg cent or 45 deg cent., rises of 85 deg. cent or SO
deg cent should not be considered harmful However, in
those special cases where the conventional methods may not
sufficiently approximate local high temperatures, as may be
the case in large turbo-generators, or in wide core alterna-
tors of large capacity, the rises. of 80 deg cent, or 85 dc«
cent should not be specified by resistance or thermometer,
but preferably some lower temperature such as 50 deg cent
thus allowing a very considerable margin for local higher tem-
peratures In such apparatus with the higher temperature*,
which require class B insulation, there fe liable to be less uniform-
itv of heat distribution
360 ELECTRICAL ENGINEERING PAPERS
If special methods of temperature measurement, such as ex-
ploring coils or thermo-couples are used in such apparatus, the
temperature limit of 125 deg cent, should be considered, and not
the conventional 50 deg cent rise. In those machines of this
class which have relatively thick insulation, and consequently
may have a high heat gradient between the copper and the iron,,
(depending upon how much heat is flowing from the copper to-
the iron) an ultimate temperature of the inside insulation of
150 deg cent is considered as the limit, this being comparable
with 100 deg. cent with insulations of class A.
In certain classes of apparatus which are artificially cooled by
air from outside the room, the cooling is accomplished partly by
dissipating heat to the artificial air supply, and partly by dissi-
pation into the surrounding room. If the temperatures of the
cooling air and of the room are widely different, the resultant of
the two temperatures should really be taken as that of the cool-
ing medium.
The variation of the temperature rise has heretofore been
considered as having a definite relation to the temperature of the
cooling medium. However, it appears that it does not follow
any definite simple law, but it is sometimes positive and some-
times negative, so that no satisfactory correction for room tem-
perature is possible at present. It is therefore desirable to make
the temperature tests at a room, temperature as nearly as pos-
sibte to some specified reference temperature, so as to make any
temperature correction negligible The reference temperature
in the guarantees should therefore be such as Can easily be secured ;
that is, it should be the average temperature of the places at
which the apparatus may be operated This is from 20 deg.
:eiit to 25 deg. cent , and as it is easier to raise than to lower the
room temperature, the upper figure is advisable as a reference
i*alue. This 'reference temperature therefore should be chosen
is 25 deg cent., which is in accordance with the previous A I E E
standard.
MEASUREMENT OF TEMPERATURE
In the conventional methods of temperature measurement,
>y thermometer, and by resistance, many conditions should be
aken into account, and good judgment is required, in all cases,
>r fallacious conclusions may be obtained
There are many conditions which affect both the accuracy of
he resistance and the thermometer methods of measuring tern*
>eraturc The resistance method measures only the average
TEMPERATURE AND INSULATION 361
temperature rise, and not that of local hot spots. However, it
measures the internal temperature of windings, and therefore no
correction is required for the temperature gradient through the
outside insulation The proposed margin between the result
by the conventional method, and the actual temperature can
therefore be allowed, in the resistance measurement, as the dif-
ference between the warmer and the average temperatures m
the windings. In the resistance metho<J of measurements, the
rate of transfer of heat from one part of the winding to another
will not greatly affect the result, as the measurement indicates
an average temperature, which is that obtained if the heat were
equalized throughout the winding. However, the rate of flow
of heat from the windings through the outer insulation to other
parts, will affect the temperature measurement by resistance, and
preferably the measurement by this method should be taken
during operation in those parts where this is practicable, as in
field coils, and some other instances. In those parts where the
resistance cannot be measured during operation, this should be
done as quickly as possible after shut-down, and the time taken
to shut down the apparatus should not be unduly long. Prefer-
ably, during shut-down of rotating apparatus the normal current
should be maintained on the apparatus until at least a relatively
low speed is obtained. This would represent only an average
condition, as the ventilation at lower speed is very greatly de-
creased, while the losses in the windings will remain normal,
thus tending to give an increased temperature in the windings.
It would be difficult to fix any definite rule which would give the
exact temperature conditions during shut-down.
In the measurement of temperatui*e by thermometer, con-
siderable judgment is required Wherever possible, the tern- "
perature should be taken during operation, but the thermometer
with its pad should be so placed that it does not interfere with
'the normal air circulation. In thermometer readings, as usually
obtained on windings, the heat gradient thrdugh the insulation
must usually be allowed for, this being 10 deg. to 15 deg as
previously defined However, depending upon the method of
taking the temperatures, this allowance should vary over a con-
siderable range, depending upon whether or not the method of
measurement approximates the actual internal temperature
For instance, the total heat gradient from the inside copper to
the outside air will be that through the coil insulation, plus the
thick covering pad over the temperature bulb If the gradient
362 ELECTRICAL ENGINEERING PAPERS
through the covering pad is very large compared with that
through the insulation, the thermometer may indicate almost
exactly the internal temperature of the copper; that is, the heat
gradient through the insulation to the thermometer, may be rela-
tively small compared with the total gradient to the air. This
is particularly true where the thermometer rests on a metallic
seat which covers a considerable portion of the coil surface. In
this case, the heat which affects the thermometer bulb will pass
through a relatively large section of surface, with a correspond-
ingly small drop in temperature, so that the bulb more closely
approximates the temperature of the inside copper.
Where there is local heating in the windings, and a consequent
liability of rapid transference of heat to other parts, the results
obtained by the thermometer method will vary to some extent
with the rapidity with which the actual measurement is made;
that is, the more quickly the thermometer can be brought up to
the full temperature, the more accurately the temperature of
the hottest part is determined. With a very rapid method of
measurement, it may be possible to measure practically the in-
ternal temperature of the copper of the winding before any great
heat transference or dissipation has occurred. In such cases,
obviously, the full allowance for the usual temperature margin
should not hold. It should be fully understood that it is the
ultimate temperature, and not the temperature rise, which
should be considered as the limiting condition, and that the
measured rise, plus the allowances for temperature gradient,
plus the measured room temperature, is simply an indication of
the possible ultimate temperature. By whatever method the
temperature measurement is made, in all cases the results may
TDC considered as more or less approximate, and in the end, it is
the manufacturer who must supply the necessary margin over
the approximate measurement, in order to make the machine
safe.
A "blind adherence to some particular rule or method of taking
temperatures, may lead to fallacious results in some instances.
In armature windings, in particular, incorrect readings may be
obtained after shut-down. For example, if the armature iron
back of the armature teeth were hotter than the armature teeth
and coils during operation, then the temperature to which the
insulation is subject during operation may be considerably lower
than that in the hottest part of the machine, due to the ventila-
tion conditions when running. However, upon shut-down, the
TEMPERATURE AND INSULATION 363
temperature at the insulation may rise to that of the hottest
part of the machine, and therefore a false temperature, by any
method of measurement, might be indicated.
RECOMMENDATIONS
That with class A insulation, 90 deg. cent, be taken as the
ultimate temperature limit, as indicated by conventional methods
of measurement, or those which give similar results, and that
100 deg. cent, be considered as the maximum ultimate tempera-
ture permissible in the insulation, where a comparatively long
life is a requirement.
That 40 deg. cent, be taken as the limiting temperature of the
cooling medium, or room, and that, therefore, 50 deg. cent, be
the permissible rise by conventional methods of measurement,
with class A insulation.
That 25 deg. cent, be taken as tine reference air temperature.
With the permissible 50 deg. cent nse, this gives 75 deg. cent,
as the average operating condition, by conventional methods of
measurement, or 85 deg cent, actual temperature, when the
usual margin represented by the temperature gradient is added.
An exception to the rise of 50 deg. cent, can be made in those
cases where space or weight limitations are such that higher
temperatures, with consequent reduced life, are commercially
economical, such as in railway motors. In such cases, with class
A insulation , a nse of 65 deg. cent, with reference air at 25 deg
cent, is at present accepted as good practice.
With class B insulations, 125 deg cent be taken as the ultimat
temperature limit, as indicated by conventional methods of
measurement, or by equivalent methods, and 150 deg. cent, be
considered as the maximum ultimate temperature permissible
in the insulation It follows therefore that 80 deg cent, to 85
deg. cent, nse is allowable, with such insulations, by the usual
methods of measurement
No temperature correction should be made for variation of
the cooling temperatures from the reference temperature of 25
deg. cent
When the method of temperature measurement shows the
highest temperature actually obtained in the insulation, the maxi-
mum temperatures specified for the given type of insulation
should hold.
In the final "decision on questions of temperature rise, the ulti-
mate temperature should be the basis, rather than the rise.
TEMPERATURE DISTRIBUTION IN ELECTRICAL
MACHINERY
FOREWORD — This paper was presented at the Chicago Section meet-
ing of the American Institute of Electrical Engineers, November
27, 1916. A number of papers by the author dealing with the
temperature problem had appeared tbef ore, but the purpose of
this paper was to put the subject in more definite shape and
bring it more nearly up to date. During the discussion of the
paper, considerable new data was presented by the author, and
it has, therefore, been included in this reprint.
This paper was listed for a second presentation before a
regular meeting of the Institute at Schenectady in April, 1917,
with a view to obtaining a further discussion, particularly by
engineers on design work. This meeting was cancelled due to
the declaration of war. — (ED.)
THE laws governing heat flow and temperature distribution
are so similar, in many respects, to those governing electric
current flow and electric potentials, that it is rather surprising
that the former have received so little attention in comparison
with the latter. Some of the laws of heat flow are so well recog-
nized that their application to the problem of temperature dis-
tribution in electric apparatus should have been a leading feature
in the early developments in such apparatus; whereas, on the
contrary, it is only recently that very careful study has been,
made of such application.
One object of this paper is to indicate, in a comparatively
simple manner, some of the conditions which fix the tempera-
tures in different parts of electric apparatus. The explanations
given cannot be considered as new or novel in substance, but are
merely the application of fairly well known principles of temperature
and heat flow to electrical machinery. Before going into the general
problem, certain simple conditions may be stated, such as:
1. The heat flow between two points is proportional to their
temperature difference and to the heat resistance of the path or
paths between .them. Note the resemblance to Ohm's law.
As a corollary to the above, it should be evident that between
365
366 ELECTRICAL ENGINEERING PAPERS
two points at the same temperature, there should be no flow of
heat.
2. The total temperature drop between any two points or
media of different temperatures will be the same through all
paths of heat flow.
3. There are no true non-conductors of heat, and, conversely,
no perfect conductors •
4 Heat conduction and electric conduction bear some quan-
titative relation to each other, in the broad sense that all electric
insulators are relatively poor heat conductors, while good electric
conductors are correspondingly good heat conductors. There
is apparently no rigid relation between the heat resistance and
electric resistance of the various materials used in electric ma-
chinery, but the general relation holds and there are apparently
no radical exceptions
5 The rise in temperature at any point, due to generation
of heat, is dependent (a) upon the total heat generated, and (b)
upon the amount of heat which can be earned away along all
available paths per decree of temperature difference. The tem-
perature will rise until the heat dissipation equals the heat
generation
6 There are two ways to lessen the heat flow along any path,
(a) By interposing higher heat resisting materials, (b) By
lessening the temperature difference, as by raising the tempera-
ture of the part through which the heat is to be conducted.
Conversely, the heat flow can be increased along any path by
the use of better heat conducting materials, or by paths of lower
heat resistance, and by lessening the temperature of any part
to which the heat is to flow.
What makes the problem unduly complicated, in electrical
machinery, is the fact that there are several different sources
of heat generation, which may be, and often are, all active at
the same time. Moreover, the heat losses may be distributed
through the various heat conducting paths in such a way as to
render any calculation very difficult and more or, less inexact,
except in a general way. For example, there is heat generated
by losses in the copper conductors, obeying one law; while there
is heat generated in the iron parts under a quite different law,
and there may be heat generated by windage and friction,
according to a third law. As these different losses may act in
different parts of the heat conducting circuit, it should be evident
that the problem of determining the exact heat distributions,
TEMPERATURE DISTRIBUTION
367
and the temperature, is a very complex one. Such a determina-
tion is in the province of the expert analytical designer of such
apparatus, but certain general conditions are of interest to all
users of electric apparatus.
Consider first the general conditions of heat dissipation from
an armature coil In Fig. 1 is represented an armature slot with
the surrounding iron, and with two separate "coils" per slot, as.
is now the most common practise. Let it be assumed that the
point a represents the "hot spot", or part at highest temperature-
in the apparatus. The heat from this part can flow along two
general paths, namely, longitudinally through the copper" con-
ductor itself to the end windings, and thence to the air, and.
laterally through the insulation to the surrounding iron, or to
the ventilating ducts. From the iron the heat flow is then
through various paths to the external cooling air.
LONGITUDINAL HEAT FLOW
Considering first the longitudinal conduction of heat in the
coil, then starting at the point a, the first unit of length con-
ductor will have a certain loss. If the heat generated by this
first unit loss were all that need be considered, then the drop in
temperature, from the point a to the end windings, would be
simply a function of the heat-conducting properties of the con-
ductor itself. But the next unit length is also generating its
368 ELECTRICAL ENGINEERING PAPERS
own unit loss, so that the heat flow from the second to the third
unit length is due to two units loss; in the same way, the flow-
to the fourth unit length will be due to three units loss, etc
Therefore, the temperature drop, or temperature difference per
unit length of conductor, increases more rapidly as the point a
is departed from, and if it is at a considerable distance from
the end winding, and the losses per unit length are compara-
tively high, a very high temperature may be required at a to
conduct all the heat longitudinally to the end windings, In
very wide core machines the longitudinal drop may be so great
that the temperature at a in practise will be so far above that
of the surrounding iron, that a very large percentage of the
actual heat is conducted laterally through the insulation to the
iron, even if the iron is at a comparatively high temperature,
However, in narrow cores, the drop to the end windings may"
be, in some cases, so very low, possibly 5 to 10 degrees, that
with good heat dissipation from the end windings themselves,
the point a may have, for instance, an actual temperature of
40 deg. cent. If the iron next to a a'so has a temperature of 40 deg.
cent, then there would be no flow of heat from a to the iron. Fxtr-
thermore, in such a case, as the iron temperature over the whole
width of the core may be lairly uniform, and as the copper
temperature decreases from a to the end windings, obviously
as we 'depart from the point a, there would be heat flow from
the iron to the copper, and thus the windings would tend to
cool the core. This is frequently., the case with light loads on
a machine, for in sucji conditions the coil loss is low, while the
iron loss remains fairly constant for all loads In such case
there may be heat flow from the iron to the copper along the
whole length of the buried portion of the coil At some higher
load, the copper loss varying as the square of the load, the in-
creased longitudinal drop will bring the copper temperature
above that of the iron so that the heat flow is from copper to-
iron, This condition is illustrated by Fig 2
It must be recognized that the lateral flow of heat, from the
coil to the iron, reduces the longitudinal drop, such reduction
depending upon the relative percentages of Jieat flow along the
t\\o paths ^ It must also be borne in mind that in order to have
such longitudinal heat flow, the end windings must be able to
dissipate their own heat at lower temperature than would b^
attained at a, or in the core If the end windings have little or
no ventilation, or heat dissipating capacity, then their own
TEMPERATURE DISTRIBUTION
369
generated heat may bring their temperatures higher than those
of the armature iron so that the heat flow actually may be from
the end windings toward a, and then laterally through the in-
sulation to the core In such case, the hottest spot will be in
the end winding rather than in the buried part of the coil Obvi-
ously when such condition occurs there is no possibility of either
the end windings or the buried part of the coil being cooler than
the iron, for the heat flow throughout is toward the iron
LATERAL HEAT FLOW
Considering next the lateral flow of heat through the insulation
to the iron, the amount of heat conducted is a function of the
temperature difference and the
resistance of the conducting
path. Or, in other words, if a
given amount of heat is to be
conducted through a path of
given resistance, the tempera-
ture in the heat generating part
iron Temp's will rise until the required heat
copper Temp's. is conducted away
Light Load
Iron Temp's
Copper Temp s.
Medium Load
Heavy Load
•Width olCore*
Copper Temp s
Iron Temp's.
^30°C Drop
" — 70«C -4CTC Rise .
in Iron with Air at 30*0"
FIG. 2
FIG. 3
To illustrate this problem more concretely, let Fig. 3 represent
the temperature conditions in a section of an armature Assum-
ing, for example, the temperature of the copper inside the coil
insulation as 100 deg cent., the iron temperature as 70 deg.
cent. , and the air temperature as 30 deg cenfy , then the following
-conclusions may be drawn.
(a) From the outer coil (the one next to the air gap) through
the wedge to the air gap, the temperature drop will be 100 —
30 = 70 deg. cent. Obviously, any temperature measurement
made outside the wedge, next to the air, will approximate the
370 ELECTRICAL ENGINEERING PAPERS
>
temperature of the air and not of the copper Any temperature
measurement made beneath the supporting wedge will measure
some intermediate temperature between the copper and the air
If the temperature drop through the wedge should be equal to
that through the insulation, then a measurement underneath
the wedge should show half the temperature drop through in-
sulation and wedge, and obviously, the measured temperature
would be far below that of the copper.
(b) If the temperature is measured at the outside of the coil,
between the iron and the insulation, it would approximate the
average of the temperatures of the iron and of the outside
.insulation, or practically the temperature of the iron If the
iron should be at different temperatures at the sides of the slot
and at the bottom, then obviously different readings would be
obtained, depending upon the location of the measuring device.
It is evident that such temperature measurements give no in-
dication whatever as to the true internal temperatures of the
coil, for the heat flow and the resistance of the insulation are
nowise involved in the measurement.
(c) At a point a, between the two coils, there should be but
little heat flow through the insulation, unless the copper is
comparatively narrow. If there is but little heat flow through
the insulation at this point, then eventually the temperature at
the point a must rise to approximately that of the copper in the
two coils. Therefore, a measuring device located at a will
approximate the temperature of the copper itself, and is, in
general, a good indication of the h&t spot at that part of the
winding Therefore, as a practical method of temperature
determination, a thermo-couple located at a is about the most
satisfactory device that we have. However, the location of the
point a along the slot is also of importance on account of the
longitudinal flow of heat in the conductor and the consequent
temperature drop In other words, the direction of heat flow
in the coil itself, musl be taken into account Therefore, £
thermo-couple located as above, is only satisfactory when the
general location of the hot spot is known beforehand This is
usually determined, in a general way, for a given type or line
of machines, by locating several thermo-couples along the slots
With narrow slots and comparatively thin conductors, and
especially with very heavy insulation, there is some flow of heat
through the insulation which lies between the two coils, this
heat passing out sidewise to the iron In such case, the point a
TEMPERATURE DISTRIBUTION 371
may be of somewhat lower temperature than the copper. It
may happen also, in some cases, that, due to unequal losses and
heating of the two coils in the same slot, one is at a higher tem-
perature than the other In such case, due to the heat flow
between the coils, the temperature indication at a will not show
better than an average of the two temperatures Furthermore,
if the temperature at c , in a coil subdivided into many insulated
conductors, is materially higher than at by then the temperature
indication at a may not be a close approximation to the maximum
temperature
PLOW THROUGH IRON PARTS
In the ordinary armature, after the heat passes from the
copper to the iron, there is still quite a problem involved m the
dissipation to the surrounding medium, which is usually the air
The direction of the heat flow to the iron will depend, to a con-
siderable extent, upon the arrangement and location of the heat
dissipating surfaces There are two general paths of heat con-
duction in all armature cores; namely, a flow along the lamina-
tions to where their edges come in contact with the air or with
other material, and a flow across the laminations toward heat
dissipating surfaces The flow along the laminations may be
calculated with fair accuracy. Across them it is difficult to
determine such flow, largely because the laminations are in-
sulated from each other by materials which are poor conductors
of heat Also such flow is affected not only by the insulation
between laminations, but by the perfection of contact In other
words, the heat flow may be affected by pressure. According
to the various figures available, the heat flow per unit volume
of material along the laminations is from ten to one hundred
times as great, for a given temperature difference, as across
them Obviously, therefore, heat dissipation from the iron by
flow across the laminations should be considered relatively in-
efficient, yet in the vast majority of rotating machines the heat
dissipation is largely across the laminations. The reason for
this is that by placing ventilating passages or ducts, parallel with
the laminations, at frequent intervals in the core, the cross
section of the heat path in the intervening iron sections, may
be made very large compared with the heat to be dissipated,
so that the density of flow is very low By the same procedure
the length of the heat path is made quite short Thus in practice,
the temperature drop through the laminations themselves may
be made relatively small compared with other drops However,
£72 ELECTRICAL ENGINEERING PAPERS
not all the heat in the iron passes across the laminations to the
ventilating ducts, for where the length of the path, along the
laminations to any heat dissipating surface, is not large, a very
considerable amount of the heat may be dissipated from the
edges of the laminations themselves. In fact, in certain types
of machines with very shallow iron cores, experience has shown
that the ventilating ducts, parallel with the laminations, may be
omitted, provided good ventilation is obtained over the edges
of the laminations. It is evident, therefore, that the flow of heat
and distribution of temperature are dependent upon the arrange-
ment of the iron, dimensions and location of the ventilating
surfaces etc.
HEAT FLOW TO THE AIR
After the heat has passed from the copper to the iron, the
resultant of the copper and iron heats must be conducted to the
cooling medium, which is usually the surrounding air In the
case of air, there is usually a considerable drop in temperature
from the solid surface to the cooling air itself, the amount of
such drop depending upon the ventilating conditions. In prac-
tise, there appears to be a film or layer of air which adheres very
closely to the solid surfaces. This forms a sort of heat insulating
film, retarding the flow of heat to the cooling air In air ven-
tilation, the effect of any considerable air movement over the
surface appears to be that of scouring this hot film away from
the surface and replacing it with a film of cooler air Merely
scouring or rubbing the hot film away from the surface is not
particularly advantageous unless some means is furnished at
the same time for supplying an ample quantity of cooler air to
take the place of the removed hot film. Rapid air circulation,
by means of a supply of air from the outside, appears to accom-
plish both results in one operation. Thus, one of the principal
actions of air ventilation appears to be that of scouring away the
hot contact film, while a second action is to carry the hot air
away without mixing it with the incoming cooler air Whatever
portion of the dissipated heat is absorbed by the incoming cool-
ing air adds that much to the temperature of the air itself and
eventually to that of the apparatus to be cooled. Thus mixing
the outgoing with the incoming air makes a sort of Siemens*
regenerative furnace and the machine bocomes cumulatively
hottert and hotter until the dissipation through other paths be-
comes equal to the heat generated. In such cases the ventilation
TEMPERATURE DISTRIBUTION 373
of the machine may only be useful in equalizing or redistributing
the temperatures in the various parts.
From the preceding analysis, it would appear that the tempera-
ture at the hottest part of the coil is fixed principally by the heat
flow through the copper, and its surrounding insulation, directly
to the air, and by the flow from the copper to the iron, and from
the iron to any exposed air surfaces, and then to the air. Along
the first path, there are three principal temperature drops,
namely, in the copper itself, then through the insulation, and
then from the outside surface of the insulation to the air. Along
the second path, there are also three temperature drops; namely,
from the copper through the insulation to the iron, then from
the iron to the exposed air surfaces, and then from the surfaces
to the air. Along the first path each part of the copper path is
generating its own heat, to be conducted away, in addition to
that which is to be conducted from other parts of the path. In
the second path, each part of the iron path may be generating
its own heat, which adds to that coming from other parts.
The relative amount of heat conducted along each path is de-
pendent upon so many conditions, which vary with the load,
that no one but an analytical designer backed by experience
could even approximate the values by calculation. However,
it should be obvious that any measuring device applied to the
outside or cooling surface does not, and cannot, directly approxi-
mate the temperature of the hottest part, except in those rare
cases where the hottest part is dissipating heat directly to the
air. This is true only in very special cases such as series coils
of bare strap, etc. In any coil or part of the apparatus which is
heavily insulated, that is, which is covered by poor heat conduct-
ing materials, an external temperature measurement is an ex-
tremely poor indication of the true internal temperature, unless
many other conditions are known which may give an indication
of the internal temperature drops- In different types and con-
structions of rotating apparatus, hot spots may hold quite
different relative positions with respect to the cores and wind-
ings, so that no reasonable rule can be made to cover all cases.
Moreover, in some classes of apparatus, it is not practicable to
make any temperature roeasurements until after the apparatus
is shut down, and this introduces otter very important errors
which should be considered, such as cooling effects as a whole,
during the period of shut-down, equalization of temperature
due to internal condttction, etc.
374 ELECTRICAL ENGINEERING PAPERS
EQUALIZATION OF TEMPERATURE, "E'TC.
When there are hot spots, or zones, or areas, of different tem-
peratures, in an armature winding, for instance, such difference
in temperature is maintained by the continual generation of
heat in the various parts But the moment that such generation
of heat is stopped there is immediately a tendency for equaliza-
tion of temperatures by flow of the stored heat from the hotter
parts to the cooler. In good heat conducting materials, as copper,
such equalization may be very rapid, so that a temperature
indicating instrument of a sluggish type may not indicate any-
thing like the true maximum temperature of the spot where it
is placed, if applied after the load is removed, especially if the
rate of heating of the thermometer bulb is much less than the
rate of heat transfer from one part of the winding to another
If located on a hot spot, the reading may nse to some interme-
diate value and then drop off as the hot spot cools by heat con-
duction to other parts. If located upon a cool spot, it may rise
slowly for a considerable period, due partly to sluggishness of
the thermometer and partly to the cool spot rising in temperature
by conduction of heat from some other part. The conditions
are so varied that no reliable conclusions can be drawn, from the
action of the "thermometer alone, in regard to the coolest or
hottest spot,
A second condition which tends to make such temperature
measurements fallacious, lies in the cooling action in the interval
between load removal and shut-down to take temperature
measurements In apparatus which depends upon a high degree
of artificial cooling, such cooling effect may be very considerable.
This is particularly true of high speed machines which require
considerable time to come to a standstill. It is, therefore, de-
sirable m such machines to obtain all possible temperature read-
ings at normal speed and with load In rotating field machines,
this is, to a certain extent, practicable, but in most rotating
armature machines, the armature temperatures usually are not
attainable until the machine is brought to a standstill, and even
then some error may result from sluggishness or delay in taking
the readings. One method which has been proposed at times,
for lessening the sluggishness, is to heat the thermometers up to
practically the normal operating temperature of the part to be
measured, while the machine is still carrying load. At the moment
of shut-down the heated thermometer is applied. This, to a
certain extent, removes the factor of sluggishness in the ther-
TEMPERATURE DISTRIBUTION 375
mometer itself, but is only a partial compensation It must be
considered that the outside of the insulation is at lower tempera-
ture than the inside, and that, therefore, the body of the insula-
tion itself must ha^e its temperature increased by flow of heat
from other parts.
FALLACIES IN TEMPERATURE GUARANTEES AND MEASUREMENTS
In the older methods of determining temperatures, it was
assumed that the thermometer readings, obtained on a winding,
for instance, was a true indication of the temperature of the
winding as a whole The manufacturers of electrical apparatus
long ago recognized the fallacy of this method, as they had found
from bitter experience that there were liable to be hotter parts
in the machine than any thermometer readings would indicate.
They, therefore, designed machines with regard to the possible
hot spot temperatures as encountered in service, rather than
any temperature which the exposed parts of the machine would
show Thus in designing a certain machine for safety at the
hottest part, not infrequently the exposed parts- of the winding
would show, by thermometer, comparatively low temperatures,
such as 25 cleg, to 33 deg cent, rise. Therefore, as the observable
temperature readings came so low it became the fashion to call
for 35 deg. cent guarantees and, in many cases, the operating
public lost sight of, or perhaps never knew, the real meaning of
such low temperatures. Among the designers of electrical
machinery, it was recognized that a temperature rise of 35 deg.
cent in itself was absurdly low, but that the object in operating
at such low temperature on a part which could be measured was
simply to protect the machine in some inaccessible hotter part,
where the temperature could not be measured. From the present
viewpoint, it is astonishing what reliance has been placed upon
temperature readings in the past. For example, if a 40 deg.
cent machine showed 41 5 deg cent rise on test, it was unsafe,
while if "it showed 38.5 deg. cent, rise, it was good. We now
recognize that neither of these temperatures have any controlling
value, unless many other conditions are known To the ex-
perienced man they simply mean that compared with the other
machines of similar constructions and characteristics, which have
proved satisfactory in service, they are reasonably safe. To the
designer they mean that when proper corrections have been
made for the various internal temperature drops, the highest
temperature attained, at any point; Vill be within the limits of
376 ELECTRICAL ENGINEERING PAPERS
durability of the insulating material used. The whole problem
is a good deal like that of a determination of the voltage generated
in a given power-house, by measuring the voltage at the end of
a transmission-line. If we know all the constants of the line,
and know the current flowing, etc., we can figure back to the
generated voltage. Otherwise the voltage at the end of the line
means but little. However, we know that if the system is de-
signed with reasonable regard to economy in general, there may
be from ten to twenty per cent, voltage drop from power-house
to the end of the line. Therefore, by adding an approximate
correcting factor to this voltage, we can make a reasonable
estimate of the generated voltage. In the same way in electrical
apparatus of certain types, a reasonable internal temperature
drop may be approximated, which added to the observable tem-
perature, gives a fair approximation to the hottest part, but
the result is an approximation and must be recognized as suck.
Primarily, the manufacturer must make a safe machine for a
specified service regardless of the temperature guarantees, and
the temperature measurements made on most classes of apparatus
should be considered simply as rough approximations to indicate
that the manufacturer has made a reasonable attempt at a safe
machine. This may seem a rather bald statement, but never-
theless it is a fair statement of the case.
*
ERRORS IN TEMPERATURE MEASUREMENT
It has been shown in the preceding that the usual observable
temperatures are in most cases only crude approximations to
the real temperature conditions. It may now be shown that
even the observable temperatures, obtained by the usual means,
are in themselves only crude approximations in many cases.
Take, for instance, the determination of temperature by in-
crease in resistance; when the coil is heated its temperature may
not be, and very frequently is not nrnforrn throughout the coil.
As an extreme example, if one-fifth of the coil length has a tern
perature of 80 deg. cent., while four-fifths of it has a rise, of
30 deg. cent-, then the increase in resistance of the coil as a whole
will correspond to a rise of 40 deg. cent. Thus, by increase of
resistance, the temperature may be more than safe, while
actually one-fifth of the coil is far above the safe temperature
for ordinary fibrous insulations. In other words, the resistance
method gives only average results and may be very misleading.
However, in those cases where it is known, by past experience
TEMPERATURE DISTRIB UTION 377
and otherwise, that there is very little liability of hot-spots, the
resistance method of determining temperature is often quite
satisfactory However, the method is limited to comparatively
few types of windings.
Considering next the thermometer method of measurement,
the theory of this is quite simple, but apparently it has been very
much misunderstood. In windings, except in rare cases, the
thermometer is not applied directly to the heat generating
material itself, but is applied outside of an insulating covering
Usually the temperature drop through this insulating covering
does not receive any consideration, and yet everything depends
upon this. Assume, for example, an insulated coil, thermometer
and covering pad, as shpwn in Fig. 4, Assuming the copper
inside the coil as being of uniform temperature, and the cooling
air at a ajid b as also at a uniform, but much lower, temperature
than, inside the coil ; then the temperature drop from the copper
to & will be the same as through the insulation, thermometer
FIG. 4
bulb and covering pad to the air at a. Obviously if the tempera-
ture drops through the insulation and through the pad are equal,,
then the thermometer bulb will show a midway temperature.
This is, of course, assuming that the surface drop to the air,
previously referred to, is very small, or that it is included as part
of the drop through the pad- Obviously, if the drop through the
covering pad is made very much higher than that through the
insulation proper, then the thermometer bulb more closely
approaches the copper temperature. Thus it is seen that all
kinds of results may be obtained, depending upon the relative
drops through the pad and through the insulation. In a low
voltage machine, with relatively thm insulation, the p,ad may
take most of the drop. With very heavy insulation, the pad may
take proportionately less and the thermometer reading departs
accordingly from the copper temperature. It might be sug-
gested that a big thick pad of very poor heat conducting material
might be used. This apparently would tend toward more ac-
378 ELECTRICAL ENGINEERING PAPERS
curate temperature readings, but, on the other hand, harmful
effects may be introduced by the use of a large pad. The resis-
tance to heat dissipation being increased in the area covered by
the pad, obviously less heat will be carried away at this point
and, therefore, the heat generated under the pad must be con-
ducted to adjacent parts of the coil. This means an increased
temperature at this point, due to the use of the pad. Again, the
use of the pad, in some cases, may affect the normal ventilation
of certain parts of the coil not directly covered by the pad. For
instance, if there is a ventilating space between two adjacent
armature coils, through which air is normally driven, a pad which
covers this space even partially may create more or less of an air
pocket, and thus materially affect the heat dissipation, and the
temperature directly under the pad. Experience has shown that
both of the above conditions are obtained when good judgment
is not used in the application of the covering pad. This, of course,
applies particularly to those cases where temperature readings
are obtained while the machine is in operation. Of course, after
shut-down, most questions of ventilation and of generation of
higher temperature under the pad need not be taken into account.
There are so many conditions entering into the interpretation
of the thermometer and resistance methods of determining
temperature, that in certain classes of apparatus it has been
very desirable to find more accurate methods. One of these
is in the use of so called resistance coils. In this method a coil
of fine wire of a known temperature co-efficient, and of known
resistance at a given temperature, is placed at the place where
the temperature is to be measured, and the temperature rise is
determined from the increased resistance of the coil One serious
objection to this arrangement, is that the resistance coil must
have considerable length and breadth so that it really indicates
the average temperature of a considerable area instead of a point.
When placed between two coils, as indicated in Fig. 5, it usually
occupies so great a proportion of the slot that it indicates an
average temperature considerably lower than at a Furthermore,
on account of the length of such coils, there may be a consider-
able difference between the temperatures at the two ends Thus
the resistance coil, like the resistance measurement of the wind-
ings themselves, gives an average result, but this average ma\
be limited to a comparatively small area, whereas, in the resist-
ance method in general the indicated rise is an average of the
whole winding. However, in 'the resistance method, the tern-
TEMPERATURE. DISTRIBUTION
379
perature of the conductors themselves is measured, whereas,
with the resistance coil the temperature measurement is outside
the insulation The resistance coil method is, therefore, a rel-
ativ^ly crude approximation, although when brought out it was
really an important step in advance In, its early application,
many misleading results were obtained, due largely to lack of
understanding of the principles governing temperature distribu-
tion and temperature drop, In some cases, the resistance coil
was placed under the wedge as at b in Fig 5 In other cases,
the coil was placed at the side of the slot next to the iron, or at
the bottom* Very rarely was it placed midway between the two
coils, probably because this was a more difficult application and
u
\
Resistance Coil
r"ft"^: Resistance
Coil
FIG 5
also because the greater accuracy of such location was not rec-
ognized From the use of resistance coils many good engineers
drew the conclusions that the upper limit of permissible tempera-
ture for fibrous insulations was only 80 deg to 90 deg cent ,
because with the coils located in certain ways and places, de-
terioration of insulation at some other point was liable to begin,
if the above temperatures were exceeded The error was in not
recognizing the temperature drop between some hotter spot and
the average location of the resistance coil When this condition
• was recognized the results obtained by resistance coils became
more consistent with the facts
A later development than the resistance coil is the thermo-
couple as a practical device for measuring temperature One
3SO ELECTRICAL ENGINEERING PAPERS
great advantage of the thermo-couple is its very small size, so
that it can indicate the temperature at practically a point instead
of a very considerable area Moreover, as it is a zero current
method of measurement, when used with a potentiometer no
question of size or length of the connecting leads need corne up
The thermo-couple is so small and has so little mass, that it can
follow very quickly any temperature changes where it is located
If properly placed it furnishes the most accurate temperature
indicator which we now have, as it can be located in all sorts of
normally inaccessible places However, its use is practically
limited to stationary apparatus, In rotating apparatus, or
rotating parts it can be used only after shut-down, which intro-
duces errors, as already shown.
MANY-CONDUCTOR COILS
In all the preceding considerations it has been assumed that
the copper inside the coils itself is at a uniform temperature, m
any given unit of length. This is practically true, provided the
coil is made up of a single conductor, or of a relatively few con-
ductors with only a moderate amount of insulation between them
When several coils or conductors are placed side by side, as in
Pig. 6, it would appear at first glance that the middle coils should
heat much more than the outer ones But, in reality, unless
there are many layers of coils, the temperatures of the different
coils will not vary greatly from each other For instance, in
Pig. 6, the 'heat generated in the middle conductor is only 'one-
third that of the total generated in the coil, and yet the two
side surfaces through which this heat passes to the adjacent coils
aggregate almost as much as the total outside dissipating surface
of the whole coil, through which. all the lateral heat flow is dis-
sipated. Considering further that the insulation between the
middle coil and its neighbors is relatively thin compared with
the outside covering, it is obvious that the temperature drop
from this coil to the adjacent ones will be comparatively small,—-
possibly not over ten per cent of the drop through the outside
insulation
However, with a large number of coils side by side, the condi-
tions become cumulatively worse. Here, the drop from the
center conductor to the next one, may be small But the 'drop
from the second conductor to the third is considerably greater
due to the heat of two conductors being transmitted. Prom the
third to the fourth thefe is a drop corresponding to the losses
TEMPERATURE DISTRIBUTION
381
of three conductors, etc Thus, there is a gradually increasing
temperature drop from the center of the coil toward the outside
surface, and if the coil be very deep, that is, if it consists of many
insulated layers, the sum total of the drops may be quite large
Or, putting it in another way, with a comparatively deep coil,
the temperature rise from the outside surface of the coil itself
toward the center will be very rapid at first, and gradually taper
off, as indicated in Pig. 7. This is indicated very clearly m the
case of an over-heated field of coil of fine wire. Here the first
outside layers will usually be found in a fairly good condition,
but at a comparatively little distance inside the coil there may
be severe roasting or evidence of overheating, which may be
FIG. 6
•Temp at Center
N— Temp at Edge
FIG. 8
1
FIG. 7
almost as bad as at the center. (See Pig. 8.) In such case, the
temperature measurement on the outside of the coil is no satis-
factory indication of the hot-spot temperature A temperature
measurement by resistance, while a closer indication than that
by thermometer, also may be very misleading It may be stated
that modern design tendencies are toward comparatively shallow
field coils, largely on account of this condition
CONCLUSION
The whole object of this paper is to show the problem of tem-
perature distribution and temperature measurement, as it
actually is. It is the writer's desire to show that no hard and fast
rules can be made for determining the facts in the case, and that
382 ELECTRICAL ENGINEERING PAPERS
the best rules and methods now practicable are only approximate.
The present limitations set for insulating materials are much
higher than were considered practicable only a few years ago.
This is not because the limits have been raised, but because,
through a better understanding of the facts, the real upper
limits of temperature as fixed by durability of insulation, are
now known to be considerably higher than was believed to be
the case only a short time ago If the real limits were in accord-
ance with former beliefs, then all the evidence of the more accu-
rate modern tests and data would indicate that the vast majority
of the existing electrical machines should have "roasted out"
comparatively early in their operation The higher temperature
limits were there, but were not recognized Now we recognize
them and attempt to make reasonable allowances for differences
between the measurable temperatures *and the actual hottest
parts. The present method may be crude, but we are not going
at it blindly, as was formerly the case. Formerly the manu-
facturer took the real responsibility for making a machine that
was safe for the service, whatever the guarantees called for.
Today the responsibility is still his, but he is attempting to
educate the public to a knowledge of his real problems, and to a
recognition that temperature determination is far from being
an exact art. There is no sharply defined line between good, and
bad in the insulating materials as affected by temperature, con-
sequently there is no sharp line between safe and unsafe
temperatures.
ABSTRACT PROM DISCUSSION
I have made tip a sketch which brings out much better than
any description, some of the fundamental differences between
Class "A" and Class "B " insulations. These might be called the "
time-temperature curves for these insulations. These must be
considered as approximations only, as, from the very nature of the
materials themselves, no exact curves are possible. The important
feature to be considered in the curves, is the general shape rather
than any absolute values.
We have made a great many temperature tests of insulations
to determine their durability; also we have made examinations of
a very large number of windings which have been in service for
many years, but for which we had only approximate data as to
temperatures. Obviously it is impracticable to carry on an ac-
curate life test covering a long period of years, so what we did in
TEMPERATURE DISTRIBUTION 383
most of our tests, was to carry the temperatures up to such
points that destruction was either reached or indicated in a
comparatively limited period of time.
Curve A indicates approximately the durability of class A
insulations for various temperatures This should be recognized
as being approximate, but it is optimistic rather than pessimistic.
Curve B applies to well built class B insulations, as now fur-
nished by some of the electrical manufacturing companies.
Such insulations contain a large percentage of heat resisting
materials with a comparatively small percent of binding material
and the insulation is applied so tightly that deterioration or de-
struction of the binder does not appreciably loosen up the true
insulating material
Considering curve A, taking 105 deg. cent., as the ultimate
temperature limit for long life without undue deterioration, then
with a very slight increase in temperature, say to 115 deg. cent.,
the life is shortened very much, and at 125 deg. cent, such in-
sulation is good for only a very few months at the most. At
150 deg. cent, it has an exceedingly short life.
Next considering curve B, our available data indicate that for
over twelve months operation at 200 deg. cent., the insulation is
in first class shape; in fact, much better than class A insulation
at 110 deg. cent., for the same length of time. At 300 deg.
cent, for six months, the insulation really shows better than class
A insulation at 115 deg. cent, for the same length of time, and,
at 400 deg. cent., the class B insulation for three months is better
than class A insulation at 125 deg. cent, for the same length
of time. If we now assume the continuous life for the class B
insulation as 150 deg. cent., then it is seen that a 33 percent
increase in temperature for one year is no more harmful than a
5 percent increase in temperature over the 105 deg. cent, for
class A insulations for one year. Also a 100 percent increase in
temperature above its continuoiis limit for six months is com-
384 ELECTRICAL ENGINEERING PAPERS
parable with a 10 per cent increase in temperature for class A
insulation for the same period. For still higher temperatures
the percentage is far more in favor of class B.
What I want to bring out in particular by means of this dia-
gram, is that the factor of safety for overloads is vastly greater
for class B than for class A insulations, on the basis of continu-
ous life being taken as ISO deg. cent, and 105 deg. cent., respec-
tively. Part of this difference is inherently in the characteris-
tics of the materials themselves, but no doubt part of it is due
to the fact that the arbitrary ISO deg. cent, limit set for properly
built class B materials is considerably too low in comparison
with 105 deg. cent, for class A. But, whatever the explanation,
the difference is there.
In regard to the very high temperatures for class B insulations,
such as 300 deg. and 400 deg. cent, shown in curve B, attention
should be called to the fact that unless there is an exceedingly
high temperature drop through the insulation itself, any outside
supporting layer or wrapper of fibrous materials is liable to be-
come unduly heated and may disintegrate. Therefore, while the
insulation proper might stand 400 deg. cent., for instance, yet if
this was continued for any considerable length of time, so that
the outside supporting material became excessively heated, such
material would have to be of something else than the usual treated
tape or fibrous wrappers. However, it so happens that very
high temperatures are rarely attained in practice, except in the
case of armature conductors buried in slots. In such case the
surrounding iron assists very materially in cooling the finishing
wrapper on the coils, unless the high temperature is maintained
for a very considerable period.
Some are inclined to look askance at mica at 150 deg. to 200
deg. cent., but it must be remembered that in certain heating
apparatus mica is used up to 500 deg. cent, and, in some cases,
even up to 750 deg. cent. Practically all micas will stand up
to about 600 deg. cent , without undue deterioration, and some
grades will stand up to 1000 deg cent. From this viewpoint,
the temperature of 150 deg. to 200 deg. cent, in armature coils
appears to be very low and the whole matter turns upon the way
such mica is used. If the percentage of mica in the insulation is
relatively high and the mica is put on so tightly that the binding
material can disintegrate and loosen up and yet the natural elas-
ticity or springiness of the mica can hold the insulation tightly in
TEMPERATURE DISTRIBUTION 385
place, then such insulation can stand very high temperature with-*
out injury. But, if the mica is wound or placed so loosely that this
disintegration of the binding or supporting material allows the mica,
part to loosen up materially, then the insulation qualities may still
be very good from the dielectric standpoint, but may be in such
poor shape mechanically that vibration or shocks may shift it
or displace it sufficiently to injure it as an insulator. This de-
fect is a mechanical one and not in the quality of the material itself.
Mr. Junkersfeld has spoken of some of his early experiences
with high temperature, and he mentioned that the data which
he and his associates obtained have had a marked nfluence in
leading the manufacturers toward better grades of insulation.
This is no doubt correct, but I wish to call attention to the fact
that the manufacturers were also following this matter inde-
pendently of the operating companies, with the same end in
view. For instance, the company with which I am associated,
insulated the 1894 Niagara generators with mica. We did not
know whether such insulation was required, but we thought t
was good material and so put it on. Later tests showed that
this was a very fortunate decision, and now7 after twenty years
of operation, this insulation is still in very good shape, although
subjected to very much higher temperatures than originally con-
templated, 150 deg. to 200 deg. cent, being not uncommon ac-
cording to later tests. Also in 1898 and 1899 the large engine-
type Manhattan Railway generators had mica insulation, in the
form of wrappers, on the armature coils. Following this, mica
insulation was used for quite a number of years, mostly on large
high- voltage alternators. About 1904 we built some large capac-
ity 60-cycle turbo-generators on which we used mica wrappers
on the armature coils. In service, one of these machines was
injured from some mechanical cause and we had to rewind it,
One of the fads about this time was special oiled-linen tape
insulation, and quite a pressure was brought to bear upon us to
rewind this machine with such oiled tape. With this insulation
the armature broke down in a comparatively short time (within
a few months, if I remember rightly). When the coils were
removed, the outside layer of insulation next to the iron was
found to be apparently in fair shape, but next to the copper the
insulation showed indications of being excessively heated; in
fact, it was badly carbonized in some places. We then reinsti-
lated with tnica aad the machine was operated for many years
without trouble. Here was a direct comparison between class A
386 ELECTRICAL ENGINEERJNG PAPERS
and class B insulations. I do not know how hot those coils ran,
but, judging from the appearance of the oiled-tape insulation,
it must have been materially above 125 deg. cent. Here was a
fortunate instance where the machine was first insulated with
mica tape and then afterwards insulated with fibrous materials,
so that actual comparison was obtained with the two materials
This was ten to twelve years ago, so that it cannot be said that
experience showing the relative merits of these two types of insu-
lation is only of recent date.
In the same way similar experience was obtained with field
insulation. Practically all our early turbo-generator fields were
insulated with fibrous sheet materials. Numerous instances oc-
curred where such insulations deteriorated so much that re-
winding was required. This led to numerous tests for tempera-
ture. In some of these earlier machines there was evidence of
practically uniform overheating throughout the whole winding,
thus indicating practically uniform temperature. In such cases
it was comparatively easy to approximate the ultimate temper-
ature from readings of the field currents and the field volts, thus
obtaining the increase in resistance and from this the temperature
rise. Such tests soon developed the fact that temperatures of
110 deg. to 125 deg. cent were not uncommon on the earlier
turbo-fields, while with the increased capacities and higher
speeds, toward which we were continually tending, the indica-
tions were that still higher temperatures would be attained.
This led to the development of mica insulation for the field
windings of turbo-generators In 1906 and 1907 a number of the
earlier hot fields were rewound with mica and such fields have
been operating up to the present time, or until discarded in
favor of larger units. The record with these mica insulated
fields has been extremely good. In some of the tests which we
made on these earlier machines to determine the suitability of
mica for field insulation, we carried one field up to 250 deg. cent,
for forty-eight hours, and would have continued the test very
much longer, but the conduction of heat from the core through
the shaft to the bearings was sufficient to overheat them How-
ever, at the end of this test the insulation was found to be in
absolutely good condition. This was a very mild test, in view
of our later investigations on mica, but at that time it was con-
sidered wonderful* I am simply bringing up such points to
indicate that mica has been used quite extensively on turbo-
generators for many years.
SOME PRACTICAL CONSIDERATIONS IN ARTIFICIAL
VENTILATION FOR ELECTRICAL MACHINERY
FOREWORD — The material given was first presented in a discussion
at one of the meetings of the Association of the Edison Illumin-
ating Companies, September, 1915. It was afterwards revised
for publication in the Electric Journal. — (ED.)
IN the artificial cooling of power-house and sub-station apparatus
especially that of large capacity, a number of conditions have
developed from time to time which have given trouble or which
have provoked more or less discussion. A number of these points
are here presented briefly.
QUANTITY OF AIR REQUIRED
There is a very definite physical relation between the heat
which must be dissipated from a machine, the resultant temper-
ature rise, and the quantity of air which is passed through the
machine to carry away the heat. The law is that one kilowatt of
loss dissipated into the air will raise 100 cu. ft. of air 18 degrees C.
in one minute. Therefore, if there is a definite loss to be
dissipated by the ventilating air and a desired limit to the permis-
sible rise in the temperature of the air leaving the machine, then
there must be a definite volume of air per minute through the
machine. The problem then resolves itself into getting this air
through the machine or apparatus. An allied problem lies in the
means for getting the heat from the copper or iron to the air.
PRESSURE REQUIRED TO OBTAIN DESIRED QUANTITY OF AIR
The pressure required for a given quantity of air is dependent
upon the size of air passages or apertures, upon the shapes of the
ducts, i. e , number of bends, abruptness of bends, length of ducts,
etc., and upon the velocity of the air. Too sma.11 passages means
high velocity of the air, with consequent high pressure required.
However, with many classes of artificially-cooled apparatus, the
space available for air passages is comparatively small at some
places, so that the air velocities are very high. This means
ventilation losses, but in many cases these are unavoidable with-
out radical changes in design whfth, in themselves, would mean
increased losses of other sorts equal to, or greater than, the possible
reduction in ventilation loss.
3&7
388 ELECTRICAL ENGINEERING PAPERS
Usually, the greater part of the pressure developed by the
ventilating fans is used up in the ducts or passages through the
machine itself. However, not infrequently, part of the pressure
is taken up by restrictions of some sort in the inlet or outlet con-
duits If the machine is self-cooling in the sense that the rotor
carries its own fan, then such restrictions in the conduits may
very seriously affect the quanity of air which passes through the
machine. It is, of course, possible to make the ventilating fans
of greater capacity, just to take care of such contingencies, but this
would be penalizing good engineering to take care of bad, for the
losses due windage would then be unduly large where proper con-
duits are furnished. Cases have been noted where as much as 30
to 40 percent of the available pressure has been taken up by
improperly designed inlet pipes.
Where the ventilating fans are driven independently of the
main rotor, that is, by motors, it is practicable to vary the air
pressure to suit the requirements, provided the driving motor can
have its speed adjusted over a suitable range. This makes the
ventilation more or less independent of restrictions. It has the
further advantage of allowing the quantity of air to be varied to
suit the load conditions. By this means an increased quantity
of air, but with correspondingly increased windage loss, is avail-
able with heavy loads, while less air with lower losses may be used
at lighter load This arrangement is somewhat more efficient
than the self-cooled arrangement with the fans on the main motor
shaft, principally because of the excessively high fan speeds com-
mon in the latter case, especially on turbo-generators in which fan
speeds far above efficient operation are used. In fact, in high-
speed turbo-generators fan efficiencies of 20 to 30 percent are not
unusual. Much better efficiencies can be obtained from separate
slower speed fans (50 to 60 percent). However, the reduction in
windage losses is not proportional to the increased efficiency of
the fans, for part of the windage loss is due to ''churning" of the
air passing over the rotor, and this will be present regardless of the
method of supplying air to the machine and is, to a certain extent,
a function of the quantity of air which passes through the air-gap.
This part of the windage loss is, therefore, greater in those machines
where all the cooling air passes through the air-gap than is the case
with those types where a considerable part of the air passes di-
rectly through the armature core, as in axially ventilated stators.
In either type of ventilation, variation in the quantity of air with
load is advantageous.
ARTIFICIAL VENTILATION 389
DISPOSAL OP HOT AIR
This was a matter of little importance in the days of small
capacity per unit-area of generating room. However, in these
latter days, where capacities of from three to ten times those of
former days are developed in the same space, the question of
disposal of hot air from the machines is becoming important. Large
turbo-generators may require from 50,000 to 100,000 cu. ft. of air
per minute. Five or six such machines in one generator room,
operating at full load, means 250,000 to 500,000 cu. ft. of air per
minute pouring into the room, this air being from 20 to 25 degrees
C. above the normal air temperature. Obviously some provision
should be made for getting this hot air out of the room. In the
average generator room, the total cubical capacity of the room will
be only five to ten times the total volume of air passing through
the machines per minute. This gives a good quantitative idea of
the extent of ventilation required in order to prevent undue tem-
perature rises of the room air. In some of the more modern
stations provision has been made for exhausting the hot air from
the machines into the boiler room.
DIRT IN THE AIR
The enormous quantity of air required for ventilating large
turbo-generators brings up the question of amount of dirt carried
into the machines by such air. Assume, for instance, 60,000 cu.
ft. of air per minute through a given machine. This weighs ap-
proximately 4800 pounds. The usual turbo-generator will, there-
fore, pass through itself, each thirty to forty minutes, a weight of
air equal to its own total weight. Or, presenting the matter in
another way, 45,000,000 cu. ft. of air passes through in twelve
hours. Assuming as a rough approximation, that only one
hundredth-millionth of the volume of air consists of dust or foreign
particles, then the above means that 0.45 cu. ft. of dust passes
through the machine in twelve hours, or 45 cu. ft. in 100 days of
twelve hours each. If the air inlet is in a dusty place, the above is
not at all an impossibility. Of course, a considerable part of this
dust will go directly through the machine, but in the air swirls
and eddies inside the machine some of it win be deposited, and
eventually this becomes a considerable handicap to the ventilation.
This dust acts harmfully in two ways. In the first place, it may
partially close the ventilating passages and thus decrease^ the
quantity of veatilatiQ^ air> la the second place, it may form a
390 ELECTRICAL ENGINEERING PAPERS
coating upon the heat-radiating surfaces so that the cooling air
cannot come directly in contact with such surfaces. Ordinarily,
in dissipating heat from a surface to the air, a thin film of hot air
adheres to the surface, and the heat is conveyed from the surface
through this film to the moving air. With high-velocity air
striking the surface, this film of hot air is scoured away from the
surface, so that new air continually comes in contact with the
surface. If however, a coating of dust, or of other heat-insulating
particles, gathers on the surface, then the ventilating air cannot
come in direct contact with the surface and the heat-dissipation is
at a lower rate. Dirt is particularly liable to adhere to the sur-
faces in case minute particles of oil are carried into the machine.
AIR WASHERS
Air washers are now being installed very generally in large
generating plants to clean the air which passes through the ma-
chines. These washers have beneficial results in two ways. In
the first place, they clean the air, thus preventing, to a great
extent, the deposit of dirt in the machine. In the second place,
they cool the air in hot weather, thus directly improving the
capacity of the machine by allowing a greater temperature in-
crease without exceeding a specified limit of temperature. A
number of attempts have been made to cool turbo-generators by
means of water in suspension in the ingoing air, that is, by "fog."
Such methods as yet have shown no particular promise.
Instances have occurred where fine, dry snow has been drawn
into artificially-cooled apparatus and there melted, with the
formation of water on the windings. This can only happen in
cold weather and could be avoided in several ways. An opening
from the inside of the building could be provided in the air intake
so that the ventilating air is not taken from the outside. Another
method would be to use the air washer at such times, by which
means the snow would be abstracted. It is usually not con-
sidered advantageous to operate the washers during extremely
cold weather, but in case of incoming snow there may be con-
siderable advantage in operating the washers.
ZERO AIR, AND WATER DEPOSIT
A number of instances have been noted where, with the in-
coming air at an extremely low temperature (near zero F.), the
end windings of turbo-generators were found covered with a film
of water. In one case this proved disastrous. Apparently this
ARTIFICIAL VENTILATION 391
was not condensation of water from the air, in the ordinary sense
for the armature windings were much hotter than the incoming air.
One explanation is that this is due to "frozen fog," or ice particles
in suspension, which melt when they come in contact with the
heated parts of the machine. One remedy for this trouble is in
the use of doors from the interior of the building to the inlet pipe,
which can be opened in extremely cold weather to admit warmer
air.
FIRE HAZARDS IN ARTIFICIALLY-COOLED MACHINERY
When a fire is started in such apparatus the artificial ventila-
tion tends to spread the fire very quickly, especially in turbo-
generators. Various remedies have been proposed, such as
firedoors or dampers in the inlet conduits, the use of "fireproof1
end windings, chemical extinguishers, etc. Firedoors have
proven only partially effective, possibly due to the fact that it is
difficult to shut off the air completely. For instance, in a ma-
chine taking 50,000 cu. ft. of air per minute, if 99 percent of the
air is shut off, the remaining 500 cu. ft which can pass through the
machine may be sufficient to maintain quite a destructive blaze.
Furthermore, there are liable to be small leaks around the end
housings of the machine which will admit a little air.
It has also been suggested that equally good results would be
obtained by enclosing the outlets from the machine in case of fire,
thus retaining the products of combustion inside the machine,
these forming a fairly good fire extinguisher in themselves.
As regards chemical extinguishers, these are practically useless
unless the incoming air can be almost completely shut off. With
50,000 cu. ft, of air, for instance, passing through a machine, the
small amount of gas which the extinguisher could furnish would be
so diluted as to be worthless. One point to keep in mind in apply-
ing extinguishing gases is that they must be applied at the incoming
side of the fan.
In some cases of fire the operators have turned on water from
high-pressure mains, on the theory that, while water may ruin the
insulation, yet fire may result in still greater damage.
Various attempts have been made to produce * 'fireproof"
insulations for the end windings of turbo-generators. The diffi-
culty lies in the fact that available fireproof materials, such as mica
and asbestos, cannot be used alone. Mica requires some support-
ing or binding material, while asbestos requires some filling
39* ELECTRICAL ENGINEERING PAPERS
varnish in order to obtain suitable insulating quality. It is these
binding or filling materials that are the real source of trouble, for
these give off gases if the temperature is sufficiently high, and these
tend to maintain or increase the blaze. Thus the outlook is not
very promising.
When the initial blaze is produced by a short-circuit or arc
inside the machine, a sudden interruption of the excitation, by kill-
ing the voltage, may extinguish the arc before a general conflagra-
tion is established. If the excitation is from a motor generator
across the terminals of the machine, then a short-circuit in the
machine may automatically shut down the exciter set. In the same
way, if the ventilating fan is driven by a motor across the terminals
of the machine, the ventilation may decrease automatically.
The above covers various suggested methods for preventing
damage by fire inside such apparatus, All of them are admittedly
defective, but each of them possesses some merit. A simple satis-
factory method of fire protection for such apparatus is much to be
desired.
NOISE
Recent high-speed turbo-generator rotors are all of the cylin-
drical type, with relatively smooth exterior surfaces. Neverthe-
less, due to their enormously high peripheral speeds and the great
quantity of air through the air gaps, there is always very consider-
able noise developed inside the machines themselves. As such
machines are always very completely enclosed, except through
their outlet and inlet pipes or openings, these latter are usually
responsible for any complaints regarding noise. Several cases
have developed where the inlet conduits, opening directly to the
outside of the btiilding, have permitted undue noise. In other
cases, sheet metal conduits have acted as sounding tubes and ap-
parently have exaggerated the noise. Changing to plaster-filled
expanded metal conduits has helped in some cases. In other cases,
carrying the conduits up to the roof of the building has proved
effective, A secondary result of this arrangement is that deaner
air is obtained, unless the inlet is exposed to an undue amount of
dirt from the chimneys.
SOME ELECTRICAL PROBLEMS PRACTICALLY
CONSIDERED
FOREWORD — This paper was prepared for the eighth annual conven-
tion of the Association of Iron & Steel Electrical Engineers held at
Cleveland, September, 1914. The object of the paper was to
present, in as simple form as possible, certain problems, such as
insulation, commutation, speed control of induction motors, etc.,
which particularly concerned iron and steel electrical engineers.
"(ED.)
IN steel mill electrical work there are a number of subjects which
are of very particular interest at present. In both alternating
and direct-current apparatus, there is the general subject of insul-
ation troubles, which is always open to discussion. In direct-
current work, commutation and commutator troubles are subjects
which are always with us. Also, as the induction motor is prob-
ably used more than any other in mill work, the problem of obtain-
ing variations and adjustments in speed with this type of motor
has become a very important one. In alternating-current work,
there is the question of the most suitable frequency, which has
come up prominently in the past two or three years. While these
various subjects may appear to be more or less disconnected, yet,
in fact, they are already allied in mill work, and all steel mill
electrical engineers are liable to be called upon to deal with them.
In the presentation of these subjects, a semi-technical method
is followed, and all mathematics, except where masked under some
other form, are omitted. The various subjects are treated in the
order of their convenience, and without regard to their relative
importance.
THE INSULATION PROBLEM
Practically all electrical apparatus uses insulation in one form
or another. Such insulation in general constitutes the weakest
part of the machine, both mechanically and electrically. Insofar
as the generation or utilization of energy is concerned, its functions
are passive, it serving merely as a protection. But in another way,
its functions unf ortunately are not passive, namely, in its effect on
heat flow and dissipation. In most cases, the parts which have to
be insulated are heat-generating. This is especially true of the
393
394 ELECTRICAL ENGINEERING PAPERS
windings of electrical apparatus. Experience shows that aH
electric insulators are heat insulators to a great extent, and ex-
tremely good heat insulators in the case of the most practicable
materials. It is well known that the best way to apply heat in-
sulations is in the form of superimposed layers, and this happens
to be the most practicable way of applying most electrical insula-
tions. It is also weU known that air pockets in heat insulations
improve their heat-insulating qualities. It is partly on this
account that, in the application of electric insulations, air pockets
are avoided as much as possible, and endeavor is made to fill such
pockets with varnishes or impregnating gums which act as better
heat conductors than air or gases. In general, it may be said that
heat is transmitted more effectively by conduction through solid
bodies, or between solid bodies in contact, than by convection
through gaseous bodies. Therefore, the more solid, or the better
filled is the insulation, the better it will conduct heat as a rule, and,
in fact, there is not such a great difference between the heat-con-
ducting qualities of the various commercial insulations, on the
basis of equal solidity. The principal differences are found in the
ways the materials are applied. While some materials may con-
duct heat two or three times as well as others, yet this difference is
very small compared with the difference in heat-conducting
qualities between ordinary insulations and any of the so-called
electrical conductors, such as metals. For instance, a difference
of temperature of 1°C. between the opposite sides of an inch cube
of copper will allow a heat flow 2500 times as great as with a cor-
responding cube built up of oil tape. And an inch cube of wrought
iron, which is considered a poor electrical conductor, will conduct
about 400 times as much heat as the block of insulation. There-
fore, when compared with electrical conductors, we may say that
the heat-conducting qualities of the usual built-up insulations are
fairly uniform.
The heat-conducting ability of insulation is a function of the
thickness or distance the heat has to traverse, just as in all other
bodies. Therefore, when a heat-generating body is covered with
insulation, it is desirable to make such insulation as thin and
compact as possible, where it is desirable to keep the temperature
as low as possible. This is an elementary fact which has been very
much neglected and overlooked in the past.
In electrical apparatus, it may be said that it is not the tem-
perature in the heat-generating body itself which is harmful, but
INSULATION PROBLEMS, ETC 395
it is the effects of such temperature upon the enclosing or con-
tiguous insulation which must be taken into account. Most of the
flexible insulations in every-day use do not have high heat-resisting
characteristics. The effect of the heat usually is more harmful
to the mechanical characteristics of the material than to the elec-
trical characteristics. Most fibrous insulations, when exposed to
fairly high temperatures for long periods, or exceedingly high
temperatures for much shorter periods, show a tendency to become
very brittle, and, in time, they may even carbonize to a greater or
less extent. However, for moderate voltage stresses, even this
very dry or semi-carbonized condition of the insulation does not
appear to seriously affect its insulating qualities. The real harm
lies in deterioration or possible injury of its mechanical properties
— that is, it may become so brittle that it will not stand mechan-
ical shocks or vibrations, and may crack or scale off so that its
insulating qualities are impaired simply through mechanical
defects. Here is where certain filling or impregnating varnishes
or gums are particularly useful. As the fibrous insulation tends
to become brittle at high temperatures, the varnish or gum may
tend to soften at the same temperature, and thus conteract, to a
certain extent, the brittleness of the fibrous material itself. A
second function of such gums or varnishes is to act as fillers for all
spaces and interstices, and thus to assist in conduction of heat,
but, still more, to act as a cushioning material to keep the con-
ductors from vibrating under shocks, etc. Of course, the impreg-
nating gums or varnishes have a certain value as insulating
material, but probably the above functions are of far greater
value. For instance, the ordinary cotton covering on a wire will
stand far more abuse when treated with some kind of gum or
varnish than when used in the dry condition, for, in the former
case, the individual fibers of the covering are actually pasted in
place, and are therefore much less liable to be separated and thus
allow metal parts to come in contact. Usually what is required
between adjacent conductors in a coil is a positive mechanical
separation of a very limited amount. In many cases, if the bare
conductors could be maintained at a distance apart corresponding
to the thickness of the usual cotton covering, this would be suf-
ficient for protection against the voltages between the wires,
TJie layer of insulation on -the wires themselves furnishes the sim-
plest and easiest method of obtaining this mechanical separation,
and the varnish or gum treatment makes this separating medium
of more mechanical and durable construction, and, at the same
time, improves the heat-conducting qualities.
396 ELECTRICAL ENGINEERING PAPERS
There are limits to the heat-resisting qualities of all practic-
able insulations. Ordinary fibrous materials of a cellulose nature
or base, will stand about 95 °C, to 100°C. without becoming too
brittle to be durable. However, the same materials, when treated
with suitable varnishes or gums, apparently stand temperatures of
about 105 °C. without undue deterioration mechanically. At
this temperature the material does not appear to carbonize, and
the varnish or gum assists in maintaining mechanical continuity
of the material. At materially higher temperatures, deterioration
gradually takes place at a rate depending upon the actual tem-
perature attained. Even at 150°C., treated fibrous materials may
have a total life of several months before the material becomes
unsuited for its purpose. If such high temperature exists only
for short periods, and during the remaining time the insulation is
subjected to relatively low temperatures, then the life of the
apparatus measured in years, may be fairly great. In other
words, high peak temperatures may not be very harmful, pro-
vided the sum total of such peak periods does not add up to as
long a period as required to injure the materials if maintained at
the same peak temperature steadily. However, the life of
insulation does not decrease in direct proportion to the
increase in temperature, but at a much faster rate.
Other insulations in common use are mica, asbestos and
certain varnishes and gums. Pure mica will stand enormously
high temperatures, such as 700°C. or even higher. Good grades
of asbestos stand at least 400 °C. as shown by actual test, and
possibly very much higher. However, neither mica nor asbestos,
in itself, is a good material for application to windings, due to
mechanical conditions. In order to obtain flexibility, mica must
be built in thin sheets and then assembled in the form of a paper
or tape. This requires some continuous supporting base, usually
a thin tough paper, to which the mica is attached by some form of
binding gum. The result therefore consists of both high and low
heat-resisting materials. If the continuity and durability of the
resultant mica insulation, after application to a coil, is dependent
upon the durability of the binding and supporting material, then
such insulation is limited to temperatures corresponding to fibrous
materials. If, however, the binding and supporting material can
deteriorate without materially injuring the insulation as a whole,
thai such composite insulation can stand comparatively high
temperatures. In present practice, such temperatures are limited
INSULATION PROBLEMS, ETC. 397
to approximately 1SO°C. for steady operation, not because this is
an actual limit, but largely because of lack of extended experience
at materially higher temperatures. Apparently, such materials,
when properly applied, will stand 300°C. on peak service about
as well as the treated fibrous materials will stand 150°C,
Asbestos, as an insulation, is pretty poor material, but as a
mechanical separator, where high temperatures are obtained, it
may be very effective. Due to its open fibrous character, there
is no true over-lapping of insulating surfaces, and, to make as-
bestos effective as an insulator, it must be filled in with some
insulating filler or gum, in which case, the gum is the real insul-
ator. However, asbestos may answer for a very good supporting
material for other insulations, such as mica, when subjected to
very high temperatures. Also, asbestos may be a suitable in-
sulation on conductors with very low potential between them, as
in field windings and in armature windings with low internal
potentials. It should be considered as essentially a separating
and supporting material, rather than as an insulation.
In recent years, a number of synthetic resins, such as Bakalite,
have been developed, which have a field in insulation work.
Such materials usually have high heat-resisting qualities, but, in
their final condition, are liable to be hard and brittle. Some of
them are used extensively as impregnating or filling varnishes,
and when so applied, are in fluid form, and require further baking
to change them to the final form. Some very extravagant
claims have been made for them by those who were not sufficiently
acquainted with the materials and their properties. They are
very valuable in many ways, but, like all other materials, they
have their limitations. In their application to armature windings,
it is advisable, in many cases, to apply the coils before being given
the final baking on account of the greater flexibility of the unbaked
coils. But the final treatment usually leaves the armature
winding in such rigid condition that, in case of repairs, it may be
necessary to completely destroy the whole winding. This looks
like a bad feature, but to counter-balance it, it may be said that,
for certain kinds of work, such prepared windings are less liable
to damage, and therefore the necessity for repairs is much reduced*
As impregnating compounds, where stiffness or rigidity is ad-
vantageous, such materials have proved very satisfactory, but,
where considerable flexibility is desirable, compounds of this
nature may not pix>ve so desirable. If the impregnating material
398 ELECTRICAL ENGINEERING PAPERS
is brittle and is liable to cracl:, tinder stresses due to change in
temperature, or movement, or shock, then it loses a certain part
of its value. Where flexibility is important, gums or varnishes
which soften with heat are desirable.
In armature or field windings, it is very unusual to find con-
stant temperatures throughout the whole winding, due to the
different heat-conducting and heat-dissipating conditions in
different parts. Therefore, the higher temperature points or ' ' hot
spots" must be considered in fixing the insulation temperature
limits. It is the highest temperature to which the insulation is
subjected that must be considered in fixing the limits, and only in
rare cases do the ordinary methods of temperature measurements
indicate the highest temperatures actually attained. Ordinary
thermometer measurements approximate the temperature at
some accessible point, but this may not be, or, likely, is not the
hottest part. A determination of the temperature by increase in
resistance gives only an average value. Therefore, by actual
measurement by the usual methods, the above mentioned tem-
perature limit of 105°C. for treated fibrous materials is not allow-
able. For instance, the usual full load guarantee of 40°C. rise
with a cooling air temperature of 40°C. will give 80°C. as the
temperature measured, thus allowing a margin of 25 °C. for some
higher internal temperature — that is, for the hot spot. The usual
overload guarantee of 55 °C. by thermometer, with air at 40 °C.,
will give 95 °C. measured, or a margin of 10°C for the hot spot,
which apparently is right on the ragged edge. But then, this 55 °C.
guarantee is usually given only for overloads or intermittent
service, and it is this condition which allows the proper margin.
If, however, an accurate means should become practicable for
determining the actual hot spot temperatures, then it would be
practicable to rate machines at the 105°C. measured temperature.
As this cannot be done at present, we must fall back on a lower
measurable temperature, and allow a suitable margin.
In certain classes of apparatus where the higher temperature
regions are pretty definitely known, it is possible and practicable
in many cases, to insulate, in the hotter regions, with materials
which have higher heat-resisting characteristics, as already de-
scribed. This is the case in many high voltage machines, and in
machines with very wide armature cores, such as some turbo-
generators, high speed large capacity alternators, etc. In such
machines, the middle part of the armature core is liable to be
INSULATION PROBLEMS, ETC, 399
much hotter than any other part. Therefore, it is rather common
practice in such machines to insulate the buried part of the arma-
ture coils with composite mica insulation, which can be easily
applied on the straight portions of the coil. On the curved end
parts of the coils, where taped insulations are required on account
of the curvature, much lower temperatures are usually obtained,
and thus fibrous tape insulations are amply safe for this part.
In apparatus subject to very heavy overloads for relatively
short periods, excessively high temperatures may be attained by
the copper inside the insulation, but if followed by much lighter
load, the high temperature may drop so rapidly that no apparent
damage occurs. Experience has shown that, not infrequently,
local temperatures of 200°C. to 300°C. are attained for a very
short time. When such temperatures occur close to any soldered
connections, there is danger of damage due to unsoldering, for or-
dinary commercial solders will soften at about 170°C. to 180°C.,
while pure tin solders will soften at about 220°C. to 230°C.
Therefore, temperatures which, due to their short duration, ap-
parently do not harm the insulation, may actually unsolder con-
nections
The above covers briefly the temperature part of the insula-
tion problem. But insulating materials also serve another pur-
pose, namely, to shield the conducting or live parts of the machine
from other foreign conducting materials, such as dirt, grease, oil,
water, etc. Oils and greases are usually considered as non-con-
ducting, but when they are liable to carry with them conducting
materials, such as copper and carbon particles, they become con-
ductors in effect. Also, ordinary dust, or dirt, or deposit from the
air, is a relatively poor conductor* but conducts far better than
the usual insulations, and is therefore, to a certain extent, danger-
ous. As a conductor, water is considered as comparatively poor,
and yet no one would class it as an insulator. Both water and oil
may be directly harmful and may be indirectly injurious by their
actions upon the insulating materials themselves. In the case of
cloth tape insulators, the cloth may be considered as simply form-
ing aKbase or reinforcing structure for the insulation proper, which
is usually some varnish or oil compound. The insulation value
of the material depends principally upon the continuity of the
layers of varnish or oil. The cloth structure itself has no true
continuity. In applying such tapes or insulations, the layers over-
lap each other in such a way as to give the best sealed circuit.
400 ELECTRICAL ENGINEERING PAPERS
During the process of taping, the surface may be varnished re-
peatedly to further seal the overlapping joints, and to obtain
greater continuity of the insulating film. Also, in the composite
mica insulations, the mica laminas are very thin and arranged in
a number of layers in such a way as to overlap as completely as
possible to form insulating films. The binding material between
layers or films is largely for the purpose of sticking or binding
the mica laminae to each other. Therefore, with either type of
insulation, continuity of the insulating film, is the first requi-
site, and any action or treatment which tends to break the
films will naturally tend to weaken the insulation. In high
voltage armature coils, in particular, it is of utmost importance
that the completed coils should not be sprung or bent to such
an extent that the insulation films are liable to be cracked or
"buckled" at any point, for this immediately produces a local
weakness. In all cases, extreme care should be taken in handling
such coils, especially in placing them on the cores. Moreover, in
machines which are liable to carry excessive currents, even momen-
tarily, and which are thus liable to distorting magnetic stresses,
the windings must be so braced that movements sufficient to
crack or buckle the insulation are not permitted. There is but
little real flexibility in such insulations when built of any con-
siderable thickness. Insulation on cables might be cited as an
exception, but here the insulating varnishes are soft and possibly
semi-viscous, so that a certain amount of bending does not break
the insulating films. To maintain this condition of soft flexible
insulation, cables are guaranteed usually only for very low maxi-
mum temperatures, compared with the temperatures usually
found in electrical apparatus.
The continuity of the insulating films may be injured in other
ways than by bending. If, for instance, a newly insulated coil
which has been insufficiently baked or " seasoned," is subjected
to a comparatively high temperature for even a short time,
certain volatile matter in the varnishes may be given off in the form
vapor, and these vapors may force or break their way through the
insulating films. The writer has in mind one case where a taped
insulation was used on a rewinding, with the shortest possible
time for the baking before applying the coils to the machine. The
insulation tests were high, but a heavy load was thrown on the
machine at once and carried for several hours. At the end of this
rim, the insulation test showed that the insulating material had
INSULATION PROBLEMS, ETC. 401
deteriorated very greatly, — so much so that the machine was
considered to be in a dangerous condition. Upon removing some
of the coils, an examination showed what looked like little vol-
canoes all over the surface of the insulation. Further investiga-
tion showed that these were real volcanoes, for the high inter-
nal temperature had vaporized some of the original solvents which
had not been entirely removed from the varnish, and such vapors
had actually erupted through the superimposed strata represented
by the insulating films or varnishes. Therefore, at each one of
these points of eruption, there was a breakdown of the insulating
strength of greater or less depth, depending upon where the vapor
was formed. This is cited simply as a very good illustration of
what can happen in "green" insulation.
Another source of difficulty which is not unusual, is that due
to water, or oil, or other foreign materials getting into the insula-
tion. Submersion of electrical apparatus, due to floods, is not
uncommon in industrial plants, due to their proximity to rivers,
in many cases. In some cases, experience has shown that a
flooded machine can be dried out with apparently no harmful
after effects, while in other cases, it has been found almost hope-
less to save the apparatus. This depends to some extent upon the
kind and character of the insulation and the means for getting rid
of the water without injuring the insulation itself. If water has
percolated into the coil and becomes sealed or trapped inside, then
high internal temperatures obtained by any means may simply
vaporize the water without getting rid of it. If the insulation is
porous, the water may be driven off readily. If the drying heat is
applied from the outside, then, before the center is heated suffic-
iently to vaporize the water, the outside insulating films may seal
together under the higher outside temperature, so that the internal
vapors cannot escape except by disrupting the film If, on the
other hand, heat is applied from the inside, by means of current
for instance, and the heating is too rapid, vapor may be formed
more rapidly than it can percolate through the insulation, and it
may injure the insulation in escaping. fc Also, in the case of elec-
trical heating, non-uniformity of temperature must be taken into
account. For instance, the armature winding of a high voltage
alternator might be operated on a short circuit for the purpose of
drying out. The drying out current may be so high that the
center of the armature core is considerably above 100°C. or the
boiling point of water, while the end windings may be 30 percent
402 ELECTRICAL ENGINEERING PAPERS
or 40 percent cooler. In such case, the water in the hot part of the
coils is simply vaporized and driven to the end windings and there
condensed. This is not an unusual condition in drying out high
voltage windings which contain moisture. One instance may be
cited, where, several years ago the power house of the Westing-
house Electric & Manufacturing Co. was flooded for several days,
and several large 2200 -volt turbo-generators were partly sub-
merged. One of these machines was dried out on short circuit for
about a week at a temperature of possibly 120°C. inside the coil.
At the end of this time, no leak to ground showed and the machine
was put in service. A few weeks afterwards, a short circuit
occured inside one of the coils, in the end winding. When dis-
mantled, this coil was found to be sopping wet in the end portion,
although the buried part of the coil was fairly dry. The baking
process had simply distilled the water from the center to the end
parts. An ftTa.Tnina.tinn of others of the submerged coils showed
the same condition. It is possible that untaping of the end wind-
ing sufficiently to have allowed the escape of vapor would have
allowed this machine to dry out properly, but apparently this
would not be the case unless the end windings in themselves could
have been brought up to a temperature considerably above 100°C.
and this might have meant 1SO°C. in the buried portion, which
would probably have been injurious, except to mica insulations,
which did not happen to be on these machines. Furthermore, it
is not always easy to get rid of moisture, even at 100°C. with
fibrous insulations. One very effective manner of doing so is by
means of a vacuum. Experience has shown that if apparatus to
be dried out is heated to tne boiling point, in a vacuum, the moist-
ure usually is removed very completely. For most effective re-
sults the water should be vaporized, for, under some conditions,
and with some materials, the force of capillarity may approximate
IS Ibs. so that a good vacuum alone may not be able to overcome
the capillary action. From the scientific standpoint, the use of
vacuums in drying goes much further than the above. For ex-
ample, the boiling point of water is very much reduced in a
vacuum, so that materially lower temperatures may be used for re-
moving water than would otherwise be the case. For rapid drying
under ordinary air pressures, considerably over 100°C. is needed,
while in a fairly good vacuum, 100°C. or less, may allow a very
rapid evaporation of moisture and a correspondingly rapid and
thorough drying.
INSULATION PROBLEMS, ETC. 403
In the same flood which submerged' the generator above re-
ferred to, vast quantities of other apparatus of various types and
designs were also flooded, and, in drying out this apparatus, a
great deal of valuable experience and data were obtained. A
summation of this and other experience may be of value and
interest, and is therefore given below.
Low voltage alternating-current windings, such as induction
motors and alternating-current generators for 600 volts and less,
dried out very readily by the application of current to the windings.
In general, low voltage, direct-current armature windings were
dried out by the application of current or by baking in ovens. How-
ever, there was great difficulty in drying out commutators, and
eventually the only real satisfactory way proved to be by heating
them in a vacuum. Therefore, the finaldrying out of direct-current
armatures was principally by vacuum.
The complete drying out of field coils was very difficult, either
by current heating or by ovens. However, the outside of the coils
could, in many cases, be dried sufficiently to show practically no
ground, while the inside of the coil was still wet. In most cases,
field coils could be operated in this condition and could eventually
dry themselves out. This would probably be satisfactory for
drying out individual machines, but was not considered satis-
factory for stock apparatus. Vaccum drying under high temper-
ature proved most satisfactory, and this was adopted.
High voltage windings for generators and transformers were
dried out in vacuum, no other methods proving entirely satisfac-
tory, except in individual instances.
It may be borne in mind that his was a situation where super-
ficial correction was not permissible. During the various tests
and methods which were carried out, searching investigations of
the results were made in order to determine the sufficiency of the
method used. Field coils and armature coils were opened up at
various stages of the process for examination. For instance, one
of a lot of street railway armatures which were dried in an oven
until apparently all right, was dismantled for exa.mina.tion. The
windings appeared to be fairly well dried out, but upon opening
the commutator V-ring, very considerable- moisture was found
tinder the commutator bars and IB the mica bushing. Apparently,
oven baiing would not remove this satisfactorily. The commut-
ator was then sealed tightly and the armature was then put in a
vacuum oven and dried for a few hoars. After this all water had
404 ELECTRICAL ENGINEERING PAPERS
disappeared from the commutator. Another commutator was then
opened and purposely filled -with water and then closed and sealed
as tightly as possible before placing in the vacuum oven. After
an over-night's treatment, the inside of the commutator was found
to be entirely free from moisture. This test illustrated the ability
of the vacuum oven to remove water. It was then adopted very
generally for drying out such apparatus as was liable to have
water sealed or trapped inside the insulation. It must be under-
stood, however, that certain kinds of apparatus were dried out
just about as well using temperature alone. In these cases, how-
ever, as intimated before, the vaporized water could readily
escape to the air.
There is one condition, however, where even vacuum oven
drying may not produce the desired result, for the operation of
drawing off the water may injure the insulating varnish films. To
illustrate, some years ago one of the large power plants at Niagara
Falls was flooded to a considerable depth by an ice jam, which
backed the water up into the power house. The machines were
flooded to a depth of twenty or thirty feet for a period of several
days, and the windings were pretty thoroughly impregnated
throughout with water. Strenuous attempts were made to dry out
these windings by heating to temperatures of 12S°C. or higher.
The end windings were untaped at points to allow the moisture to
escape. Also, attempts were made to create a vacuum around
the machines by means of air-tight covers or casings and vacuum
pumps, but this latter was not very satisfactory. After a few weeks,
apparently but little progress had been made. A chemist then
advanced the suggestion that, IE linseed oil varnishes had been
used in the insulation, then, under the conditions of flooding
which had occurred in this plant, the varnish itself would have
absorbed water, and he was of the opinion that heating alone,
unless carried up to the destructive point, would not drive off
this water. Investigations were then made along this line, and
it was actually found that the varnished films were thoroughly
filled with water, and moreover, this water could not be removed
without more or less injury to the film itself. For moderate or low
voltage machines, apparently, the removal of the water would not
injure the insulation sufficiently to prevent operation, but in high
voltages, such as 6600 volts or higher, the insulation would be left
in a relatively weakened and unsafe condition. In the machines
INS ULA TION PROBLEMS, ETC. 405
in question, it was found" advisable to remove the insulation en-
tirely and replace with new.
As a rule, field coils can be dried out in a fairly satisfactory
manner by heating with current for a sufficiently long period.
When a field coil is thoroughly wet inside, its resistance may fall
considerably, due to low resistance between turns and layers, but
when current is applied, there is but little danger of burnouts, as
the leakage of current through the insulation is distributed over
such large surfaces that there is no danger of burning at any one
point, unless there is some defectively insulated point in the coil.
Therefore, after the coil is sufficiently dried so that its leakage to
ground, or any metal supports, is sufficiently low to be safe, then
usually the coil can be put in operation and allowed to dry out in
regular service. If, however, the field coil rotates and is subject
to centrifugal or other forces, the wet condition of the internal in-
sulation may allow internal distortions or movements which might
cause partial short circuits.
COMMUTATION AND RELATED PROBLEMS
In the practical design and operation of electrical apparatus,
there is no problem which is apparently more enshrouded in mys-
tery than that of commutation. Theoretically this problem has
been treated in various ways and analyzed to various degrees, but
the practical results not infrequently disagree with the theoretical,
principally because the latter are predicated upon conditions which
are not, or can not, be obtained practically. Moreover, even when
the problem can be correctly analyzed, and a proper solution
indicated, it may not be practicable or feasible to apply such
solution. In other words, the theory may show just where a
trouble lies, but the application of a suitable remedy is another
story.
The difficulty is that the theories of commutation are built
upon many conditions which are inter-dependent. But many of
these conditions differ, in different types, designs or sizes of
machines, and, even in a given machine, a change in one condition
may greatly modify other conditions. For instance, the local or
short-circuit currents which are present in the coils short-circuited
by the brushes during the operation of commutation, have a pre-
ponderating influence on the commutation, and yet, these local
currents are greatly influenced by many conditions, such as the
dimensions and grade of brush, condition of contact surface,
406 ELECTRICAL ENGINEERING PAPERS
rigidity and type of brush holder, etc. Obviously, with such
variable elements entering into the problem, any rigid analysis is
most difficult. In such cases, the theory is valuable in locating
any probable causes of difficulty.
A great variety of conditions or phenomena are encountered
in commutating machinery, which require more or less knowledge
of the theory of commutation in order to understand them. For
instance, the causes for sparking, flashing, burning of brushes,
undue wear of commutator copper, etc , are all directly related to the
commutation problem. Even questions of composition, or grade
of brushes, type of brush holder, etc., are related problems.
As it is the writer's purpose to treat the above points from
the practical side, he considers it advisable first to give a brief
explanation of the commutation problem from the standpoint
which he has found to be simplest and most illuminating.
THEORY OF COMMUTATION
A direct-current armature, when carrying current, becomes
a true electro-magnet, with the poles located on the armature at
positions corresponding to those coils which are in contact with
PIG. 1.
the brushes. If the armature were surrounded by a smooth ring
of iron, (Fig. 1) then a magnetic field would be set up between the
armature and the surrounding ring, this field having maximum
values at points corresponding to the brush contacts and zero
values midway between. The magnetic field would rise, from
the zero points, uniformly to the highest values, because the arma-
ture winding, which is a magnetizing winding, is uniformly dis-
tributed over the armature core. If, now, deep notches were cut
in the surrounding ring at points corresponding to the highest
field, (Fig. 2) there would be comparatively weak field at these
points, due to the high reluctance of the gap or notch. The ex-
INSULATION PROBLEMS, ETC. 407
ternal ring in this case represents the field structure of an ordinary
D. C. machine, and, in such machines, the armature when carrying
current actually tends to set up magnetic fields in this manner, and
the coils in contact with the brushes are practically always located
in the space between poles, — that is, in the notches in the sur-
rounding ring in the above illustration. Also, the coils in contact
with the brushes are those in which the current is reversed in
direction when passing under the brushes, or, in other words, are the
commutated coils. Therefore, it may be seen that the commutated
coils always lie in what would be the strongest magnetic field set
up by the armature winding, if there were no polar notches. But,
even with such notches or interpolar spaces, the armature winding,
when carrying load, tends to set up some magnetic field, part of
which is in the space over the armature, and part of it across the
armature slots. This latter flux from slot to slot, is not influenced
by the notches in the surrounding iron, — that is, by the interpolar
spaces. In addition, the armature winding sets up a magnetic
field around the end windings.
PIG. 2
The annature winding, when carrying current, therefore
always tends to set up a magnetic field, through which the arma-
nire conductors rotate and generate e. m. f.'s, just as when they
cut the mai'r> field set up by the field windings. These coils short-
circuited by the brushes also generate e. m. f.'s and as their ter-
minals, which are conomutator bars, are connected together or
short-circuited by the brushes on the commutator, the e. m. f.'s
generated by cutting the armature flux tend to cause local or short-
circuit currents to flow in such coils. Such currents will be known
hereafter as the local or short-circuit currents, to distinguish them
from the useful or work currents of the annature.
As an armature coil carrying current in a given direction,
approaches and passes under the brush, the current should die
403 ELECTRICAL ENGINEERING PAPERS
down to zero value at the midpoint of the brush and should rise
to full value in the opposite direction by the time the coil leaves
the brush. This would be a theoretically perfect condition, but
is very difficult or almost impossible to attain in practice. The
coil, while under the brush, has an e. m. f . generated in it due to
cutting the armature field, as already described, and a local
current circulates. This short-circuit current normally adds to
that of the work current before reversal, and thus tends to main-
tain it right up to the moment that the coil passes out from under
the brush. The reversal of the current in the short-circuited coil
is thus accomplished almost instantaneously instead of gradually.
If, however, this local current could be generated in ike opposite
direction, then it would tend to oppose the work current as the coil
came under the brush, so that the resultant current would first die
to zero and then rise in the opposite direction, if the short-circuit
current were just large enough; so that the work current would
simply replace the short-circuit current in direction and value as the
coil passes out from under the brush. Therefore, if the short-
circuit current were of exactly the right value, the resultant
effect would be the same as if the work current alone were present
and this current died down to zero value as the coil passed the
middle of the brush, and rose to full value in the opposite direction
by the time the coil left the brush. In other words, a local current
of the proper direction and value in the commutated coils will give
theoretically ideal commutation. Such local current therefore,
might be designated as the commutating current. In practice
it is found however, that a current somewhat higher than the
ideal value gives the best general results as will be explained
later. In any case, however, this local current, to be effective,
must be in the reverse direction to that which would normally
be set up by the armature coil cutting the magnetic field due to
the armature winding itself. This means therefore, that where
commutation is accomplished by means of short circuit or local
current, an external field in the opposite direction to the armature
field is necessary for setting up such local currents. This result
may be accomplished in several ways. The brush may be rocked
forward or backward until the commutated coil comes under the
magnetic field, or fringe of the field, set up by the main field
winding. If rocked in one direction (forward in the generator,
backward in the motor) the direction of the main field will be in
opposition to the armature field. Obviously, if shifted into a
INS ULA TION PROBLEMS, E TC 409
strong enough external field, the armature field may be com-
pletely neutralized at some given point, such as that of the short-
circuited coil, or the resultant field might be even strong enough
in the opposite direction to set up the desired local or short-circuit
current in the commutated coil. Under this condition, ideal corn-
mutating conditions should be obtained. However, as the
armature magnetic field at this point tends to vary with the
armature current, while the external field tends to remain constant,
it is evident that the ideal resultant field will only obtain at one
particular load. Therefore, only an average condition can be
obtained in this way. However, by shifting the brushes backward
or forward under the external field, the proper local or commutating
currents should be obtained for any given load; but brush shifting
is not usually considered a very practical method of operation,
although required by many non-commutating pole machines in
service. What is needed is an external field directly over the
commutated coils which is always of the proper strength to set up
commutating currents of the right direction and of the proper
value with respect to the work currents, so that the resultant in
the short-circuited coil will give the effect of the work current
reversing at the middle of the brush at all loads. To accomplish
this, an external field to produce this local current should always
be in opposition, to the armature magnetic field, should be some-
what greater in value, and should vary in proportion to the
armature field, — that is, to the armature current. This result is
accomplished by the now well-known commutating pole, which is
simply a small pole placed over the commutated coil, and usually
excited by a winding directly in series with the armature, but
having a somewhat greater magnetizing force than the armature
winding. The function of this pole is solely to set up in the
armature coil a local or commutating current of the proper di-
rection and value.
A condition which makes the problem of commutation very
much easier to solve is the use of a relatively high resistance in the
short-circuited path of the coil which is being commutated. Due
to the extremely low resistance of the ordinary armature coil, a
relatively low magnetic field set up by the armature would generate
enormous local currents in the short-circuited coil if the resistance
of the coil itself were the only limit. These .currents might be ten to
twenty times as great as the normal work, current, and would add
seriously to tfce difficulties of commutation. Even if a, commut-
410 ELECTRICAL ENGINEERING PAPERS
ating field were present, this would have to be proportioned and
adjusted so accurately, to get the right value of the commutating
current, that the construction would be almost impracticable.
But if considerable resistance, compared with the coil itself,
could be interposed in the short circuited path, this obviously
would so greatly assist in fixing the value of the short-circuit
current that undue refinement and adjustment would not be
necessitated. Let us suppose, for instance, that the short circuit
e. m. f , in the commutated coil is two volts, and a copper brush of
practically zero resistance at the contact is used, then the resist-
ance of the short-circuited coil itself limits the current which
flows. Let us assume that this gives a local current of ten times
the value of the work current. Now, if, instead of the zero resist-
ance brush contact, one of about ten times the resistance of the
coil is used, then the total resistance in circuit becomes over ten
times as great, and the short-circuit current is cut down to a
value comparable with that of the work current. Obviously this
in itself would represent an easier condition of reversal without
any external reversing field, and, with such a field, extreme ac-
curacy in proportions and adjustment are not necessary to give ap-
proximately the right value of the local current which assists in
commutation. Therefore, a relatively high resistance brush, —
that is, one with contact resistance high compared with the re-
sistance of the coil — is of very material aid in commutation. This
is wherein the carbon brush is such a successful, or even necessary
adjunct of the commutating machine. It serves such a vital
purpose that it may be said that, without the carbon brush or
its equivalent, the electrical industry would never have made
anything like the progress it has made.
The principal function of the carbon brush being that of
limiting the local current, it might be assumed that the advan-
tages might be increased indefinitely by further increasing the
resistance, but there are usually limits to all good things. The
carbon brush increases the resistance in the path of the local
currents, but it also increases it in the path of the work current.
If the resistance is carried too high, the losses due to the work
current may constitute a more serious objection than the local
currents. Consequently, practice is one continual compromise on
this point. In those cases where the short-circuit current is
normally relatively small due to low value of the armature mag-
netic field, it is obvious that a lower resistance in the short-circuit
INSULATION PROBLEMS, ETC. 411
path can be used, or, in other words, a low resistance carbon
brush is practicable, with consequent low loss due to work cur-
rent. In other cases with higher inherent local current, higher
resistance carbon will give better average results. It is thus
obvious that one grade of carbon brush is not the best one for
different machines unless they all have similar inherent commut-
ating conditions. It is exceedingly difficult to give equal com-
mutating characteristics to machines of different sizes and types,
and, in most cases, even of the same type or line. In non-com-
mutating pole machines, the grade of the brush is of more im-
portance than in the commutating pole type, for in the latter, we
have a means, in the commutating pole strength itself, of modi-
fying or controlling the value of the local current. But the best
commutating pole gives only average correction, — that is, average
Fig. 3.
value of the desired local current, and the resistance of the brush
must be depended upon to take care of pulsations or irregularities
in the local current, acting to smooth them out to a greater or less
extent. Thus a fairly high resistance brush is required on the
commutating pole machine, but its resistance tisually can be
lower than that required in the non-commutating pole type.
The above gives a crude idea of the phenomena of commuta-
tion. However, there are a number of very closely related condi-
tions, such as burning and blackening of the commutator, causes
and effects of high mica, effect of under-cutting of mica, rapid
and undue wear of commutator copper and brushes, etc., which
can be explained more or less directly by the above theory.
Blackening of the commutator, high mica, and rapid wear of
the commutator copper and brushes may aH be credited to actual
burning, or something similar to electrolytic action, occurring under*
412 ELECTRICAL ENGINEERING PAPERS
the brushes. It is not usually the bright sparks at the brush tips
which cause trouble, but it is frequently on unnoted sparking under
the brush face. These sparks may be very minute, — so much so that
they would naturally be assumed to be harmless. The apparent
electrolytic action under the brushes may be really a similar
sparking action which cannot be observed. Experience has
shown that usually there is a tendency for minute particles of the
conducting material to be burned or carried away from the con-
tact surfaces, (Fig. 3) depending on the direction of the current.
These particles appear to travel in the direction the current i& flow-
ing, but they do not always deposit on the opposite contact sur-
face. If the current is from the brush to the commutator copper,
the brush surface tends to be eaten away, while with the current
from the copper to the brush, the copper eats or burns away.
Fig. 4.
With ordinary current densities and very low loss in the brush
contact, this action seems to be very minute, but it appears to in
crease rapidly with increased loss at the brush contact. There-
fore, high current density in the brush contact may produce
this action. This does not mean high density due to the work
current alone, but means the high actual density, due to both
work and local currents. In non-commutating pole machines
and in commutating pole machines with bad adjustment, the
local current under the brush may exceed in value the work
current. As this adds to the work current at one edge of the
brush and subtracts at the other edge, the result will be greatly
increased density and high watts tinder one part of the brush.
This may result in burning away one edge of the brush surface,
and is frequently observedin examination of brushes. This usually
is most noticeable where the current passes from the brush to the
commutator, but at the holders of the other polarity, a similar
•action is tending to burn away the commutator copper. How-
ever, the commutator mica does not tend to burn away, and there-
INSULATION PROBLEMS, ETC.
413
fore, if the mica does not wear down mechanically at the same rate
that the copper burns away, eventually the mica stands an in-
finitestimal amount above the copper (Fig. 4) and the brushes will
make a decreasingly good contact with the copper itself. This
increases the loss at the brush contact and increases the burning
action which results in still poorer contact, so that the results
become cumulatively worse. If, however, these periods of burn-
ing are intermittent, due to variable load conditions, and there is
considerable operation at lighter loads or non-burning conditions,
the mica may wear down somewhat and the commutator and
brushes may polish sufficiently during these periods to mask the
direct effects of the burning. But the results may show in
grooving and apparent rapid wear of the commutator face. There
may thus be burning without blackening, or without direct evi-
tl
Fig. 5.
dence of high mica. If, however, the burning pe±iods exceed the
polishing, then visible evidence of burning and high mica may be
found. The brushes may also show this burning and, in some
cases, may honey-comb badly at one edge, or even over the whole
surface. Where one edge burns over a very distinct area, (Fig. 5)
it usually may be assumed that the burnt area could just as well
be cut away, with but little harm to the operation, and possibly
some good, for the fewer the commutator bars that the brush spans
the lower will be the total short-circuit current, as a rule. And,
moreover, by doing away with the localized burning tinder the
brush, it may be assumed that the commutator burns less also.
However, cutting away part of the brush face will crowd the work
current into the remaining portion, so that burning in this portion
414 ELECTRICAL ENGINEERING PAPERS
may be increased. Therefore, narrowing the brush face is not
a general remedy for the trouble, but is successful in some cases.
Burning of the commutator may also be coincident with a
deposit of copper on the brush face. This is usually known as
"picking up copper. " Apparently, in some cases, where the
copper is burnt away from the commutator face, it actually
collects or deposits on the brush face, forming low resistance spots
or surfaces. This gives the equivalent of low resistance brushes,
with consequent increase in local current and still greater burning
action. Moreover, with several brushes in parallel, any one
brush with copper on its face, may tend to take more than its
share of the total work current, which tends to cause further heat-
ing and burning. Increased heating in itself will cause a greater
tendency of the brush to take an undue proportion of the current,
for carbon brushes, unfortunately, have a negative coefficient of
resistance. This means that if any brush carries more than its
share of current and becomes heated thereby, its resistance is
reduced and it tends to take still greater current. This is particu-
larly the case with a large current per brush arm, with a large
number of brushes in parallel on each arm. If one brush, for any
reason, such as picking up copper, takes an undue share of the
current, it may take an increasing share until the contact surface,
or the whole commutator end of the brush, may become red hot
and slowly disintegrate. Such action, if continued, will event-
ually so destroy or injure the brush contact that it carries a de-
creased current, the resistance increases, and eventually the current
falls, not only to normal, but probably far below normal value,
due to bad contact, and the other brushes must then assume an
excess. If other brushes repeat this action, then the condi-
tions become increasingly bad for the remaining brushes, and
they may repeat the same action. In time, all the brushes may
thus become badly burned or honey-combed.
Such conditions are sometimes very difficult to correct.
In some instances, higher resistance brushes bring improve-
ment, while in other cases, lower resistance brushes are better.
If, for instance, the local currents are relatively small, and the
burning or picking up of the copper is due principally to the work
current, then a lower resistance brush may actually reduce the
watts at the contact, even though the local current may be in
creased. If, on the other hand, the local currents are high and
are principally responsible for the burning action, then a still
INSULATION PROBLEMS, ETC. 415
higher resistance may actually reduce the loss. Thus it may
be seen that, in many of these commutator and brush prob-
lems, it is impossible to make a definite statement regarding
the effect of any given make of brush unless one knows what
is actually taking place in the machine. And every time the
brush is changed, the conditions change, for they are more or
less inter-dependent.
Another remedy for some of the above troubles is under-
cutting the mica between commutator bars. This does not re-
move the primary cause of the trouble, namely, the large local
currents or high current density on the brush contact, but it
lessens the harmful effect of these by allowing the brush to main-
tain better contact with the commutator copper, thus reduc-
ing the contact losses. In this way the burning action can be
diminished, in most cases, to such an extent that the commut-
ator face will polish, and this in turn will enable the brush to
make better contact with the copper. Undercutting in general
is advantageous where the commutator mica takes up a large
percent of the total surface, such as 20% or more. The larger
the percentage of mica, the less liable it is to wear away as rapidly
as the copper, and the greater the liability of the brushes being
lifted above the copper, with consequent burning and blacken-
ing. Not only must the percentage of mica be relatively small,
but the actual thickness between two adjacent bars must also be
limited, unless the mica is undercut. The general practice at
present with non-undercut commutators is about 1-32 in. thick-
ness between bars; and even considerably less than this, as^low
as .018" to .020" is not unusual in small machines which are
not undercut. Where commutators axe undercut, there is a pos-
sibility, or liability, of carbon dust collecting in the slots and short-
circuiting between bars, unless the peripheral speed of the com-
mutator is sufficient to keep the slots dear. Therefore, in slow
speed commutators which are undercut, it may be necessary at
times to brush out or dean the slots. In high speed commutators,
or in variable speed machines which intermittently reach high
speeds, there is usually but little difficulty from carbon collecting
in the slots. Obviously, where a commutator is to be slotted,
there is no necessity for maintaining a minimum thickness of
mica, as the limitation in such cases is in the width of the slot,
which may be as much as 1-16 in. in some cases. Wide slotting,
however, is liable to produce brush chattering in some cases.
416 ELECTRICAL ENGINEERING PAPERS
Slotted commutators, while advantageous in some ways,
present certain operating objections in others. Except where
the brushes cover several bars, the slotted commutators are liable
to produce more or less chattering of the brushes, unless fre-
quently lubricated. Therefore, with such commutators, self-
lubricating brushes are recommended. Such brushes usually
contain, or consist of graphite, and, in consequence, generally
they are of lower resistance than ordinary carbon brushes, and
therefore are not as useful in assisting commutation. In com-
mutation pole machines where the resistance of the brushes is of
relatively less importance, graphite brushes are often very satis-
factory. As such brushes are usually soft in texture, they are
not well adapted for wearing away the mica in commutators
which are not undercut.
In the application of the commutating pole to direct-cur-
rent machines, certain conditions have arisen which are pecul-
iar to this construction. For instance, according to the theory
already given above, the flux of the commutating pole should
arise and fall directly in proportion to the armature current.
This means that there must be practically no saturation in the
commutating pole circuit. Probably many of the early diffi-
culties with commutating pole machines were due to a lack of
appreciation of this point. Also, in machines with rapidly
changing current, the commutating pole flux should change
at the same rate as the armature current or the proper local cur-
rent conditions for commutation are not obtained. This means
that the commutating field winding should not be adjusted or
varied in strength by means of a non-inductive shunt, as is com-
mon practice in adjusting series field winding. As the com-
mutating pole winding is normally inductive, then in the case
of sudden change in current, an improper proportion of the
current will flow through a non-inductive shunt at the time
that the armature current is changing. Either no shunt should
be used, or, if one is necessary, it should have the same induct-
ance as the commutating field circuit. The former is prefer-
able but requires most accurate designing.
Another requirement in commutating pole machines, is
accurate setting of the brushes. As a certain definite value of
the local or commutating current is desired in the short-circuited
coil, it is obvious that the coil must be short-circuited by the
brushes at some very definite position with respect to the com-
INSULATION PROBLEMS, ETC.
417
mutating pole. This is especially true in reversing machines.
Otherwise, the commutation in the two directions would not be
alike. Furthermore, an incorrect setting of the brushes, with
respect to the commutating pole, will have a slight effect on the
inherent regulation of the machine. In a direct-current generator,
for instance, with the brushes set so that commutation is exactly
central to the commutation pole, the magnetic flux of these poles
has no resultant effect on the generated e. m. f. of the armature
winding as a whole, and therefore has no effect on the regulation.
But if the brushes are shifted ahead of this correct point in a gener-
Fig. 6.
ator, (Fig. 6) part of the commutating pole flux becomes effective
in generating e. m. f., and in opposition to th.Q armature e. m. £.
A back lead in the same way would tend to increase the armature
e. m. f . Thus the inherent regulation of the generator is affected by
the brush setting. In a motor with commutating poles, a for-
ward lead of the brushes tends to increase the counter e. m. f .
generated and thus tends to lower the speed with increase in
load, while a back lead tends to increase the speed. With per-
fect setting of the brushes with respect to the commutating
poles, and an adjustment of the commutating pole strength
just sufficient to give the theoretically ideal short circuit or
commutating current, the commutating 'poles should have prac-
tically no effect o*r the speed/ But in actual practice, in direct-
current motors, it is found better to actually over-compensate
418 ELECTRICAL ENGINEERING PAPERS
slightly — that is, to make the commutating pole slightly stronger
than the ideal value. This increases the local or commutating
current above the ideal value so that commutation is well com-
pleted before the coil leaves the brush. This gives less spark-
ing, or "blacker*' commutation, at the brush edge, and ap-
parently is more satisfactory from the operator's standpoint.
But this over-compensation has an effect on the speed character-
istics of a motor. It means that the zero point of the current
is shifted backwards, and the resultant effect is similar to shift-
ing the brushes backwards, and it therefore tends to speed up
the machine, as described before. But this speeding-up ten-
dency will vary with the load, as the commutating pole strength
increases with the load. If the motor normally has a "flat"
speed curve, this increase may be sufficient to bring the speed
with load above the no-load speed, and this is an unstable condi-
tion in the operation of constant speed motors. For instance, if
a motor with rising speed characteristics has a high inertia load
suddenly thrown on it, the heavy current required will tend to
speed up the machine, and thus take a still heavier current.
But a drooping speed curve has the opposite effect. Therefore,
in motors built for general market conditions, where the load
conditions may be of any nature, it is desirable that so-called
constant speed motors should always have slightly drooping
speed characteristics at least. But commutating pole motors, if
designed along ideal lines, — that is with high armature magneto-
motive forces — and with comparatively flat inherent speed
characteristics, are liable to be affected, in speed, to a certain
extent, by overcompensation of the commutating pole. In some
cases, this effect may be so small that it does not over-balance
the inherent droop in the speed curve. In other cases, it may
more than over-balance, so that the actual speed curve rises with
load. This is particularly noticeable in adjustable speed ma-
chines for a wide range in speed. Such machines have full field
strength at lowest speed, and here the effect of the local or com-
mutating current on the speed may be very small. At three or four
times speed, however, the main field is very weak, while the com-
mutating current is practically the same as at low speed, and
therefore has three or four times the effect in increasing the speed.
Therefore, such motors are liable to have rising speed curves
at Ijigher speeds, although they may be slightly drooping at
the lowest speeds.
INSULATION PROBLEMS, ETC 419
Obviously, as this effect is a function of the armature cur-
rent, it should be corrected by means of the armature current.
This is readily accomplished by adding to the main field wind-
ing a very small winding in series with the armature, and con-
nected to magnetize in the same direction as the shunt winding
on the field poles. While this might be looked upon as a series
winding, yet its function is that of compensation for commu-
tating pole action. The ampere turns in this compensating
winding are normally very small, being just sufficient to bal-
ance the effect of the excess short circuit current in the corn-
mutated armature coils. In adjustable speed machines, at low
speed and full field strength, this small compensating winding
has but very little effect, as it is so small in proportion to the
shunt ampere turns. At the highest speeds, however, where the
shunt ampere turns are very low and the rise in the speed curve
is liable to be greatest, this compensating winding has the most
effect. It therefore tends to produce proper compensation at
all speeds and loads.
Another phenomenon which has appeared in direct cur-
rent machines, and which, at times, has been falsely credited to
commutating conditions, is that of "pitting," or "eating away"
of the mica between commutator bars. Nearly all manufac-
turers and operators have encountered this difficulty at some
time or other. This has also been credited to high voltage be-
tween bars, too thin mica, quality of carbon brush, use of lubri-
.cants, etc. Some years ago, the writer and his associates made
an extended study of this matter, based upon a very large number
of cases of actual trouble. The results which were derived from
the general practical data from machines in actual service were
so conflicting that no positive conclusions could be drawn di-
rectly from such data. However, eventually the evidence pointed
to oil as apparently one of the fundamental conditions in this
trouble. Extended tests were then made to determine the
effects of oil on the mica, and the results indicated very clearly
that those insulations which absorb oil were liable to pit or eat
away in time. Apparently where the oil could dissolve out the
binding material in the tnica^ ininute particles of carbon or copper,
wotild be disseminated through the mica, thus decreasing its re-
sistance locally. Combustion of these particles would usually be-
noticed as "ringfire" around the onimmtator. Ring-fire is almost
always due toincaadesc^it carbon particles scrapedoff the brushes,
420 ELECTRICAL ENGINEERING PAPERS
but is not usually harmful if the mica adjacent to the spark does
not burn or deteriorate. Experience shows that the ordinary good
grades of mica plate are not affected by such ring-fire, and it is
only when foreign conducting particles penetrate into the plate
that this burning may gradually eat away the mica. It was found
that some binding materials used in building mica-plate were
much more soluble in oil than others, and it was noted that in
those plates with soluble binders, the pitting was most pro-
nounced. In fact, in those grades of mica plate, where the
binder was practically insoluble in oils, no pitting was found,
even under very extreme conditions of test This led then to
one solution of the pitting trouble, namely, the use of what
might be designated as insoluble binders in the mica plate, with
very tight construction of commutator, so that oil could not
penetrate along the sides of the plate, and with care in prevent-
ing oil from getting on the commutator. With the first two con-
ditions, the latter should not be so important, yet one never
knows whether the first two conditions are perfect, especially
after a machine has been in operation for a long period and has
been subjected to severe changes in temperature at the com-
mutator.
After getting at the probability of oil as a pause of pitting,
many careful examinations were made of pitted mica, and in
general, there was evidence that the mica binder had been at-
tacked by oil. In some instances where the operators were ab-
solutely sure that there had never been any oil on the commut-
ator, careful chemical and microscopical analysis showed the oil-
In some cases the mica was actually spongy with oil, and yet
it was claimed that no evidence of oil had ever been noticed on
the commutator.
Much* depends upon the grade of mica used in the plate
for building up in commutators. Certain micas seem to wear
much faster than others, and yet be just as good insulators. The
well known amber micas seem to be by far the most successful
for this purpose. Many attempts have been made to use cheaper
grades of white mica, and, in some cases, with good success, but
the difficulty is that it is not uniformly successful, and trouble
from high mica may develop only after a large number of ma-
etjines have been put on the market. Many costly experiences
of this sort have made the manufacturers very conservative in
this matter* It takes so long to find whether a new mica is good
INSULATION PROBLEMS, ETC. 421
or not, that it Is questionable iii most cases whether it should be
tried out at all.
In the early days, the commutator mica was made com-
paratively thick, and was punched out of solid material. When
the slotted types of direct current armatures came into use,
with their greater sparking tendencies, the old solid thick mica,
used with surface-wound armatures, immediately showed trouble
due to high mica. This soon led to thinner mica, which helped
the trouble somewhat. Then somebody discovered that, by
splitting the mica into very thin plate and reassembling, without
binder, the results were still better, as this split-up mica seemed
to wear or flake off at the edges much better than solid mica.
Then someone discovered that stall better results were obtained
by splitting or flaking the mica and building up into plates, with
a suitable binder Since that time, practically no radical im-
provements have been made in commutator mica, except in the
binding material possibly, and in the better choice of the grades
of mica used, but the mica-plate of today in general is very similar
to the mica-plate of IS or 20 years ago. Of course, refinements
in manufacture have occurred, which, in most cases, however,
have had but little effect on the quality of the product. At
present, it does not look as if a more suitable material can be
found for this purpose Many attempts have been made to
substitute other materials, but these have only proved successful
in certain applications. The built-up mica possesses certain
physical qualifications which have not been obtained with any other
material. For instance, under heating and cooling, the commut-
ator changes in dimensions circumferentially, as well as axially,
and under this action the mica undergoes much more compression
at times than at others. Therefore, a material of a more or less
elastic nature is required between bars, in order to avoid per-
manent compression, with resulting eventual looseness. Struc-
turally the mica-plate meets this condition very well. In the
second place, the material between bars should be one which
wears down properly and yet does not have any cutting or grind-
ing action on the commutator and brushes as it wears off. Mica
apparently meets this condition, while many other mineral com-
pounds, such ate asbestos, appear to have a grinding action. In
the third place, the material should be more or less heat and
spark-resisting. Again, it should be a non-absorbent of oil.
tnica-plate seems to be the oaity material so far which
422 ELECTRICAL ENGINEERING PAPERS
meets all the requirements for general purposes. Hard, inelastic
materials of various sorts have been tried and have not proved
successful. Asbestos in sheets and plates and in conjunction
with other materials, has not proved very satisfactory. Fibrous
and cellulose materials have given good results in some cases,
but are not sufficiently heat and oil-proof for general purposes.
The only material departure has been made in micas used with
undercut commutators. In such cases, white micas and others
which have all the good characteristics of the amber micas, except
their wearing characteristics, can be used, for the undercutting
eliminates the necessity for good wearing qualities. At the same
time, undercutting, as explained before, is advantageous in other
ways.
There are a number of mechanical conditions entering into
the practical side of the problem of commutation. As shown
before, it is very important to maintain good contact between
the brush face and the commutator in order to keep down losses
and burning action. Moreover, good contact in general should
mean good contact over the whole brush face in order to keep down
the current density. Therefore, if the brushes chatter or vibrate
in their holders, or have a rocking action tending to give alternate
""heel-and-toe" contact, obviously the operation is liable to be
affected thereby. Vibrating brush holders, vibrating brushes
and chattering or movements of any kind with respect to the
commutator face, are objectionable and, not infrequently, very
harmful.
Vibrating brush holders may be due to various causes, which
do not show up on the manufacturer's test. The machine may
be so located that its environments are to blame for vibration.
Bad gearing may cause chattering. The foundations or sup-
ports may not be as substantial as on the shop test, so that some
small disturbance may be exaggerated and produce vibrations in
parts or in the whole machine. Sometimes the brushes may
chatter due to lack of lubricant, and this may set the whole brush
holder structure into vibration. Whatever the cause, it is always
best to stop such vibrations as far as possible, especially in ma-
chines handling large currents.
Vibration of brushes in their boxes may be due to badly
fitted brushes, (Pig. 7) or, on machines which have long been
in operation with heavy currents per brush, the brush boxes
may be eaten away inside so that they are not of uniform di-
INSULATION PROBLEMS, ETC. 423
mensions. Low resistance shunts on carbon brushes are for
the purpose of carrying away the current from the brush by
some other path than through the sides of the brush box. How-
ever, due to the raking or dragging action of the commutator
on the brushes, they are liable to bear rather heavily against
one side of the box, especially at the lower edge next to the com-
mutator. Some current will naturally pass to the box, and this in
time will tend to burn away the boxes and the carbons. How-
ever, as the carbons burn away, they are eventually replaced
by new ones; but the boxes are seldom replaced, and in time
they may burn away so that they are larger next to the commut-
ator. The brush then fits tightly only at the top and is free to
move or vibrate or chatter at the commutator end, which is just
the place where such movement should be avoided. Attention
is called to this action in particular on account of the carelessness
often exhibited in regard to the shunts on the brushes.
Fig. 7.
Chattering is not infrequently due to lack of lubrication
on the commutator or in the brushes. When the commutator
gets too dry and has a high polish, a radial, or almost radial
brush may vibrate or chatter just as a pencil does when moved
along a pane of glass. If the commutator is lubricated with
oil to overcome this, care should be taken not to use an excess
of oil or the mica may absorb it. Frequently immediately after
oiling, a commutator shows ring-fire, which is due to combustion
of minute particles of carbon and oil over the top of the mica.
Sometimes chattering is best overcome by the use of self -lubri-
cating brushes. In undercut commutators, the slots are liable
to cause chattering with non-lubricated brushes, giving out a
noise of a pitch comparable with the product of the revolutions
by the number of commutator bars. As oil-lubrication should
be used with caution on undercut machines, practice now usually
calls for some form of self-lubricating brush, partly or wholly
graphite, as has been referred to under "under-cutting.1*
In communicating pole machines it is especially important
that the brushes should not have any heel-and-toe movement,
424 ELECTRICAL ENGINEERING PAPERS
for when the brush makes contact at one edge or the other, the
result is equivalent to rocking the brushes backward or forward,
which, as explained before, is particularly objectionable in such
machines.
In direct-current machines, burnt or black spots will some-
times develop on the commutator at points removed from each
other a distance corresponding to that between holders of the
same polarity. This is sometimes very bothersome, and the
cause of the difficulty is not always easy to find. Any condi-
tion which produces one bad spot may tend to produce similar
spots symmetrically displaced around the commutator. When
one spot is formed, and this spot passes under one brush arm,
the brush contacts at this arm are naturally poorer and the other
brush arms of the same polarity tend to take the load, and the
current density in their brushes is correspondingly increased
during this short period. If there is any tendency toward high
mica, for instance, then the increased current at these points will
produce increased burning away of the copper and burnt spots
may develop. If once developed they may gradually travel
around the commutator until the whole commutator is black.
A local or high mica strip may be the initial cause of the trouble,
or a rough spot on the commutator may give the same result.
But very often, resultant high mica, following the initial cause,
tends to spread the trouble. As soon as such black spots are
noted, further trouble frequently can be headed off by scraping
or cutting the mica below the copper surface in the burnt regions.
One of the most severe conditions that any direct-current
generator can encounter is a dead short-circuit across its ter-
minals, or in the immediate neighborhood of the machine. Very
few machines outside of those of comparatively small capacity
and of low voltage, can stand such short-circuit without severe
flashing. Tests have shown that moderately large direct-cur-
rent generators will give, at the moment of short-circuit, from
20 to 30 times full load current. No ordinary commutating
machine can be built to take care of such a current rush, and
vicious arcing and flashing generally results. This is an inherent
condition in the design. No responsible manufacturer who
knows his business will guarantee to overcome this character-
istic. However, fortunately, the great majority of short-circuits
on direct-current power systems occur at some distance from the
generator, and moreover, in many cases, such short-circuits are tnade
INSULATION PROBLEMS, ETC. 425
through arcs rather than by dead contact, so that the generators
do not get the maximum possible current rush.
It might be suggested that quick-acting circuit breakers
would take care of such extreme conditions by opening at the
loads for which they are set. But this setting is that at which
the tripping mechanism works, and if the current rises rapidly
enough, it may be far in excess of the tripping value by the time
that the breaker actually opens or ruptures the circuit. In fact,
this is just what happens in the case of a severe short-circuit.
Oscillograph tests have shown that the current "rush" on short-
circuit may reach its maximum value in one-fiftieth of a second,
or even less, while the ordinary commercial circuit breakers
seldom operate in less than one-tenth of a second, which, in
reality, is pretty rapid action for a mechanical device There-
fore, it will have to be an extremely rapid-acting breaker which
can get the circuit open before the short-circuit current has risen
to several times the full load value.
One other subject might be considered under commutation,
namely, the influence of the commutating characteristics upon
the permissible range of speed variation and speed adjustment in
direct-current motors. There are two general methods for ob-
taining speed variation in such apparatus, namely, by variation
in the e. m. f . supplied to the armature terminals, and by varia-
tion in the field strength or flux.
In the early development of adjustable speed motors, the
first of the above methods was used almost exclusively, largely
on account of the fact that the commutation problem was more
easily handled with this method. As the motor could be given
full field strength much of the time, and as the reduction in field
strength was not great under any conditions, fairly good com-
mutation was obtainable in general. Where constant torque was
required, this method was fairly satisfactory and economical
However, where constant horse-power was required, obviously, with
this method, the armature current had to be increased directly as
the armature voltage and speed were reduced. Thus the armature
had to be designed for a voltage capacity corresponding to the
highest voltage, and a current capacity corresponding to the
lowest voltage. Thus it became quite large for a given horse-
power rating, and was therefore very tineconornical in material.
However, the larger currents at lower vblta^s did not tepresent
such a hardship m confutation, for %M& increases in current
426 ELECTRICAL ENGINEERING PAPERS
were accompanied by corresponding reductions in speed, which,
made commutating conditions proportionately easier, Thus
the commutating problem was not so serious with this method
of speed control. However, for constant horse-power service,
it was obvious, early in the development, tliat the most econ-
omical arrangement as regards material, would be the use of a
constant voltage across the armature, thus requiring constant
armature current, speed control being obtained by variation in
the field strength. But this meant that the field had its full
strength at the lowest speed, and the field flux would be decreased
directly as the speed was increased. This was the ideal arrange*
ment, but, unfortunately, commutating conditions were very
difficult at the weaker fields, — that is, at the higher speeds. In
consequence, a number of more or less freakish designs were put out,
with the idea of overcoming the commutation troubles, by using
variable field speed control. Some of these designs were satis-
factory from the operating standpoint, but this method of speed
control did not reach its full development, except in the com-
mutating pole type of machine, thus showing that the commut-
ation problem was a serious one in this method of operation.
With properly proportioned commutating poles, the commutating:
conditions are practically independent of the speed, so that,
with their use, the real limitations in speed range are found in
other conditions, such as the instability of very weak fields, etc.
It is evident from the above that, as regards speed regu-
lation in direct-current work, a constant field motor is at a serious
disadvantage compared with one in which the field strength can
be varied. In fact, this holds true for alternating-current as
well as for direct-current motors, as will be shown later. The
alternating-current induction motor as essentially a constant field
machine, and normally operates at constant speed, on a given fre-
quency. In the constant field direct-current motor, it was shown
that speed variation is accomplished by variation in the voltage
applied to the armature. The analogous condition in the induction
motor would be in variation in the frequency applied, and not
in the voltage. This, then leads up to the next subject, namely*
SPEED CONTROL OP INDUCTION MOTORS
Repeating preceding statements, the induction motor is
primarily a constant speed machine when supplied with constant
frequency and e, m. f ., which is the standard condition in all
INSULATION PROBLEMS, ETC. 427
alternating power service. When running at full speed, the
secondary frequency and e. m. f . are both very small, the frequency
being only such as will generate enough e. m. f. to send
the required secondary currents through their own windings
when closed upon themselves. If the secondary resistance
is increased, with a given current flowing, the secondary
e. m. f. must be proportionately increased, and the secondary
frequency, to generate such e. m. f., must also be correspondingly
increased. This secondary frequency, which represents the
departure from synchronous speed, or the "slip," is therefore
always proportional to the secondary e. m. f . Therefore, speed
regulation of the motor, by means of the secondary circuit, means
corresponding, or proportional variation in the secondary frequency
and e. m. f ., and all methods of speed regulation or adjustment of
induction motors through secondary control are based upon fre-
quency and voltage variation in the secondary circuits.
All methods of speed regulation of induction motors may be
classified under two general heads; (1) primary circuit control,
and (2) secondary circuit control.
PRIMARY CIRCUIT CONTROL
Two general methods are practicable, namely, variation in
the number of primary poles, and variation in the frequency
supplied to the primary. The former method is very limited in
the range of control which is practicable. Usually, two operat-
ing speeds can readily be obtained, while three or four lead to much
added complication, and more than four speeds does not appear to
be commercially practicable except in very special cases. For
fine graduations in speed, pole changing is apparently out of the
question. c
By suitable change in the primary frequency supplied to the
motor, any desired speed, or speed range, is obtainable. But in
general, the problem of furnishing this variable frequency is just
as serious as that of speed adjustment of the motor itself on a
fixed frequency. In other words, it takes the difficulty away
from the motor and transfers it elsewhere, but does not eliminate
it.
There are various ways of generating variable frequency.
For instance, an alternator may be driven by an adjustable speed
motor. This should be af direct-current motor, for, if an alter-
nating motor is used, the problem of varying its speed is just
the same as that of the induction motor which is to be regulated.
428 ELECTRICAL ENGINEERING PAPERS
Another way is to connect the alternating-current generator to
an adjustable speed prime mover, such as an engine or water-
wheel. Such methods of regulation require one generating
outfit for each motor to be regulated, except where two or more
motors are to be regulated over the same range at the same time
The method in general is very seldom used.
Other possible methods of regulating the primary frequency
lie in frequency changers of certain types by which a given fre-
quency can be converted to any other frequency by commutation
of alternating current. Various types of such machines are
possible but they possess certain very objectionable limitations,
in that they must commutate currents of frequencies approxim-
ating those of the primary supply system At 25 cycles, this may
be practicable, in some cases, but on 60 cycle supply circuits it is
out of the question. One other serious objection to regulating
the primary frequency is that the frequency controlling device
must have a capacity equal to that of the motor to be regulated, —
that is, the entire input of the induction motor must be handled
by the frequency regulator.
In general, therefore, regulation of induction motor speed by
change in primary frequency is not advisable, and appears to be
practicable only in certain very special applications. This then
brings us to the alternative of secondary circuit control.
SPEED CONTROL BY CHANGE IN SECONDARY FREQUENCY
As brought out before, any speed variation of an induction
motor with unchanged primary frequency means accompanying
change in the secondary frequency and voltage. At standstill,
the secondary voltage is a maximum, and the secondary frequency
is 100 percent of that of the primary, — that is, it is the same as
the primary. At true synchronous speed, the secondary voltage
and frequency are zero. At any intermediate speed, the secondary
voltage generated and the secondary frequency are respectively
equal to the standstill voltage, and the standstill or primary
frequency, multiplied by the slip, in percent, the slip being the
drop from synchronous speed. It should be noted that the second-
ary generated voltage is mentioned, for this is not the same as the
secondary terminal voltage, due to a certain internal drop in the
windings when current is flowing. This internal drop is usually
small compared with the secondary standstill voltage, usually
being from 2 percent to 3 percent except in small motors, and
INSULATION PROBLEMS, ETC 429
therefore may be neglected in any general discussion not involv-
ing exact calculations.
All methods of secondary circuit control in induction motors
include some methods of regulating or controlling the secondary
voltage and frequency. The simplest practical device is the use
of resistance inserted in the secondary circuit. In order to get
the required current, for a given torque, through such resistance,
the voltage must be increased and this requires increase in the
secondary frequency, — that is, drop in speed. But with a given
resistance, if the load or torque is varied, the secondary current
must vary, which means corresponding variation in voltage and
secondary frequency, — that is, in speed. Therefore, speed
regulations by secondary resistance means variable speed with
variations in torque; and constant speed with variation in torque
is only obtainable by varying the resistance inversely with the
current, in order to obtain a constant voltage drop. Such method
of speed regulation is therefore satisfactory only to a limited
extent. Moreover, this method of speed regulation is unecon-
omical, in that there is a rheostatic loss practically proportional
to the drop in speed below synchronism. At half speed, for
instance, half the output of the motor is wasted in resistance.
Obviously what is needed is some arrangement which will
absorb the required secondary voltage in other than resistancef
and which will automatically hold such voltage constant, with
varying current, in those cases where constant speed character-
istics are required for each speed setting The difficulty in ob-
taining such a device is not simply in the voltage range required,
but is largely on account of the range in frequency necessary.
Therefore, all such devices must be of adjustable frequency, and
therein lies the true difficulty, just as in the case of frequency
changers in the primary circuit, as already referred to. The
difficulty, however, is not nearly as serious in the case of regula-
tion of the secondary circuit, for the variable frequency device
needs to be of a total capacity corresponding to the slip, in
percent. Furthermore, where the departure from synchronism
is not large, the actual frequency in the frequency controlling
machine is so low that commutator type alternating-current machines
are permissible up to relatively high capacity. The problem there-
fore resolves itself into one of variable frequency, just as in the
case of primary circuit j^gulatibn, as already referred to, except
that the frequencies and capacities dealt \ffith usually are very
430 ELECTRICAL ENGINEERING PAPERS
much lower in the case of secondary circuit control The problem
is simply easier, but not of a different nature.
In all methods of rating by secondary control, the regulating
device must absorb power corresponding in percent practically
to the secondary terminal voltage, or the secondary frequency,
or slip. This power must be utilized if economical operation is
required. There are three general methods by which it can be
utilized, namely, it may be transformed to mechanical power
and assist in driving the motor shaft, or it may be transformed
to the primary or line frequency and fed back into the line, or it
may be transformed to direct current for use in some other part
of the system. Combinations of these three methods may be
used. For instance, this secondary power may be transformed
to direct current and then be transformed to mechanical power
by means of a direct-current motor connected to the induction
motor load. Or, it may be transformed to direct current and
then re-transformed to the primary frequency and fed back into
the line.
Three types of variable frequency devices have been pro-
posed for absorbing the secondary terminal voltage, namely,
A. C. commutator motors, rotary converters, and commutator
type frequency changers. In the first named, the A. C. commut-
ator motor either delivers its power directly to the shaft of the
induction motor, or to an A. C. generator which returns it to the
line, or to a D C. generator which delivers its current to some
D. C. system or load where it can be utilized. In the second type
mentioned, a rotary converter absorbs at its collector rings the
secondary terminal voltage and transforms it to a proportional
direct-current voltage. The direct-current power is then fed into
a direct-current motor connected with the induction motor load,
or is transformed to the primary frequency by a suitable motor-
generator set. In the third type, a commutator type frequency
changer transforms the secondary terminal voltage and frequency
to a proportionate voltage at the primary frequency, and, by
means of suitable transformers, the secondary power is then re-
turned to the primary supply circuit.
Each of these arrangements possesses some advantages over
the others, and also some disadvantages. The A. C. commutator
motor is a relatively expensive type of machine, especially for
very low speeds. Therefore, when the induction motor to be
regulated is of comparatively low speed, placing the commutator
INSULATION PROBLEMS, ETC 431
motor on the induction motor shaft means a relatively expensive
commutator machine. In such cases, it may be advisable to
either gear it to the load or connect it to a generator which returns
power to the line or delivers it to another system. By such
means, a smaller and higher speed commutator type A. C. motor
may be used, but at a certain expense in auxiliary apparatus. For
a frequency of 25 cycles, the A. C. commutator motor does not
present any undue inherent difficulties if the speed range of the
secondary control is not too large. With 50 percent drop in
speed, for instance, the frequency handled by the A. C. commut-
ator motor is only 12J^ cycles. But with a 60 cycle supply
system, a speed range of 50 percent means that the A. C.
commutator motor must handle 30 cycles, which is a much more
difficult and expensive proposition.
With the rotary converter speed regulation, no new or diffi-
cult problems are involved, either in the transformation or utiliza-
tion of the secondary power. Where the induction motor speed
is not too low, a direct-current motor connected to the shaft may
utilize the direct-current power from the rotary converter. How-
ever, unlike the A. C. commutator scheme above described, the
rotary converter arrangement makes its best showing in connec-
tion with 60 cycle supply systems,- for, with the higher frequency,
the secondary frequency of the main motor is correspondingly
higher for the same speed range, which allows the use of a relatively
smaller rotary for the same percentage of power transformed.
To illustrate— On a 25 cyde supply system, with 30 percent speed
range, the maximum secondary frequency is 7 J^ cycles. A 4-pole
rotary operating at this frequency will run at 225 r.p.m. ; that
is, at this speed, it transforms or utilizes 30 percent of the power
of the induction motor. Considering now, 60 cycles, with the
same speed range, the secondary frequency becomes 18 cydes,
and a 4-pole rotary of 30 percent of the motor capacity will
operate at 540 r.p.m. on this frequency. Obviously, a rotary
converter of much smaller dimensions can be used, than in the
former case. The auxiliary means for absorbing the direct cur-
rent power from the rotary converter can be practically the same
for either frequency. Therefore, with this method, 60 cydes
makes the better showing.
In the third scheme, (Fig. 8) the secondary frequency of the
induction motor is transformed directly to the primary frequency
in a single machine. The auxiliary means for utilizing the trans*
432
ELECTRICAL ENGINEERING PAPERS
formed power consists of suitable stationary transformers with
tap for varying the voltage. As the frequency changer is a rather
unusual device, a brief description of its principle may not be
out of place at this point. As usually built, it consists of an
armature like that of a rotary converter, equipped with both
commutator and collector rings. Unlike the rotary, the field
may consist of a simple " keeper" or ring, (Fig. 9) without wind-
ings, which encircles the armature. Also, unlike the rotary con-
Fig. 8.
Fig. 9.
verter, the commutator is equipped with a double or triple set
of brush holders for handling polyphase current. The ordinary
spacing of the D. C. holders on a direct current rotary would
correspond to one ph&oe of the frequency changer. The arma-
ture can be driven by any suitable small-capacity, adjustable
speed device. Practically the only load carried by the driving
device consists of brush friction and windage.
If such a machine has its collector rings connected to the
main supply system through suitable transformers, a rotating
field will be set up in the armature core (and keeper) which travels
around the core at a speed corresponding to the frequency divided
by the number of poles, just as in an induction motor. If, now,
the core is rotated mechanically in the opposite direction, at a
speed equal' to the frequency divided by the number of poles, then
the magnetic field set up in the core will stand still in space and
could be replaced by an external field excited by direct current,
INSULATION PROBLEMS, ETC 433
just as in a rotary converter. Under this condition, the brushes
on the commutator would tend to deliver current, — that is, alter-
nating current having zero frequency. Under this condition,
the external stationary keeper has zero frequency in it, while the
armature core has normal frequency. Assume now that the core
is rotated either faster or slower than synchronous speed. The
magnetic field set up by the armature winding will travel back-
ward or forward in space at speed corresponding to the departure
of the core from synchronism and the brushes on the commut-
ator will tend to deliver alternating current at a frequency pro-
portional to the departure of the armature core from synchronous
speed. Thus by varying the speed of the armature core from
synchronism, any desired frequency can be obtained at the commu-
tator brushes But the voltage at the commutator brushes is
practically equal to the voltage at the collector rings, regardless
of the speed of rotation, and by varying the voltage supplied to
the collector rings, the voltage at the commutator can be varied
independently of the frequency, which is dependent solely upon the
spead of the armature. Thus, independent control of the voltage
and frequency is obtainable, which makes the device quite flexible
in its application. But such a device has other very desirable
characteristics. As it is primarily one form of rotary converter, we
should naturally expect that it would show some of the small-cop-
per-loss characteristics of the rotary converter. Analysis, however,
shows that it goes even further than this. In a 6-phase rotary
converter, for instance, the armature copper loss averages about
26 percent of that of a corresponding direct-current winding, due
to part of the alternating current being fed directly through to the
direct-current circuit without transformation. But as there is
transformation from one kind of current to another, the operation
is incomplete, and there are certain transformation losses which
are especially large at and near the so-called tap coils, which are
connected to the collector rings. But in a 6-phase frequency
changer of the above type, the transformation is from 6-phase
alternating current to 6-phase current of another frequency, and a
still larger percent of the current passes through without transform-
ation than is the case in a 6-phase rotary converter. In consequence,
the frequency changer has only about two-thirds as much copper
loss as a rotary converter; that is, for 6-phase, it is less than 18
percent of that of a corresponding direct-current machine. More-
over, the tap-coil losses of the fotary converter are practically
434 ELECTRICAL ENGINEERING fAPERS
absent. It thus becomes an extremely effective transforming de-
vice, as far as frequency is concerned.
Such a device is also very economical as regards iron losses-
As it generates voltages, when connected to the secondary ter-
minals of an induction motor, which are proportional to the speed
range, obviously, with moderate speed variations, the magnetic
flux in the armature core will be small compared with what would
be necessary to generate full secondary voltage. Also, even this
reduced induction is at a comparatively low frequency in the
surrounding ring or keeper, and is only at full frequency in the
armature core proper. Evidently therefore, the armature core
and armature teeth sections can be made relatively small where
the range of speed adjustment is small, such as 25 percent to 35
percent from synchronism. This small average core loss, together
with the very small copper loss tends toward a very economical
construction of machine.
In such a frequency changer, the problems of commutation
are very similar to those in the A. C. commutator motor, and at
25 cycles the design becomes simpler and easier than at 60 cycles.
The machine is independent of the speed of the induction motor
to be controlled, which is not the case with the A. C. commutator
motor in its simplest application, namely, direct connection to the
•main motor shaft. Such frequency changer in its simplest form
may be arranged to be self -compensating, and the conimutating
conditions can be brought well within those of well-proportioned
A. C. commutator motors.
In the application of these various speed regulating devices,
two power conditions should be given consideration, — namely,
whether the motor outfit is to develop constant horse power at the
shaft, or constant torque, with the developed power varying in
proportion to the speed. In most cases, in steel mill work, con-
stant torque is all that is necessary, while in a few special cases
constant horse power may be desired.
Where constant torque is preferred, the frequency converter
should prove to be most desirable in many ways, particularly on
account of its flexibility in application, so that a few suitable
sizes should cover range of application. In this feature, and in a
number of others, it has the advantage over the rotary converter
or the alternating-current commutator motor schemes.
Where constant horse-power is required, it is questionable
whether any one scheme has the advantage in all cases. Where
INSULATION PROBLEMS, ETC. 435
the induction motor speed is fairly high, and the frequency is low,
the A. C. commutator motor directly connected to the induction
motor shaft is a good arrangement, as only one regulating ma-
chine is required. If, however, the speed is so low that the A, C.
commutator motor connection to the main shaft is inadvisable, so
that power must be returned to the supply system, then this
arrangement will not compare favorably with the frequency
changer scheme. The rotary converter scheme, delivering
direct-current power to a motor on the induction motor shaft,
also makes a good constant power outfit, but where the speed is
too low to allow an economically proportioned direct-current
motor, the scheme is also at a disadvantage compared with the
frequency changer. But where the frequency changer is used
with constant horse-power, the main induction motor must be
large enough to deliver the rated power to the shaft at the lowest
speed, the excess power being transferred to the line by the fre-
quency changer. If, however, the main motor is operated above
synchronism at its highest speed, by an amount corresponding to
the slip below synchronism at its lowest speed, then the increase
in capacity of the main motor and of the frequency changer, to
give constant power at the shaft, will be only about half as much
as if all the speed variation were below synchronism. This brings
up a point not yet brought out, namely, that some of these ad-
justable speed devices allow operation of the main motor above
synchronous speed. This is particularly true in those cases where
the speed-regulating or auxiliary apparatus can impress its own
frequency upon the secondary of the main motor, and where such
impressed frequency can be independently controlled. In such
cases, by gradually varying the frequency down to zero and then
up in the opposite direction, the main motor can have its speed
varied through the synchronous position.
Various other methods of speed regulation have been pro-
posed, but most of them have not yet seen actual test. Several
schemes have been proposed for utilizing mercury vapor rectifiers
for transforming the secondary current of the induction motor to
direct current. This is one case where a frequency-changing
controlling device does not form a fundamental part of the con-
trol. On the other hand, such method of control is as yet more
theoretical than practical, and moreover, the mercury rectifier is
not yet in general use for power service. At best, therefore, this
method is one of the future.
436
ELECTRICAL ENGINEERING PAPERS
Correction of power factor in induction motors, by means of
a low frequency exciter in the secondary circuit is feasible. In
connection with the above described adjustable-speed devices, it
may be said that almost all such devices can be designed to correct
power factor, as well as to produce change in speed, and, in many
cases, this involves practically no extra complication. For
instance, in the frequency changer method, where the voltage can
be varied independently of the frequency, an increase in the
frequency changer voltage without change in speed would simply
mean the transfer of wattless current from the supply system to
the secondary circuit of the induction motor, and this replaces
the primary wattless magnetizing current. By proper voltage
adjustment, the primary wattless component could be reduced to
zero, or even changed to a large leading, instead of lagging, com-
ponent, with consequent change in power factor from lagging to
leading of any desired value. This simply illustrates the general
method of power factor correction by all these various devices.
Fig. 10.
While on the subject of power factor correction, it may be
stated that only two general methods of power factor correction
are practicable — namely, by means of static condensers connected
across the system, and by means of rotating condensers of some
form. (Fig. 10).
The static type of condenser is commercial on a small scale,
and, possibly, may become so on a large scale in the not far dis-
tant future. Large capacity static condensers can be built at
present, but possibly not at a cost which will compete with the
rotating type.
INS ULA TION PROBLEMS, E TC. 437
Rotating condensers may be divided into two sub-classes, —
namely, synchronous and non-synchronous. The synchronous
type is well known commercially. Usually it is simply a syn-
chronous motor with over-excited field. It may or may not
deliver power as a motor while acting as a condenser.
The non-synchronous condenser is simply a non-synchronous
or induction motor with its secondary excited, instead of its
primary. When acting as a condenser, the secondary is over-
excited. It is therefore somewhat similar to the synchronous
coiidenser, low frequency alternating current, instead of direct
current being used for excitation. The condenser also may act
as a motor delivering power. This type of condenser has not
been used to any extent in this country.
From the foregoing discussion of speed control, it is apparent
that the frequency of the supply system has an important bearing
on the induction motor problem in general. There are only two
accepted standard frequencies in general use in this country, —
namely, 60 and 25 cycles, and both are in use in central power
stations. The tendency for mills and factories to purchase power
from such central power stations, instead of generating it them-
selves, appears to be increasing. This therefore, leads to another
subject of direct interest to steel mill engineers, namely, —
CHOICE OP FREQUENCY
This question is not limited to mill work, but has become
a very general one in the whole electrical business. Some years
ago a committee of steel mill engineers decided upon 25 cycles
as a standard frequency for steel mill work. The reasons for this
decision were amply sufficient at that time and still hold good to
a certain extent. But, in more recent times, the general tendency
of the large central station or power companies toward 60 cycles,
together with the sale of such power to steel mills and other in-
dustrial plants, has changed the situation somewhat. At the
time that the steel mill committee recommended in favor of 25
cycles, there was an apparent tendency of the large power com-
panies toward this frequency. But, as intimated, that tendency
is now reversed, partly -due to improvements in certain types of
apparatus, such as rotary converters. It therefore may be
pertinent to discuss this subject of frequency more fully, in view
of its possible influence on -mill work.
438 ELECTRICAL ENGINEERING PAPERS
The principal loads to be handled by general power or central
station alternating current plants are: first, lighting, including
arc, incandescent, etc.; second, motor power service; and, third,
direct-current service for various purposes, such as railway, etc.
In general, there is no particular question regarding the
better frequency for lighting service, for 60 cycles, for direct use
in both arc and incandescent lamps undoubtedly gives better
results than 25 cycles.
When it comes to motors, either synchronous or induction,
60 cycles present more advantages in general, except for very low
speeds, and, even in this case, with synchronous machines, the
choice is in doubt. In the case of induction motors, however,
there are certain fields where 25 cycles will show better results.
This is in very slow speed work, or very slow speed in proportion to
the capacity. It is a rule in practically all types of generators
and motors that the greater the number of poles, the greater must
be the total magnetizing ampere turns. In windings excited
by direct current, the number of exciting turns may be increased
with increase in the number of poles, at a certain expense in cop-
per, so that the actual exciting or magnetizing current may not be
excessive, even with a very large number of poles — that is, in very
slow speed machines. But in induction motors, the same turns
are used for magnetizing and for generating counter e. m. f . The
latter condition usually so fixes the number of turns, in a given
capacity and speed of machine, that the actual magnetizing
current increases very greatly with increase in the number of
poles, — that is, with decrease in speed, so that, with a large
number of poles, this magnetizing current becomes so large in
comparison with the work current that the characteristics of the
machine are very seriously affected. This increase can be limited
to a certain extent by increasing the dimensions of the machine, —
that is, its cost. Herein is where 25 cycles may give consider-
able advantage over 60 cycles. For instance, a 4-pole, 25 cycle
motor will have about the same speed as a 10-pole, 60 cycle
motor. The 4-pole motor should, and usually does have smaller
magnetizing current than the 10-pole. However, the 4r-pole
machine for the same speed should require more material than
the 10-pole, on account of higher magnetic flux conditions. There
fore, if the 10-pole machine were made of larger dimensions than
the 4-pole, but utilizing the 4-pole magnetic material, its magnet-
izing current might be made fairly comparable with that of the
INSULATION PROBLEMS, ETC. 439
4-pole machine. However, with the same total useful material,
but arranged in larger dimensions, the idle material, such as
frame, supports, etc., will be somewhat greater in the 10-pole
machine of the same speed, and therefore, in general, for equal
speed and equal characteristics, the 60 cycle induction motor
should cost more than the 25 cycle. However, for general power
distribution with relatively small motor capcities, it is not correct
to compare a 10-pole 60 cycle motor with a 4-pole, 25 cycle; for,
in most cases, 60 cycle motors of higher speed can be used, such
as eight, six and four-pole, giving respectivley 900, 1200 and 1800
r.p.m., neglecting the small slip. These higher speed and smaller
number of poles in general more than offset the advantages of the
25 cycle, 4-pole, 750 r.p m. motor as regards cost and character-
istics, and at the same time, the greater choice in speeds is very
advantageous. In 25 cycles, the highest speed is 1500 r.pm.,
with, two poles, and experience has shown that, in size and con-
struction, a 2-pole induction motor has very little advantage over
a 4-pole, except possibly in very small capacities. Therefore, 60
cycles, with its 4-pole 1800 r.p m., 6-pole 1200 r.p.m., 8-pole 900
r.p.m. motors, has a decided commercial advantage over the 25
cycle system with its 2-pole 1500 r.p.m., and 4-pole 750 r.p.m.
motors.
However, when we compare, for instance, a moderate capacity
12-pole, 250 r.p.m., 25 cyde with a 30-pole, 240 r.p.m., 60 cycle
motor we may find the advantage considerably in favor of the 25
cycle, — so much so that if all the motors to be used in a given
plant were of this speed or lower, and there were no other offsetting
advantages for 60 cycles, such as lighting, etc., then the proposi-
tion ;would look like a good one for 25 cycles. However, if only a
small percentage of the total load is represented by such low speed
motors, then the 60 cycle supply may make otherwise a sufficiently
good showing to warrant its use. If, however, we go to the extreme
case of moderate, or even very large, capacity motors at 75 to 100
r.p.m., then we run into almost prohibitive constructions with 60
cycles, either in size or in operating characteristics. At 60 cycles,
such motors are liable to have such low power factors that the
actual current taken by the motors is so large compared with the
work current that, even with poor performance, a very large
motor is required for a given capacity. In 25 cycles however, such
motors can make a very much better showing. Therefore, at the
present time, 25 cycles prepresents the most suitable frequency
440 ELECTRICAL ENGINEERING PAPERS
for such motors. However, hope may be extended for the 60
cycle motor. If such motors are to be operated at constant
speed, or even tinder variable or adjustable speeds, as has been
described under an earlier subject, it is possible and practicable
to overcome the difficulty of the poor power factor and large
current from the supply system by connecting a special low fre-
quency exciter in the secondary circuit of the induction motor,
which will supply the magnetizing current to the secondary
instead of the primary, just as in the non-synchronous type of
condenser already referred to. This does not eliminate the
magnetizing current in the motor, but simply puts it in the
secondary circuit.
The above is a considerable digression from the central station
problem, but it has a direct bearing on the purchase of power by
fmills from central stations. From the above, it is obvious that
or the general sale of motor power to varied industries, the 160
cycle central station has a direct advantage over the 25 cyce,
in the great majority of service.
When it comes to the question of delivering direct current
from an alternating-current system, the 25 cycle system, in con-
nection with rotary converters, is generally assumed to have
considerable advantage over the 60 cycles. However, even that
advantage is disappearing, due to recent advances in the design
of high speed apparatus for converting from alternating to direct
current. Where motor generators are used, 60 cycles in general
allow a more satisfactory choice of converting set; for, in many
cases, for a given capacity, the 60 cycle set can be, given a some-
what higher speed than the 25 cycle. Therefore, the advantage
of 25 cycle, if such exists, must lie in rotary converters. But
recent advances in 60 cycle rotary converter construction have
made the 60 cycle rotary a strong, and pretty reliable competitor
of the 25 cycle rotary, — so much so that, at the present time, quite
a number of electric railways have shut down their own D. C.
generating stations, and are buying power from 60 cycle central
stations through 60 cycle rotaries. This development has removed
one of the most serious handicaps of the 60 cycle system, so that
the present tendency of central station work, and even power
transmission, is strongly toward 60 cycles. The steel mill en-
gineers should therefore keep this tendency strongly in mind.
SOME CONTROLLING CONDITIONS IN THE DESIGN
AND OPERATION OF ROTARY CONVERTERS
FOREWORD-^-This raper was presented at the twenty-eighth annual
convention of the Association of Edison Illuminating Companies
at Hot Springs, Va., September, 1912. At that time, the syn-
chronous booster type of converter was becoming well estab-
lished and it was the author's purpose to show in this paper some
of the conditions of commutation which were encountered in the
synchronous type of machine. — (ED.)
EXPERIENCE shows that the rotary converter is one of the
most satisfactory and reliable of the various types of rotating
electrical machinery. In its efficiency of transformation, its com-
mutation and temperature characteristics, and its operating
characteristics in general, it makes an extremely good showing.
Furthermore, it is a type of machine which has not changed greatly
in the last decade. The more recent developments have been
principally in the use of commutating poles and in a very material
increase in the rotative speeds, these two features, however, being
closely allied, as will be shown later.
In considering the various characteristics of the rotary con-
verter, such as its current and voltage capacities, e. m. f . regula-
tion, commutation and the use of commutating poles, maximum
speeds permissible with a given output, etc., certain fundamental
conditions or limitations in the design, are of controlling import-
ance. In order to obtain a fuller understanding of the possibilities
and capabilities of such apparatus, a brief consideration of these
fundamental conditions will be given.
COMMUTATION LIMITS AND SHORT-CIRCUIT E. M. F.'s
One condition of controlling importance in all commutating
machinery is the commutation. If the machine does not com-
mutate well, then perfections in other features are overshadowed.
High efficiency, low temperature rise, and low first cost, do not
outweigh bad operation at the commutator.
In the ordinary commutating machine, the armature winding,
when carrying current, sets up local magnetic fields, or fluxes,
across which the armature conductors cut and thus generate
441
442 ELECTRICAL ENGINEERING PAPERS
e. m. f.'s, just as when they cut across the main field fluxes. These
local fields, due to the armature ampere turns, usually have peak
values at those points on the armature where one or more armature
coils are short-circuited by the brushes on the commutator. The
conductors or turns which are thus short-circuited, have certain
voltages generated in them, and the brushes are short-circuiting
across these voltages. It may thus be said that there is a certain
short-circuit voltage per armature coil, or between adjacent com-
mutator bars, which may be called the inherent short-circuit e, m. /.
per bar. If the brush is wide enough to cover several bars, then it
short-circuits the voltages of several bars. The average value of
this may be called the inherent brush short-circuit e. m. f. The value
of this latter is of utmost importance in commutating machinery,
for it is upon this, and the resistance of the brush, that the amount
of short-circuit, or "local," current depends.
When the work current, or that which flows to the external
circuit, passes from the commutator to the brush, it should be
distributed evenly over the whole brush contact, providing there
are no disturbing conditions. On the basis of uniform distribu-
tion of current over the brush contact, the minimum current
density at the brush contact would naturally be obtained, which
would be an ideal condition in many ways. This ideal distri-
bution of the work current over the brush contact area will be
called the apparent current density in the brush, to distinguish it
from the true current density, which is due to the resultant current
in the brush, which is always greater than the work current.
The principal cause of the difference between the true and the
apparent densities in the brush lies in the local or short-circuited
current, due to the brush short-circuit voltage just described
This local current distributes over the brush contact according to
the short-circuited voltages under the brush contact, and is thus
practically zero at the middle of the brush, and maxitnum at the
edges, flowing from the commutator to the brush at one side of
the mid-point, and from the brush to the commutator at the other
side. It thus adds to the work current at one side of the brush,
and subtracts from it at the other side, and, not infrequently, the
local current is so great, relatively, that the resultant current at
one brush side will be several times that due to the work current,
while at the other edge it will actually be in the opposite direction.
This condition can be illustrated by Figs. 1, 2 and 3.
SYNCHRONOUS BOOSTERICONVERTERS
443
Fig. 1 represents the conditions where only the work current
flows.
The height ab, which is uniform, represents the value of the
work current.
Fig. 2 represents the conditions under the brush if only the
local current is considered (on the assumption that the field due to
the armature work current is present, but the work current itself
is absent).
ac represents the maximum current in one direction at one
edge of the brush, while de represents an equal and opposite current
at the other edge.
ftgl
fig3.
Fig. 3 represents the conditions when both currents are
present. At one edge of the brush the current is excessive com-
pared to the work current, while at the other edge the current is in
the opposite direction. Obviously, the part of the brush between
d and f in this figure is not only useless, but is worse than useless,
for it not only does not carry any current into the armature, but
actually adds to the current carried by the part between a and /.
Therefore, if the part between d and/ were actually cut away, the
remaining part between a and / would not be worked as hard as
before. This diagram represents a- somewhat extreme condition,
but is not an unusual one, as experience has shown, for in a great
many commutating machines in actual service, improved results
have been obtained by narrowing "the brush contact a certain
444 ELECTRICAL ENGINEERING PAPERS
amount. Obviously, the apparent current density in the brush
would be represented by the height ab, while the true current
density would be represented by the maximum height ag, in Fig- 3,
which may be several times as great as the height ab.
It is evident from consideration of the above figures that the
conditions would be greatly improved by any reduction in the
value of the local or short-circuit current. Narrowing the brush,
as mentioned above, is, to a certain extent, effective. This reduces
the local current, but at the same time it reduces the effective path
for the work current. Another partial remedy would be in the use
of higher resistance at the brush contact, such as is furnished by
certain makes of brush. This would reduce the local current
without reducing the area of the brush contact, but at the same
time it introduces resistance in the path of the work current, which
is practically equivalent to reducing the area of the path. It is,
therefore, to a certain extent, equivalent to narrowing the brush.
A third and more satisfactory method is to reduce the inherent
short-circuit voltage across the brush, while at the same time
retaining the full width of the brush. This, however, is a question
of design and the proportioning of the machine itself, and obviously
such modification cannot readily be supplied to a machine al-
ready constructed. This method of correcting trouble will be
referred to again.
The above figures illustrating the effect of the local current,
do not make the story quite as bad as it actually is. If the brush
contact resistance in a given brush were of constant value, irres-
pective of the current in it, then the above illustrated conditions
would hold. But the brush resistance is actually variable in
effect; that is, at ordinary working current densities, the e. m. f.
drop across the brush contact does not increase directly with the
current, but at a much less rate. This, therefore, is equivalent
to a decrease in the resistance of the brush contact with increase
in current and, unfortunately, this decrease is very pronounced,
even within the limits of permissible current densities. Therefore,
with local current in the brush, giving high densities at the outer
edges, the resistance of the brush may be so reduced as to give even
worse distribution than indicated by Fig. 3.
Cotisidering next, actual permissible brush drops, it may be
noted that, as the local current enters at one side of the brush and
leaves at the other side, the contact resistance in series with the
SYNCHRONOUS BOOSTER CONVERTERS 445
local'cttrrent path is twice the ordinary contact resistance between
brush and commutator. From an examination of a large amount
of data on brush drops, it appears that, with the ordinary com-
mercial brushes, there is about 1 to 1.25 volts drop between the
brush and the commutator when carrying currents of 30 to SO
amperes per square inch. With the brush contact resistance
indicated by these drops, it is evident that with a short-circuit
voltage of 2 to 2 ^ volts across the brush, a local current could
flow which would have a value at the brush edges corresponding
to a current density of 30 to 50 amperes. Assuming a short-cir-
cuit voltage which would give a density of 50 amperes per square
inch at the edges, then with a work current flowing which also
gives an apparent current density of 50 amperes, the resultant
density at one brush edge would become zero, while at the other
edge it would become 100 amperes per square inch. With brushes
having a low contact resistance the conditions would be worse,
and there would be a current of negative direction at one edge of the
brush.
In practice, an inherent brush short-circuit e. m. f . of 2 to
volts is very seldom found, as it is too low a value for commer-
cial designs. However, with much higher short-circuit e. m. f .'s
the conditions would obviously be very much worse than indicated
above, and yet in commutating machines of the non-commutating
pole type, inherent short-circuit e. m. f.'s of 4 or 5 volts would be
considered relatively low, and even 7 or 8 volts would not be
considered unduly high in some cases. Evidently, with such
e. m. f.'s actually across the brush, the local currents in the brush
should be excessive and there should be severe sparking and
burning at the brushes and commutator. However, this im-
possible condition is overcome to a considerable extent by generat-
ing an opposing voltage in the short-circuited coils. This result
is obtained in non-commutating pole machines by shifting the
brushes toward one of the pole corners to such an extent that the
short-circuited coils are cutting across a small part of the main
field flux, which thus generates a small e. m. f . in them. The shift
of the brushes must always be in such a direction that this e. m. f .,
due to the main field, is in opposition to the short-circuit e. m. f .
To illustrate the above case, let it be assumed that the in-
herent short-circuit voltage across the brush at full load, with no
lead at the brushes, is six volts. This, if not partially neutralized,
would generate an unduly high local current, so that the operating
446 ELECTRICAL ENGINEERING PAPERS
conditions would be comparatively bad. Then, assume that the
brushes are shifted so that the short-circuited coils are cutting
across a main field flux sufficient to give three volts. As this is in
opposition to the normal short-circuit e. m. f ., the resultant short-
circuit e. m. f . will be equal to 6 — 3 = 3 volts, which would not
be anything like as bad as before. If, now, the load is removed
from the machine, the brushes still retaining their lead, the three
volts due to the main field will still be generated in the short-
circuit armature coils, and there will be a no-load short-circuit
e. m. f. of three volts, which would set up a local short-circuit
current. However, as no work current is present under this con-
dition, the short-circuit current could obviously be practically as
great as the maximum value of the resultant current at the full
load conditions. Therefore, if three volts short-circuit e. m. f . is
permissible at full load, then four or five volts would be permissible
at no load with practically the same commutating conditions as at
full load. Therefore, the brush could be shifted forward into a
field representing four volts, for instance, and thus at no load the
short-circuit voltage will be four volts, while at full load it would be
6 — 4 = 2 volts. Therefore, by this means an impossible com-
mutating condition, represented by no lead at the brushes, be-
comes a possible and practicable condition by giving a certain
amount of lead. On non-commutating pole machines where a
slight amount of lead is almost always required, a resultant short-
circuit e. m. f . of three volts across the brush may be permissible,
in some cases, at full load, but this cannot be assumed to be true in
all cases, for there are other conditions, besides commutation, which
are dependent upon the amount and distribution of currents in the
brush. Of these other effects, the principal ones may be classified
as, burning of the commutator and brush faces, high mica, and
picking up of copper.
"WEAR" OR "EATING AWAY" OF COMMUTATOR AND BRUSHES
An elaborate and long extended series of tests has shown that
when a relatively large current passes from a brush to a commutator
or collector ring, or vice-versa, there is a tendency for undue
"wear," as it might be called, of either the commutator or brush
face, depending upon the direction of current. If the current is
from the commutator to the brush, then the commutator face
"wears" or is "eaten" away, while with the current from the
brush to the commutator, the brush shows increased wear. This
SYNCHRONOUS BOOSTER CONVERTERS 447
is not a true mechanical wearing away of the commutator or
brush, but is more like an electrolytic action, except that usually
the particles taken from one surface do not deposit on the other.
This rate of wear, as shown by test, is a function of the current
density, the area of surface through which the current passes, and
the contact drop. It is not directly proportional to the contact
drop, or the current, but increases in a much greater proportion
than either, or possibly even more rapidly than the product of the
two. However, this is difficult to determine definitely, for with
the wear once started, the trouble tends to accentuate itself. In
other words, this wear will increase the contact drop and in turn
the increase in contact drop will exaggerate the wear, so that the
action is cumulative. This wearing action is apparently very slight
in amount at true brush densities of SO to 60 amperes per square
inch, with carbon brushes, and if the commutating characteristics
are very good, even much greater true densities are practicable,
possibly up to 100 amperes per square inch. If the apparent
density could be brought up to the true density; that is, if no
current but the work current were present, then this high current
density in the brush might be utilized in well designed machines,
but this implies the absence of all local currents, also, perfect
division of the current between the various brushes and brush
arms, as will be referred to later. These two conditions are rarely
attained in practice, and it would probably be dangerous to
attempt apparent densities of 100 amperes per square inch in the
ordinary carbon brush; but with commutating pole machines,
where an opposing e. m. f . is generated in the short-circuited
armature coils, the condition of relatively small local currents can
be obtained by very careful proportioning of the commutating pole
field. This means therefore that higher current densities in the
brushes are feasible in commutating pole machines in general than
in the non-commutating pole type. This has a direct bearing on
the synchronous converter problem, as will be shown later when
considering high speeds and marimum outputs with a given
number of poles. However, the condition of perfect division of
current between the different brushes has not been obtained in any
simple, practical manner, and therefore some margin in brush
current density must be allowed, even in commutating pole ma-
chines.
448 ELECTRICAL ENGINEERING PAPERS
HIGH MICA
When the maximum current density in a brush contact is
comparatively high, due to local currents or other causes, the
commutator and brush "wear" may be relatively rapid compared
with the mechanical wear due to friction of the brushes on the
commutator. Under this apparent wear the commutator copper
will be slowly eaten away by the current, but the commutator mica
will not be materially affected. The mica must wear down by the
mechanical friction of the brushes, If the "eating away" of the
copper exceeds the mechanical wear of the mica, then a condition
is reached which tends to increase the def ect. As soon as the copper
face is burned even an infinitesimal amount below the mica, the
brush face tends to "ride" on the mica and thus has a reduced
contact on the copper surface, or even none at all. This condition
increases the burning action and eventually results in the so-called
"high mica" where there is an actual gap between the brush and
the commutator face Such a condition, once started, does not
tend to cure itself, except tinder certain special conditions of
operation. This high mica is frequently charged to the use of
"hard" mica, which tends to produce a similar condition.
In some cases, this trouble from high mica may not be due to
either excessive local currents or hard mica, but may be due to a
relatively high proportion of mica to copper surface. Where
comparatively thin commutator bars are used on a machine, the
thickness of mica between the bars is not reduced in proportion,
so that the percentage of mica may be relatively high. In con-
sequence of this high percentage, the mica itself does not wear as
rapidly as where a less total amount is used, while the copper may
eat away at the same rate. This may therefore tend toward high
mica, even where the local currents are relatively small. This
condition of high percentage of mica is found particularly in high
voltage machines where the number of bars is necessarily great
and the thickness, of each bar correspondingly small. On the
other hand, with low voltage machines, the percentage of mica is
relatively less, but other conditions may enter which partly
neutralize this advantage. With lower voltages, for a given
capacity, the current is correspondingly greater and, with a given
contact drop, the losses are correspondingly increased and the
tendency to produce noise by the brushes is also greater. To
overcome these objectionable features, a soft, low resistance brush
is frequently used. This, however, increases the tendency for
SYNCHRONOUS BOOSTER CONVERTERS 449
local currents and thus increases the copper wear, while at the same
time a softer brush has less grinding action on the mica. There-
fore, the low-voltage machine may also tend toward high mica.
A common, and very effective, remedy for this tendency
toward high mica is to "undercut" the mica so that, everywhere
on the brush wearing surface, it lies slightly below the copper
surface. This does not remove the initial cause of the trouble,
namely, the tendency to eat away the copper surface. But it
must be considered that this initial tendency is usually very slight,
and that the major part of the wear is due to the lessening of the
contact between the brushes and the copper, thus increasing the
burning tendency. In consequence of undercutting the mica, the
brush can always maintain good contact with the commutator
face, and thus the actual burning may be so slow as to be practically
negligible. The true gain from undercutting the mica thus lies
in the maintenance of more intimate contact between the copper
and the brush.
This eating away of the commutator face may occur in service
and yet the commutator may polish beautifully. This is found
in some cases where the burning action is pronounced, and yet the
conditions of operat? jn are such that the mica can be worn down
mechanically as rapidly as the copper bums away. This is not
infrequently the case with machines where there are heavy peak
loads of relatively short duration, followed by very much longer
periods of operation with but little load. Under such conditions
the burning action during the peak loads, with a consequent
tendency to high mica, is hidden by the grinding action of the
brushes on the mica during the long periods of operation at light
load, so that the mica is kept practically flush with the copper and
the copper surface is polished. That real burning is present is
often indicated, in such machines, by relatively rapid wear on the
commutator in grooves when the brushes are not well staggered.
"PICKING UP COPPER"
Another condition which sometimes accompanies high current
density in the brushes, is the so-called "picking up of copper."
Apparently, under some conditions, particles of copper, eaten
away from the commutator face, will collect on the brush face.
This may result in glowing at the brush contact, eventual burning
away or "honey-combing" of the brush surface and general
trouble at the commtitator. This difficulty is possibly largely
cumulative in its action. A slight qoating of copper, or copper
450 ELECTRICAL ENGINEERING. PAPERS
"spots," may form on a brush. This gives a more intimate, or
lower resistance, contact with the commutator face. With many
brushes in parallel, an undue percentage of the total current may
then pass through this one point, or brush, or low resistance con-
tact, and the current density at this point may even become so
great that the burning will be excessive. The resistance of the
carbon brush, in itself, does not help this condition, for, un-
fortunately for this case, carbon has a negative coefficient of
resistance so that heating lowers its resistance and thus accentuates
the unequal division of current. One remedy for this condition
is a more uniform contact resistance between the brush and the
commutator. Experience has shown that undercutting the mica
will frequently overcome this difficulty of picking up copper,
particularly so if the machine can be "nursed" until the com-
mutator face acquires a glaze. In some cases, a different grade
of brush will be an improvement, but it is generally difficult to
predict the most suitable brush, unless the inherent commutating
characteristics of the machine are well known. This picking up
of copper appears to be, to a great extent, a function of the cur-
rent density, and is apparently somewhat of an electrolytic action,
the copper eating away from the commutator and depositing upon
the brush. Whatever tends to materially reduce the tendency
for the commutator face to eat away, also tends to reduce the
picking-up effect.
The foregoing features, while apparently minor in nature, are
all of fundamental importance in commutating machinery in
general, and particularly so in the case of commutating-pole
rotary converters, especially in those commutating-pole rotaries
which have what might be called self-contained or "auto" regula-
tion of voltage, such as those with synchronous boosters, or with
regulating poles.
COMMUTATING POLES
In the direct-current generator of large capacity and high
speed the commutating pole has proved to be a real necessity.
In such machines, due to the reduced number of poles and high
armature ampere turns per pole, and consequent large fields or
fluxes set up by the armature, together with the high speed, the
inherent short-circuit voltages across the brush have reached
excessive values, such as 12 to 14 volts at normal load. Such
e. m. f /s, unless largely neutralized, would obviously set up exces-
SYNCHRONOUS BOOSTER CONVERTERS 451
sive short-circuit currents under the brush. As a resultant short-
circuit voltage under the brush of about 2 volts or less at full load
is desirable, it is obvious that some such device as the commut-
ating pole, which introduces an opposing e. m. f. in the short-
circuited armature coils, is practically a necessity; and, further-
more, this opposing e. m. f . must vary practically in proportion to
the load, in order to keep within the permisssible short-circuit limits
across the brush at all loads. Shifting the brushes forward into
an active field to neutralize 12 volts, for instance, is obviously
impracticable, for if a sufficient opposing e m.f., such as 10 volts,
is thus introduced into the short-circuited coils at full load, then
it is so large that it will give prohibitive currents at no load if the
same brush lead is maintained. Therefore with such a machine
of the non-commutating pole type, the brushes must be shifted
with the load, which, in many cases, is not a practicable condi-
tion. Consequently, the commutating pole, with its neutralizing
e. m. f . varying in proportion to the load, is a necessary device
with such machines.
In the rotary converter, however, the conditions are not so
severe. On account of the alternating and direct currents in the
armature winding opposing each other, the resultant armature
magnetizing effect is very smaU compared with that of a corres-
ponding D. C. generator. Therefore the magnetic fields set up by
the armature winding are relatively much smaller, and the inherent
short-circuit e. m. f.'s are also lessened. Therefore, the speed,
current, number of poles, etc., being equal, the rotary converter
would naturally have a materially lower inherent brush short-
circuit e. m. f. than the D. C. generator. In many cases this
e. m. f . may be within the permissible limits of the 6 to 8 volts,
when the brushes are to be given a fixed lead, while the corres-
ponding *D. C. generator might have 10 to 12 volts, which cannot
be sufficiently corrected by a fixed lead. Therefore, the addition
of the commutating pole to the rotary converter usually will not
represent the same gain or improvement as in the D. C. generator,
and its use, in some cases, is more in the nature of a refinement of
operation than an absolute necessity. It may be suggested that,
by the use of commutating poles, the inherent short-circuit e. m. f .
might be made higher, or given the same values as in D. C. gen-
erators, with a consequent gain in cost of the machine, due to the
use of higher speeds or 'a reduced annount of material There
might be some saving, wit&«sucli a procedure, but, on the other
452 ELECTRICAL ENGINEERING PAPERS
hand, there are certain operating conditions in commutating pole
rotaries, not encountered in D. C. generators, which make it
inadvisable, in many cases, to work at as high commutating
limits -as on commutating-pole D. C. machines. In D. C. gener-
ators the armature has a definite magnetizing action, depending
upon the current carried, and this magnetizing action is always
of the same value for the same armature current,regardless of speed,
voltage, or any other condition. The function of the commut-
ating-pole winding is to overcome or neutralize this armature
magnetizing effect at the point where the armature coils are
short-circuited, and in addition, to set up a magnetic field in the
opposite direction to that which the armature winding will tend
to establish. A positive relation is thus established which is
practically unaffected by conditions of operation.
In the rotary converter, however, the conditions are somewhat
different. As the resultant armature ampere turns are normally
very small, the commutating-pole ampere turns required are cor-
respondingly reduced, and have a much smaller value than on a
corresponding D C machine. If the resultant armature ampere
turns always held a definite value, for a given direct current
delivered, under all conditions of operation, then the commutating-
pole winding could readily be given the necessary proportions for
setting up the desired commutating field. But the resultant
armature ampere turns in the rotary can vary over a considerable
range, while delivering a direct current of practically constant
value, and consequently with a constant commutating-pole
strength. Obviously, with a constant commutating-pole strength
and a resultant armature magnetizing effect which can vary over a
considerable range, the resultant short-circuit e. m. f . can also
vary up or down, while commutating a given current, and, if the
variation is excessive, bad commutating conditions will result.
As the average value of the resultant ampere turns of the rotary
converter armature is only about 15 percent of that of the same
armature as a D. C. machine, it is obviotis that a relatively small
unbalancing of the opposing alternating and direct currents may
give a great increase in the resultant ampere turns, which may
greatly disturb the commutating-pole conditions and set up
relatively large resultant brush short-circuit e. m. f.'s.
As such disturbances can actually occur in rotary converters
from several causes, it is usually advisable to make the inherent
short-circuit e. m. f as small as possible, without undue sacrifice in
SYNCHRONOUS BOOSTER CONVERTERS 453
the design of the machine. One condition which can produce the
above unbalancing between the alternating and direct currents is
"hunting." When a rotary hunts it alternately stores energy in
the rotating parts and returns it to the system, during which the
speed of the rotary oscillates with respect to the frequency of the
supply system. While storing energy in the moving parts the
alternating-current in-put is higher in value and, in restoring
power to the line, is lower in value than is required for the average
D. C. output. In consequence, where hunting occurs, the result-
ant armature ampere turns periodically vary in value and there is
a corresponding periodic short-circuit voltage across the brush
which may reach excessive values and cause vicious sparking, or
even flashing.
Another cause of variation in armature reaction is found in
sudden changes of load on a rotary converter. When a sudden
load is thrown on, the rotary may momentarily carry part of its
load as a D. C. generator. This means disturbance of the corn-
mutating field, in the wrong direction, at the very moment that
this field should be at its best. But by avoiding too high normal
short-circuit voltages in the armature winding, the above condi-
tions of undue voltages across the brush can be relatively lessened.
In rotaries with " self -contained " regulation, another dis-
turbance is introduced, which will be described later.
RELATION OP SPEED TO CURRENT CAPACITY, ETC.
In the design of all rotating machines for transformation pur-
poses, as high speeds should be chosen as conditions of economical
design will allow. In D. C. generators, the speeds and the number
of poles have no rigid relation to each other. Thus, a 1000 kw, 500
r. p. m. generator could have from 4 to 12 poles, as desired. For
600 volts, and corresponding currents, it could have 6 poles, for
instance. For half this voltage, with twice the current, it could
have 12 poles, with the same speed. There is therefore a certain
freedom in the design of such a machine.
In the rotary converter, however, the above condition is
absent. The frequency is fixed, which at once fixes the relation
of the number of poles to the revolutions per minute, for the
frequency is the product of the two. Therefore, if a 600 volt, 1000
kw 25 cycle rotary converter would require 6 poles at 500 revolu-
tions, then a machine with half this voltage and twice the current
end with 12 poles, must operate at 250 revolutions, and not 500.
454 ELECTRICAL ENGINEERING PAPERS
In rotaries where the current per brush arm, an£ per pole, is at the
highest permissible limit, the number of poles must vary directly
and the speed inversely, as the total current to be handled. Thus,
for example a 270 volt rotary of large capacity will inherently have
more poles, and will run at a lower speed, than a 600 volt rotary
of equal capacity, which is not necessarily the case with D. C.
generators.
The minimum number of poles in either a rotary converter or a
D. C. generator is practically fixed by the direct current to be
handled. There is a practical limit to the current per brush arm,
as fixed by the permissible current density in the brushes and the
permissible breadth of the commutator face. There are physical
conditions which limit the breadth of the commutator face, de-
pending upon the speed, expansion conditions under temperature,
etc. The maximum breadth being determined for any given case,
the circumferential thickness of the brushes being fixed by limits
of inherent short-circuit e. m. f ., and the current density in the
brushes being fixed by limits of brush and commutator wear, as
before described, it follows that the maximum current per brush
arm is pretty definitely fixed, with present constructions. For a
given total output in current, the limiting current per brush arm
thus fixes the total number of brush arms and poles, and thus fixes
the speed for a given frequency. These limiting conditions are
pretty closely approached in recent 25 cycle rotaries of the com-
mutating pole type.
LIMITING CURRENT PER BRUSH ARM
As indicated above, this is a function of the length of the
commutator, which depends, to some extent, upon the peripheral
speed of the commutator face. With 25 cycle rotaries, consider-
ably lower peripheral speeds are obtainable than with 60 cycle
rotaries, without unduly decreasing the distance between adjacent
brush arms or neutral points The peripheral speed, in feet per
minute, of any commutator is equal to the distance in feet between
two adjacent neutral points, multiplied by the frequency in alter-
nations per minute \ thus, with 25 cycles per second (or 3000
alternations per minute) with one foot, or 12", between adjacent
neutral points, the commutator peripheral speed will be 3000 ft.
per minute. With 60 cycles per second (7200 alternations per
minute) with 8", or 2-3 ft. between adjacent neutral points, the
peripheral speed of the commutator will be two-thirds of 7 200 =
SYNCHRONOUS BOOSTER CONVERTERS 455
4800 ft. per minute. Or, in other words, with equal peripheral
speeds, the 25 cycle rotary can* have 2.4 times as great distance
between neutral points- as a 60 cycle machine. The above relation
of commutator speed to frequency holds true regardless of the
number of poles. It therefore follows that, as the 25 cyde ma-
chine can have much lower peripheral speed at the commutator,
the difficulties of building the commutators should be very much
less. It should therefore be practicable to build much wider
commutators for 25 cycle rotaries than for 60 cycle, and experience
bears this out. With the wider commutators, at 25 cycles, the
brush bearing surface is increased, and thus with a given width of
brush, the number of brushes per arm can be correspondingly
greater than for 60 cycles.
In the second place, even with considerably lower peripheral
speeds at the commutator, the thickness of the commutator bars
will be considerably greater, in most cases, than can be used on
60 cycle machines of the same rated voltage. In consequence,
with a given thickness of brush, fewer bars will be short-circuited
on the 25 cycle machine, than on the 60 cycle, and therefore, in
general, somewhat thicker brushes are permissible for given
inherent brush short-circuit limits. This, again, allows more
current per brush, so that the 25 cycle machine has an advantage
in total current per arm, due to the thickness of brushes, and to
the number of brushes which can be used per arm. On the basis
of a brush %" thick, and a current density of 50 amperes per square
inch, experience shows that a normal rated current of about 1000
amperes per brush arm is possible on large 25 cyde rotaries which
are designed to carry heavy overloads for moderate periods, such
as two hours. With such brush thickness, these rotaries can be
designed for moderately low inherent short-circuit voltages and
abnormal refinement in proportioning of the commutating pole
dimensions is not required, as extremely dose adjustment of the
resultant short-circuit voltage is unnecessary. With thicker
brushes, such as 1" instead of ^", it is possible to operate at
somewhat higher current per arm, possibly up to 1200 amperes,
but this is at a certain expense in higher inherent short-circuit
e. m. f ,'s and less all-around margin in general. With the thicker
brush there is necessarily a greater tendency for local currents,
and therefore doser proportioning of the commutating poles is
required. However, with equally careful proportioning, with
the %" thickness of brush, the results would be relatively better
also.
456 ELECTRICAL ENGINEERING PAPERS
One of the possible troubles with very heavy currents per
brush arm, lies in the difficulty of obtaining equal division of
current among all the various brushes per -arm. The possibility
of trouble is apparently considerably increased, the greater the
current per arm, and if this greater current per brush arm is ob-
tained by the use of thicker brushes rather than by greater length
of commutator, then the result is practically equivalent to working
the machine harder, or nearer the limit. If the operation of two
commutators be compared, one with a %" thickness of brush
and the other with a 1" brush, both having such brush capacity
that they are worked at equal apparent current densities, then,
other conditions being equal, the commutator with the %"
brush will be found in general to give superior results. And ex-
perience has shown that in many cases the 1" brush can have its
width cut down to %" width, with apparent improvement in
operation. However, if both the %" and 1" brush actually show
the same true current density; that is, including all local currents
and unbalancing of current between brushes, then with equally
well proportioned commutating poles, there should be but little
difference in the operation with the two thicknesses of brushes.
Assuming 1000 amperes as representing the limiting current
per arm with %" brushes on 25 cycle machines, then on 60 cycle
rotaries, which usually have brushes of less than %" thickness,
and considerably narrower commutators on account of higher
peripheral speeds, the maximum rated current per arm will be in
the neighborhood of 600 amperes. This smaller current per arm
should apparently handicap the 60 cycle machine compared with
the 25 cycle, but, in compensation, on the basis of equal revolu-
tions per minute, a 60 cycle rotary will have 2.4 times as many
brush arms, which more than makes up for the lower current per
arm. Therefore, from this standpoint it should be feasible to
operate the 60 cycle rotary at considerably higher speed than the
25 cycle. This, however, has not been carried to the limit, in
present practice, as the speeds which would be obtained would be
so high, in some cases, that present commercial conditions will not
allow them. This means, therefore, that we have probably not
yet reached the possible maximum speeds which are practicable
with 60 cydes.
SYCHRONOUS BOOSTER CONVERTERS 457
E- M. F. REGULATION OF ROTARY CONVERTERS
There are three well-known methods for varying the D. C.
e. m. f . of rotary converters, with a fixed A. C. supply voltage.
These three are known as the induction regulator, the syn-
chronous booster, and the regulating-pole methods of control.
In the induction regulator method, an induction regulator varies
the A C. voltage up or down over the range necessary to give the
desired D. C. voltage change. In the synchronous booster
method, an A. C. generator of a capacity corresponding to half
the range of control is operated synchronously with the rotary
converter and, by means of direct-current field control of this
booster, the A. C. e. m. f . supplied to the rotary is varied up or
down. In the third method each main pole of the rotary proper
is made up of two or more smaller poles, one or more of which may
have the excitation varied and by this means the ratio of the D. C.
to the A. C. e. m. f ., in the rotary converter armature itself, may be
changed.
Each of these three methods has certain possibilities, advan-
tages, and disadvantages, depending upon the conditions of oper-
ation The induction regulator method has been used very con-
siderably in the past, but is but little advocated, in more recent
work, due probably to the fact that it is more complicated and
expensive than other methods Both the synchronous booster
and the regulating pole methods of voltage regulation have
been used more or less extensively, however, principally with-
out commutating poles. With the introduction of the latter, a
new problem enters, which has a very considerable bearing on the
design of such apparatus, especially in machines of very large
current capacity where the maximum permissible current per
brush arm is approximated. This problem lies in the variable
armature magnetizing force of the rotary, with change in D.
C. e. m. f , while delivering a given current. Obviously, if
the resultant armature ampere turns vary, the commutating-pole
ampere tun^ should vary a corresponding amount. But if the
commutating-pole winding is in series with the direct-current
armature current, which may not be varied with change in voltage,
the desired conditions are not met by such an arrangement. In
this lies the real problem.
In the rotary converter with synchronous booster, but with-
out commutetmg poles, the dffictaity<of variable armature reaction
458 ELECTRICAL ENGINEERING PAPERS
such as indicated above, exists also, but is usually not serious, as
indicated by the following:
In a rotary converter without synchronous booster or regulat-
ing poles, the ratio of the alternating current to the direct current
is in normal operation pretty definitely fixed. The two currents
oppose each other in the armature winding to such an extent that
the resultant ampere turns vary between about 7 percent and 22
percent of the value in a D. C. machine, or with a mean of about
17 percent, when a full pitch armature winding is used. When a
"fractional pitch" or "chorded" winding is used, this value is
reduced, depending upon the amount of chording. This small
resultant acts in the same direction as on a D. C. machine, and sets
up a small field which affects the commutation slightly. Any-
thing which will increase the ratio of the alternating-current
in-put to the direct current will tend to reduce the resultant
armature ampere turns, for normally the D C. effect is slightly in
excess. Therefore, if the rotary should act, to a certain extent
as a motor, thus receiving some A. C. in-put which is not trans-
formed to direct current, the resultant armature ampere turns will
be reduced, and may even pass the zero value and be in the op-
posite direction.
Again, if the rotary converter armature transforms some
mechanical power received at its shaft, into direct current, so that
the direct-current output is correspondingly greater than the A. C.
input, then the resultant armature ampere turns will be increased.
In the synchronous booster method of regulation, the above is
just what happens. The normal A. C. e. m. f . corresponds to the
midway point on the D. C. e. m. f. range. When the booster
neither "boosts" nor "bucks," the alternating current supplied
corresponds properly to the direct current delivered, and the
resultant armature ampere turns have a mean value of 17 percent
approximately, assuming a full pitch winding. If the D. C. e. m. f .
is boosted 15 percent, for example, the A. C. supply e. m. f. re-
maining constant, then obviously the current supplied to the"
alternating end is increased with respect to the current delivered
by the D. C. end, in the ratio of the percentage boost. Therefore,
the normal resultant armature ampere turns are reduced to
17 — 15 — 2 percent.
Again, when the D. C. e. m. f. is reduced IS percent, the
direct current is increased IS percent relatively to the A. C. and
the resultant armature amperes are increased 15 percent, and
SYCHRONOUS BOOSTER CONVERTERS 459
become 17 -h 15 = 32 percent. Therefore, with a boost and buck
of IS percent voltage, while carrying the same direct-current load,
the resultant armature reaction would be varied from 2 percent
to 32 percent of that of a D. C. armature. This, however, is not
serious in a rotary converter without commutating poles, as even
with 32 percent armature reaction, the conditions are much better
than in a D. C. machine where the armature reaction is 100 percent.
But when commutating poles are introduced the conditions
are quite different. The commutating-pole winding normally
should be equal to the effective or resultant armature ampere turns,
plus the magnetizing ampere turns for setting up the required
magnetic field under the commutating poles This latter com-
ponent usually is small. Counting the effective armature ampere
turns as 17 percent of that of a D. C. armature, and assuming the
magnetizing component as 25 percent, then normally the total
commutating pole turns would be 42 percent. If this 42 percent
is furnished by series excitation from the D. C. end of the rotary,
then it will be constant in value, with a constant value of the direct
current, regardless of the variations in the D. C. e. m. f.
Now, suppose the D. C. voltage is boosted IS percent by
means of a synchronous booster, then the resultant armature
ampere turns fall to 2 percent, as shown before, and, the commut-
ating-pole ampere turns remaining at 42 percent, the difference,
which is 40 percent, wiH all become magnetizing. Therefore, with
a boost of IS percent, the magnetizing component of the com-
mutating-pole winding is increased from 25 percent to 40 percent,
although the current to be commutated is unchanged. In the
same way, if the D. C. voltage is bucked 15 percent, then the
armature ampere turns become 32 percent and the magnetizing
component of the commutating-pole field winding becomes 42 —
32 = 10 percent, when it should be 25 percent. Therefore, the
commutating field strength actually varies up or down 60 percent
from the required value, due to the synchronous booster action,
when, in reality, it should remain constant.
If a resultant short-circuit e. m. f . of 3 volts across the brushes
were aJlowed, then, this 60 percent variation in the commutating-
pole strength, would mean that the inherent short-circuit e. m. f .
is only 5 volts, which is normally neutralized by the commutating
field. However, an inherent short-circuit e. m. f . of 5 volts is so
low that it wou!4 require a rather difficult and expensive design,
and therefore seven to 8 volts inherent short-circuit e. m. f . should
460 ELECTRICAL ENGINEERING PAPERS
be considered in most cases. Obviously, with the above conditions
of variable armature reaction, this would lead to vicious sparking
conditions, especially at heavy overload, or at no-load conditions.
Therefore, series excitation of the commutating pole by the direct
current delivered, should not give satisfactory results. What is
needed is a variation in the commutating pole excitation in accord-
ance with any changes in the armature reaction of the rotary ; that
is, a reduced excitation at boost and increased excitation at buck.
Looking at the variable elements, it may be seen that the
field current of the synchronous booster had its current in one
direction at boost and the reverse direction at buck. Herein
would appear to be a solution of the problem, by putting the
booster field current through an auxiliary winding on the comwmt-
ating fole, so that it opposes the series commutating-pole coil at
boost and adds to it at buck. At first thought, this seems to fit
the conditions perfectly, and, in fact, it does, at one definite direct
current delivered, but does not do it perfectly at other loads.
This is shown by the following figures. Assume the preceding
value of 42 percent series ampere turns on the commutating-pole,
with an additional auxiliary winding having the same percent
ampere turns at full load as the percentage boost or buck. For
example, with IS percent boost, then at full load the auxiliary
winding has 15 percent ampere turns, which are in opposition to
the 42 percent series turns, while at 15 percent buck, at full load,
the 15 percent auxiliary winding acts with the 42 percent series.
(
With 15 percent boost at full load, the armature reaction is
lessened by 15 percent, and the total commutating field excitation
is also reduced 15 percent by means of the auxiliary winding.
Thus the resultant magnetizing component of the field winding
remains at the required 25 percent. At no boost or buck, where
there is no current in the booster field and auxiliary commutat-
ing-pole circuit, the resultant magnetizing component of the com-
mutating-field winding remains at 25 percent, as explained before.
When the booster field is reversed, in order to buck the A. C. voltage,
the auxiliary field ampere turns on the commutating pole also
are reversed, and at 15 percent buck they add 15 percent to the
series commutating-pole winding, and thus give an effective mag-
netizing value of 25 percent instead of 10 percent, as given before.
Hence, with this arrangement, the resultant commutating-field
strength is correct for all the voltages, at the assumed full load
current.
SYNCHRONOUS BOOSTER CONVERTERS 461
Considering, next, the half-load condition, then the armature
Ampere turns, both A. C. and D. C. are halved and the resultant
armature reaction is also halved. However, for the same percent-
age boost or buck in D. C. voltage, the synchronous booster must
operate over the same voltage range as at full load, and therefore, if
the booster field current is the same for the same voltage range,
regardless of load, then the auxiliary winding on the commutating
pole adds or subtracts 15 percent, when, for correct commutating-
field conditions, it should add or subtract only 7% percent.
Therefore, the excess field strength at the two extremes of voltage
is 7J^ percent, or 30 percent of the normal full load magnetizing
component of the commutating-pole winding of 25 percent, which
was assumed as that required to neutralize the assumed inherent
brush short-circuit e. m. f. of 8 volts. A 30 percent component
of this would mean 2 4 resultant volts across the brush. Prac-
tically the same condition would also be found at 50 percent over-
load. This apparently would not be a prohibitive condition if it
represented the full range of operation. At no-load, however, the
excess effect of the auxiliary winding would be 15 percent instead
of 7J^ percent, giving a magnetizing component equal to 60
percent of the normal magnetizing effect of the commutating-pole
winding, or 4.8 resultant volts across the brush, which is higher
than desirable. The above arrangement therefore fails for extreme
changes in load, if the synchronous booster excitation is constant
for a given percentage boost or buck, independent of the load on
the rotary. What is required with this scheme is an excitation of
the synchronous booster, which, for the same range of voltage
variation, increases and decreases with the load on the rotary.
If, for instance, the 15 percent boost or buck could be obtained
at no-load on the rotary, with one-half the fijeld excitation that
would be required for full load, then the excess ampere turns in the
auxiliary winding on the commutating pole would be only 7%
percent total, at no load, instead of the 15 percent indicated above,
and the resultant short-circuit e. m. f . across the brush at no-load
would be 2.4 volts, which is entirely practicable.
From the above analysis, the solution of this problem is in-
dicated. It lies in giving the synchronous booster such
characteristics that its field current varies greatly with change in
the load on the machine. This can be done in various ways, but
most readily by designing the synchronous booster with relatively
ampere turns on its armature compared with its field ampere
462 ELECTRICAL ENGINEERING PAPERS
turns, which is the very construction needed for making the most
efficient and least expensive booster. In such a booster, with very
high armature reaction, the field current can be made to vary over
a relatively wide range, with a given percentage boost or buck,
with any considerable changes in the armature current. With
this construction therefore, it is practicable to build a synchronous
booster type of rotary converter with commutating poles which
will automatically adjust its commutating-pole exciting conditions
to suit changes in both load and voltage, and thus there is no occasion
to revert to the induction regulator, or other outside means of
control.
As a proof of the correctness of the above principles, may be
cited the largest capacity synchronous booster, commutating-pole
rotary converters yet built, namely those recently furnished to the
PIG 4, NEW YORK EDISON 3500 KW SYNCHRONOUS BOOSTER COMMU-
TATING POLE ROTARIES.
New York Edison Company, one of which is shown in Fig. 4.
These machines have a normal continuous rating of 3500 kw at
270 volts, and 13,000 amperes D. C. They must also carry 50
SYNCHRONOUS BOOSTER CONVERTERS ~ 463
percent higher current for two hours, or 19,000 amperes at 270
volts. In addition, by means of their synchronous boosters, they
can vary the voltage from 270 up to 310 or down to 230, while still
carrying the rated current. As these are the most remarkable
machines of this type yet constructed, a more complete decrip*
tion of them will be in order.
The contract included five machines of 3500 kw, of the
horizontal shaft type, and two machines of 3000 kw of the vertical
shaft type, these latter to fit existing foundation plans. Each
3500 kw machine has a normal rating of 270 volts D. C. at 13,000
amperes, and is arranged to boost and buck approximately 15
percent. The synchronous booster therefore has a normal
capacity of about 525 kw. The A. C. end of the rotary is arranged
for 6-phase double-delta connection, requiring about 165 volts
normal. The alternating current handled by each of the six
collector rings is enormous, being approximately 6300 amperes.
As the rotary has 28 poles, the current from each collector ring is
carried by 14 leads, through the armature windings of the booster,
to the rotary converter armature, where it divides into 28 paths, or
one per pole, in the usual manner. The normal alternating
current per armature circuit in .the booster thus becomes 450
amperes, and in the rotary it is 225 amperes. As the machine
has 6 collector rings, with 14 leads per ring, there are 84 windings
on the synchronous booster. Each winding, however, simply
consists of a single group of coils. As the booster has 28 poles, the
same as the rotary itself, it has therefore three groups of coils per
pole, the same as an ordinary three-phase generator. The booster
armature is therefore simply an ordinary type of three-phase
generator, except that the various groups of coils in each phase of
the armature are not connected in series, but are in reality con-
nected in parallel at the collector rings and at the main armature
winding. This arrangement of the booster armature between the
collector rings and the rotary converter armature thus presents a
relatively simple arrangement, and tends toward compactmess
and symmetry in the complete armature ttnit, as shown in Fig. 5.
The brushes on the collector rings are of a metal-carbon
type, arranged in box-holders somewhat like ordinary carbon
brushes. The type of metal-carbon brushes used has a very low
contact drop under normal operation, being approximately 1-10
that of ordinary carbon brushes. The total number of brushes
per ring is 20, and each brush has a section of 2.15 square inches.
464 ELECTRICAL ENGINEERING PAPERS
thus giving a normal current density of 147 amperes per square
inch-
On the direct-current end there are 28 brush arms, giving a
normal rated current per brush arm of 930 amperes, approximately,
and, for the two hours overload, of 1400 amperes approximately.
There are 15 brushes per arm, each of %" x 1%" section, thus
giving an apparent current density of 47}^ amperes per square
inch.
The armature winding of this rotary converter is thoroughly
cross connected in order to equalize the circuits, — a point of very
considerable importance in commutating pole machines. The
field poles are also equipped with heavy, well distributed copper
dampers in order to destroy any tendency to hunt, which is a very
important condition in commutating-pole rotaries, as previously
explained.
The air gap -under each main field pole is one-half inch. The
use of this large gap naturally lessens any tendency for magnetic
noises. As the brushes are of a lubricating type, and as the brush
holders have special devices for adjusting the brush tension very
accurately, the machines run very quietly. The commutator
mica is undercut about 1-32 inch.
As these rotaries are equipped with both synchronous boosters
and commutating poles, very careful designing as regards commut-
ation characteristics, had to be done. The variable armature
reaction, for all the various conditions of load and boost and buck
of the D. C. e- m. f , were carefully calculated, and the commutat-
ing field proportions for correcting these reactions were deter-
mined. In the analysis and example previously given, showing
what conditions of inherent short-circuit e. m. f., etc., could be
allowed, and still obtain permissible results, and armature reaction
of 17 percent under normal conditions and a magnetizing compo-
nent of commutating-pole strength of 25 percent were assumed,
giving a total of 42 percent. It was shown that, with a suitable
auxiliary winding oti the commutating pole, satisfactory conditions
could be obtained from no-load to 50 percent overload, with IS
per cent boost or buck, with an inherent bnash short-circuit e. m. f .
as high as 8 volts. But in these 3500 kw New York Edison ma-
chines, by very careful analysis of the conditions of commutation,
the inherent short-circuit e. m. f . at full load was gotten down
to 6.3 volts instead of 8, while the average armature reaction was
made as low as llj^ percent, instead of 17 percent, both of which
SYNCHRONOUS BOOSTER CONVERTERS
465
conditions are very favorable, compared with the former assumed
permissible limits The normal or series commutating field ampere
turns are 39 percent, instead of 42 percent, so that the magnetizing
component is 27^ percent, the other llj^ percent simply opposing
the normal armature reaction. This large magnetizing component
is obtained by the use of a %" air gap under each commutating
PIG. s,
pole. Such a large gap, in itself, is of direct assistance in obtaining
the desired distribution of the commutating field flux, and thus
makes the design problem somewhat easier
A brief description of some of the unusual features of these
machines may be of interest.
The rotary converter main frame or field is of cast steel, in
order to reduce somewhat the overall dimensions, and keep inside
th,e customer's requirements. The synchronous booster field frame
is of cast irao. Both the main, field and the booster have bolted-in
laminat&d
466 ELECTRICAL ENGINEERING PAPERS
The commutator, main armature, booster armature, and col-
lector rings are each assembled on separate spiders. The com-
mutator spider, however, is pressed on the hub of the main ar-
mature spider, so that the shaft can be removed for shipment,
-without disturbing the connection of the armature winding to the
commutator.
The commutator is of the through-bolt construction with
heavy steel "V-rings." These rings are of large section in order
to avoid distortion under the heavy clamping strains to which they
are normally subjected. The commutator bars are designed to give
the same deflection at all points. The commutator diameter is
120", and the width of exposed face is 30".
The two 3000 kw vertical units for the same company are of
practically the same general design as the 3500 kw except that they
are somewhat smaller, and operate at higher speed. They have 22
poles, and the normal current per brush arm is 1010 amperes,
compared with 930 on the 3500 kw.
An extensive series of tests were made on both the 3500 kw
and the 3000 kw, some of the results of which are as follows :
Armature iron loss at 270 volts, 3500 kw, 16.3 kw.
3000 kw, 13.8 kw.
That is, the normal armature iron loss in both sets is less than
0.47 of one percent, — a remarkably low figure.
The booster armature of the 3500 kw unit showed an iron loss
at 15 percent boost or buck, of 4.6 kw, or less than 0.9 of 1 percent
of its own rating, which is only 15 percent of that of the unit.
At 310 volts D. C , the 3500 kw unit showed 20.1 kw iron loss,
and at 230 volts, 8 8 kw. The total iron losses, including the
booster armature, thus varies between 13 4 kw and 24.7 kw over
the entire range of voltage operation, or between 0.4 and 0.7 of 1
percent of the rated capacity of the machine.
Under all conditions the efficiency of the unit showed apprec-
iably higher than the guarantees, due partly to the relatively low
iron loss, as given above.
The following temperature test results were obtained on the
3500 kw unit:
Amp. V. Hrs. Run Arm.Rise Comm Rise
13000 270 10 31.5°C. 37°C.
12950 231 5 21.5 29.5
12950 317 6 31.5 30
SYNCHRONOUS BOOSTER CONVERTERS 467
On account of lack of certain facilities, a 50 percent overload
temperature test was not made on this unit, but this was carried
out on the 3000 kw unit, as shown in the following results of tests :
Amp. V. Hrs. Run. Arm. Rise Comm.Rise
"11100 270 13 17S°C. 28.5°C.
*166SO 270 2 42 45.4
11100 232 8 165 36
11000 3125 8 27.5 305
In these temperature tests, the first run was made, in each
case, for a period long enough to reach constant temperature. The
other tests followed, while the machines were hot, so that steady
temperature conditions were reached in a shorter time.
In the commutation tests, the results were equally satisfac-
tory. At 270 volts the 3500 kw machine was tested from no-load
up to 19,300 amperes; also, at 310 volts from no-load up to 14,000
amperes; and at 230 volts from no-load to full load; and at 257
volts, up to 15,550 amperes. Under all these conditions the com-
mutation was remarkably good, and this may therefore be taken
as evidence of the correctness of the principles given in the earlier
part of this paper. Furthermore, as an illustration of the accuracy
that is possible in the design of such apparatus, when the funda-
mental principles are sufficiently well known, it may be stated
that, in the case of this 3500 kw unit, aH drawings were made up,
and all the above shop tests made on the completed machine,
without any changes whatever, in the electrical or magnetic
design, from the original engineering design specification. Also,
on shop test, absolutely no re-adjustments were necessary in any
of those parts where provision is usually made for such adjustment
by reason of possible slight variations in material or workmanship,
or inability of the designer to predetermine certain characteristics
with sufficient accuracy.
*These runs were duplicated. The results given are the highest rises obtained from
either test.
SIXTY-CYCLE ROTARY CONVERTERS
FOREWORD— This paper was prepared for the twenty-ninth annual
convention of the Association of Edison Illuminating Companies
at Cooperstown, N. Y., September, 1913. At the time it was
presented, the subject of 60 cycle ^rotaries was becoming a very
"live" one, as improvements in this type of machine were bring-
ing it very rapidly to the front as a competitor of the 25 cycle
rotaries. — (ED.)
ONE of the most significant developments in the past year has
been the greatly increased purchase of large 60 cycle rotaries
by central station plants. Here is an example of a type of ma-
chine which has been more or less discredited in the past, but which,
all at once, is coming prominently to the fore. The present
machine itself is not radically different from its older forms, but it
contains many minor improvements which, individually, do not
stand out prominently, yet, collectively have served to overcome
those little difficulties which formerly were just sufficient to put
the machine in the questionable class. However, a number of
general conditions were also involved in this improvement. It is
the purpose of this paper to show wherein the new machine is
superior to the older type, and also to indicate wherein a number
of modifications, each in themselves of a small amount, have
combined to form a relatively large improvement.
Shortly after the 25 cycle rotary began to be prominent in
electrical work, that is, about 15 to 18 years ago, the problem of
60 cycle rotaries was also presented, as the relatively numerous
60 cycle plants also had need of economical means for transform-
ing to direct current. In consequence, there being a field for 60
cycle rotaries, such machines were built and installed in a number
of places. These early machines were in some cases, fairly suc-
cessful, while, in others, they were failures. Apparently, in some
of these cases of failure, the rotary itself was not entirely to blame,
as it was operated under conditions which would now be considered
impracticable, with our present knowledge and experience.
These early 60 cycle rotaries were very greatly handicapped
in design by the limitations of commercial and manufacturing
practice of those days. Relatively low speeds were considered
necessary from the comnaercial standpoint, and with 60 cycles
469
470
ELECTRICAL ENGINEERING PAPERS
this meant a large number of poles, even for relatively small out-
puts. Also, manufacturing limitations called for relatively low
peripheral speed of the commutators. In those days commutator
speeds of much in excess of 4,000 feet per minute were considered
excessive, and unduly dangerous, both from the manufacturing
and operating standpoints. Herein was a handicap of the worst
sort upon the design. The peripheral speed of the commutator is
equal to the distance between adjacent neutral points multiplied
by the number of alternations per minute (revolutions per minute
x No. of poles). On this basis, 3600 feet peripheral speed with 60
Co/r> mutating Zone
w/ffi no /eacf.
Fig. 1. Commutating Zone with No Lead.
cycles per second (7200 alternations per minute), gave 6 inches,
between adjacent neutral points. Even 4200 feet peripheral
speed gave only 7 inches between neutral points. It is
obvious therefore that, even with this higher peripheral speed of
the commutator, there was undue crowding of the brush holders,
60 CYCLE CONVERTERS 471
which in itself was a bad feature. But the worst feature was in
the fact that, with only 7 inches between commutator neutral
points, the maximum permissible number of commutator bars was
unduly limited. Assuming, for example, a thickness of bar-plus-mica
of 3-16 inches, whichis very thin, the 7 inches between neutral points
would allow about 36 commutator bars between neutral points, or
per pole. This number was ample for 250 to 300 volt machines,
but for 600 volts, experience indicated that it was on the ragged
edge, especially with the field flux distributions obtained with those
early machines. In consequence, 60 cycle rotaries for 250 to 300
volts, rendered a better account of themselves than the 600 volt
machines, and the latter were very much inclined to flash at times,
due to the small number of commutator bars, and a high maximum
voltage between bars.
The field flux distribution had something to do with the
questionable operating conditions. With these earlier machines,
very high peripheral speeds of the armature core were considered
objectionable, for several reasons. One was, that the construc-
tions of that time did not allow very high peripheral speeds of the
armature windings, and, a second reason was that, with the
relatively low speeds, and consequent large number of poles, the
armature dimensions and cost would have been excessive for a given
output. In general, a 12 inch pole pitch was considered as large as
desirable or practicable, which corresponds to 7200 feet per
minute at 60 cycles per second.
With this small pole pitch, in order to obtain a sufficiently wide
commutating zone between the poles, it was necessary to make the
poles relatively narrow. The use of narrow poles led into one
difficulty, as regards flashing, as will be explained later, while
widening the pole and narrowing the interpolar space led into
another difficulty of flashing which was equally serious. The
situation can be illustrated by Figs. 1 and 2. In Fig. 1 the field
flux distribution is indicated for an extreme case of a pole face as
wide as 8 in. and with only 4 in, interpolar space, the total pole pitch
being 12 in., and the poles without polar horns. The "field form,11
which indicates the flux distribution, in this case has a relatively
wide top, and the proportions are such that the maximum e. m. f .
between the bars is about 40 percent greater than the average
3, m. f . per bar. With 36 commutator bars, for instance, at 600
volts, the average volts per bar would be 16 2-3, and the maximum
voltage per bar almost 24, which, in itself, may be a safe figure if
472 ELECTRICAL ENGINEERING PAPERS
never exceeded. However, the flux distribution in the interpolar
space, as indicated by Fig. 1, is such that there is almost no width
to the neutral or commutating zone, and therefore the brushes are
short-circuiting the armature coils in an active field, even at no
load, and, in some cases, this short-circuiting action may be so
great that there are excessive local currents in the brushes. Fur-
thermore, with the neutral point so narrow, a very slight forward
shifting of the brushes, to take care of load conditions, would place
the brush in such a strong field at no-load, that there is danger of
Commutotinq Zone
w/th no /eacf.
Fig. 2. Commutating Zone with No Lead.
flashing when the load goes off, or changes suddenly. Therefore,
with such proportions, the neutral point would be too narrow for
reasonably safe operation. The remedy for this particular condi-
tion, with these former machines, was obviously in the use of wider
interpolar spaces, and consequently narrower poles, the pole pitch
being limited to about 12 inches as previously stated.
60 CYCLE CONVERTERS 473
In Fig. 2 is illustrated the conditions with the wider interpolat
space, and narrower pole face, these being taken as 5}^ in. and 6J^in.
respectively, instead of 4 in. and 8 in. Obviously the flux conditions
in the interpolar space are much better than in Fig. 1 , and it should
be possible to shift the brushes slightly for full load conditions with-
out excessively bad conditions as regards sparking and flashing at
no load. But the same figure also shows that the field flux distribu-
tion as a whole is considerably narrower at the peak value than
in Fig. 1, and therefore the ratio of the maximum value of the
e. m. f . per commutator bar to the average e. m. f . is much greater.
In this case, the maxium per bar is about 65 percent greater than-
the average, and, with 16 2-3 average per bar, the maximum be-
comes almost 28 volts, which is in the danger zone as regards
arcing between bars, except in relatively small machines. There-
fore, in overcoming the sparking and flashing difficulties incident
to the narrow neutral zone of Fig. 1, an equivalent difficulty is
encountered, due to the narrow field distribution, or field form.
Plainly, in these older machines, whichever way we turned, we
were in difficulty.
An obvious remedy for the above difficulties was in the use of
wider pole pitches, which would allow both the commutating or
neutral zone of Fig. 2, and the wider field form of Fig. 1. But in-
creasing the pole pitch, with a given number of poles and given
speed, means increasing the diameter of the armature, and even
though the armature could thereby be narrowed, the cost of the
larger diameter machine would necessarily be somewhat in-
creased. The remedy for this condition was in reduction in the
number of poles as the pitch was increased, thus keeping down the
size of the armature for a given output. But reduction in the
number of poles necessarily means higher speeds, which were
formerly considered commercially objectionable, as no one had
yet been educated up to high speeds. Therefore, between com-
mercial limitations, difficulties in design and manufacturing condi-
tions, the 60 cycle rotary was in a bad way. Mild attempts were
made from time to time to increase the speed by decreasing the
number of poles, but this could only be done commercially in
relatively small steps. In such increases in speed, and decrease
in the number of poles, other difficulties began to be encountered,
such as somewhat poorer inherent conrnrutating characteristics,
due to the higher speed and greater current per brush arm to be
commutated. The higher the speed was made, and therefore the
474 ELECTRICAL ENGINEERING PAPERS
more commercial the machine became as regards size and cost,
the greater were the inherent difficulties in the design. However,
with increased experience in commutator constructions, one great
advance was made by increasing the commutator speeds of the 60
cycle rotaries. Instead of approximately 7 in. between points, the
distance was increased to 8% or 9 inches for 600 volts, giving 5100 to
5400 feet peripheral speeds at the commutator face. This allowed
as many as 45 to 48 commutator bars per pole, which is well
within the range of good direct-current 600 volt practice. This
increase in the number of bars reduced the average and the maxi-
mum volts per bar. In this manner, one of the principal weak-
nesses of the former designs was eliminated Also, by improved
mechanical design which allowed higher peripheral speed of the
armature windings, the pole pitch could be increased to about 16in.,
instead of 12, without an unduly large diameter of armature for
a given output. This also allowed a much better field flux distri-
bution, or field form, such as in Fig. 1, and better interpolar space
of Fig. 2. In consequence, the maximum voltage per bar on the
60 cycle rotaries has been brought down well within accepted D. C.
practice for 600 volt work. For lower voltage work, these limit-
ations have never been so prominent, but the same steps in the
development have proved advantageous in lower voltage rotaries
also.
With increased speed and decreased number of poles, the
current per brush arm on the larger 60 cyde rotaries has gradually
increased until it is practically double what it was on former ma-
chines of same capacity This higher current per arm, with the
increased number of commutator bars per pole, and the higher
speeds, all tend toward making the commutation problem more
difficult. But at this stage in the development, the commutating
pole began to loom up as a possibility in rotary .converters, and
this has furnished the latest important step in the improvement
of these machines. By the addition of commutating poles, still
higher revolutions are permissible than formerly. While relatively
high speed rotaries of large capacity can be made without com-
mutating poles, yet the addition of such poles has rendered the
design less difficult and has allowed still further increases in speed,
which are very welcome in the way of improving the standing of
the 60 cyde rotary. With these higher speeds, and greater out-
puts with a given diameter of machine, the losses have not in-
creased anything like in proportion, so that the difficulties cf the
60 CYCLE CONVERTERS 475
60 cycle rotaries have been gradually increasing until now they are
treading on the heels of the 25 cycle. In fact, when the greater
efficiency of the 60 cycle step-down transformers is taken into
account, the difference between the efficiencies of 60 cycle and 25
cycle converting units in large capacities, is not enough to attract
any particular attention. Thus the use of the commutating poles
has been of advantage principally in allowing higher speeds, with
consequent better characteristics in general.
The modifications above described cover electrical defects
principally. However, there were a number of other minor condi-
tions in these earlier machines which might be considered as
mechanical defects, or mechanical and electrical combined. These
were found principally in the brush holder and commutator con-
structions, and in the materials in the commutator. On the
higher voltage machines, in which a large number of commutator
bars per pole was necessary, the thickness of each bar was, and
still is, very small, and thus the proportion of thickness or mica
between bars to the thickness of the bars themselves is a very
considerable percent. On this account, it has been difficult to
obtain, in many cases, a wear or abrasion of the mica equal to the
so-called copper "wear," which, in reality, is more in the nature of
slow burning than actual wear from friction. No matter how
perfect the commutation may be in appearance, there is always
a slight tendency to burn the face of the commutator by the cur-
rent passing between the commutator and the brushes. This
burning normally may be at an extremely slow rate, but if the
mica does not wear down at the same rate, the result will be that,
after a time, the mica lifts the brush surface away from contact
with the copper, and thus an almost infinitestitnal gap exists
between the brush and the copper of the commutator. This gap
then exaggerates the burning tendency, and the difficulty thus
accentuates itself." The hardness and wearing quality of the mica
must be such that it will always wear down as fast as the copper
burns away, so that normal contact is maintained between the
copper and the brush. Where the percentage of mica is high, and
where the mica varies ia hardness, as is liable to be the case in
practice, it is difficult to avoid more or less tendency to high mica
and consequent trouble. This trouble is also accentuated by high
commutator peripheral speeds, as it is more difficult to maintain
uniform contact between the brush face and the commutator. In
consequence, in 60 cycle rotary converters in geueral, and in high
476 ELECTRICAL ENGINEERING PAPERS
voltages in particular, experience has shown that it is advisable to
undercut the mica slightly, in order to avoid any tendency toward
high mica, and also in order to be able to use brushes which contain
some lubricant such as graphite. It is obvious that where any con-
siderable grinding action by the brushes is necessary, to keep down
the mica, such lubrication is not practicable to the same extent as
where no grinding action is necessary. In consequence, on later
types of 60 cycle rotaries, the commutator mica is usually under-
cut, thus allowing good contact to be maintained, and thus
reducing any resultant burning action to the minimum. The true
causes of the difficulty with high mica were not thoroughly ap-
preciated, in the older 60 cycle rotaries, and, in consequence, in
many cases, brushes of a hard, grinding character were used, with
consequent increased losses and other disadvantages.
Also, on some of the older machines, even with the much lower
peripheral speeds than at present, the design and construction of
commutators were not as nearly perfected as at present, and there
was always more or less danger from unevenness, and other defects,
which, while not showing in themselves any particularly harmful
results, would very often show indirect harm by causing high mica,
sparking, brush troubles, etc.
Furthermore, in many of the earlier machines, the brush
holders were not as rigid or as well suited for operation on high
speed commutators as in present practice. In some cases, the
operating characteristics of the rotary were greatly modified by
simply changing the angle of inclination of the brush to the com-
mutator, or the direction of inclination, or the brush pressure,
etc. Brush chattering was not uncommon, and if there is any-
thing which will surely cause bad commutators and commutation,
it is severe chattering at the brushes, as this prevents good contact
between the face of the carbon and the commutator face.
On many of the earlier machines the brush* holders were not
arranged with due regard to harmful results from incipient arcs
between bars, or in the neighborhood of the brush holders and
brushes. On sudden changes in load, or partial short-circuits, or
even in normal operation in those cases where the maximum voltage
between bars is unduly high, the not uncommon "ring-fire " around
the commutator, due to burning of the carbon or graphite de-
posited on the mica or between bars, may develop into small arcs,
with consequent vaporization of copper, the resultant vapor being
a good conductor. If the brush holder or other parts axe in dose
60 CYCLE CONVERTERS 477
proximity to the point where such small arcs may form, the con-
ducting vapor may bridge across from the commutator face to the
adjacent parts, where there is any considerable difference of
potential between them, and may develop real arcs or flashes
which are of a destructive nature, possibly necessitating the shut-
down of the machine until the commutator can be smoothed up.
In many of the older machines, with their very small distances
between brush holders, and their generally crowded conditions,
and their voltages per bar, such arcs were much more liable to occur
than in the modern machines.
In the development of the 60 cycle rotary converter, there were
other conditions beside commutation, flashing, etc , which had to
be taken into account. The rotary converter is a synchronous
machine, and must follow rigidly in step with its source of e, m. f .
supply, or there will be difficulties in the operation. The early
rotaries, in many cases, were operated from generators driven by
slow-speed reciprocating engines, which did not run at uniform
rotative speed, there being pronounced periodic speed fluctuations
during each revolution. In some cases this condition was so bad
that the generators in the power house would not operate decently
in parallel. As the engines and generators varied in speed period-
ically, obviously the frequency of the electric circuit varied to the
same extent, and any synchronous apparatus operated on such
system would also have to vary in speed to the same extent, if the
conditions were such that the machine should follow the supply
system, as is the case in rotary converters. If the rotary did not
follow rigidly, it would periodically either "under-run" or "over-
run.1' This action is called hunting, and it was very serious at
some of the early plants. Not infrequently the generators at the
power house would not, hold a rigid relation to each other, and
hunted badly.
There are causes of hunting, other than variations in speed
of the prime mover on generating unit, but usually these have been
of secondary importance, and will not be considered further.
The action of hunting of the rotary, with variations in speed of the
generator, may be explained briefly, as follows: The rotary gen-
erates an alternating e. m. f . wave similar to that of the generating
or supply system, but in opposition, or as a counter e. m. f . If
the generator momentarily rtms faster, then its e. m. f . will be
ahead of that of the rotary. A motor current flows, tending to
raise the speed of the rotary to that of the generator. If the
478 ELECTRICAL ENGINEERING PAPERS
generator now drops back in speed, its e. m. f . wave drops back,
and the rotary tends to deliver current to the generating system,
thus tending to slow the rotary converter speed down to that
of the generator. The action in the rotary is therefore one which
tends to speed it up or slow it down to follow the generator. This
action of the rotary, acting alternately as a motor or as a generator,
is what constitutes hunting. Usually this action of following the
generator speed is not a serious one, as a relatively small current
may produce the necessary accelerating or retarding action. The
difficulty is that the rotary may over-run; that is, it may speed up
too much or drop back too much, and thus have an increased
motor or generator action. In other words, this accelerating or
retarding action may exaggerate the swinging effect, just as in the
case of a swinging pendulum, where a very slight force, if timed
just right, may gradually increase the swing of the pendulum. In
those cases in the early rotaries where hunting was most severe,
the periodic speed changes in the generating system were usually
timed just right to cause the rotary to over-run, and thus exag-
gerate the hunting action.
The direct result of this hunting was visible in bad operation
at the commutator. In the normal rotary converter, when run-
ning properly in synchronism, there is practically no armature
reaction in the armature winding, such as is found in direct-cur-
rent machines, for the alternating current supplied to the armature
winding is in opposition to, and practically neutralizes, the magnet-
izing effect due to the direct current delivered. Therefore, as far
as reactions on the field are concerned, the rotary is quite different
from a direct current machine, and, at full-load, the armature has
very little more effect on the field than at no-load. However,
when the rotary is hunting, the current due to the hunting action
above described is not balanced by the direct current delivered, so
that this current acts like that in a straight A. C. or D. C. machine,
and sets up magnetic fluxes in the interpolar space, and under the
edges of the poles, which are harmful in character. These fluxes
create bad commutating conditions by reason of the armature
coils under the brushes being short circuited in a periodically
varying magnetic field, which is not the case when the rotary is
not hunting. Therefore, as a rotary hunts, there is usually periodic
sparking at the brushes, which is in time with the periodic "beat"
which usually can be heard in a machine when it hunts. This
sparking will get more and more severe as the rotary hunts more,
60 CYCLE CONVERTERS 479
until it may become so bad that the machine flashes over. This
hunting in some of the early machines was a very puzzling phen-
omenon, and it was not until its nature and cause were determined
that an effective remedy was applied. The corrective now uni-
versally applied consists in the use of copper dampers, or "cage
windings," in the field pole faces of the rotaries, It is not within
the province of this paper to explain the action of these dampers,
but it may simply be said that they exert, to a certain extent, a
braking action on the over-running action of the rotary, and also
they damp out the field distortions due to hunting, such distortions
materially exaggerating the hunting action. The dampers thus
reduce one source of accentuation of the hunting, and exert a
braking action to overcome the effects of the others. Such damp-
ers were used early on 60 cycle rotaries, but in comparatively
crude forms. Moreover, the angular variations in speed with 60
cyde generating units, were usually greater, in degrees per electrical
cycle, than in 25 cycle machines, due to the much larger number
of poles, and this made the hunting tendencies of the rotaries much
greater, and the damping problem correspondingly more difficult
than in 25 cycle rotaries. In consequence, 60 cyde rotaries should
have had more damping action than 25 cyde machines, while,
on the contrary, they actually had much less. The 60 cycle rotary
was therefore considered a much more delicate machine as regards
hunting, than its 25 cycle brother, and yet the fault was really in
the generating plant in many cases.
The advent of the later 60 cycle turbo generating plants have
been a large item in the successful development of the later type of
60 cyde rotaries. The problem of angular variation in speed of
the prime mover has disappeared, and therefore the dampers on
modern 60 cycle rotaries have to take care of only those secondary
causes of hunting, which were present in the old conditions, but
were masked by the much greater cause in the generating condi-
tions. Also, with the 'newer high speed rotaries, with their
relativdy wider poles, it is practicable to add many more damper
bars per pole than in the older machines, and, in fact, with the
later machines, the problem of hunting is rardy encountered.
However, a new problem in connection with hunting has come
up in connection with the advent of the commutating pole, both
in 25 and 60 cydes. In the commutating-pole generator, the
ampere turns in eadi commutating-pole coil is sufficient to not only
neutralize the entire magnetizing force of the armature winding
480 ELECTRICAL ENGINEERING PAPERS
per pole, but also to furnish an excels flux for conrmutating. In the
connnutating-pole rotary, there is normally but little resultant
magnetizing effect in the armature winding, due to the A. C. and
D. C. currents being normally in opposition, and therefore the
cominutating pole winding must only be strong enough to neutralize
the very small resultant armature reaction, and give, in addition,
a magnetic flux sufficient for commutation. In consequence, the
ampere turns on the commutating-pole winding may be only 30
percent to 40 percent of the total armature ampere turns, con-
sidered as in an A. C. or D. C, machine, whereas, in a D. C. gen-
erator, the commutating-pole winding is usually at least 125
percent of the armature ampere turns. Therefore, the rotary
converter with its 30 percent to 40 percent commutating-pole
ampere turns, instead of 125 percent, cannot act as a generator
or motor with good commutation, as its commutating-pole strength
is then much less than required. As a generator or motor, the
armature reaction may not only over-power the commutating-
pole winding, but may set up a strong magnetic flux in the wrong
direction The commutating conditions may thus become much
worse than if the commutating pole were absent Therefore, the
commutating-pole rotary converter, when acting as a generator or
motor, is a much worse machine than if the commutating-pole
itself were omitted. Herein lies a source of possible trouble with
commutating-pole rotaries. In case there is hunting, the arma-
ture will act alternately as a generator and motor, and, under such
conditions, the magnetizing force of the armature may be such
that it will demagnetize the commutating pole, or even reverse the
flux under it, so that the machine acts in the same way as if it
were operating with the current reversed in the commutating-pole
winding, which would obviously give very bad commutating-
conditions. Therefore, when the commutating-pole rotary hunts,
it represents a worse condition than when a non-commutating-
pole machine hunts to an equal extent. In consequence, with
commutating-pole machines, it is very important to suppress any
hunting tendency, and this, in general, requires somewhat better
damping conditions than in the non-commutating-pole machine.
Therefore, although improved conditions of generation, etc., have
eased up on the damper requirements, yet the necessities of the
commutating poles have made the damper requirements more rigid.
In some cases, this has led to a very curious situation. It is well
known that the commutating pole, whether on a direct-current
60 CYCLE CONVERTERS
481
machine or on a rotary, should not have any closed conducting!
circuit around it, as such closed circuit acts as a secondary or op-
posing circuit in case of sudden change of load, preventing the
commutating-pole flux from rising or falling in step with changes
in load. Therefore,- from the standpoint of commutating-pole
construction, there should be no closed circuit surrounding the
commutating pole itself. However, from the standpoint of the
best arrangement of the damper to prevent hunting, a complete
cage winding, tying all the poles together, as shown in Fig. 3, is, in
general, the most economical and effective. But such a closed
\ O \
; o i
o
b
FIG. 3.
winding forms a rather effective closed secondary circuit around
the commutating pole. One would therefore assume that it is in-
advisable to dose this damper circuit around the commutating
pole, and that a break at a or b in Fig. 3 for instance, would be an
improvement. However, in some instances, experience has shown
that the improvement in the damping action as a whole, in pre-
venting hunting, by tying together at a and 6, more than over-
balances the harmful effects of the dosed secondary circuit around
the commutating pole, caused by the dosed damper winding.
This is not necessarily always the case, the results depending upon
individual and local conditions, to some extent. The same
damping effect as tying together at a and 6 might be obtained
theoretically by special proportioning of the damper on each pole,
but, in some cases, especially on 60 cyde machines, space require-
ments do not permit such proportioning of the damper, so that
it may prove betefcer, ty> tie the dampers, together at a and b. ,
482 ELECTRICAL ENGINEERING PAPERS
A new condition also developed in connection with self starting
of mmtrnit.fl.ting.pnle rotaries. In the older 60 cycle rotaries, start-
ing motors were rather commonly used, due, not to the inability
of the rotary to start itself, but to the effect of the large start-
ing current upon the relatively small generating plants of those
days. Later practice tends strongly toward self -starting, except
in special cases. There are some very considerable advantages in
this self-starting, and at the same time, there are some disadvan-
tages, especially in the 60 cycle rotaries. The greatest advantage
lies in the rapidity with which the rotary can be started from rest
and brought up to synchronism, together with the fact that no
synchronizing devices are required. With the old starting motor,
the machine had to be brought to synchronous speed and then
thrown in step. This was more difficult with 60 cycles than with
25 cycles, and self-starting eliminates this trouble. On the other
hand, while starting and accelerating, the rotary converter is
purely an induction motor of a rather crude sort, and will take a
relatively large starting current — in some cases approximately full
load current from the line — and this current is at very low power
factor ; that is, at least, 90 percent to 95 percent of it is purely watt-
less. When starting a large capacity rotary, this will represent a
relatively large inductive load thrown suddenly on the power
plant.
However, the new condition which developed with the
advent of commutating poles, lies in sparking, and not in the
starting current. As the rotary converter at start acts like an
induction motor, it has a rotating magnetic field flux set up, which
travels around the armature. The armature coils short-circuited
by the brushes form secondaries to, or are cut by, this field, and
therefore have relatively large e. m. f.'s set up in them, which
develop large local currents. The e. m. f 's set up in the short-circuit-
ed coils are usually somewhat greater in the 60 cycle rotaries than
in 25 cycle, due primarily to the fact that there are usually fewer
conductors in series for the normal voltage of the machine, and
therefore the normal voltage per conductor is relatively higher
than in the 25 cycle rotary. In consequence, at start, assuming
that similar voltages are applied for starting both 60 and 25 cycle
machines, the relative voltage per conductor generated by the
rotating field set up by the armature winding will also be higher
in the 60 cycle rotary. Also, the number of commutator bars
covered by the brush will usually be greater on the 60 cycle rotary.
60 CYCLE CONVERTERS 483
In consequence of these two conditions, the short-circuiting action
of the brushes and the sparking will be worse on the 60 cycle
rotaries, but it is liable to be excessive on all large machines.
With the advent of the commutating-pole rotary converter,
a still more difficult condition has been encountered in self -starting,
namely, that the flux conditions in the zone of commutation of the
short-circuited coils are materially higher than in the non-com-
mutating-pole machine. In the latter type, while the short-
circuited coils cut an alternating flux and therefore have local
currents set up in them, these coils, in commutating or reversing
these currents, lie midway between the poles, and therefore in the
region where the conditions of reversal are easiest. But in
placing the commutating pole directly over the short-circuited
coils, the conditions of reversal of the short-circuited current are
made much more difficult during starting. In consequence, during
starting and accelerating, the sparking conditions in the commut-
ating-pole rotary, both for 60 and 25 cycles, are much worse than
in the older non-commutating-pole type. In fact, in the larger
machines, the conditions are so bad that it has been found neces-
sary to add brush lifting devices which will lift all the brushes but
two, during starting and bringing up to speed. This is an added
complication, but it is offset, to some extent, by the fact that,
with the brushes lifted, there is no sparking at all, and therefore
the commutator does not suffer at all during the operation of
starting.
In the earlier 60 cycle rotaries, the question of variable voltage
came up in connection with 250 to 300 volt machines. The
general means of voltage variation in these machines was almost
entirely by means of induction regulators, or step-by-step trans-
formers. It is only in very recent years that the self-contained
units, such as the synchronous booster rotaries, and the regulating
pole type, have been brought forward. For 60 cycle, the syn-
chronous booster appears to be the only really practical method,
due largely to limitations in design and in space requirements.
If commutating poles are to be used, then the regulating pole type
of machine, with main and auxiliary poles, in addition to the com-
mutating poles, requires a very crowded design of field, unless a
larger pole pitch is chosen than in the synchronous booster ma-
chine, in which there are only the commutating and the ma.in poljes.
When synchronous boosters are used with commutating
poles, the problem of proper adjustment of the commutating-pole
484 ELECTRICAL ENGINEERING PAPERS
strength, with varying loads and voltages, comes in. This has
been treated before rather fully in a paper before the association,
and nothing further need be said, except that this problem of
adjustment is just as pronounced in 60 cycle machines as in 25.
Where the range of voltage is relatively small — say, never exceed-
ing 10 percent up or down — it is practicable to so proportion the
commutating-pole windings that, without any automatic or hand-
adjusting devices, good commutation can be obtained over the
whole working range. However, if materially higher voltages are
needed, such as 15 percent to 20 percent up or down, practice
indicates that some auxiliary device is required for automatically,
or by hand, adjusting the field strength at the extreme condition,
which appears to be at no-load with maximum boost or buck.
For this condition, an automatic device has been developed, which,
when the main current falls to a relatively low value — say, one-
fourth full load — automatically short-circuits that part of the
commutating-pole winding which is in series with the booster field.
The same operation cuts into the circuit a resistance equivalent to
the section of the winding cut out. This latter is a necessity, due
to the fact that any variation of the resistance of the booster field
circuit will vary the amount of boost or buck, and thus affect the
main voltage of the machine. Any automatic device therefore
should hold the resistance of the booster circuit constant. Such
devices have been installed on a number of synchronous booster,
commutating-pole type machines. They can be located at the
rotary, and, being purely automatic in their action, require no
attention from the switchboard operators or anyone else. As
such a device operates only very infrequently, but at fairly regular
intervals, such as once or twice a day, it is not liable to wear out
due to excessive operation, or to stick due to non-use. Experience
has shown that, except for extremely wide ranges in D. C. voltage,
only one step is needed in such automatic device.
60 cycle rotary converters are now being manufactured in
relatively large capacities, such as 1000, 1500 and 2000 kw for 270
volts with synchronous boosters, and up to 2500 kw for higher
voltages. Larger capacities, for either voltage, can be constructed
without difficulty, and with as good performance as in the capac-
ities mentioned. The modern 60 cycle rotary converter for either
270 or 600 volts, is approaching very dose to the 25 cycle rotary
in its general characteristics, such as efficiency etc. In commu-
tation, it can be fully equal to the 25 cycle. In general retta-
60 CYCLE CONVERTERS 485
bility, the modern machine is far ahead of the older types. This
development of the 60 cyde rotary therefore removes one of the
most serious handicaps formerly encountered by the large 60 cyde
generating systems.
IRON LOSSES IN DIRECT-CURRENT MACHINES
FOREWORD — This paper was presented before the Schenectady Sec-
tion of the American Institute of Electrical Engineers, March,
1916, before an audience composed almost entirely of engineers
of the_ General Electric Company. It is principally of interest
to designing engineers, in general, and it brings out some of the
problems actually involved in an analysis of the loss conditions
occurring in direct-current machinery. Certain explanations
of eddy current losses, due to saturation of the armature teeth,
are brought put here for the first time, the author believes, and
some approximate methods of calculating these losses are given.
In fact, a careful study of this paper will indicate wherein the
calculation of the no-load losses in any direct-current machine
is, necessarily, more or less empirical, while the conditions with
load are very much worse.
After the presentation of this paper, there was a general
discussion, largely of a constructive and educational nature,
which appears in the Proceedings of the American Institute of
Electrical "Engineers. — (ED.)
IRON loss is a general term to cover a number of losses,
of various kinds, which, by the nature of the tests,
are included in one set of measurements and which, in reality,
should be known as core loss. The term has been used so
promiscuously, without indicating what it really includes, that
many have come to believe that it means the true iron loss and
nothing else. In fact, however, the true iron loss, due to magnetic
conditions in the iron itself may be, in many cases, only a moderate
percentage of the total core loss. What might be called the
normal hysteretic and eddy current losses in the iron itself may
be overshadowed by abnormal losses due to improper flux dis-
tribution and other causes consequent upon incorrect propor-
tioning of flux paths and directions. Also, usually no distinc-
tion has been made between the losses simply located in the iron
itself, and those directly due to magnetic conditions. Further-
more, the losses in non-magnetic parts adjacent to the iron, and
lying in the flux paths, may, in some instances, even exceed the
total losses in the iron. The readily practicable methods of
measuring the core losses show only their sum and there is
no true indication of the relative values of the various com-
487
488 ELECTRICAL ENGINEERING PAPERS
ponents. To separate the total core loss into its various com-
ponents, except by complicated and expensive laboratory meth-
ods, appears to be alrrost impossible However, it is possible
to indicate the various components and their probable causes,
and in some cases they can be segregated very crudely by
calculation.
In most rotating machinery the calculation of the individual
elements, which rrake up the total core loss, is necessarily only
approximate, in comrrercial apparatus. This is due partly
to the fact that there are many possibilities of variation in loss
on account of conditions of manufacture and materials, as
will be described later. This is evidenced by the fact that
two machines, built at different times from the same draw-
ings and the same tested grade of materials, will ofttimes show
materially different core losses. If two such machines vary
twenty -per cent from each other in core loss, it is obviously
impracticable to expect any refinement in calculation closer
than twenty per cent Even if ^e always could come within
twenty per cent by direct calculation and could place any
great reliance upon the results, it would be a great step ahead,
in certain types of apparatus. In the discussion of the various
losses and their causes, given throughout the following paper,
it \\ill be sho\\n \\hy it is impracticable to calculate, with any
exactness, certain of these losses.
In separating the total core loss into its components, two
principal classifications of losses rray be rradc. Cne of these
is eddy current loss, either in the iron laminations themselves
or in other conducting parts wherein e.m.fs are generated
during rotation. Such e.m.fs. will set up local currents where
closed paths are possible, and if such paths are in the lamina-
tions themselves, instead of in neighboring solid parts, it is
simply incidental Eddy current loss in the laminations is,
therefore, not a special kind of loss, and it should rightly be
classed with other eddy losses in the machine.
The second class of losses includes those due to changes
in the magnetic conditions in the iron itself; these are known
as hysteresis losses. These latter are dependent upon the
material itself and not its structure. Lamination is primarily
for increasing the resistance in the eddy current paths and not
for the purpose of affecting the hysteresis. In fact, lamina-
tion may increase the hysteretic losses, for a given volume of
material
IRON LOSSES IN D C MACHINES 489
The principal object of this paper is to show causes for some
of the principal losses. These are usually related to two sets
of frequencies, namely, the normal frequency (revolutions per
second times number of pairs of poles), and some very high
frequency, dependent upon the number of slots, commutator
bars, etc. The hysteretic losses are undoubtedly affected by
these higher frequencies but apparently not to the same extent
as the eddy losses. These high-frequency losses are liable to
be present in most classes of rotating machines, while in some
instances they may overshadow all other losses Certain of
them are characteristic of certain types of machines only, while
others are liable to be present in any type of rotating machine
In most classes of rotating machines, only the no-load core
losses can be measured with any accuracy by ordinarily con-
venient methods of measurement. However, if the various
components of the no-load loss can be approximately deter-
mined, then it is possible to indicate in what way these same
components' will be affected by load. A quantitative deter-
mination of the component losses with load is, however, very
difficult to determine except in a very few classes of machines.
In direct -current machines the principal no-load armature
core losses are the hysteresis loss in the iron, eddy losses in
the iron and copper, and eddy losses in other adjacent conduct-
ing parts, which may be seats of e m.fs. The relative values
of these losses are dependent upon many conditions. In a
thoroughly well designed machine the eddy losses in the
copper and any other parts than the iron should be relatively
small compared with the iron loss proper. Again, the pro-
portion of hysteresis to eddy loss in the iron itself depends
upon many conditions, such as the various frequencies in the
machine, the grade of material, the degree of lamination, the
perfection of the insulation of the laminae from each other,
the distortion of the material in handling and building, the
conditions of punching, treatment during assembly, grinding,
filing, etc. Here, at once, so many variables appear that one
cannot reasonably expect any great accuracy in any prede-
termination of eddy loss in the iron itself. Hysteresis loss is
also affected by some of these conditions-
It is a fact well known to designers that the iron loss -tables
used by transformer engineers do -not directly apply to ro-
tating machinery, but that an increase, in some cases, of one
hundred per cent „ art more is necessary, depending upon the
490 ELECTRICAL ENGINEERING PAPERS
type of machine. This increase is due largely to additional
causes of loss which do not occur to any appreciable extent
in transformers. Some of these additional losses are as follows:
(a) Handling of iron. Experience shows that well annealed
armature iron will have its losses very materially increased by
springing or bending If a lamination is given a decided bend,
beyond the elastic limit, and then is straightened out, the loss
at the part which has been bent may be increased as much as
100 per cent. This fact must be taken into account in ^ ma-
chinery where armatures with many light teeth are used. Here
it is almost impossible to prevent some abuse of the iron,
especially in the teeth, which are the parts usually worked the
hardest. Furthermore, tests have shown that if iron is bent,
even at a small angle, and not beyond the elastic limit, the
loss is materially higher with the iron in this strained con-
dition, although the loss may return to normal when the iron
is allowed to spring back to normal position. And if the iron
is annealed in a curved or warped position, then when straight-
ened out in building the strain is present, with increased loss.
In building up armature cores, undoubtedly part of the iron
is put under stress, especially in the teeth. Any dent in the
iron, produced by hammering or otherwise, also tends tor in-
crease the loss.
(b) A second source of increased loss in the iron is due to
the operation of punching. In shearing the iron a small amount
adjacent to the sheared part is affected much in the same way
as when iron is bent beyond the elastic limit. In transformer
plates this strip next to the sheared edge represents but a very
small percentage of the total volume of each plate or lamina-
tion. However, in armatures with many comparatively long
narrow teeth, this sheared part may represent a relatively
large percentage of the whole plate and, moreover, this is a
part which often has the largest losses. But this may not
have as great effect on the losses as another result of the shear-
ing, namely, the sharp burrs which are left on the iron. These
may be very small or almost negligible in appearance and yet
represent quite a large percentage of the thickness of the plate.
For example, a burr of two mils height, or 1/500 in., seems to
be very small indeed, and yet it is about 12 per cent of the
thickness of a 17-mil lamination. Dies must be maintained
in very good condition to keep the burr below two mils. The
effect of this burr is to bring increased thickness and pressure
IRON LOSSES IN D.C^MACHINES 491
at the edge of the sheets, particularly at the teeth. If the
laminations are all turned one direction in building and the
edges match perfectly the sheets might fit -together so accur-
ately that the burr would cause no extra thickness. But it
is impossible to obtain such accuracy in practise and, there-
fore, the burrs of one sheet "ride" upon the surface of the
next sheet, thus increasing the total thickness of the built-
up iron. In -practise, however, the iron is pressed down to
approximately uniform height throughout. This means that
the burrs carry considerable of the pressure at the armature
teeth and there is more or less of a tendency to cut through
the insulating film on the plates, thus increasing the eddy
current losses. This is 'obviously a variable condition depend-
ing upon the accuracy of building, upon the condition of the
dies, etc., and no method of calculation can take this loss into
account with any accuracy. In small machines with low
voltage per unit length of core i this loss usually is not of great
importance. However, in high-speed large-capacity machines,
it becomes increasingly .important and in some, cases special
means are used for removing tihe burr before insulating the
individual armature plates,
(c) Another source of iron loss, and one which also is be-
yond the scope of calculation, is found in the filing of armature
slots and cores. In ideal armatures with perfect punchings
and assembly, there should be no occasion for filing. However,
the practise, in many cases where the armature iron does not
build up with perfectly smooth surfaces in the slots, is for a
limited amount of filing to be done. Usually this takes off
only isolated high spots, sp that the adjacent laminations are
not bridged over to any great extent by the burrs due to filing.
The tendency of most workmen is to file down to a nicely
polished surface, whereas a coarse filing gives better results
as it tends to break the laminations away from each other.
Filing is most harmful in machines having a relatively high
voltage per unit length pf core. A milling cutter for cleaning
out slots is usually worse than a file, as it produces greater
burring of the edges. However, if the milling is followed by
filing with a very coarse file the results may be just as satis-
factory as with filing alone. Obviously, no method of cal-
culation can show accurately the losses due to such burring-
(d) The iron losses are affected to a certain extent by pres-
sure, that is, by the tightness with which the core is clamped.
492 ELECTRICAL ENGINEERING PAPERS
The loss due to this is probably closely related to some of the
preceding losses, such as bending and springing of plates,
effect of burrs, etc. -In small machines the effect of pressure
apparently is of little moment, but in large very long cores it
may become very appreciable. It is particularly noticeable
in large turbo-generator armatures where the cores are very
wide. In such machines, in attempting to draw the core
down to a sufficiently solid condition as a whole, the parts
next to the end plates are liable to receive abnormal pressure,
with consequent increase of loss -in those parts. For this
reason, it is the practise in some cases to add an extra separation
of paper at frequent intervals near each end of the core. Ex-
perience shows that this equalizes the losses and temperatures
very materially. That this is due to undue pressure and not
to stray field or other conditions, is indicated by the fact that
when high temperatures are found in the iron, at each end
of the core, very often the condition can be relieved by s'mply
lessening the pressure to a comparatively small extent. The
writer has known cases where the temperature in the end sec-
tions of the iron has been reduced 30 to 50 per cent by "easing
off" the end plates. The total loss in the core may not be re-
duced very .much, for the reduction in pressure usually affects
only the end sections to any great extent. Presumably this
loss is due to increased contact between the adjacent plates,
possibly from the burr, but not entirely so, for similar results
have been found in some cases where the burr had been fairly
well removed before enameling the plates. The character of
the enamel coating used for insulating purposes also has some-
thing to do with this. ,
In connection with pressure, the effect of heating of the core
may be considered. Cases have been noted where the effect of
high temperature of the core has been to increase the pressure
between the laminations, due to expansion. This in turn
increased the loss and thus still further increased the tem-
perature. This effect has not been uncommon, to a minor
extent, but a few cases have occurred where the combined
pressure and temperature cumulatively have resulted in ex-
cessive core temperatures. In one case which the writer has
in mind, a certain large machine operated for about two years
without any noticeably high temperature in the core. Then,
in a comparatively brief time, it showed evidence of increas-
ing temperature until finally an entirely prohibitive tempera-
IRON LOSSES IN D.C MACHINES 493
ture showed at one place. Examination showed that the core
was very tight and all evidence indicated that increased tem-
perature was causing increased pressure and thus further in-
creasing the loss. In this machine, fortunately, the construc-
tion of the armature core and winding was such that the end
plates could be released very easily about \ in. on each end.
This was tried as an experiment and the temperatures all
returned to the former normal of about 30 deg. cent. rise.
As an interesting- side issue, it may be mentioned that on this
machine the armature teeth at each end of the core had been
breaking off, although stout brass supporting fingers had been
used. Apparently under the increased pressure, due to heating,
the fingers would be bent away from the core, thus releasing
the tooth laminations. Repeated tightening of the brass
fingers did not relieve this condition. However, when the end
plates were released J in. at each end of the core, the brass
fingers were then sprung in against the teeth and afterwards
remained in position so that no breakage of tooth laminations
was ever reported afterwards.
Obviously, with losses dependent upon pressure, no extreme
accuracy in calculation of such losses is possible. However,
in moderately small size machines, and especially in those of
very moderate frequency and of very low voltage per unit
length of core, the effect of pressure is not serious, within a
moderate range of practicable pressures.
(e) Another source of iron loss, but which is not in the arm-
ature core, is that of the pole face, ,due to the tufting or bunch-
ing of the flux between the field pole and the armature teeth,
where slotted armatures are used. Obviously, with all other
conditions the same, this pole face loss will depend upon a
number of variables in the lamination of the material itself.
The effect of burrs from punching, the burring over of the
surface due to turning, the effect of pressure, etc., all appear
in the pole face loss. Therefore, it is evident that great ac-
curacy in the calculation of such loss is impossible, in com-
mercial apparatus. There are other conditions that affect
this pole face loss which will be considered later under this
subject.
Armature Ring Loss. The true iron loss in the aimature
ring is dependent upon the total flux per pole, distribution of
flux, rate of change of flux, etc. The problem is much com-
plicated by the fkct that the flux distribution in the ring usually
494 ELECTRICAL ENGINEERING PAPERS
is not uniform, that is, certain parts of the core have higher
maximum densities 'than other parts However, in ordinary
practise the core densities used are relatively low, so that the
losses can be Approximated by averaging the inductions in
certain parts. However, the rate of change of flux in the
ring is dependent, to a certain extent, upon the flux distribution
in the air gap and armature teeth, and this introduces some
error, always in the direction of increased loss.
The distribution of flux in the armature ring is also depend-
ent upon the effective length of the various flux paths. These
latter will naturally depend upon various conditions, such
as the number of poles, diameter of armature; flux distribution
in the air gap and teeth, etc. Therefore, any method which
does not take this distribution into account is necessarily only
approximate. However, in practise there are so many other
variables, as already described, in connection with manufactur-
ing conditions, such as burring, filing, etc., that empirical rules
have been developed, based upon numerous tests, which ap-
proximate the armature core loss in a standard type of ma-
chine about as- accurately as any attempt toward exact cal-
culation.
Armature Tooth Losses at No-Load. Apparently the flux
densities in the armature teeth can be calculated with more
accuracy than in the various parts of the core, for in the teeth
the fluxes are limited to fairly definite paths. Therefore,
exclusive of the losses due to manufacturing conditions, as
already described, the tooth losses can be fairly accurately
calculated, probably with much greater accuracy than many
other losses, as will be described. The tooth losses may be
considered further as follows:
The flux density in each individual armature tooth passes
through a cycle, indicated by the shape of the field form. With
the field form of the shape illustrated in Fig. 1, the tooth den-
sity will be a maximum at A, and this density will remain
practically constant as the tooth moves toward C until the
point B is reached. It will then decrease as the ordinate of
the field form curve decreases and will reach zero value at C,
The cycle of flux change is not sinusoidal, and therefore, the
actual tooth iron loss should not agree with that represented
by the usual iron loss curves based upon sinusoidal changes
in induction. The difference, however, may be relatively
small in the ordinary types of machines. The error may be
IRON LOSSES IN D.C. MACHINES 495
taken care of by some suitable correcting factor, which of
course, will be only approximate for the average case
The density in the armature teeth is involved in the iron
loss This density is not uniform over the entire depth of
the tooth, with the usual parallel-side slots, for the section
of the tooth tapers off. This difference of section, in small
diameter machines, may be very considerable. However, a
higher density at the base of the tooth, tending to give higher
iron loss, is compensated for, to some extent, by the reduced
volume of material. In consequence, the mean section at
some point from one-half to two-thirds the way down the
tooth may be taken and the mean density and volume of ma-
terial, based upon this section, may be used for approximating
the iron loss. The accuracy of this method will be dependent,
to some extent, upon the actual density used. For instance,
if both the minimum and
maximum densities in the
tooth are relatively low, then
the loss calculated for the
[ |" mid-point density, at the mid-
j j point section, will be closer
B A to the true loss than if the
maximum density is exces-
sively high.
pIG> i Armature Copper Eddy Cur-
rent Loss at No-Load. There
may be a number of eddy current losses in the copper, some of
which are of a minor nature. However, there may be two
relatively large losses, depending upon the design of the ma-
chine. One of these is due to the flux from the' field poles
entering the armature slots and cutting the conductors. This
is, to a certain extent, a function of the saturation of the tops
of the armature teeth. It is also dependent upon the width
of the slot opening Compared with the iron-to-iron clearance.
At first thought, one would say that the larger the air gap
the more would the lines from the pole pass into the tooth
top. However,- the opposite is the case, for the larger the gap,
the nearer do the lengths of paths into the slot approach to
the iron-to-iron clearance, in percentage.
In moderate size machines with relatively small air gaps
and moderate slot widths, the eddy current loss from fringing
into the top of the slot is comparatively ,small, and, as a rule,
496
ELECTRICAL ENGINEERING PAPERS
no special precautions need be taken to minimize it. This
particular loss is usually greatest in high-voltage, large-capac-
ity turbo-alternators, where relatively wide slots, up to 1 5
in. or more, may be used, and where the air gaps are very large.
In such cases lamination of the top conductors to avoid eddies
from this cause may be desirable.
The second source of eddy current loss in the copper, which
is liable to be larger than all others combined, is due to the
peculiarities of flux distribution in the armature teeth. Let
Fig. 2 represent the magnetic conditions in a given machine.
It is evident from this figure that under the central flat part
of the field form, the armature teeth are worked at a uniform
induction, assuming that there is no field distortion. How-
ever, at the edges of the pole the tooth density decreases
slightly. If the saturation of the teeth under the flat part of
the field form is very high
(materially above 120,000
lines per sq. in.), the ampere-
turns required to magnetize
the teeth may be very con-
siderable. However, at the
edge of the pole a compara-
tively small decrease in the
flux density in the teeth (15
to 20 per cent) will mean a
relatively enormous decrease
in the ampere-turns for the teeth. For instance, the tooth c
in Fig. 2, under the central flat part of the field form, may
require 2000 ampere-turns, while the next tooth bt under the
pole edge, which is worked at possibly 20 per cent lower den-
sity, may require only 10 to 20 per cent as many ampere-turns.
Assuming such conditions, then the magnetic potential at the
top of tooth c will be higher than that at the top of b by 1600
to 1800 ampere-turns. Therefore, under this condition there
will be a very considerable flux across the slot between c and
b. A little earlier or a little later in the rotation this flux across
this slot will not exist to any extent, for the ampere-turns for
b and c will then both be comparatively low or very high,
while the difference between them will be small. In conse-
quence, near each pole edge, there is a very rapid rise and fall
of flux across the armature slots. This is illustrated in Fig. 2.
Obviously, the armature conductors lying in the path of
PIG 2
IRON LOSSES IN D.C. MACHINES
497
this flux will be the seat of e.m.fs. which will tend to set up
local currents, the value of which will be some function of
the e m.f. producing the current, of the dimensions of the
conductor, etc If the flux across the slot is large, this e.m.f.
may also be considerable, for the rate of this flux change will
be high compared with the normal frequency of the machine.
As the e.m f . generated is a function of the maximum difference
between the ampere-turns required for two adjacent teeth
and as the loss in any given case will vary as the square of the
e.m f , obviously the loss in one slot will vary as the square of
the maximum difference between the ampere-turns of two
FIG. 3
adjacent teeth. At very high saturation, the maximum dif-
ference between the ampere-turns required for two adjacent
teeth may be relatively high and the loss may be correspond-
ingly great. Due to the shape of the permeability curve of
steel at very high saturation, the difference between the ampere-
turns of two adjacent teeth may increase faster than the square
of the terminal e.m.f. Therefore, the eddy current loss due to
this cause may increase faster than the fourth power of the
total induction per pole. Evidently, therefore, it is desirable
to keep these eddy current losses at a low value at no-load,
for the high tooth ampere-turns under the distorted field con-
ditions of full load will tend to increase the percentage of these
losses very greatly. Fig. 3 , shows a characteristic core loss
498 ELECTRICAL ENGINEERING PAPERS
curve for a generator in which the copper loss, due to the above
cause, is very large at the higher e.m.fs.
Several years ago, the writer spent considerable time in
attempting to determine the value of this eddy current loss at
no-load. Neither sufficient nor entirely satisfactory data
were available. From the data at hand, the following em-
pirical formula was derived,- which appeared to accord fairly
well with the facts in a number of cases whjch were worked
out. This formula applies, however, only to windings with
two conductors in depth per slot. This formula for the loss
in conductors is
Watts loss = ft Mi™ +
a = Maximum ampere-turns for one tooth.
Ve = Total volume of copper, in cubic inches, in one slot.
R» = Revolutions per second.
p = Number of poles.
The values for the watts eddy current loss in the copper
were approximated by taking the iron loss curves at the lower
e.m.L values (where the above eddy current loss would be very
low), and then projecting them for the higher values accord-
ing to the laws which the iron loss alone should follow. The
difference between this corrected iron loss and the actual test
curve was assumed to consist largely of eddy current loss. As
this difference usually increased very rapidly at higher induc-
tions, the above assumption was in line with the preceding state-
ments that this eddy current loss may increase much more
rapidly than the square of the flux. In this determination
obviously the pole face loss would have to be taken into ac-
count. This was taken care of as far as possible, by tests
with relatively large air gaps, the pole face loss thus being
very small.
It may be noted that in the above empirical formula, the
ampere-turns for one tooth under the maximum field has been
used, instead of the maximum difference between the ampere-
turns of two adjacent teeth. However, the tests indicated
in general that the maximum difference was approximately
proportional to the maximum ampere-turns in one tooth and,
therefore, it was simpler to use the total turns for 6ne tooth.
Also, where the total tooth ampere-turns are tapered off over
IRON LOSSES IN D.C MACHINES 499
several teeth, the difference between the ampere-turns for
adjacent teeth is reduced, but more slots and more copper is
involved, whereas the empirical formula includes only the
copper for one slot. Various attempts were made to include
all the different factors, such as ampere-turns across each
slot, number of slots, number of conductors involved, counter
magnetomotive force of the eddy currents, etc., but none of
the resulting formulas gave as consistent results as the above.
It must be admitted that this formula is an extremely crude
one, but it happened to fit most of the cases that the \\riter
was able to analyze. In deriving this equation, it was found
that if the loss was assumed to vary directly as the square of
the tooth ampere-turns, then it would be too great at very
high tooth saturation. At high tooth densities, the flux across
the slots, at the pole edge, is distributed over several successive
slots, so that the maximum difference between the ampere-
turns of two adjacent teeth bears a lower proportion to the
ampere-turns for one tooth. Also, at very high tooth densi-
ties there is more or less fringing of flux down through the slot,
in parallel with the tooth flux, and this makes the determina-
tion- of the actual tooth flux difficult. In the formula, there-
fore, the term (1000 + a)2 is used in place of az to take care
of these conditions. This term, however, is obviously wrong,
in that it indicates a loss when the tooth saturation is negli-
gible. However, this loss under low saturation usually works
out from the formula to be of comparatively small value, so
that the error is not of much importance.
A modified formula, which agrees with the above fairly
closely at high saturations, but gives no 'loss at zero saturation,
is the following:
Watts loss = 135F.*.M4000
The following table shows the comparison of the copper
eddy loss compared with the calculated loss by the first formula
above, for a number of machines. It will be noted that the
agreement is not particularly close, but possibly as good as
could be expected, considering how -the test losses were de-
rived. It may be stated that these were all comparatively
old types of machines, for" in recent years great pains have
teen taken to eUinitiate large eddy losses of this character, so
500
ELECTRICAL ENGINEERING PAPERS \
that it was necessary to go to old machines in order to obtain
exaggerated cases.
Eddy loss
Eddy loss
Kilowatt
Terminal
Rev
No of
Calculated
estimated
calculated
rating
e m.f
per
poles
ampere turns
from
from
mm
in
test curve;
formula;
tepth
kw
kw
340
600
C83
G
1400
2 7
3 4
"
700
"
3000
10 0
9 7
500
600
22-5
10
2500
7 5
6 15
"
625
"
4000
17 5
12 5
750
250
514
10
1200
1 5
2 76
"
320
"
7200
32 0
3Q 3
750
550
514
8
1500
4 5
3 3
"
700
"
7000
33 0
3G 5
1000
250
514
12
000
2 5
2 2
u
330
"
0000
50 0
41 3
1000
600
514
10
1225
4 3
4 C
M
700
"
2iSO
10 0
11 3
2000
575
300
14
3000
12 0
7 1
*'
675
"
7000
'•{(. 0
28 2
Losses at No-Load. Il has long been known that,
with open slot armatures, there arc liable to be considerable
losses in the field pole faces due to bunching of the magnetic
flux from the armature teeth to the pole face, the armature
teeth thus acting as small poles of an "inductor" type alter-
nator, of which the pole face, to
a small depth, serves the function
of the armature core.
While the effect of this "inductor
pole action has long been known,
the amount of loss due to it has
frequently been underestimated,
especially in machines with rela-
tively small air gaps compared
with the width of the armature
slots.
—a b-
FIG. 4
The following crude description will illustrate the extent of
the variations in flux in the air gap due to the, open armature
slots. In Fig. 4, a represents the width of one armature tooth
and b represents the width of one armature slot. Let g rep-
resent the single air gap (iron to iron).
In the lower diagram, which represents the flux distribution
in the air gap, let Ba represent the flux density in the air gap
IRON LOSSES IN D.C MACHINES 501
under the armature teeth and Bb the minimum flux density
corresponding to the center of the slot.
Then, a X Ba — the total flux under one tooth, for unit
width of core, and b (Ba — Bb) c — the total decrease in flux
for the space covered by one slot represents the average
height of the curve def in Fig. 4. If this curve be assumed to
be sine shaped, then c would be 0.636 Any other shape which
would be likely to be found in practise would not be far from
this value. A V-shape, as one extreme, would give c = 0 5
while a circular shape, as the other extreme, would give c =
0.784. Apparently the value would lie somewhere between
these two extremes.
In calculating the effective gap from the above diagram
and assumptions, the following equation would be obtained-
Increased gap g> = g X
(a + _ (Ba _ Bk)e
°r' *' = * X . b(B\-Bb)c = * X , (6) (B. - ft) c
(a + b) Ba (a + b) (Ba)
The resemblance of this equation to Carter's well-known
equation for the increased air gap may be seen at once.
In Carter's equation, gr = g X ,
x a + b
Comparing these two formulas, it is evident that k
*
(Bq - gft) C
An extremely close approximation to k can be obtained
J?_
frt>m the empirical formula k = — ^ . This holds closely
V , -f-+"«
502 ELECTRICAL ENGINEERING PAPERS
to Carter's curve over almost the entire range. Equating the
above two values of k, we obtain the equation
Eg -Bb 1 (ft)
Ba
This gives the ratio of the flux density at the middle of the
slot to the flux density under the tooth.
As an example of what these relative values may be, assume
that a = by or the slot width = the tooth width, and that
g = 0.25 ft, which is extreme for large a-c. or d-c. generators,
but not unusual for induction motors. Assuming c = 0.635,
•o
then ~ = 0.3, or the density under the middle of the slot
JDa
is only 0.3 of that under the tooth. With these same values,
the value of g' becomes 1.2859, pr the gap increase is 28.5 per
cent, which is not- unusual for some machinery. Obviously,
a variation in the flux density at the pole face of 70 per cent
should tend to give high iron losses in the pole face itself. In
fact, some 'of the inductor type alternators which were in com-
mon use a few years ago did not give variations in armature
flux materially better than indicated by the above value. Such
proportions as the above example would, therefore, be fairly
good for an inductor alternator.
The above analysis is given simply to furnish a means for
determining the possible variations in the flux density which
may be obtained with open slots. This gives a much better
conception of the problem than can usually be obtained directly
from Carter's formula for the increased length of gap. It
also gives a good idea of the possibilities of tooth losses in those
cases where the teeth of ,one element or member of a machine
alternately pass under the teeth and slots of the other member.
Considerable work has been done aL various times to de-
termine the pole face losses due to open armature slots. The
difficulty in determining a workable formula is very consider-
able, as there are many conditions which may directly or in-
directly affect this loss- For example, the thickness of the
IRON LOSSES IN D.C. MACHINES 503
laminations, or the material in the pole face, may have an in-
fluence. Any general formula for this loss would require
different constants for different types of pole faces. One
formula for this loss has been given by Professor C. A. Adams
and his associates.* The formula is very complex and some-
what difficult to use.
A much simpler formula for laminated pole faces is as fol-
lows, ior 0 031-in. laminations:
Watts loss
CfW*gL R,g
E = Generator voltage.
b — Width of slot.
g = Single air gap (iron to iron) .
Wt = Arm a lure wires in series.
L = Width of pole face.
Cf = Field form constant.
Se = Total slot space = width of slot X No. of slots.
It is very difficult to obtain any reliable data on pole face
losses alone, for other core losses are liable to be included in
any tests. Variation of air gap., with everything else in the
construction unchanged, gives a partial measure. However,
this changes the field form somewhat and thus modifies the
*Pole Face Losses, by Comfort A. Adams, A, C. Lamer, C. C. Pope
and C. O Schooley. P*oc. A. I. E. E., July, 1909, page 1151.
(Bo V 4 / v V-66
"loO x(lo/
x
Wp * Pole face loss.
Sp = Section of one pole face (average section where the
density is BQ).
p «= Number of poles.
0.000462 = Constant for &-in. laminations.
Bg — Density in the gap over the section Sp.
v — ' V^ocity of the armature surface in feet per second.
q =^ Ratio of iwidth of slot, to air gap.
504 ELECTRICAL ENGINEERING PAPERS
tooth saturation and the tooth and eddy losses, to a certain
extent, thus rendering doubtful the pole face component.
The above formula is necessarily approximate and applies
only to laminated pole faces. The effect of cutting away
part of the laminations in order to produce high saturation
at the pole face is not included. However, it is possible that
this may not influence the loss to any great extent. The
greater part of the loss is represented by eddy currents, and
cutting away part of the laminations will tend to break up the
losses between plates and this may compensate to a con-
siderable extent for the higher densities in the remaining plates
It is hoped that some time in the future more complete data
may be obtained, over a sufficiently wide range of conditions,
to cover the practical range of ordinary design.
The following table covers a number of machines with ad-
justable air gaps in which the pole face losses were worked
out according to the above formula. Also, the total calculated
and the total test losses are given, to indicate the agreement in
a general way. The writer is perfectly willing to admit that
he believes that the fairly close agreements between some of
the calculated and test totals are largely accidental, and they
should not be taken as proof of any great accuracy of the
methods.
It is obvious from this table that the pole face losses may
be comparatively high in some cases, provided the formula is
reasonably correct. Evidently, if these losses could be cal-
culated with any great accuracy, the design of thfe machine
might be considerably modified, compared with more recent
practise, with advantageous results. The pole face losses will
evidently be greatly increased by ' field distortion when the
machine is carrying lo^d. Eddy currents in the copper are
'also affected by field distortion, and a correct method of cal-
culating both the eddy current and the pole face losses with
various loads should lead to considerable modification in the
proportions of d-c. machines, in general,
Stray Losses. Under this heading may be included _a number
of no-load losses which are usually of a minor nature. Among
these may be included secondary losses in the armature wind-
ing due to unsymmetrical cross-connections or unbalanced
voltages in parts of the winding which are connected in parallel,
There are various possibilities for losses from this source and1,
tn consequence, it is always advisable to use armature wind-
IRON LOSSES IN D C MACHINES
505
00 i-< CO f» (
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oo'ddododo'd
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i I I I II
506 ELECTRICAL ENGINEERING PAPERS
ings which are as symmetrical as possible. Also, the arrange-
ment of the winding should be such as always to generate bal-
anced e.m.fs. in parallel circuits. This condition is not in-
frequently overlooked in the design of direct-current machines.
A second cause of undue loss in the armature winding may
be occasioned by short-circuiting one or more of the armature
coils under an active field. The brushes may be shifted from
the magnetic neutral point so that some of the armature con-
ductors are short-circuited under the main field flux; or the
neutral point may be so narrow and the brush so wide that
some of the armature turns are short-circuiting in an active
field, even when the brush is set for the no-load neutral. An
armature winding which is considerably "chorded" in a field
with a narrow neutral point may have two sides of a coil short-
circuited in fields of the same polarity. The e.m.fs. in the two
sides of the coil should, therefore, balance each other if the
brush is set at the true neutral. However, if the brush short-
circuits several coils or turns, obviously only one of them can
be at the true neutral and have balanced e.m.far. set up in its
two halves. The other turns may have more or less local
current in them, which may be* a source of considerable loss.
A third condition may occur when there are considerable
pulsations in the reluctance in the air gap under the main,
poles as the armature teeth move under the poles. This vary-
ing reluctance usually gives varying main flux and at a relatively
high frequency. The armature coils short-circuited by the
brashes will act as secondaries to these .pulsating flaxes and
in consequence there may be some loss in the short-circuited
cofils due to this cause. Any solid parts of the yoke or poles
may also have losses due to this cause. Usually, however,
such losses are small.
A fourth source of loss may rise from stray fluxes fronL'the
main fields to the armature, which do not pass through well
laminated parts of the armature core. For instance, the
ventilating spacers may be so dimensioned and shaped that
eddies can be set up in them. Also, the finger plates at each
end of the core, the end plates, etc., may cany light fluxes
which produce some loss. Bands on the armature core or
at the ends may also be the seat of e.m.fs. and will have some
loss in them. Thes'e losses are difficult to determine, and,
in practise, should be eliminated as far as possible.
IRON LOSSES IN D C. MACHINES
507
FULL LOAD LOSSES
It is evident from the foregoing that the no-load core losses
are dependent upon so many variable conditions that there
can be no great accuracy in predetermining such losses unless
all the details of construction, material, treatment, etc., are
known for each individual machine. The impossibility of
accurate calculation is shown by the fact that the individual
machines built on the same stock order will vary considerably
from each other, especially in certain types.
While the no-load losses are difficult to predetermine, the
full load losses are still much more difficult to calculate, as
will be shown in the following rough analysis. Here, the
effects ot flux distortion by the armature magnetomotive force
tend to exaggerate the pole face losses and those in the arma-
ture copperj which are the two relatively large losses which
are most difficult to calculate
at no-load. Also commuta-
tion and brush losses, due
to load, now enter into the
problem. The individual core
losses may be considered
briefly as follows:
Armature Ring Lo$sy with
Load. This loss should not
change greatly with load,
provided the total flux at load is practically the same as at
no-load. Under this condition a variation in the distribu-
tion of this flux is about the only factor which should pro-
duce any material change -in loss. The full load field form
may be illustrated by Fig. 5. It -is evident from this figure
that the flux is now crowded toward one pole edge and,
therefore, the major part is concentrated in a narrower
space. The average length of the flux path may, therefore,
be somewhat greater than at no-load, but in some cases this
may tend to distribute the flux more uniformly through the
depth of the ring. However, where the flux enters the core
at the base of the teeth there will *be slightly more crowding
and, therefore, somewhat ir^creased loss. Taking everything
into consideration it would appear that, in general, the arm-
>ature ring loss can be considered as practically constant with
constant t£&al , ftuix; apd; .speed^ independent of ' the yariation
in. '
FIG. 5
508 ELECTRICAL ENGINEERING PAPERS
In variable-speed and adjustable-speed d-c. machines, the
armature ring loss may vary over a wide range due to changes
in total flux and speed. Such cases are difficult to calculate
with any degree of accuracy, although no more so than other
losses in the same machines.
Armature Tooth Loss, uiih Load. As shown by Pig. 5, the
tooth flux density at one edge of the pole is decreased and at
the other edge is increased when the field flux is distorted by
the armature magnetomotive force. The increased density
in the armature teeth means increased iron loss and, if the dis-
tortion is very great, the increase in tooth loss may be very
large, being in some cases even doubled or trebled, compared
with the no-load tooth loss. No direct rule can be given for
the calculation of this loss, except that it may be determined
approximately by calculating" the flux distribution with oad
and thus determining the flux densities in the teeth.
In variable-speed and adjustable-speed machines, particu-
larly in the latter, the tooth loss with load will be affected very
considerably by changes in both speed and total flux. In
variable-speed machines of the series type, reduction in speed
usually accompanies increase in total flux, so that, as regards
the losses, one effect partly neutralizes the other, so that the
increase in tooth loss with load may be less than in a constant-
speed machine. In adjustable-speed machines, however, es-
pecially in those of constant horse power and constant voltage,
the tooth losses will vary over a very wide range with change
in speed. Here, the armature magnetomotive force is con-
stant (assuming a constant horse power) and the field flux is
varied from a maximum value at lowest speed to one-quarter
value at four times speed, assuming a four-to-one range. The
total flux, therefore, varies inversely as the speed and the two
effects should nearly compensate each other, as regards losses,
if it were not for the variation in flux distortion. At lowest
speed, with considerable saturation in the pole horns and
armature teeth, the armature magnetomotive force, even if
relatively large compared with the field magnetomotive force,
may not produce very large distortion, so that the tooth loss
is not increased excessively over the no-load tooth loss. How-
ever, as the field is weakened, the armature magnetomotive
force remaining constant, the distortion is relatively increased,
so that the peak value of the distorted field may remain almost
constant in height. As the armature tooth losses are dependent
IRON LOSSES IN D.C MACHINES
509
upon the peak value of this field, then obviously the combined
effect of this field and the increase in speed will mean very
greatly increased tooth losses. With very low field magneto-
motive force, the distortion may be so great as to give a double
peak, as indicated in Fig. 6. This double peak gives, to some
extent, the effect of a double frequency and thus further in-
creases the loss.
Eddy Currents in Copper. When the field form is distorted,
with load, the ampere-turns in the teeth at one pole corner
are greatly increased, while those at the other corner are de-
creased. Therefore, there will be an increased loss in the
copper at one pole edge and a decreased loss at the other pole
edge. However, as this loss at high inductions will vary al-
most as the square of the
ampere-turns in the armature
teeth, it is evident that the re-
duction in the loss at one pole
corner may be small compared
with the increase in loss in the
copper at the other pole corner.
The resultant loss can be calcu-
lated approximately by using the
formula already given for no-
load conditions, but with the
ampere-turns in the teeth based
on the load conditions. This
would give a loss corresponding
to no-load with the maximum
induction in the teeth raised to
peak value with load. This would include losses for the two
pole corners; therefore, the result should be halved, as the
peak density occurs at only one pole edge.
If the empirical formula given for the copper loss repre-
sents the facts, even to a merely approximate degree, the re-
sults are very startling when applied to some of the old-time
machines. The calculations show that in some cases the
eddy current copper loss at heavy load was several times greater
than at no-load. This should be true, but to a much less extent,
in more modern types of machines. The results indicate that
in many cases there will be considerable gain by reducing
the field distortion through high saturation in the pole face,
pole horns, etc. This saturation, however, would have to be
FIG. 6
510 ELECTRICAL ENGINEERING PAPERS
so arranged as to give the most beneficial field distribution
with load, and haphazard methods of cutting off pole corners,
without regard to the field form with load, would have to be
avoided. In fact, in the past, the cutting away of pole corner
laminations, in many cases, has been largely for the purpose
of improving commutation, and not to obtain the best field
form with load.
Pole Face Losses, with Load. The pole face losses will obvi-
ously be affected locally by change in the flux density in the
air gap or at the pole face. Field distortion will tend to increase
the loss at one pole corner and decrease it at the other. The
increase will usually considerably exceed the decrease, but the
resultant will not be increased in anything like the same pro-
portions as the copper eddy current losses under the pole corners
are increased with load. A rough approximation for the in-
creased iron loss could be obtained by comparing the squares
of the densities, at several points along the distorted field
form, with the squares of the densities of the no-load field
form corresponding to the total induction.
As the increase in pole face losses with load will, in some
instances, be considerably less than the increase in the eddy
current losses, it might be advantageous in such cases to de-
crease the field distortion by pole face saturation, even at the
expense of increasing the no-load pole face losses. For example,
if, in an extreme case, the air gap were decreased 20 per cent
and the air gap ampere-turns thus gained* were expended in
suitably saturating the pole face material, then the full load
field distortion might be much less than with the larger gap,
with the same total field magnetomotive force. The no-load
eddy current copper losses would be practically unchanged,
while the no-load pole face loss would be increased. However,
the full load pole face loss, due to the reduced distortion, might
be no greater than with the larger gap, while the eddy current
losses in the copper might be very much less than with the
•larger gap.- In consequence, while the total no-load losses
[would be increased somewhat, the full load loss would be smaller
than before, and the carrying capacity of the- machine would
be actually increased. This would apply, however, only to
those machines where the no-load eddy current and armature
tooth losses are relatively high and where the distortion is
rather large with load.
Stray Losses^ When the machine is carrying load, the stray
IRON LOSSES IN D.C. MACHINES 511
losses given under the no-load conditions may also exist and
at the same time some of these may be greatly exaggerated.
Also, other losses may appear which are not found at no-load.
Copper loss due to short-circuiting the armature coils in an
active field will sometimes be more pronounced than at no-
load, particularly in non-commutating-pole machines in which
the brushes are shifted into an active field to produce com-
mutation. This field, as a rule, will only be of proper value
to produce proper commutation at some definite load, while
at other loads there may be very considerable local currents
in the short-circuited coils which may produce loss.
As the main field flux is crowded toward one pole corner
and the field form becomes more pointed in shape, the effect
of variable reluctance in the air gap may become more pro-
nounced than at no-load, and, therefore, pulsations of the main
field flux may cause more loss in the short-circuited armature
coils.
Stray fluxes from the main poles will be distributed differ-
ently from the no-load condition and the densities of these
stray fields may be considerably higher at certain points and
thus give increased losses.
Additional losses at full load may be due to fluxes set up
by the magnetomotive force of the armature winding itself
when carrying load. For instance, the armature winding will
set up magnetic fields, through the end windings, which fields
are fixed in space, in a rotating armature machine. Bands or
supporting parts, or other solid metal, rotating with the end
winding, may cut these stationary fields or fluxes, and thus
losses may be set up which are a function of the load.
Another source of loss at load may be found in the operation
of commutation itself. A magnetic field or flux is set up by
the armature winding across the slots from one commutation
zone to the next. At the point of commutation this flux is re-
versed in direction with respect to the armature conductors,
and, therefore, there will be local currents set up in the arm-
ature copper tself, due to this action. This, however, should
be more properly charged to commutation loss rather than
to armature core loss.
The above covers the principal core losses in direct-current
machines. It was the original intention to analyze the core
losses in the various types of rotating machines, but it soon
developed that the subject was too extensive for the scope
512 ELECTRICAL ENGINEERING PAPERS
of this paper, therefore it was limited to d-c. machines only.
However, many of the conditions which hold for d-c. machines
also apply, to a certain extent, to many other types. In ad-
dition there are losses in d-c. machines which are relatively
large compared with those in other apparatus, due to the fact
that the tooth saturation in d-c. machines is frequently carried
much higher than in other apparatus.
The foregoing treatment of core losses is qualitative rather
than quantitative, and it deals with the simpler phenomena
only. It omits some very complex conditions, such as the
effect of pulsations in flux superposed on high densities, dis-r
placed minor hysteresis loops, etc., which mean • additional
losses. The principal object of the paper is to give a better
idea of the possibilities and impossibilities of the problem of
core losses.
IRON COMMUTATORS
FOREWORD— During the past two years 1916-1918, frequent in-
quiries have been made as to why iron is not used instead of
copper in the construction of commutators. Apparently it has
been assumed, in some instances, that the present use of copper
is more or less of a fad and that other metals, such as iron, could
be used if desired.
This paper appeared in the Electric Journal, July, 1918.
—(ED.)
IN the course of the development of commutating machinery
various metals have been tried out in commutators, all the way
from pure copper, both hard and soft, through various alloys and
brasses, cast copper of various purities, aluminum, wrought iron,
clear down to cast iron. All such materials have received con-
sideration at some time or other and have been given fairly con-
clusive tests. Experience has shown that all of them could be used
in commutators if one is willing to pay the price, this price being
in the first cost of apparatus, in maintenance or in less satisfactory
operating characteristics, or a combination of all. Under the
stress of war conditions it may be necessary to pay any price, and
apparently this is the condition which has confronted German
manufacturers. In consequence, materials and constructions are
used simply as a matter of necessity which, however, may not con-
form to conditions of even reasonably good design.
The use of copper in modern commutators is a matter of
development and not simply a fad. In fact, most of the early
commutating machines used other metals in their commutators,
which would now be considered quite unsuitable. Cast copper and
various brasses and bronzes were used quite extensively, with
more or less bad results. Pure copper was considered too expen-
sive for general use and it was only after very considerable de-
velopment that the conclusion was reached that its apparent
higher first cost was more than neutralized by improved mainten-
ance and operation. Even after pure copper had come into
general use for p-nm-miif.fl.tnr construction, it was not known, or
understood, why it was so superior to other metals.
About twenty-seven years ago the writer made extended
tests on the use of iron in street railway commutators. The ma-
513
514 ELECTRICAL ENGINEERING PAPERS
chines soon developed "high mica" and the commutators grad-
ually blackened, the contact surfaces blistered and sparking
gradually increased until the commutating conditions became
practically impossible from the operating standpoint. These
conditions repeated themselves in every test until finally this con-
struction was given up as impracticable. The difficulty was
blamed largely upon high mica, as it was assumed that, in some
way, the metal wore below the mica, thus causing bad brush con-
tacts, with resultant burning and blackening. It was not recog-
nized that the converse was really the case and that the high mica
was the result of burning rather than the cause. In all machines
of those days there was more or less tendency for the commut-
ators to "wear " considerably, and it was not recognized that such
was not true mechanical wear, but that it was the result of burn-
ing away the contact surfaces.
A little later, the writer made quite complete tests on the use
of aluminum on street railway motor commutators. This material
worked better than iron, in the sense that burning and blackening
and high mica did not appear as quickly as with the iron. How-
ever, like the iron commutator, there was no tendency to polish,
but the commutator soon assumed a dull appearance which
gradually changed to a blackened and burnt condition.
Bronzes and brasses were tried on similar railway commut-
ators, and while these gave better results than the aluminum or
iron, yet they developed high mica much more quickly than the
copper commutators. With such evidence at hand, the use of
forged or drawn copper for commutator bars was a natural con-
clusion. However, even with the best copper obtainable, there
was some tendency toward blackening and burning of the com-
mutators, generally accompanied by high mica, and the difficulty
was blamed primarily on the mica. It was assumed that the cop-
per bars did not wear as rapidly under the carbon brush as was the
case with other metals. At the same time it was recognized that
when the machine was operated without current none of these
metals seemed to wear unduly. It was only when considerable
current was carried that the wear was excessive. At that time,
the real explanation of this difficulty was not fully appreciated.
Later investigations on collector rings and commutators, de-
veloped the fact that whenever a current is carried between a
stationary brush contact and a moving surface, there is a tendency
to burn away either the brush contact face or the moving surface,
IRON COMMUTATORS 515
depending upon the direction of the current and upon the current
density. It was found that this burning action, which is some-
what similar to that occurring in an arc, was to some extent a
function of the contact loss. This was indicated partly by the
fact that the burning was a function of both the brush contact
drop and the current density. A given current, for instance,
might produce very little burning as long as the contact drop was
quite low; whereas, if for any reason such contact drop increased
materially, noticeable burning would begin. If the current was
from the brush to the commutator or collector, the brush contact
surface would tend to burn away more than the opposing surface.
If, on the contrary, the current was from the collector or commut-
ator to the brush, then the collector surfaces would tend to burn
and, in some cases, deposit the burnt material on the brush face.
When carbon brushes are used, there is usually a very con-
siderable contact drop due, apparently, to the nature of the ma-
terials in the brush itself. This drop, in many cases, is in the
nature of one volt for each contact and it is fairly constant over
quite a wide range of current. In consequence, the contact loss
varies nearly in proportion to the current and not as the square of
the current. Due to this very considerable loss with carbon
brushes, there is a tendency to burn away the brush surface and to
burn and blister the commutator or collector surfaces with which
the brush is in contact. This tendency to burn is dependent upon
the actual current density in the brush (including local or short-
circuit currents), but the resultant burning is largely a function of
the material in the commutator or collector face. As the brush
cannot make perfect contact with the metallic surface to which it
is opposed, there are minute arcs at the contact and these evi-
dently burn away the surfaces. However, the real burning action
is dependent upon the inability of the surface to conduct away
heat rapidly, for if the heat developed in the surface film is not
conducted away with sufficient rapidity, then such surface is liable
to be blistered or burned locally, even though moving with respect
to the brush. Such burning or blistering naturally roughens the
contact surface and increases the contact drop and thus tends to
increase the arcing and burning action. Thus, if there is any
burning action it tends to grow worse, cumulatively. This burn-
ing away of the surface leaves the metal surface of the commutator
slightly lower than the mica, imless the latter wears mechanically
at the same rate that the comtiiutator metal bums away. As this
516 ELECTRICAL ENGINEERING PAPERS
is not usually the case, high mica soon develops, simply by the
action of burning away of the metal. Thus high mica is a result
of the trouble, rather than the cause. However, as even a very
gradual burning away will eventually leave the mica above the
surface, modern practice has tended toward undercutting of the
mica, so that even with a slight burning tendency the brush still
maintains contact with the metal, thus preventing accentuation of
the trouble.
As mentioned before, this burning action is a function of the
contact voltage, the current density, and the non-burning or non-
blistering qualities of the metal constituting the commutator. It
is in this latter feature that copper has proven so superior to other
metals. Extended experience shows that the heat conducting
qualities of pure copper are so good compared with most other
metals or alloys that the burning or blistering action of the current
under the brush is very small, except for high current densities.
Anything which tends to decrease the heat conducting properties
of the commutator metal, tends to increase burning action. This
has been very clearly demonstrated in elaborate tests of carbon
brushes on collector rings, etc., where questions of commutation
did not come in to disturb the conclusions. Such tests have been
made covering copper, bronzes and alloys of various sorts, wrought
iron, cast iron, etc. In practically all cases, with high current
densities, the burning and blistering action appears to be dependent
upon the ability to conduct the heat away from the contact sur-
face. By such conduction the local heating of the contact film of
metal is kept at a low point which results in reduced fusion of the
metal, and with very good heat conducting materials the fusion of
the metal may be so minute that the polishing action of the brush
keeps the surface in a smooth glossy condition.
It is an interesting fact that the electrical conductivities of the
metals and their mixtures and alloys, bear a fairly dose relation to
their heat conductivities. Experience shows that very little im-
purity in copper will reduce its electrical conductivity to possibly
one-third or one-quarter, and its heat conductivity will be decreased
nearly in proportion. Most of the alloys of copper have a very low
conductivity compared with copper itself, while wrought iron is
worse than most of the copper alloys in this regard. The series of
tests above referred to, indicated quite clearly that the burning
tendency varied very much as the electrical resistance of the ma-
terial, that is, with the heat resistance. Wrought iron, having
IRON COMMUTATORS 517
from eight to ten times the resistance of copper, would burn or
blister and get rough at very much lower current densities than
copper commutators or rings. Even some of the alloys which ap-
peared to be good for collector rings, showed blistering effects at
very much lower limiting current densities than copper. Conse-
quently, it developed that the limiting carrying capacity of dif-
ferent metals in commutators and collector rings, varied roughly
with the heat conducting qualities, and thus copper proved to be
superior to any of its alloys or any other available material. Ac-
cording to this line of reasoning, silver should be better than cop-
per, but this is not an available metal. The above also explains
why alloys of copper in which other elements have been introduced
for the purpose of hardening, etc., usually do not have the ultimate
carrying capacity found in copper. Aluminum has fairly good
heat conductivity, if pure, but it is so easily oxidized and the re-
sistance of the oxidized surface rises so rapidly, that presumably
this fact neutralizes any possible gain otherwise. Experience on
actual commutators showed that aluminum did not take a polish,
even under moderate current densities and, in fact, it acted very
much like some of the higher resistance metals used in the tests.
It should be evident from the above that, when materials of
higher heat resistance, that is, with poorer heat conductivity than
copper, are used in commutators, the operating current densities
should be reduced accordingly. Thus, it may be possible to use
iron or steel for commutator bars, provided the brush current
densities are. reduced sufficiently. In very small machines, this
might mean only an increase in the dimensions of the commutator
and brushholders. In larger machines, however, any material
modification in the proportion of the commutator may lead to
radical changes in the machine as a whole, so that the total cost
would be materially higher than in the copper commutator ma-
chine. This depends entirely upon how much sacrifice is to be
made in operating conditions and maintenance. If these are to
be kept at the same high standard as on present copper commut-
ator machines, then it is questionable whether the iron commut-
ator would prove to be practicable under any conditions. The
same conditions hold true, to a certain extent, with certain alloys
instead of copper in the commutator. As such alloys, as a rule,
cost nearly as much as copper itself, it should be obvious that any
material increase in the dimensions of a commutator will soon
balance any possible gain.
51S ELECTRICAL ENGINEERING PAPERS
In larger machines one serious condition would be liable to be
encountered with other than copper commutators. At present
these machines are built for quite high peripheral speeds of the
commutators, and construction difficulties are encountered winch
would make any increase in their length or diameter very objection-
able. Consequently, serious modifications in the general construc-
tion of the machine, and possibly in its speed conditions, are liable
to be necessitated. In fact, in many cases the whole design of the
machine is predicated on the commutator construction In such
cases the use of a poorer material in the commutator would un-
doubtedly be a backward step in the development.
It is thus obvious, that the use of iron in commutators, while
possibly practicable under the urge of necessity, is not in the di-
rection of an advance in the art. In fact, it is a big step backward.
It should be assumed naturally that if, in the past thirty years of
development in commutating machinery, iron commutators have
not come to the front, it is for very good reasons, and the pre-
ceding is simply an attempt to bring out some of the foremost
reasons.
POLYPHASE INDUCTION MOTOR WITH SINGLE-
PHASE SECONDARY
FOREWORD — Repeated requests had been made of the author, from
time to time, for a simple explanation of the half speed charac-
teristics of f a polyphase induction motor with single-phase
secondary circuit. The analysis presented here does not require
more than a working knowledge of the characteristic principles
and curves of the polyphase induction motor.
This appeared in the Electric Journal, September, 1915.
—(ED.)
IT is well known that when a polyphase induction motor is
operated with only one secondary circuit closed — that is, with
a single-phase group-wound secondary, it will develop at full
speed a maximum torque much less than with polyphase secondary,
and then with increasing load will drop to approximately half
speed, where it will develop comparatively high maximum torque.
However, a simple non-mathematical explanation of the causes
of this action has not yet been put forward, to the writer's know-
ledge. Such an explanation is possible, and the following is one
which should be grasped without difficulty by those who are
familiar only with the general characteristic curves and actions
of induction motors.
To begin with, consider the relations between the rotation of
the magnetic field and the mechanical rotation of the rotor in the
two cases of rotated and stationary primary windings — that is,
with the primary winding (1) on the rotor, and (2) — on the stator.
In the case of the primary winding on the rotor, let the direction
of the magnetic field rotation be in the lefthand direction (counter-
clockwise), as indicated in Pig. 1. This rotating field tends to
pull the stator around in the same direction (left hand). As the
stator core and winding cannot rotate, the rotor, due to the torque
between the rotor and stator, turns in the opposite direction
(right hand). When starting from rest, the stator or secondary
has the same frequency as the primary; then as the rotor speeds
up in the right-hand direction, the magnetic field set up by the
primary winding rotates in the left-hand direction, and therefore
its speed relative to the stator becomes less and less until synchron-
ism is reached. Thus the secondary or stator frequency generated
#19
520 ELECTRICAL ENGINEERING PAPERS
by the rotating primary field decreases until synchronism is reached;
which is the normal action of the polyphase rotor.
Considering next a stationary primary winding and a rotating
secondary, and assuming right-hand rotation of the magnetic
field, as shown in Fig. 2, it is obvious that the secondary winding
and core will be pulled around in the same direction — that is, the
rotor will turn in the right-hand direction. Thus, left-hand
rotation of a primary magnetic field on the rotor, and right-hand
rotation of a primary magnetic field on the stator, both tend to
give right-hand rotation of the rotor. These two conditions are
explained rather fully as they enter into the following explanation,
of the action of the induction motor with single-phase secondary.
FIG. 1. PRIMARY ON ROTOR FIG. 2 PRIMARY ON STATOR
The next consideration is the resolution of a single-phase
field in an induction motor into two components rotating in
opposite directions at the same speed, each of half the maximum
value of the single-phase field. Such component rotating fields, it
may be asserted, do not actually exist, but, nevertheless, the
•resultant of two such fields of proper value and rotation will
actually be a single-phase field corresponding to that set up by a
single-phase winding on the motor. This assumption of two
oppositely rotating fields as the equivalent of a single-phase field
is a great aid in explaining the speed characteristics of the poly-
phase motor with single-phase secondary.
Assume next that the induction motor with single-phase
secondary has its primary winding on the rotor and its secondary
on the stator.* Consider first the standstill condition. The
primary field is assumed to be rotating in the left-hand direction,
as in Fig. 1. This field, cutting the secondary winding at syn-
chronous speed, generates e. m. f . and current in the secondary, of
*This particular arrangement is chosen, as it appears to the writer to allow a somewhat
dearer conception to be obtained of what takes place in the motor.
INDUCTION MOTOR— SINGLE PHASE SECONDARY 521
a frequency equal to the primary, but single-phase, due to there
being but one closed circuit. This secondary current may be
considered as setting up a single-phase field which is actually fixed
in space, but which may be replaced by two oppositely rotating
fields, each of half value, traveling around the core at a speed
synchronous with the frequency of ike secondary current generated.
One of these rotating fields travels in the same direction and at the
same speed as the primary field set up by the rotor windings. It
thus corresponds to the rotating magnetic field set up by the usual
polyphase secondary winding. The action between this rotating
secondary field and the primary is that of a polyphase motor, and
torque is developed at all speeds from standstill up to synchronous
speed, as in the usual polyphase motor, as shown in Pig. 3. The
rotor under the action of this torque tends to rotate in the right-
hand direction.
Considering next the other component rotating field set up
in the stator by the single-phase secondary current in the rotor,
this rotates in the right-hand direction, or opposite to the primary
rotating field. This secondary component field traveling around
the stator may be considered as the primary field of an induction
motor. For a secondary, it makes use of the windings on the
rotor core, such secondary circuits being closed back through the
primary transformers, supply system, etc. This may not be a
very good secondary closed circuit, but it is all that is available
and the motor does the best it can under the circumstances.
Let us now consider what torque conditions obtain with this
right-hand rotating primary field with its freak secondary circuit.
Taking standstill conditions first, it is obvious that as the primary
field is on the stator and rotates right-handedly, the turning
effort, or torque, will tend to run the rotor in the right-hand di-
rection. Therefore, at start, the torque is in the same direction as
in the case of the left-hand component. The two torques there-
fore add at start.
Considering next slow rotation of the rotor, as the primary
winding on the rotor moves slowly in the right-hand direction the
left-hand rotation of its flux decreases in speed with respect to the
secondary winding, so that the secondary or stator frequency is
correspondingly reduced. Therefore, the two oppositely rotating
secondary component fields rotate more slowly. The left-hand
one rotates at the same speed in space as the fundamental primary
field, as described before. The right-hand component travels in
522
ELECTRICAL ENGINEERING PAPERS
the opposite direction, while its secondary circuit, namely, the
primary coils on the rotor, are rotating in the-same direction (right
hand) , but at a somewhat lower speed. The torque exerted by this
right-hand component is therefore still in the right-hand direction
— that is, the same as that of the other component.
Torque
FIG .5.
O — Torque of left-hand component, In synchronism with primary field and in the same
direction. B — Torque of nght-hand component, rotating in opposite direction and in syn-
chronism with A, relative to the secondary winding C — Resultant of A and B. D — Torque
of the same motor with polyphase secondary.
However, when half synchronous speed of the rotor is reached
a new condition enters. At this speed the secondary frequency
has fallen to one-half that of the primary or supply circuit. The
INDUCTION MOTOR— SINGLE PHASE SECONDARY 523
left-hand component of the secondary field is now traveling in the
left-hand direction at half the speed it had when the rotor was
stationary, but the primary field is also traveling left-handedly
at the same speed in space, so that the two fields are still in
synchronism.
Considering next the right-hand component, this is traveling
at half speed in the right-hand direction, while the rotor is travel-
ing at the same speed in the same direction. Therefore, the second-
ary circuit for this right-hand field (the winding on the rotor) is
now traveling in synchronism with it, and therefore no secondary
current or torque can be generated. This, therefore, corresponds
to full speed on the usual induction motor. The torque-speed
curve up to half speed, therefore, may be indicated by the lower
half of the curve shown in Fig. 4. - At higher than half speed the
stator frequency is still further reduced and the right-hand field
travels at a still slower speed, while its secondary winding on the
rotor core is now traveling faster than its primary field, or it is
running above synchronism. It therefore develops a negative
torque. This negative torque above half speed should show a
negative characteristic somewhat similar to the positive speed-
torque curve below half speed. This is indicated in Fig. 4.
However, there is this difference; as the rotor speed approaches
true synchronism, the frequency of the stator circuit approaches
zero, until at full speed of the rotor (synchronous speed) the
secondary frequency becomes zero. Under this condition the
stator field and currents fall to zero, and there is no torque from
either the right or the left-hand component field. Therefore, as
this zero frequency is closely approached, both torque curves
rapidly approach the zero value. By combining the speed-torque
curves for both component fields the resultant speed-torque curve
may be plotted as in Fig. 5. It will be seen from this resultant
curve that stable torque conditions are found at about half speed.
Also, the starting torque is good. Above half speed the torque
conditions are somewhat indefinite, depending upon individual
circuit conditions, etc. In general, the rotor will continue to run
at full speed, if first brought up to this speed by means of poly-
phase secondary operation, and will pull considerable load with-
out dropping to the lower stable speed.
While the torque at start, due to the resultant of the two
torque curves shown in Fig. 5, is larger than that due to the left-
hand component alone, yet it must be borne in mind that this
524 ELECTRICAL ENGINEERING PAPERS
latter may be much smaller than the starting torque of the motor
with polyphase secondary. Therefore, this method of starting
with one secondary circuit only is not, in general, an improvement
on starting with a polyphase secondary. To illustrate this,
another speed-torque curve should be added, representing, in a
general way, the conditions with the same motor if a symmetrical
polyphase secondary winding is. used. This is shown in Fig. 6.*
In general, this will show better starting and also higher maximum
or pullout torque than with single-phase secondary.
To the experienced designer it will be obvious that such a
motor is but one form of internal cascade, and a very poor one at
that. A motor under such conditions of operation carries exces-
sive currents, the primary winding carrying both primary and
secondary currents, these being of different frequencies, except at
standstill. The power-factor is also comparatively poor.
*The curves C and D in Fig. 6 have been plotted partly from actual test data.
A PHYSICAL CONCEPTION OF THE OPERATION OF
THE SINGLE-PHASE INDUCTION MOTOR
FOREWORD — In the training of young engineers, directly from the
technical schools, the author has found that very few of them
have any conception of the operation of the single-phase induc-
tion motor. In attempting to work out a simple method of
presenting the problem, the subject matter of this paper was
gotten together from time to time, and eventually it was written
in its present form and jpresented before the American Institute
of Electrical Engineers in April, 1918. It should be understood
that the purport of this whole paper is to illustrate the prin-
ciples of operation and not to indicate a method of calculation.
The usual methods of treating the single-phase induction prob-
lem are so mathematical that the average engineer or student
cannot follow them. In the method given in this paper a
knowledge of the characteristics of the polyphase motor is
necessary, as the entire method is based upon the fundamental
idea of a pair of polyphase machines operating with variable
voltages and opposing torques. From this viewpoint, the
various characteristics of the single-phase motor are explained
in a non-mathematical manner.
It may be considered, to a certain extent, as supplementary
to the author's paper on "The Polyphase Motor, which was
published twenty-one years before, and which is reprinted in
the first part of this volume. — (ED.)
THE underlying principles and the operating characteristics
of the polyphase induction motor are so well understood that
it is found desirable to consider the single-phase induction motor,
simply as a special case of the polyphase. The following treatment
of the subject should not be considered as an analysis of the true
phenomena of the motor but should be looked upon more as a
ready means of visualizing the actions in the form of well known
polyphase motor Characteristics. Also, it should not be con-
sidered as a presentation of new material, for the underlying
methods used are old and relatively well known. It is simply
an attempt to describe the operation of the single-phase motor
in a way which may be most easily understood by those not
versed in the mathematics of the subject.
Starting with the old assumption that a single-phase alter-
nating magnetic field may be considered as being made up of two
constant fields, each of half the peak value of the single-phase
field and rotating at uniform speed in opposite directions, then
525
526 ELECTRICAL ENGINEERING PAPERS
if the single-phase flux distribution is of sine shape and varies
sinusoidally in value, it may be replaced, or represented, by two
sine-shaped fields of constant value rotating in opposite direc-
tions. This is the simplest case and allows a relatively easy
explanation of many single-phase problems. However, when
the flux distribution, or field form, due to the single-phase
winding, is other than of sine shape, then the oppositely rotating
components cannot be considered as of sine shape, but will
assume certain varying forms as they rotate, the resultant of
each instantaneous pair always giving the single-phase field
corresponding to that instant.
As other than sine-shape fields tend toward complications in
the physical conception of the single-phase induction motor
actions, and lead more or less into the mathematical conception,
the following analysis will be limited essentially to sine-shape
distributions.
As a starting point and to show reasons for certain later
analysis, let us assume a single-phase induction motor operating
at no-load, full speed, with its polyphase secondary winding
short-circuited. The single-phase primary field, of assumed sine
shape, is considered as made up of the two sine-shape' equal
components of constant value, and of half the peak value of the
single-phase field, and rotating synchronously in opposite direc-
tions. One of these fields is traveling in the same direction as,
and slightly faster than, the rotating secondary. The slip of
the secondary with respect to this field is of the same nature as
in the ordinary polyphase motor. As the machine is carrying
no load the secondary current corresponding to this rotating field
is very small, being just large enough to overcome the rotational
losses in the motor itself, and its frequency is equal to the slip
frequency due to the forward field component.
As there is an assumed backward flux or field component of
equal value, the rotating secondary winding cuts this at almost
double the frequency of the line. Stated exactly, the sum of the
backward and the forward frequencies, in the secondary winding,
is equal to exactly double the frequency of the primary supply
system. The secondary winding cutting the backward field at
this high frequency tends to generate a very considerable e. m. f.
and, with the winding closed on itself, short-circuit currents will
flow, which tend to damp out or suppress the flux which causes
them. This secondary current will rise until its magnetizing
effect is practically equal and opposite to the magnetomotive
SINGLE-PHASE INDUCTION MOTOR
527
528 ELECTRICAL ENGINEERING PAPERS
force which produces the backward field, which thus becomes
almost zero in value. Consequently there are two distinct sets
of secondary currents flowing, one of very small value and of a
frequency corresponding to that of the forward rotation, and the
other of very much larger value and of almost double the line
frequency. Actual tests of the secondary circuit of a single-phase
induction motor at small load, taken with an oscillograph, Fig.
J , show both of these currents as above described.
MAGNETOMOTIVE FORCES AND MAGNETIC FLUXES
It is seen from the preceding that, right at the beginning of our
analysis, a new condition is encountered, namely, the introduc-
tion of a secondary opposing magnetomotive force which reacts
on one of the primary field components and practically neutral-
izes it. Also, there is a mixture of magnetomotive forces and
magnetic fields, which is liable to lead to confusion. Obviously
the introduction of the opposing secondary magnetomotive force
rotating synchronously with the backward component of the:
primary introduces some entirely new features. Therefore,
before going any further with the above method, it is desirable
to set aside for awhile the viewpoint of two equal oppositely
rotating fields and begin with a preliminary study of the magneto-
motive forces and the magnetic fields resulting from them.
It may be mentioned that while the assumption of two op-
positely rotating component fields, in place of a single-phase field,
is well known and has been used quite frequently, the correspond-
ing analysis, from the viewpoint of magnetomotive forces, ap-
parently has been but little used. When magnetomotive forces,
instead of magnetic fluxes, are considered, then the single-phase
primary magnetomotive force, fixed in position, can be replaced
by two equal components of constant value, such as would be
developed by* direct current, each of half the peak value of the
single-phase, and rotating at synchronous speeds in opposite
directions.
Returning again to our analysis, let us consider two funda-
mental magnetomotive forces, namely, a. primary single-phase
one, fixed in position and varying sinusoidally and a secondary
one of constant value, of half the peak value of the primary
which rotates synchronously in one direction and which is in
opposition to the primary in the position where the two coincide.
Let us assume that the primary single-phase magnetomotive
force is split into its two equal oppositely rotating components,-
SINGLE-PHASE INDUCTION MOTOR
529
then the results may be illustrated as in Figs, 2, 3, 4, and 5.
In Fig. 2, C and D represent the two components forming the
single-phase magnetomotive force A. At the position chosen,
C and D are of equal value and coincide in position and polarity,
B, which represents the secondary magnetomotive force, is also
of half the peak value of A, but is of opposite polarity. It,
therefore, neutralizes one of the components C or D, thus leaving
a resultant of half the peak value of A .
In Fig. 3, the component D has shifted thirty degrees to the
left, while C has shifted an equal distance to the right. The
secondary magnetomotive force B is shifted thirty degrees to the
left, thus neutralizing D and leaving only the component C.
In Fig 4, D and B are shifted sixty degrees to the left, while C
is shifted sixty degrees to the right In the same way, in Fig. 5,
B and D have shifted ninety degrees to the left and C has shifted
a corresponding amount to the right.
PIG. 4
Thus from the above it is seen that a single-phase magneto-
motive force, fixed in position and varying sinusoidally, and a
constant magnetomotive force of half the peak value of the
single-phase, which is in opposition at the point of coincidence
of position, and which rotates synchronously in either direction,
will give a resultant constant magnetomotive force, rotating in
the opposite direction, but which is of the same polarity as the
single-phase magnetomotive force at the position of coincidence.
530
ELECTRICAL ENGINEERING PAPERS
In other words, a single-phase magnetomotive force, fixed in
position, and an opposing constant one of half the peak value
rotating in either direction, will give a resultant rotating magneto-
motive force equivalent to that of a polyphase induction motor.
As a continuation of the above, the resultant magnetomotive
force C could be replaced by a magnetic field or flux, resulting
from such magnetomotive force. If this magnetic field is
plotted to the same scale as the magnetomotive force which
produces it, then C, in Figs. 2 to 5, can represent a magnetic
field. This field will be constant in value and of half the peak
value of the field which the single-phase magnetomotive force
alone would set up.
Thus according to Figs. 2, 3, 4 and 5, by the introduction of an
"opposing" magnetomotive force, equal m value to one of the
component magnetomotive forces of the single-phase and rotating
synchronously with it, one of the two components of the mag-
netic field can be suppressed and only the other component left,
FIG. 5
the resultant is thus a rotating magnetic .field, just as in the
polyphase induction motor.
However, a further modification of this should be considered.
Assuming again, that the single-phase primary magnetomotive
force is replaced by its two equal rotating components, as in Figs,
2 to 5, then by the addition of an opposing magnetomotive force,
similar to B in the same figures, but of less value than the com-
ponent D, then the resultant of this opposing magnetomotive
force and the component D is a reduced magnetomotive force
of the same polarity as D. There will then remain two magneto-
motive forces, each of constant value, one of half the peak
value of A and the other of some smaller value, depending upon
the opposing force B. These two rotating magnetomotive
forces can, therefore, set up two oppositely rotating fields of
unequal value. These are illustrated in Figs. 6, 7 and 8r
In Fig. 6, B is assumed at some less value than the component
D. The resultant of D and B is shown as E. Therefore, at this
SINGLE-PHASE INDUCTION MOTOR
531
position C and E represent the two resultant magnetomotive
forces and the two component fields. In Fig. 7, the conditions
are shown for thirty degrees shift and here again E and C repre-
sent the two fields. In Fig. 8 the shift is for sixty degrees.
Thus by the introduction of a constant "opposing" magneto-
motive force of less than either of the components of the single
phase, two oppositely rotating fields of unequal value may be
set up. As extreme cases of this, if the constant opposing' mag-
netomotive force is made zero in value, the magnetic field corres-
ponding to its position and rotation will rise to the full value of
the oppositely rotating field; and, on the other hand, if the
constant opposing magnetomotive force is made half the peak
value of the single phase, the correspondingly rotating field
becomes zero. Both of these cases are in accordance with the
oarlier assumptions
The above conditions of the single-phase primary magneto-
\
FIG. 6
FIG. 7
motive force and a constant secondary one, in opposition, which
may be of half the peak value, or some less value down to zero,
and which rotates synchronously in one direction, resulting in two
magnetic fields which may be of equal or unequal value, and
which rotate synchronously in opposite directions, all form
essential parts in the physical conception or visualization of the
actions of the single-phase motor which will be given below.
It should be observed that in the above method of considering
the production of a rotating field in the single phase induction
motor, the two primary components of the single-phase magneto-
motive force and the secondary damping magnetomotive force
all rotate synchronously, and such rotation is independent of the
speed of the secondary core. In some methods of considering the
single-phase induction motor problem^ the single-phase primary
winding is assumed to generate a magnetomotive force in the
secondary which, by rotation of the core, is carried around until
it generates- a second magnetic field or flux at right angles to the
532 ELECTRICAL ENGINEERING PAPERS
original primary flux, thus giving the equivalent of a polyphase
magnetic field. - However, the above method does not involve
such method of treatment.
It should also be recognized that the foregoing analysis only
covers no-load conditions and that with the addition of load new
conditions are brought in to the problem. These, however,
will be brought out later, for the no-load conditions require
further consideration, especially as regards the generation of the
primary counter e. m. f. by the above descnbed rotating fields.
As already shown, there may be a single magnetic field rotating
synchronously, or there may be two component fields of equal
value rotating in opposite directions, or there may be inter-
mediate conditions of oppositely rotating fields of unequal value,
depending upon the value of the damping or opposing secondary
magnetomotive force.
FIG. 8
COUNTER E. M. P. GENERATION AND EXCITATION
Considering next the counter e. m. f . generated in the primary,
we should first look into the e. m. f. conditions produced by two
oppositely rotating fields of equal values. If the secondary
circuits are open, the two component fields are both present and
are concerned in the generation of the counter e. m. f . This is
true whether the secondary is stationary or is rotated at full
speed. If, however, the secondary is closed upon itself, then
when running at speed, one of the component fields is practically
damped out and the other jnust generate the entire primary
counter e. m. f. Thus, two entirely different conditions are
encountered, depending upon whether the secondary is open or
closed. To explain this properly, some further analysis is re-
quired, as follows:
In the first place, it may.be stated that the e. m. f., produced
in the primary winding by cutting its two component fields, is the
same as that generated by the single phase sine shape field,
varying sinusoidally and acting on the primary winding as in a
SINGLE-PHASE INDUCTION MOTOR
533
transformer. Herein lies a simple illustration of the equivalence
of the transformer and the flux cutting methods for calculating
e. m. fs. In Figs. 9, 10 and 11, are shown several positions of
the two oppositely rotating fields and their relation to the
primary winding.
In Fig. 9 is shown the magnetic flux, or field, A, which is set
up by a primary winding a. This winding, of course, would
FIF. 9
require a tapered distribution to give such a field. This is
mentioned incidentally as it has no direct bearing upon the
explanation, except from the mathematical standpoint.
Assuming the single-phase field at its maximum or peak value,
then, at this instant, the two component fields, B and C, each
of half the peak value, will coincide both in position and polarity.
From the transformer method of calculation, the e. m. f. gener-
Fia 10
ated at this instant, in the winding, will be zero, as the rate of
change of the flux is zero. Also from the flux* cutting method,
the e. m'. f . in the primary winding will be zero, for, as is evident
from the figure, each belt or group of the primary winding is
cutting fields which have equal positive and negative areas or
values.
Considering liext the conditions in Fig. 10, in which the two
rotating components have traveled ninety degrees. The fields
534
ELECTRICAL ENGINEERING PAPERS
are shown as B and C It is evident that the resultant of these
two fields is zero in value, that is, the single-phase field is passing
through its zero value, and, accordingly, is generating the maxi-
mum e m f. by the transformer method Also, considering
component B of the rotating fields, obviously, by the cutting
method it is generating maximum e m. f in the winding: a Also,
component C is generating maximum e m f in winding a
However, as one of these fields is positive in this position and is
traveling in one direction, while the other field is negative and is
rotating in the opposite direction, the two e m fs will be in the
same direction, and thus will be added. Thus, from the figure,
this position will give the maximum e. m f. in the winding by
the cutting method It can be shown by calculation that this
maximum value is the same with either the cutting or the trans-
former methods of considering e m. f generation.
shows that both of the component fluxes must be taken
PIG. 11
into account in generating the total primary e. m. f , and if either
component is decreased in value or suppressed, the total e m f.
generated in the winding will be decreased correspondingly,
unless the other component is increased a corresponding amount.
Pig 11 is simply a continuation of the conditions of Figs 9
and 10, in showing an intermediate position of the component
field. The result is the same as if the two fields were momen-
tarily replaced by the field D
According to the above analysis, to produce a given counter
e. m. f, in the primary, with one of the component fields damped
out, the other component must be doubled in value It was
shown before that in the single phase induction motor, running
at. full speed with no load, the backward field is practically
damped out by the secondary current. Thus with only the
forward component field remaining, either the counter e m f.
will be halved or the forward flux component must be doubled,
the latter being the case This means, in turn, that the primary
SINGLE-PHASE INDUCTION MOTOR 535
magnetomotive force must be doubled in value. In other words,
suppressing one of the two rotating field components results
in doubling the no-load excitation of the motor. Furthermore,
doubling the magnetomotive force of the primary and thus doub-
ling the forward component of the field also doubles the
backward component, which, in turn, is suppressed by doubled
secondary current. The above conditions of doubled excitation
is on the basis of sine flux distribution. With other distributions
the same result holds approximately, but not exactly, due to
conditions involving the shape.of the field.
It is evident from the above that, with the secondary circuits
open, the excitation required is of constant value regardless of
the speed of the rotor core and windings; also when running at
speed, the primary excitation is doubled as soon as the secondary
circuit is closed. However, it is not obvious, on first considera-
tion, that even with the secondary circuits closed the primary
excitation falls to half the full speed value, when the motor is
brought to standstill. This involves load conditions which will
be treated later, but nevertheless' this feature may be brought
out at this time. The explanation lies in the fact that at rotor
standstill the damping action of the secondary current will be
exerted equally on both the forward and backward components
of the primary field, so that necessarily these must be maintained
at equal value, and, by the above analysis, this requires but half
the excitation, compared with the no-load full-speed condition
where the backward field is practically completely suppressed.
LOAD CONDITIONS
When the single-phase induction motor is loaded, the total
input current can be considered as made up of two components,
namely, the no-load (practically all magnetizing) and the load
current. This latter is simply the increased current in the pri-
mary due to the load and does not entirely represent energy.
This load current, being single-phase, may be represented by two
equal oppositely rotating magnetomotive forces in the primary
of the motor, just as in the cas6 of the no-load current. The
fields which these two magnetomotive forces tend to set up are
both practically suppressed by two equivalent secondary mag-
netomotive forces rotating in opposite directions. The forward
secondary component corresponds to the secondary load mag-
netomotive force in the polyphase motor and the interaction
between this magnetomotive force and the forward primary field
536
ELECTRICAL ENGINEERING PAPERS
develops torque just as in the polyphase motor. The backward
component, at first thought, would appear to develop an opposing
torque, corresponding in value to that of the polyphase motor at
approximately 200 per cent slip. This, however, is not the case,
for at this slip the ordinary polyphase motor takes an excessive
primary current tending to develop a large magnetic field, which
is suppressed by a correspondingly large secondary magneto-
motive force. In the single-phase induction motor, howlever,
the primary backward rotating magnetomotive force component,
due to the load current, can be only of the same value as the
forward. This fact must be borne in mind as it is a very import-
ant factor in the later analysis.
To illustrate the characteristics of thfe single-phase induction
20
40
60
j 80
I too
[120
140
160
200
A
iZ
4-
10 20 30 40 50 60 70 80
TORQUE
FIG ,12
motor, it may be compared with the action of two polyphase
induction motors rigidly coupled together,, and connected to the
line to give opposite rotations. Such a set or unit has certain
characteristics which are so similar to those of the usual single-
phase induction motor that on first consideration one would
assume them to be identical. However, a more careful study of
the individual operating conditions shows that the similarity
is only a general one, and a number of decided discrepancies are
found.
The characteristics of the above two-motor unit and the single-
phase motor may be compared as follows:
(1) The speed torque characteristics of the two motors of the
polyphase unit may be represented by A and B in Fig. 12 and
SINGLE-PHASE INDUCTION MOTOR
537
their resultant by curve C. According to this latter curve, the
resultant torque is zero at standstill, and a slight change in speed
in either direction will give an effective torque tending to speed
up the unit in whichever way it is started. This, therefore,
corresponds to the well known starting characteristics of the
single-phase motor.
(2) It may also be seen that the maximum torque the unit
develops is materially less than that of either of the two com-
ponent motors This fact is also consistent with single-phase
motor operation compared with the same machine on poly-
phase.
(3) At full speed, according to this resultant curve, the slip
20
40
60
120
.
140
160
180
200
7
I
L
7
0 10 20 30 40 50 60 70 80
TORQUE
FIG. 13
for a given torque is very much larger than that of the corre-
sponding polyphase motor. This is not true of the single-phase
motor and herein lies one of the discrepancies in this method of
illustrating the operation.
(4) It is well known that in the' polyphase motor the maxi-
mum torque it can develop, with constant voltage applied, is
independent of the secondary resistance; while, in the single-
phase motor, in general, an increase in the secondary resistance
will decrease the maximum torque and a decrease will have the
opposite effect. This may be illustrated by repeating the curves
of Fig+ 12 with modified secondary resistance in the two com-
ponent motors. In Fig. 13 the secondary resistance is increased
and in Fig. 14 is decreased relatively to that of Fig, 12. The
538
ELECTRICAL ENGINEERING PAPERS
resultant speed-torque curves for the three figures show that the
maximum torques are materially affected by the secondary re-
sistance. The same holds true for the single-phase induction
motor.
10 20 30 40 50 60 70 80
TORQUE
FIG. 14
(5) However, this method of illustrating the characteristics
of the single-phase motor torque fails when -the conditions of
secondary resistance is such that the maximum polyphase torque
o
20
40
60
_
«>
"0
120
140
160
180
200
0 10 20 30 40 50 60 70 80
TORQUE
PIG. 15
is developed at about 100 per cent slip. Fig. 15 illustrates this.
From this speed torque curve it appears that the unit has a very
low resultant torque, but this is not the case in the single-phase
SINGLE-PHASE INDUCTION MOTOR
539
induction motor, for with a polyphase motor developing its
maximum torque at 100 per cent slip, the same machine on single-
phase will give a very considerable maximum torque. Herei
again is a discrepancy which the assumed equivalent arrange-
ment does not cover properly.
(6) In Fig 16, the current-torque curve D, for the component
motors in the above figures, is shown. This indicates plainly
what a wide discrepancy there is between the currents taken by
the primaries of the two motors when running at speed. For
example, at a given speed a, the current taken by the forward
rotating motor is b, while c represents the current taken by the
backward motor. Obviously, the current taken from the line,
which is the resultant of b and c, is much greater than that re-
quired to produce the resultant torque and the power factor of
such a unit must necessarily be very poor. However, such is not
the case with the single-phase
motor, for the inputs and the
power factors are not greatly
different from those of polyphase
motors of the same capacity.
Herein lies a radical difference
between the single-phase motor £
and the above assumed unit.
(7) Another difference be-
tween such a unit and the true
single-phase motor lies in the
no-load or magnetizing input.
Obviously, the combined magnetizing components for the two
motors will be twice as great as for a single machine, whereas,
in the single-phase motor the magnetizing input is practically the
same as in the corresponding polyphase machine. Here is
another pronounced discrepancy.
It is evident from the above that while this method of illus-
trating the action of the single-phase motor by means of two
polyphase motors, coupled for opposite rotation, is in the right
direction, some special modifying conditions must be introduced
to account for the discrepancies. The action of this two-motor
unit, therefore, will be followed up further, with the introduction
of certain modifications derived primarily from consideration of
certain characteristics of the single-phase induction motor itself
In the first place, curves A , B and C of Pig. 1 2 were based upon
equal and constant e. m fs. applied to the terminals of both
100
TORQUE
PIG. 16
540
ELECTRICAL ENGINEERING PAPERS
motors. That this is not a correct assumption can be deter-
mined from the operating conditions in the single-phase motor.
From the analysis of the component rotating fields it was shown
that at full speed the backward component was practically
damped out by a secondary ^magnetomotive force, thus leaving
only the forward component, which then rose to practically
double value in order to generate the required e, m. f . However,
at standstill, the secondary winding holds the same rotational
relation with respect to both component fields and, therefore,
neither field can be damped out more than the other. Conse-
quently, at standstill, both component fields are equal in value
and the counter e. m. f. of the primary is generated by the two
oppositely rotating fields, instead of a single one of double value
180
200 , .
0 10 20 30 40 50 60 70 80
TORQUE
FIG. 17
as is the case at full speed. Therefore, at standstill, the forward
field is of only half the value of the full speed field. This corre-
sponds to the operation of the polyphase motor at half field
strength, that is, with half the primary voltage applied, thus re-
quiring one-quarter the magnetizing input. The same voltage
condition applies also for the backward component at zero speed.
It would appear, therefore, that in the unit composed of two
polyphase motors coupled together, the voltage applied to the
terminals of the forward motor should be at practically full value
at synchronous speed and should fall to half value at standstill
or 100 per cent slip, and should have practically zero value at
200 per cent slip. Then assuming, as a first approximation,
that the decrease in voltage from full speed to 200 per cent slip
SINGLE-PHASE INDUCTION MOTOR
541
is. a straight line law, new speed torque curves, corresponding to
Fig. 13, but with the torques decreasing as the square of the
voltage, can be illustrated as in Fig. 17. Here curves A and B
correspond to Fig. 12, while D and E correspond to the above
proportionate reductions in voltage. The resultant F of these
latter curves is also shown.
This new resultant F is similar in general shape to C of Fig. 12,
but indicates some quite different characteristics. For instance,
at the higher speed values it coincides quite closely with the
polyphase speed torque curve, which is actually the case in the
single-phase motor. In the second place, with high secondary
resistance, as shown in Fig. 15, the speed-torque curves are
modified a's in Fig. 18, which shows both the former characteristic
20
40
60
§5 80
140
160
180
200
X
A
FIG. 18
10 20 30 40 50 60 70 30
TORQUE
and the new one. Here the resultant torque, under the new
assumption is materially higher and more nearly conforms with
the condition in the single-phase motor.
Under the earlier assumption of constant voltage on both
motors, it was shown that the magnetizing current would be
twice as great as in the single-phase motor. On this new assump-
tion, however, at full speed, with practically full voltage on one
motor and zero voltage on the other, the total magnetizing cur-
rent will be only half as great, and will approximate that of one
motor alone, and, therefore, that pf the single-phase 'rtiotor.
Furthermore, under the new assumption, the current taken
by the primary of the backwardly rotating motor is quite small
at high speed and, therefore, the resultai^t current taken from the
542
ELECTRICAL ENGINEERING PAPERS
line is not excessive and is more nearly consistent with actual
single-phase motor conditions.
Thus, with this new condition of reduced terminal voltage with
reduction in speed, practically all the conditions of the single-
phase motor are met, except possibly from the quantitative view-
point. The two-motor combination thus serves as a very good
illustration. There is, however, one further condition which
must be rigidly met if the new curves are to be reasonably exact,
namely, the primary currents taken by the two motors must be equal,
for, as shown in the early part of this analysis, the forward and
backward rotating components of the primary current in the
single-phase induction motor are equal at all times. Conse-
quently to duplicate this condition, the primary e. m. fs. im-
TORQUE
FIG. 19
pressed upon the terminals of the two polyphase motors should
be varied in such a way that the primary currents will always be
equal. In addition, it is assumed that the sum of the two im-
pressed voltages is constant. This, however, is only an approxi-
mation.
The next step is to determine what is the actual law of voltage
variation which will satisfy the above conditions of current and
voltage. A ready means for obtaining this lies in the speed-
torque and current-torque curves of the polyphase motor at
constant voltage. From the current-torque curve at constant
voltage corresponding curves for any other voltage can readily
be plotted by varying the abscissae as the square of the voltage
and the ordinates directly as the voltage. This is illustrated in
Fig. 19. Here A is the polyphase motor speed-torque curve at
SINGLE-PHASE INDUCTION MOTOR 543
constant voltage B represents the part below the 100 per cent
slip line, but turned above the zero speed line for convenience.
B can also be considered as the back torque at full voltage, but
thrown to the right of the zero torque line for convenience.
Curve C represents the primary current for full voltage condi-
tions Then at a speed a, for example, the primary currents
corresponding to the forward and back torque will be b and c
respectively.
Assume next that the voltage is halved for both rotations, then
the new speed-torque curves will be A\ and B\ in which the tor-
ques are reduced as the square of the voltage. The new current
curve will be C\. The currents for speed a will now be 61 and
ci, or half of b and c, as they are varied as the voltage.
The above figure is simply to illustrate the rule for variation
of the primary current with the voltage, in the polyphase motor,
and does not represent the actual conditions which we are after;
for in the above the voltage reductions are the same for both the
forward and the back torques. But, according to our former
analysis, this condition of equal voltages, for the two rotations,
holds only for the 100 per cent slip point. For other speeds the
two voltages are reduced unequally, but with the sum of the two
approximately constant according to the assumptions.
If, for any speed a, we let x represent the percentage of voltage
reduction for the forward torque, then 1 — x will represent the
corresponding reduction for the back torque. Let // be the
primary current, corresponding to the forward torque for this
speed at full voltage, and /& the current for the back torque at
the same speed and also for full voltage. Then Ifx will represent
the primary current at the reduced voltage for the forward
rotation and Ib (1 — x) will be the primary current for the back
rotation. One of the conditions of our two-motor unit, to make
it correspond with the single-phase motor, is that these two
primary currents must be equal. Therefore, Ifx =* Ib (1 — x)t
and
and (1 -
The above allows the determination of the percentage x of
full voltage which must apply for each speed between zero and
synchronism, when the values of the current If and Ib for full
voltage are known.
A second method of determining the percentages of vqltage
544 ELECTRICAL ENGINEERING PAPERS
for the two rotations is available when the speed-torque curve
of the motor on single phase has been determined, by test or
otherwise. By our former assumption this single-phase torque
is the difference between the speed torque curves for the forwar^
and backward rotations with the respective voltages reduced
the proper percentages. These torques for any given speed vary
as the square of the terminal voltage. For example, calling Tj
the forward torque, at full voltage and speed a, and T$ the back
torque, and Ti the single phase torque for the same voltage and,
speed, then Tfoc2 — Tb (1 — x)z = TI, from which x may be
determined, with Tf, Tb and Ti known.
>It would appear from the preceding that, if the assumptions
made are anyways close to the actual conditions, this method of
analysis shows a means for deriving the single-phase speed-
torque curve from the polyphase curves of the same machine.
Methods of calculating the primary current and speed-torque
characteristics of the polyphase motor have been developed quite
completely, so that it is not necessary at this place to give any
details of such methods. The accuracy of the methods for calcu-
lating the polyphase curves depends almost entirely upon the
correct determination of the reactance and saturation constants.
All methods for the direct determination of the single-phase
speed-torque characteristics also involve the use of corresponding
reactance and saturation constants. Therefore, the above
method brings in no new and more difficult conditions. The
primary object of this paper, however, is not to develop a new
method of calculation, but simply to give a better conception of
the close relation of the single-phase and polyphase characteris-
tics.
After development of the above method, an attempt was made
to check it by applying certain existing test data, but without
positive results, although the indications were quite satisfactory.
It was discovered that in all the existing test data at the writer's
command, where the polyphase speed-torque and current-
torque curves has been obtain by actual test, constancy of
temperature had been more or less disregarded. The effect of
change in the secondary resistance on the polyphase speed-
torque curve is to change the slips but not the maximum torque.
The difficulty, however, in the polyphase tests available was that
apparently the resistance had varied very considerably during
the tests, especially at the points of high slip, where the second-
ary losses were very large. As a result the speed-torque curves
SINGLE-PHASE INDUCTION MOTOR
515
corresponded to those of motors in which the resistance increase^
as' the Ipad and slip increased. ^ As a consequence, the torques
below the zero speed line were considerably too large, which
meant that in applying these curves to the above method, the
back torques were presumably entirely too great, thus apparently
introducing errors in the derivation of the resultant single-phase
curve.
The effect of these discrepancies are shown in Fig. 20. Here,
A shows the speed-torque curve as it should be at constant tem-
perature,, whereas, B shows the curve with the resistance of the
secondary increasing with increased slip. The corresponding
current-torque curves are also shown. A consideration of these
curves would seem to indicate
that the resultant single-phase
curves derived from A and B
should differ somewhat.
It was then decided to make
a more accurate set of tests on a
10 h.p., 60;cycle four-pole, three-
phase motor of the wound- •
secondary type, so that the i
secondary resistance could be !
varied if so desired. It was also <
decided to obtain a test with two
similar motors rigidly coupled
together, with their individual
primary windings in series, but
with their secondaries indepen-
dent. As already explained, the
theory of the foregoing method
calls for equal currents in the two oppositely rotating fields. This
condition is automatically obtained by coupling two primaries in
series with each other.* With this arrangement, if the power
factors of the two motors were always equal, then it should be
equivalent to the method already described. However, these are
practically never equal except at the standstill position, although
an analysis of the problem shows that the two primary voltages,
with this series arrangement, are not greatly out of phase with
each other over a very large part of the working range. The
writer has not yet sufficiently analyzed the series arrangement
*In reviewing an early draft of this paper, thfe suggestion, with a number of other most
excellent ones* was made by Mr. R. B. Hetaond- Hoover, it developed later that tfcfe 9amg
suggestion appeared ab<mt twenty years agoin Mr. B. A. Behxend'sboofc/^The Induction Motor/1
0 10 20
30 40 50
TORQUE
FIG. 20
60 70 BO
546 ELECTRICAL ENGINEERING PAPERS
to be sure that it exactly represents all the conditions of the
two rotating fields in the single-phase motor, but is inclined to
think that such is the case. However, the approximate method
developed in this paper lends itself so readily to calculation, that
it was considered worth while to check it up carefully by test
to see what degree of accuracy could be obtained.
The following series of tests was planned:
(1) Three-phase speed-torque and primary current curves
at 220 volts with one motor alone, with its secondary short-
circuited on itself.
"(2) Single-phase speed-torque and primary current curves on
the same motor as (1) at 220 volts and with the secondary
short-circuited on itself.
(3) Three-phase speed-torque and primary current curves on
the same motor and at same voltage, but with external resistance
in the secondary circuits.
(4) Single-phase speed-torque curves under same conditions
as (3).
(5) Speed-torque and primary current curves with two similar
motors with their primary windings coupled in series, and with
the secondaries independently short circuited on themselves, one
of these motors to be that used in tests (1) arid (4)
(6) Similar tests to (5), but with resistance in the secondaries
as in (3).
In carrying out these tests, the torque was measured by a
special dynamometer brake, the power absorbing element of
which consists of a special separately-excited direct-current
machine. Below zero speed, power was supplied to the direct-
current machine in order to obtain negative rotation.
Difficulties in obtaining consistent tests, especially at negative
speeds, soon developed, due to variations in temperature. With
the very heavy currents at low and at negative speeds, the
motor would heat so rapidly that all kinds of speed-torque
readings could be obtained. Test after test was made and while
these would agree very well for the higher speed points where
the heating was small, they showed all kinds Of inconsistencies
for the negative speeds, in particular. The currents for these
speeds also showed very wide discrepancies Eventually it
was found that those tests taken with extreme rapidity, and
which covered only a comparatively small number of points,
would plot in quite reasonable curves above zero speed, so that
the writer was enabled thus to obtain quite consistent curves
SINGLE-PHASE INDUCTION MOTOR 547
for both torque and current between 1800 rev. per min. and
standstill. Not only were the curves, consistent in themselves
but those taken with different secondary resistances were fairly
consistent with each other. It then remained to obtain rea-
sonable readings for the negative speeds. Obviously it was
wrong to take a large number of test points and then draw
an average curve through them, for it is evident that the er-
rors, due to heating, tend to throw the torques and currents
to one side of the proper curves. Consequently the correct
curves should really be boundary lines rather than averages. It
was noted, in particular, that heating did not appear to affect
the speed to the same extent as the torque at very large slips,
and, consequently, by plotting the current in terms of speed
rather than torque, less erratic curves were obtainable, and it
was possible to plot speed-current curves which were quite con-
sistent for the different conditions of secondary resistance.
Furthermore, from the speed-torque and speed-current curves
above the zero line, which appeared to be reasonably correct,
as they were consistent with each other, it was possible to de-
rive the constants for the general equations for speed-torque.
It was found that such derived equations fitted these curves
quite accurately and, moreover, they held the proper relation of
constants for both high- and low-resistance secondaries The
various agreements between the calculations and the tests for the
higher speeds were such that one could assume that the derived
equations were practically correct and that from them the curves
for the negative speeds could be plotted with fair accuracy. In
this way the curves for the negative speeds were first obtained
and it then remained to check them by actual test. Finally a
method of testing was tried which appeared to give quite good
results. This consisted in setting the apparatus at about the
desired speed and torque conditions ; then cooling the motor down
to the required temperature preparatory to obtaining the desired
test, the power was then thrown on and readings obtained in the
shortest possible time, five seconds, for instance. Allowing the
motor to run, additional readings were obtained at five second
intervals. A series of consecutive readings, at definite intervals
apart, was thus obtained and plotted in a curve. By extending
this curve back to the instant of starting, results were obtained
which were undoubtedly quite close to those corresponding to
the starting temperatures, and were not only quite consistent
with each other, but also plotted very close to the negative exten-
548
ELECTRICAL ENGINEERING PAPERS
sions of the calculated curves. As a result of a series of tests
extending over several weeks, data was obtained which plotted
in curves which agreed fairly well with each other throughout.
20
0 Points on Curve without External Resistance
200 o
10
20
30 40 50
TORQUE IN POUNDS
FIG. 21
60
70
80
RESULTS OF TESTS
Polyphase Speed-Torque, Speed-Current and Current-Torque
Curves
In Fig. 21 are shown the polyphase speed-torque and primary
current both with the secondary short-circuited, and with re-
sistance added In the speed-torque curves the circled points
SINGLE-PHASE INDUCTION MOTOR
549
torque test was selected in which no correction had been made
for temperature and where the conditions were quite closely
comparable with those of the single-phase tests. From the
speed-torque and current data of this polyphase test, the re-
sultant single-phase speed-torque curve was calculated, making
no attempt at corrections of any sort. This speed-torque curve
is represented by the small squares in Fig. 23. This lies much
closer to the tested single-phase curve, thus indicating that tem-
perature is possibly an explanation of a considerable part of the
discrepancy between the calculations and the tests. This would
TABLE II.
Primary
Reduced
Slip
Torque at
amperes per leg
torque
Re-
full voltage
at full voltage
X -
suit-
For
For
ant
tor-
posi-
nega-
j
For-
que
tive
tive
Tf
Tb
If
Ib
*
1-x
ward
Back
speeds
speeds
f
0 02
1.98
8.2
64 3
12 5
134 2
0.915
0 085
6 9
0 5
6 4
0 05
95
18.9
64 8
18 0
133.8
0 881
0 119
14 7
0 9
13.8
0 10
90
33 3
65 4
28 0
133.0
0 826
0 174
22 5
2 0
20.5
0 15
85
41 5
66 1
37 0
132.3
0 781
0 219
27.5
3 2
24,3
0 20
80
53 1
66 9
46 0
131 5
0 740
0 260
29 3
4 5
24 8
0 25
75
59 8
67 6
53 0
130 8
0 712
0 288
30.3
5 6
24 7
0 30
70
65 1
68 4
60 0
130.0
0 684
0 316
30 5
6.8
23 7
0 35
65
69 2
69 1
66.0
129.0
0 662
0 338
30 4
7 9
22 5
0,40
60
72.2
69 9
71.2
128 0
0 643
0 357
29.9
8 9
21 0
0.50
50
76 5
71.4
81 0
125.5
0.608
0.392
28.2
11.0
17 2
0 60
1,40
78 7
72 9
88.0
122 7
0 582
0 418
26.6.
12 7
15 9
0 70
1.30
79.6
74.4
94.0
120 0
0 561
0 439
25 0
14 4
10 6
0.80
1 20
79 6
75 9
99.5
118.1
0 542
0 458
23.4
15.9
7.5
0 90
1.10
79.2"
77.8
104.0
112.2
0.519
0.481
21.4
18 0
3 4
1 00
1.00
78 9
78 9
108 2
108 2
0 50
0 50
19.7
19 7
0
also indicate that heat effects as referred to in connection with
Fig. 20 are not as objectionable as anticipated However, the
writer does not believe that all the discrepancy is due to heating,
but considers that this approximate method of dealing with the
problem makes the back torque too small In the arrangement
with two motors in series, as mentioned before, the voltages of
the two motors will not usually add up directly to give the line
voltage, and the motor which represents the back torque, will
have a relatively larger percentage of the total voltage than is
tlie case with the above method of considering the prpblexn.
This will be considered further under the two-motor tests,
550
ELECTRICAL ENGINEERING PAPERS
Unfortunately, due to the very short time available, it was
not possible to make any extended tests on single phase with
a view to correcting for temperature In consequence, the
calculated single-phase speed-torque curve, which is on the
basis of constant temperature, is compared with tested curves in
which no temperature correction has been made. It, therefore,
is noL known in this case how much of the discrepancy is due to
temperature.
In Table II is shown data similar to that of Table I, but for
the tests with resistance in the secondary. It will be noted that
the resultant of the forward and back torques is considerably
lower than in Table I, which is consistent with the fact that in-
10
20
30 40 50
TORQUE IN POUNDS
FIG. 22
60
70
creased secondary resistance reduces the maximum torque of the
single-phase motor.
In Pig. 23 is shown the calculated single-phase speed-torque
and the tested torques of the motor with resistance in secondary.
Here the circled dots represent the actual test readings and the
crosses represent the points obtained from the last column of
Table II, The discrepancies are somewhat smaller than in the
motor with short circuited secondary. This should be the case,
if heating is responsible for any considerable part of the dis-
crepancy, for the currents are relatively smaller.
In order to get a crude idea as to how much of the difference
may be due to this feature of temperature, a polyphase speed-*
SINGLE-PHASE INDUCTION MOTOR
551
represent actual test readings, while the solid line covers the
points calculated from the derived equations.
In Table I, covering data on the short-circuited-rotor tests,
are shown the forward and back torques and the corresponding
forward and back currents for the various speeds between zero
and 200 per cent slip, as derived from Fig. 21; also the calculated
values of the ratio of voltages, x and (1 — #), by which the for-
ward and back torques should be reduced in order to get the
equivalent single-phase speed-torque curve. The corresponding
reduced values for the forward and back torques are also given
as calculated from the values x and (1 — x). The last column
shows the difference between the reduced forward and back
torques, which should represent the single-phase torque, accord-
ing to the foregoing analysis.
TABLE I
Primary
Reduced
Slip
Torque at
amperes per leg
torque
Re-
full voltage
at full voltage
X -
sult-
For
For
tor-
posi-
nega-
lh
For-
que
tive
tive
Tf
?b
*f
lb
1 — »
ward
Back
speeds
speeds
f b
0 02
1 98
20
35 8
19 0
154 8
0 89
0.11
15 8
0 4
15 4
0 05
1 95
41
36 3
34 0
154 5
0 819
0 181
27,5
1 1
26 4
0 10
1 90
61 7
36 9
55.5
154 0
0 735
0.265
33 3
2 6
30.7
0.15
1 85
71 6
37 7
71 0
153 5
0.684
0 316
33 5
3 8
29 7
0 20
1 80
77 3
38 3
85.0
153 0
0 643
0 357
31 9
4 9
27 0
0 25
1 75
79 4
39 2
96 0
152 5
0 614
0 386
29 9
5 9
24 0
0 30
1 70
79,6
39.9
104 0
152 0
0 594
0 406
28 1
6 6
21.5
0.35
1,65
78 8
40 8
110.0
151 5
0 580
0.420
26 5
7 2
19 3
0.40
1 60
77 6
41 6
113.0
151.0
0 572
0.428
25 4
7 6
17 8
0 50
1 50
74 0
43 6
121.0
150 0
0.554
0 446
22 9
8 7
14 2
0 GO
1 40
70 0
45 5
128.0
149 0
0 538
0.462
20 3
9 7
10 4
0 70
1 30
65.9
47 8
133 0
147 3
0 526
0.474
18 2
10.8
7.4
0 80
1 20
62 1
50.0
136 5
145,5
0 516
0 484
16 6
11 7
4 9
0 90
1 10
58 8
52 7
139 5
143 5
0.507
0 493
15 1
12 8
2 3
1 00
1 00
55 5
55 5
141 5
141 5
0 50
0 500
13 9
13 9
0
In Fig. 22 are shown the single-phase speed-torque and cur-
rent-torque curves with short-circui ted secondary, as plotted from
Table I, and checked by actual test. The circled dots represent
actual test points, while the crosses represent points plotted from
the last column in Table I. The agreement of test and calcu-
lated values are as close -as can really be expected considering
the difficulties in obtaining the data, and the possible errors.
552
ELECTRICAL ENGINEERING PAPERS
Two Motors in Series
In Table III is shown the test data and the calculations de-
rived therefrom, for two motors with their primaries in series
and with their secondaries short-circuited independently In
this test no external resistance was used in the secondaries.
Considerable difficulty was encountered in making this test, due
partly to bad alignment of the machines, as they were rigidly
coupled together. Furthermore, in several of the earlier tests,
the effects of temperature were disregarded and all indications
were that the secondaries were quite hot during the tests. There
was so much discrepancy between the various results that the
10
20
30 40 50
TORQUE IN POUNDS
FIG. 23
70
80
writer cannot feel sure of the data shown, in this table, although
it was obtained under quite careful conditions of test.
In the above table the percentage of line voltage applied to
each motor is shown. It is of interest to" compare these per-
centages with those shown in Table I. This is illustrated in Fig.
24. This shows that the percentage of voltage on the forward
rotating motor is higher at the higher speeds, than in Table I,
but is lower at the low speeds. On the other hand, the voltage
on the backward-rotating, motor is higher at all speeds than in
Table I. Thus, the back torque has always a higher value than
in Table I. Consequently, with the reduced forward torque at
the lower speeds and the higher back torque, the resultant torque
SINGLE-PHASE INDUCTION MOTOR
554
ELECTRICAL ENGINEERING PAPERS
derived from the polyphase curve will naturally be lower than
in Table I, which appears to be the case in all the tests made.
The data in Table III indicate that the two motors have their
10 20 30 40 50 60 70 80 90 100
PERCENT OF VOLTAGE PER MOTOR
FIG. 24
primary voltages very nearly in phase at all times. The sum of
the two motor voltages is never much greater than that of the
line.
20
60
100
10
15 20
TORQUE IN POUNDS"
FIG. 25
25
30
In Fig. 25 is shown the calculated and test speed-torque results
corresponding to Table III. The test result shows lower torques
at the low speeds than can be derived from the voltage percent^
SINGLE-PHASE INDUCTION MOTOR
555
8-3
n3
I
6 •
ooooooooooooo
Sg S g S
oootoiflooooiaooo
ooooooooooooo
556
ELECTRICAL ENGINEERING PAPERS
ages applied to the polyphase torques Part of this difference
may be due to temperature conditions.
0
20
40
60
80
100
120
1Af\
S*
<**
u
Two-Motor
nit Forward Motor
\.
/
/
/
*
"-»
i An
//
/
'h
r
200
0
1
^~~
0 2(
^
X^-**1*
3 30 40 50 60 70 80 90 10(
PERCENT VOLTAGE PER MOTOR
FIG. 26
In Table IV is shown the corresponding data for two motors
with resistance in the secondary. Under this condition the
various tests made were more consistent with each other and
20
40
60
80
100
10 15 20
TORQUE IN POUNDS
FIG. 27
25
30
the writer has more confidence in the data than in the case of
Table III.
In Fig. 26 is shown the percentages of line voltage on each of
SINGLE-PHASE INDUCTION MOTOR 557
the two motors, compared with those in' Table II These show
the same differences as in Fig. 24, where there was no external
resistance.
In Pig. 27 is shown the speed-torque curve for both calculation
and test, as taken from Table IV. Here the discrepancies are
much smaller than in Fig, 25.
CONCLUSION
While the data is not as exact as the writer would desire, yet
he feels that the general results obtained from the various tests
have indicated that the method of analysis followed in this paper
is along proper lines and that this conception of the action of the
single-phase induction motor is of considerable assistance in
obtaining a proper understanding of the machine. As stated
before, the primary purpose of this paper is not to develop a
method of calculation, but is sinlply to illustrate some of the
characteristics of the single-phase motor. It is hoped that this
will bring out more clearly the very intimate relation between the
polyphase and single-phase induction motors in their operating
characteristics.
SINGLE-PHASE LOADS FROM POLYPHASE SYSTEMS
FOREWORD — This paper was presented at the thirtieth annual
convention of the Association of Edison Illuminating Com-
panies, held at White Sulphur Springs, Va , September, 1914.
Its purpose was to show some of the possibilities of phase con-
version from polyphase to single-phase, in view of the increasing
requirements for single-phase service for electric furnace work
and various other special applications. The paper deals with
some of the problems of synchronous phase balancers, etc. —
(ED.)
THE broad statement may be made that it is not practicable
to transform a polyphase load to single-phase by means of
transformers alone. There is a definite, positive reason for this,
namely, a single-phase load represents power which is pulsating
or varying periodically from zero to a maximum, value, while a
balanced polyphase load represents continuous power of constant
value. It is obviously not feasible to transform from continuous
power to pulsating, or vice versa, without some means of storing
and restoring power, which is not practicable with transformers.
Keeping the above statements in mind, it is obviously a waste
of time to attempt to accomplish the result by special transformer
connections or arrangements. However, many attempts have been
made to produce this result with transformers alone, and some with
superficial evidence of success — that is, in some cases, it has been
possible to load the three phases equally in current when delivering
single-phase load. But balanced currents in this case do not mean
balanced power loads, nor do they, as a rule, mean less total loss in
the generator windings. In fact, the equality of the currents in the
different leads is obtained simply by out-of -phase currents, part of
them usually being leading and part lagging. The resultant re-
actions and unbalancing effects of these leading and lagging cur-
rents have precisely the same effect on the generating system as
the single-phase alone would have.
On the basis therefore of storing and restoring power in order
to obtain balanced three-phase loads when delivering single-phase,
various possible methods of accomplishing this result may be con-
sidered. The obvious method is by means of a motor-generator in
which a three-phase motor drives a single-phase generator, the
entire single-phase load being transformed from electrical to
1 559 , •. :: -;
560 ELECTRICAL ENGINEERING PAPERS
mechanical, and then back to electrical*. Where entire inde-
pendence of the single-phase and three-phase currents is desired,
this of course, is the ideal method. On the other hand, it is
possibly the least efficient method. But where both change in
frequency and change to single-phase load are involved without dis-
tortion of the polyphase load conditions, then double transforma-
tion of power appears to be necessary, such as from electrical to
mechanical and back to electrical, or from electrical to some other
form of electrical power, involving a second complete transforma-
tion. The motor-generator is an example of the first, while trans-
formation from three-phase to direct current by a rotary conver-
ter, arid from direct current to single-phase of another frequency
by a second converter, is an example of the second.
Where the power-factor of the load is low, as in some electrical
furnace systems, one advantage of the motor-generator method is
that the power-factors of the supply system and the load are ab-
solutely independent of each other.
However, where the transformation from three-phase to
single-phase is at the same frequency, it would appear that part
of the single-phase load could be delivered directly from one phase
of the three-phase system, while the other part of the load could
be taken from the other phases and re-transformed in phase by
rotating apparatus to that of the single-phase load, so that otily
part of the load would thus need transformation. For instance,
assume that one-third of the single-phase power is taken from one
phase, and the other two phases supply power to a suitably wound
motor, which drives a single-phase generator having the same
phase relation as the third circuit of the three-phase system.
Obviously, the generator could feed its single-phase load in parallel
with the other single-phase circuit. The three generator circuits
would thus be equally loaded and the single-phase generator of
the motor-generator set would not be transforming the full single-
phase load. This illustrates the principle of transforming from
three-phase to single-phase without transforming the whole load,
but this particular arrangement of apparatus is not a very practical
one. But the question naturally arises whether this cannot be done
in comparatively simple manner by means of a single machine, con-
nected across the three-phase circuit, which will serve to transfer
power from part pf its circuits to others at a 'different phase
relation. This principle has been utilized in the past to transform
from single-phase to polyphase, and in the same apparatus the
SINGLE-PHASE FROM POLYPHASE
561
operation has proven to be reversible. It may, therefore, be con-
sidered as settled that such transformation is possible and practic-
able.
Fundamentally, the action of phase balancing is as follows:—
When a single-phase load is taken from a polyphase circuit, it tends
to distort the phase relations in the latter circuit. Any synchron-
ous or induction type polyphase motor connected to a distorted
polyphase circuit will act in such a way as to have a balancing
effect on its supply system. Any such motor will naturally tend
to do this, for the motor, with its own balanced phase relations will
tend to take current and load in accordance with the supply
voltages — that is, it will tend to takfe more from the higher volt-
ages, and if the power taken from the higher circuits exceeds the
load or losses of the motor itself, then the excess is fed back into
PIG I—SCHEME OP CONSTRUCTION FOR CONVERTING FROM
SINGLE-PHASE TO BALANCED THREE-PHASE
the lower voltage circuits. It thus has a balancing action on the
supply circuit. This is the natural tendency of all polyphase
synchronous and induction types of rotating machines when con-
nected to a supply circuit. However, in the motor itself, this
tendency to correct the unbalancing of the supply circuit will be
accompanied by a corresponding tendency inside the motor itself
to distort its own internal phase relations until they match those
of the supply system. But if the distortion of the phase relations
inside the motor can be prevented or neutralized in any manner,
then the motor will transfer loads between its phases or circuits
to such an extent that it wilLcorrect the tmbalanting of the poly-
562
ELECTRICAL ENGINEERING PAPERS
phase system. In other words, if balanced three-phase potentials
are held at the point of delivery of single-phase load, then the
three-phase supply system, up to that point, will be balanced.
The operation of the various phase-balancing methods therefore
lies in correcting the effects of the internal phase distortions in the
phase-balancing motor, whether it be of the induction or of the
synchronous type.
The action of a phase-converting device in a simple form can
probably be shown best by an arrangement used in railway work
for converting from single-phase to balanced three-phase, and
from three-phase to single-phase when acting regeneratively.
Fig. 1 illustrates such ah arrangement, consisting of a trans-
former, a phase splitter, and single and three-phase circuits. The
transformer is connected across the single-phase circuit, which, for
simplicity, also is shown as one phase of the three-phase circuit.
The phase splitter has one phase connected across the same phase
FIG 2— VOLTAGE CONDITIONS IN THE CIRCUITS INDICATED IN FIG 1
WHEN TRANSFORMING SINGLE-PHASE TO THREE-PHASE
as the transformer; while its other phase, which is wound in 90-
degree relation to the former, has one end connected to some in-
termediate point of the transformer, and its other is connected to
the third phase of the three-phase circuit.
The voltage relations, both without and with load, when
transforming to three-phase, are indicated in Fig. 2. In this
SINGLE-PHASE FROM POLYPHASE
563
diagram, ab represents the single-phase e. m. f. delivered to the
transformer. The line/c represents the e. m. f. generated in phase
2 of the phase splitter, this being 86.6 percent of ab. Therefore,
with fc at right angles to ab, lines ac, and ab are equal, and a
balanced three-phase circuit is obtained at the three-phase termin-
als.
Next, assuming that a three-phase load is carried, then, due to
internal distortions, fc is both reduced in value and shifted in phase
to the position fd. The three-phase voltage relations are then
indicated by ab, ad and bd. To correct this distorted condition,
assume (1) — that the e. m. f. across phase 1 of the phase converter
is increased sufficiently to increase the e. m. f . of phase 2, so that it
will be represented byfe, instead of fd, the increase being such that
a line connecting c and e will be parallel with ab. Then assume
(2) that the connection at / is moved along ab to a point g such
FIG. 3— VOLTAGE RELATIONS WHEN TRANSFORMING THREE-
PHASE TO SINGLE-PHASE
that/g equals ce. This brings terminal e to the position c, and the
internal phase relations will then be such that balanced e. m. f.'s,
corresponding to ab, ac and be, will be delivered to the three-phase
circuit when carrying load, and the three-phase circuit will neces-
sarily carry balanced three-phase load, although the source of
power is single-phase.
In Fig. 3 is shown a similar arrangement, except that the
transfer of power is from three-phase to single-phase, using the
564 ELECTRICAL ENGINEERING PAPERS
same apparatus as in Fig. 2. As in Fig. 2, ab, ac and be represent
three-phase balanced voltages, or the no-load condition. With
load, the conditions are the reverse of those in Fig. 2. The voltage
fc is shifted in phase with respect to ab, but in the opposite direction.
Also ab is shortened with respect to fc. The unbalanced phase
relations can therefore be represented by the triangle a^ bi, d.
Therefore, if aj)i is to be maintained at the value ab, then yd will be
increased proportionately tofdi, and the relations are represented
by the triangle abdi. This triangle therefore has to be corrected to
correspond with the balanced diagram abc. This can be done by
(1) reducing the e. m. f . of phase two of the phase converter (by
reducing phase one, for instance), and by (2) — moving /to g.
This brings di in coincidence with c and a balanced three-phase
condition then results.
It is obvious in Fig. 2 that the addition of an e. m. f . at the
terminal d corresponding in value and direction to the line cd
would have corrected to a balanced condition for the assumed
load and power-factor. Also, in Fig. 3, a correcting e. m. f. d\c
would have accomplished the desired result. In the actual dia-
grams, instead of supplying this correcting e. m. f . directly, it was
obtained indirectly by combining two right angle e. m. f .'s of suit-
able value and direction, these two being readily obtainable in the
arrangement shown. However, the illustration shows how a
single correcting e. m. f. of proper phase and value can correct
from a distorted three-phase system to a balanced system.
Instead of the above special arrangement for changing from
three-phase to single-phase, any standard type of three-phase
motor, either synchronous or induction, could be used for phase
balancing by the addition of a suitable correcting e. m. f. in one
of the phases, and if this correcting e. m. f . is of such value and
direction as to maintain balanced e. m. f.'s across the three termi-
nals, then the phase-balancing motor will correct the single-phase
load.
If an induction motor is used as a phase balancer under the
above conditions, then it will simply serve as a phase converter,
but has no ability to correct or adjust the power-factor. If the
phase balancer is of the synchronous type, however, it can be
adjusted and controlled to act as both a phase converter and a
power-factor corrector. If the single-phase load to be carried is
at a relatively low power-factor, then it will exert a demagnetizing
effect upon the phase balancer which must be taken into account
SINGLE-PHASE FROM POLYPHASE 565
when the e. m. f phase relations are adjusted for proper balancing.
This means that the field excitation of the phase balancer must be
increased sufficiently to overcome the demagnetizing tendency of
the single-phase load. This increase in field excitation will tend
to increase the e. m. f.'s of all the armature circuits but, as one
winding, when balanced conditions are obtained, will carry
practically all the wattless current corresponding to the single-
phase load, while the others will be carrying power only (on the
assumption that 100 percent power-factor is maintained on the
three-phase system) the effect of the internal self-inductions of the
phase balancer will be such that the resultant e. m. f.'s of some
of the windings will be increased to a greater extent than others
when the field excitation is increased. Therefore, when correcting
for inductive loads, a different value and direction of the correct-
ing e. m. f. is necessary than would be required for single-phase
loads without power-factor correction.
It is obvious from the above that what is needed for obtaining
balanced conditions and corrected power-factor on the polyphase
system when carrying a low power-factor single-phase load, is a
suitable synchronous motor acting as a phase balancer in connec-
tion with some auxiliary means for introducing a correcting
e. m f . which should vary in value and direction with the load and
power-factor.
There are various ways by which this result can be accom-
plished. To illustrate: It may be assumed that the desired
correcting e. m. f . may be obtained by means of a small synchron-
ously running booster which is connected in series with one phase of
the phase balancer. The value of this e. m. f . can be varied by vary-
ing the field excitation of the booster field. The phase relation of
this booster e. m. f . can be regulated in various manners, as, for
instance, by mechanically shifting the field structure circunofer-
entially with respect to the armature. Or, the armature of the
booster might have two fields side by side, but with their poles
displaced circumferentially 90 degrees with respect to each other.
Then, by separate adjustment of the excitations of the two fields
up and down, or reversed, the e. m. f . generated by the booster
armature can be given any desired direction or value. Or, instead
of two fields side by side, a single field structure can be used in the
booster, with two exciting windings overlapping or displaced 90
degrees with respect to each other, Kke the primary windings of a
two-phase induction motor. By proper adjustment of the- eafcdt-
566 ELECTRICAL ENGINEERING PAPERS
ing current in these two windings, the same results as with two
fields side by side may be obtained. With the booster e. m. f . thus
under control, it is obvious that any desired phase or voltage
correction can be obtained in the phase balancer. There are
various other ways of obtaining the corrective e, m, f., such as by
induction regulators, etc., but the above is sufficient to illustrate
the general arrangement or method of operation. Mr. E P. W
Alexanderson* has also proposed a method of accomplishing this
result.
The very considerable complication of such methods of phase
balancing may be necessary where widely fluctuating loads and
non-related variations in power-factor are encountered. In such
cases, automatic voltage regulations can be used in connection
with the main and the booster fields to obtain the desired cor-
rective action. However, combination of the synchronous ma-
chine and its booster, or boosters, requires, as a rule, considerably
less total apparatus than a straight motor-generator, and the
losses should also be materially less.
However, where the single-phase load conditions are not too
widely fluctuating, it is possible to use much simpler arrangements.
In electric furnace work the single-phase load and power-factor
may be almost constant when the load is on. In such cases,
phase splitting may be accomplished in a fairly simple and effective
manner by a single synchronous machine, either with or without a
small additional autotransformer, and with suitable taps and
switches for varying certain voltage relations.
In synchronous phase balancers there is a very considerable
magnetic action on the field poles and structure by the armature
winding when carrying load, unless the field poles are equipped
with ample cage dampers similar to those required on the fields of
large single-phase generators. If these dampers are of proper
proportions, tlie pulsating eSect of the armature on the field can
be suppressed with comparatively small loss in the dampers.
However, the alternative of such machine, namely, the straight
motor-generator, must also have heavy dampers on its single-
phase element, so this does not change the relative efficiencies
of the two methods.
When power-factor correction is required, as well as phase
balancing, then the size or capacity of the phase balancer will
depend to a certain extent upon the amount of power-factor
*PBase Balancer for Single-Phase Load on Polyphase Systems," by Mr. B. P. W. Alexan-
derson, General Electrical Review, December, 1913.
SINGLE-PHASE FROM POLYPHASE
567
correction. As it may be of interest to know what capacity of
phase balancer is required in, terms of single-phase load, the ap-
proximate curves shown in Fig. 4 have been worked out for dif-
ferent power-factors, showing the capacity (three-phase) re-
quired in phase balancers for each 1,000 k.v.a. single-phase load
taken off. The ordinates represent power-factors of the single-phase
load, while the abscissae show the k.v.a. ratings of the phase
balancers required at various three-phase power-factors. The
phase balancing k.v a. is given in terms of three-phase capacity —
that is, the capacity which the machine would have as a three-
phase generator, with a current rating corresponding to the
largest of the unbalanced currents in its three phases. In other
words, this rating is on the basis of maximum local losses, instead
of averaging, and thus represents the most severe condition.
The capacity of the booster or other apparatus for supplying the
correcting e. m. f . is not included. This can be assumed roughly
as about 15 percent of that of the phase balancer, whether it is a
separate piece, such as a separate booster or transformer, or is
obtained in the balancer windings.
— rafer"^ \m *-iK3B
,va yhaae I aland jg Cap; olty |
\
1350"
PIG. 4— CURVES SHOWING THE BALANCING CAPACITY REQUIRED
(THREE-PHASE) FOR EACH 1 000 K.V.A. OP SINGLE-PHASE LOAD
These curves show that usually there is considerable saving
in capacity of apparatus in the use of a phase balancer, as com-
pared with a straight motor-generator where power-factor cor-
rection is not important. For example, assume a single-phase
load is at 70 percent power-factor, while the corresponding three-
568 ELECTRICAL ENGINEERING PAPERS
phase balanced power is to be held at the same power-factor.
From the table, the approximate capacity of the phase balance is
1,000 k.v.a. Adding IS percent for the booster, gives 1,150 k.v.a.
as the total balancing capacity required. Comparing this with a
straight motor-generator, the driving motor will have a normal
capacity of 700 kw approximately, while the 1,000 kv.a. single-
phase generator would approximately correspond in capacity to a
1,500 k.v.a. three-phase machine — thus requiring a total of 2,200
k.v.a., compared with 1,150 k.va. for the phase balancer. The
latter means, therefore, materially less expensive apparatus — also
more efficient. It may be noted throughout that where there is
no correction of power-factor, the balancer capacity in k.v.a/ will
be equal to the k v.a. of the single-phase load. If, however, in the
above example, 70 percent single-phase power-factor is to be cor-
rected to 90 percent in the three-phase circuit, then the balancer
capacity will be 1,390 k.v.a. Adding 15 percent for the correct-
ing booster gives 1,600 kv.a. against 2,200 k.v.a. for the motor-
generator.
The phase balancer therefore apparently does not correct for
power-factor as advantageously as the straight motor-generator.
Also, where automatic correction of power-factor is desirable,
the motor-generator arrangement is somewhat less complicated.
THE TECHNICAL STORY OF THE FREQUENCIES
FOREWORD — This paper was presented before ^the Washington
Section of the American Institute of Electrical Engineers in
January, 1918. It covers briefly the history of the various
frequencies used in America and the engineering and technical
reasons which have influenced their ultimate choice or rejection.
The author had in mind the preservation of this in more or less
historical form, in order that it should not eventually be entirely
lost. Since the publication of this paper, the author has
received many favorable comments on it, as being the only
reliable source of information on the subject which is now
available. It has been reprinted in its entirety in a number of
technical papers and the material drawn from it has been used
in a number of technical lectures by various engineers and
educators. — (ED . )
IN the early days of the alternating current, there were no well
established tendencies toward any definite frequencies, either
in this country or in Europe. Each manufacturer selected that
frequency which best suited his particular style of generating
apparatus, and the greater the number of manufacturers, the
greater the number of frequencies. But quite early, in America,
there developed definite tendencies toward certain standards.
Later, similar tendencies in Europe operated to bring about a
general adoption of a limited number of definite frequencies.
It is not the purpose of the paper to deal with the history of
any but the American tendencies and developments, as these form
a sufficient story in themselves.
The story of how and why the various commercial fre-
quencies came into use and then iropped out again, in most
cases, is not primarily the story of the frequencies themselves,
but of the various uses to which the alternating current has
been applied. In other words, fundamental changes in the
application of alternating current have led to radical changes in
the frequencies. Some of the applications which have had a
determining factor on the frequency of the supply system are
as follows; incandescent lighting, transformers, transmission
systems, arc lighting, induction motors, synchronous converters,
constructional conditions in rotating machinery, and operating
conditions. A brief consideration of these items individually,
569
570 ELECTRICAL ENGINEERING PAPERS
from the present viewpoint, indicates that while some of them
had, at one time, very considerable influence in determining
frequency conditions, yet, in a number of cases, the original
reasons have disappeared through improvements and refine-
ments, as will be described later.
At various times the following standard frequencies have been
in use in this country, namely, 133H» 125, 83J^, 66%,
60, 50, 40, 30 and 25 cycles per second. These did not appear
chronologically in the order given above, and a few odd fre-
quencies in a few special applications are omitted.
In the following, the various frequencies will be considered
more or less in the order of their development and basic reasons
will be given for their choice, and the writer will endeavor to
show why certain of them have persisted, while others have
dropped out. It will also be shown why the commercial situa-
tion has first tended strongly toward certain frequencies and
afterwards swung toward others.
133 AND 125 CYCLES
In the earliest alternating work, the whole service consisted
of incandescent lighting, and the electric equipment was made
up of small high-speed belted single-phase generators and house-
to-house distributing transformers. As the transformers were
of small capacity and as their design was in a very crude state,
it was believed that a relatively high frequency would best meet
the transformer conditions. A choice of such an odd frequency
as 133j/£ cycles per second, is due to the fact that in those
early days (1886 to 1893) frequencies were usually designated
in terms of alternations per minute. One of the earliest com-
mercial generating units constructed by the Westinghouse
company had a speed of 2000 rev. per min. and had eight poles.
This presented a fairly convenient constructional arrangement
for the surface-wound type of rotating armature, which was the
only one recognized at that time. The speed of 2000 rev. per
min., with eight poles, gave 16,000 alternations per minute, or
133J^ cycles per second according to our present method of
designation. Thus the earliest frequency in commercial use in
this country was fixed, to a certain extent, by constructional
reasons, although the house-to-house transformer problem ap-
parently indicated the need for a relatively high frequency.
The Thomson-Houston company adopted a standard fre-
quency of 15 000 alternations per minute, (125 cycles) instead
STORY OF THE FREQUENCIES 571
of the Westinghouse 16,000, but the writer does not know why
this difference was made. However, the two frequencies were
so close together that practically they could be classified as one.
At this time, it should be borne in mind, there were no real
transmission problems, no alternating-current arc lighting, no
induction motors and the need for uniform rotation of the genera-
tors was not recognized. The induction motor, in its earliest
stages, came in 1888 and considerable work was done on it in
1889 and 1890, but it required polyphase supply circuits and com-
paratively low frequency and, therefore, it had no connection
whatever with the then standard single-phase, 133f and 125
cycle systems. The synchronous converter was also unheard
of (one might say almost undreamed of) at that time.
60 CYCLES
In 1889 or 1890 it was beginning to be recognized in this
country that some lower frequency than 125 and 133 1 cycles
would be desirable. Also about this time direct-coupled and
engine-type alternators were being considered in Europe and it
was felt that such construction would eventually coftie into use
in America. It was appreciated that in such case^ 133f cycles
would present very considerable difficulties compared with
some much lower frequency, due to the large number of poles
which would be required. For instance, an alternator direct
driven by an 80-rev. per min. engine would require 200 poles
to give the required frequency and such construction was looked
upon as being practically prohibitive. About this time Mr.
L. B. Stillwell, then with the Westinghouse company, made a
very careful study of this matter of a new frequency, in connec-
tion with the possibilities of engine type generators, and after
analyzing a number of cases, it appeared that 7200 alternations
per minute (60 cycles per second), was about as high as would
be desirable for the various engine speeds then in sight. Trans-
former constructions and arc lighting were also consideredln
this analysis. While it was deemed that a. somewhat higher
frequency might be better for transformers, yet a lower fre-
quency than 60 cycles was considered as possibly better for
engine type generators. A compromise between all the various
conditions eventually led to 60 cycles as the best frequency.
However, while ^this frequency originated about 1890, it did not
come into use suddenly, for it was impossible to introduce such
a radical change in a brief time. Moreover, the direct-coupled
572 ELECTRICAL ENGINEERING PAPERS
or engine-type generator was slow in coming into general use and,
therefore, there was not the necessity for the introduction of
this low frequency in many of the equipments sold from 1890
to 1892. However, by 1893, 60 cycles became pretty firmly
established and was sharing the business with the 133i -cycle
systems. It should be borne in mind that, at this time, the
adoption of this frequency was not considered as a direct means
for bringing forward the polyphase induction motor, for the
earlier 60-fcycle systems, like the 125- and 133^-cycle, were all
single-phase Also, it was then thought that the polyphase
motor would possibly require a still lower frequency and, more-
over, the polyphase system was looked upon as in a class by
itself, suitable only for induction motor work. At that time
the introduction of polyphase generators for general service was
not contemplated. This followed about two or three years later.
In 1890 the Westinghouse company, which had been de-
veloping the Tesla polyphase motor laid aside the work, largely
on account of there being no suitable general supply systems for
this type of motor. The problem was again revived in 1892,
in an experimental way, with a view to bringing out induction
motor which might be applied on standard frequencies such as
could be used in commercial supply circuits for lighting and other
purposes. It should be understood that at this time such cir-
cuits w^re not in existence but were being contemplated. In
1893, after the polyphase motor had been further developed up
to the point where it showed great commercial possibilities, the
best means for getting it on the market were carefully considered.
It was decided that the best way to promote the induction motor
business was to create a demand for it on commercial alternating-
current systems. This meant that, in the first place, such sys-
tems must be created. Therefore, it was decided to undertake
to fill the country with polyphase generating systems, which were
primarily to be used for the usual lighting service It was
thought that, with such systems available, the time would soon
come when there would be a call for induction motors. In this
way experience would be obtained in the construction and opera-
tion of polyphase generators and the operating public would not
be unduly handicapped in the use of such generators, compared
with the older single-phase types.
An early example of this new practise ^as in the 2000-kw.
polyphase generating units used for lighting the Chicago World's
Pair in 1893. Here the single-phase type still persisted, as each
STORY OF THE FREQUENCIES 573
generator unit was made tip of two similar frames placed side by
side, but with their single phase armatures dsplaced one-half
pole pitch from each other so that the combined machine de-
livered two single-phase currents displaced 90 degrees from each
other. It was considered that each circuit could be regulated
independently for lighting service, and polyphase motors could
be operated from the two circuits. These generators (at that
time the largest in this country) were designed in 1892 and were
of 60 cycles. These, therefore, indicate the tendency at that time
toward lower frequency and /polyphase generation, although
commercial polyphase motors were not yet on the market.
25 CYCLES
At the same time that 60 cycles was selected as a new standard
it was refcognized that at some future time there would be a
place for some much lower frequency, but it was not until two
years later that this began to narrow down to any particular
frequency. In 1892 the first Niagara electrification, after several
years consideration by eminent authorities, had centered on
polyphase alternating current as the most desirable system. The
engineers of the promoting company had also worked out what
they considered the most suitable construction of machine. This
involved 5000-h. p. units at 250 revolutions per minute. Prof.
George Forbes, one of the engineers of the company had furnished
the electrical designs for a machine with an external rotating
field and an internal stationary armature. His design used eight
poles, thus giving 2000 alterations per minute, or 16f cycles per
second. Quite independently of this, the Westinghouse com-
pany, in 1892, had been working on the development of synchron-
ous converters, using belted 550-volt d-c. generators with two-
phase collector rings -added. The tests on these machines had
shown the practicability of such conversion and had even proved
at this early date, that the converter copper losses were much
lower than in the corresponding d-c. generators. Thus it is an
interesting fact that the first evidence of this important principle
was obtained from a shop test rather than by calculation. The
writer, from an analysis of the tests, which were made under his
immediate direction, concluded that the armature copper losses
must be considerably lower than in the same machine used as a
d-c. generator, He also brought the matter to the attention
of Mr. R* D, Mershon, -then with the Westinghouse company,
and the problem was then worked; gut mathematically by him
574 ELECTRICAL ENGINEERING PAPERS
and the writer, in two quite different ways, but with similar
results, showing that the converter did have actually very much
reduced copper losses.
As a result of this work of the Westinghouse company on the
synchronous converter, it was decided that, to make such ma-
chines practicable, some suitable relatively low frequency was
required. This appeared to be about 30 cycles. About this
time the construction of the Niagara generators was taken up
with the Westinghouse company to see whether it would con-
struct these machines according to the designs submitted by the
promoting company's engineers. These designs were gone over
as carefully as the knowledge of such apparatus, at that time,
permitted, and many apparent defects and difficulties were
pointed out. The Westinghouse company then proposed, as a
substitute, a 16-pole, 250-rev. per min. machine (the speed being
definitely fixed at 250 rev. per xnin.). This gave 33f cycles or as
near to the Westinghouse proposed 30 cycle system, as it was
possible to get. Then many arguments were brought forward,
pro and con, for the two machines and frequencies. Prof.
Forbes1 preference for l&f cycles was based partly on the pos-
sibilities it presented for the construction and operation of com-
mutator type motors, just as with direct current circuits. The
Westinghouse contention was that this frequency was too low
for any kind of service except possibly commutator type ma-
chines. Tests were made with incandescent lights and it was
found that at 33| cycles there was little or no winking of light,
while at 16f cycles, the winking was extremely bad. Tables
were also made up, showing the limited number of speed com-
binations at 16f cycles for induction motors, in case such should
come into use. This showed how superior the 33£ cycles would
be as regards such apparatus. It was also brought cut that
synchronous converters, when such became commercial, would
be much better adapted for the higher frequency, as the choice
of speeds would be much greater. Prom the present viewpoint
the arguments appear to have been much in favor of the West-
inghouse side of the case.
As a consequence of all this discussion the suggestion was
advanced by some one, that a 12 pole, 250-revolution machine,
(that is, 3000 alternations, or 25 cycles), might meet sufficiently
the good qualities of both of the proposed frequencies and would
thus be a good compromise. In consequence a 12-pole, 25-cycle
machine was worked up by the Westinghouse company and
STORY OF THE FREQUENCIES 575
eventually this frequency was adopted for the Niagara genera-
tors. Afterwards, while these generators were being constructed
it was brought out pretty strongly that the great advantage of
this frequency would be in connection with synchronous con-
verter operation, but that it was also extremely well adapted for
slow-speed engine type generators, which were then coming into
use. In consequence of the prominence given this frequency it
was soon adopted as a standard low frequency, especially in those
plants where synchronous converters were expected to form a
prominent part of the system.
However, while 60 and 25 cycles came into use; as described
above, it must be recognized that they had competitors. For
instance, 66f cycles (8000 alternations or one-half of 16,000)
was used to a considerable extent by one of the manufacturing
companies. Also 50 cycles came* into use in certain plants and,
to a certain extent, is still retained, but has become the standard
high frequency of Europe. Instead of 25 cycles, the Westing-
house company advocated 30 cycles for some of its plants, largely
because with the 25 per cent higher speeds permissible with such
frequencies, the capacities of induction motors could be cor-
respondingly increased and also incandescent lighting was more
satisfactory. However, it was soon recognized that the 66f and
30 cycle variations from the two leading frequencies of 60 and 25
cycles were hardly worth while, and they were gradually dropped,
except in plants already installed. A brief attempt was made
at a somewhat later period to place '40 cycles upon the market
as a substitute for both 25 and 60 cycles. This was done under
the impression that 40 cycles would give a universal system for
arc and incandescent lighting, transmission, induction motors,
synchronous converters and about everything else. This fre-
quency possessed many merits and it was thought, at One time,
that it might win out, but apparently the other two frequencies
were too well established, and the 40 cycle system eventually
lost ground.
The problem of the frequencies finally narrowed down to the
two standards, and these two were accepted because it was
thought that they covered such entirely different fields of ser-
vice that neither of them could ever expect to cover the whole.
In other words, two standards were required to cover the whole
range of service. It was recognized that 25 cycles would not
take care of alternating-current arc lighting and that it was
questionable for incandescent lighting in general. In other tfays,
576 ELECTRICAL ENGINEERING PAPERS
such as suitability for engine-type construction, application to
induction motors and synchronous converters and transmission
of power to long distances, it tnet the needs of an ideal system,
as then understood. Also, in parallel operation of engine-type
alternators, which was one of the serious problems of those days,
the 25-cycle machines were unquestionably superior to the 60-
cycle ones, due to the lesser displacement of the e. m. f. waves
with respect to each other with a given angular variation in the
engine speeds. However, although the 25-cycle system pre-
sented so many advantages, it could not take care of the lighting
business, and, therefore, could not entirely dominate the situa-
tion.
As regards 60 cycles, it was felt that this could handle the direct
lighting situation in a very satisfactory manner and was pos-
sibly better suited for transformers than 25 cycles, although
there were differences of opinion in this matter, especially when
it came to the larger capacities. It was reasonably well adapted
for induction motors in general, but not for very low speeds. In
matters of transmission and in the operation of synchronous
converters it was thought to be vitally defective.
From the above consideration it would appear that the 25-
cycle systems presented the stronger showing as a whole and,
therefore, there was a decided tendency toward this frequency,
except in those cases where lighting directly from the alternating-
current system was considered of prime importance. In those
systems, such as many of the Edison companies, where low-
voltage three-wire direct current was used from synchronous
converters, the tendency was almost solidly toward the 25-cycle
system. In those days the central station, which had gotten
itself committed to the 60-cycle system so deeply that it could
^not change, was looked upon with commiseration. Sixty-cycle
plants were looked upon, to a certain extent, as a necessary evil.
In fact, so strong was the tendency toward 25 cycles that in many
cases 25-cycle plants were installed for industrial purposes, where
60 cycles would have been better. The 25-cycle synchronous
converter development advanced by leaps and bounds and the
machines were so good in their operation that it was believed
that 60-cycle converters could never be really competitive with
them.
On the other hand, in those large plants, which were so "un-
fortunate" as to have 60 cycles installed, many apparent make-
shifts were adopted to meet the various service requirements.
STORY OF THE FREQUENCIES 577
In arc lighting, incandescent lighting, transformers and motors
there was no need for makeshifts. However, in conversion to
direct current, one of the greatest difficulties appeared. There
were many who advocated motor-generators for this purpose,
largely because the 60-cycle converter was thought to be im-
practicable, in spite of the fact that the manufacturing companies
were putting them on the market. The 60-cycle converter at
that time bore a bad name. It is now recognized that many of
the faults of the early 60-cycle synchronous converter operation
were not in the converters themselves, but were, to a consider-
able extent, in the associated apparatus. Low-speed engine-
type, 60-£ycle generators were not always adapted for operation
of synchronous converters. In fact, in numerous cases such
generators would not operate in an entirely satisfactory manner
in parallel with each other, and yet when it was attempted to
operate synchronous converters from these same generators the
unsatisfactory results were not blamed upon the generating
system but upon defects of the converters themselves. Unfor-
tunately, defects in the generating and transmission systems
usually appeared in the converters as sparking and flashing,
and such troubles naturally would be credited to defects in the
construction of the converters themselves. In fact, in those
days, 60-cycle converters were expected to do things which now
are considered as absurd. For instance, in one case in the writ-
er's knowledge a 60-cycle synchronous converter was criti-
cized as being a very badly designed piece of apparatus, due to
serious flashing at times. Investigation developed that this
converter was expected to operate on either one of two indepen-
dent 60-cycle systems with no rigid frequency relation to each
other. The converter in service was thrown from one system to
the other indiscriminately, and sometimes it flashed in the trans-
fer and sometimes it did not. The machine was considered to
be "no good" because it would not always stand such switching.
At one time the writer stood almost alone in his belief that
the 60-cycle synchronous converter presented commercial pos-
sibilities sufficient to make it a- strong future contender with
the 25-cycle machine, provided proper supply conditions were
furnished and certain difficulties in the proportions of the con-
verter itself were overcome. One basis for his contention was
that in some of the 60-cycle plants, where the generator rotation
was quite uniform, the converters were evidently much superior
in their operation to other plants, using slow-speed engine-type
578 ELECTRICAL ENGINEERING PAPERS
generators with considerable periodic variations. In such plants
the hunting tendency of the converters was very greatly re-
duced, with consequent improvement in sparking and general
operation. It was early recognized that hunting was a very
harmful condition, both in 60- and 25-cycle synchronous con-
verters, but whereas it was a relatively rare condition in 25-cycle
plants it was much more common with 60 cycles. However,
the operating public was not particularly concerned whether
the trouble was in the generating plant or in. the converters
themselves, as long as such trouble existed and was not overcome.
Very early in the synchronous converter development it was
found that hunting would produce sparking or flashing at the
commutators of the converters. However, even in those plants
where there was no hunting apparent, there was difficulty at
times due to flashing, especially with sudden change of load,-
which resulted in temporary increase in the d-c. voltage. This
was a difficulty which was inherent in the converter itself and
could not be blamed entirely upon the generating or transmitting
conditions, for 25-cycle machines were practically free from
this trouble under similar conditions of operation. Investiga-
tion developed the fact that this flashing trouble was due Jargely
to unduly high value of the maximum volts between commutator
bars. This difficulty was recognized long before it was over-
come, simply because certain physical limitations in construction
had to be removed. There were two ways in which the maximum
volts per bar could be reduced, namely, by increasing the number
of commutator bars per pole and by decreasing the ratio of the
maximum volts to the average volts per bar, that is, by increas-
ing the ratio of the pole width to the pole pitch, but both of
these involved structural limitations in the allowable peripheral
-speeds of the commutator and the armature core. Here is
where a little elementary mathematics comes in. The per-
ipheral speed of the commutator is directly proportional to the
distance between adjacent neutral points on the commutator,
and the frequency. Therefore, with, a given frequency the
distance between the adjacent neutral points is directly propor*
tional to -the peripheral speed. Thus, a commutator speed of
4500 ft. per min. which was then considered an upper limit,
the distance between adjacent neutral points on a 60-cycle
converter is only 7$ in. (19 cm.) This distance is thus fixed
mathematically and is independent of the number of poles or
revolutions per minute, or anything else, except the peripheral
STORY OF THE FREQUENCIES 579
speed and the frequency. With this distance of 1\ in., (19 cm ),
about the only choice in commutator bars per pole was 36,
giving an average of 16f volts per bar on a 600-volt machine,
and nearly 20 volts per bar with momentary increase of voltage
to 700, which is not uncommon in railway service.
However, it is not this average voltage which fixes the flashing
conditions, but it is the maximum voltage between bars, and
this is dependent upon the average voltage and upon the ratio
of the pole width to the pole pitch. Here is where one of the
serious difficulties came in. As mentioned above the pole pitch
is directly dependent upon the peripheral speed of the armature
core and the frequency. Therefore, in a 60-cycle machine, if
the peripheral speed is fixed, the pole pitch is at once fixed.
For example, with an armature peripheral speed of 7200 ft. per
min., which was considered high at that time, the pole pitch
becomes 12 in (30,48 cm.) , regardless of any other considerations,
and here was where a most serious difficulty was encountered.
If a sufficiently wide neutral zone for commutation was allowed
the interpolar space became so wide that there was not enough
left for a good pole width. For instance, if the interpolar space
was made 6 in. (15 24 cm.) wide, in order to give a sufficiently
wide commutating zone to prevent sparking or flashing, due to
fringing of the main field, then this left only 6 in. for the pole
face. With this relatively narrow pole face the ratio of the
maximum volts to the average volts was so high that with the
36 commutator bars per pole the machine was sensitive to arcing
between commutator bars thus resulting in flashing. By widen-
ing the pole face this difficulty would be lessened or overcome
but with the fixed pole pitch of 12 in. (30.48 cm.) the neutral
zone would be so narrowed as to make the machine sensitive to
sparking and flashing at the brushes. Thus, no matter which
way we turned we encountered trouble. Obviously there were
two, directions of improvement, namely, by increasing the
number of commutator bars, thus reducing the average voltage,
and by increasing the pole pitch, thus allowing relatively wider
poles with a given interpolar space. These two conditions look
simple and easy, but it took several years of experience to
attain them. When we have reached apparent physical limita-
tions in a given construction, especially when such limitations
are based upon long experience, we have to feel our way
quite slowly toward higher limitations. For instance, in the
case of the 60-cy"cte converters we could ndt boldly jump our
580 ELECTRICAL ENGINEERING PAPERS
peripheral speeds 20 to 25 per cent higher and simply assume
that everything was all right. We first had to build apparatus
and try it out for a year or so. Troubles, due to peripheral
speed, do not always become apparent at once, and thus time
tests are necessary Therefore, while the peripheral speeds of
the 60-cycle synchronous converters were actually increased 20
to 25 per cent practically in one jump, yet it took two or three
years of experimentation and endurance tests before the manu-
facturers felt sure enough to adopt the higher speeds on a broad
commercial scale. Thus, while the change from the older more
sensitive type of 60-cycle converter to the later type occurred
commercially within a comparatively short period yet the actual
development covered a much longer period.
Let us see now what an increase of 25 per cent in the peripheral
speeds actually meant. As regards the commutator, the number
of bars could be increased 25 per cent, that is, from 36 to 45 per
pole, which was comparable with ordinary d-c, generator practise.
In the second place, an increase of 25 per cent in the peripheral
speed of the armature core meant a 15-in. (38.1-cm.) pole pitch,
where 12 in. (30.8 cm.) was used before. Assuming, as before,
a 6-in. (15.24-cm.) interpolar space, then the pole face itself
became 9 in. (22,8 cm,) in width instead of 6 in. (15.24 cm.)
or an improvement of 50 per cent, In fact, this latter improve-
ment was so great that some manufacturers did not consider it
necessary to increase the number of commutator bars, although
in the Westinghouse machines both steps were made.
The above improvements so modified the 60-cycle converter
that it began to approach the 25-cycle machine in its general
characteristics. It was still quite expensive compared with the
25-cycle, due to the large number of poles, and its efficiency was
considerably lower than its 25-cycle competitor, on account of
high iron and windage losses. However, due to the need for
such a machine it was gradually making headway, in spite of
handicaps in cost and efficiency.
Almost coincident with the initiation of the above improve-
ments in the 60-cycle converter, came another factor which has
had much to do with the success of this type of machine. This
was the advent of the turbo-generator for general service. As
stated before, one of the handicaps of the 60-cycle converter was
in the non-uniform rotation of the engine type generators which
were common in the period from 1897 to about 1903 or 1904.
But, about this latter date, the turbo-generator was making
STORY OF THE FREQUENCIES 5S1
considerable inroads on the engine-type field and within a rela-
tively short period it so superseded the former type of unit, that
it was recognized as the coming standard for large alternating
power service. With the turbo-generator came uniform rotation
and this at once removed one of the operating difficulties of the
60-cycle converters. However, in the early days of the turbo-
generator, 25 cycles still was in the lead and many of the earlier
generators were made for this frequency, especially in the larger
units. But it was not long before it was recognized that 60
cycles presented considerable advantage in turbo-generator
design due to the higher permissible speeds. In the earlier days
of turbo-generator work, this was not recognized to any extent,
as the speeds of all units were so low that the effect of any speed
limitations was not yet encountered. For instance, a 1500-kw ,
60-cycle turbo-generator would be made with six poles for 1200
revolutions, while a corresponding 25 cycle unit would be made
with two poles for 1500 revolutions. This slightly higher speed
at 25 cycles about counterbalanced the difficulties of the two-
pole construction compared with the six-pole. However, before
long, more experience enabled the six pole, 60-cycle machine to
be replaced at 1800 revolutions, and a little later by two poles at
3600 revolutions. This, of course, turned the scales very much
in the other directioA. In larger units, however, the advantage
still appeared to be in favor of 25 cycles, but in the course of
development, 1500 revolutions was adopted quite generally for
25-cycle work, and this was the limiting speed, as such machines
had only two poles, or the smallest number possible with ordinary
constructions. On the other hand, for 60 cycles, 1800 revolutions
was adopted quite generally for units up to almost the extreme
capacities that had been considered, consequently the con-
structional conditions in the large machines swung in favor
of 60 cycles. Therefore, with the coming of the steam turbine
and the development of high-speed turbo-generator units, the
tendency has teen strongly toward 60 cycles. This, with the
greater perfection of the 60-cycle converter, had much to do with
directing the practise away from the 25 cycles.
'However, there were other conditions which tended strongly
toward 60 cycles. In the early development of the induction
motor, the 25-cycle machines were considerably better than the
60-cycle and possibly little or.ao more expensive. However,
as refinements in design and practise came in, certain important
advantages of the 60-cycle began to crop out. For instance,
582 ELECTRICAL ENGINEERING PAPERS
with 25 cycles there is but little choice in speed, for small and
moderate size motors. At this frequency a four-pole motor has
a synchronous speed of only 750. The only higher speed per-
missible is 1500 revolutions with two poles, and it so happens
that in induction motors the two-pole construction is not mate-
rially cheaper than the four pole, consequently the principal ad-
vantage in going to 1500 revolutions was only in getting a higher
speed where such was necessary for other reasons than first cost.
However, in 60 cycles the case is quite different, where a four-
pole machine can have a speed of 1800 revolutions, synchronous,
a six pole 1200, an eight pole 900 and a ten pole 720 revolutions.
In other words, there are four suitable speed combinations where
a 25 cycle motor had only one. Moreover, with the advance in
design it developed that these higher speed 60-cycle motors could
be made with nearly, as good performances as with the 25-cycle
motors of same capacity, and at somewhat less cost. However,
leaving out the question of cost, the wider choice of speeds alone
would be enough to give the 60-cycle motor a pronounced prefer-
ence for general service.
However, there is one exception to the above. Where very
low-speed motors are required, such as 100 rev. per rain., the 60-
cycle induction motor is at a considerable disadvantage com-
pared with 25 cycles, or this has been the case in the past. It
is partly for this reason that the steel mill industry, through its
electrical engineers, adopted 25 cycles as standard some ten or
fifteen years ago. At that time, it was considered that in mill
work, in general, there would be need for very low-speed motors
in very many cases. However, due to first cost, as well as other
things, there has been a tendency toward much higher speeds in
steel mill work, through the use of gears and otherwise, so that
part of this argument has been lost. However, there still remain
certain classes of work where direct connected very low-speed
induction motors are desirable and where 25 cycles would ap-
pear to have a distinct advantage.
In view of the above considerations, steel mill work has hereto-
fore gone very largely toward 25 cycles, particularly where the
mills installed their own power plants. However, in recent
years there has been a pronounced tendency toward purchase of
power, by steel mills, from central stations, and the previously
described tendency of central stations toward 60 cycles has
forced the situation somewhat in the steel mills, particularly in
those cases where the central power supply company can furnish
STORY OF THE FREQUENCIES 583
power at more reasonable rates than the steel mill can produce in
its own plant. This, therefore, has meant a tendency toward 60
cycles in steel mill work, even with the handicap of inferior low-
speed induction motors. But, on the other hand, remedies have
been brought forward even for this condition. The great diffi-
culty in the construction of low-speed, 60-cycle induction motors
is in the very large size and cost if constructed for normal power
factors, or the very low power factor and poor performance if
constructed of dimensions and costs comparable with 25 cycles.
In the latter case the extra cost is not entirely eliminated because
a low power factor of the primary input implies additional gener-
ating capacity, or some means for correcting power factor on the
primary system. However, in some cases it is entirely practi-
cable to correct the power factor in the motors themselves by the
use of so called "phase advancers" of either the Leblanc or the
Kapp type. Such phase advancers are machines connected in
the secondary circuits of induction motors and so arranged as to
furnish the necessary magnetizing current to the rotor or second-
ary instead of to the primary In this way the primary current
to the motor will represent largely energy and the power factors
can be made equal to, or even much better than in, the corre-
sponding 25-cycle motor; or, in some cases, the conditions may
be carried even further so that the motor is purposely designed
with a relatively poor power factor, in order to further reduce the
size and cost, and the phase advancers are made correspondingly
larger. In those cases where the cost of the phase advancer is
relatively small compared with the main motor, there may be a
considerable saving in the cost of the main motor and then add-
ing part of the saving to the cost of the phase advancer.
One difficulty in the use of phase advancers is found in the
variable speeds required in some kinds of mill work. In those
cases where flywheels driven by the main motors are desirable
to take up violent fluctuations in load, it is necessary to have
considerable variations in the speed of the induction motor, in
order to bring the stored energy of the flywheel into play.
T/nfortunately this variable speed in the induction motor is one
of the most difficult conditions to take care of with a phase
advancer, so that here is a condition where the 60-cycle motor
is at a decided disadvantage.
Thus it may be seen from the above that ev^n in the steel
mill field, where the induction motor lias the most extreme appli-
cations, there is quite a strong pendency towax<J 60 cycles, due
to the purchase of power from central sttpply systems.
584 ELECTRICAL ENGINEERING PAPERS
There remains one more important element which has had
something to do with the tendency toward 60 cycles, namely,
the transmission problem. In the earlier days of transmission
of alternating current, 25 cycles was considered very superior
to 60 cycles due to the better inherent voltage regulation con-
ditions. At one time, it was thought that 60 cycles had a -very
limited field for transmission work. However, a number of
power companies in the far west had installed 60-cycle plants,
principally for local service and with the growth of these plants
came the necessity for increased distance of transmission through
^ development of water powers. At first it was thought they were
badly handicapped by the frequency, but gradually the apparent
disadvantages of their systems were overcome and the distances
of transmission were extended until it became apparent that
they could accomplish practically the samfe results as with 25
cycles. Part of this result has been obtained by the use of
regulating synchronous condensers. It is a curious fact that
the possibility of synchronous motors used as condensers for
correction of disturbances on transmission systems, has been
known for about 25 years, but it is only within quite recent years-
that they have come into general use as a solution of the trans-
mission problem, and largely in connection with 60-cycle plants.
In 1893 the writer applied for a patent on the use of synchronous
motors as condensers for controlling the voltage at a^iy point
on a transmission system by means of leading or lagging currents
in the condenser itself. A broad patent was obtained, but there
was no particular use made of it until it had practically expired.
Another improvement came along which still further helped
to advance 60 cycles to its present position, namely, the use of
commutating poles in synchronous converters. The principal
value of commutating poles in the 60-cycle converters, has not
been so much in an improvement in commutation over the older
types of machines, as in allowing a very considerable reduction
in the number of poles with corresponding increase in speed,
resulting in reduction in dimensions. As a direct result of this
increase in speed the efficiencies of the converters have be&n
increased. If, for instance, the speed of a given 60-cycle con-
verter can be doubled by cutting its number of poles to one-half,
while keeping the same pole pitch and the same limiting per-
ipheral speed, then obviously the amount of iron in the armature
core is practically halved and, at the same magnetic densities
the iron loss is also practically halved. Also with the same
STORY OF THE FREQUENCIES 585
peripheral speed and' half diameter of armature the windage
losses can be decreased materially. Thus the two principal
losses in the older converters have been very much reduced.
There have also been reductions in the total watts tor field
excitation, and in other parts, so that, as a whole, the efficiency
for a given capacity 60-cycle converter has been brought up quite
close to that of the corresponding 25-cycle machine, even when
the latter is equipped with commutating poles. This gain of
the higher frequency compared with the lower is due to the
fact that the lower-frequency machine was much more handi-
capped in its possibilities of speed increase, and furthermore,
the iron losses and windage represented a much smaller propor-
tion of the total losses in the low-frequency machine. This
improvement in the efficiency of the 60-cycle converter together
with the lower losses in the 60-cycle transformer as compared
with the 25-cycle, has brought the 60-cycle equipment almost
up to the 25-cycle, so that the difference at present is not of
controlling importance. This development has given further
impetus toward the acceptance of 60 cycles as a general system.
Formerly a serious competitor with the 60 cycle converter
was the 60-cycle motor-generator. This was installed in many
cases because it was considered more reliable and more flexible
in operation than the synchronous converter. Both of these
claims were true to a certain extent. However, with improve-*
ments in the synchronous coverter the difference in reliability
practically disappeared, but there remained the difference in
flexibility. In the motor-generator set, the d-c. voltage could
be varied over quite a wide range, while in the older 60-cycle
rotaries the d-c. voltage held a rigid relation td the alternating
supply voltage. However, with the development and perfection
of the synchronous booster type of converter, flexibility in
voltage was obtained with relatively small increase in cost and
minor loss in economy. This has been the last big step in putting
the 60-cycle converter at the front as a conversion apparatus,
so that today it stands as the cheapest and most economical
method of converting alternating current to direct current,
Moreover, while the 25-cycle synchronous converter has appar-
ently reached about its upper limit in speed, there are still
possibilities left for the 60-cycle converter.
In line with the above it is of interest to note that for units of
1000 kw, and less, the 60-cycle converter has nearly driven the
25-cycle out of business from the manufacturing standpoint.
586 ELECTRICAL ENGINEERING PAPERS
For the very large size converters, 25 cycles still has the call,
but largely in connection with many of the railway and three-
wire systems, which have been installed for many years; that is,
the growth of this business is in connection with existing genera-
ting systems. However, the 60-cycle converter, in large capacity
units, is gaining ground rapidly and it is of interest to note that
the largest converters yet built, namely, 5800 kw., are of the
60-cycle type.
One most interesting point may be brought out in connection
with the above described "battle of the frequencies", namely,
it was fought out in the operating field, and between conditions
of service, and not between the manufacturing companies.
This is a very good example of how such matters should be
handled. Here the engineers of the manufacturing companies
were expending their efforts to get all possible out of both
frequencies, and consequently development proceeded apace.
When 60-cycle frequency seemed to be overshadowed by its
25-cycle competitor, the engineers took a lesson from the latter
and proceeded to overcome the shortcomings of the former.
It was no innate preference of the designing engineers that has
brought the higher frequency to the fore ; it was the recognition
that it had greater merits as a general system, if its weak points
could be sufficiently strengthened; and, therefore, the engineers
turned their best efforts toward accomplishing this result.
It must not be assumed, for a moment even, that because 60
cycles appears to be the future frequency in this country, that
25 cycles was a mistake. Decidedly it was not. In reality it
formed a most important step toward the present high develop-
ment of the electric industry Many things we are now ac-
complishing with 60 cycles would possibly never have been
brought to present perfection, if the success of the corresponding
25-cycle apparatus had not pointed the way. The success of
the 25-cycle converter, and the high standard of operation at-
tained, gave ground for belief that practically equal results were
obtainable with 60 cycles. Therefore, the 25-cycle frequency
served a vast purpose in electrical development; it was a high
class pacemaker, and it isn't entirely out-distanced yet.
There has been considerable speculation as to what two stand-
ard frequencies would have met the needs of the service in the
best manner, and would have resulted in the greatest develop-
ment in the end. It has been claimed by some, that 50 and 25
cycles would have been better than 60 and 25. In the earlier
STORY OF THE FREQUENCIES 587
days possibly the former would have been better, but as a result
both standards might ha\te persisted longer. In any case, the
general advantages would have been small. In one class of ma-
chines, namely, frequency changers, consisting of two alternators
coupled together, the 25-50 combination would certainly have
been advantageous.
Again it has been questioned whether 30 and 60 cycles would
not have been a better choice. This was the original Westing-
house choice of frequencies, but not on account of frequency
changers. As stated before, it was felt that 30 cycles could do
about all that 25 cycles could, and would give an advantage of
25 per cent higher speed in motors and converters, with corre-
spondingly higher capacities. Also for direct coupled alterna-
tors, the two-to-one ratio of frequencies would fit in nicely with
engine speeds, in most cases. Possibly, from the present view-
point, the choice of thirty cycles, would have longer retained the
double standard.
Something further may be said regarding the 40-cycle system*
brought out by the General Electric Company. This contained
many very good features, for the time it was brought out. It
was then believed that if the 60 cycle frequency was retained,
the double standard was necessary. The 40-cycle system was
an attempt to eliminate this double standard. It apparently
furnished a better solution than 60 cycles then promised for the
synchronous converter problem, and was a fair compromise in
about everything else. But it came too late, for the 25-cycle
system was too firmly entrenched, and for further development,
the designing engineers preferred to expend their energies in
seeing what could be accomplished with 60 cycles, as this seemed
to present greater possibilities than either 25 or 40, if it could be
sufficiently perfected. Thus the 40-cycle system probably
missed success due to being just a little too late.
As to 50 cycles, it was stated that this is still in use to a limited
extent. Most of the 50-cycle plants in this country are in Cali-
fornia. Such plants were started during the nebulous period of
the frequencies, and have persisted, to a certain extent, partly
because certain 60-cycle apparatus could be easily modified to
meet the 50-cycle requirements. Also, as 50 cycles is the
standard in many foreign countries to which this country exports
equipment, the use of 50 cycles in some home plants has not been
unduly burdensome from the manufacturers' standpoint.
In addition to the preceding, there have been certain classes
588 ELECTRICAL ENGINEERING PAPERS
of electric service which have depended upon frequency, but
which have not been a determining factor in fixing any par*
ticular frequency, Among these may be considered commutat-
ing types of a-c. apparatus. The first a-c. commutating mo-
tors of any importance, which appeared, were, of course, the 25-
cycle, single-phase railway motors. These as a rule have
operated from their own generating plants, or from other plants
through frequency-converting machinery. One exception in the
railway work may be noted in the use of 15 cycles on the Visalia
plant in California, There is a pretty well defined opinion among
certain engineers experienced in such apparatus that some low
frequency, such as 15 cycles, would present very considerable
advantages in the use of single-phase railway motors in very
heavy service, such as on some of the western mountain roads.
Here the problem is to get the largest possible motor capacity
.on a given locomotive, and the main advantage of the lower fre-
quency would be in allowing a very materially higher capacity
within a given space. This does not imply reduced weight or
cost compared with the 25 cycles, but simply means greater motor
capacity. With the modern, more highly developed, single-
phase types of railway motors, it would appear that there may be
very considerable possibilities in 15 cycles.
Outside of the railway field, there has been more recently a
development of various types of a-c. commutating apparatus,
principally in connection with heavy steel mill electrification
work. Such apparatus has been largely in the form of three
phase commutating machines and these have been used prin-
cipally in connection with speed coritrol of large induction mo-
tors. As these regulating machines are usually connected in the
secondary circuits of induction motors, the frequency supplied is
represented by the slip frequency. Consequently where the slip
frequency never rises to a large percentage of that of the primary
system, such commutating motors ate applicable without undue
difficulties. Such motors, presumably are better adapted for
25-cycle mill equipments than for 60-cyde, but due to the ten-
dency, already described, for steel mills to go to 60 cycles on pur-
chased power, it has been necessary to build these three-phase
commutating motors for the regulation of 60-cycle main motors,
in many cases.
There is still another class of service, which has come in re-
cently, where the choice of frequency is of much importance,
but where there is no great necessity for adhering to any standard.
STORY OF THE FREQUENCIES 589
namely, in heavy ship propulsion by electric motors. As each
ship equipment is a complete system in itself, and as it cannot tie
up with other systems, there is not any controlling need for main-
taining any definite frequency or voltage. Except in similar
vessels, there is little chance for duplication in parts, as the
various equipments vary so much in size and capacity. In conse-
quence it has been found advisable, at least up to the present
time, to design each propulsion equipment for that frequency
which best suits the generator and motor speeds, taking into ac-
count the various operating conditions and limitations, such as
the different running speeds, steaming radius, etc. In conse-
quence, different maufacturers bidding on such equipments
may specify different frequencies, depending upon the construc-
tional features of their particular types of apparatus. At the
present time with the relatively small amount of experience ob-
tained with the electrical propulsion of ships, it looks as if it
would be a considerable handicap to attempt to adopt some
standard frequency for all service. Later, with wide experience,
it may be possible to adopt some compromise frequency, which
will not unduly handicap any of the service.
CONCLUSION
It has been the writer's intention to show that, as a rule, the
choice of frequency has been a matter of most serious considera-
tion, based upon service conditions at the time. Moreover, in
view of the wide range of conditions encountered, it is surprising
how few frequencies have been seriously considered in this coun-
try. Occasion has arisen, times without number, where an
obvious solution of a given problem would lie in modification
of the frequency to allow the use of apparatus and equipment
already designed, but the engineers of the manufacturing or-
gahization have steadily held out against such policy, regardless-
of the apparent need of the moment. The swing of the pendulum
from 60 cycles to 25 cycles and back, has covered a period jof
many years and, therefore, cannot be considered as a fad of the
moment, but is the result of well defined tendencies, backed by
the best engineering experience available. As a rule no manu-
facturer has made any particular frequency his "pet," but all
have worked to develop each system to its utmost.
THE DEVELOPMENT OF THE ALTERNATING-
CURRENT GENERATOR IN AMERICA
FOREWORD — The following article, which first appeared in the
Electric Journal, contains a fairly complete brief history of the
evolution of the alternating-current generator in so far as the
Company, with which the writer is connected, is concerned.
Reference is made incidentally to the work of other manufactur-
ing companies, but this is not very complete, as the writer did
not have the necessary material available for describing such
developments, except m a very general way. — (ED.)
IN the early days of the alternating-current generator, it was
constructed in almost as many types as there were designers.
The principal endeavor of each designer appeared to be toward the
development of a new alternator which would bear his name. A
few of these early types were of the rotating field construction,
while a much greater number were of the rotating armature type.
Some had iron core armatures, while others had coreless armatures,
and there were many discussions as to whether the core or the
coreless type was superior and would survive. Many of the early
predictions would now form quite interesting reading, in view of
the fact that present practice is so far removed from the early
anticipations. Here and there among the early machines was one
which contained some of the important elements of recent ap-
paratus, but in many cases such machines disappeared in the
general course of development, the meritorious features being
insufficient to save the type.
SURFACE WOUND ARMATURES
In America, the principal early type of alternator had a
rotating armature with surface windings and an external cast
iron multipolar field. This type was used very considerably or,
in fact, almost exclusively, from 1886 to 1890. This was the type
built by the Westinghouse and the Thomson-Houston Companies.
There were only minor differences in the construction of the ma-
chines built by these two companies which, however, at that time,
appeared to be very great. These differences consisted principally
in the way the end windings of the armature coils were supported,
in the construction of the end bells and ventilating openings in the
armature core, in the method of attaching th e armature core to the
591
592 ELECTRICAL ENGINEERING PAPERS
shaft, in the winding of the field coils in metal bobbins, etc. Both
machines had surface -windings with concentric coils, one layer
deep in the radial direction. In the Westinghouse construction,
the end windings were turned down toward the shaft and were
supported by radial wooden clamps, as indicated in Fig. 1. In the
Thomson-Houston armature, the end windings were arranged in
an axial instead of a radial direction, and were supported by bands
or external clamps. This construction is also indicated in Fig. 1.
The Slattery machine, which was also on the market at that time,
was of the same general type as the above machines. Presumably
these two different methods of end winding were used on account
of the patent situation. At that time there was much discussion
of the respective merits of the two constructions.
These early machines were built principally for frequencies of
15,000 and 16,000 alternations per minute (125 and 133 cycles per
second). In those days, everything was rated in alternations per
minute, as this represented the product of the number of poles by
the number of revolutions. Such high frequencies were selected,
mainly, on account of transformer conditions, and not alternator
design. Practically all alternating service consisted of house to
house lighting, and in relatively small units, and the higher fre-
quency was supposed to be of great advantage in transformer
design and operation, which presumably was the case with the very
small amount of data and experience available at that time.
About the only commercial voltage for alternating work at
that time was 1000 or 1100 volts. This was supposed to be ex-
cessively high and dangerous, and there was much question
whether such an excessive voltage should be permitted. This-
matter was actually taken before a number of the state legislatures
for the purpose of obtaining laws prohibiting or limiting the use of
such voltage. Another reason why no higher voltage was used
was in the construction of the alternators and transformers. With
the experience and materials available at that time, together with
the high speed rotating armature construction ajid the surface
windings, even 1100 volts was a very serious problem in the gen-
erator. About 1889 or 1890, there appeared some slight demand
for higher voltages, and a few 2000 or 2200 volt surface-wound
alternators, of the then standard type, were built. However, even
then it was recognized that the surface-wound type of alternator
was not well adapted for higher voltages, and there was much,
question whether a different type winding should not be developed
DEVELOPMENT OF THE A C. GENERATOR
593
for 1100 volts. This gradually led to the next big step, namely,
the*development of the " toothed7' type of alternator with one big
tooth per pole, in distinction from the slotted type of armature
with a number of slots per pole, which was a considerably later
development.
TOOTHED ARMATURES
The first commercial toothed type of armature appears to have
been gotten out by the Westinghouse Company. These first ma-
PIG. 1— SURFACE WOUND ARMATURE WITH RADIAL CLAMPS (UPPER)
AND WITH AXIAL CLAMPS (LOWER)
chines were radically different, in details of construction, from the
later toothed armature types of machines which came into general
use. The first toothed armatures were small air-gap machines.
In the surface-wound armatures, the clearance between the arma-
ture surface and the field poles was comparatively small, although
the total air-gap (iron to iron) was large on account of the surface
winding. In constructing the new toothed armature, the actual
clearance (iron to iron) between armature and field was kept about
the same as in the surface-wound alternators (bands to iron), but
this clearance actually represented the total air-gap in the toothed
type. Moreover, in sinking the windings below the surface, it was
endeavored to maintain a practically uniform outside surface, so
that overhanging tooth tips were used with relatively narrow slots
for putting in the windings. The general construction was similar
to Fig. 2. On account of the sma.11 clearance, and consequent
higher magnetic additions, it was fottpd necessary to use lamin-
594 ELECTRICAL ENGINEERING PAPERS
ated poles with these machines in order to avoid excessive field
heating.
The self-induction of the armature windings on these machines
was very high compared with the old surface-wound armatures and
therefore, in order to obtain passably good regulation, fewer
armature turns had to be used, with correspondingly higher induc-
tions, and this made the use of solid poles impracticable on account
of heating. Furthermore, on account of the overhanging tooth
FIG 2.
tips, the small air-gap and the high induction per pole, this early
type of toothed armature was very noisy. In one instance, it was
credibly reported that one of these machines could be heard two
miles away on a quiet night. However, several machines of this
construction were put out by the Westinghouse Company, and
operated for many years.
Meanwhile, the possibilities of the toothed armature con-
struction in the old cast iron field were being given consideration,
The writer made a special study of this matter, and finally decided
that, in order to make this construction possible with solid cast
iron poles, it would be necessary to work at relatively low induc-
tions per pole, and with a very large air-gap, (fully as large as on
the old surface-wound machines) and with a shape of tooth tip
which did not have such great width compared with the pole tip as
shown in Fig. 2. This meant that a pole tip and air-gap as shown
in Fig. 3, should be used. " With this arrangement, the armature
DEVELOPMENT OF THE A.C. GENERATOR 595
self-induction would still be relatively high, and the regulation
correspondingly bad, necessitating some form of compounding for
regulating the voltage, similar to the compounding of a direct-
current generator. This armature construction was worked out
in detail for a 37.5 kilowatt field (that is, for the standard field of
the 37.5 kw surf ace-wound type of machine) . The armature teeth
PIG. 3
were similar to those in Fig. 3, in shape, and the air-gap or clear-
ance from iron to iron, was made % inch on each side of the
machine. The field was also compounded. When this machine
was put on test, it was found at once that it could be loaded to 60
kilowatts without undue heating of the armature and field iron,
and the problem of perfecting this machine then became one
merely of increasing the amount of armature copper to carry the
current at the 60 kilowatt rating. This, therefore, represented a
big step in the development of the American type alternator. It
was found that all the other Westinghouse standard cast iron
machines of the rotating armature type could readily be changed
in line with the above improvement.
COMPOUNDING ALTERNATORS
The compounding of the 60 kilowatt machine was not a new
feature, for already some of the laminated field toothed-armature
type of machines had been compounded, in order to improve their
regulation. Two different methods of compounding alternators
had been developed by the Westinghouse ajsd Thomson-Houston
Companies, respectively. In the Wesftiaghottse armature constrtic-
596
ELECTRICAL ENGINEERING PAPERS
tion, the armature discs were punched in single pieces, with spokes,
and were threaded directly on the armature shaft, no spider being
used. This construction is illustrated in Fig. 4. In the assembled
armature, the spokes were therefore of laminated material. These
laminated spokes were utilized as the core of a compounding trans-
former. One lead from the armature winding was carried around
the spokes of the armature before passing to the collector ring.
This winding formed the primary of a series transformer. The
secondary was also wound on the spokes, and the two ends were
carried to the bars of a rectifying commutator on the shaft. The
number of commutator bars was equal to the number of poles.
The alternating current from the secondary winding was by this
means changed to a pulsating direct current.
In the Thomson-Houston method of compounding, the main
armature current was carried directly to a rectifying commutator,
and, after being commutated, was passed to the field-compound
winding, and back to the commutator, and then to a collector ring.
FIG. 4-SKETCH OP COMPENSATED TYPE OP WINDING
The main armature current therefore passed directly through the
field, while in the Westinghouse method the secondary current
from a series transformer was passed through the field. Both
methods represented series compounding, and gave practically
equal results, but there was much discussion as to the merits of the
two methods. Both of these methods delivered pulsating direct
current to the field winding. There was considerable inductive
e. m. f. set up in the field windings by this pulsation, and this
tended to cause inductive discharges across the rectifying com-
DEVELOPMENT OF THE A C GENERATOR
597
mutators. In the Thomson-Houston method this trouble was
overcome to a considerable extent by the use of a non-inductive
shunt in parallel with the rectifying commutator, i.e., across the
compound winding. In the Westinghouse method a similar result
was accomplished by saturating the series transformer (or armature
spokes) to such a high point that the inductive kick from the field
could readily discharge through the secondary winding of the
transformer without giving high enough voltage to flash across the
commutator.
FIG. 5— EARLY WESTINGHOUSE 60 KILOWATT ALTERNATOR WITH
COMPENSATING WINDING
The details of this method of compounding have been gone
into rather fully, as this compounding was, at that time, an im-
portant step in our progress. The fact that of all these machines
were built for single phase, allowed us to use such compounding.
With the advent of polyphase generators, such methods of com-
pounding soon disappeared, principally for the reason that a great
majority of the early polyphase machines handled separate single-
phase loads on the different phases, and it was not practicable to
compound for these independently.
The above toothed type generator came into use about 1890
and1 lasted for several years, or practically until polyphase gener-
ators actually came into fairly general use before true polyphase
loads became common. These toothed type generators allowed
598
ELECTRICAL ENGINEERING PAPERS
the use of relatively high voltages, as far as the armature winding
was concerned, so that 2200 volts became comparatively common,
and even 3300 volts or higher was used in some cases. In fact,
the limit in such machines appeared to be at the collector rings,
rather than in the armature winding.
Something may be said regarding the type of winding used
on the armatures of these machines. In the Westinghouse con-
struction the armature coils were machine-wound and taped before
placing on the armature core. Each coil was made wide enough
to slip over the top of the armature tooth, as shown in Figs. 6 and
7. This made the coil considerably wider than the body of the
armature tooth, so that, after slipping over the tooth top the coil
had to be reduced in width by special clamping tools. Supporting
wedges were then driven in between adjacent coils.
Something may be said regarding the temperatures of these
early alternators, both of the surface-wound and of the toothed
types. In those days temperature measurements were very
crude compared with present practice, which is admittedly still
only approximate. In some of the surface-wound armatures
excessively high temperatures must have been encountered in
many instances, judging from the appearance of the insulation on
the individual wires, after a year's service, for instance. However,
FIG. 6— SKETCH SHOWING METHOD OP PUTTING MACHINE WOUND
COILS ON THE POLES
it was difficult to obtain reasonably correct temperature of the
armature windings, for the actual temperature of the conductors
was undoubtedly reduced very greatly before the armature could
be brought to a standstill. Even after this, temperature rises of
50 or 60 degrees C. were not considered as excessively high. With-
out doubt, some of these early machines, at times, attained actual
internal temperatures of 120 to 130 degrees C., or even higher,
with insulation on the conductors consisting of untreaded cotton
fibre. No overloads were possible, for each size of machine was
rated in as many "lights " as it could carry on a shop test without
DEVELOPMENT OF THE A.C. GENERATOR 599
breaking down. The first few minutes, while starting up a new
alternator in the testing room, were always anxious ones for the
operators, especially so if any "improvements " had been made on
the armature winding. Any defect in winding, or wrong con-
nection usually resulted in a stripped armature and much flying
copper. If nothing happened within the first few minutes after
the machine was put on load, the attendants all came out from
behind posts and other protections and went on with their work.
When the toothed armature came into use the above condi-
tions were much alleviated. Defects in construction, or short-
circuits, could not strip such armatures, and thus the danger and
excitement were removed. However, it was found that the first
short run did not tell the story of excessive heating as promptly
as in the case of the surface-wound type. Experience showed that
the toothed construction apparently could stand a severe shop
test and still go wrong under similar loading within a short time
after being installed. It was found that a given size of conductor
would not carry as much current in the concentrated coils of the
toothed construction as was the case in surface-wound coils.
However, the method of testing the temperature did not show this,
as the main part of the toothed armature coil was so embedded and
so covered with insulation that the thermometer readings did not
indicate nearly the true temperatures. The size of wire and the
amount of copper in the coils then had to be increased until the
machines did stand up in service. The true explanation of the
discrepancies was not well understood at that time. In these
toothed alternators, as in the surface-wound machines, the first
machines were rated in "lights," but gradually the kilowatt rating
came into use and became standard practice.
INTRODUCTION OP POLYPHASE ALTERNATORS
In 1892 and 1893, polyphase alternators began to be con-
sidered seriously. In 1889 and 1890, a few such alternators had
been built for the operation of Tesla induction motors. These
early polyphase alternators were of the surface-wound, rotating
armature type* These machines were very special in construction,
and, like the Tesla motors, did not find much of a market. How-
ever, in 1892 and 1893, it began to be recognized that the best way
to encourage the development of the induction motor would be
by creating a demand for it, and it was decided that a good way to
create a demand would be by encouraging the general adoption of
€00
ELECTRICAL ENGINEERING PAPERS
polyphase alternators and supply circuits, with the idea that, when
a, suitable supply circuit was available, there was eventually bound
to be a demand for motors to operate upon such circuits. With
this general policy in view, there was great activity in the develop-
ment of polyphase generators. ^This very quickly led to a very
considerable departure in armature construction from the usual
toothed armature as used in single-phase machines. The poly-
phase winding, requiring two or more coils per pole, naturally
FIG. 7— VIEW OP ARMATURE IN PROCESS OF PLACING COILS AND
CLAMPING THEM INTO SHAPE IN THE SLOTS
tended toward the slotted armature construction with two or more
slots per pole. It was soon recognized that, in general, the larger
the number of slots per pole and the smaller the number of con-
ductors per slot, the better would be the general characteristics of
the machine, so that the construction naturally tended toward the
modern slotted type. Moreover, practically all the development
in polyphase alternators was at relatively low frequency, com-
pared with former practice. It so happened that there had been a
well-defined tendency toward lower frequency in the period from
1890 to 1892. This tendency was largely independent of the
induction motor problem for, at the time it became most pro-
nounced, there was no true induction motor problem. It was
becoming recognized that 125 to 133 cycles per second was too high
for certain classes of work and for engine type generators, and
that, in general, a very considerably lower frequency must event-
ually be adopted. A great many lower frequencies were tried by
the different manufacturing companies, ranging from 50 to 85
cycles. However, 60 cycles seemed to have the preference at the
time polyphase alternators began to come in.
The early polyphase generators were mostly of the rotating
armature type, and usually with a fairly large number of slots per
DEVELOPMENT OF THE A C. GENERATOR 601
pole. One notable exception was tlie "monocycle" machine
which usually had only two slots per pole, one large slot for the
main armature winding, and one smaller slot for the so-called
"teaser" winding. Also, the early two-phase alternators of the
"inductor" type, built by the Stanley-Kelly Company, frequently
had only two slots per pole. However, it may be said that, from
1893 to about 1898, the great majority of the American built
alternators were of the rotating armature type with distributed
armature windings. The principal exceptions were the Stanley
inductor type of machines and a few special " rotating field"
machines, as distinguished from the inductor type.
The rotating armature machines were usually of 1100 or 2200
volts, although a few of considerably higher voltage were con-
structed. A few cases may be cited where special constructions
were used. For instance, the principal lighting plant at the Chic-
ago World's Pair in 1893, consisted of a large number of Westing-
house "twin" type generators. Each unit had two single-phase,
standard toothed type armatures side by side on the same shaft.
The teeth of the two armatures were staggered 90 electrical
degrees with respect to each other, so that the two together could
deliver currents having 90 degrees relation to each other. The
object of this construction was to obtain polyphase current with
standard single-phase types of machines without any radically new
development. This type of unit did not persist and, in fact, was
simply an expedient for this particular occasion.
THE FIRST NIAGARA GENERATORS
Also, in 1892 and 1893, the first large Niagara electrical de-
velopment was worked out. The advisory engineers of this plant,
proposed 5000 horse-power generators, having stationary internal
armatures and rotating external fields to obtain large flywheel
capacity. In fact, the construction was not unlike the usual
rotating armature machine of that period, as far as general ap-
pearance of the armature and field cores and windings were con-
cerned. However, the method of supporting and rotating the
heavy external field at a speed which, at that time, was con-
sidered excessively high, required an "umbrella" type of field
support, which gave these machines a distinctive appearance.
This type of construction did not persist, although these early
machines are still in operation.
602 ELECTRICAL ENGINEERING PAPERS
A further distinctive feature in these first Niagara machines
was in the frequency employed. A speed of 2SO revolutions per
minute was decided upon. The engineers of the power company
proposed eight-pole machines, giving 2000 alternations per minute
or 16 2-3 cycles per second. The Westinghouse Company pro-
posed, as an alternative, 16 poles, giving 33 1-3 cycles, the advan-
tages claimed for this frequency being that it was better suited
for motors and rotary converters, which were then promising to
become of importance. One advantage claimed for the 16 2-3
cycle machine was that it would permit the use of commutator
type alternating-current motors. After much discussion, and
weighing and balancing of all the various arguments for and against
these two frequencies, it was finally decided to use 12 poles, giving
3000 alternations per minute, or 25 cycle polyphase current and,
as fax as the writer knows, this was the origin of 'the present 25
cycle standard.
Considering what a radical departure from ordinary construc-
tion was made in these first Niagara generators, it is self-evident
that many curious and interesting conditions developed during their
design, construction and tests. As far as the writer knows, these
were the first large alternators which were deliberately short-cir-
cuited at their terminals when running at full speed and at normal
field charge. There were no instruments available to measure the
first current rush, but it was obvious that this current was far
greater than the steady short-circuited current of the machine
tinder similar field charge, for there were ample evidences of a ter-
rible shock at the moment of short-circuit. It was suspected at
that time that the first rush of current was only limited by the
armature impedance, and not by the so-called synchronous im-
pedance which fixes the value of the steady short-circuit current.
This also was the earliest machine of which the writer pre-
determined the field form and wave form by analysis of the flux
distribution. Later, when making shop tests on one of these
machines, the e. m. f . wave form was measured directly by rotating
the field at normal field charge at such an extremely low speed
that a voltmeter connected across the armature terminals showed
such gradual variations in e. m. f . that readings taken at regular
intervals could be plotted to form the voltage wave. Slow
rotation was obtained by means of a steel cable wrapped about the
outside of the external field and with one end of the cable attached
to a small diameter spindle around which it was wrapped at a very
DEVELOPMENT OF THE A C. GENERATOR 603
slow rate. This was a very crude method, but the wave form thus
obtained checked very accurately with tests made some years later.
Also, the early Niagara machines embodied one of the first
distinct attempts to ventilate alternators artificially. Early belted
machines had had small ventilating bells on each end. But these
Niagara machines were designed primarily with a view to setting
up an abnormal air circulation by means of special "scoops" or
ventilators on the umbrella supports. Very much thought and
discussion were given to this subject of artificial ventilation. The
results of our tests led to the arrangement of the scoops so that
they acted as exhaust pipes.
Also, water cooling of the armature spider was tried on some
of these early machines, but proved ineffective, due to the fact
that the cooling medium was applied too far away from the point
of development of the larger part of the armature iron and copper
losses.
INFLUENCE OF DIRECT-CURRENT DESIGN
It must be kept in mind that the general trend of direct-
current development had a certain influence on alternating-current
generator work. For example, there had been a slow, but positive
tendency in direct-current generators, toward the engine type
construction. Also, from 1890 to 1893, direct-current generator
armature construction had changed from the surface wound to the
slotted type. This doubtless had some influence in changing al-
ternator design toward the slotted type, especially when the poly-
phase type of windings came into use. Also, there was a pro-
nounced tendency toward the engine type, slow speed alternator,
accompanying direct-current practice. Practically all of these
early engine type alternators, except the inductor type, had
rotating armatures. Meanwhile, an interesting development took
place in the armature construction of some of these machines.
In most of the smaller belted machines, open armature slots were
used with machine-wound armature coils. However, many of the
early larger machines, especially of the engine type, were built for
relatively low voltage, such as 440 volts, two or three phase. This
admitted in many cases of simple bar windings with one or two
conductors per slot. This allowed partially closed armature slots
with shoved-through straight conductors, and bolted-on end
windings, giving a very strong substantial type of winding for re-
sisting the rotational Stresses. The partially closed slot became a
604 ELECTRICAL ENGINEERING PAPERS
sort of standard in Westinghouse machines, and endured for a
number of years, and was even carried into the stationary armature
type of machine when rotating fields came into general use. This
partially closed slot arrangement was a very good one as long as
the generator voltages were relatively low. The same may be
said of the rotating type of armature as a whole. However, when
high voltages came into more general use, a different construction
was preferable.
In reviewing the period of the rotating armature, slotted types
of machines, the monocyclic system should be briefly described.
Apparently this was gotten out with the idea that it avoided the
patented features of the Tesla polyphase system, The armature
circuits on this monocyclic system were so arranged that, when
dairying load, one phase carried nearly all of the energy load,
while both phases supplied magnetizing current for the operation
of induction motors. During the period when this machine was in
vogue, single-phase lighting work represented the principal
service, while induction motor loads were relatively small. With
increased use of polyphase loads, and with the elimination of the
patent situation, the monocyclic system gradually dropped out.
It was early recognized that a stationary armature winding
would be an ideal one in some respects, but it was thought that any
rotating field construction was bound to be a difficult and expen-
sive one. The inductor type construction was supposed by some
engineers to overcome the objections to the rotating field, but
many others considered that this type was not a final one, as it did
not use the magnetic material in the machine to the best advan-
tage. In the earlier alternators, with insufficient ventilation
through the armature core, relatively low magnetic densities were
necessary to avoid excessive iron heating, and the inductor alter-
nator, with its non-reversal of armature flux, was worked at almost
double the induction of the rotating armature type of machine,
and thus the disadvantages of the non-reversal of flux of the in-
ductor type were masked. In other words, the inductor alter-
nator was worked well up toward saturation, while the other
types were worked at only about half saturation. However, with
improvements in ventilation due to radial ventilating ducts, im-
provements in iron by better annealing and painting of the lam-
inations, etc., the flux densities in the rotating armature machines
were gradually increased until high densities, approaching satura-
tion, were reached. A corresponding increase in flux densities
DEVELOPMENT OF THE A C GENERATOR 605
in the inductor type was not possible, on account of saturation.
Therefore the rotating armature type of machine, in the later
designs, was much more economical than the inductor type, al-
though the latter had a very considerable advantage, especially
at high voltages, in its stationary armature construction. Due to
the merits of the stationary armature construction, the present
rotating field type of machine was gradually evolved, which pos-
sesses the advantages of the stationary armature of the inductor
type machine and the reversing flux of the rotating armature al-
ternator. It was the development of this type of machine which
sounded the death-knell of the inductor type. However, the
Westinghouse Company, about 1897, decided to bring out a line
of inductor type alternators to meet market conditions, although
such decision was contrary to the recommendations of the design-
ing engineers of the company, whose recommendation in particular
was in favor of the rotating field construction as a more permanent
type. However, as the rotating field type was not yet established,
except in a very minor way, and as the inductor type had been on
the market for years, it was decided to build the inductor type,
although the desigfi adopted was somewhat different from the
Stanley type. Three sizes of these machines were built, two
belted and one engine type, but the inductor type, as a commercial
proposition, soon died out.
One of the interesting peculiarities of the inductor type
alternator, as usually built, was in the enormous stray field appear-
ing in the shaft, bearings, bedplate, and sometimes in the engine-
governing mechanism in engine type units, necessitating in at
least one case, the use of brass governor balls. In the usual con-
struction of inductor alternator, there was but one exciting wind-
ing. The magnetic circuit and the field winding were arranged as
in Fig, 8, which shows both the Stanley and the Westinghouse
constructions. The normal or useful path of the magnetic flux
is indicated by the dotted lines a, a. Obviously, the field coil
which set up flux through these paths could also send magnetic
fluxes through the shaft, bearings and bedplate along the dotted
lines b, b. Moreover, if the two bearings were not connected by a
magnetic bedplate, as might be the case in engine type machines,
then, in two-crank engines the engine cylinders and other parts
became opposite poles of a very powerful electro-magnet, when
the field coil was excited. The stray magnetic field set up in
engine type units was sometimes so strong as to interfere with the
606
ELECTRICAL ENGINEERING PAPERS
governing mechanism. Also, with a strong unidirectional flux
between the bearings and shaft, each bearing became part of a small
unipolar generator, of which the bearing surfaces formed the
brushes. In some machines, quite heavy currents were generated
in the bearings, sufficient to ' ' eat away " the bearing surfaces or to
pit them so that bad bearing operation resulted. As this was
primarily a magnetic trouble, insulating the bearings from their
pedestals would not stop the action. To overcome this trouble,
PIG. 8— SKETCH OP MAGNETIC CIRCUIT OP AN INDUCTOR
ALTERNATOR
the Stanley Company added a "bucking " coil placed around the
shaft at one side of the generator, this coil being in series with the
main field winding and magnetizing in the opposite direction. The
ampere-turns of this bucking coil being made equal to those of the
field coil, the resultant ampere-turns between the two bearings
would be zero. Obviously, in an alternator with a bedplate and
two bearings in which the armature frame rested directly on the
bedplate, a single bucking coil at one side of the machine would
not neutralize the stray field through both bearings.
ROTATING FIELD GENERATORS
Considering next the rotating field type of machines, possibly
the earliest example was the Niagara type, mentioned before. This
had an internal stationary armature, with windings on its outer
periphery like the ordinary rotating armature. Outside this was the
rotating field, consisting of a heavy forged steel ring with inwardly
projecting poles. However, this type of construction was relatively
expensive, and was never adopted generally. The more modern
DEVELOPMENT OF THE A.C GENERATOR COT
rotating field type of alternator, with external stationary armature,
was a rather gradual development and, during this period, there
was much heated discussion as to the relative advantages of the
rotating field and rotating armature types. The rotating field
gradually superseded the rotating armature construction for a num-
ber of reasons, the principal one having to do with the armature
windings and voltages. In the rotating armature, the end wind-
ings were more difficult to support than in the stationary armature.
Also, with the gradual advent of higher voltages, the stationary
winding proved to be far superior. However, as a goodly pro-
portion of the alternators built during this transition period were
of the engine type and for low voltage, in which heavy bar wind-
ings could be used, (such being conditions tinder which the rotat-
ing armature made its best showing,) this type persisted for several
years after the rotating field type became commercial. Gradually
increasing voltages, however, necessitated the use of stationary
armature machines, for at least part of the business. The manu-
facture of two types of apparatus for the same general purpose
could not persist, and eventually that type was adopted exclusive-
ly, which allowed both high and low voltages. By 1900, the rot-
ating field alternator had come into very general use, and the
rotating armature type was disappearing. This rotating field type
has persisted until the present time, although many minor modi-
fications have been brought out from time to time, due largely to
change in speed conditions, etc.
In the rotating field development, the tendency for a number
of years was strongly toward the engine type construction and
relatively low speeds in many cases. The construction was carried
to the extreme, in some cases, where the usual flywheel capacity
required for the slow speed engines was incorporated in the field
structure of the alternator itself. In some cases, this meant
enormously large machines for the output. A prominent example
of this is found in the seventeen 6 000 kilowatt engine-type ma-
chines designed in 1899 and 1901 respectively, and installed in
the Fifty-ninth and Seventy-fourth Street power stations of the
Interboro Rapid Transit Company of New York City. As an
indication of the changes taking place in the electrical field, it may
be stated here that arrangements have been made recently to take
out a number of these machines atid install in their place 30 000 kw
turbo-generator units* The existing engine type machines are
probably in as good condition mm as wbuea first installed, and are ,
608
ELECTRICAL ENGINEERING PAPERS
being replaced simply because they occupy too much space in
proportion to their output.
The rotating field alternator of the early days was not radically
different from the rotating field alternator of today, the principal
PIG 9— SHOP VIEW OP 5 000 HORSE-POWER TWO-PHASE NIAGARA
ALTERNATOR
differences being in the type of armature windings, methods of
ventilation, etc.
FIELD CONSTRUCTION
In the types of field windings there has been but little change.
In many of the old stationary field machines of large capacity, the
field windings consisted of strap wound on edge, one layer deep.
For smaller machines, either square or round wire was commonly
used. In the latter rotating field machines, similar constructions
are used. In the construction of the field itself, there have been
some variations and modifications. In many Of the older ma-
chines the poles were laminated as at present. The method of
DEVELOPMENT OF THE A C GENERATOR
609
attaching the poles varied in different constructions. In many
of the earlier Westinghouse rotating fields the laminations were
punched with two or more poles in one piece, the poles having
no overhanging tips, and the field coils being held in place by
metal wedges between pole tips, fitted into notches or grooves at
the pole tips, each pole being attached to the field ring or yoke
by means of bolts or dove-tails. This latter construction possesses
numerous advantages, in that cheap dies can be used, and the
same pole punchings can be used for a number of different designs,
in which either the diameter or the number of poles is varied.
WATER WHEEL TYPE GENERATORS
With the advent of the turbo-generator on a large scale, the
engine type rotating field alternator almost disappeared from the
manufacturing field, except in the smaller size units. However,
during this period there has been a gradual development in the use
yj?Unfiri.Mri.MMJlf>i.f ti I "•>' (*?t1M
PIG. 10— STATOR OR ARMATURE OP NIAGARA ALTERNATOR
of water powers, and water-wheel driven generators have come
into much greater prominence in the past few years. In this line
of development, speeds and capacities, unheard of in the earlier
days, have become accepted practice with the development of both
high-head and low-head water powers. In the former the ten-
dency has been toward very high speeds for a given capacity such
610 ELECTRICAL ENGINEERING PAPERS
as the 17 000 k v.a., 375 r.p.m., Westinghouse machines, built for
the Pacific Light & Power Company, and the 10 000 k.v.a , 600
r.p.m,, Westinghouse generators, built for the Sao Paulo plant in
Brazil. Typical examples of low-head, slow-speed practice are
found in the 60 cycle, 75 r.p.m., 96 pole, 2 700 k.v a. Westinghouse
generators for the Stevens Creek development, and the 25 cycle,
58 r.p.m , 52 pole, 9 000 k v a. General Electric generators for the
Keokuk plant. The former are abnormal in the very large number
of poles required for moderate output, while the latter are ab-
normal in the very low speed. Both of the above machines are of
the vertical type, and are examples of a very pronounced tendency
toward vertical machines, which has been apparent in the later
water wheel practice.
On account of the high speeds of some of the modern rotating
field alternators, mechanically stronger spiders have come into
general use. Even in moderate speed units the usual high run-
away over-speed of 100 percent has necessitated the use of very
substantial spiders.
During the past few years, some very interesting spider con-
structions for the rotating fields of large high speed alternators have
been built to meet the severe speed requirements. Some of these
have been made up of cast steel centers or spiders with cylindrical
rims built up of overlapping laminated punchings, thoroughly
bolted together and attached to the spider by dove-tails. The outer
periphery of the laminated ring carries dove-tail grooves for poles.
In another construction, the entire spider consists of thick rolled
iron plates, bolted together, and with dove-tail grooves on the out-
side for the poles. In still other constructions, the rim of the
spider consists of a heavy steel ring in one or more sections to
which the cast spider is bolted. Usually with this cast rim the
poles are bolted to the spider. In some cases the rim forms an
integral part of the spider itself, being cast with the spokes and
hub. The type of construction adopted in each case is, to a large
extent, dependent upon the stresses to be taken care of, so that no
one type seems to fit all cases to best advantage
THE PROBLEM OF VENTILATION
In the later rotating field alternators the problem of ventila-
tion has received much consideration, especially in the case of
machines operating at abnormal speeds: In very high speed
machines of very large output the armature and field cores have
DEVELOPMENT OF THE A C. GENERATOR 611
a ratio of width to diameter which is relatively much greater than
in ordinary machines, and this has necessitated abnormal conditions
of ventilation. Something may be said here regarding the general
problem of ventilation of alternators and its influence on the evolu-
tion. Back in 1891 or 1892, radial ventilating ducts or passages
came into use commercially on certain direct-current machines.
The results being quite satisfactory, it was natural that alternators
should have the same method of ventilation. The use of such
ducts was in reality one of the great steps forward in the evolution
of dynamo-electric machinery, although but little recognition has
been given to this fact in electrical literature. The use of radial
ventilating ducts has continued to the present time with little
change except in the construction of the spacers themselves, which
have been many and varied in design and materials. With the
change from the rotating armature to the rotating field construc-
tion of alternators this feature was retained in full. In some of the
earlier Westinghouse rotating field machines the field structure
also had numerous ventilating ducts, principally for the purpose of
supplying ample air to the armature ducts. Also, about ten years
ago, special ventilating end bells and vanes began to be used on
rotating fields, in order to set up an extra air circulation through
the armature end windings, etc., due largely to the fact that the
slow-speed engine-type machines of that period did not have much
natural blowing action. Following this, and partly as an out-
growth of turbo-generator enclosing, came the semi-enclosed
alternators, mostly for high-speed water-wheel driven units, and
this practice is not uncommon at present.
The proper ventilation of an alternator or, for that matter, of
any dynamo-electric machine, is very much of a problem, for no
two cases, in different sizes or types of machines, are quite alike.
The problem Hes first, in furnishing the proper quantity of air to
carry away the heat developed, and in then distributing such air
in proper proportion through the complex multiple paths in the
machine. The proper distribution of the ventilating air is usually
the most serious part of the problem. The present solutions of the
problem are based largely upon past experience, and no really work-
able rules have yet been developed. In arriving at the present
practice many disheartening experiences have been undergone by
all designing engineers. The writer has known many cases where
totally unexpected i^esiaits, both good and bad, have been devel-
oped and, ia soma <o£ these cases, no logical explanation was forth-
612
ELECTRICAL ENGINEERING PAPERS
coming, so that the results could not be taken advantage of, with
any 'assurance, in future work. This has been one of the most
discouraging features in the general problem of ventilation.
ARMATURE WINDINGS
Something might be added here on the subject of armature
windings. There have been probably as many types of armature
windings developed as there have been types of alternators. The
windings for the earliest smooth body and the toothed armature
constructions have already been described. In the early West-
inghouse polyphase alternators, two-phase was used mostly, due
principally to the fact that single-phase lighting circuits formed
the principal load, and, with two-phase machines, there were only
two circuits from a machine instead of three circuits with the three-
phase winding. Moreover, many of these very early polyphase
ff^xfff^
FIG. 11— VARIOUS TYPES OF EARLY STATIONARY ARMATURE WINDINGS
alternators were used in reality as straight single-phase machines,
taking current off one phase only. For this purpose a closed
coil armature winding, like that of a direct-current generator or
rotary converter, with four taps for taking off the two phases,
gave about the most economical type of winding, as far as arma-
ture copper losses were concerned. When such an armature is
used for single-phase it can deliver seven-tenths as much output
DEVELOPMENT OF THE A C GENERATOR 613
as a single-phase machine as it can give two-phase with the same
total copper loss per coil. It was partly for this reason that many
of the early Westinghouse polyphase machines had a single closed
coil winding. Another reason for such winding was that there
were no definite phase groups and no high potential between
phases. Furthermore, the arrangement of the end windings was
such that the coils tended to interlock and support each other,
thus assisting in resisting centrifugal forces. This winding was
used mostly for two-phase machines, but was also used to a con-
siderable extent on three-phase armatures.
With the advent of the rotating field type of machine, this
closed coil type of armature winding was not used to any great
extent, open-coil two-phase and star-connected three-phase taking
its place. Delta-connected three-phase was used in very rare
cases, as there was danger of circulating current with such wind-
ings.
In the construction of armature windings possibly more
radical changes have taken place than in the types of windings.
Many of the larger low speed rotating armature alternators had
bar windings with separate end connectors, soldered or bolted on.
Many of the earlier stationary type armatures had either built-up
bar or strap windings, or concentric type windings in which each
phase winding was arranged in a concentric group, and the groups
of (the different phases overlapped each other. Some of these
were made with partially closed slots and others with open slots.
The built-up bar or strap windings were frequently of the partially
closed slot type, while the concentric windings were more usually
of the open slot type. Gradually, however, both these types of
windings were superseded by the "duplicate coil'* type of winding,
similar in appearance to the usual direct-current armature and
induction motor primary windings. This later type of alternator
winding was arranged in two layers of coils at the ends, in either
one or two layers in the slots, The two-layer, two-coil per slot
arrangement is now practically the standard. These types are
illustrated in Fig. 11.
In the rotating field machines, partially closed slot construc-
tion was carried to comparatively high voltages. For instance, the
6 000 kilowatt, 75 r.p.xn., 11 000 volt, three-phase generators built
for the Manhattan Elevated Railway in 1900 had three bars side
by side, in each slot, with soldered-on end collectors.
t>14
ELECTRICAL ENGINEERING PAPERS
As the partially closed slot and the open slot constructions are
radically different from each other, something should be said
regarding the reasons which prompted the use of either type. As
already indicated, the partially closed slot type came in with the
larger rotating-armature low-voltage alternators in which bar
windings could be used This construction gave good mechan-
PJG. 12— BAR AND END CONNECTOR TYPE OP WINDING WITH
PARTIALLY CLOSED SLOTS
ical support for the bars in the slots, thus avoiding the use of
bands. Moreover, with the very narrow slot openings at the top
of the slots, there was very little "bunching" of the magnetic flux
at the armature tooth tips with the consequent low pole face
losses, even with very small air-gaps, and high gap flux densities.
The disadvantages of the partially closed slot is found largely ia
the type of windings required.
DEVELOPMENT OF THE A C GENERATOR
615
In these early machines, it was found practicable, in general,
to use completely formed and insulated coils with such slots, and
therefore, either hand windings or built-up types of windings were
used. While these were possible and practicable in a manufactur-
ing establishment, yet such types of windings are usually difficult
to repair by the ordinary operator inexperienced in the refinements
of armature winding. When it comes to repairs, the usual ma-
chine-wound coil, which is completely insulated before being
placed on the armature core, is very superior but, in general, this
type of winding requires an open slot construction. However, when
PIG. 13— DUPLICATE COIL TYPE OP WINDING, TWO COILS PER SLOT
the stationary armature construction came into general use, the
advantages of the overhanging tooth tips in supporting the coils
largely disappeared. There remained therefore the disadvantages
of the flux bunching, against the advantage of coil construction,
if open slots were used. However, the use of laminated poles, and
the judicious proportioning of the air-gaps and flux densities, to a
great extent eUmtaated the losses dtia to open slots* Ip.
616 ELECTRICAL ENGINEERING PAPERS
quen.ce, the open slot construction and the duplicate type of
armature coil, have apparently come to stay, in this country.
Various attempts have been made to obtain the advantages
of both the open and the partially closed slot arrangements.
Probably all large manufacturers of alternators have tried some
form of magnetic wedge, instead of the usual fibre or wood wedges
which serve to retain the coils in the slots. Another arrangement
is the equivalent of combining two or more open slots in one, with
an over-hanging tooth tip, which covers the slot with the exception
of the widths of one coil. Two or more completely insulated coils
are fed successively into the slot opening and arranged side by
side. This does not give any narrower slot opening than with the
open slot construction, but the number of openings is reduced to
one-half, or one-third. This construction is used rather extensive-
ly in the rotors of large induction motors, but apparently is but
little used in generators.
Bracing of the end windings against short-circuit shocks has
been a comparatively recent practice. The necessity for such
bracing has been dependent to a considerable extent upon the
output per pole, and the old time machine seldom had such a large
output per pole that the short-circuit current-rushes were suffi-
cient to cause dangerous distortions of the end windings. How-
ever, such bracing was used on the Niagara machines, previously
described, and also on the Manhattan generators above referred
to. These, however, were very rare instances. However, with
the recent high-speed, high-output water-wheel generators, the
outputs per pole have become such that some form of end bracing
has become rather common.
Modern Westinghouse machines of this kind are braced to
stand a dead short-circuit across the terminals without damage to
the windings. Under this condition, these large machines may give
a momentary current rush of from ten to twenty times the rated
full-load current. However, the bracing required on the end
windings of such machines is of relatively much less importance
than on turbo-generators of corresponding capacity, due to the
fact that, in the former class of machines, the end windings are
relatively short compared with those of turbo-generators.
The above description brings us practically up to date, as far
as the ordinary synchronous alternator is concerned. No de-
scription of the development of the turbo-generator has yet been
given. This forms a rather distinct development which should
DEVELOPMENT OF THE A C GENERATOR 617
follow at this point presumably, but it is thought advisable to
interpolate here some description of the problems of parallel
operation, e. m. f. wave form, regulation, etc., which came into
prominence and were practically taken care of previous to the
advent of the turbo-generator on a large scale.
PARALLEL OPERATION OF ALTERNATORS
One of the great problems which developed in the operation
of alternators was that of the parallel running of two or more units.
At one time this was a very serious question, but in recent years,
it is very seldom heard of. Considering the almost universal
PIG. i*— DETAIL VIEW OP THREE-PHASE CONCENTRIC WINDING
practice of paralleling alternators, which holds at the present time,
one might be led to wonder why there ever was any trouble. Far
back, in the days of the high-frequency surface-wound alternators,
paralleling was attempted in many cases and, not infrequently,
with considerable success. However, a failure in an attempt to
parallel, in those days, usually meant the destruction of the ap-
paratus. Those old time surface-wound alternators usually had
very low self-induction, so that, in case of sudden short-circuit, an
enormous current could flow, ' sufficient' usually to strip the arm*
618
ELECTRICAL ENGINEERING PAPERS
ature winding from the core, by bursting the bands, or otherwise.
A failure in an attempt to parallel two machines was practically
equivalent to a short-circuit, and this usually meant destruction
of the apparatus. However, if once paralleled successfully, the
machines usually did not act badly. One favorable condition, not
then appreciated, was that all these early machines were belt-
PIG. 15—75 K.V A., THREE-PHASE. 60 CYCLE, 2 300 VOLT, 150 R. P. M.
ROTATING FIELD ENGINE TYPE ALTERNATOR
driven. It may be said, however, that in those days parallel opera-
tion, while considered possible, was also considered more or less
risky. In the period immediately following the surface-wound
alternator, parallel operation was very much the exception, rather
than the rule and, when engine-type alternators came into use,
paralleling was considered for several years as very questionable.
At this time the situation was as follows: — Belted alternators
could be paralleled in many cases. Direct-coupled alternators,
DEVELOPMENT OF THE A.C GENERATOR 619
if f flexibly driven, could be paralleled almost as well as belted
machines, while direct-coupled or engine type generators, without
flexible coupling or drive, could not be relied on to parallel with-
out hunting. It thus became recognized that some flexibility
between the generator and its prime mover was an important
adjunct to parallel operation. This led to the consideration that
the engine might be back of the difficulty in many instances, and
it was then assumed that inequalities in the regular rotation resiolt-
ing from insufficient flywheel or from hunting governors, tended
to cause hunting in the generators. Investigation showed that
such conditions did tend to produce hunting, but that the magnetic
conditions in the machine itself would oftentimes maintain, or even
accentuate, the hunting. Obviously, therefore, the trouble was
both in the prime mover and in the generator, It was noted fur-
ther 'that if the angular fluctuations in the driving power were
relatively small, hunting usually would be very small, or would not
be apparent at all. It was further recognized that, with belt or
flexible drive, which tended to smooth out the speed fluctuations
due to the prime mover, tjie hunting tendency tended to disappear.
Attention was then turned toward improvement of the prime
movers, especially in engine-type machines, in order to reduce
fluctuations in angular velocity by means of heavy flywheels, -and
by means of dampers of some sort, such as dashpots, on the
governing mechanism of the engine. Much improvement was
accomplished in this way,
THE INTRODUCTION OF DAMPERS
During this period many attempts were made to lessen the
tendency of the alternator to maintain hunting. Investiga-
tion showed that, during hunting, the magnetic flux in the field
poles shifted back and forth across the pole faces in time with
the hunting, while such action did not occur when there was
no hunting. This at once led to the theory that a lo^1 resist-
ance winding on the pole face, or imbedded in the poles, would
prevent or oppose this flux shift, and thus assist in overcoming
hunting. However, about this time, rotary converters were
coming into use, and it was found that, in such machines,
hunting was usually more severe than in alternators, so that, in
this country, the first true application of damping windings or
devices to stop hunting were applied on rotary converters* It was
also noted at this time that solid pole generators and rotary con-
verters did not tti&t to the sam® extent as did laminated pole ma-^
620
ELECTRICAL ENGINEERING PAPERS
chines, and it was correctly assumed that the solid pole faces gave
an effect similar to that of low resistance damping windings. How-
ever, as it was desirable to use laminated pole tips, copper dampers
on the poles gradually came into use. Some of these early dampers
were very crude in form and type compared with present construc-
FIG. 16— VARIOUS FORMS OF DAMPERS
tions. However, imperfections in the construction of the dampers
were balanced to some extent by the large section of copper used
and consequent low resistance. The earliest form of damper used
in this country consisted of copper rings surrounding the poles and
PIG. 17— GRID DAMPERS ON FIELD POLES
copper tips overhanging the beveled pole edges. This was the form
most commonly used on converters. On alternators, in some cases
the damper consisted simply of a low resistance ring around each
pole. In still other cases the damper consisted of a heavy copper
plate covering the pole face. This latter construction was only
DEVELOPMENT OF THE A.C. GENERATOR 621
possible in machines with large air-gaps and very narrow or partial-
ly closed armature slots. These crude forms of dampers were
gradually superseded by the so-called "grid" damper which con-
sisted of a copper grid surrounding the pole and with ribs which lay
in slots in the pole face. These various types of dampers are
shown in Fig 16. In very few cases were these old types of
dampers so interconnected as to form a complete cage winding
around the field.
Many tests were made at various times to determine the
effect of interconnecting the grids on the different poles to form
one complete cage. As a rule, there was no appreciable gain,
and it was then assumed that such interconnection had no material
advantages. However, it later developed that the reason why
interconnection of the dampers did not improve the damping
action very materially, was due largely to the very great amount
of copper in those parts of the grid dampers m lying between the
poles. The grid damper was very effective, but was expensive in
material, and was not easily applied on poles with overhanging
PIG. 18— CAGE WINDING TYPE OP DAMPERS
pole tips. This type of damper was gradually superseded by one
similar to the usual cage winding on the secondaries of induction
motors, and this is the type which is in most general use at the
present time. This construction has practically the same effect-
iveness as the old grid type, but is much more economical in
material and, being placed in partially closed slots, it does not as
greatly affect the iron losses in the machine, as was liable to be the
case with the open slots, generally used with the grid damper.
With the gradual introduction of dampers and improvements
in angular rotation of the prime movers, hunting troubles in alter-
nators practically disappeared, and parallel operation presented
622 ELECTRICAL ENGINEERING PAPERS
no difficulties, except under very abnormal conditions. Apparent-
ly these dampers or "amortisseurs," as they are sometimes called,
were first proposed by the French engineer, Maurice LeBlanc,
about 1891. However, they were "rediscovered" in this country
by engineers who were not familiar with the above engineer's
work.
VOLTAGE WAVE FORM
The e m. f . wave form of alternating-current generators has
been a matter of much discussion since the early days of alter-
nator design. The old surface-wound machines gave a very close
approximation to a perfect sine shape, due to the arrangement of
the winding and to the very large air-gap. The first toothed ar-
matures, with their very small air-gaps, gave e. m. f. waves which
I [ | I
JLJ
A
FIG 19— VOLTAGE WAVE FORMS
Of early toothed armature machines and of Later toothed armatures with larger air gaps and
beveled poles.
departed very widely from a true sine. In fact, this had about
the worst wave form of any of the alternators which have been put
out by the Westinghouse Company. Its shape was somewhat
like that shown in Fig. 19, as would now be expected when the
configuration of the armature tooth tips is taken into account.
The later toothed armatures with large air-gaps and beveled tooth
tips gave much better wave shapes.
With the advent of the true polyphase windings and the
slotted armatures with several slots per phase per pole, fairly
close approximation to sine shaped e. m. f . waves became common,
In the first Niagara Falls 5 000 horse-power, two-phase alter-
DEVELOPMENT OF THE A C. GENERATOR 623
nators, the voltage wave was slightly flattened on the top due to
the fact that the pole face width was somewhat greater than the
width of each phase group in0 the armature. When very high
voltages came into general use, and especially in machines with
small pole pitch, the number of armature slots per phase per pole
was reduced to a minimum in order to lessen the total insulation
space. In extreme cases, but one slot per phase was used, giving
but two slots per pole for two-phase and three slots per pole for
three-phase. Such windings required special shaping of the field
pole tips in order to approximate even roughly a smooth wave
form of the sine shape. Later practice, however, has tended
toward the equivalent of at least two slots per phase per pole, in
order to obtain. better results. Sometimes the desired result is
obtained by the use of one extra idle or "hunting" tooth per
phase.
In the early days of parallel operation of engine type alter-
nators which, as described before, represented the most difficult
conditions, great stress was laid upon the question of wave form
in some of the discussions of parallel operation, and particularly,
in the operation of rotary converters without hunting. Grad-
ually, however, this question disappeared and it became recog-
nized that all the cases of hunting encountered could be explained
in some other way than by the e. m. f . wave forms, and it is now
generally accepted that about the only effect on parallel operation
due to wave form lies in possible circulating currents of higher
frequency than the fundamental.
At the present time, a very close approximation to the sine
shaped wave is considered preferable for general purposes, es-
pecially in transformation and transmission work. There have
been some instances of telephone disturbances due to wave form
but, as a rule, some local peculiarities of the distribution circuits
have been involved in this trouble, for, in other cases, similar or
even worse shaped waves have given absolutely no telephone dis-
turbances.
REGULATION AND COMPOUNDING
Something should be said on the subject of regulation of
alternators, for this is a very important characteristic, and has
had considerable influence on types and designs. The old surface-
wound alternators had extremely good regulating characteristics
due to their low amiature self-induction and low armature reac-
624 ELECTRICAL ENGINEERING PAPERS
tion consequent upon their large air-gaps. The writer does not
know what valite the current rose to, on steady short-circuit,
compared with the normal rated current, but it was probably four
or five times full load. The current rush on short-circuit was
probably five times as great as the steady value. It is not to be
wondered at that such armatures not infrequently wrecked them-
selves in case of a dead short-circuit. In the later toothed arma-
ture types, the armature self-induction and reaction on the field
were very much larger, proportionately, than in the surface-
wound machines. This, however, spoiled the regulation and some
method of compounding was used, as already described. This
compounding was common practice until larger capacity machines,
especially the engine type, came into use. Even some of these
latter were compounded by commutating the armature current
(either directly or from a series transformer) and compounding
the exciter field by means of the commutated current. A few of
the smaller size alternators were both self -excited and compounded
by commutating derived alternating-current circuits from the
armature. This, however, was found to be very delicate, as the
excitation and compounding were greatly affected by changes in
the power-factor of the load, and by changes in speed.
One early attempt was made to compound single-phase
alternators to correct for power-factor. In this case the com-
mutated armature current was sent through the series or compound
winding of the exciter. The brushes on the alternating-current
commutator were so set that at 100 percent power -factor they were
commutating about the middle of each voltage wave. In con-
sequence, the current delivered to the brushes was not a true
direct current but consisted of a double number of half waves,
half of which were inverted, and the direct-current component of
this commutated current was small and had but little compound-
ing effect. However, with change in power-factor of the load, the
phase of the current shifted, so that at some reduced power-factor,
commutation occurred at the zero point of the current waves and
the resultant current was all effective for magnetizing the exciter
field. The total commutated voltage was very low and the com-
mutator bars were shunted by a resistance so that there was no
bad sparking, even when commutating at the middle of the current
wave. This method did actually compound fairly well for change
in power-factor, but the field for such method proved to be very
limited, for compounding of alternators fell into disuse shortly
after this.
DEVELOPMENT OF THE A C. GENERATOR 625
The usual method of compounding on the early alternators
was simple series-current compounding, just as in direct-current
apparatus. Where the commutated current was supplied directly
to the field compound winding, voltages of about 30 to 60 volts
were most common at rated full load. With much higher than 60
volts, there was a liability of short-circuiting the compounding by
arcing between bars on the commutator There was also a liability
of arcing or flashing when the phase of the current shifted due to
change in power-factor.
When polyphase rotating armatures came into use, similar
methods of compounding were resorted to. However, the second-
ary current was a resultant of the two, or three primary currents,
for each of the primary phases was carried around the compensat-
ing transformer (or spokes of the armature) and the secondary
winding carried a current in phase with the resultant of the primary
ampere-turns. In the case of three-phase windings, the direction
of one lead was reversed around the compensating transformer.
Some curious conditions arose from the phase relations of the
secondary current when parallel operation was practiced. It was
necessary, when paralleling the main winding, to parallel also the
compound winding. As the compounding current from each
machine pulsated from zero to maximum value in each alternation,
it was necessary to so parallel the terminals that all the commut-
ated currents had zero value at the same instant, otherwise, the
brushes on one commutator would, at times, short-circuit the cur-
rent from the other commutator.
With the advent of larger belted machines, and of engine-type
machines in particular, the compounding of polyphase machines
was more or less unsatisfactory and was practically abandoned.
To compensate for the lack of compounding, bettei inherent regu-
lations were aimed at in the designs. This meant, primarily,
machines which would give comparatively large currents on steady
short-circuit, three to four times full load being rather common, and
even six times full load being attained in some machines. The
momentary current rush at the instant of short-circuit must have
been excessive on some of these machines, due to their very low
armature self-induction. However, due to the relatively small
ampere-turns per pole, no very destructive distortions were found
in practice. This characteristic of the short-circuit currents was
carried into the rotating field construction, and even into the
early turbo-generator work.
626 ELECTRICAL ENGINEERING PAPERS
This practice o£ giving the alternators good inherent regula-
tion was expensive in a number of ways, as it usually meant
higher iron losses and less output than was possible otherwise, with
a given size machine, or a given amount of material. Even at this
early date, it was recognized that some form of automatic field
current regulator which would maintain the terminal voltage con-
stant, regardless of the inherent regulation would be a very useful
piece of apparatus. Some form of regulation which would take
care of change in power-f actor, as well as load, was the aim of many
designers. Among the different schemes brought out, the Rice
method of compounding, brought out by the General Electric
Company, is of interest. This was used principally with rotating
field alternators. In this scheme, the exciter was usually placed
on the same shaft as the alternator field, and, in such case, had
the same number of poles as the alternator. The leads from the
alternator armature were carried through the exciter winding in
such a way that a lagging current, carried by the alternator,
tended to strengthen the field of the exciter by shifting the arma-
ture reaction with respect to the exciter field poles. In this way a
compounding action on the exciter was obtained which was prac-
tically in proportion to the demands of the alternator field with
varying power-factor. In the case of engine-type machines of
comparatively low speed, the exciter was geared to the alternator
shaft, so that it ran at a considerably higher speed and the number
of poles in the exciter was correspondingly reduced
This method of compounding was effective, but the whole
combination was apparently unduly complicated and expensive.
Furthermore, it did not give the desired compensation under all
conditions of operation, as it would not correct for changes in
speed.
A later method of compensation for power-factor was devised
by Alexanderson, and was used on a limited number of General
Electric machines. In this scheme a derived current from the
alternator itself was commutated in such a manner that compensa-
tion, proportional to the power-factor, was obtained. This was a
purely self-excited alternator scheme and, like all self-exciting
schemes in such apparatus, it was sensitive to speed changes,
probably to a much greater extent than the Rice arrangement
above described. A fundamental defect in all self -exciting ^com-
pensated alternator schemes lies in the fact that stability of ex-
citation is dependent upon having considerable saturation in the
DEVELOPMENT OF THE A C GENERATOR 627
alternator magnetic current and, coincidently, if there is such
saturation, the compound current has no direct relation to the
load or power-factor. Thus such machines are either sensitive to
speed changes, or their compounding is only approximate.
Following these schemes came the use of automatic regulators
of which the Tirrill is best known. This regulator acts directly on
the exciter field by short-circuiting a resistance in series with the
field winding, the range of exciter voltage being controlled by the
length of time the rheostat is short-circuited. Instead of cutting
the resistance out in steps, which tends to give sluggish action in
the fields, the Tirrill regulator cuts the whole resistance out each
time, and the length of time is varied. This results in quick
action. As the regulator tends to hold constant voltage at the
alternator terminals, or on the line, change in power-factor or in
speed does not modify the action. This type of regulator has
proven very effective, especially in the case of alternators sub-
jected to sudden and violent changes in load, power-factor and
speed.
With the advent of larger alternator units, in proportion to
the changes in load, the inherent regulation has been made relat-
tively poorer, primarily because better machines otherwise are
thus obtained. The short-circuit currents are reduced, and
relatively lower iron losses, and lower temperatures or, higher out-
puts with a given temperature, are obtained. This has been car-
ried further in turbo-generator design than in any other class of
alternators, due partly to fundamental limitations in design.
However, this poorer inherent regulation has proven to be of no
practical importance, where suitable automatic regulators have
been used with the machines.
One fallacy which was frequently found in the past, and which
still persists to some extent, is that alternators should have equal
inherent regulation to parallel properly. This is based partly on
the feeling that the field currents of the alternators should vary
over equal range when carrying their proper proportion of load,
together with the knowledge that the variations in field current
are dependent, to some extent, upon the inherent regulation.
However, the fact that the shape of the saturation curve, in a
given alternator, may have much more influence on the excitation,
especially at high saturations, is usually overlooked.
628 ELECTRICAL ENGINEERING PAPERS
TURB O-GENERATORS
The advent of the turbo-generator has had a predominant
influence on alternator design. After the turbo-alternator once
became established commercially in this country, it quickly revo-
lutionized conditions by driving the large engine-type alternators
out of the field. The evolution of all electrical apparatus has been
comparatively rapid, but that of the turbo-alternator has possibly
exceeded anything else in the electrical field. This evolution
therefore merits a fairly complete description.
The first turbo-alternators built by the Westinghouse Com-
pany, were installed in the power plant of the Westinghouse Air
Brake Company about 1898. These were three rotating armature
machines of 300 kilowatts capacity, which ran at a speed of 3 600
r. p m , giving 7 200 alternations per minute, or 60 cycles per
PIG. 20— FIELD OF EARLY ROTATING ARMATURE TURBO-GENERATOR
second. They were coupled to Parsons turbines, built by The
Westinghouse Machine Company. The Parsons Company in
England had been building rotating armature alternators for a
number of years, and the Westinghouse Company simply followed
the Parsons' precedent. These first machines were operated for
several years, but it was obvious, soon after their installation,
that the rotating armature type of machine would not serve for
DEVELOPMENT OF 7 HE A C GENERATOR
629
general turbo-alternator purposes. It was evident that, for
voltages even no higher than 2 200, the rotating armature con-
struction, at the necessary turbo-generator peripheral speeds,
would become almost impracticable. Attention therefore was
soon turned toward a 3 600 revolution,two-pole, rotating field type,
FIG. 21.— ARMATURE FOR TURBO-GENERATOR OF THE TYPE SHOWN
IN FIG. 20
and a very large number of possible constructions were con-
sidered. Finally one like that shown in Fig. 23 was worked out
and built in 1899. This had the field windings completely em-,
bedded in a number of parallel slots, with supporting metal wedges
FIG. 22—1 000 KW OPEN TYPE TURBO-GENERATOR
at the tops of the grooves or slots. One machine of this type was
built and tested. It operated in a satisfactory manner, except as
regards windage and noise. The machine was not closed at the
ends, like modem turbo-alternators, and thus any noise generated
in the machine could be readily transmitted to the outside. The
noise was caused largely by the two flat sides of the rotor. It was
630
ELECTRICAL ENGINEERING PAPERS
so shrill and penetrating that it was very disagreeable to be around
the machine, and was even painful to the ears after a short time.
This construction was therefore abandoned temporarily, but after
a few months it was taken up again and a new rotor was built
which was entirely round, as shown in Fig. 24, but was otherwise
very similar to that shown in Fig. 23. This new rotor, although
noisy compared with modern machines, was so quiet, compared
with the first construction, that it was immediately adopted as a
standard construction. This is the now well-known parallel slot
construction which has been used very extensively by the Westing-
house Company, although many very radical changes have been
made in the constructive features of the rotor itself. This type of
rotor was used originally only for the 400 kilowatt size at 60 cycles.
In the earlier machines of this type a number of very curious
conditions developed. In the first machines the rotors were built
of a number of thick discs or "cheeses" side by side, which were
put on. the shaft at high pressure. The two end discs were thicker
than the others in order to accommodate the grooves in which the
rotor end windings lay. The discs were made of high grade f org-
o
PIG. 23— -EARLY TWO-POLE ROTATING FIELD
ings. After some of these machines had been in operation for a
•considerable period it was found that sotne of the discs in the field
core were traveling axially, i.e., quite appreciable gaps or spaces
were showing between adjacent discs. In one instance they trav-
eled to such an extent that the field windings were stretched
longitudinally at the openings between the discs, until the con-
ductors were actually attenuated to an extent visible to the eye.
Obviously, the stretching force must have been enormous.
DEVELOPMENT OF THE A C GENERATOR 031
Eventually, the construction was changed on these two-pole
rotors to a single disc of forged steel. Still later, steel castings
were used quite extensively instead of forgings although, later
still, the castings were abandoned in favor of forgings. There was
much adverse opinion regarding the advisability of using castings
for the 3 600 revolution machines, as some engineers held that
they were more liable to contain flaws than would be the case with
forgings. An interesting fact in connection with this is that, while
a number of these early high speed machines " exploded,7' gener-
ally during runaways, yet in no instance was a cast steel field wreck-
ed from this cause. This, however, does not constitute a proof
of the superiority of cast steel, for it so happened that all the
serious runaways were on machines with forged rotors. However,
o
PIG. 24— ROUND TYPE TWO-POLE ROTOR
the record is a clear one as far as cast steel fields are concerned,
for, of all the sizes and speeds of steel rotors which the Westing-
house Company has put out, not a single cast steel disc has burst.
Present speed and output requirements have now carried the
construction up to a point where special forged materials are the
accepted practice.
Soon after the two-pole, 400 kilowatt rotating field machine
was put on the market, a four-pole, 750 kilowatt, 1 800 revolution
machine was built. The rotor of this machine had four salient poles
bolted on. These poles were provided with overhanging pole tips,
and the field winding consisted of four coils wound with strap-on-
edge. In fact, this first construction was very similar to the
present type of rotor fields now used for other than turbo work.
This construction proved difficult and expensive, but was applied
to a number of six-pote, 1 200 revolutiop machines. However,
632
ELECTRICAL ENGINEERING PAPERS
the parallel slot construction used in the two-pole machines was so
satisfactory that it was soon adopted for the four and six-pole
machines, as shown in Fig. 25 . In the six-pole machine it was not
possible to make the poles integral with the central core, on
account of the inability to machine the parallel slots in the sides of
PIG, 25— PARALLEL-SLOT FOUR-POLE AND SIX-POLE FIELD
CONSTRUCTION
the poles, or to put in the windings. Therefore, separate poles were
constructed, with parallel slots, and these were first wound and
then bolted into place on the central core which, in this case, waa
made integral with the shaft. The four-pole machine was con-
structed for 750 and 1 000 kilowatts capacity, and the six-pole con-
struction was made for 1 500 to 3 000 kilowatts.
Meanwhile, there had grown up some demand for moderate
capacity 25-cyde machines at 1 500 revolutions. These were
constructed along exactly the same lines as the two-pole, 3 600
revolution machines above described.
In this early work one order for four 5 500 kw, four-pole, 1 000
revolution machines was taken. This was entirely beyond the
constructions undertaken before by the Westinghouse Company.
The parallel slot type of rotor was adopted. An attempt was made
DEVELOPMENT OF THE A C. GENERATOR
633
to get forgings in a single piece large enough for these rotors, but
they were found to be glass hard and brittle, except at the outer
surface. As very large steel castings" were frowned upon, it was
decided to make these rotors of discs turned out of very thick steel
plates, somewhat like the early 400 kw machines already de-
scribed. Parallel slots were used as in the smaller four-pole
machines. This construction proved to be feasible but was very
expensive, and shortly after this, large cast steel discs were used,
two discs side by side being used to form one rotor. This con-
struction was satisfactory, and was used for many years
7
7
FIG. 26— TWO-POLE FIELD OF THE BOLTED ON CONSTRUCTION
Shortly after turbo-generators came into general use, there
was considerable complaint regarding the noise due to windage.
All these machines were equipped with some form of ventilating
device, which either formed part of the normal construction of the
rotor or consisted of some special blowing device at the ends of the
rotor. Both the high speed and the large^quaixtity of cooling air
634 ELECTRICAL ENGINEERING PAPERS
required, tended to make a noise which was very objectionable.
A series of experiments with covers over various parts of the
machines, showed that, by completely enclosing the two ends of
the machine and by enclosing the field frame except at the top and
bottom, (in a horizontal machine) the windage noise could be so
deadened as to be practically unobjectionable. However, the
tests also showed that artificial ventilation was necessary under
this condition. This very quickly led to the practice of enclosing
and artificially cooling turbo-generators, which practice has been
maintained to this day. The first Westinghouse enclosed ma-
chines were built about 1903.
The use of artificial cooling marked a great step in advance in
turbo-generator work, for the results indicated that, by supplying
a sufficient quantity of air and properly distributing it through
the machine, very marked increase in capacity was possible, and a
point was soon reached where the possible capacities were beyond
the mechanical limitations of the construction. This led to radical
modifications in the type of rotor, with a view to taking advantage
of the increased capacity. Apparently all manufacturers did
more or less development work along such lines. In the Westing-
house constructions, the use of a through shaft was found to be
one of the serious limitations, and this led to types of rotors with-
out any through shaft. In the two-pole machines, this was
particularly important, and the problem was especially difficult
with the parallel-slot construction, provided ample space was al-
lowed for the field winding. The old through-shaft two-pole con-
struction lost considerable winding space, due to the shaft- space,
as shown before in Fig, 24. Attempts to construct such a machine
with the shaft forming part of the core, resulted in still less ef-
ficient use of the possible winding space. It was obvious that if the
whole possible winding space were taken up with slots, then the
capacity of the field winding would be greatly increased. In
consequence, a rotor construction, such as shown in Pig, 26, was
designed and constructed. In this, bronze end supports or
"heads" were bolted to each end of the field core, and the shaft
proper was attached to these bronze heads. Bronze, or a similar
non-magnetic material, -was necessary to prevent magnetic short-
circuiting of the field flux, This design was constructed and tested
on a 1 000 k.v.a., 3 600 revolution machine, and then was built
successively for 1 500, 2 000, 3 000, 4 000 and 5 000 k.v.a. machines,
all at 3600 r. p. m. The same construction was also applied to
DEVELOPMENT OF THE A C GENERATOR 635
two-pole machines of 25 cycles, up to 12 000 k.v.a. capacities.
This construction of rotor has given an extremely good account of
itself. However, it proved to be expensive on small capacity ma-
chines, as the bronze heads formed an undue proportion of the
cost of material. For higher capacities of 3 600 r. p. m. machines,
increase in capacity is obtained largely by increasing the length of
the rotor core, and thus the bronze heads form a relatively lower
percentage, and the construction becomes more reasonable in cost.
From the preceding, it may be seen that only two types of
turbo-generators have been used very extensively, namely, the
parallel-slot type and the radial-slot type. Each of these types
has some very pronounced advantages. The principal advantage
of the parallel-slot type is in the arrangement and support of the
field coils. Each coil can be wound directly in place, with the
conductor under tension, and the finished winding is completely
encased, and is thoroughly protected against dirt, movement of the
conductors, etc. Against this, the radial-slot machine allows more
room for copper, and is magnetically more economical in material.
However, the field windings are more difficult to apply and must
be supported at the ends by auxiliary means, such as separate
external steel rings.
The enormous increase in output of turbo-generators, within
very recent years, has made the electric and magnetic proportions
of the rotors a feature of first importance in the design, so that the
radial-slot type for two-pole machines has become the standard
construction, almost universally. This will be referred to again
under the four-pole construction.
While the two-pole parallel slot construction was being de-
veloped for larger capacities, the four-pole construction for 60
cycle machines has been pushed up to capacities of about 12 000
k.v.a. with the parallel slot, cast steel rotors. In order to do away
with the through-shaft construction, the rotor was made of two
castings or discs, each of which was cast solid with the shaft, as
shown in Fig. 27. The two discs, after machining, were bolted
together by a number of very heavy bolts located near the pole
tips and, in some cases, shrink links were placed in the pole face,
connecting the two halves together. The parallel grooves were
then machined in the steel core, just as in the through-shaft type.
In this four-pole construction the* problem of armature ventila-
tion was comparatively simple. Air-gap ventilation (that is, all
air through the armature core supplied froqa air-gap) was easily
636
ELECTRICAL ENGINEERING PAPERS
accomplished, due to the open spaces between the poles, which
could admit an ample air supply. However, the same construction
tended toward high windage losses due to air "churning."
T ^ -* "
r--r--r:-rzr[
«___._«._ p<
r
PIG. 27— FIELD CONSTRUCTION WITH TWO HALVES HELD TOGETHER
BY HEAVY BOLTS
This problem of ventilation has had much to do with the
evolution of turbo-generator design.* In the two-pole, parallel slot
machine for 3 600 r. p. m., in which the diameter of the rotor is
relatively small, the amount of air which can be forced into the
air-gap from each end is rather limited. Assuming, for example,
a rotor diameter of 24 inches, which is almost as large as we can
go for a 3 600 r. p. m. machine, then, with an air-gap (iron to iron)
of %-inch, which is also a fairly large gap, the total cross-section of
the air inlet at the air-gap at both ends of the rotor will be 1 12 sq.
in. With the very high air velocity of 10 000 ft. per minute, this
means a total air supply of less than 8 000 cu. ft. per minute. This
may be sufficient for a moderate capacity turbo-generator, but
for machines of high capacities, such as 3 000 to 5000 k.v.a., this is
not nearly enough cooling air. Obviously, either much larger
inlets through the air-gap are required, or some additional method
of cooling is necessary. Larger air-gaps usually mean either more
expensive machines, or reduced output with a given machine, due
to lower flux densities. Therefore, the tendency, in machines of
the very high capacities, and very high speeds, has been toward a
combination of air-gap with other methods of ventilation. In the
25 cycle, two-pole machine with a maxicnum speed of 1 500 r.p.m.,
rotors of larger diameter are possible and, as a rule, much larger
air-gaps are practicable than in 60 cycle machines. In conse-
quence, air-gap ventilation comes nearer being practicable but in
*A more complete exposition of the subject of "Turbo-Alternator Ventilation, "etc.r
Is contained in the paper on page 313.
DEVELOPMENT OF THE A.C. GENERATOR 637
the larger capacities, even this is insufficient and auxiliary methods
have been necessary in some cases.
This need for auxiliary methods of ventilation led to the axial
method of ventilating armature cores in distinction from the
radial method, in which the air was carried out through numerous
radial air ducts or passages. In the axial method, a large number
of ventilating holes are arranged in the armature core parallel to
the axis of the machine. These form ventilating paths in parallel
with the air-gap path. With the small diameter long cores
necessary for 3 600 r. p, m., high capacity machines, the develop-
ment of this method of ventilation was contemporaneous with the
development of the higher capacities. The same has proved to be
the case for the later types of Westinghouse four-pole, 60 cycle,
1 800 r. p. m. machines, which departed very considerably in rotor
construction from the four-pole cast steel type already described.
As the capacities of the 3 600 r. p. m , 60 cycle machines were
gradually pushed up, a corresponding development occurred in the
1800 r. p. m. machines. At 10 000 to 12 000 k.v.a., the four-pole
cast steel construction was apparently approaching its limits.
FIG. 28— MODERN ROTATING FIELD ON BALANCING WAYS
For larger sizes, therefore, a different construction was adopted
which allowed more suitable material to be obtained. For the
largest diameters and highest speeds, a plate construction was
adopted by the Westinghouse Company, in which the end discs
and the shaft ends were forged as units, and the intermediate discs
were made of rolled plate material, the whole construction being
bolted together permanently to form a solid core. This core was
then slotted with radial slots, and the usual radial slot type of field
winding is used. A similar construction was adopted on the larger
25 cyde machines. For intermediate capacities, both 60 and 25
638
ELECTRICAL ENGINEERING PAPERS
cycles, solid discs are used in some cases instead of the plate
construction, This brings the larger turbo development up to
the present date.
In the comparatively small 60 cycle turbo-generators, where
the parallel slot construction with the bronze driving heads was
relatively expensive, as already described, the later development
has been towards core and shaft forged in one piece, and with
FIG. 29— STATOR OF 6Z5 K.V.A., 2 300 VOLTS, 3 600 R. P. M..
TURBO-GBNERATOR
With aerial ventilation and central duct. Supporting ring both inside and outside thfc
end windings. Typical method of bracing smaller machines.
radial slots, and eventually this construction may be carried up
to the largest practicable size of 3 600 r. p. m, machines. It is diffi-
cult to predict the limit in capacity which may be reached even-
tually in 3 600 r. p. m. generators, but 6 250 k.v.a. appears to be
practicable.
Some special radial-slot machines had been developed for the
New Haven Railroad about 1907. As these machines were de-
signed to deliver 25 cycle single-phase current, and as the pulsating
armature reaction of *such machines would be relatively high, the
rotors were designed with laminated cores, with a view to lessening
core losses. The rotors were made of single disc laminations shrunk
on the shaft. The discs were provided with radial slots. The con-
struction was very similar to the later radial-slot rotors, except
that* the rotor end windings were also embedded in slots, and
DEVELOPMENT OF THE A.C GENERATOR 630
supported by wedges embedded in the periphery of the core,
whereas, in the later radial-slot rotors, the end windings are sup-
ported by external rings. These early radial-slot rotors showed
very considerable overheating in single-phase operation, and it
was found necessary to apply a very complete cage damper em-
bedded in the periphery of the rotor. Later experience showed that
the solid-core parallel-slot rotor with an equal damper applied to
its surface was just as effective, and many of the later single-phase
machines were built in this manner. However, some recent 1 1 250
k.v.a. single-phase generators are being built of the plate construc-
tion already described,
REGULATION AND SHORT-CIRCUIT CURRENTS OP TURBO-ALTER-
NATORS
Like the ordinary synchronous generator, the modern turbo-
alternator is designed with a comparatively high inherent regula-
tion. In fact, in order to avoid excessive short-circuit currents,
the inherent regulation must be made comparatively poor by
making the armature self-induction as high as practicable. Even
under the best condition, such machines are liable to give 12 to
15 times rated current during the first current rush. Furthermore,
the solid plates or discs, of which most turbo-rotors are now made,
tend to prolong the period of maximum short-circuit current. The
consequence of these conditions is a tremendous racking force
acting on the end windings during a short-circuit current rush,
which tends to distort the winding badly unless it is very strongly
braced. The Westinghouse Company encountered such a diffi-
culty on some of their earliest turbo-alternators and there has been
a practically continuous development along the lines of more
substantial bracing which has kept pace with the increased require-
ments of the higher speeds and the higher capacities. The bracing
used on the modern machines is designed to resist distortion of the
end windings, under dead short-circuit, without reactances inter-
posed, and each new size as it is developed is given such a short*
circuit test. A 20 000 k.v.a* 60 cycle, 1 800 r. p. m, high voltage
alternator was recently subjected to such short-circuit tests at full
voltage without injtiry.
The preceding gives a brief history of tba developmeixt of the
turbo-geaerator, insofar as carried out by the Westinglxouse Com-
pany. The General Electric Company went through a correspoxid-
640
ELECTRICAL ENGINEERING PAPERS
ing course of development, in general, although not in the specific
constructions described, and a number of interesting types or con-
structions have been brought out. The gradual increase in speed
has undoubtedly had much to do with the evolution of their various
types, just as in the case of the Westinghouse evolution. One of
the most radical steps which the General Electric Company has
made in the past few years is in the change from the vertical to the
horizontal type of machines. Presumably the very high speeds
which later came into use have had much to do with this change.
In the earlier turbo-generator practice, the speeds of the General
Electric Company's machines were relatively lower 'than the
PIG. 30— SAME MACHINE AS SHOWN IN PIG, 29 BEFORE WINDING
Westinghouse, presumably on account of the type of steam turbine
used. Many of the early rotor constructions were of the salient
pole type for four poles and higher. Gradually these were super-
seded by constructions leading up to a radial-slot type iti which
the slots were formed by teeth inserted in dovetail grooves in the
rim of the spider. This type was very similar in appearance to the
later types, except that the slots had overhanging tooth tips, thus
giving a partially closed slot construction. More recently, with
greatly increased speeds, this construction has been superseded by
solid forged cores with, shaft forged on, and with radial grooves
milled in the surface for the field winding. These latter rotors are
used largely in the horizontal type high speed machines,
DEVELOPMENT OF THE A.C GENERATOR 641
In the Allis-Chalmers construction, in the larger machines
having four or more poles, the earlier construction of the rotor
consisted of forged discs with through shafts. These discs had
radial slots for the windings very similar to the present construc-
tion of all manufacturers. The smaller machines generally had
PIC. 31—STATQR OP LARGE MODERN TURBO-ALTERNATOR
cores forged in a single piece with the shaft, and with radial
windings. As regards methods of ventilation, both the General
Electric and Allis-Chalmers Companies went through a course
of development leading up to their present practices. "
As regards parallel operation, turbo-generators have been
particularly free from this old time difficulty, due largely to the
uniform rotative effort of the steam turbine, and partly to the high
flywheel capacity of the turbo-generator and turbine rotors, which
tends to limit any speed oscillations, due to the governors, to a
relatively low period, such as would not tend to accentuate the
hunting action in the generators themselves* Moreover, in those
rotors which have been built with solid cores or of thick plates, the
solid material tends to act as a damper circuit. As a consequenoe,
hunting in toto-gaaemtosrs, or <3ttfficulties ia parallel nmnaag,
have been eattremely rare*
642 ELECTRICAL ENGINEERING PAPERS
INDUCTION TURBO-GENERATORS
This type of turbo-generator has been proposed commercially
a number of times during the past ten years, and a few installations
have been built. The first of any importance, consisting of a 1 250
kilowatt generator of 30 cycles, 1 800 r.p. m., two poles, was in-
stalled in the plant of the Baltimore Copper Smelting & Rolling
Company. This generator was a true polyphase induction motor,
direct connected to a steam turbine. The construction of the
generator was exactly the same as would have been used at that
time in a two-pole, 1 800 r. p. m. induction motor of the same
capacity. The entire load of this machine consisted of a 1 200
kilowatt rotary converter connected directly to the terminals of
the generator. The generator and converter were brought up to
speed separately and the rotary converter, with its field excited,
was connected directly to the generator and furnished the excita-
tion for the generator. There was no other synchronous apparatus
in circuit except the converter.
Several years ago, a number of much larger induction gener-
ators were built by the General Electric Company for the Inter-
borough Rapid Transit Company of New York City. These
machines are of 6 000 k.v.a. nominal capacity and operate in
parallel with the 11 000 volt, three-phase, engine-type generators
previously installed in the same power house. The engine-type
generators furnish the excitation for the induction generators. The
entire load of this station is represented by rotary converters.
There have been no prominent instances of the use of induction
generators for other than steam turbine drive. Apparently this
type of generator has no very wide field.
CONCLUSION
This history is admittedly far from complete, in that it has
not mentioned the work of some of the earlier, and also some of
the later manufacturing companies. The field is far too large to
permit everything to be covered. Moreover, no attempt has been
made to describe European constructions and developments in
alternating-current generators. It may be stated, however, that
in some very important features, European engineers antedated
the Americans, while in other equally important constructions
American designers were first in the field. As a rule, the represen-
tatives of the electrical manufacturing companies have been so
DEVELOPMENT OF THE A.C. GENERATOR CM
wide awake and ready to adopt new principles when they con-
tained any promise, that it is sometimes very difficult to give any
company or individual proper and deserved credit for being first
in any given development. Furthermore, no attempt has been
made to give credit to the various engineers who have been closely
identified with alternator development, for it would be impossible
to do justice, or give deserved credit to all of them.
THE DEVELOPMENT OF THE DIRECT-CURRENT
GENERATOR IN AMERICA
FOREWORD — This history is not merely a collection of facts or near
facts drawn up from old records or from second-hand leports,
but is an original story prepared by one who has been in the
thick of the battle almost from the early skirmishes, almost
thirty years ago. This, therefore, might be called a reminis-
cence, as well as a history. Being written almost entirely from
personal observation and experience, obviously it cannot be
considered as a complete history of direct-current generator
and motor development, but probably no other individual
in the country could write as complete an account of the de-
velopment, from his own observation and contact with the
work itself. This subject, broadly considered, should cover all
kinds of direct-current rotating machines, including constant-
current arc lighting generators, unipolar generators, etc. How-
ever, as the development of the railway motor is to appear in a
separate article, and as the constant-current generator has now
become commercially obsolete, or practically so, the scope of
the following article is limited to the development of the con-
stant-potential generators and motors,
This article was first published in the Electric Journal. —
(ED.)
HE history of the direct-current machine goes so far back that
-*• it is not within the scope of this paper to cover the earliest
developments. Many of the earliest machines were of the con-
stant current type for series arc lighting, Doubtless the peculiar
types which appeared in the constant current arc machines im-
pressed themselves upon the early constant potential generators,
for these latter were about as numerous in type and construction
as the arc machines. One of the characteristic features in the
early direct-current design was the radical differences in construc-
tion of the machines built by different designers or manufac-
turers. In fact> every designer appeared desirous of getting out
a new type which could bear his name. In consequence freak
designs, from the present viewpoint, were much more common
than those built upon sensible principles as understood to a
limited extent in those days* Real development toward the
present almost universal standard types did not take place until
the early "cut and try'1 methods of design were superseded
partly, or wholly, by calculations based upon the principles of
the electric and magnetic circuits.
Aside from the desire of each particular designer to have his
name connected with some new or special type of machine, many
645
646 ELECTRICAL ENGINEERING PAPERS
of the freakish characters of these early machines were due prim-
arily to an incomplete or wrong conception of the magnetic
circuit. As soon as the magnetic circuit became sufficiently well
ttnderstood to permit fairly accurate calculations of the magnetic
conditions, then the design of direct-current machines began to
take a definite trend toward certain constructions, When the
"figures*1 showed that a certain construction was magnetically
better, and considerably cheaper, than other known constructions,
the manufacturer naturally favored it, In the direct-current
machine, as in other types of electrical apparatus, the real develop-
ment and eventually the standardization of general types was a
result of the development of the calculating engineer as distin-
guished from the experimental and the "cut-and-try" designer.
From the present viewpoint, some very absurd constructions
appeared in the early machines. There were some very ponderous
arguments put forward for and against such construction, both
sides usually being wrong according to our present ideas. For
example, the early Edison bipolar field construction used two^or
more magnet cores attached to each pole piece, each core carrying
a field winding. Other manufacturers pointed out the absurdity
of such field construction, but as a rule, they did not recognize that
they were using, in many cases, similarly absurd magnetic condi-
tions. Two magnet cores per pole piece, or per pole, were found in
the " Weston" type, as shown in Fig. 1-&, and in the " Brush " or
later ' ' Short " type ; and each magnet limb carried its own exciting
coil, just as in the early Edison machine. This peculiar Edison
construction was soon abandoned, while the same feature was
retained for some years afterwards by many other manufacturers,
while they were still laughing at the Edison absurdity.
THE BIPOLAR GENERATOR
The first tendency toward any very definite types for general
use appeared in railway generators. There were then four leading
types of railway equipment, namely, the Edison with the Sprague
motor system, the Thomson-Houston, the Westinghouse, and the
Short manufactured by the Brush Company, Each of these com-
panies put out its own type of bipolar railway generator.
The Edison railway generator was practically a duplication
of the Edison lighting generator. The general arrangement of the
magnetic circuit was as shown in Fig. l-£. The field cores, yoke
,and pole pieces were usually of wrought iron. The construction
DEVELOPMENT OF THE D C GENERATOR
647
was comparatively massive, . The armature was of the surface-
wound, two-pole " drum " type, and hand wound. On some of the
earlier generators, copper brushes were used, but carbon brushes
were adopted later. Many of these machines were compound-
wound, the same as in present standard railway practice.
Occasionally some very weird engineering was used in the
early days in connection with compound windings, when operating
two or more machines in parallel. For instance, in one railway
plant of about 1889, which the writer examined personally, the
machines were properly installed as far as armature and field leads
and equalizer leads were concerned, but the main ammeters were
connected in the series coil circuits, beyond the equalizer leads, so
that they indicated the current in the series coils and not in the
armature. Moreover, each series field was provided with an ad-
justable shunt so that the currents of the different series coil cir-
cuits could be properly equalized. A very noticeable characteristic
of this plant was that some of the armatures heated and sparked
FIG. 1— EARLY GENERATOR FRAMES
A— The Edison type. B— The United States (Western) type. C— Later Bdiaon type, xrith
magnetically insulated base. D — The Thomson-Houston type.
much more than others and had to be rewound frequently, while
others never had to be rewound. The engineer in charge was much
worried over this situation until the writer, in discussing the in-
stallation of a Westinghouse generator in this plant, jokingly
asked him whether he wanted the ammeter of the Westinghouse
machine placed in the armature circuit, or in the series field
circuit. The engineer immediately "saw something," for over
night he revised the arrangement of his existing circuits, although
the former arrangement was in accordance with the manufac-
turer's drawings. This case is cited simply as an illustration
of the mistakes which were not uncommon in those days, and
were not confined to any one manufacturer. , .
648 ELECTRICAL ENGINEERING PAPERS
The Edison type of generator had one serious handicap from
the magnetic standpoint, namely, the pole pieces had to be in-
sulated magnetically from the bedplate, as indicated in Fig, 1-c.
This insulation was of some non-magnetic metal, such as zinc or
brass. It had to be of considerable thickness to prevent undue
shunting of the magnetic field, for this shunt path was in parallel
with the air-gap between the armature and field, which was
usually quite long, due to the heavy surface windings on the
armature core. This Edison type of machine, however, survived in
railway work as long as the bipolar type lasted.
One of the early Thomson-Houston constant potential gener-
ators was modeled after the characteristic Thomson-Houston arc
generator. It had a globular type armature, and the general ar-
rangement of the field type armature, and the general arrangement
of the field structure was similar to that of the arc generator.
This machine had a demagnetizing or "compensating'* coil over
the armature, with a view to compensating for armature reaction.
Apparently, this machine was used but little, if at all, in railway
work. The principal type of Thomson-Houston generator for
railway work was practically equivalent to the Edison machine
turned upside down, Fig. 1-rf. One of the best known machines
of this type was designated as the "D-62." This had a normal
rating of about 80 horse-power, or 60 kilowatts. Magnetically
the construction of the machine was superior to the Edison bi-
polar, in that the pole pieces, being at the top of the machine, did
not have any undue leakage to the supporting parts. The arma-
ture of this machine, like the Edison bi-polar, was of the drum
type, with the coils wound on the surface by hand. Some of these
machines also had "compensating " coils over the armature. This
machine was in great repute at one time, and was undoubtedly a
good operating machine, for those times. Like the Edison, the
Thomson-Houston machine was belt-driven. The writer was
much impressed back in the 90's, upon seeing a generating station
containing what was said to be 80 of these D-62 machines in one
generating room, all belt-driven from a system of line shafting
overhead. The forest of belts was exceedingly impressive. Like
the Edison, this type of generator persisted as long as bi-polar
generators were used in railway work.
A third type of bi-polar generator which was used in the early
railway work, was the " Weston" type, built by the United States
Electric Co. (controlled by the Westmghouse Electric Co.) Or-
DEVELOPMENT OF THE D C. GENERATOR
G49
iginally, this type of machine was arranged with horizontal mag-
nets, as indicated in Fig. 2-a. In the smaller machines the bear-
ings were carried by bronze brackets connecting the pole pieces.
In larger machines, separate pedestals carried the bearings.
In the railway generators, most of the machines of this type were
arranged with vertical instead of horizontal magnets, as shown
in Fig. 2-fe. Separate pedestals carried the bearings in these ver-
tical machines. Like the Edison and Thomson-Houston machines,
above described, this United States machine had a surface-wound,
drum type of armature, hand wound. This bi-polar railway ma-
chine was used to a less extent than the Edison or Thomson-
Houston machines, because the Westinghouse Company did not
get into electric work as early as the Edison and Thomson-
Houston Companies. However, this type persisted as long as any
of the other bi-polars.
A fourth type of bi-polar generator which was used exten-
sively in railway work, was the " Short " generator. This was
modeled after the general lines of the Brush arc generator, the
Short railway system being manufactured by the Brush Company.
FIG. 2— EARLY GENERATOR FRAMES
A— The United States (Weston) type, with horizontal magnets. B— The United States
(West on) type, with vertical magnets. O— The Short (Brush) type,
Like the Brush arc machine, the Short railway generator had a
ring armature with the armature coils lying between teeth on the
two side faces of the armature core, the pole pieces being presented
toward the sides of the armature. The armature, therefore, was
really of the "disc" type. The field magnets were arranged on
each side of the armature, just as in the Brush arc machine. The
commutator was placed outside the frame on one end of the shaft
aad the armature leads were carried down radially from the ar-
mature winding to. the shaft arid along the shaft to the commut-
ator* The whole construction of the armature was very awkward*
650 ELECTRICAL ENGINEERING PAPERS
from the present viewpoint. The general construction is in*
dicated in Fig. 2-c. The armature required a non-magnetic spider
as was the case in all bi-polar ring armatures. Possibly one of the
worst defects of this type of machine was the liability of a strong
side pull due to inequality of air-gaps on the two sides of the ring
armature. Any inequality meant an unbalanced magnetic pul]
with a tendency for an axial movement of the shaft. Thrust
bearings were necessary to prevent this. In this machine were
evidences of the later slotted armature construction. However,
it is questionable whether the armature teeth on these early Short
generators were designed primarily for magnetic purposes or for
mechanical reasons. They did not constitute a toothed armature,
as we design it nowadays. However, the machine must have
acted, to a certain extent, as a toothed type. Like all the others,
this machine was belt-driven. It also persisted as long as the bi-
polar machines were used for railway service.
From the above it may be seen that all of the leading bi-polar
railway generators were quite different from each other in their
general appearance and construction. There were many warm
discussions regarding the merits and demerits of each type. When
equipped with carbon brushes, all of them operated reasonably
well. All of them ran rather hot in the armature, due to the fact
that little provision was made for ventilation. In this respect the
Short armature was probably better than the others, as it was of
a fairly open ring construction. Being surface-wound in practic-
ally all cases, the commutation was not difficult, as the self-induc-
tion was low. When the multi-polar types of railway generators
came in, there were lots of " stand-patters " who insisted that the
old two-pole machines were good enough, and that we were foolish
in trying to do away with them.
In these various types of bi-polar generators, the Edison was
carried up to ISO kw capacity, or possibly somewhat larger; the
United States was carried up to ISO kw capacity. Apparently
the Short and Thomson-Houston were not carried up to such
large sizes, the Thomson-Houston "D-62" being the "crack"1
machine, to the end of the bi-polar dynasty.
There were a number of other railway generators at this time
in this country, but they were not as well known as the above and
did not persist as long, presumably because the railway systems of
which they usually formed a part, did not persist.
DEVELOPMENT OF THE D C GENERATOR 651
MULTIPOLAR TYPES
About 1890, the Thomson-Houston Company, in bringing out
a larger capacity railway generator, adopted a multipolar design,
in which an external octagonal-shaped yoke supported four in-
ternally projecting poles, each of which carried a field winding.
This arrangement, shown in Fig. 3-a, was thus an approach to the
present almost universal type of field construction. The armature
was of the ring type, with four circuits, one per pole, and there
were four brush arms and four sets of brushes on the commutator.
This machine was separately excited, an exciter being provided.
The opinion was somehow spread broadcast that separate excita-
tion was necessary in general, and for parallel operation in par-
ticular, in multipolar generators. No real explanation was forth-
coming as to why this was so, but apparently almost everybody
accepted it as a fact without explanation. Shortly after the intro-
duction of this multipolar type of generator, the writer examined
several such machines which had just been installed in the Du-
quesne Traction power house in Pittsburgh. The conclusion
A B
FIG. 3— EARLY MULTIPOLAR GENERATORS
A — Octagonal frame. B— Cylindrical frame.
drawn was that separate excitation was necessary only because
the machines were not worked sufficiently high on the saturation
curve to give stability when self-excited. With the surface-
wound armatures and consequent large air-gap, together with the
multipolar construction, a relatively low saturation was used ap-
parently. Possibly the writer drew a wrong conclusion in this
case, but nevertheless he made up his mind that self-excitation
was just as practicable in multipolar railway generators as in
bipolar.
652 ELECTRICAL ENGINEERING PAPERS
As stated before, the United States bi-polar machines were
furnished by the Westinghouse Company for railway work.
These were built at the United States Works at Newark, New
Jersey. But early in 1890, the Westinghouse Company con-
sidered the construction of larger generators at its Pittsburgh
shops, and a contract was taken for a 250 horse-power generator
for railway work. The electrical design for this machine was
prepared by the writer. A cylindrical external field ^with in-
wardly projecting poles, as shown in Fig. 3-fc, similar to the West-
inghouse alternators of that time, was chosen as the ideal type.
The four poles were laminated and were cast into the yoke similarly
to the Westinghouse laminated field alternators of that date.
This field was also a close approach to the present standard con-
struction, being a slight step ahead of the Thomson-Houston
machine described above, in the use of laminated poles. The
armature was of the ring type, surface-wound. At this time the air
was filled with talk that the ring armature was the coming type.
There were some good reasons for this. In the older bi-polar
drum armatures, most of the over-heating had been in the piled
up, unventilated end windings. As the ring armature had no
end windings to speak of, it was naturally supposed that all
troubles from heating would be overcome by the adoption of this
type. Thus the last weak point in the railway armature was sup-
posed to be done away with.
Being convinced that multipolar generators would operate
satisfactorily when self -excited, if worked high enough on the
saturation curve to give stability in excitation, the writer deliber-
ately designed this first four-pole machine for self -excitation, but
this was not known to anyone but the Company's superintendent
Mr. Albert Schmid, who was fully in accord on this point. How*
ever, when the machine was about completed and ready for test,
the information leaked out that it had been designed for self-
excitation, which, of course, was entirely contrary to all good
and accepted practice. The writer was criticised from all sides
for his temerity and for his lack of good judgment. However, the
machine was put on test, and did operate in an entirely satisfactory
manner when self-excited. But some of the wise ones still shook
their heads, for we were violating all known "laws." Neverthe-
less, we stuck to self-excitation, and it is still with us.
When testing this first machine, considerable new experience
was obtained. For instance, when moiling at normal voltage,
DEVELOPMENT OF THE D C. GENERATOR 653
the machine was dead short-circuited across the outside terminals
with a somewhat surprising display of fire-works. Also when,
after this short-circuit test, the surface-wound ring-armature
winding was found to be shifted about two inches circumferentially
at certain points, some of us had doubts regarding the desirability
of this type of winding. This was one of the points that led to the
slotted armature construction described later.
This first Westinghouse multipolar machine was considered a
"giant," and railway people all over the country were invited to
witness its operation in the Company's Pittsburgh works. Quite
a number of visitors did come long distances to see this 250 h.p.
machine, and some comments were made that this was probably
the upper limit in size that would ever be made. It was, at that
time, hard to conceive that any electric railway would ever need
anything larger than this capacity. Moreover, it was thought by
some that the limit in belting had been reached. As everything
was belted in those days, it was difficult to see that any other
method of drive was possible. Nevertheless, this machine was
quite a wonder, compared with what had preceded it.
SLOTTED ARMATURE TYPES.
Several machines of this type and capacity were built and put
out* However, the writer was not entirely satisfied with the ring
winding in particular, nor the surface winding in general. At
this time, in alternating-current work, there was a strong tendency
toward "toothed" armature constructions, with the windings
completely embedded below the surface of the core. These alter-
nating-current armature types with one tooth per pole did not
lend themselves to direct-current work, but the idea of embedding
the windings persisted. In the summer of 1890, while scheming on
a new railway motor, a slotted armature construction was worked
out by the writer, with a view to improving the magnetic condi-
tions so greatly that a slow-speed single-reduction railway motor
would be possible. The calculations for the magnetic condition
(crude as they were in those days) showed such astonishingly good
results that the same construction was considered in connection
with the design of a large Westinghouse slotted armature railway
generator which in tnany ways may be considered the forerunner
of present practice. These calculations on the railway motor
resulted in the well known Westinghouse No, 3 single reduction
motor, which was practically 'the f orefatlter of the present tmi*
654 ELECTRICAL ENGINEERING PAPERS
versal type of railway motor, This was not actually the first single
reduction motor, but was the first which anyways nearly ap-
proached the present type.
It was while making the original calculations on the slotted
armature for the single reduction motor that the "two-circuit" or
"series" type of armature winding was devised for multipolar ma-
chines. In working out the railway motor, it soon became evident
that a four-pole design was necessary. With any of the then known
armature windings, either four-brush arms were required on the
commutator, or the commutator had to be cross-connected at
every bar, in order to allow the use of two-brush arms only. The
writer deliberately set about to devise an arrangement of connec-
tions which would allow the use of two-brush arms on a multipolar
winding without any other cross connections than the normal con-
nections of the winding. The two-circuit winding was the result,
and the law of the winding was worked out for various combina-
tions of poles, etc., while still closing on itself properly. This
winding was included in the design of the trial single reduction
motor then being designed. Question was raised regarding this new
winding, when it was first proposed, by those who appreciated that
something radically new was involved in its use. The writer had to
"swear up and down" that it was absolutely correct in principle,
even if it was new and untried, but he apparently convinced the
others more by his vehemence than by his theories, for most people
in those days had very little conception of the theory of armature
windings. However, when the first single reduction railway motor
armature came on test, the theory proved to be all right — at least
the armature was all right and had but two brush arms on a four-
pole machine. This, as far as the writer- knows, was the original
two-circuit multipolar winding in this country. Application for a
patent was refused however, on the basis of a certain, until then
unknown, foreign patent — that is, unknown as far as the writer
and any of his colleagues were concerned. It may be worth mention-
ing that at the time this two-circuit winding was first used, the
criticism brought against it was that it was entirely too com-
plicated to be adopted generally. This is interesting in view of
the fact that at the present time this is our simplest direct-current
winding, and it is used probably to a greater extent than all other
windings together. Prophecies in those days were no more reliable
than they are at present.
DEVELOPMENT OF THE D.C GENERATOR 655
Returning to the slotted type of railway generators, as stated
above, it was decided to build an armature of this type. Slotted
armatures had previously been used in America by the United
States Company and others on comparatively small capacity
generators and motors, but apparently on nothing "within gun-
shot " of the size which we were contemplating. Therefore, opinions
were obtained from a number of then eminent engineers who had
had experience of some sort with slotted armatures. All opinions
were unanimous that we could not make a 250 horse-power rail-
way armature of the slotted type which could commutate suc-
cessfully without rocking the brushes with change in load. This
was very discouraging, but it was then decided that this was pos-
sibly a case where everyone was wrong, and that we had better
build one armature in order to obtain some positive information.
This new railway armature was designed with 95 slots and 95
turns and 95 effective commutator bars, the new two-circuit drum
winding being used, although it was intended that there should be
four brush arms. As 95 turns were all that could be used, with the
desired saturation of the existing field frame, and as there did not
seem to be enough bars for a four-pole, 525 volt machine, the
actual number of commutator bars was made 190, but only every
other bar was connected to the armature winding. The intervening
bars were idle (or ' 'dummies ")> and really constituted broad insul-
ating or separating segments between the active bars. The
brushes covered practically four bars, so that they touched two
active bars all the time.
There was considerable discussion regarding the type of ar-
mature slot to be used, namely, whether it should be partially
opened at the top or should be entirely closed* It was finally de-
cided to make the slots entirely closed, on the principle that the
dosed slot would be the ideal one if it prove satisfactory, and if
it didn't prove satisfactory, the slots could then have openings cut
in the top, without rewinding.
When this first machine came on test^ some most remarkable
results were obtained, due apparently to both the idle segments
in the commutator and the entirely closed armature slots, Spark-
ing was present at all times, even with only the exciting current as
a load. Rocking the brushes was tried for curing this, but when
any considerable load was carried uo point of sparkless commut-
ation could be fouaxi However, a curious feature of the results was
that the brushes cottld be locked practically anywhere cm the
656 ELECTRICAL ENGINEERING PAPERS
mutator without causing flashing. Copper brushes were tried with
like results. Also, copper brushes were tried behind the carbon
brushes, and, in some cases, such heavy local currents were gener-
ated between the copper and carbon brushes that the brushes got
red hot over almost their full length, and yet we did not produce a
single flash from this machine, although we explored around over
almost the entire commutator with the experimental brushes.
Mr. Chas. F. Scott and the writer spent almost an entire night
experimenting with the brushes and brush-holders, with our faces
at times almost against the commutator and brushes, where a
flash would probably have caused permanent injury to us. In
view of the vicious flashing which occured at times on later ma-
chines, it is still somewhat of a puzzle why this first machine was
so absolutely non-flashable. Apparently, the ' ' dummy ' ' commut-
ator bars should receive most of the credit for this result.
Finding that the closed slot construction was a failure, the
armature slots were then cut open as wide as possible while still
retaining sufficient overhanging tips for holding the armature
conductors in place. The first test after this showed a marvelous
improvement. The armature now would carry from no-load up
to considerably above its rated load without serious sparking and
without shifting the brushes. The machine was then put on
exhibition and many prominent people saw it put through its
" stunts." The only serious defect that developed was in slight
spotting or burning of alternate commutator bars. In an attempt
to overcome this, each idle bar was connected to an adjacent
active bar, thus reducing the total number of bars to 95. Under
this condition the spotting was stopped, and the commutation ap-
peared to be just as good as before; therefore it was decided that
95 bars were sufficient for a four-pole, 525 volt railway generator
of this general construction.
This slotted armature railway generator turned all future
construction of large machines toward the slotted type. However,
this first machine by no means fixed the final design of this type of
armature, but merely set the general type. Many variations ap-
peared in the following years, but all contained the slotted con-
struction and the drum type of armature winding. As far as the
armature itself was concerned, the principal variations were in the
shape of the armature slots and in the form or construction of the
armature coils. Furthermore, some experience was required in.
order to determine the best proportions of armature teeth, air-gap,
DEVELOPMENT OF THE D.C GENERATOR 567
etc., in order to produce good commutation over a wide range of
load without brush shifting, a very necessary condition in railway
work. While in fact this first large generator did not require brush
shifting, yet the reasons for this were not fully appreciated at the
time, and therefore the good results obtained were, to a certain
extent, accidental. The right conditions were aimed at in making
up the design, but as it was largely a question of how far to carry
certain proportions, it was partly accidental that these conditions
were carried just far enough to obtain such satisfactory results.
In this first machine the armature teeth were made comparatively
thin and short and were saturated to an excessive degree. Also,
the air-gap was purposely made quite large, with the idea that the
air-gap and tooth saturation together would require very high
magnetizing ampere-turns compared with the armature ampere-
turns, which was considered as a very desirable condition for com-
mutation. However, the extremely beneficial effect of high tooth
saturation in holding the brush lead constant was not then fully
appreciated. This was discovered when a somewhat larger machine
was built a few months later. In this larger machine the tooth
saturation was considerably lower than in the first armature, al-
though the air-gap ampere-turns were comparatively high. This
later machine was found to be much more sensitive to shifting of
lead than the former machine. A careful study was made of the
influence of tooth saturation in holding the lead constant, and from
this study a scheme for saturating the pole face instead of the
armature teeth was suggested, which will be referred to later.
The Thomson-Houston earliest slotted type railway generators
were also subject to change in lead, but evidently the cause of the
difficulty was soon discovered, for the later machines were not so
sensitive in this regard. Also, apparently their earlier slotted
machines had weaker fields compared with the armatures than was
the case with the Westinghouse machines.
The early Westinghouse slotted armatures for railway gen-
erators all had partially closed slots, while some of the early
Thomson-Houston machines had rectangular open slots and others
had partially closed slots. The slot construction depended, to a
certain extent, upon the the type of armature winding used. The
early Westinghouse machine had only two round conductors per
slot, which were threaded through two stout insulating tubes made
of rolled up paper and shellac, as shown in Pig, 4-a, These tubes
had walls of 1-16 to 3-32 of an inch in thickness. The winding
658 FLECTPICAL ENGINEERING PAPERS
consisted of either round solid conductors or of twisted cable,
threaded through these tubes. The conductors were first cut in
lengths corresponding to one complete turn. All the conductors of
the lower layer were threaded through the lower tubes and then
bent down at each end in an involute shape, as indicated in Fig.
4-i and c. At the front, or commutator end, the conductors
extended just sufficiently to furnish the front end connection to the
commutator. At the rear end, the conductors extended far enough
to furnish the return or upper layer. The lower layer, after being
bent down at each end to an insulated support over the shaft, was
banded or clamped down solidly to the support. The extended
rear ends of the coils or conductors were then bent outward to the
periphery of the core, in an involute form and were shoved through
the upper layer of tubes, and carried directly to the commutator,
PIG. 4— EARLY WINDING SCHEMES
thus completing the winding. The various steps in this construction
are indicated in Fig. 4-d In the smaller machines, that is, from
about ISO kw down, solid conductors were used, these being in
some cases as large as No. 2 B,& S. gauge wire. The maximum size
of solid conductor was determined by the ability of the winders
to handle it without undue difficulty. For larger sizes, twisted
cables were used, made up of fairly large wires, such as No. 10 or
No. 12 B. and S. gauge. Considerable stiffness was preferred itx
order to give mechanical strength to the winding. This type of
armature winding was used for a number of years, and was some-
times modified to the extent of four, or even six tubes and con-
ductors per slot, arranged radially. Also, in some cases, the section
of the tubes was made elongated to take two or three parallel con-
ductors forming one turn.. In the larger machines with this
winding, with the very high tooth inductions used, undoubtedly
the use of cable materially lessened eddy currents in the conduc-
tors. This, however, was not a prime reason for the use of cable,
ease of winding being the principal reason-.
DEVELOPMENT OF THE D.C GENERATOR 650
Some of the early Thomson-Houston slotted armatures had,
open slots, while others had partially closed slots, of rectangular
shape in both cases. Straight copper straps or bars of rectangular
section were either laid in or shoved through the slots from one
end, depending upon whether the slots were of the open or partially
closed type. Separate strap end connectors of the involute type
were riveted or soldered to the armature bars at each end. This
general construction is shown in Pig. S-a. The writer does not
know whether this was the earliest Thomson-Houston winding
for slotted armature generators, but it was, at least, a very early
one. In some cases, two or even three bars were placed side by
side in one slot, forming two or three separate turns. This general
type of winding was retained by the Thomson-Houston Company
(G. E.) for several years.
PIG. 5— EARLY COIL FORMS
FORMED COILS
After two or three years' use of the Westinghouse "shoved-
through" type of armature winding above described, the develop-
ment of a type of armature coil, which could be com-
pletely formed and insulated before placing in the slots,
was taken up. Various schemes to accomplish this were under-
taken* The first one attempted consisted in forming the rear end
and the two straight parts of the coil as a complete coil which was
then shoved through the partially closed slots from the rear end,
the front end connectors being formed of copper strap which were
then riveted or soldered on, after the conductors had been shoved
through the slots, as shown in Fig. 5-b. One armature of the sort
was actually constructed. It was appreciated however that if open
armature slots were used, instead of partially closed, the entire coU,
including both front and rear end connections, could be constructed
in one piece* This construction was then tried out and adopted, as
illustrated in Pig. 5-c, It may be noljed that both end windings,
in this early one piece coil, were of the involute type. This con-
struction was retained by the Westiugbotiae Company for some
years, and was eacteaded to tv<ro, three, and even four and five,
660 ELECTRICAL ENGINEERING PAPERS
separate conductors side by side in one slot. Then gradually the
involute winding at the front end was replaced by axially ar-
ranged end windings between the armature core and commutator,
just as in present practice. The rear end was later straightened
up in the same way, so that the present type of winding was thus
attained.
Incidentally, it should be mentioned that the completely
wound coil, with involute end connections, was developed and
applied by Rudolph Eickemeyer, to surface-wound armatures,
several years previous to this. In this, as in several other things,
Eickemeyer was considerably in advance of his time. In some of
the earlier armatures with open slots, the windings embedded in
the armature core were supported by bands over the core. This
appeared to be the usual Thomson-Houston practice, (some of
the above developments occurring during the formation of the
General Electric Company from the Thomson-Houston and
Edison Companies). With open slots, the preferred Westinghouse
construction consisted of fiber wedges over the embedded parts of
the winding, but the writer does not know whether this construc-
tion originated with the Westinghouse Company or not* There
was considerable discussion as to the relative merits of the two
arrangements, but apparently both were entirely successful.
END WINDING SUPPORTS
As regards supports for the end winding, the early shoved-
through winding on the Westinghouse machines, shown in Pigs.
4-fc and c had good supports at each end against centrifugal
force. The slots being partly closed, this type of winding the re-
fore had no bands or wedges on any part of it. With the develop-
ment of the strap coil, as shown in Pig. 5-c, it soon developed
that in high-speed machines the rear end of the winding required
some sort of support. This was first made in the form of bronze
end bells, which braced the end winding, both axially and
radially, as shown in Fig. 6. The front end winding had no
support. However, in the early years of this winding, very low
speed armatures were the rule, for this was the age of engine-
type generators, which will be referred to more fully. Except iti
rare cases, the armature end connections were rigid enough to be
self-supporting without belts or bands. When rotary converters
and motor-generators came into general use, with their very much
higher peripheral speeds, the end bell over the rear end was
eventually replaced by axial end windings with heavy bands, as in
DEVELOPMENT OF THE D.C. GENERATOR
(561
present practice. The Thomson-Houston or General Electric
Company preceded the Westinghouse Company in the use of
bands on the end windings, probably in part because their built-up
end windings had more need for some external support. Also, as
they abandoned the built-up end construction in favor of complete
coils, they changed to the axial construction on the rear end,
which also necessitated the use of bands. Thus both companies
eventually came to the same construction, through different
courses of development.
PIG. 6— METHOD OF BRACING THE END WINDINGS BY A METALLIC
END BELL
The writer has gone into this history of the slotted construc-
tion and the armature windings, because these constitute probably
the most radical points in the history of direct-current generator
design.
OTHER MULTIPOLAR TYPES
Something should be said regarding other types of multipolar
generators developed during this time. The Edison Company did
not go into the multipolar design for railway generators, as far as
the writer knows, for about this time, the Thomson-Houston and
Edison Companies were combined into the G. E, Company. The
Edison Company, however, had designed and built some large
low-voltage generators for the Edison licensee companies. These
had large cylindrical external fields with inwardly projecting poles
of cast steel or wrought iron. The armatures were 'of the ring type,
surface wound, and were fitted with radial commutators on one
face of the armature core, the commutator bars forming part of
the armature winding* These machines, as a rule, used metal
brushes. They were manufactured up to quite large capacities
by the General Electric Company in continuing the Edison design.
The Short bi-polar type of railway generator was simply ex-
panded into a multipolar type, having the same general con-
662 ELECTRICAL ENGINEERING PAPERS
structional features. This apparently presented no advantage
over the Short bi-polar machine, except that it permitted machines
of larger capacity to be built. At one time it was claimed by some
authorities that the Short multipolar generator was the coming
type. However, it was apparently too expensive, for later, in or-
ganizing the electrical work of the Walker Company, Prof Short
abandoned this construction in favor of one similar to the Westing-
house and G. E. machines.
ENGINE-TYPE GENERATORS
All the earlier generators were of the belted type, This was
eventually carried up to comparatively large capacities in either
belt or rope drive, 500 kw machines being not uncommon. How-
ever, shortly after the slotted type of armature construction came
into general use, a tendency was manifested toward direct driving
from the engine. Once well started, direct driving soon became
almost exclusive practice, except for extremely small units. Two
methods of direct driving were used about equally in the earlier
practice, namely, direct coupling of complete generator units to
the engines, and straight engine-type machines in which the gen-
erator armature was placed on the engine shaft. The former might
be said to be an adaptation of the belted type to direct driving.
The engine-type machine, however, might be considered a distinct
type, as the units were designed primarily in connection with the
prime movers.
Designers of direct-current machines rather welcomed the
engine type, even if it did make much of their former work ob-
solete, for the engine-type machine very much simplified some of
the problems which had been encountered in the larger capacity
belted machines. For example, the commutation problem became
very much easier, due to the much lower speed, larger commut-
ators, etc. The heating problem was also temporarily solved, for
the engine-type machines were comparatively large and massive
for a given output, and thus could dissipate their heat rather
easily.
The direct-coupled and engine-type practice, once started,
came in rather quickly. The first railway units appeared about
1892, and by 1893 they had made great progress commercially.
A number of large engine-type and direct-coupled railway gener-
ators were exhibited by various manufacturers at the Qhicag,
Worlds Fair in 1893. The power house for the Intramural Rail-
DEVELOPMENT OF THE D C. GENERATOR 0(33
way at the Fair contained practically only such machines, if the
writer remembers rightly. The Worlds Fair engine-type generators
were presumably all exhibition machines; however, they were
but little, if any, ahead of the times for, during the same year
both the Westinghouse and G. E. Companies contracted for a
number of very large machines of the engine type. It might be
said therefore that the engine-type railway generator was well
established commercially, in 1893, or within about two years after
the first slotted armature for large railway generators was devel-
oped. Without the slotted construction, it is doubtful whether
such rapid and enormous development could have taken place.
There was one exception to the slotted armature construction
in large machines for railway work, namely, the Siemens-Halske
generator, which was exploited in this country for several years
from about 1895. This was the well-known external armature
construction, in which a ring wound armature surrounded a
stationary multipolar internal field structure. The armature was
ring-wound, the inner surface cutting the field, while the outer
surface formed the commutator. The brushholder thus sur-
rounded the entire armature. When first introduced into America,
these generators used metal brushes, this being possible due to the
surface type of winding, low voltage per bar, wide neutral zone, etc.
However, in American railway practice, metal brushes did not
prove entirely satisfactory, especially in case of short-circuit, as
they burned, and burred and "welded" badly. Carbon brushes
were used later, but the general construction was not very suit-
able for such brushes, This type of machine as a whole was not
competitive with the rugged, well-protected armature and com-
mutator construction of other American makes, and it dropped
out when the American Siemens-Halske Company went out of
business. It is interesting, however, as a late survivor of the
surface-wound type of railway generator armature.
The engine-type construction in general soon spread into all
fields of electric generator work, such as lighting, electrolytic work,
etc., and was a standard construction for many years, before it
suffered a decline. In small lighting work, the type persists today,
but has now almost disappeared in railway work, due largely to
the general introduction of the polyphase alternating-current
system of generation and transmission of power, with conversion
to direct current by rotary converters and motor-generators. The
period ^of decline b^g&a about 1898 to 1900, whan large capacity
rotary converters began to take the field.
664 ELECTRICAL ENGINEERING PAPERS
When the engine-type practice was in vogue, some very large
units were constructed for comparatively low speeds — 1 000, 1 500
and 2 000 kw units at 75 to 80 r. p. m. were common, and quite a
number of railway units of 3 000 kw were built. For lighting service,
some units of still larger capacity were built.
The engine type machine in its prime was a magnificient piece
of apparatus. On account of its low speed, it was of comparatively
large dimensions for a given output. In the largest capacity, low-
speed engine-type generators, overall dimensions of 25 to 27 feet
were attained. This is very large, compared with present practice,
which is confined almost entirely to relatively high-speed machines
However, large as they were, they were midgets, both in size and
capacity, alongside some of the alternating-current engine-type
generators at their maximum. The latter were constructed up to
capacities of 5 000 to 6 000 kw compared with 3000 kw for
direct current, while the engine-type alternators attained overall
diameters as high as 42 feet. Incidentally, as regards capacity alone,
the race between alternators and direct-current machines has been
very much one-sided, almost since the polyphase system became
thoroughly commercial, the earliest Niagara generators (constructed
in 1893), of 3 750 kw, being practically of as large capacity as the
largest direct-current machine ever built; while in later poly-
phase work, generators of the usual multipolar construction have
been built up to 17 000 kw, and turbo-generators up to 30 000 and
35,000 kw. Obviously, as regards marimum capacity, the direct-
current machine makes but a poor comparison, for reasons which do
not come within the scope of this paper. Nevertheless, this should
in nowise detract from the direct-current generator, as an engineer-
ing accomplishment.
In general, the engine-type constructions of different manu-
facturers were very similar, except in details. The principal dif-
ferences were in the way the field yoke was split, in the construc-
tion of the field poles and field winding, and in the details of the
armature winding, as already described. In the earlier Westing-
house machines, the field yoke was split vertically, so that the two
halves could be moved away from the armature in a direction at
right angles to the shaft. The G. E. construction, in general, was
horizontally split, and access to the armature was obtained either
by sliding the field parallel to the shaft or by removing field poles
or by lifting off the top half of the field. There was much argument
regarding the respective merits of these two constructions.
DEVELOPMENT OF THE D.C. GENERATOR 665
FIELD POLES AND WINDINGS
On the subject of field poles and field windings, something may
be said, because this part of the direct-current machine underwent
many modifications in type, materials, etc. In the early bi-polar
machines already described, the pole pieces and poles varied with
the different types. The Edison and T-H constructions used
wrought iron or cast steel in both the poles and yoke, as far as the
writer knows. The field cores in the Short machines were of wrought
iron or cast steel, and presumably similar material was used in the
pole pieces. All these machines had cylindrical magnet cores with
cylindrical field coils surrounding them. The United States
(Westinghouse) bi-polar machine had cast iron fields throughout.
The magnet cores were oval in shape instead of circular.
When the multipolar generators came in, various constructions
of poles and pole pieces were used by different manufacturers.
The Westinghouse Company used poles of rectangular shape, of
laminated steel, which were cast into the yoke. The field coils
were of rectangular shape and were slipped over the poles from
the air-gap end. The rectangular shape of magnet core and the
laminated construction has been retained throughout by the
Westinghouse Company in their multipolar generators, except
in some early, relatively small capacity belted and engine-type
generators, in which cast-iron poles were cast integral with the
yoke. These also were rectangular in shape.
Many of the other manufacturing companies, in their early
multipolar machines, used wrought iron and steel very extensively
in the magnet cores and pole pieces and, in some cases, in the yoke.
Frequently the magnet cores were made cylindrical, while the pole
pieces or caps were rectangular. The theory was that the cylin-
drical core was the most economical shape for both iron and copper.
This of course, was true where the armature diameter was the lim-
iting dimension in the machine and where, in consequence, there
was plenty of field space for use of the cylindrical poles. For a
given section of field iron, obviously the cylindrical type of core
and winding required more room rircumf erentially around the ar-
mature, than rectangular poles of equivalent section.
The solid pole face was not very objectionable on the eajrly
machines^ especially where the air-gaps were large, and the arma-
ture slots were relatively narrow. However, the tendency of design
was towaxd widecr armature slots with several bars side by side in,
each' slot, as this allowed considerable increase i# capacity for a
«66 ELECTRICAL ENGINEERING PAPERS
gjven armature diameter, and also the wider slot permitted better
oommutating conditions. Also, especially in engine-type machines
with many poles, the design tended towards smaller air-gaps
Consequently, conditions were soon reached where there was con-
siderable "bunching " of the magnetic flux in the pole faces, due to
the relatively wide armature slots". This meant loss and heating in
solid pole faces, especially under flux distortion with load. With
laminated poles, this heating was apparently very small, but with
solid poles it was sometimes excessive — so much so that, in
some cases, the mantifacturers of machines with such solid pole
tips would turn circumferential grooves in the pole faces to "semi-
laminate ' ' them In some cases, solid magnet cores were used with
laminated pole tips. The Bullock Company, like the Westing-
house, used laminated poles, but its successor, the Allis-Chalmers
Company, adopted solid poles in some of its large machines, but
eventually "returned to the laminated construction. The T-H
Company and later the G. E. Company used solid poles and pole
tips for many years. In many cases, however, their magnet cores
were rectangular in shape just as in present practice. Unlike the
early Westinghouse machines, the G. E, poles were bolted to the
yoke which was sometimes of cast steel and at other times of cast
iron, while the early Westinghouse poles were laminated and cast
into the yoke, as already described, the yoke being cast iron. Thus,
both constructions contained some of the elements of present
standard practice, which embodies laminated poles of rectangular
section, bolted to either cast iron or cast steel yokes.
In the earlier generators, the Crocker-Wheeler Company used
cylindrical poles with solid pole tips, but with somewhat larger
air-gap than used by other manufacturers, thus avoiding, to a con-
siderable extent, any undue losses in the pole faces.
FIELD WINDINGS
The construction of field windings is so closely related
to that of the pole pieces that a brief account of their
development may be given at this point. Practically all the
early field coils were wound in metal bobbins or shells. They were
usually very heavily insulated, both inside and outside. The metal
shells were first lined with paper or other insulation to a consider-
able thickness; the wire was then wound in, usually with much
paper or cloth between the layers, and thea the outside surface
was covered possibly }^ i&- deep with a finishing layer of rope.
The whole construction was a most excellent one for keeping in the
DEVELOPMENT OF THE D C. GENERATOR 667
heat. If a coil ran too hot, more copper and insulation were added,
instead of improving the heat dissipating and ventilating condi-
tions. Naturally, in following such lines, the field coils eventually
became very massive. Shunt field coils on railway generators were
not infrequently four or five inches deep. When one of these coils
roasted out it was usually found that the first half inch of wire next
to any heat-dissipating surfaces was usually in fair condition,
while deeper in the winding was progressively worse. To overcome
this, in some cases the field coils were made in two concentric parts
with a narrow space between. This was the first step towards im-
proving the ventilation.
In the construction of the early field coils, the writer ob-
jected often, and strenuously, to the enormous amount of insula-
tion embedded between layers in such coils, and also to the great
depth of insulation in the metal shells. This great depth in the
shells was due largely to the fact that the various parts of the
insulation were "butted" instead of being overlapped, so that
great thickness was required to give sufficient creepage distance
One early improvement was in the use of overlapped insulation at
the joints, which allowed a great reduction in thickness. Also, the
introduction of coils without metal shells, which followed from the
use of similar coils by the Westinghouse Company in railway
motors, allowed the outside surfaces to be insulated after the coil
was completed. This was another step in the direction of reduced
insulation, for this type of coil could be insulated more satisfactor-
ily and with less danger of bad joints, than when the shells were
used. But still enormous quantities of insulation were used between
layers. The writer arranged a " horrible example " of this one day
when tearing down a large field coil. The insulation between layers
was carefully piled up as the coil was unwound, until, at the finish,
the pile of insulation from the inside of the coil was several times
larger than the original coil, due of course to being loosely piled,
But it was hardly believable to the observer, that all that "stuff"
came from the inside of the coil. Gradually, however, it was
found that much of this internal insulation could be omitted. Its
only use originally was to prevent short-circuits between layers
while winding the coil, as the wire was hammered pretty hard while
winding, in order to take out the "bulge/*
In series field coils, originally the Westinghouse Company
used round wire for the woxding, and as the size of machines in~
creased, two or more wires, or two or more field coils, were
668 ELECTRICAL ENGINEERING PAPERS
leled. In all cases the series winding was placed beside the shunt
winding, and generally next the yoke in the earlier machines.
Later, strap, wound flatwise, was used in some cases; but about
1895 the strap on edge alternator field winding was developed,
and almost immediately the Westinghouse Company used this
same winding for series field coils. Incidentally, it may be men-
tioned that the writer applied for a patent on this edge-wound
field coil construction but, to his surprise, found that it had been
covered by a patent about 50 years before, in connection with
electro-magnets.
In the earlier Thomson-Houston (and G. E.) machines, the
field coils were wound in metal bobbins, and this construction was
retained somewhat longer than by the Westinghouse Company.
In many cases the series winding consisted of strap or ribbon, wound
flatwise, outside the shunt winding. The merits of this construc-
tion, compared with the strap-on-edge, were much discussed, but
apparently both were sufficiently good constructions for those
times.
As heat-conducting and radiating conditions and ventilation
became better understood, the outer insulation on the coils was
reduced materially, and precautions were taken to ventilate the
field wmdings more thoroughly. Series windings were better ex-
posed to the air, and shunt windings were, in some cases, sub-
divided in order to increase the effective ventilating surfaces. Also,
in view of the fact that, with heavy deep coils, the center portion
would be roasted out, while the outside part would be comparatively
good, practice gradually tended toward comparatively shallow coils,
arranged for good air circulation over them. In series coils and in
coirnnutating-pole windings, where comparatively heavy strap or
bar conductors are used, the individual turns are now separated by
air spaces in many cases. In other words, in modern design, low
temperatures are obtained not by piling on material, but by
improvements in heat dissipation.
COMMUTATION
The problem of commutation and the conditions which in-
fluenced it were of paramount importance in the early days. The
theory of commutation was understood crudely, and the conditions
which gave good commutation were more or less appreciated. It
was known that a surface-wound armature should commutate bet-
ter than the slotted type, with the same number of turns per com-
DEVELOPMENT OF THE D.C GENERATOR 669
mutated coil, and with the same current per coil. It was well under-
stood that embedding the coil in the slot would increase the self-
induction, and thus render commutation more difficult. The
advantages of the slotted construction were pretty well appreciated
before its adoption, but everybody feared the commutation. It
was not appreciated that, in adopting the slotted construction, the
number of armature turns in general, and the number of turns in
series per coil in particular, could be reduced sufficiently to over-
come the inherently higher self-induction of the slotted construc-
tion. As soon as the slotted construction proved practicable in
large machines, a new era began in the commutating problem.
Designers studied and analyzed the comtnutating conditions and
limitations much more closely than ever before, and many tests
were made solely for the purpose of getting commutation data.
In this study it was soon determined that high saturation of the
armature teeth was beneficial in maintaining a fixed lead at the
brushes. At that time, in preparing a brief written analysis of
commutating conditions in slotted machines for Mr. Albert
Schmid, then superintendent of the Westinghouse Company, the
writer showed the beneficial effects of high armature-tooth satur-
ation and explained the reason why this was so, as well as the
theories of that time would permit, and he furthermore showed
that saturation of the pole face in general, and the pole corners or
edges in particular, should accomplish similar results. For then
apparently good reasons (but which afterward proved to be en-
tirely wrong) it was decided that it was not worth while trying for
a patent. A year later, however, Mr. N. W. Storer applied for and
obtained a patent covering cutting away part of the laminations
in the field pole corners in order to produce high saturation. Mr.
Wm. Cooper (formerly with the Bullock Company, and afterward
with the Westinghouse Company), also obtained a patent on cut-
ting away the laminations across the whole pole face. These two
patents led into certain expensive lawsuits, but both arrangements
were considerably antedated by the author's writtea analysis re-
ferred to above.
The advantages of a "stiff" field in preventing shifting of the
armature neutral point was known comparatively early. With the
big air-gaps on the surface-wound machines, there was not much
difficulty in getting the field ampere-turns, ot field strength, touch
higher than that of the armature* But with the adoption of the
slotted armature construction, there was
670 ELECTRICAL ENGINEERING PAPERS
toward reduction of the air-gap in order to obtain more economical
designs. Experience soon indicated that it was much more econ-
omical to obtain a "stiff" field by saturating the armature teeth
or the field pole tips or pole face, than by putting the excitation in
the air-gap alone. Thus saturation in the path of the armature
cross ampere-turns soon became the regular practice. Saturating
the armature teeth meant more slot or copper space, but meant
higher iron losses. Saturating the pole face or pole comers gave
much lower iron losses, but slightly less copper space and copper.
However, in general, saturating the pole corners appeared to give
better all around results, and this method eventually became
standard practice with practically all manufacturing companies.
Another important condition in the problem of commutation
was the armature self-induction. In the early days much was talked
and written about mutual induction in commutation After the ad-
vent of the slotted construction experience soon began to point out
that the important factor in limiting commutation was the self-
induction of the individual coils, rather than their mutual induc-
tion. Therefore, slot construction soon tended toward lower self-
induction, that is, toward wide slots. At first, on account of the
imaginary large effect of mutual induction, it was not considered
advisable to place two or more separate coils in one slot, and there-
fore a large number of comparatively narrow slots, corresponding
to the number of commutator bars, was common. However, with
the recognition of self-induction, and not mutual induction, as the
controlling factor, practice soon tended toward two and three coils
per slot, with correspondingly fewer slots and relatively better slot
proportions. The results in general were favorable, and at the same
time, with fewer slots and more conductors per slot, the total insul-
tion space was decreased and the copper space was correspond-
ingly increased. This was one of the really big steps in increasing
the capacity and decreasing the dimensions of generators. How-
ever, like many other good things, this had to be carried too far
before the best proportions could be found, and in quite a number
of cases too few slots and too many bars per slot were tried, result-
ing in special commutating troubles, due to improper magnetic
conditions.
In working over the problem of reducing the self-induction,
the writer conceived the idea of purposely so arranging the arma-
ture winding that the upper and lower coils in the same slot would
not be commutated or reversed at the same moment.* This was
*U. S. Patent No. 588,279
DEVELOPMENT OF THE D C, GENERATOR 071
accomplished by changing the throw of the coil from full pitch to
one or more slots more or less than the full pitch. In two-circuit
windings with one turn per coil, the end connector at one end ne-
cessarily has to span more than full pitch if the end connector at the
other end spans less. This scheme of " fractional pitch," or
"chordcd" winding was soon tried out and proved to be quite
beneficial, except in those cases where the neutral or commutating
zone was too narrow. This arrangement was very widely adopted,
and remained in general use until the commutating pole came in.
With this, at first, full pitch windings were used, but now the
" fractional pitch" or "chorded" armature winding has come into
extended use in some types of commutating pole machines.
EQUALIZING CONNECTIONS ON ARMATURE WINDINGS
The various types of armature windings and their effects
should be considered. As indicated bef ore, the series or two-circuit
winding was used principally on the early slotted armature ma-
chines of moderate capacity. The parallel drum type winding on
multipolar machines was well known at this time, but most of the
machines built were not large enough to require this winding.
However, as larger capacities came in, it was recognized that the
armature winding would have to be subdivided into more paths,
principally on account of commutation, and the parallel type of
winding began to be used. With this type of winding it was soon
noticed that the commutating conditions were, not infrequently,
considerably poorer than in the two-circuit winding, on the basis
of equivalent windings and commutator bars. This was particu-
larly true in machines with more than four poles. It was soon dis-
covered that there was unequal division of current among the
various parallel circuits, and tests indicated that this was due
primarily to unequal e. m. f/s generated in the different parallel
circuits by inequality in field strengths of the different poles.
This necessitated very careful adjustments of the air-gaps around
the machine and, where the discrepancy was apparently due to the
magnetic material itself, such as the poles or yoke, it was in some
cases the practice to adjust the individual field coils to give the
required equality of field magnetic strengths. This was a prac-
ticable but not very satisfactory situation. In some cases, the
unbalancing was so bad that some of the parallel circuits would
672 ELECTRICAL ENGINEERING PAPERS
feed back through others, so that the relative current unbalancing
was actually increased. This action appeared to be as follows . —
When any armature circuit carried a current, it tended to "cross
magnetize" the field pole, strengthening the flux at one pole edge
and weakening it at the other. Without saturation, these two
actions should balance each other, so that the total pole strength
remained practically constant regardless of the flux distortion.
In consequence, the armature e. m. f. per pole should remain
practically constant. However, with any considerable saturation
in the path of the cross flux, the increased flux at one pole corner
was not equal to the reduction at the other corner, so that the
resultant total flux, and the e. m. f. were decreased. Assume,
for instance, a ten-pole parallel-wound armature in a field in which
one pole, or one magnetic circuit, was much weaker than the others.
The stronger circuits tended to feed current back through the
weaker. There would be distortion under all the poles, but if
eight circuits fed current through two circuits, then the distor-
tion in the two circuits would be much greater than in the eight.
If there were high saturation in the path of the cross magnetic
circuits, then all the magnetic fields would be weakened to a
certain extent, but the two normally weaker ones would be
weakened much more than the others, due to the larger currents.
Thus their e. m. f 's would be still further reduced and more cur-
rent would flow through them. The action thus would become cu-
mulative, and might increase until destructive local currents would
flow in some of the circuits. In certain of the early parallel-wound
machines, the writer observed some extreme cases of this action,
in which the current gradually increased to such values that the
carbon, brushes became red hot over the whole length, and the
sparking at the commutator was terrific. Measurements of the
armature voltages in such cases, with the brushes raised, always
showed considerable unbalancing.
The problem of unbalanced circuits in parallel-wound multi-
polar armatures was known and the conditions accepted for several
years before a true remedy was found for it. As in many other
cases, this remedy resulted from an unusually severe case of trouble.
The Westinghouse Company had sold a number of high current
machines for electrolytic work. These were built with 14-pole
fields and parallel-wound armatures. The then usual methods of
balancing the magnetic circuits were relied upon. However, on test,
the first of these machines developed undue difficulty in maintain-
DEVELOPMENT OF THE D.C. GENERATOR 073
ing balanced magnetic circuits. The finest possible adjustments
were necessary to obtain reasonably good operating conditions.
Also, due possibly to the dimensions of the frame, and the lack of
rigidity in the temporary foundation, the machine would get out
of magnetic alignment very easily, and would get into vibration.
As soon as vibration began, commutation troubles would com-
mence and would grow worse. Mr. Philip Lange, then superin-
tendent, gave this machine his personal attention with a view to
finding how to adjust for permanently good results. After several
days of adjustment, he became somewhat discouraged and told the
writer that he did not believe that mechanical adjustment was a
satisfactory solution of this difficulty. In discussing the matter,
the writer suggested that, as two or more separate armatures, oper-
ating in parallel, would have their field strengths equalized by
tying them together electrically through polyphase alternating-
current connectors, therefore, as a parallel-wound multipolar
armature was equivalent to a number of separate armatures feed-
ing into a common direct-current circuit, it was theoretically pos-
sible to balance the different field fluxes by tying all the parallel
armature circuits together by polyphase connections.* The writer
at that time was very familiar with such action, through extended
tests of alternators in parallel, rotary converters, etc. ; also, having
applied for a broad patent covering the principle of controlling
the field strength of synchronous generators or motors by leading
or lagging alternating currents.! After making this suggestion, as
to a possible cure for the above trouble, he then proposed that it be
tried on this machine in a comparatively simple manner by wind-
ing three insulated copper bands over the front end of the armature
winding between the commutator necks and the armature core,
and then carrying suitable insulated connectors from these bands
to the tops of the commutator necks, using seven such connectors
per ring. In this way, a crude but easily accessible set of poly-
phase connections was added to the machine. This work was
cai'ried far into the night before being ready to test. Mr. Lange left
word that the results of the tests be telephoned him as soon as ob-
tained. About midnight he received a message that the commuta-
tion was perfect and there was no vibration. He then suggested
that, possibly, unusually good mechaucial adjustment had been
obtained in setting up the field, and that, therefore, the cross CCH>
*0, $, Patent No. 573,009. ttl. S. Puteftt No, 582,131,
674 ELECTRICAL ENGINEERING PAPERS
nections might not be responsible for the results. As a check on
this, he asked that the cross connections be opened, without dis-
turbing the machine otherwise in any manner, and the test then
be repeated. Under this condition, the sparking and vibration
were as bad as ever, or possibly worse than the average former
results, for in setting up the field after adding the cross connec-
tions, no particular attempt had been made to obtain good adjust-
ment of the magnetic circuit. The results therefore appeared to be
conclusive, and the several machines on this order were then fitted
with three-phase cross-connections, and all showed up equally
well on shop test. A curious condition developed in one of these
machines after installation in the customer's plant. It was found
that one of the generators did not commutate as well as the others,
and the reason for this was not discovered for several weeks It
was then found that this machine did not have the same shunt
field current as the others. Investigation then showed that two
field coils had -wrong polarity, namely, those marked No, 6 and
No. 9. In assembling the field coils on the poles, the numerals
painted on the coils had apparently been read upside down, and
the coils thus interchanged. In those days, the field coils had the
connections "open" or " crossed'* inside the coil so that one could
not determine from its outside appearance what its polarity
would be. Here was a case where a 14-pole parallel-wound arma-
ture had operated for several months with two field coils reversed,
and yet the armature cross-connections actually neutralized the
wrong polarity and established fields of the correct polarity in
their place. This was very good evidence as to the effectiveness
of the cross-connections.
As soon as this method of balancing parallel circuits was
developed, it was applied to all new machines being built by the
Westinghouse Company, and was also applied to a large number
of parallel-wound armatures already in operation. It was soon
found that with three cross-connections, there was, in some cases,
a tendency to "spot*1 the commutator at as many points or
regions as there were cross-connecting taps to the commutator.
These spots or regions were always between the cross-connecting
taps to the commutator. To overcome this, four cross-connecting
rings were tried on one flagrant case, and the spots were still
found, but of less width than before. Six cross-connections were
then tried on the same machine, with still evidence of a little spot-
ting. A total of nine cross-connections was then tried and the spot-
DEVELOPMENT OF THE D.C. VENERATOR 675
ting entirely disappeared. This was then tried on various ma-
chines, with equally good results, and therefore a comparatively
large number of cross-connections was adopted as standard West-
inghouse practice. Sometime later, it was common practice to
cross-connect all the commutator bars, but it was found that this
apparently gave no better results than a considerably less number
of cross-connections. Present experience seems to indicate that one
cross-connection per armature slot is as far as it is necessary to go,
even in the most extreme cases.
Cross-connection of parallel-wound armatures was grad-
ually adopted by other companies, until now it is practically
universal. Doubtless, most of the manufacturers have gone
through the same course of development a*s indicated above, in
regard to the number of cross-connections used. The first G. E,
cross-connected armature that the writer saw had only two cross-
connecting rings, but later, this was changed to 11 rings, the ma-
chine having 22 slots per pole. This was one of the things that
everybody had to find out by actual experience. The use of
cross-connections on parallel windings has undoubtedly had a very
great influence on direct-current development, and yet normally
it has appeared to be simply one of the incidental features of
direct-current design.
In equalizing the c. m. f .'s by equalizing the pole fluxes, natur-
ally the magnetic pulls around the machine should be equalized.
This was recognized in the first place, but an actual proof of it was
obtained very early in the practice. In one case, with a large engine-
type machine, one of the engine pedestals slipped, the armature
being thrown to one side until it was practically touching the field
poles. With a non-equali/,ed armature winding, the unbalanced
magnetic pull under this condition would have been so great that
the field would have "hugged" the armature presumably to the
point of destruction. But in this case, the armature ran freely in
the field, and there was no evidence of any magnetic pull or un-
balancing, except possibly a slight sparking at the commutator,
In the early days, numerous attempts were made to retain
the good features of the two~drcuit winding, and still increase the
number of armature circuits. This was mostly before the parallel
winding had been perfected by the development of cross-connec-
tions. The most obvious method of extending the field of the two-
circuit winding was by using two or more two-circuit windings on
the same armature core and arranging them to operate normally
676 ELECTRICAL ENGINEERING PAPERS
in parallel at the brushes. When the several two-circuit windings
were entirely independent of each other, they were known as
"sandwich windings." In other modifications of these windings,
the various circuits closed on each other and formed the so-called
' ' re-entrant " windings. The writer had some early experience with
both these arrangements, but neither proved very satisfactory.
In the first case tried, a direct-connected machine of moderate size
had a sandwich winding, consisting of two entirely independent
two-circuit windings connected to alternate commutator bars. This
was run on test for 24 hours with excellent results. Fortunately, in
order to do some special testing, it was then operated a few hours
longer, and burning of alternate commutator bars developed.
The burnt bars were marked, the commutator was turned down,
and the tests were repeated. Burning again occurred. This opera-
tion was repeated several times with like results, except that it
was noted that the same set of bars did not always burn. After
possibly a week of testing, this winding was abandoned as im-
practicable. Apparently, similar results were found by other
manufacturers, except that in some cases they got their machines
on the market before they discovered the difficulty of burning
alternate bars. Some years later, Prof. E. E, Arnold of Karlsruhe,
Germany, developed a system of cross-connections for such arma-
ture windings which, to a great extent, overcame this burning
action at the commutator. This system consists in interconnecting
various points of equal potential in the different circuits. The
writer at an earlier date similarly cross-connected some sand-
wich type two-circuit closed coil windings on some large multi-
polar low voltage alternators.* The arrangement of armature wind-
ing and cross-connections was the same as Prof. Arnold's patent
of later date. If commutators had been connected to these alter-
nator windings, the arrangement would have "been the same
as Prof Arnold's. These same machines are, the writer believes,
in operating service at the present time.
COMMUTATOR MICA
While considering questions of commutation, the effect of
windings on commutation, etc., the story of commutator mica
should not be overlooked, for much interesting history is involved
in this. The use of mica as an insulating material between com-
mutator bars dates far back. In the latter Ws, the use of mica in
*IT. S. Patent No. 680,793.
DEVELOPMENT OF THE D.C GENERATOR 1>7T
this way was well established, although red fiber and similar ma-
terials were still used occasionally. However, the mica practice in
those days was not at all standardized or uniform. Various thick-
nesses of mica were used from possibly 1-32 up to % in, A thick-
ness of 1-16 in. seemed to have the preference in the larger
machines. With the surface armature windings, used entirely in
those days, one thickness of mica appeared to serve as well as any
other. Also, practically all mica was punched out of solid sheets*
and was unsplit as far as possible. In railway motors, 1-16 in.
mica was also in fairly common use.
In designing the first slotted armature, single reduction rail-
way motor in 1890, as already described, the mica between the
commutator bars was made 1-32 in. thick, for some reason which
the writer does not now recall. On test, the commutators of the
first two machines, which were made with this thin mica, showed
no mica trouble whatever. However, this very thin mica was noted
in particular by the railway people, and a "howl went up " against
it. In consequence of the great criticism, later motors were made
with much thicker mica, although not nearly as thick as the
general criticism called for. However, when these later motors
went into commercial service, trouble soon developed at the com-
mutators. Very bad blackening and burning of the commutator
face occurred in all motors. It was soon noted that, in all cases of
such burning, the commutator mica stood above the copper sur-
face. It was not evident at first, however, whether the burning
was inherent in the slotted type of machine, with the high mica
merely as a result of such burning, or whether insufficiently rapid
wear of the mica, compared with the copper, started the trouble.
However, it was found that scraping down the mica, below the
surface of the copper, stopped the burning action. It thus ap-
peared that insufficiently rapid wear of the mica was back of this
trouble. Undercutting of the mica was resorted to for awhile, but
was considered as only a temporary remedy. In looking for a
permanent remedy, the action of the first two motors built, with
1-32 in. mica, was carefully studied. It was noted that, although,
these two motors had been in service longer than any of the others,,
yet no tendency for burning or high mica had ever developed!,
This was a pretty fair indication of what to do, and therefore, a
number of additional commutators were built with 1-32 in. mica,
and installed in places where there was comcnutator blackeoang*
All these new comtrmtators were & graat improvement, so that
678 ELECTRICAL ENGINEERING PAPERS
many of the old commutators with thicker mica were changed to
the 1-32 in. mica. This practically eliminated the trouble, but
occasionally there were cases where black spots or regions devel-
oped on the commutators which could apparently be traced to local
hard places in the mica. Thus the problem of more rapidly wear-
ing mica came up, and various experiments were made to find such.
The first effective step consisted in splitting the mica into a number
of fine sheets before building it in the commutator, with the idea
that its rate of wear would be increased in that way. This did prove
fairly effective, particularly in large generators. As the slotted type
of railway generator, however, followed about a year after the
motor, fortunately the investigations of the motor troubles were
then under way and their temporary remedies were applicable very
early in the generator work. Sub-dividing the mica as described
almost eliminated the motor mica troubles and did help the gen-
erators very considerably; but the generator trouble was harder
to eliminate, because everyone was opposed to the use of 1-32 in.
mica in generator commutators, and therefore a considerably
thicker mica was retained. It was recognized that soft quick
wearing mica was most desirable, and it was soon found that some
kinds of mica were better than others. Thus the softer "amber"
micas were soon chosen in preference to the harder " white" micas
for use between commutator bars. Incidently, in connection with
this question of soft mica, the writer recalls an incident which hap-
pened in 1892. A fire occurred in one of the Pittsburgh car barns
which destroyed, among other equipment, a car containing two
Westinghouse single-reduction motors. An examination of these
motors was made by the writer after the fire, and it was found
that the commutators had been apparently red hot. In dismant-
ling one of these commutators, the mica between commutator bars
which formerly had been in solid pieces, came out in the original
form, but was semi-calcined to a white appearance, and was split
into extremely thin laminae and appeared to be very soft. The
writer suggested at the time that here was the kind of mica that we
ought to have in commutators. However, it was considered of in-
sufficient strength to use in commutators, the use of built-up mica
with shellac or other binding material not being then well known.
The use of finely split mica without any binder, in commuta-
tors, lasted for a year to two. Such construction, however, re-
quired relatively large sheets of mica, which were unduly expen-
sive. Then, "Micanite" which consisted of small thin laminae of
DEVELOPMENT OF THE D.C. GENERATOR 670
mica built up into sheets, with a suitable binder, came into use, and
this eventually solved the mica problem, at least partially, as far
as the material was concerned. But several grades of this built-up
mica were developed, and various binding materials were used by
different manufacturers, which eventually led to very serious
trouble from "pitting," etc. In this pitting, sparks between ad-
jacent commutator bars would gradually eat away the edges of the
mica, and this action would follow the burnt edges until deep places
were eaten down between the bars. All manufacturers of electrical
machinery encountered more or less trouble from this pitting
which, in many cases, was charged against the design of the ma-
chine. Eventually the cause was found to lie principally in the
binding material in the mica plate, and with improvement in this
point and care in keeping free oil off the commutators, pitting grad-
ually disappeared.
Recognizing the fact that mica is not an unmixed blessing in
commutators, various attempts have been made from time to time
to find substitutes. Electrically, substitutes may be found without
difficulty, but up to the present time, none of them have shown
suitable physical properties, except in limited applications. " Red
fiber" and paper were used many years ago on commutators of
surface-wound machines, apparently with very good success.
Such materials wore down rapidly under the brush, especially if
any sparking occurred. Therefore, if high fiber should lift the
brush away from the commutator face, the resultant sparking
would soon burn the fiber down flush with the copper so that good
contact between brush and copper would again result. This
action in itself is an ideal one. However, all fibers or papers are
subject to more or less expansion or contraction, due to moisture
conditions, and this was a serious objection. If any considerable
expansion of the fiber occurred in its thickness, that is, in the cir-
cumferential direction, of the commutator, then, when shrinkage
followed, due to drying out of the moisture, there would necessarily
be some slight looseness circumf erentially and oil or other foreign
material could penetrate between commutator bars, which would
eventually lead to pitting. What was required was a material with
some elasticity, so that the space between commutator bars would
always be filled solidly regardless of expansion or contraction of
the cjotnmutator* The finely laminated structure of inica plate,
furnishes the necessary elasticity, but apparently no other mater-
ial yet available fc&$ satisfactorily, *&et this condition. The
680 ELECTRICAL ENGINEERING PAPERS
ical conditions required however, were not as well understood many
years ago, and hence the many attempts to use other materials
than mica in commutators. The Westinghouse Company tried
''fish paper" quite extensively years ago, in a number of low
voltage machines. In the preliminary tests the material used ap-
peared to be influenced but little by atmospheric conditions, and
excellent results were obtained. However, in attempting to extend
its use, very considerable difficulty was encountered in finding
material which was as little affected by moisture as that used in
the first tests. It developed that the particular qualities desired
for this service were exceptional rather than normal, in the manu-
facture of this material. Thus it soon became evident that this
material would not meet the requirements in general. Various
other materials were tested, such as asbestos and paper built up
in alternate layers, mica and paper built up in alternate layers, etc.
While all of. these were operative, yet, in general, they did not
show sufficient promise to extend their use. Such experience and
developments were not confined to the Westinghouse Company,
for presumably all enterprising manufacturers have had more or
less the same experience.
Within recent years, practice has tended very largely toward
undercutting the mica. This has not been due to mica trouble
primarily, but has arisen from brush conditions. Experience has
shown that certain grades of brushes are electrically and mechanic-
ally very desirable, with the exception that they do not have suf-
ficient grinding or wearing action on the mica. In order to ob-
tain the full benefits of such brushes, in many cases, it is necessary
to undercut the mica, and thus eliminate entirely the problem of
mica wear. This is especially the case in those modern relatively
high-speed machines with comparatively thin commutator bars,
in which the thickness of mica represents a fairly large percentage
of the bar thickness. In such machines, undercutting was first
adopted, but as the beneficial effects of the better brushes became
recognized undercutting has been very generally adopted on all
high-speed machines, in order to use such brushes. This under-
cutting has been the latest important step in the mica problem.
BRUSHES AND BRUSHHOLDERS
The types and constructions of brushes and brushholders have
held a not unimportant place in the development of direct-current
apparatus. On the very early apparatus, copper or metal alloy
DEVELOPMENT OF THE D C. GENERATOR
681
brushes were used almost exclusively. These were even used on
early railway motors, but the results could not be considered as
highly satisfactory. It is hardly conceivable that electric traction
could have reached its present high development if the metal
brush had been retained. About 1887 and 1888, the carbon brush
began to come into use and it is still with us, with no prospects of
being displaced by anything else, except in very special applications,
such as extremely low voltage work. It may be said that no one
thing has had a greater influence on direct-current development
than the carbon brush.
By the time the larger railway generators began to come into
•use, as described in the first part of this article, the carbon brush
PIG 7— THE DEVELOPMENT OF THE BRUSHHOLDER
A — The sliding type B — The swivel type. C — Parallel motion type. D— Reaction type
was well established. However, the manufacture of such brushes
in those days was rather crude compared with present practice,
which also may be said of everything else in the electrical business.
There was no wide range of varieties or grades to choose from,
and the carbon was a carbon brush only. If there had been many
grades, we probably would not have known how to apply them.
We found what brush gave us good results in a certain case, and
we stuck to it " through thick and thin. ' * When there were troubles,
they were frequently blamed on the mica or the brushholders.
The latter were thus subject to continual change. Types came and
went and then came back again. However, out of the multiplicity
of brushholders, several comparatively distinct types arose, Fig.,7,
such as the "sliding," the "reaction" (which was one form of the
sliding type), the "swivel" and the *' parallel-motion'1 types.
Each had its good points as weU as bad. All of these types are still
in use to a certain extent, but certain of them predominate in
present manufacture. It so happens that the one which is now fur-
nished almost exclusively with the larger apparatus, namely, the
sliding type, was alao one 6f the earliest developed.
682 ELECTRICAL ENGINEERING PAPERS
The early Weston type railway generator built by the U. S.
Co. (described in the early part of this article), had a sliding type
carbon brushholder. When the Westinghouse Company took tip the
manufacture of the multipolar generator, sliding carbon holders
were used. As far as the writer knows, the early T-H generators
also had sliding holders. The railway motors of that time, built by
the Edison (Sprague system), the T-H, the Westinghouse, and the
Short Companies, all had some form of sliding holder, and us-
ually with the carbons standing radially to the commutator. In
railway motors, there was a definite reason for this, for, as such
motors operated in either direction, the radial carbon was as-
sumed to give the best average working conditions. Also radial
carbons were used on some of the early railway generators, but it
was soon found that a slight inclination of the brushes to the face of
the commutator allowed a somewhat smoother action, there being
less chattering and less "screeching" in the case of highly polished
commutators. It was a good deal like moving a pencil over a
sheet of glass. With the pencil held too nearly vertical to the
glass, there is liable to be chattering and screeching. Thus it soon
became standard practice to incline the brushes when the sliding
type was used.
In the early sliding type holders, it was found that when
heavy currents per brush were carried, there was a tendency to-
wards burning of both the brush and the inside of the brush box.
In some forms of sliding holders it was attempted to overcome
this by clamping each carbon tightly in a metal box, and arranging
for the boxes to slide up and down on the holders. The transfer of
current was thus between metal surfaces. But eventually this de-
veloped trouble. The obvious remedy for all these cases was to
attach flexible shunts from the carbon itself to the solid frame of
the brushholder. However, the designers had many trials and
tribulations before this remedy was well developed. In the early
Westinghouse generators, before the use of shunts became general,
it was found that very long carbons were effective in preventing
burning of the carbons in their boxes, and this practice was ad-
hered to pretty faithfully for several years. Of course, the bene-
ficial effects of the long carbon were largely in increasing the con-
tact surface, and in lessening any tendency to chatter, as a long
carbon would not "rattle about" in its box, as readily as a short
one.
DEVELOPMENT OF THE D,C\ GENERATOR (>S3
Due to the difficulty in transferring current from the carbon
to the holder, in the sliding shunt type, the Westinghouse Com-
pany (and presumably all other companies, also)tried out various
forms of the swivel type holder. In this type, the brush was
clamped in a metal box which was attached to an arm which
swiveled about a holder rod or pin. This soon showed trouble at
the swivel contacts, due to the current, and therefore, shunts had
to be attached from the swivel arms to the holder frame in order to
protect the swivel joints or bearings. However, as this shunt con-
nected metal to metal, it was not difficult to apply. This type of
holder therefore, seemed to solve the problem. But another dif-
ficulty came up. About this time, engine-type generators came into
general use, and it was soon found that the swivel type holder was
liable to give trouble on engine-type machines, owing to the
" weaving'* action of the armature and commutator due to move-
ment of the shaft in the bearings, resulting from the engine
crank action. As long as the commutator ran perfectly true with
respect to the brushholder, the brush faces would follow the
commutator perfectly. But, with the brushholders hung from
the generator field frame, or pedestals on the generator base, it
may be seen that with any weaving action due to the engine
cranks, the brush faces, with swivel holders could not possibly
remain in intimate contact with the commutator face, and a
periodic "hcel-and-toc" contact would result. This necessarily
meant sparking under the brush face, with consequent gradual
burning away of the brush face and the commutator copper.
Therefore, the commutators gradually "smutted"; that is, they
got "dirty," and would show no polish. This, of course, was a
fatal defect, and eventually put the swivel holder out of business,
as far as the large engine-type generator was concerned. However,
this type of holder had much greater success on self-contained
machines, in which the commutator and brushholder could be
made to run perfectly true with respect to each other.
Another type of holder which later came into use, and for
which great claims were made, was the parallel-motion holder.
This was somewhat similar to the swivel type, except that the
brush box moved up and down parallel to itself through a parallel-
motion arrangement. This parallel-motion part usually consisted
of two parallel arms of flexible material, which were connected at
one end to the brushholder frame and at the other to the brush
box. The flexible axtns were made of laminae of copper, bronase or
684 ELECTRICAL ENGINEERING PAPERS
steel, and were flexible enough to allow a slight up or down
motion, but were not flexible enough to make the holder unduly
flimsy. In prmtiplej this holder seemed a very good one, and it
held its own for some years. The Crocker-Wheeler Company
probably used this type to a greater extent than any other manu-
facturer. It appears to be applied but little at present, presum-
ably due to questions of cost and space requirements.
A fourth form of brushholder, namely, the reaction type,
is in reality, one form of the sliding type holder, for the brush
slides up and down parallel to itself. In this holder the sliding
brush is inclined to the commutator and holder at such an angle
that the reacting forces tend to make it hug the brushholder face,
and thus give contact between the carbon and holder. This type of
holder was, at one time, applied quite extensively to railway gen-
erators by the Bullock and the Walker companies, and is still
applied to small machines, to some extent.
During all these departures and variations in brushholder
design, the straight sliding carbon type was still going through
a course of development, which consisted principally in simplify-
ing and "improving " the construction of the holder itself, and the
application of shunts between the holders and carbons. This
latter was no simple matter, and almost as much effort has been
expended in suitably attaching shunts to carbon brushes as in
developing carbon brushholders themselves. One great difficulty
was that any new method of attaching the shunt to the carbon had
to be tried out in actual service for a comparatively long period
before it could be accepted or condemned, and usually it was
condemned. A certain shunt attachment might prove perfectly
satisfactory in one class of service, and would be almost worthless
in another class. One principal difficulty was that the current, in
passing from the carbon to the shunt, or vice versa, would tend
gradually to eat away the points of contact so that eventually the
shunts would loosen or lose contact. This was a pretty big prob-
lem, and in the early part of the development, the manufacturers
of the electric machines usually attached the shunts, developing
various methods of doing this. Later, however, the carbon manu-
facturers took up the matter and, in general, were able to produce
simpler and better methods by attaching the shunt during the
formation or manufacture of the carbon, the shunt thus forming
an integral part of the carbon instead of being an after attachment.
With the greater perfection of the shunt attachments, the sliding
DEVELOPMENT OF THE D.C GENERATOR 685
type carbon holders began to dominate the field until, today, this
type is most generally used.
There were, of course, many variations in the construction of
the sliding holders themselves, such as in the types and arrange-
ments of springs, the materials and methods used in the manu-
facture of the holders, the sizes and shapes of carbons, but these
have apparently had no very controlling effect on the general de-
velopment. In generators, the inclination of the carbon either
toward or against the direction of rotation, was at one time a much
mooted point, but apparently it has never been definitely decided
which practice is better, as both are used at the present time, and
apparently the choice depends upon local conditions, such as
commutator speed, lubricating quality of the carbons, and a
number of other conditions. In many cases, changing the holder
from either direction of inclination to the opposite direction, has
apparently helped the operation.
GRADES OF BRUSHES
In recent years, much more attention has been paid
to the various grades of carbons, as regards their conduct-
ing and lubricating qualities, softness, etc. Graphite brushes,
or the use of graphite in carbon brushes, was long ago recognized
as furnishing some very good qualities. However, it was soon noted
that brushes with much graphite in them were liable to give
41 smutty" or burnt commutators, at least in railway work. This
was blamed largely on the brush, which was possibly true to some
extent, but it was later recognized that the fault was partly in the
inability of such lubricating brushes to wear the mica^down
rapidly enough. In some cases, two grades of brushes were used
on a machine at the same time, part having high abrasive qualities
and the others being of a graphite nature and furnishing good
lubrication. With a better understanding of the problem has again
come the use of graphite types of brushes, with undercut com-
mutators, and they appear to be very successful in many cases.
Thus a type of brush which, at one time, was condemned for rail-
way work, has later come into extended use, due partly to changes
in constructive conditions.
Where better conducting qualities in the brushes were de-
sired, the so called carbon-gauze brushes have been tised at
times. These originated probably as early as 1892. They were
used on large railway generators to some extent, but principally
in connection with lower voltage machines. In these brushes,
686 ELECTRICAL ENGINEERING PAPERS
sheets of fine wire gauze were embedded in the carbon during the
manufacture.
The question of plated versus unplated brushes came up very
early in the application of carbon brushes, and is not satisfactorily
settled yet. One theory was that plating assisted in the transfer of
current between the carbon and the brush box, reducing the
burning action. Another theory was that there should be little or
no flow of current between the carbon and box, and therefore,
plating was harmful, especially on carbons with good shunts.
Again, where the shunts have been attached simply to the outside
surface of the carbon, it has been claimed that plating assisted
in getting the current to the shunt. And the question is still open
for discussion. In many cases probably it is merely a matter of
personal opinion. There are so many variable conditions in
each machine that one can get quite different results at different
times, or under different conditions of service.
BURNING OF BRUSHES, "PICKING UP COPPER," ETC.
Ever since carbon brushes came into use there has been more or
less trouble from burning of the brush faces, honeycombing of the
carbon structure and picking up of copper. These do not always go
together, but there are certain common causes for all these actions.
In the very early slotted armature generators ample brush capa-
city was usually furnished. However, gradually the ratings of such
machines were increased, without radical changes in the propor-
tions, due largely to improvement in ventilation, so that eventually
the carbon brushes were worked at very high apparent current
densities (densities due to work current only). It was soon evi-
dent that the brushes were worked too hard, and steps were taken
to improve this condition by increase in brush size, etc. Brushes
were made thicker circumferentially, with a view to reducing the
current density, the fact being overlooked, or not recognized, that
the local or cross currents of the brush face were back of a consider-
able part of this brush trouble. In many cases these thicker brushes
did not improve conditions, or were even harmful. This latter
was proved to be the case, in many instances, by simply beveling
the "toe" of the thick brush in order to reduce the breadth of
contact. Very often, much better operation was obtained with
these beveled brushes, although the apparent current density in
the brush was increased, but in fact, the actual current density
was decreased. This led up to an appreciation of the fact that the
local current in the brush in many cases, was actually greater than
DEVELOPMENT OF THE D C GENERATOR «S7
the useful or work current. The writer very early reached the con-
clusion that the apparent current density in carbon brushes was of
no real importance in designs or guarantees, unless other conditions,
such as thickness of brush, etc., were also apecified.
Due largely to too high actual current density in the brush,
there was much trouble in some of the early machines from burn-
ing of the brush faces. This burning would begin at one edge of the
brush and gradually travel across the whole brush face, until the
entire face had been burned away and the brush tip badly honey-
combed in some instances. This honeycombing was usually co-
incident with " glowing," that is, red hot spots would appear in the
brush tips. Many attempts were made to cure such conditions by
substitution of a different kiiad of brush, and sometimes with suc-
cess, due principally to change in brush resistance, with conscqunt
change in local currents. But this was largely "cut-and-try". It was
also found that improvement in the inherent commutating con-
ditions would also lessen the brush trouble. Obviously, this simply
reduced the local currents, which consequently helped both the
commutator and the brushes,
POLARITY
It was noted very early in direct-current work that
the positive and negative carbon brushes did not act exactly alike.
Those of one polarity would some times take a good polish at the
brush face, while those of the other polarity would show but little
polish. Also, the brush faces would sometimes have a coating of
copper formed on them, or small particles of copper would embed
themselves in the brush face. This action was not the same for
both polarities. It was quite a long time before this unequal polish-
ing and picking up of copper was even partially understood. Even-
tually it was found that when a current passed through a moving
contact, such as that between a brush and a moving commutator,
or collecting ring, there was a tendency for minute particles of the
material of the contact faces to be eaten or burned away, depend-
ing upon the direction of current. When the current passed from
the brush to the commutator, the brush face tended to eat away,
while with current in the reverse direction, the commutator copper
showed this effect. With low current densities in the points of con-
tact, it was noted that this action was very slight. Also, the better
the contact, that is, the lower the resistance of contact, the less
this action was. In some cases- the material burned away from one
surface was deposited on the opposing fape, possibly mechanically.
688 ELECTRICAL ENGINEERING PAPERS
For instance, with a carbon brush and current passing from the
carbon to the commutator, the commutator conditions were
averaged, and it was only in the brushes that any difference would
show. Long before this action was well appreciated it was indi-
cated on the collector rings of certain rotating armature alter-
nators and rotary converters. In some of these machines, with
copper brushes on the rings, but with very high current densities
at the brush contacts, it was found that the rings tended to wear out
of round, with half as many low places as there were current alter-
ations per revolution, or number of poles in the field. This was
quite pronounced in some cases, but was usually blamed on loose
brushes, because increasing the brush contact pressure usually
helped it temporarily. The fact was, that this was a true burning
action, as above described, and it was only in every other alterna-
tion that the current was in the direction which would burn the
collector ring. The fact that the different collector rings did not
have their low spot in phase with each other was not appreciated
for a long time.
With the carbon brushes, this action between the commut-
ator and brushes became much more pronounced as the apparent
current densities were increased. Also, picking up of copper became
more pronounced. Both brush polarities suffered a great deal from
burning. One polarity would have the brush face burned away due
to the direction of current, this action being cumulative for, as the
face burned away at one edge, due to the sum of the local and work
currents, the contact arc would be decreased, and the contact
would continue to burn away, although the local currents would be
lessened. On the other polarity, where such burning should not be
expected, a coating of copper would form in some cases, and this
would tend to lower the brush contact resistance, and thus in-
crease the local currents, which depended upon the contact resist-
ance. Thus the brushes of this polarity would also be burned, due
to the excessive current. Moreover, as the copper deposit was
frequently very irregular, the reduction in brush contact resist-
ance would be local only. At the spots of lower resistance, an excess
part of the work current would flow, tending to produce local heat-
ing. As the temperature coefficient of resistance of carbon is
negative, any local heating would mean still lower local resistance,
a larger percentage of the total current concentrated at this point,
and thus more heating, the action becoming cumulative, until
glowing occurred at times. This abnormal local heating tended to
DEVELOPMENT OF THE D C GENERATOR i>89
disintegrate the brush, so that cavities formed at or near the brush
tip and the carbon became "honeycombed." This action was not
always coincident with "picking-up-copper," for anything which
produced unequal division of current among the brushes or over the
brush contact, tended toward glowing and honeycombing. This
action apparently was more closely connected with high current
densities, either locally or as a whole, than with any other cause.
Obviously, with the brushes worked normally very close to the
limit as regards permissible current densities, any little inequal-
ities in current were liable to have a more pronounced effect.
This action has been dealt with rather fully, as it was one of
the very serious troubles in old time machines. Many attempts
were made to overcome this trouble by changing the kind of
brush, the type of brushholdcr, proportions of the armature, etc.,
and with varying success. Burning of the brushes was frequently
accompanied by high mica on the commutator, and this in turn
exaggerated the burning. Undercutting the mica, by allowing
more intimate contact between the brushes and copper, quite fre-
quently alleviated this contttion. But where the actual current
densities were very high, even undercutting did not cure the
trouble. Eventually, it was recognized that lower actual current
densities must be had, and when this was thoroughly appreciated
and embodied in the designs, burning of brushes and picking up of
copper were of much less usual occurrence. In the commutating-
pole machine, referred to later, the local currents are under partial
control, and thus the apparent current densities in the brush can
be brought up much nearer to the actual limiting densities, so that •
today considerably higher apparent densities are used regularly.
The above covers one principal cause of brush trouble. How-
ever, there were many cases of trouble in which the brush densities
were not unduly high, considering the size of brush face, but where
the effective brush contact area was reduced by bad mechanical
conditions, such as chattering of the brushes, commutators out of
round, etc. It was not always possible to distinguish between the
various causes of brush burning and, not infrequently, a remedy
which worked in one case was an entire failure in the next. Un-
equal division of current between different brush arms in parallel,
and also between the different brushes on the same arm, also
greatly complicated the problem. ' Back of this is the negative
temperature coefficient of resistance of the carbon brush, as
mentiotxed before* With a positive coefficient, any local increase
6SO ELECTRICAL ENGINEERING PAPERS
in current would be opposed by a local increase in resistance, thus
tending to equalize the current distribution between the various
brushes. However, with the negative coefficient, a more or less
unstable condition exists. This unfortunate condition has been
recognized for many years and presumably it has been a serious
handicap in direct-current design and development Various
devices for overcoming it have been suggested from time to time,
but no very practical one has yet been produced.
BRUSHHOLDER SUPPORTS
Having dealt with brushes and brushholders, the brushholder
arms and supports should be given consideration, as there is some
interesting history connected with this feature of design. In the
earlier machines the brushholder arms or supports were carried by
brackets attached to or surrounding the bearing. This was com-
mon practice in all early belted machines. Provision was usually
made few some easy, quick method for rocking the brushes forward
or backward to suit the commutation. Even on the railway gener-
ators, where the point of commutation was supposed to be fixed,
such brush-rocking devices were alwayff furnished, so that the best
average position of commutation could readily be found.
When the engine-type generator came in, new problems were
encountered. In the first place the engine bearing was not always
a suitable place to attach a brushholder, and in the second place,
with large diameter commutators, this made a rather flimsy sup-
port for a large diameter of holder. Also, a new problem came up
in the weaving action of the armature of the engine-type generator,
'as already referred to. If the brushholder frame was held sta-
tionary, then the weaving action of the commutator meant con-
tinual motion of the brushes up and down in their holders, wHch
was considered undesirable. In one early Westinghouse engine-
type generator, an attempt was made to make the brushholder
follow the commutator by suspending it directly on the engine
shaft by a sleeve or bushing which fitted over the shaft, thus form-
ing a bearing. This was prevented from rotating with the shaft by
means of a brace to some stationary part of the engine frame. This
worked for awhile, until one day the bearing "froze" on the shaft,
the brace broke, and the brushholder started to rotate around the
commutator. This ended the history of that particular type of
support.
The next step in the development of the brushholder support
consisted in hanging it from the field yoke, either centering it in
DEVELOPMENT OF THE D C GENERATOR m»I
the yoke itself (early Wcstinghouse practice) or centering it on a
number of rigid arms extending out from the yoke toward or over
the commutator, (early G. E. practice). Of course, these two
methods were practically equivalent. Eventually, for purely con-
structive reasons apparently, centering in the yoke itself became
the general practice and is standard practice at the present time
in the larger machines. This method of support did not eliminate
the difficulty from weaving action of the commutator, but in fur-
nishing a rigid brush support, the resultant troubles, due to weav-
ing action, were partly overcome and the development of good slid-
ing type brushholders took care of the rest.
Another trouble developed occasionally, principally in con-
nection with brusliholders for long commutators, that is, wide
commutator faces. The individual brushholder arms would some-
times vibrate or chatter badly. At first, it was attempted to make
the individual arms rigid enough to take care of this, but as each
arm had to be insulated from the brushholder frame, it was dif-
ficult to obtain sufficient rigidity without undue complication
and expense. As an alternative, the practice was adopted of tying
adjacent arms to each other at their ends by means of insulated
supports, so that the entire system of brush arms thus formed one
rigid body. This was very effective and is standard practice today.
On the earlier machines, the brush arms, to which the brush-
holders were attached, were made of brass or some other fairly
good conducting material. For some reason or other, iron was con-
sidered objectionable, and it was many years before it came into
general use for the brushholder arms. Now it is standard practice.
Possibly, commercial reasons may have influenced this delay in the
use of iron in brush arms, for it was criticised as being "cheap " in
appearance,
COMMUTATORS
Commutators and commutator constructions also have a
history, but it is rather difficult to trace this systematically. Very
early in direct-current generator practice, the present "V" con-
struction for supporting the commutator bars was developed and,
with various minor modifications, it has come through to the
present. This construction, Pig, 8-a, was adopted on the earliest
Westtnghouse tnultipolar generators and, with only one exception,
namely, the shrink-ri&g oonstruction in ttirbo-getierator commut-
ators, it foas been retained on these machines throughout. The
692 ELECTRICAL ENGINEERING PAPERS
angle of the V's, the shape and construction and material of the
insulation have varied from time to time, but this general method
of supporting the bars has remained unchanged.
Another early method of supporting the commutator bars,
which was used considerably by some manufacturers, including
the Thomson-Houston, if the writer remembers rightly ,was as
shown in Fig. 8-6. This was apparently a fairly satisfactory con-
struction in the early days, but was abandoned later by practically
everybody, in favor of the V construction. When built-up mica
insulating bushing came into use for insulating the commutator
' A ' B
PIG. 8— TYPES OF COMMUTATOR BAR CONSTRUCTION
bars from their supports, apparently the V-ring construction was
simpler as regards mica bushings than any other construction, and
this may have been enough to turn the manufacture toward this
one construction.
In the early days, there was a great variety of methods of
attaching the armature windings to the commutator* In some
cases, the commutator was made without " necks" in the modern
sense of the word, the windings being carried directly to the com-
mutator face and attached thereto by solder or screws. When
railway generators began to come in, the Westinghouse Company
used comparatively long necks to which the armature conductors
were attached by means of slots in the end of the necks in which
the conductors were laid and then soldered. In some cases, these
necks fitted tightly against each other with mica between, as
between commutator bars, as in Fig. 9-6. In other cases, especially
where the commutator bars were comparatively wide, thin separ-
ate necks with air spaces between them were used, Fig. 9-a. Us-
ually these necks were made of copper strap, riveted or soldered
to the end of the bars. In other cases, the neck and bar was
sawed out of one piece. The open neck was most common in the
larger Westinghouse generators. In practically all cases, these
necks were made so stiff that they were self-supporting and re-
quired no insulation between them.
DEVELOPMENT OF THE D.C GENERATOR
693
In the Thomson-Houston and early General Electric large
railway generators, these necks were frequently made of flexible
material, and were usually insulated throughout their length in
consequence. With the built-up type of strap winding used on
these early machines, as has already been described, presumably
these flexible commutator necks were of material advantage in
winding and connecting. In many cases, these necks were at-
tached to small brass or copper blocks or terminals, of rectangular
shape which, in turn, were attached to the commutator bars by
means of screws so that they could be disconnected, if desired, Fig.
9-c and d. Eventually the rigid neck construction came into
general use.
PIG. 9— METHODS OF CONNECTING COMMUTATOR BARS TO ARMATURE
WINDINGS
MATERIAL
There was quite a variety of materials tried out in
the earlier commutators. For the bars, copper, either drawn or
rolled, has been used from almost the earliest times, but many
attempts have been made to get away from this material, largely
on account of the expense. Various brasses and bronzes, and even
cast copper, have been used quite extensively, and not entirely on
account of lower cost* for some of these were about as expensive as
drawn copper. One idea was that the rapid "wear" of copper
commutators which was sometimes encountered, was due to the
softness of the material and that, therefore, some much harder
kind of material would give less wear. Of course, it was not known
then that the rapid wear in those cases was not true frictional wear,
but was due to burning under the brushes, to high and hard mica,
etc. This wear was a principal reason for using the various brasses
and bronzes. After long trials of each of these materials, the con-
clusion was usually reached that the average results were no better
than with copper. In some of the early Westinghouse experience,
cast segments were used, with apparently good results. However,
in the larger bara, blow-hotes were liable to be found near thfc
664 ELECTRICAL ENGINEERING PAPERS
center of the bar. This was taken up with the manufacturer of
these bars, but the trouble was not entirely overcome.
One rather amusing case of trouble came within the writer's
experience in connection with one of these early cast copper com-
mutators. This was a fairly large capacity, low voltage belted ma-
chine, with very thick commutator bars. The commutator ran
very hot in the early service, due largely to brushholder troubles,
and the writer was surprised to find solder was being thrown over
everything in the neighborhood. He looked the commutator necks
over, but could not find that any solder was missing at these
points. Throwing of solder still continued, and in comparatively
large quantities. Then the man who had charge of the building
of the commutator was questioned, and he asked, innocently
enough, whether this could have resulted from filling blow-holes in
the commutator bars with solder. He then explained that the
heavy cast bars had developed so many and such large blow-
holes some distance below the wearing surface that he had thought
it best to fill them up with solder. It may be added that eventually,
this commutator ran all right, either due to lower temperature or
to the escape of all the solder that could find an outlet.
As the mica and brushholder troubles were gradually elimin-
ated, it became much better recognized that pure copper rolled,
drawn or hammered — was about the best possible material for
commutator purposes. It took time and additional experience to
prove that this was the best polishing material. Various tests were
made with iron, aluminum and other materials, in comparison
with copper, and it was found that copper polished best of all
practicable materials, under heavy load conditions. It was found
that other materials under sparking conditions developed minute
globules or "beads" on the commutator face, and thesev beads
were liable to be very hard in some cases, so that they destroyed the
brush polish, and also prevented the commutator face from polish-
ing. The conclusion drawn eventually was that the copper was so
much better a conductor of heat that these tiny metal beads
would not be formed, as the heat would be conducted away too
' rapidly. Iron was particularly bad in this regard. Since the good
characteristics of copper have been more thoroughly recognized,
this material has been used almost exclusively.
With the exception of the bars, about the only materials
which need be considered are the insulation and the supporting
rings. In the early days, the supporting insulation, under the
DEVELOPMENT OF THE D C. GENERATOR 695
metal clamps, was made of almost any kind of sheet-insulating-
material, such as paper, fiber, oiled canvas, or sheet mica. When
built-up and moulded mica came into use, this was quickly adapted
to commutator purposes, and is still standard practice.
One of the most serious problems in commutator insulation,
in general, has been that of keeping out oil. Where oil could creep
into the commutator, it was very liable to carry copper and carbon
dust with it, and incipient short circuits or arcs sometimes resulted
which developed into more serious trouble. One of the great prob-
lems has been to obtain "tight" commutators. Modern practice
seems to be pretty successful in this. In the question of tight com-
mutators, there have long been two schools, (or two sets of advo-
cates), one favoring the so-called " arch-bound" construction and
the other the " drum-bound." These terms practically define
themselves. In the arch-bound construction the commutator is
drawn down until the circumferential pressure is the limiting re-
sistance. In the drum-bound, the commutator is drawn down until
it binds upon a central drum or support which is the commutator
bush. One advantage claimed for the drum-bound construction is
that the commutator is affected less by temperature, as the cir-
cumferential pressure is not a controlling condition. Moreover, it is
claimed that it is easier to assemble such a commutator. Against
this, the claim for arch-bound is that it gives greater tightness than
the drum-bound, and tightness is a most essential characteristic in
commutators. For many years the writer has favored tight com-
mutators, as his experience with pitting, (dealt with under the sub-
ject of mica) indicates that tightness is a necessary condition. At
the present time, the so-called V-bound construction which might
be considered as intermediate between the arch and drum-bound
constructions, seems to be the most satisfactory, in general.
It is not necessary to say much about the supporting rings for
commutators. On the early machines, these were frequently made
of cast iron. When engine-type machines came in, the supporting
rings were usually made segmental as they had to be split to get
them over the shaft, the low commutator speeds allowing segmental
construction without danger. However, as higher speed machines
began to come in, such as rotary converters and motor-generators, '
solid supporting rings of cast steel or wrought iron came into very
general use. This was not due altogether to the higher speeds, but
was partly due to the necessities for making tighter commutators
696 ELECTRICAL ENGINEERING PAPERS
than formerly, which necessitated stronger materials in the sup-
porting rings.
WEARING DEPTH OF COMMUTATORS
Practice has changed greatly in this feature, especially in
recent years, due partly to improvements in design, and partly to a
recognition of consistency in proportions. On very early gener-
ators and motors, the wearing depth of commutators was, rightly,
very large. As commutators "wore" rapidly, due to high mica,
poor commutation, etc,, they had to be sandpapered or turned
down rather frequently. A good part of the commutator was thus
wasted. But when engine-type generators came, with their much
better commutating characteristics, the great wearing depth was
retained in general, apparently largely for traditional reasons.
Some of these engine-type generators did not require even sand-
papering once in two years, and yet any proposed reduction in
wearing depth was looked at askance.
To illustrate the above, the following incident is cited: — The
writer broached the subject of commutator wear with the en-
gineer of a large railway system, in which 2J^ in. wearing depth
of commutators was standard practice with his larger commu-
tators. He was asked how much the large commutators had worn
down in the previous nine years, of pretty steady operation. The
answer was, "About one-sixty-fourth of an inch.*' " Then, at that
rate, how long will your commutator last ? ' ' After a little figuring,
— "About 1500 years.'1 "And how long will the rest of the ma-
chine last?" After a little thought, — "Not over 50 years at most."
By actual figures, a 3-32 in, wearing depth in this case, correspond-
ing to 50 year's life, would have been an absurdity of the opposite
extreme. But a factor of safety of ten would have given a total
available wearing depth of one inch, while the commutators ac-
tually had iy% times this. The extra material is thus useless
during the actual life of these machines. As the inconsistency of
abnormal wearing depths, usually specified for commutator
became better realized, they were gradually decreased. This, of
course, had to be recognized by the users of such apparatus, as well
as the manufacturers. With the advent of the commutating-pole
machines, with their better commutating characteristics, the
wearing depth of commutators has been reduced to a fairly
reasonable amount, still allowing a wide factor of safety. It is
somewhat saddening to think of the thousands of tons of copper
tied up uselessly in abnormal commutator proportions, but then
DEVELOPMENT OF THE D.C. GENERATOR 697
one has only to look in various other directions to see what pos-
sibly may be similar extravagances some of which are in full force
at the present day, especially in methods of rating and applying
electrical apparatus,
TEMPERATURE AND VENTILATION
One important general subject has not yet been touched upon
very fully, namely, that of temperature, together with the related
subject of ventilation. In the early days, all electric machinery ran
hot and the manufacturers, as a rule, knew why the apparatus ran
hot, but did not know just how to remedy the case. Armature
cores were ventilated to a limited extent, but the windings were
very poorly ventilated. The temperature of the windings was high
(how high nobody knew or appreciated) but as no one had any
particular experience with lower temperatures, the high tempera-
tures were taken as a matter of course. This was particularly true
of some of the early railway generators, On continuous full-load
run, some of these would reach 125 degrees C. by thermometer, but
as railway load in those days was far from continuous, this ap-
parently did not make any difference. A rise of 60 to 75 degrees
C. was considered fairly good on continuous temperature test.
However, it was decided about 1892 that some lower standard,
such as 40 degrees rise, should be adopted. When this went into
effect in the Westinghouse testing room, some very amusing in-
cidents occurred. The testing room men who had been accustomed
to rises of 60 or 70 degrees would be much worried over nominal
40 degree machines which actually showed 42 to 45 degrees rise,
as they feared the machines might burn up on test. They seemed to
accept the newly set 40 degree limit as an absolute limit of safety,
regardless of past experience.
After the 40 degree limit was adopted, it has stayed with us
more or less constantly until the present time* The writer does
not know where this exactplimit originated, nor who was back of it.
It just came and stayed.
In those early days temperature measurements could be made
by thermometer about as accurately as at the present time, but
people did not know how to hunt for hot spots and, in conse-
quence, were liable to put the thermometer on the coldest part of
the winding, and then wonder why such a cool machine (60 to 70
degrees C. rise) should burn out so readily. But what they did
e, they aimed to measure carefully*
698 ELECTRICAL ENGINEERING PAPERS
In those days all temperatures were measured after shut
down of test, and usually by covering the thermometer bulb with
a great wad of cotton waste. But the thermometers used were not
particularly accurate, and variations of five degrees or more
between different thermometers tested at the same air temper-
attire were found by the writer in a number of cases.
In this early work, some almost unbelievable incidents oc-
curred. For instance, one of the routine testing men one day
announced to the writer that he had found a method of cutting
the temperatures of railway motors (old double reduction surface-
wound armatures) to about one-half. He claimed he had accom-
plished this repeatedly and was sure of his results. As this ap-
peared to be a very valuable idea, he was urged to divulge his
method. After a good deal of coaxing, he stated that he had
attained this result by leaving the waste off the thermometer while
taking the temperatures. This was a case of absolute faith in
what the thermometer said. A little explanation of the functions
of the covering pad of waste, and of the principles of temperature
measurement, soon put this man in the right.
As soon as the necessity for lower temperatures was recog-
nized, the problem of ventilation became very active. Armature
windings were arranged for more or less effective air circulation,
and special ventilating ducts were placed in the armature cores
at intervals. The writer does not know who first introduced venti-
lating ducts in the armature cores, but they did not originate in
the Westinghouse Company. With the surface-wound armatures
of course, there was little or no occasion for radial ventilating
ducts, as the armature surface was pretty thoroughly covered up.
Openings or holes parallel to the shaft were, however, rather com-
mon in surface-wound armatures for alternators, but in direct-
current machines, except of the ring type, even such ventilation
was usually impracticable. However, with the advent of the
multipolar railway generators, with the; drum armature windings
and slotted armature cores, there was an opportunity to use
radial ventilating ducts effectively, and they soon cafne into
general use. The Thomson-Houston Company preceded the
Westinghouse Company in the use of such ducts, according to the
writer's memory. However, -by the time that engine-type rail-
way generators had practically monopolized the field, radial ven-
tilating ducts in armature cores were standard practice with prac-
tically everybody, and this is standard construction at the present
DEVELOPMENT OF THE D.C. GENERATOR M9
time. Many varieties and constructions of ventilating ducts have
been devised and tried out. About the only important departure
from this construction has been in armatures equipped with
ventilating fans at one end in which the air is drawn axially
through the armature instead of radially. This has been used
mostly on recent railway motors, and on certain lines of industrial
motors.
The ventilation of direct-current armature windings has
varied much, depending upon other controlling conditions. For
instance, the end windings of railway motors were formerly much
better ventilated than at present, and with very beneficial results
as regards temperature. However, the railway motor, being an
enclosed machine, circulated its own dirt (carbon and copper dust,)
to such an extent that the windings, especially back of the commu-
tator, would become so coated that surface leakage became serious.
To overcome this, practice gradually tended toward unventilated
end windings, that is, they were so completely boxed in that the
dust trouble was pretty thoroughly eliminated. But the railway
motor may be considered as an exceptional case, due to its normal
inaccessibility for cleaning, and the tendency in other classes of
machines has been toward better ventilation, rather than the
reverse.
In commutators, the subjects of temperature and ventilation
have always been with us, and probably are destined to stay with
us as long as the business lasts. Primarily, the reason for this is
that the commutator, in large machines, is so costly and sometimes
so difficult to construct, that the natural tendency is toward
crowding it down in dimensions, with a resulting tendency to in-
crease the temperature. Thus the battle between size and temper-
ature is always on.
In the very early railway commutators, in belted type ma-
chines, the temperature of the commutator, like all the rest of the
machine, was usually fairly high. However, these early commu-
tators were not very large, so that expansion troubles were not very
serious- After the multipolar generators came in, it was soon found
that long commutator necks, with air spaces between them, Fig.
£-a, were quite effective in cooling the commutator. The writer
had this impressed upon him particularly in connection with an
early direct-connected railway generator in which the necks and
tnica were solid deaor up to the outer periphery where the winding
joined the coftmtftetor, Fig. 9*c. Tlie speed of the armature was
700 ELECTRICAL ENGINEERING PAPERS
only 140 r. p.m., and the diameter of the commutator was small, so
that the ventilation was comparatively poor. This commutator
ran very hot on test. It was concluded that the solid necks had
much to do with this, as these did not permit the usual heat dissip-
ation which probably occurred with open necks The writer then
had long radial slots milled in the center of the bars, as shown in
Fig. 9-a. This set up a slight air draft across the commutator. The
reduction in temperature was so pronounced that the writer
became a thorough convert to the use of ventilated necks, and he
adhered to such construction as far as possible on all large com-
mutators thereafter. However, when engine-type generators came
in, the commutators were usually made so large, compared with
belted machines, that the temperature problem practically dis-
appeared as far as commutators were concerned. However, when
rotary converters and motor-generators became the prevailing
practice, with the general introduction of the polyphase system
in railway and central station work, this problem of temperature
again became active, and has become more important as the speeds
and ouputs have increased, so that today the problem is a "real
live" one. In modern commutators, auxiliary "necks'1 or ventilat-
ing vanes are sometimes attached to the outer ends of the commut-
ator bars, or ends farthest from the winding. Like the open com-
mutator necks, these are quite effective in dissipating the commut-
ator heat.
Various rules have been developed from time to time for
determining the size of commutator required for a given current,
without overheating. However, all such rules have proved to be
only crudely approximate, for the heating is dependent upon the
commutation and friction losses, which are extremely variable in
different types and sizes of apparatus. The modern cotnmutating-
pole construction of machine, which furnishes a means for partially
controlling the commutation losses, has been a great help in the
commutator heating problem. This however, has simply al-
lowed higher speeds with correspondingly smaller diameters of
commutator for a given output, and thus the battle between size
and temperature goes on.
In the modern high-speed motor-generators, probably the
ventilation has been carried farther than in any other class of
direct-current apparatus. In the modern machine, two funda-
mental conditions in the problem of ventilation are recognized,
namely: supplying a sufficient quantity of air to carry away the
DEVELOPMENT OF THE D.C. GENERATOR 701
heat, and so distributing this air that it can take up the heat with
the least temperature drop in the various parts of the machine.
The whole modern theory of ventilation is built up upon these
two conditions.
SPECIAL CLASSES OP DIRECT-CURRENT MACHINES
In the foregoing, direct-current generators and motors in
general have been considered. However, there are several rather
special classes or types of machines which merit separate
consideration, in some of their features. Among these are double-
commutator machines, turbo-generators, unipolar generators, and
double-current generators (a.c,-d.c. machines). Also, commut-
ating-pole machines in general have not been taken up, but as
these represent practically the latest great step in the direct-cur-
rent development, and therefore are newer in history than the above
special types, the latter will be considered first.
DOUBLE-COMMUTATOR MACHINES
By this is meant an armature with two separate commutators*
usually placed at opposite ends of the armature core. Such ma-
chines usually have been designed only for very special purposes,
such as the collection of very heavy currents, or where two separate
voltages are desired from the same armature core. Obviously,
where the current to be handled is too large to come within the
limits of a single commutator, the first suggestion would be to add
a like commutator on the other end of the armature, and prefer-
ably connected to the same armature winding. This looks like a
simple, easy solution of the problem, and so it proved to be from
the mechanical or constructional standpoint purely. Prom the
electrical standpoint, it sometimes proved to be a very unsatis-
factory construction.
The earliest machine of this type that the writer had any
practical experience with was built by the United States Company
about 1890, this being of the Weston type, previously described.
This was a two-pole, 200 kw, 60 volt machine and had a commut-
ator at each end connected to a common winding of the surface-
wound type. This machine was not very successful and was later
provided with a slotted type of armature, which was also not en-
tirely successful, due largely to the fact that copper brushes
required to handle the large
702 ELECTRICAL ENGINEERING PAPERS
In 1893, the Westinghouse Company built some 60 volt, 3600
ampere, six-pole belted generators with two commutators con-
nected to the same winding. These had carbon brushes. No
particular trouble was encountered in the operation of these
machines, except it was found that rather careful adjustment of
the two sets of brushholders was necessary in order to produce
proper division of load. After this, from time to time, double
commutator machines of moderate size were built, and it was found
in some cases that it was difficult to divide the load equally be-
tween the leads from the two commutators, ana at the same time
obtain good commutation at both sets of brushes. Various schemes
were introduced for overcoming this trouble. In some cases, the
leads from the two commutators were tied solidly together, and the
ammeter was connected in the combined circuit. The brushes on
the^two commutators were then shifted until best commutation
conditions were obtained. Later experience showed pretty clearly
that, under this condition of best commutation, the two commut-
ators were usually supplying quite unequal currents, especially
where both were connected to one armature winding. This cured
the trouble simply by hiding it. In one plant, where some 4 000
ampere, 250 volt; double commutator generators were installed,
it was found that with the best commutation, one commutator
supplied 3 000 amperes, while the other furnished only 1 000. No
adjustment of the brush lead would overcome this and maintain
good commutation. When one commutator carried 3000 amperes
without sparking, then the brushes on the other one could not be
rocked from the 1 000 ampere non-sparking position into a position
where it would divide current equally with the other commutator,
without sparking. There appeared to be no non-sparking position
which would give equal current division. Finally, a low resistance
in the form of a heavy cast iron grid, was introduced into the leads
from the higher current commutator, with the brushes on both
commutators set for the best commutation. This forced a larger
percentage of the current to pass through the other commutator,
and thus equalization was obtained. It was surprising how little
was required to balance the two commutator loads. This case illus-
trates the general difficulty which appeared in double commut-
ator machines of larger capacity when one winding only was used.
This led the Westinghouse Company to advocate two independent
armature windings when double commutators were required.
With this arrangement, any equality of current would mean in-
DEVELOPMENT OF THE D.C. GENERATOR 703
equality in resistance drops, which would tend to equalize the loads
A number of armatures of this type were actually built.
It may be of interest to note that the largest capacity, highest
speed machine ever built by the Wcstinghouse Company had two
commutators connected to a single armature winding. This was
the generator end of a flywheel type motor-generator set for
furnishing current to a reversing mill at the Illinois Steel Com-
pany's plant in South Chicago, and was rated as a 3 000 kw, 375
r. p. in , 600 volt machine. In this case, however, the commutators
feed into separate loads, which are adjusted to divide approxi-
mately equally. The armature of this machine has some unusual
constructive features. On account of the large output and high
speed, and the fact that the load varies with great rapidity, it
was desired to obtain the effect of one-half-turn armature coils
instead of the one-turn coils, which are usual practice. The arma-
ture winding was made of the usual parallel-drum type with one
turn per coil, but with only half as many coils as there are bars in
each commutator. The commutators were connected to the wind-
ing at each side of the core in the usual manner, except that only
alternate commutator bars were connected. Then, from the ac-
tive bars on one commutator, strap connections or conductors
were carried under the armature core to the idle or intermediate
bars of the other commutator, and from the active bars of this
second commutator similar conductors were carried through to
the intermediate bars of the first commutator. Thus the potential
of any intermediate commutator bar was midway between the
potentials of the two adjacent active bars, and the result was
equivalent to the use of a half -turn winding on the armature. As
far as the writer knows, this is the only large machine ever built
with this type of winding. It has been in successful operation for a
number of years.
Another type of very large capacity, high-speed double com-
mutator generator was built by the G. E. Company for the
Niagara Falls plant of the Aluminum Company of America* These
machines are of 3 500 kw capacity, 600 to 700 volts, 300 r, p. m.
and are direct-coupled to waterwheels. Each commutator carries
brushes of one polarity only. The number of poles in each ma-
chine is comparatively large and, in consequence of this and the
high speed, the distance between commutator neutral points is
relatively small, and, presumably to avoid crowding the bruafct-
holders too much, alternate holders are omitted. Thus one ccro*
704 ELECTRICAL ENGINEERING PAPERS
mutator has only positive brushes, and the other only negative.
This increased the distance between brushliolders, but, of course,
did not increase the distance between adjacent neutral points on
the commutator. Therefore, as regards flashing around the com-
mutator, this double spacing of the holders may be considered as
more or less fallacious. Due to this arrangement of brush holders,
some unusual commutator and brushholder operating conditions
were found The two commutators of each machine did not polish,
or ' ' wear, ' ' equally, due largely to the fact that in one commutator
the current flow was entirely from the brushes to the commutator,
while in the other it was the reverse, the effect of which has al-
ready been described under brushes and commutation. However,
these machines have been in operation for a number of years, and
the above is not intended as a criticism of this particular design,
but is merely to call attention to a very unusual construction.
The Bullock Company, some years ago, built some large
capacity double-commutator machines for the Massena plant of
the Aluminum Company of America. In these machines, unbalan-
cing of the commutator current was encountered. This condition
was corrected by the use of brushes of different resistance in the
two polarities of each commutator.
It should be evident from the preceding that the double-com-
mutator machines, in large capacities, as built by various manu-
facturers, have necessitated either special operative, or special
balancing conditions. The trouble is, to a certain extent, an inher-
ent one. The advent of the commutating pole apparently has not
improved the position of the double-commutator machine, and
at the present time such machines are only recommended where
some very special conditions require such construction.
DIRECT-CURRENT TURBO-GENERATORS
Direct-current generators, driven by steam turbines, were
introduced in this country many years ago by the DeLaval Com-
pany. However, these generators were geared to the steam tur-
bines and operated at only comparatively high speeds. They were
not turbo-generators in the modern meaning of generators direct-
coupled to the turbine. It is in this latter type that special features
are involved.
Probably the first true turbo-generator which was tried in
commercial service in this country was one designed by the Wes-
inghouse Company in 1896 for direct connection to a Parsons
DEVELOPMENT OF THE D.C. GENERATOR
705
5 000 r. p. m. turbine. This generator was designed for a capacity
of 120 kw at 160 volts. When one considers that this machine had
a speed of practically double that of the modern turbo-generator
of corresponding capacity, it may be appreciated that this was
quite a problem for a first machine. This was one of Mr. N. W.
Storer's early "pets," and it required an extraordinary amount of
petting to make it behave.
The real operating difficulties in this machine were due to the
exceedingly high speed. There was no undue difficulty in making
an armature which would hold together. The armature had par-
tially closed slots with two rectangular straps shoved through
from one end and then carefully formed at each end, over sup-
porting shelves or brushes. There was a commutator at each end.
The commutator peripheral speed was over 8 000 feet per minute,
and herein occurred the real troubles with the machine. There
FIG. 10— RADIAL TYPE COMMUTATOR
were four poles and four brush arms, with carbon brushes origin-
ally, and graphite brushes later. Neither carbon nor graphite was
successful, as intimate contact between the brushes and commut-
ator apparently could not be maintained at the high commutator
speed. Fine V-shaped grooves were then turned in the commut-
ators, and brushes of parallel brass wires were used, similar to those
on some machines in England. These brushes maintained pretty
fair contact, but with the slotted type armatures used, the corn-
mutating conditions were not satisfactory enough to allow the us©
of metal brushes. There was always more or less sparking at the
brushes, so that, after a certain amount of service, this machine
was taken out. It was redesigned later for a speed of 3 600 r. p. m.,
but apparently was never completed.
Turbo-geuemtor work was then dropped by the Westing-
house Compaay, turtil 1904, except that, for several years previous
706 ELECTRICAL ENGINEERING PAPERS
to this, exciters had been built from time to time for direct-con-
nection to turbo-alternators at both 1 800 and 3 600 r. p. m. These,
however, were usually standard machines of small capacity,
simply modified for these high speeds. Previous to 1904 the G. E,
Company built and put in service a number of turbo-generators of
moderate size, which operated with such success as to encourage
the growth of this business. In 1904 the Westmghouse Company
again took up this work, and three units were designed of 100 kw,
200 kw and 500 kw capacity, the latter for 600 volts for railway
work.
The 100 kw unit was designed for a speed of about 2 000 r.p.m.
and did not prove such a difficult machine to build or operate. The
200 kw was designed for 250 volts. Two of these machines were
put in operation and eventually developed commutator trouble.
New commutators were then furnished of the radial type, such as
the British Westinghouse Company had been building. In this
radial type commutator, as shown in Fig. 10, the brushes were
located in grooves in the commutator and bore on opposite faces
of the grooves. By this construction, much higher commutator
speeds were allowable, as radial vibration, or radial inequalities of
the commutator did not affect the brush contact. The only two
machines of this type which were built are still in service. The
radial commutator construction, however, as used on these two
machines, proved unduly expensive, and no more were built for
service.
The 500 kw, 600 volt turbo-generators operated at a speed of
1 500 r. p m. The commutator speed was about 5 500 feet per
minute. The shrink-ring type of commutator construction was
used. As tlje metal of these rings was very close to the commu-
tator face, any little arcing or sparking was liable to bridge over to
the rings and thus cause the machines to flash over. It was there-
fore necessary to insulate these rings completely in order to prevent
flashing. This, however, was successfully accomplished. In service,
these Westinghouse machines operated fairly well, with the ex-
ception of certain mechanical difficulties, due primarily to high
speed. In specific applications, they operated very well, but they
proved too delicate to send out broadcast and their manufacture
was dropped for a while.
In 1909, turbo-generators were again taken up by the West-
inghouse Company. In this case, however, the construction was
limited to sizes of 150 kw and lower. A large number of these
DEVELOPMENT OF THE D.C. GENERATOR 707
small units were put out and have been quite successful from the
operating standpoint, but they were expensive to build, from the
generator standpoint, compared with machines of similar capaci-
ties at much lower speeds and low in economy on account of low
turbine speeds.
It was long ago recognized that the turbo-generator unit was a
bad compromise between the most desirable turbine and generator
speeds. In general, the highest practicable speed for the gener-
ator was much below the desired speed for the steam turbine. In
practically all cases of actual turbo-generators, the engine was
therefore operated at too low and the generator at too high speed.
In turbo-alternators, the capacities and speeds were continually
being increased, while in direct-current work the tendency, es-
pecially in larger capacities, was toward lower speeds. Obviously,
this was going in the wrong direction, and there appeared to be
little or no hope of carrying the turbo-generator into the large
capacities. Obviously, the solution of this problem lay in some
mechanical or electrical form of drive which would allow higher
turbine speeds and lower generator speeds. In the electrical drive, a
solution was obtained by substituting for the generator a very
much higher speed alternator, the current from which was supplied
directly to a rotary converter of any preferred speed. In a 500 kw
unit, for instance, a 3 600 r. p, xn. turbo alternator was used in-
stead of 1 500 r. p. m. required with the direct-current unit. This
enormous gain in speed was sufficient to offset, in cost 3nd per-
formance, the additional apparatus required. Moreover, the com-
bination was much less delicate than the straight turbo-generator.
A number of such sets was supplied, of capacities from 300 up to
2 000 kw. However, a mechanical solution of the problem was then
brought forward in the Westinghouse floating gear, which solved
the gear problem for very large capacities, and allowed high-speed
turbines to drive moderate speed generators* In this way, turbines
built for turbo-alternator units, which were about as high speed as
practice would permit, could be connected to generators designed
tor motor-generator sets which were also usually of as high speed
as best design would permit, as regards cost and good operation.
Thus, with this gear, the best speed conditions for both engine and
generator, could be obtained, and moreover, standard turbines and
generators designed for other purposes could be combined in one
unit — a very desirable condition from both the inantifacturiag
and the commercial standpoint.
703 ELECTRICAL ENGINEERING PAPERS
Quite a number of these geared sets in capacities from 500 to
3 750 kw have been built and put in operation. The results ob-
tained have sealed the doom of the large direct-connected turbo-
generator. In fact, they are so favorable that there is good reason
to believe that eventually the geared sets will be carried down to
sizes much less than 300 kw with very considerable gain in econ-
omy at least. This looks like a logical line of development,
UNIPOLAR GENERATORS
The saying that, ' ' Happy is the country which has no history "
may be paraphrased in the electrical manufacturing business, into
* * Happy is the company which has no unipolar history." Yet there
was a time when the unipolar generator appeared to fill a long-felt
want, namely, as large capacity turbo-generators. It was long ago
recognized that the turbo-generator could not be carried to large
capacities unless unduly low turbine speeds were used. Against
this, the unipolar generator appeared to furnish a satisfactory
means for getting direct-current in large quantities, and at com-
mercial voltages, from very high-speed generators.
From the standpoint of size, weight and cost, the higher the
speed of the unipolar generator, the more commercial it becomes.
But from the current-delivering standpoint, which is the import-
ant function of the machine, the higher the speed the more difficult
does successful operation become. The difficulty is not in making
a machine which will hold together at very high speeds, but is
almost entirely in making the current-collecting devices work
satisfactorily at such speeds. In the unipolar generator, the voltage
obtainable per conductor, that is, per pair of collector rings, is a
direct function of the section of the magnetic circuit and of the
number of revolutions of the machine. But the collector rings
must surround this magnetic circuit, and therefore, the peripheral
speed of the collector rings is also a function of the section of the
magnetic circuit and the revolutions. Therefore, the voltage per
pair of collector rings is related to the peripheral speed of the col-
lector rings ; and, unless a relatively large number of collector rings
is used for ordinary commercial voltage, the unipolar turbo-
generator is bound to have extremely high collector-ring speeds,
practically between 12 000 and 20 000 feet per minute. By making
the section of the magnetic circuit larger and reducing the speed
in proportion, the peripheral speed of the collector rings may be
reduced somewhat, as the periphery of the magnet does not in-
rEVELOPMRXT OF THE D.C CBXERATOR 709
crease as fast as its section. However, this cannot be carried very
far, in large capacity machines, without running into abnormal
weights and costs. Therefore, in large capacity unipolar turbo-
generators, it is not commercially practicable to get below certain
collector ring speeds.
As already mentioned, about 1904 there was a considerable
demand for large turbo-generators. The Westinghouse Company
put out nothing above 500 kw, but the General Electric Company
put out a few much larger si zes, such as 800 kw and even one of
1 700 kw for railway work. These larger machines, however, re-
quired such low turbine speeds as to be commercially unsatisfac-
tory. Moreover, the generators themselves were not particularly
satisfactory, being beyond the limits of practical design of those
days. Therefore, the General Electric Company, apparently in
looking for a substitute, took up the unipolar design for turbo-
generator work. This did not appear to present any great diffi-
culties, as the unipolar principle had been well proven out years
before, A number of unipolar generators in capacities up to 500 kw,
and even one unit of 2 000 kw were built. These machines appar-
ently were very promising at first, but later a number of unexpected
difficulties developed.
In 1896, and later, the Westinghouse Company built and dis-
posed of a number of small three-volt unipolar generators for meter
testing; but about 1906, a contract was obtained for its only large
unipolar turbo-generator. This was a 2 000 kw machine, 260 volts,
at 1 200 r. p. m. This differed from the General Electric machine
in a number of respects, having a considerably lower peripheral
speed at the collector rings, and using special bronze instead of steel
in the rings. It turned out that these two differences were more or
less fundamental in their effect on the operation. This machine was
finally put into successful service after discouraging experiences,*
and operated satisfactorily for several years. It has been shut
down very recently, and is now held as reserve to a rotary con-
verter transforming plant, which has taken its load. This change
was not on account of any operating defects of this unipolar unit,
but on account of very cheap power rates, a condition which has
recently been responsible for putting many industrial and railway
generating plants out of business.
The General Electric 2 000 kw unipolar generator showed
difficulty in current coUectic>&. The collector rings were of steel
p*g» H5.
710 ELECTRICAL ENGINEERING PAPERS
and the peripheral speed was about 40 percent higher than on the
Westinghouse machine. These conditions introduced certain fun-
damental difficulties which could not be overcome, and eventually
this generator was replaced by an alternator which furnished
current to a rotary converter.
These two cases practically end the history of the large
capacity unipolar generator in America, for the alternator, with
rotary converter, and the geared generator, as referred to under
turbo-generators, have practically put the unipolar generator out
of business.
AC-DC GENERATORS
Both alternating and direct currents have been required
from the same generating station at times, such as for railway
service directly from the station, and for lighting or for trans-
mission to remote rotary converter or motor-generator substa-
tions. Therefore, ever since both alternating and direct current
have been generated in the same station, there have been pro-
positions that both services be supplied from one generator. As
early as 1893, the Westinghouse Company took a contract for two
150 kw generators capable of delivering SO cycle alternating and
525 volt direct current from the same armature. These were 8-pole,
750 r. p. m. belted machines, and therefore were not unlike other
belted machines of that time, in speed and capacity. The larger
number of poles somewhat complicated the conditions, and made
the commutation more difficult, due to the comparatively narrow
neutral zones. It was recognized in the design of these early ma-
chines that separate excitation would be required on account of
the alternating-current load, as it was well known at that time
that self-exciting machines were very unstable when carrying
inductive loads. Also, on account of the two classes of service
from the same machine it was considered useless to compound the
machine for direct-current load. In fact, it was pretty thoroughly
recognized that in general the two classes of service could not be
very consistently handled from one machine.
When these machines were put on test, some very interesting
results were obtained. For instance, when an alternating inductive
load was thrown off, the direct-current load conditions remaining
unchanged, the voltage would rise possibly 30 to 40 percent, due
to the fact that, as alternating-current machines, the magnetic
circuits could not be highly saturated, as was then common
DEVELOPMENT OF THE AC GENERATOR 711
practice in direct-current work. With the high resultant voltage,
there was liability of considerable flashing at the commutator.
Also, when the direct-current terminals were short-circuited, the
commutator developed the largest fireworks that the writer has ever
seen from a small machine. This was due primarily to the separate
field excitation and the high field ampere-turns compared with the
armature. In the ordinary self -excited machine, there will usually
be vicious fireworks momentarily in case of a short-circuit, but the
machine quickly "kills0 its excitation. In this separately excited
machine, the field excitation was not killed in this manner, and if
flashing or ' ' bucking ' 'was once started, it kept up the performance.
This trouble was finally reduced by means of a special field circuit
breaker which killed the field in case of excessive load.
These machines were so sensitive on the direct-current end
that the writer advised against their shipment, However, they
were so badly needed that they were sent out to help matters tem-
porarily, and astonishing as it may seem, additional machines,
exact duplicates of the first, were ordered from time to time. It
developed that the power company used them principally for
alternating-current work, the direct-current end representing
reserve or emergency conditions for a railway plant. They were
perfectly satisfactory as straight alternators, and they could
have been used to supply direct-current if any emergency had
occurred.
About two years later, the Westinghouse Company sold
some belted a.c.-d.c. machines, in which the principal service was
to be direct-current with some alternating-current to be taken for
operating a rotary converter. This was not such a difficult condi-
tion, and proved satisfactory in service. The tendency in railway
work, however, was toward engine-type generators almost ex-
clusively and, of course, the engine-type a.c,-d.c. generator had to
receive some attention. But here a stumbling block occurred in the
frequencies and the usual engine-type speeds. With 60 cycles., for
instance, an engine speed of 120 r. p. m. (which was high for a 500
kw unit, for example) would require 60 poles to give the desired
frequency. But a 60-pole direct-current machine of 500 kw was
coniinercially impracticable. The same held true for practically
all engine speeds and generator capacities, so that the a.c,-d.c«
60 cycle engine-type machine was never considered commercial.
A few 60 cycle high-speed belted a,c,-dc. generators were sold,
these being usually 60 cycle rotary converters modified into
erators.
712 ELECTRICAL ENGINEERING PAPERS
In 25 and 30 cycles, however, there were possibilities in engine-
type generators and in consequence, a few of them were built.
The Westinghouse Company furnished four 1 250 kw, 550 volt
a.c.-d.c. generators with 32 poles for 94 r. p. m. Some 500 kw
slow-speed machines for 25 cycles were also built. Quite a number
of 12-pole, 250 r. p. m , 25 cycle and 14-pole, 257 r. p. m., 30 cycle,
500 volt a.c.-d.c. direct-coupled generators were built and put in
service. Most of these machines were intended for railway service
with both kinds of current, the alternating current being trans-
mitted to rotary converter substations.
All the above were good operating machines, but more or less
at the expense of abnormally large designs. They had to be made
with exceptionally good commutating characteristics, for the
armature reaction and field distortion were dependent upon the
alternating as well as the direct-current loads.
Apparently, experienced designing engineers have never been
wildly enthusiatic over the a.c,-d c. generator, for its interfering
characteristics were against the machine. In consequence, other
methods of accomplishing the same result in a more satisfactory
manner, were given very careful consideration. With improvements
in the straight alternator and in the rotary converter, it gradually
developed that an alternator and a rotary converter could, in
many cases, be built as cheaply as a corresponding a.c.-d.c. gen-
erator. When this stage was reached, the a.c.-d.c. generator, in
most cases, had no real excuse for existing, and so it dropped out of
sight commercially. Here is a case of a type of machine which at
one time had good commercial prospects, but which is now en-
tirely obsolete from the manufacturing standpoint. If anyone
imagines there is any discredit attached to this situation, then the
Westinghouse Company, which put out most of the a.c.-d,a ma-
chines, will have to shoulder the greater part of it. The enormous
development of the alternating-current power stations, with rotary
converter substations, has put a number of very good lines of ap-
paratus out of business.
COMPENSATING AND COMMUTATING-POLE MACHINES
The cotnmutating-pole machine is the latest big step ia
direct-current development. It is very closely allied to the com-
pensated machine, although it may be noted that the latter came
into use many years ago while the straight commutating-pole type
was comparatively modern in its application. Crude forms of
DEVELOPMENT OF THE D.C. GENERATOR 713
compensating windings were proposed comparatively early in the
electrical work. However, the more complete form in which the
distributed compensating winding was used appeared about 1893.
This was the Thompson-Ryan compensating winding. A line of
direct-current generators, known as the Thompson-Ryan, was put
on the market. However, compensating windings did not come into
general use, apparently because the conditions under which they
make their best showing did not exist at that time. The compen-
sating winding possessed three advantages : ( 1) , it helped commut-
ating conditions; (2), It reduced the maximum voltage between
commutator bars, with a given number of bars per pole, and (3), it
allowed a higher no-load induction in the armature teeth. However,
when the first compensating machines were brought out, none of
these advantages were controlling — ( 1) , due to the fact that engine-
type generators then practically had the field, and in such gener-
ators as a rule, commutation was not a limit ; (2) , there were usually
more commutator bars than were actually needed as regards maxi-
mum voltage between bars; (3), those slow-speed, low frequency
machines usually had their armature teeth worked so very high
that the elimination of the cross-magnetizing effect of the armature
would not mean a very large gain in permissible flux, in many cases.
The real field for compensating windings in generators was in
high-speed, high-frequency machines with a small number of com-
mutator bars and with comparatively low teeth saturations, such
as in the generators of motor-generator sets. But it so happened
that when these began to reach their limits in capacity and speed,
commutation was the first serious difficulty encountered, and the
adoption of commutating poles overcame this, so that -the field
for the compensating winding was again narrowed. The field
seems now to be limited largely to those machines in which cross
induction is objectionable and where there is need for reducing the
number of commutator bars per pole below what has heretofore
been permissible practice. In consequence, the compensating
winding has recently extended only to two new classes of appar-
atus, namely, very large motors and generators for reversing mills
and steel plants, and high voltage generator work, in which there
is difficulty in finding room for the requisite number of commut-
ator bars without excessively high commutator peripheral speeds.
The ajmrnui^tibog pole which teas, during the past few years,
come into such general ttse, is &ot a modem idea, as it was pro-
-Dosed about 1 889 to 1890 m EagtaxwL Ttes was a field for it i&
714 ELECTRICAL ENGINEERING PAPERS
the early belted multi-polar railway generators, but before practical
designs progressed up to the point of commercially using such a
device, the engine-type generator came in, and this, to a great
extent, did away with the necessity for the commutating pole.
Thus the commutating pole idea dropped out of sight, and did not
come back again until a real need for it developed. This was ap-
parently in connection with adjustable speed motors having speed
ranges of three or four to one. The occasion for such a speed
range developed in connection with machine-tool electric drives.
In some of the earlier machine-tool drives, a two-voltage, three-
wire supply was used. With such a system, a shunt motor having
an adjustable speed range of two to one by means of a shunt field
could be given a four to one total speed range by means of the
three-wire supply system. This, however, was a rather complex
arrangement, taken as a whole, and was not of general application,
and it soon became evident that a four to one speed range in the
motor itself, with the standard two-wire or otic-voltage supply
system, would be much simpler and of more general application.
This, therefore, led to the four to one adjustable speed motor for
such service.
Various schemes were tried for building such motors, among
others being commutating poles. The great difficulty, of course,
was to maintain good commutation at the highest speeds and
weakest fields. Eventually the commutating pole furnished the
simplest solution from the design standpoint and was adopted by a
number of the different manufacturing companies, the Electro-
Dynamic Company apparently being earliest in the field. How-
ever, the use of commutating poles was limited principally to such
special service until occasion arose to apply it on railway motors.
The railway motor had been developed into a well-established
piece pf apparatus, with apparently only a few serious defects,
among which was an occasional tendency to "buck over," ap-
parently without sufficient reason in some cases. This was credited
partly to "breaking-and-making" the circuits when passing over
gaps in the trolley system, etc. Under such conditions it was
found that the motors would take a comparatively heavy current
rush which sometimes would cause flashing. Early tests de-
veloped the fact that a railway motor equipped with commutating
poles was apparently much less sensitive to flashing than the
standard type. This was a promising idea and was quickly fol-
lowed up. This was one of the reasons for adoption of commutating
DEVELOPMENT OF THE D.C. GENERATOR 715
poles in railway motors, but there was quite a number of other
reasons, possibly none of them controlling, but, taken together,
they made quite a showing. In an extremely short time after corn-
mutating poles began to be talked about for railway motors they
became pretty much a "fad," and this assisted in their adoption.
This revolution was accomplished very quickly, and within about
two years after they were first considered seriously, practically
everything in the way of new railway motors was of the commut-
ating-pole type. But this was one of the fads that lasted, for there
was much more merit in the commutating poles in railway motors
than the public first appreciated.
The quick revolution in railway work accomplished by com-
mutating poles had its effect upon all other classes o£ moderate
and large sized generators and motors. In some classes of appar-
atus where the commutating pole was embodied it was not actually
needed, such as in small slow-speed generators. However, in other
classes of machinery, such as high-speed generators, it practically
revolutionized design in a few years1 time by allowing the use of
much higher speeds for a given output, or much larger output for
a given speed. This was true particularly in those cases whore com-
mutation was the real limit. The commutating poles, in removing
this limit, or greatly increasing it, allowed radical changes in the
design.
It has long been known that maximum outputs for a given
amount of material meant high armature ampere-turns for a given
size of armature. Nevertheless, such constructions could not be
carried to their logical limits in the usual non-com-mutating pole
machines, due to limitations of commutation. However, the use of
commutating poles overcame this difficulty, and thus, to a con-
siderable extent, revolutionized the design of moderate and high-
speed motors for general purposes* A leading example of this is
found in the Westinghouse "SK" line of motors, which was de-
signed with commutating poles to use the material throughout to
the very best possible advantage, This line was designed with a
view toward future tendencies, and was apparently considerably
ahead of the times when it first came out, judging from some of the
criticisms which were brought against it. At the present time the
commutating-pole construction is used in practically everything
in direct-current apparatus that the Westinghouse Company
builds, with the exception of very small apparatus.- Marry of
other manufacturing companies can say the same.
716 ELECTRICAL ENGINEERING PAPERS
Since the commutating pole has come into general use, gener-
ators and motors for some very extreme applications have been
carried out. Very large capacities of generators at speeds tin-
dreamed of with non-coirunutating-pole machines have been
carried through successfully. For example, a 3000 kw, 600 volt,
375 r. p. m. generator, forming part of a flywheel motor-gener-
ator set, was furnished by the Westinghouse Company for the
Illinois Steel Company for operating a large reversing mill. Also,
a number of 3 500 kw, 300 r.p.m., watershed driven generators of
600 to 700 volts were furnished by the General Electric Company
for an aluminum plant at Niagara Falls. These two examples
represent about the extremes in direct-current design that have yet
been built; for, while larger capacity machines have been or are
being built, yet they are for much lower speeds. In these two
extreme examples, furnished by two different manufacturers, there
are certain superficial resemblances. For example, in both cases,
the armatures are of the double commutator type, both com-
mutators being connected to the same winding.
In slower speed machines, some 3 750 kw, 270 volt Westing-
house machines at 180 r. p. m. have been geared to 1 800 r. p* m.
steam turbines. These are possibly the largest current-capacity
machines yet built. The field for large direct-current generators
now appears to be limited principally to electro-chemical or electro-
metallurgical work where direct current is necessary, or to special
applications, such as certain classes of mill work, etc. Some com-
paratively large generators have been built for motor-generator
sets; but the synchronous booster rotary converter now seems to
be making considerable headway in that special field where the
motor-generator formerly stood alone, namely, where fairly wide
variations in direct-current voltage are required,
HIGH VOLTAGE GENERATORS WITHOUT COMMUTATORS
This is a chapter which should possibly be recorded simply
on account of the persistency of its subject, and of the vast amount
of unproductive work which has been expended upon it. This
work, however, has been of more or less educational value, on the
theory that as much is learned through failures as from successes.
The production of unidirectional high voltage in generators with-
out commutators or a multiplicity of collector rings, has been one
of the "will-o'-the-wisps " of the electrical field. Apparently there
are only a few engineers and analysts who have gone into this
DEVELOPMENT OF THE D C GENERATOR 717
problem so thoroughly that they recognize certain fundamental
reasons why such machines cannot be built.
This problem may be compared, in some ways, with the per-
petual motion fallacy. A perpetual motion scheme may be made
so complicated and may involve so many principles and combina-
tions that it is very difficult to put one's finger on the real fallacy;
yet, if the law of conservation of energy is brought to bear upon it,
the details of the scheme need not be considered at all, for this
one fundamental law condemns it utterly, regardless of methods
or means involved. In the same way, in the direct-current ma-
chine without a commutator, certain fundamental principles of
flux cutting and e. m. f. generation are sufficient to condemn all
machines of this sort, regardless of their type or construction. In
the final analysis they usually come down to one effective con-
ductor, or turn, per pair of collector rings, which is the well-known
unipolar generator. However, the fundamental principles are
difficult to make clear to the inexperienced, just as it is hard to
convince some people that the law of conservation of energy holds
good over the whole finite scale, from the practical standpoint.
Therefore, the writer anticipates passing upon such schemes in
future, just as he has done for some 25 years past, and he, coin-
cidentally, will be obliged to dampen many bright hopes.
As indicated, the fallacies are principally due to misunder-
standing of fundamental principles. For instance, & favorite
scheme is to have the " magnetic lines " of the field move across the
conductors, or vice versa, generating e. m. f . in one direction, and
then have the lines closed back on themselves through some path
which the conductors do not cut; not recognizing that, as the
magnetic lines are closed circuits and the electric circuit is also a
closed circuit, the lines cannot be cut once unless they are cut
twice, if the action is to be continuous* The second cutting is
always such as will generate e. m. f . in opposition to the first, and
the only way to avoid cutting twice is to interpose some relatively
non-moving or non-cutting part, which means two sliding con-
tacts for each effective turn. This, of course, leads at once to the
usual unipolar generator with one turn for each pair of collector
rings.
As another instance, a common mistake has been to assume
that, as the movement of the coil across fluxes or fields of alternate
directions or polarities will give an alternating e. m. f ., therefore,
by revwsing tbe fields at the proper rate, the armature e. m. 1 will
718 ELECTRICAL ENGINEERING PAPERS
be correspondingly reversed, thus making it unidirectional;
whereas, in fact, it is still alternating, but of double frequency.
Other schemes involve "inductor" alternator constructions,
with a view to obtaining half waves, or those of only one polarity,
thus giving a pulsating unidirectional e. m. f . In such schemes the
various transformer actions and the reverse cutting of the flux by
the conductors are usually overlooked. Still other schemes are
dependent upon the assumption that magnetic lines may be open
or discontinuous; or, if continuous, may be stretched or length-
ened indefinitely. Again, combinations of several or all of these
ideas may be involved in the same proposed device, thus making a
lucid explanation almost an impossibility. One of the most amus-
ing schemes, which not infrequently appears, is where the apparatus
generates a true alternating e. m. f ., but in which the inventor has
followed the action only through one e. m. f. wave, and over-
looked the rest of the cycle.
All told, probably hundreds of thousands of dollars have been
expended on this general fallacy, and doubtless many more
thousands will be expended, just as in the case of perpetual
motion. Moreover, much valuable time has been expended by
those who did not believe in the possibility of such apparatus in
showing wherein individual schemes submitted to them are not
operative. The writer probably has been requested, two or three
times per year on an average, to make a careful analysis and, in
some cases, a full written report on schemes of this nature, which
have been submitted to the Westinghouse Company. * In fact, he
has repeatedly threatened to prepare a printed form which could
be used as a "blanket" report for all such cases. However, the
fact that many of these cases come from "very good friends"
apparently precludes such procedure.
CONCLUSION
As will at once be noted by any "old-timer/* this history is
far from being a complete one. The writer's endeavor has been to
cover those points within his direct knowledge and experience
which have had an important effect on direct-current generator
and motor development ; in other words, he has attempted only to
hit the "high spots." If all the interesting sidelights, incidents,
etc., within his own experience were to be included it would have
extended this article to triple length, possibly, and it would have
become much more reminiscent than historical. This article has
DEVELOPMENT OF THE D.C GENERATOR 719
been made very broadly impersonal, as due credit cannot be given
to all who have expended so much time and energy in bringing the
development up to its present high stage. Occasionally personal
references have been included, partly to break up the historical
tenor, and partly to counteract any impression which may have
been created, wholly unintentionally, that the writer personally,
or the company with which he is associated has been the only
active participant in this great development. Much of the history
covering the inside story of direct-current generator development
has never been recorded and will eventually be lost. If a few of the
ancient mariners of this sea could be induced to tell their tales it
would be a boon to the younger generation. If the writer has aided
even a little in preserving this early history, he feels thoroughly
repaid for his effort*
THE DEVELOPMENT OF THE STREET RAILWAY
MOTOR IN AMERICA
FOREWORD — The author took an active part in some of the earliest
commercial successful electric railway developments and has
been in close touch with much of the later work. His direct
knowledge regarding details of development by companies
other than the one with which he is identified is, therefore,
necessarily limited, to a certain extent. No claim is made that
this article covers the history of all railway motors. It is
rather the history of the author's own experience in this very
interesting field. The present article is limited to street railway
motors and no attempt is made to cover heavier service as
represented by interurban and main line railways. Neither are
controllers and control systems more than merely touched upon.
This article was first published in the Electric Journal. —
(ED.)
RAILWAY motor development in America began back in the
early 80 's but much of this was of a purely pioneer nature
and, while it left its impress, in most cases it was not a lasting one.
On the other hand, certain of this early pioneer work led directly to
the commercial railway motor of the later 80's.
Principal among the pioneers in this work may be mentioned
— Van Depoele, Henry, Daft, Bentley-Knight, Sprague and Short.
Some of the railway systems brought out by the early inventors
simply flashed up for a short time and then disappeared. Others
came and, through merit, stayed until forced out of the field by
later developments, many of their good points being embodied in
the later systems. The Van Depoele system, with its under-
tunning trolley, left its impress on the future systems in the form
of the tinder-running trolley itself, which has been used almost
universally since. Professor Short, with his'series system attracted
some attention for awhile, but being defective in certain funda-
mental principles, this system disappeared in favor of the parallel
system, which Short himself later adopted, The Sprague system,
which came a little later than some of the others, was along more
nearly correct lines. It contained certain good fundamental prin-
ciples; it persisted longer than the other early systems, and
eventually established electric propulsion as the coming system of
traction for street railways, etc. This will be referred to more
completely -under the description of railway motors.
721
722
ELECTRICAL ENGINEERING PAPERS
RAILWAY MOTORS
Practically all the early railway motors which were com-
mercially successful were of the double-reduction gear type, i. e.,
there were two sets of gears between the armature shaft and the
car axle. There were two reasons for this, namely, the compar-
atively slow speed of the cars of those days, and the high speed of
the motors, necessitating something like a ten-to-one speed re-
duction. In most of these designs the motors themselves were
suspended from the car axle and were connected thereto by means
of spur gearing. In a few special instances attempts were made to
drive the axles through bevel gears, one motor being connected to
two axles. None of these survived. Also, chain drive was used on
the early Van Depoele system.
FIG. 1— SPRAGUE DOUBLE REDUCTION MOTOR 1889
By 1889 the electric railway had become quite firtnly estab-
lished. Even at this early day the* most successful systems had
certain points of similarity, which apparently had some bearing on
their success, At this time, the Thomson-Houston (a development
of the Van Depoele system), the Sprague (Edison Company) and
the Short (Brush Company) systems were at the fore and all were
STREKf RAILWAY MOTOR IN AMERICA 723
apparently quite successful. Early in 1890, the Westinghouse
Company entered the field with a street railway system, thus,
making four principal manufacturers. Thereafter for several years
these four systems were the leading ones on the market. Gradually
two of these dropped out, or combined with others, leaving the
General Electric (Thomson-Houston and Edison) and the West-
inghouse as the only large manufacturers. Therefore, the follow-
ing description will be confined largely to the motors of the four
earlier systems and the two later ones.
SPRAGUE RAILWAY MOTOR
The Sprague electric railway motor system of 1888 to 1890
was unquestionably the most perfect one of that time from the
standpoint of control and economy of operation. This was due
principally to certain fundamental features of design, which had
been carried to the utmost. This motor was of the two-pole
type. The armature was of the surface-wound type with several
layers of wire. It is obvious that such a motor was inherently
poorly protected and, from the present standpoint would be con-
sidered an extremely doubtful piece of mechanism to place tinder
a car. However, in those days, all other makes of motors were just
as questionable and, therefore, this motor did not suffer by com-
parison.
The interesting f eature about this motor was in the method of
starting and speed control. The field structure was made of a good
grade of wrought iron of high magnetic permeability. The field
coils were wound in three sections of different sizes of wire and
different numbers of turns and the field windings were so propor-
tioned that, with all the field coils in series at start, a heavy torque
was obtainable with a very small starting current, thus avoiding
overheating the fields without the use of a starting rheostat,
However, it should be said that, with all the field coils in series,
the combined resistance of the armature and field was sufficient to
fix the starting current at a relatively small value. Following
the series starting position, by series-paralleling of the field coils,
various combinations of speed were obtainable up to the maximum
desired. Here was a system where all starting and controlling was
done without external rheostats, a very economical method of
operation and one which has possibly not been exceeded in any of
the ^later commercial direct-current methods of operation. This
due largely to the relatively high speed of the armatttee of thfe
724 ELECTRICAL ENGINEERING PAPERS
double-reduction type and to the fact that the field magnetic flux
could be worked over a very wide range, while the total motor
capacity was small compared with modern practice. These favor-
able conditions disappeared largely in the later, lower speed, single-
reduction motors.
While this early Sprague motor was a very fine one from the
viewpoint of economy of power, yet according to the writer's ex-
perience, it did not have the ruggedness for emergencies found in
some of its competitors. The very element which made it so econ-
omical, namely, the series-parallel field windings and the absence
of a rheostat, made it more delicate in emergency conditions which
required abnormal currents for prolonged periods; such as push-
ing snow plows, for instance, during severe storms. In some cases
the Sprague motor proved very inferior to some of its competitors,
due to overheating when running at low speeds. Nevertheless,
with all of its weaknesses, this Sprague double-reduction motor
must be considered as the high class one of its day,
THE THOMSON-HOUSTON MOTOR
In general, the Thomson-Houston motor was of the same
general type as the Sprague. The magnet core was of wrought iron,
or equivalent material. The armature was of the usual surface-
wound type. Unlike the Sprague motor, speed control was only
partially obtained by varying the field strength. The field was
wound with loops or taps brought out near the middle of its
length. For starting and acceleration, the full field winding was
used with a rheostat in series. To accelerate, the rheostat was cut
out gradually and for still higher speed, only part of the field wind-
ing was used, the other part remaining idle. Thus there was no
true series-paralleling of the field windings. This method of opera-
tion, therefore, was less economical than the Sprague arrangement
but, on the other hand, the proportions of the field winding and the
rheostat were such that the motor could stand more severe con-
ditions during starting and acceleration. The field magmetic cir-
cuit was apparently much more highly saturated than that of the
Sprague motor, resulting in a flatter speed curve. In consequence
this motor would run somewhat faster than the Sprague on heavy
load, and was considered by many operators as a better hill
climber, simply because it ran faster up hill. Due to its lower
saturation, the Sprague motor tended to drop off very considerably
in speed on heavy grades and this was considered an evidence of
STREET RAILWA Y MOTOR IN AMERICA 72o
weakness, that is, of lack of power; whereas, in fact, it was a real
merit in those days of limited power supply. The range of current
taken by this Thomson-Houston motor, due to its flatter speed
characteristics, was apparently considerably greater than that of
other types of railway motors. The commutation on this motor
was apparently very good compared with the Sprague motor. In
fact, the latter, according to the writer's experience, appeared to
be one of the poorest commutatitig motors on the market. Never-
theless, due to its special method of control and the consequent
FIG. 2— THOMSON-HOUSTON DOUBLE REDUCTION MOTOR— P-30
smaller currents required, this poorer commutation did not seem
to have as harmful effects as one would infer from looking at it.
In other words, the commutator of the Sprague motor had about
as good life as any of the others.
One thing that counted against good commutation on these
early motors was the extremely heavy mica between commutators
bars. One-sixteenth inch mica was not at all uncommon on such
motors and when trouble developed at the commutator, there was
frequently a cry for thicker mica and, as a consequence, the thicker
the mica the greater the trouble. This persisted up into the later
motor practice and was a source of much trouble for several years.
THB SHORT MOTOR
In construction, the Short railway motor was a close relative of
the Brush arc machine, that is, its magnetic circuit and other parts
were arranged very similarly to that of the arc machine. A disc
armatttre was used with polefaces presented at the sides of thearma-
tuxe, The early machines were of a two-pole type and later
726 ELECTRICAL ENGINEERING PAPERS
general construction was developed in four poles in connection
with later Short systems. The armature of this Short motor was of a
.toothed type, this also being apparently a development from the
Brush arc machine, It is questionable whether the teeth on this
armature were proportioned for magnetic purposes or for mechan-
ical. The teeth were few in number and the slots between were
quite wide. Magnetically the arrangement might be considered
as some improvement over the surface-wound type, but the pro-
portions were not such as would be considered effective, even in the
true slotted types of armatures which followed two or three years
later.
This Short type railway motor contained a number of more or
less fundamental defects, which in the end were sufficient to rule
out the type. In the first place, due to the disc type of construc-
tion and side poles, there was a tendency for strong unbalanced
side pull between the armature and the pole pieces, and strong
thrust collars were necessary to overcome this. On account of this
PIG. 3— SHORT DOUBLE REDUCTION MOTOR— 1890
arrangement no end play was permissible, as in ordinary railway
motors. In the second place, the method of connection between the
commutator and armature winding was a very awkward one,
since the armature leads had to be carried radially to the shaft and
then along the shaft to the commutator. In the third place, with
this general construction, a non-magnetic spider had to be used, as
a rule. This meant a construction which was not as solid 6r as
durable as was obtainable with the cylindrical drum, type of arma-
STREET RAILWA Y MOTOR IN AMERICA 727
ture with the laminations pressed directly ou the shaft or upon
a cylindrical supporting spider.
Even with all these defects this type of machine was continued
for several years and was carried into the single reduction type and
into the gearless, when the construction was somewhat simplified
by the use of four and six poles respectively. However, the type
was destined to disappear due to fundamental defects, and ap-
parently only the persistency of Professor Short, who originated
it, kept it going as long as it did. Eventually Professor Short him-
self abandoned the type, when he put out the Walker motor, which
will be mentioned later.
WESTINGHOUSE MOTOR
The remaining double-reduction motor, which made any con-
siderable impression on the railway field, was the Westinghouse.
This was brought out in the Spring of 1890, somewhat later than
the other systems mentioned. In general type, this motor was quite
similar to the Sprague and the Thomson-Houston. However, the
field core was of cast iron and the motor was, therefore, somewhat
heavier than its competitors. The armature was surface-wound
and similar to almost all railway motors of that time. The field
winding was arranged in two coils without metal "bobbins," with
different sizes of wire and different numbers of turns. For starting,
all field windings were in series and the rheostat was connected in
series. For higher speed the smaller winding was cut out. Ob-
viously, this arrangement was electrically very similar to the
Thomson-Houston.
The principal differences were in details of the mechanical con-
struction. The fields were hinged to the supporting yoke in such a
way that they could swing back to give more easy access to the
armature. Also the gears were enclosed in gear cases which were
filled with lubricating grease. The purpose was to overcome the
very objectionable noises of the double reduction gears. Anyone
who is familiar only with the present gear noises from traction
motors can have no comprehension of the fearful racket some of
the double-reduction equipments made, especially after the gears
had worn badly. At night, when other noises had ceased to a
great extent, the electric cars could be heard, in some cases, at a
distance of one to two miles*
On many of the early double-reduction eqtdpments cast iroa
gears were used and, as a consequence, stripped gears were riot
728
ELECTRICAL ENGINEERING PAPERS
uncommon. In those days cars were operated under conditions
which no one would dream of attempting in these times. In one
case, in the writer's experience, a track was being repaired in a
certain part of Allegheny City and the only way to get around
it was to run up a parallel street and part way over a cross street
to the end of the track, which was about thirty feet from the
original track. This intervening section, paved with rough cobble
stones, was overcome by getting the car up to considerable speed
FIG. 4—500 VOLT WESTINGHOUSB DOUBLE REDUCTION MOTOR— 1890
and running across the space by means of inertia. If the car did
not get across, then a long wire was carried from the controller
on the car back to the end of the truck and thus a "ground" was
obtained for covering the rest of the way. In one instance, a car
was stalled in this section and the motorman left his controller
on "full " position while he carried his conducting wire back to the
end of the track. Upon touching the rail, the car did not move out
of its steps, so as to speak, but simply gave a jerk and the gears
were stripped.
The Westinghouse double-reduction motor was made of cast
iron, but its operating characteristics were quite comparable with
STREET RAILWAY MOTOR IN AMERICA 729
the other systems, except the Sprague. However, although a con-
siderable number of these motors were put out in 1890, the writer,
along with certain other engineers of that time, did not believe
that any one of the then existing railway systems was final,
due primarily to the fact that the motors were too susceptible to
injury, not being sufficiently protected in view of their location
under the car. It was believed that it was merely a question of time
when all such motors would have to be rebuilt. The first West-
inghouse motor was put in service in Allegheny, Pa., on July 3,
1890. This date is given to indicate the short time which elapsed
before the writer, who had been instrumental in getting out this
Westinghouse system, undertook to get out a radically different
system to supersede it.
GENERAL TREND OP DEVELOPMENT
The above brings us up to the period when the single-reduction
motor was developed. The double-reduction motor very quickly
disappeared from the market after the single-reduction arrived,
but it must be said that the double-reduction motor, and the early
system as a whole, left its impress on the future development.
There were several features in this early development which sur-
vive even to the present time, such as the use of carbon brushes,
series-wound motors, motors suspended from the axles and geared
to them, enclosing gear cases with grease lubrication, mummified
field coils, under-running trolley, platform controllers, etc. The
fact that a number of these features have survived in very much
their original form indicates that they were fundamental in their
nature. The early designers of such systems must be given credit
for a quite comprehensive knowledge of the real problem of electric
traction* Their short-comings were more in their inability to con-
struct, than in their lack of knowledge of the correct principles.
Those early days were times of experimentation by the
operators as well as by the manufacturers and it was not an unusual
thing for a small electric system to have two or three different
types of equipment, and in one case in a small system near Pitts-
burgh having seven cars total, there were five different kinds of
equipment at one time. Furthermore, the operator was rathet
proud of the situation. In this early work there were a number of
points which were taken v^ry seriously in those dayg, but which,*
from the present iriewpomt, are rather amttsfog,
730 ELECTRICAL ENGINEERING PAPERS
For example: The earth was considered as being of negative
potential and, therefore, many Engineers (or so-called engineers)
held the opinion that the positive terminal of the motor could not
be connected with safety to the ground side as there was danger
of a short-circuit. The writer spent many weary hours attempting
to show some people the absurdity of this opinion, but generally
without success.
Also another subject on which there was considerable contro-
versy was that of large-diameter vs. small-diameter armatures.
Many people contended that even with the same horse-power and
speed a large diameter armature necessarily gave more tractive
effort than a smaller diameter.
There was also much discussion concerning the speed and
power characteristics of the various motors. Certain makes of
motors ran faster up hill than others. The Sprague motor, for
instance, was a slow hill climber; on the other hand, the Thomson-
Houston double-reduction motor was a fast hill climber and the
Westinghouse was in between. As a rule, most people believed
that the Thomson-Houston motor was, therefore, a more powerful
one than either of its competitors. The writer had quite frequent
contentions that the Sprague type of motor, with its drooping
speed characteristics, was more nearly ideal for railway work than
the Thomson-Houston with its flatter speed curve. His claim was
that the drooping speed characteristics called for a more uniform
and a lower average current from the generating system, and there-
fore, required less generating plant, He contended that the place to
make speed was on the level and rjot on the hills. Apparently this
argument has never been definitely decided in favor of either view-
point, but today it is generally recognized that the steeper speed
characteristic is a more economical one as far as the generating
or transmission system is concerned.
In comparing the merits of these early types of motors, a not
unusual test was to couple cars with two different makes of equip-
ments, end to end and then determine which could outpull the
other, starting from "rest." Of course, a good deal depended upon
the skill of the motorrnen, but in many cases those motors with
drooping speed characteristics had the advantage, and therefore,
according to this test, were more powerful, although when it caxne
to climbing hills they were supposed to be less powerful. Here was
a contradiction which puzzled a great many people.
STREET RAILWAY MOTOR IN AMERICA 7,'U
One interesting feature in connection with the early motors
may be dwelt on more extensively, namely, the use of the series
motor. Very early in the development, shunt motors were tried
but it was soon recognized that they did not meet practical condi-
tions, and the scries motor was adopted exclusively. However, in
the use of the series motor itself there were certain differences in
practice. For instance, most of the railway systems paralleled the
field windings and the armatures, independently. For reversing it
was necessary to bring out leads between each armature and its
field windings, and the field windings of the different motors were
permanently paralleled with each other. The same was true of the
armatures. Then by means of one reversing switch all the arma-
tures, or all the fields, could be reversed. In the Thomson-Houston
system, however, the different field coils and armatures were not
paralleled with each other, but separate reversing switches were
supplied for each motor. Obviously this required more wiring and
reversing switches than the other systems and was a subject of
much criticism. But, this arrangement was fundamentally correct,
and has come down to the present day. The other methods, with
paralleled field coils, were subject to the difficulty that there could
be greatly unbalanced currents in the armatures, where the mag-
netic fields were not of equal strength ; whereas, with the Thomson*
Houston motors there could only be unbalanced currents between
the motors as a whole and not between individual armatures, and
any unbalance in the current in the field coils tended automatically
to correct the difficulty.
In the double-reduction motors, with their excesssively large
air-gaps compared with later practice, differences in the magnetic
properties of the materials did not count for much becaxise such a
large percentage of the field magnetizing force was expended in the
air-gaps. However, when it came to the later single-reduction
motors, with their smaller air-gaps and higher saturation in the
cores, the fallacy in the parallel arrangement of the field coils began
to show up quite early.
SINGLE REDUCTION MOTORS
In August, 1890, the writer began work on a radically new
type of railway motor of only about one-third the speed of the
ordinary motor, with a view to using only one gear reduction
between the armature and axle* In goittg into this matter mw
the electrical and magnetic standpoint, it soon developed that tito
732 ELECTRICAL ENGINEERING PAPERS
surface-wound type of armature was impracticable. Furthermore,
it became evident that a cylindrical type of field construction with
inwardly projecting poles, such as was common in alternators in
those days, would furnish magnetic conditions much better than
any previous type, provided more than two poles were used. The
writer then laid out a four-pole field construction with radial poles
and external cylindrical type yoke, and with a slotted type of
armature. It was at once obvious that such type of machine was
inherently better protected than the ordinary construction, due
to the external yoke. However, in this general construction one
serious stumbling block appeared, namely, the fact that for acces-
sibility only two sets of brushes were desirable with a four-pole
armature. This appeared to be quite a problem, for apparently
the only known solution was in cross-connecting the commutator
at every bar, which was at that time a fairly well-known construc-
tion. This construction, however, appeared to the writer to be
prohibitive and he, therefore, set out to devise some other arrange-
ment, and in doing so developed the now well known two-circuit or
series type of winding for "drum" armatures. A great deal of
criticism appeared in connection with this winding, but the writer
was nevertheless sure of the principle and felt confident that it was
a correct solution of the problem, and his confidence was sufficient
to carry it through to a test. Two trial motors were built of this
general construction, in the Fall of 1890. In these two early motors
the lower half of the field yoke, or frame, was carried out and
upward, forming housings which enclosed the lower half of the
field winding and shielded the armature from injury from below.
The two brush arms were placed on the upper quadrants of the
armature, making them more accessible.
The armatures of these two motors were of the slotted type,
with ninety-five slots (one less than a multiple of the number of
poles, on account of the two-circuit winding). At first, attempts
were made to wind these armatures by hand, but it was quickly
recognized that this would be a rather doubtful construction and
the writer proposed machine-wound coils which were at once made
up and tried on the cores. Various modifications were tried on
these first sets of coils and one attempt was made to shape the coils
in such a manner that they would all be exact duplicates and could
be placed symmetrically on the armature, in two layers in the slots,
one half of each coil being in the lower layer, the other half on top,
just as in modern railway armatures. We succeeded in getting
STREET RAILWAY MOTOR IN AMERICA
733
about two-thirds of the winding in place in this manner, but then
the end parts began to interfere so that \ve failed in getting the
other one-third in place, and this experiment was temporarily
given up. It developed later that a little more knowledge of the
correct shape of the coil would have allowed a successful construc-
tion of this type, and thus one of the big steps in the later develop-
ment would have been anticipated. However, after several weeks
of experimenting, it was decided to put the machine wound coils
PIG. S— DIAGRAM OF WENSTROM MOTOR— 1890
on in two layers, hammering down the ends of the first layer in
order to obtain end space for the second. With this arrangement,
machine-wound coils ^rere used successfully and the first two
armatures were then wound in this manner, the writer personally
winding one of them, although not an experienced winder.
The first completed machine was put on test and at the first
trial, for a wonder, it started off and performed admirably over the
whole range for which it was designed* The commutation was very
good — unexpectedly so — as this was one of the points where
trouble was feared. The two-circuit type of winding functioned as
expected. By good fortune, one big departure from previous
practice proved to be a stepping-stone to later work, namely, in
these first machines the mica between commutator bars had been
made only 1-32 in. thick; whereas, in double-reduction types of
motors 1-16 in* mica was common practice* This "thin** tmca,
however, was objected to so seriously by almost everybody in-
terested, that on the following motors it was changed to practicaJly
double thickness, but with, disastrous results, as will be described
later* This first Westinghouse siagleHt^uctiofr motor was tested
734 ELECTRICAL ENGINEERING PAPERS
in the Fall of 1890, but was not considered quite ready for the
market from the manufacturing standpoint, although in its elec-
trical characteristics it had proven entirely satisfactory. It was
decided to improve the motor by hinging the two halves of the
cylindrical field to a supporting frame which carried the armature
and axle bearings It was also decided to enclose more completely
the lower half of the frame so that the armature and field would be
protected from below. The motor was considered to be a very
radical step, and it was thought advisable to take ample time in
getting it ready for the market.
THE WENSTROM MOTOR
Meanwhile, during this development, a situation arose which
materially hurried up the work. The Wenstrom Company came
out with a single-reduction motor which was heralded as being
revolutionary in character. This motor was of the foxir-pole type
with two salient and two consequent poles The armature
was of a four-pole type. The armature winding was imbedded in
holes or tunnels below the surface of the core. This armature was,
therefore, one form of the slotted type. This machine created such
interest that it was immediately decided to rush the completion of
the Westinghouse motor for the next Spring trade, whereas, the
former intention had been to continue the double-reduction motor
for sometime to come. Moreover, the appearance of this Wenstrom
motor immediately hurried all other motor manufacturers in their
development of single-reduction motors. Apparently a number of
them had already been working on this line, for their new single-
reduction motors appeared so quickly on the market, that there
was good reason to believe that they had already partly developed
the machines before the demand came. Some of these motors were
put on the market before they were properly developed and they
proved to be merely makeshifts to be superseded soon by radically
different types. This Wenstrom motor did not persist as it ap-
parently contained certain defects which put it ' ' out of the running "
before it had gotten very far. It, however, hurried the situation
very materially,
WESTINGHOUSE No. 3 MOTOR
The commercial single-reduction motor, which the Westing-
house Company put out in the Spring of 1891 was simply a further
development of the experimental Westinghouse four-pole single-
reduction motor already described. This motor immediately "took"
STREET RAILWA Y MOTOR IN A MRRICA 735
and a very large number (for those times/ was sold1 the first'season.
In fact the demand for this motor was so pronounced that the
company could not dispose of all of the double-reduction motors
on hand partly or wholly completed
This No. 3 motor might be called the progenitor of the present
practically universal type of direct-current railway motor. It con-
tained a fairly large number of the fundamental features found in
the present motors. Some of these may be classified as follows : —
1 — Four-pole field construction with internal radial poles.
2 — Symmetrical flux distribution, thus improving commutation.
3 — Four coils all similar in size and shape.
4 — Field coils without bobbins or supports, each coil being wound on a
form and afterwards insulated.
5 — Electrical parts naturally protected from below by the iron-clad con-
struction of the magnetic circuit and frame.
•6 — Four-pole slotted drum typ-* armature \vith open slots.
7 — Machine wound armature coils, insulated before being placed on core,
8 — Two-circuit or series direct-current armature winding, which is in
almost universal use at present for railway work.
9 — Saturated pole tips.
In addition the first motors built had 1-32 in, mica, which is
now a standard for such work. However, on later No, 3 motors,
the mica was changed to practically double this thickness, on ac-
count of the general insistence that 1-32 in. mica was utterly
impracticable from the commercial standpoint. In the early days
of the railway motor, thick mica was supposed to be the " cure-all"
for all flashing troubles. If the mica did not wear fast enough, and
lifted off the brushes, the machine sooner or later would spark and
flash badly, The cry would be for more mica and, in some cases,
thicknesses of as much as 1-8 in. were used, but without advantage
as far as the writer could see, but the claim was made that the
trade absolutely required such mica.
The writer and his associates yielded to this demand, with
unfortunate results, The motors with thicker mica soon developed
blackening and burning at the commutators, and the only direct
remedy found for this was undercutting the mica. This was prac-
ticed on a number of the first motors put out, but was considered
such an impossible practice that it was evident that some other
remedy was necessary. Meanwhile the first two experimental
motors had been running in regular service on the Second Avenue
Line in Pittsburgh, and had developed no trouble whatever from
commutator blackening or burning* After axx exhaustive uavestt*
gation of the conditions, the writer recommended going b&ok to
736 ELECTRICAL ENGINEERING PAPERS
the 1-32 in. mica, regardless of any demands to the contrary. A
large number of the commutators with thick mica were then
replaced with this thinner mica and the results were soon apparent
in the fact that undercutting was unnecessary. This was con-
clusive proof that the thinner mica was a solution of the problem.
However, it must be borne in mind that even the 1-32 in. mica of
that early date (1891), was inferior to modern mica in wearing
characteristics, as it was simply punched out of solid mica, the only
sub-division being the splitting up of the mica segments into thin
sheets and then assembling again in exactly the same form. ' ' Mica-
nite" or built-up mica did not appear until some time after this.
This No. 3 motor was very heavy for several reasons. It had
a cast iron magnetic circuit; it had a relatively low gear ratio com-
FIG. 6— WESTINGHOUSE No. 3 MO TOR— 1891
pared with later practice, as it used an eighteen-tooth pinion and a
sixty-four-tooth gear. In service, one difficulty soon showed itself,
which had not been noticed in the corresponding double-reduction
motors, namely, a very decided tendency to unbalance, in the
armature currents of the two motors on a car. It was soon found
that this was due to unequal counter-e. m. f.'s due to inequalities
in field material, slight differences in manufacture, etc. On account
of the relatively small air-gap, errors in manufacture produced an
exaggerated effect. However, this difficulty was overcome by ad-
justing the air-gaps of the motors. It happened that this could be
easily done by means of the two hinged halves of the fields. This
arrangement permitted the motor to be opened slightly at the two
STREET RAILWAY MOTOR IN AMERICA 737
opposite joints, so that sheet iron liners of suitable thickness could
be inserted in the joints of one motor until a suitable balance in the
currents was obtained. It so happened that the Westinghouse
Company had on hand a large stock of small compact ammeters
built for the Waterhouse arc system, which had practically become
obsolete. Little testing sets were made, using two of these am-
meters mounted on a supporting base. These were furnished to the
customers for use in balancing their car motors. Later the
straight series arrangement of armature and fields was adopted
and this unbalancing trouble was thereafter negligible.
When the single-reduction motors first came in, one of the
subjects for frequent argument was in regard to the torque which
such motors could develop. Many people claimed that inherently
the single-reduction motor could not pull a car as well as the
FIG. 7— THOMSON-HOUSTON SINGLE REDUCTION MOTOR— 1891
double-reduction, even at the same horse-power rating, when de-
veloping the same car speed. This even went so far as to result in
competitive tests. In one case in the writers experience, a com-
petitive test was run, about 1891, on the Second Avenue Railway
under the impression that such a test would prove conclusively
that the single-reduction motors did not have the required torque,
and, therefore, would take enormous currents compared with the
double-reduction. Local representatives of the Thomson*Houston
Company agreed to, and took part in, this test, but apparently
without any definite opinions as to which equipment would make
the better showing. The test was continued during the greater part
of one day, several round trips being tatoa over the whole tagtth
738 ELECTRICAL ENGINEERING PAPERS
of the system, and current and voltage readings were taken at ten-
second intervals. An interesting result, noticeable during the
progress of the test, was that the Westinghouse equipment seldom
took less than 25 to 30 amperes when running light and seldom
above 60 to 70 amperes under the heaviest conditions; whereas,
the Thomson-Houston equipment at times took as low as 10 am-
peres and at other times up to 100 amperes. This was just what
the writer expected, from his knowledge of the speed character-
istics of the two machines, and he did not consider that the tests
proved anything more than the general characteristics of the two
machines would indicate. However, most of those present com-
pared the maximum currents taken by the two equipments and
drew the conclusion at once that the single-reduction was more
economical. The writer, however, did not consider this a just
comparison and took the trouble to carefully analyze the whole set
of readings and found that the total power consumptions for the
two equipments were so nearly equal that differences in the motor-
men's method of operation could easily account for any discrepan-
cies. As a result of this test many people who heard of it revised
their opinions of the pulling characteristics of the single-reduction
equipment.
THOMSON-HOUSTON SINGLE-REDUCTION MOTOR (S, R. G.)
This was one of the motors which was rushed on the market
shortly after the Wenstrom motor appeared. It was a two-pole ma-
chine. The magnetic core was made of wrought iron in order to
keep down the weight. The armature of this machine, according
to the writer's memory, was of the ring type. From the electrical
standpoint this motor was no improvement over the old double-
reduction, and the ring armature in reality proved to be much
poorer than the drum type used on the Thomson-Houston double-
reduction motors. In fact, the only real merit of this machine was
in its lower speed, thus allowing single-reduction gears. An at-
tempt was made to protect this machine by an encasing or pro-
tecting sheet metal pan underneath. This pan was to a certain
extent effective, but unless rigidly supported it made very notice-
able noise, due to vibration.
STREET* RAILllrA V MO'WRJX AMERICA 730
W P. MOTOR
It was soon recognized that the S, R. G. motor was not a
permanent one, so that very soon a new type was gotten out,
namely, the " W. P." (weather-proof). This was an enclosed motor
and it was, from the electrical and magnetic standpoint, of a very
peculiar design. There was but one field coil, placed above the
armature. The armature itself was of very large diameter and
weight and of the slotted type, with partially closed slots and the
winding was of the ring type. The winding consisted of a copper
ribbon threaded through the openings at the top of the slots and
was wound in place by hand. On account of the magnetic arrange-
ment, a non-magnetic spider was necessary . Alsoonaccountofthere
being only one magnetizing coil there was some stray field out
through the shaft and bearings. This, of course, was minimized to
a great extent by the non-magnetic spider. Possibly one of the
worst features in this W. P. motor was the unsymmetrical corn-
mutating zone. Due to the type of the magnetic circuit, the flux
distributions were not symmetrical under the two Doles. Further-
more the armature reaction tended to distort the field quite seriously,
thus affecting the commutating conditions. Very heavy mica was
used in commutator and sparking was so bad that the life of com-
mutator, in many cases, was only a few months. The armature
leads had "eye" terminals to permit easy change of commutators,
In order to keep down the weight, this W. P. motor was either
xnade of steel or an iron-aluminum alloy of good magnetic proper-
ties. This motor survived for a number of years, but due to in-
herent defects in its characteristics and construction it was doomed
to eventual obsolescence. The ring type of armature and the un-
symmetrical flux distributions were two conditions sufficient to con-
demn this machine, from the present viewpoint. However, it must
be borne in mind that in those days certain features were considered
very meritorious which now would be looked upon as prohibitive,
the ring type of armature being one example. This W. P. motor
had its place in the ultimate development of railway apparatus,
regardless of the fact that it did not survive,
EDISON SINGLE-REDUCTION MOTOR
The Sprague double-reductiott motor was one of the best of
its type, and 'persisted longest of any of this type. However,, the
Edison Company who had taken over tbe manufacture of the
Sprague xaotor, finally -recognised that the day of the
740 ELECTRICAL ENGINEERING PAPERS
reduction motor was past and a single-reduction motor was then
gotten out. This was a steel frame four-pole motor. The armature
was of comparatively large diameter and, according to the writer's
memory, was of the surface-wound type.* An attempt was made
to retain some of the features of the Sprague double-reduction
motor, by having commutated field coils, but due to the more
highly saturated magnetic circuits, this was not very satisfactory.
FIG 8— EDISON SINGLE REDUCTION MOTOR— 1891
This motor had a comparatively short commercial life and it was
evidently simply rushed into the market to meet the competition
of other single-reduction motors.
THE SHORT SINGLE-REDUCTION MOTOR
Professor Short, early recognizing the trend of development,
got out a single-reduction railway motor along lines somewhat
similar to his former double-reduction. The principal difference
was that this new motor was of a four-pole instead of two-pole
type. The disc type of armature, with side poles, was retained
along with most of the other characteristic features of the older
motor. This motor attracted much attention, but as it possessed
a number of fundamentally wrong features, such as a ring type of
armature, danger from unbalanced side pull, etc,, it was a type
which was doomed to disappear eventually.
*Mr. W. E. Moore, Consulting Engineer, writes the author as follows:
4 'The old Edison S.R G motor had a Gramme ring armature: the coils beiagwound
of flat copper ribbon in a toothed core. This motor was built in two sizes. The one
which you illustrate in Figure No 8 was the smaller size, known as the Edison No, 14,
The larger size was known as the Edison No 16, which was quite similar, except that the
armature bearings were earned in arms projecting from the axle housing forward, instead
of the vertical yokes and the consequent pole pieces ware split vertically, with A hinge on
top and bolted together at the bottom for removal of the armature."
STREET RAILWAY MOTOR IN AMERICA 741
In this early period of the single-reduction motor, the belief
was held, rather generally, that the ring-type railway armature was
essentially superior to the drum- type. As the Wcstinghouse Com*
pany never put out anything but the drum-type railway armatures
and as, at different stages in the early development, several of the
competing companies used the ring-type, the writer was "hard
put " at times to defend his company's practice. Many and long
were the arguments which he had on this score. At one time it
looked, to an outsider, as if the ring-type was capturing the field.
This was when the Short single-reduction motor and the Thomson*
Houston "WP" were the principal competitors of the Westing-
house single-reduction. Both the former motors had ring-type
armatures against the Westinghouse drum-type. However, prac-
tical operation gradually developed thfe superiority of the drum-
FIG. 9— SHORT SINGLE REDUCTION OR WATER TIGHT MOTOR
type and the use of machine-wound armature coils had much to do
with deciding the problem, for unquestionably the machine-
wound armature coil was much more applicable to the drum-type
than to the ring-type. Moreover, there were inherent weaknesses
in the ring-type, such as the use of non-magnetic spiders, methods
of attaching the spider to the core, etc. In the light of present
experience, it is surprising that the ring-type armature made as
good showing as it did*
GEARLESS MOTORS
Following the success of the single-reduction motors, two of
the companies, txamely , the Westioghouse and the Short, attempted
to make gearless motors alon^ the same geneiul lines as the single
type, Thfc Weetata^bouse Cotaypariy pat out two
742 ELECTRICAL ENGINEERING PAPERS
stractions, one having four poles and the other having six, the
latter being considerably lighter. However, both of these motors
were too heaw and it soon developed that the gearless principle
was not a satisfactory one for ordinary street car purposes, due
largely to undue weight directly on the axle, and to the difficulty
in removing an armature from the axle, in case it was necessary for
repair purposes.
The Short Company built a gearless motor along the same
lines as its single-reduction and tested it out in practice, but it was
soon abandoned for the same general reason as the Westinghouse,
namely, that the gearless principle was fundamentally incorrect
for ordinary street railway service.
FURTHER DEVELOPMENTS OF SINGLE-REDUCTION MOTORS
As indicated, the Edison motor soon dropped out of the run-
ning. It contained nothing lasting in its type. Also, although it
persisted longer than the Edison, the Short type gradually dropped
out. Meanwhile the Edison and the Thomson-Houston Compan-
ies had combined and formed the General Electric Company.
This company continued to develop its railway motors in the at-
tempt to find something better than its W. P., already described.
The Westinghouse Company also persisted in its development,
principally with a view to reducing the size and weight of the No. 3
motor. The future development of the railway motors, therefore,
lies almost entirely with these two companies.
The Walker Company, about 1895 or 1896, appeared on the
market with a railway motor and did a very considerable amount
of business until absorbed by the Westinghouse Company. The
Lorain motor attracted considerable attention for a time, but was
also taken over by the Westinghouse Company* Both of these
were so nearly along the general lines of the Westinghouse, that
they need not be considered as special types,
LATER TYPES OP WESTINGHOUSE MOTORS
After the No. 3 Westinghouse motor had proved to be com-
mercially a very successful type, the writer turned his attention
toward improvement in its general type without losing any of the
more advantageous features. One of the features in the design of
the No. 3 was the use of as many slots in the armature as there were
armature coils and commutator bars. This was supposed to give
ideal magnetic symmetry and, therefore, was assumed to be the
STREET RAILWAY MOTOR IN AMERICA 743
best possible arrangement. However, the writer in going over the
magnetic principles and proportions of the motor, decided that by
sacrificing magnetic symmetry to a certain extent, considerable
gains could be made in reducing the dimensions of the machine.
For instance, calculations indicated that by cutting the number of
armature slots to half the number of armature coils or commutator
bars, there would be an appreciable saving in slot space with a cor-
responding gain in iron section in the armature teeth which war>
one of the limiting conditions in the machine. However, this in*
volved the use of two coils side by side per slot and, with a four
pole machine it meant an unsyrnmetrical armature winding, for
FIG. 10— WBSTINGHOUSE NO. 12 MOTOR
with the two-circuit winding on a four-pole machine, an odd num-
ber of armature coils was necessary. This meant an idle coil, or idle
coil space, on the armature. This was considered as detrimental in
theory, but, on the other hand, it was believed that the wider arma-
ture slots with their lower self-induction, together with the much
shorter armature core resulting from this construction, might com-
pensate for some dissymmetry in the winding. This was coaly a
theory, but it was tjxottght worth while trying out* According to the
calculations, with tibfe constmctioja together "with higher spaed daft
to increased gear ratio, the old No, 3 itt&tor
744 ELECTRICAL ENGINEERING PAPERS
same diameter) could be shortened about 40 per cent and the field
could be modified in proportion. This meant a very considerable
reduction in size and weight and was well worth going after. A
trial machine was built and tested and, instead of being materially
poorer in commutation, it developed that the gain due to the wider
slots and shorter core, more than offset any harmful effects of the
unsymmetrical winding, so that the resultant machine was a
somewhat better commutating, cooler, more efficient and much
lighter machine than the No. 3. This was a somewhat startling
result, but the tests showed conclusively that it was correct. It
PIG. 11— ARMATURE OF WESTINGHOUSE NO. 12 MOTOR
was then arranged to bring out a new Westinghouse motor to take
the place of the No. 3. It was decided to go as far as possible in
reducing the dimensions and weight of this machine and, therefore,
the supporting or surrounding frame of the No. 3 motor was aban-
doned and extensions from the yoke of the motor itself, forming
the end housings, were designed to carry the armature bearings,
In this way a further reduction in weight resulted.
THE WESTINGHOUSE No. 12 MOTOR
This new motor was known as the Westinghouse No. 12. In
this motor the lower half of the field was enclosed by means of the
end housings. The armature winding was of the formed-coil type,
like the No. 3, arranged in two layers and with the end windings
hammered down.
Very shortly after this motor was put out an improved f orm,
known as the No. 12*A was brought out. This was quite similar
in general to the No. 12. The principal improvement in the No.
12-A was in the armature construction. The armature core was-
ventilated, to secure increased continuous capacity and the arma-
STREET RAILWA Y MOTOR IN AMERICA 745
ture winding was of the modern type with all coils of the same size
and shape, and arranged symmetrically. The armature core of this
machine was quite highly saturated at heavy load and this was
found to materially improve the commutation. This No. 12-A
motor was found to be quite superior to any preceding motors in
its general characteristics, especially in its continuous capacity.
In its field construction it resembled the old No. 3, in the fact
that it had cast iron yoke and poles and the field poles were cast
integral with the yoke and were straight-sided so that the field coils
could be slipped on directly over the pole tips. There was one
feature in these motors and their variations which materially af-
1 1 1
,r - I
FIG. 12— WESTINGH00SE No, 3» MOTOR
fected their operation, but which was not fully appreciated at the
time they had been designed, namely, the effect of the cast-iron
poles in improving the commutation. The pole tips of these motors,
as a rule, were somewhat smaller in cross-section than the pole,
bodies or cores and, theref orre, there was quite high saturation in
the pole tips, particularly at heavy load. This high saturation had
very much the effect of the " cut-away" pole corners, used later
on laminated pole machines.
THE WBSTINGHOUSB No. 38 MOTOR
Recognizing that in the No. 12-A motor the general type of
construction had been carried as far as possible, due to the Httuta-
tiotis in the cast-iron field structure, it was decided to attempt a
different field construction, in which the limitations in* design
cottld be pushed up very considerably. This was embodied in the *
746 ELECTRICAL ENGINEERING PAPERS
Westinghouse No. 38 motor. This motor, in general type, was
similar to the No. 12-A, except that in the first motor built, the
field was made of solid cast steel, both poles and yoke, with the
poles cast integral with the yoke. This construction allowed very
materially higher field fluxes than in the former motors, so much
so that again the armature teeth became the limit in saturation.
Therefore, in the armature three coils per slot were used instead o£
two, thus gaining in armature tooth section. This, the writer be-
lieves, was the first use of the three-coil-per-slot arrangement in
railway motors. This first No. 38 solid-steel-pole motor showed
unduly high losses due to the solid-pole construction. Immediately
it was changed to laminated pole construction with the poles cast
integral with the yoke. This apparently was the first use of lamin-
ated poles with steel yokes, in street railway motors.
This No. 38 motor represented, with minor differences, the
present type of railway motor. One principal difference was in the
cast-in laminated poles, instead of the present practice of bolted-in
laminated poles It had ventilated armature windings and relatively
high saturation in the armature core to help commutation at heavy
loads. Also with the three-coil-per-slot arrangement, with four
poles, a more symmetrical armature winding was possible than in
the two-coil-per-slot No. 12-A motor, there being no idle coils. In
the former motors the bearings were lubricated with grease, as was
common practice in all motors at that time. However, when
heavier and more difficult service was encountered, as was the case
with the No. 38, which was of higher capacity than most of the
former motors, it was found that the grease method was not very
effective. This resulted in a modification which provided a felt
wick and an oil well under both the armature and axle bearings, so
that the motor was adapted for use either with grease or oil. This
was on the No. 38-B , which was a modification of the No. 38, Like
all compromises which attempt to adopt all the good features of all
methods, it was only moderately successful, although it served to
keep the motors in service for many years.
WESTINGHOUSE No. 49 MOTOR
This motor had much the same lines as the No. 38-B. It had
laminated poles cast in. The fractional pitch or "chorded" type
of armature winding was purposely used in this motor to improve
commutation, careful shop tests being made with an approximately
STREET RAILWA Y MOTOR IN AMERICA 747
full pitch and with various chorded windings to find what would
give the best result. It was found that a " throw " of the armature
coil, one and one-quarter slots less than full pitch, gave materially
better commutation than any other combination. Chorded wind-
ings had been used on other types of machinery, to a limited
extent, before this,but it is believed that this was the first time that
it was used on a railway motor purely for the purpose of improving
commutation.
THE G. E. No. 800 MOTOR
This was a new motor gotten out by the General Electric
Company to replace the W. P. It was a four-pole machine with
two salient and two consequent poles. This was a more symmetrical
type of machine than the W. P., but yet was not a purely sym-
metrical machine, such as the Westinghouse motors from No. 3 on,
and the later types of G. E. motors. Its designation of No. 800,
was a new method of rating, to indicate its tractive effort instead
of its horse-power. Its nominal rating was about 27 h.p, This
tractive effort method of rating was carried into several other sizes
such as the G, E. 1200 and G. E. 1000.
PIG. 13— G. E. 800 MOTOK \VITH COMMUTATOR LID OPEN
This G. E. No. 800 motor was a very considerable improve-
ment over the W. P., but possessed certain fundamental defects.
For instance, the consequent pole arrangement meant very con-
siderable magnetic fluxes, through the shaft and bearings with con-*
sequent tendency for unipolar action in the bearings, tha bearing
shells and stuiaoe foi^ng tOie coUectiug brushes. Therefore, th«re
748 ELECTRICAL ENGINEERING PAPERS
was a tendency for current in such bearings, as in all consequent-
pole machines. It may be assumed that this defect was encountered,
for in some of these motors very deep bronze shells were used, ap-
parently for the purpose of introducing so large a gap in the shaft
magnetic path that the flux through the bearings would be mini-
mized to a non-injurious point. Moreover as in consequent-pole
machines in general, the commutating zones were not truly sym-
metrical and thus commutation troubles were, to a certain extent,
existent.
A similar motor to the No. 800 was the No. 1 200. Both of these
motors persisted for several years, but were later dropped in favor
of the radial pole type with salient poles of which the G. E, 1000
was an example.
From this point on the general design of the direct-current
railway motors of all manufacturers has been practically along the
same lines. In other words, a definite type has become universal.
The fundamental features of this universal type may be classified
as follows: —
1 — Outside cylindrical or approximately cylindrical yoke.
2 — Extension of the yoke to form protecting end housings and to carry
the bearings.
3 — Radial field poles, usually four in number,
4 — Laminated field poles.
5— Bolted-in field poles.
6 — Field coils without bobbin shells.
(Mummified coils)
7 — Drum wound armature.
8 — Slotted armature core.
9 — Two-circuit or senes direct-current winding.
10 — Two or more armature coils per slot.
11 — Machine wound armature coils, insulated before placing on the core,
12 — Relatively thin mica between commutator bars.
It is of interest to note how many of these characteristics ap-
peared in the very early motors. For instance, 1 , 8, 6, 7, 8,9,11 and
1 2 all appeared in the original experimental Westinghouse single-
reduction motor described, which later was developed into the
No. 3. Item No. 2 appeared in the Westinghouse No, 12 and in the
Thomson-Houston "W.P." motor. Item 4 first appeared in the
Westinghouse No. 38 motor. Item No, 5 appeared in one of the
earliest radial-pole G. E. motors and also in the Westinghouse Nos.
56, 68 and 69. Item 10 appeared first in the Westinghouse No. 12
motor.
STREET RAILWAY MOTOR IN AMERICA
749
Thus it is obvious that the Wcstinghouse No. 3 motor, in its
first experimental form (back in 1890), contained nearly all the
fundamental features of the present universal type. The end
housings carrying the bearings, and the laminated bolted-in poles,
constitute the two principal additional developments. Moreover,
the experimental No. 3 motor did partially contain the element of
enclosing end housings. Thus it may safely be stated that the No.
3 motor practically fixed the type of the modern railway motor.
PIG, 14r-G. E. 1000 MOTOR, OPEN
It may also be mentioned that there was much argument over
the various types of armature windings used by different manu-
facturers. In connection with the machine-wound coil, as used on
the No. 3 motor, many weird claims were made for it In one case
within the writer's knowledge, an over-enthusiastic representa-
tive of the Company, with practically no knowledge of the matter
assured a customer (and he was doubtless sincere in his assurance)
that spare coils could be carried along with the car and in case of a
bttm-out, the trap-door could be lifted and new armature coi'&
dropped in place. In this case, fortunately, the customer actually
knew both what oould and could not be done and he had many a,
good laugh afterwwds while telling the incidaat.
750 ELECTRICAL ENGINEERING PAPERS
LATER MOTOR DEVELOPMENTS
Following the Westinghouse No. 49 and the G. E. No. 1000,
the developments of the two companies might be said to be so
nearly along the same general lines that the differences were
largely in details, although some of the improvements in details
were of great importance. A few of the improvements in the West-
inghouse later motors might be mentioned. The General Electric
Company had already adopted bolted-in-poles, following the West-
inghouse No. 38 motor with cast-in poles. The Westinghouse
followed in its No. 56 and No. 68 motors with bolted-in poles.
Both of these motors had ventilated armature windings and
curved field coils, this latter practice being derived from the
Walker and Lorain motors, both of which companies had been
taken over by the Westinghouse. In the No. 68 motor the alternate
FIG. 15— .WESTINGHOUSE NO. 68 MOTOR
corners of the pole tip laminations were cut away, in order to give a
higher degree of saturation with heavy load and thus lessen the
field distortion and reduce loss in the pole face. This had been com-
mon practice for some time in the railway generators. Various
detail improvements were also incorporated, notably, brush
holders with adjustable spring tension.
STREET RAILWAY MOTOR IN AMERICA 751
THE WESTINGHOUSE No, 101 MOTOR
A most important step in the development of the street rail-
way motor came in 1904 in the Westinghouse No. 101 motor. In
this motor it was planned to incorporate all the requirements of
service as indicated up to that time, together with all the good
results found in previous motors. The No. 101-B motor, which
was a modification of the original No. 101, has had a most enviable
reputation. It contained a number of most desirable features,
such as field coils, wound in a straight mould, of copper strap in-
sulated with asbestos paper between turns; a symmetrical arma-
ture winding with three co Is side by side per slot and no idle coils,
armature coils banded solidly to coil supports, and completely
enclosed; armature core and commutator built up on a spider,
thus permitting the shaft to be replaced without interfering with
the armature winding or core; brushholdcrs insulated in the same
way as more modern motors, with micarta tubes protected by
cartridge shells, and clamped firmly in position, allowing for radial
adjustment.
Probably the most noteworthy improvement in the No.
101 B motor was in the armature bearings and lubrication. The
journals were made larger, the shafts of a higher grade of material
and the old system of combined oil and grease was discarded and
oil-soaked woolen waste was substituted. This motor had the
armature bearings carried in housings which were bolted to the
top half of the field and clamped between the two halves of the
field. The housings had large reservoirs for the oil and waste and
allowed for separate gaging of the oil, This motor made a phe-
nomenal record in respect to armature lubrication. Where former
motors were overhauled each two or three months, in order to
change the bearings, with the No. 101-B it was unnecessary to
change bearings until they had been operated several years.
The above improvements were not added without a substan-
tial increase in weight, which, however, was considered well worth
while. This motor had a tremendous sale and there are still
operating companies who prefer the No, 101-B to any of the more
modern motors which have been developed. Other sizes corres-
ponding to the No. 101-B were the No. 92 and No, 93-A.
752 ELECTRICAL ENGINEERING PAPERS
COMMUTATING POLES IN RAILWAY MOTORS
The next great improvement in railway motors came in 1907
and 1908 in the use of commutating poles. In stationary motor
practice, a number of electrical manuf acturing companies had used
commutating poles for motor work, especially for variable speed
service over wide ranges. It was but a direct step from this to the
use of commutating poles in railway motors. However, the General
Electric Company was the first to put such motors on the market,
to be followed soon after by the Westinghouse Company in their
No. 300 line of motors, Nos. 305, 306 and 307, being motors which
PIG. 16— WESTINGHOUSE NO, 101 B MOTOR
corresponded to non-commutating motors immediately preceding
them. These motors had all the mechanical characteristics and
general features of design of their predecessors, with the addition of
the commutating poles. Since that time commutating poles in rail-
way motors have been so thoroughly established that no new rail-
way motors would be considered without them.
LIGHT WEIGHT MOTORS
Somewhat later than this an agitation was started against
excessive weight in cars, trucks and electrical equipments. This
agitation bore fruit, and a weight cutting campaign began which
has resulted in the adoption of extremely light weight cars, trucks
and motors. The question of car and truck design may not be dis-
cussed here, although it looks now as if the weight-cutting cam-
paign has gone past the best limit. However, a large part of the
reduction in the weight of motors has been entirely logical and is
largely the result of careful design and improvements in ventilar
STREET RAILWA Y MOTOR IN AMERICA 753
tion. Motors are now built with large fans, mounted on the pinion
end of the armature shaft, which pull air through the armature
core and over the surface of the armature and between the field
windings, which has made an increase of probably 50 per cent in
the continuous rating of the motors. In addition to this, the arma-
ture speed has been very considerably increased and the gears have,
in many cases, been changed from 3-pitch to 3}^, 4 and even 4^.
Open ventilation of the motors has been a natural consequence
of the great improvement in insulation made in the last few years.
The early motors were made open to the weather but this had to be
abandoned because of the large amount of insulation trouble.
After a good many years with the enclosed motor, it gradually
became the practice to open the motor up somewhat for better
ventilation, and finally fans were installed to create a circulation of
air, so that now the continuous rating of railway motors is higher
per pound than ever before.
TECHNICAL TRAINING FOR ENGINEERS
"FOREWORD — This paper was compiled from two addresses, one
given by special request before the Pittsburgh Section of the
American Institute of Electrical Engineers in 1916, and the
other, covering much the same subject matter, was given before
the National Association of Corporation Schools at its annual
meeting in Pittsburgh, 1916. On account of the favorable
comments on the two addresses, they were afterwards combined
and printed in the Electric Journal. The author has had a wide
experience in the education of so-called "educated" men.
Almost since his entrance into the employ of the Westinghouse
Electric & Mfg. Company, early in 1888, he has given a con-
siderable part of his time^to the development of the more prom-
ising young engineers with whom he came in daily contact.
Being himself extremely fond of the analytical side of his work,
he has been very free in imparting his methods, data and ex-
perience to his associates and assistants, thus in fact, ^although
not in name, becoming an educator along advanced lines. He
always has been in search of young men of the right turn of
mind whom he could develop into "stars" in his profession, and
many men prominent in the electrical industry today can speak
with pride of the training they received while associated with
him. Recognizing that the engineering development work of
the manufacturing companies is becoming increasingly difficult
from year to year, he has given special attention, during the
past several years, to the selection and training of graduates of
the technical schools who show, to an unusual degree, certain,
characteristics and aptitudes which he believes to be necessary
in maintaining the high standard of the Westinghouse Com-
pany in the engineering field. In other words, he is applying
ids analytical methods to men very much as he has applied them
to apparatus and principles in the past years. — (E&.)
IN the earlier days of the Westinghouse Electric & Mfg. Com-
pany many young technical students were taken directly into
the various departments and there trained. But in time the student
problem became so large and important that an educational de-
partment was developed to meet in a systematic manner the grow-
ing needs of all departments. This educational department works
in conjunction with the other departments in training men and in
placing them where they will have opportunities in accordance
with their special abilities*
The following remarks represent the writer's own personal
opinions based largely upon a comparatively wide experience with
the young engineers who have entered the student's course during
the past five or six years. In that time this company has taken into
756
756 ELECTRICAL ENGINEERING PAPERS
its educational department over one thousand graduates of tech-
nical schools from all over the United States and Canada. Of these,
several hundred have wished to specialize in engineering, while the
aim of the others has been toward the manufacturing and the
commer ial lines, both of which require good technical training.
The electrical salesman of today is quite technical, regardless of
how he got his training. Also the complexities of the electrical
business of today require many high-class technical men in the
manufacturing departments. As to engineering, it goes without
saying that those who follow this branch of the electrical business
should be technical men, if they are to advance very far. In con-
sequence the Westinghouse Company takes on technica graduates
almost exclusively for its student's course, regardless of what
branch of the electrical buiiness they expect to follow.
The writer's personal experience has been very largely with
those students who expect to follow the engineering branch of
electrical manuf a storing. During the past few years he has come
in contact with practically all those who leaned toward engineer-
ing work. One of the most important considerations in the engi-
neering student problem has been that of fitting the men to the
kinds of work for which they are best adapted. In former years this
was done in a more or less haphazard manner by trying the men
out in different classes of work to see whether they would make
good. This procedure proved so unsatisfactory that it became
necessary to adopt some method of classifying the students ac-
cording to their aptitudes and abilities, and then try each one out
on that line of work for which he seemed to be best fitted. Obvious-
ly, this method was in the right direction, but the primary diffi-
culty lay in determining the characteristics of the individual
students. The writer has spent quite a considerable amount of
time in the past few years in studying the characteristics of the
students to see whether their natural and their acquired abilities
can be sufficiently recognized, during the preliminary stages of the
work, to allow them to be properly directed toward that field in
which they will make the best progress, In this study, in which
hundreds of young men were analyzed with regard to their char-
acteristics, many very interesting points developed, quite a number
of which have a direct bearing on the subject of technical training.
In the first years of this study the results were very discouraging,
due largely to the fact that the young men had been brought to us
in a wholesale way, regardless of their characteristics or their
TECHNICAL TRAINING FOR ENGINEERS 757
suitability for our engineering work. Many of them had no ideas
whatever in regard to the kind of work for which they were fitted.
Apparently the man who had not, at least partly, made up his
mind as to his preferences or his capabilities for some given line of
endeavor by the time he had gone through four years of college and
then entered our course, had much difficulty in making up his mind
after he had been with us a year or two. It developed, in many
cases, that he was lacking in decision. This was a very predomin-
ant fact in the first few years after the writer had gotten into this
work more actively. After a careful study of the situation it was
recommended that an attempt be made to get a different class of
college men, namely, those who had more definite ideas as to what
they wanted and what they were fitted for. This policy was tried,
and with great improvement in the grade of men obtained. It is
principally from the study of these later men that the writer has
been able to draw some of the conclusions which are here given.
One of the most prominent features which has developed from
the study of these young men is that in practically all cases the
most valuable aptitudes or characteristics which they have shown
were possessed by them long before they entered college. In fact,
many of them have apparently possessed such aptitudes, more or
less developed, from comparatively early childhood. For example,
the best constructing or designing engineers all had a strong ten-
dency toward the construction of mechanical toys and apparatus in
cMldhood. In regard to such characteristics, the schools and the
colleges have merely directed and developed to a greater extent
what is already there. Prom this viewpoint, therefore, the college
simply develops* If the tendency isn't there, it would seem that
there is but little use to try to develop or cultivate it. Viewed from this
standpoint, quite a large percentage of the young men who take up
engineering courses in college are quite -unfitted for such work.
Therefore, one function of the college should be to sort out and
classify the young men according to their characteristics, to dis-
courage them from following along any line of endeavor for which
they have no real aptitudes, and to direct them into more suitable
lines. This applies particularly to technical schools. It might be
said that in our present educational system the usual method is to
educate the young men and then select the real engineers, this
selection being made afterwards through bitter experience. The
ideal method, apparently, would be first to select the real engi-
neers and then to educate them. In other words, those who show a
758 I!! ELECTRICAL ENGINEERING PAPERS
natural aptitude for engineering should be educated along tech*
nical lines.
In the technical school one of the first efforts should be toward
finding the student's natural aptitudes. Some boys apparently
have no leaning toward any special line of endeavor. On the other
hand, many boys really have some inherent preference which,
however, may not have been strongly enough developed to stand
out prominently. Too often his real preference has been entirely
neglected or even discouraged. In the writer's own case, as a boy,
he was very frequently and severely criticised for his inclination to
' ' waste valuable time ' ' in trying to make what were called ' ' useless
things." However, fortunately for himself, no real pressure was
brought upon him to prevent him from following his preferences
or tendencies, and eventually the "call" was so strong that it took
him into the very work which he wanted above all else.
On the other hand, the boy may express a preference for a line
of work for which he is entirely unfitted. In other words, this
preference may not be based upon natural aptitudes or character-
istics and is not a real f ' call. " It is these boys, who are unfitted for
the lines which they have chosen, who are a real handicap on their
classmates. The class never moves along faster than its average
man, and very often at the speed of the poorest men. If these
poorest men were eliminated, naturally the progress would be much
faster. Apparently the present methods of training have not yet
overcome this difficulty, although very many teachers recognize
the evil, and are attempting to correct it. This will be referred to
again later.
Coming to the technical training of the students, experience
indicates that too much specialization is a mistake. He gets enough
of that in after years, What is needed is a good, broad training in
fundamental principles. In engineering matters, a thorough grasp
of such fundamentals is worth more than anything else, By
fundamentals is meant basic principles or facts. These should not
be confused with theories or explanations of facts, A fact is basic,
and does not change, although the theories which explain it may
change many times. A thorough knowledge of basic principles will
enable a direct answer to be made in many cases, even where the;
conditions of a problem may appear to be very complex. Take, for
example, the perpetual motion fallacy in its various forms* A per-
petual motion scheme may be made so complex and involved and
may include so many principles and appurtenances that the beet
TECHNICAL TRAINING FJR ENUMEERS 759
analyst may be more or less puzzled to explain the various rela-
tions clearly. But by applying the principle of conservation of
energy no further explanation is necessary. This one fundamental
fact covers the whole case. In the same way a thorough grasp of
some basic principle will often clear up the most complex problems
or situations and will allow a conclusive answer to be made. With
such a grasp of fundamentals, one is not liable to believe that a
"pinch" of some wonderful new powder or chemical, mixed with a
gallon of water, will give the equivalent of a gallon of gasoline, and
at the cost of few cents. And yet this fallacy * ' breaks loose ' ' period-
ically, and is given wide circulation in the news of the day. What
is needed in such cases is a little knowledge of fundamental prin-
ciples.
This very grasp of fundamentals accustoms the boy to think
for himself. In other words, it develops his analytical ability. As
one educator mentioned to the writer some time ago, *' If a boy has
analytical ability, there is hope for him; if he has none, he is
'punk.' " By analytical ability is not necessarily meant mathe-
matical ability with which some people are inclined to confuse it.
By analytical ability is meant the ability to analyze and draw cor-
rect conclusions from the data and facts available* This faculty
can be cultivated to a considerable extent, although, in the writer's
opinion, it originates rather early in life. This is considered by
many as the first and foremost characteristic that an engineer
must have, and therefore the schools should expend their best
energies in this direction.
Allied with a grasp of basic principles is the requirement of a
physical conception of such principles as distinguished from the
purely mathematical This can be cultivated, as the writer's
personal experience with many students has indicated. As a con-
crete example of the value of a physical conception the following
may be cited: — Three electrical engineers, familiar with induction
motor design, are given some new problem regarding the action of
an induction motor. One of them immediately thinks of a "circle
diagram1'; the second thinks of a mathematical formula; the
third thinks of flux distributions and conductors cutting them at
certain speeds, etc. Assuming equal mathematical skill for these
three men, the one with the physical conception of the conductors
cutting fluxes has a broader means for attacking the problem than
either of the others can be said to have, He can tackle a new con-
dition with better chance of success, as he goes back to the funda-
760 ELECTRICAL ENGINEERING PAPERS
mental principles of the apparatus. He thus may create, con-
fidently, new formulae and diagrams to meet new conditions and
problems.
- This physical conception is closely related to the development
of imaginative powers, and without such powers highly developed
no engineer can expect to advance far in his profession. The man
with originality, resourcefulness or with the constructive faculties
well developed, or the man who "can see through things'1 readily,
must have strong imaginative powers. This faculty also should be
developed to the utmost, but should also be directed. It begins
early in some children, but, unfortunately, instead of being direct-
ed, it is too often discouraged, both at home and in the school.
If the boy in the public school develops a new method of solving
& problem, or reaches any conclusion by other than the well-
established routine way, he is criticised more of ten than encouraged
for his departure from the beaten track, or rather his instructor's
particular methods.
As stated before, the student should be well trained in funda-
mentals or basic principles. In many branches of engineering this
means that he should have a good training in mathematics. Most
of the graduates of the technical schools are woefully weak in
mathematics. Apparently this is not due entirely to lack of mathe-
matical ability on the part of the students, but largely to defective
training in their earlier work. One great defect in many colleges
is due to passing the entrants, in algebra and trigonometry, on the
basis of their high school training. In most cases this early training
in algebra is very defective, as sufficient skill is not developed in the
student and the practical side is largely neglected, , Algebra and its
applications to geometry, trigonometry, etc., should be taught in a
more practical manner in the engineering college course, as a found-
ation for the higher engineering mathematics. The higher the struc-
ture is to be, the stronger must be the foundation. If the engineer-
ing student is not sufficiently practiced in these elementary mathe-
matics, then he should be drilled specially as a step to further
engineering work. In the practical engineering work, beyond the
college, skill in the use of algebra and trigonometry is of relatively
much more importance than practice in the higher mathematics,
for it is needed one hundred times where the other is used once.
In the writer's experience with engineers he has reached the con-
clusion that the principal reason why mathematics axe not used
mote in everyday work is because the average engineers have not
TECHNICAL TRAINING FOR ENGINEERS 761
the necessary skill. Most of them claim that they have become
"rusty" in such mathematics through disuse. However, in many
cases, this excuse is worse than none at all, for the occasion for such
mathematics exists in practical engineering work and has been
there all along.
In the education of the engineer, higher mathematics forms a
very valuable part of the training. One of its uses is to show how
one can do without it. In other words, if properly taught, it gives
a broader grasp of methods of analysis; it tends to fix certain
fundamental principles. However, as a tool in actual engineering
work it is seldom required, except in rather special lines. The
higher mathematics might be looked upon as a fine laboratory in-
strument or tool to be used on exceptional occasions, while the or-
dinary mathematics should be considered as an everyday tool in
engineering work, and should be ready at hand at all times.
There has been quite a fad for specialization in engineering
training. The writer's personal opinion is that specialization in
college training is not advisable, except possibly in a very general
way. There has been a false idea in many schools that if a man
specialized along some individual line of work it would advance
him more rapidly when he leaves school for active work. The
writer almost never asks the student in what field he specialized.
It is desired to know whether he is a good analyst, if he is fairly
skillful at mathematics, if he has the imaginative faculty and
what goes with it. Has he initiative, resourcefulness, etc.? Is he
a man with a broad grasp of general principles rather than one
who has made a special study of one individual subject?
In college training the time spent oil commercially practical
details is usually largely wasted, as it may give the student en-
tirely wrong ideas. When a young man says that he has had a
course in practical design and is positive that he can design, the
chances are about ninety-nine out of one hundred that he knows
nothing about the really fundamental conditions in practical de-
sign. The chances are that he doesn't even know the real starting
point in making up a commercial design. Even worse, if he has
taken such training seriously, he tnay have to "unlearn*' many
of his ideas, if the use of this term is allowable. The mental train-
ing and the aid in grasping principles which he may have obtained
through his school design is, of course, worth something, but in
many cases the same time expended in other channels may produce
larger results. Teaching of design should, therefore, be for the
762 [• IELECTRICAL ENGINEERING PAPERS
purpose of exemplifying principles rather than practice. There are,
of course, some lines of specialization in colleges which lead
directly to practical results afterwards. Research work is one of
these. However, it is probable that if a large part of the time given
to research work by the student in college were expended in ac-
quiring a broader foundation in fundamental principles the
results would be better in the end.
As referred to before, there has been one serious defect, in our
systems of technical training today, namely, it holds back the
leaders and pushes the laggards, thus tending toward mediocrity
as the general result. There should be some system in colleges for
weeding out the " negatives" in any given line of endeavor.
Many of these are simply "misapplications," to use a manufactur-
ing company term. In some other lines they may be highly success-
ful.
In an ideal engineering course each student should be pushed
to the utmost of his capabilities. One solution of this problem
would be for each teacher to assign a certain amount of work to his
students individually, and they should report to him individually
on such work, explaining to him fully what they have accomplished.
Each man thus could be pushed along independently of his fellows.
The weaknesses of the individual men would soon appear. If, for
example, it develops that certain of the students are behind in the
necessary mathematics, then steps could be taken to correct this
defect. Each student would have to think more for himself and
would be put more or less upon his own resources. His various
characteristics could be studied and developed. He should be made
to work out and apply fundamental principles* He would thus
practice using his own mind. As soon as it develops that he has no
mind of his own, then he could be dropped. In such a course of
teaching the advancement of each man would be dependent upon
himself, to a large extent. At this point a principle of mechanics
can be applied rather aptly. In machines a force does work in
overcoming resistance. In man the same principle holds true.
No matter how much force a man may have, if no resistance is
presented, no result is accomplished. And if the force is small,
then the result is also liable to b,e small. But a stnaller force over-
coming a larger resistance may result in greater accomplishment
than a larger force with but little resistance. An unusually bril-
liant boy with too small a task set for him may accomplish little.
His task must be enlarged to suit bis abilities; for, as in machines^
TECHNICAL TRAINING FOR ENGINEERS 703
to obtain the greatest result the resistance, or task, must be com-
mensurate with the force acting. Unfortunately, many good men
of great capabilities accomplish practically nothing, through too
little resistance, due to life being made too easy for them.
Such a course of "forcing," as indicated above, might be diffi-
cult to apply in many of the schools as constituted today. But thq
writer's personal experience indicates that the better class of men
will develop rapidly under such treatment, while the laggards are
eliminated more quickly. He has tried this system in general on
many graduates from the technical schools and unusually satis-
factory results have been obtained.
All of the foregoing points to the fact that the mere accumula-
tion of knowledge is not a training, nor an education. The old
saying that "knowledge is power" is not technically correct any
more than is the statement that torque (or force) is power, to use
an engineering comparison. Torque, or force, is not power, but
torque in motion is power and, to continue this comparison, knowl-
edge in motion, or in action, is power. Activity in some form is one
of the essential factors.
To sum up, the colleges should aim to develop the student's
characteristics, as far as practicable. They should aim to develop
analytical ability, imaginative faculty, ability to do independent
thinking. They should teach fundamental principles, and the
course of teaching should be such as to give the individual student
a real grasp of such principles. A broad general training is most
desirable for the man who has the ability to do something in the
world.
ENGINEERING BY ANALYSIS
FOREWORD^— In the latter part of 1916, the engineering students at
the Ohio State University decided upon the publication of a
college engineering paper, and the author was asked to prepare
an article for the first issue. In answer to this request, a paper
entitled, "The Electrical Engineer of Today" was submitted.
This article appeared in the first issue of the Ohio State En-
gineer, in January, 1918, and it is here reproduced in practically
the same form as the original, except in title. — (ED.)
THE early engineering in any field is usually of the "cut-and-
try" kind, followed later by the refinements of more highly
trained specialists. A comparatively recent development in indus-
trial and manufacturing engineering is the analytical engineer. By
this is meant the engineer who translates facts into relationships,
formulae and figures, and eventually retranslates them into other
facts. The analytical engineer in this sense does not mean the
mere user of figures and formulae. He starts with fundamental
principles and laws from which he then draws his conclusions, the
applications of which are made directly to the final product with-
out intermediate experimentation. The analytical engineer has
led the way to new and more difficult fields of endeavor and many
of our most rapid advances have been made under his guidance.
Electrical engineering, is one of the youngest of the en-
gineering lines of endeavor, but its "cut-and-try" period was of
comparatively short duration. The coming of the analytical en-
gineer was almost coincident with the rise of electrical engineering
as a business. This branch of engineering deals with more or less ob-
scure phenomena, of which there are only indirect evidences in
many cases. Many of the laws primarily are only mathematical
relationships. Many of them can only be grasped or handled by
those who have considerable analytical and mathematical ability.
In consequence, even comparatively early in the work, the highly
technical engineer was a necessity. Probably in no other branch
of engineering, since its first development, has there been as large
percentage of men, having high technical training, engaged in the
work; and as a consequence, in no other lines of engineering has
there been as rapid growth as in the electrical,
Coincidentally with the growth of electrical engineering, there
have been rapid advances in the older and better established lines
765
766 ELECTRICAL ENGINEERING PAPERS
of engineering, especially in those which have been rather inti-1
mately associated with the electrical industry. The steam" tur-
bine which now dominates the field of steam prime movers, re-
ceived its greatest impetus in connection with electrical work, and
its present high development may be said to be the product of
the analytical engineer. Water-wheel development has also
made great advances under much the same conditions,
One characteristic of the analytical engineer of the present
time, especially in electrical work, is that he is very often working
far ahead of his available data. He is obliged to plot his existing
data and experience and then exterpolate for the new points which
he finds necessary in his work. He is thus working in the un-
known to a greater or less extent, but his ability to analyze and
correlate very often leads him to be fairly certain of his results.
It is this abibty to work with confidence in comparatively un-
known fields, which has produced such astonishing results in
electrical engineering.
The analytical engineer of today, whether electrical or other-
wise, must forsee, through his analysis of data and practice, what
the trend of future practice will be. If his analysis shows him
that certain lines of development are scientifically more consistent
than other lines, he will naturally tend to work along what he
considers to be the correct direction. If he sees that certain
practices are fundamentally wrong and represent only makeshift
conditions, or merely commercial expediency, he will naturally
feel that such practices eventually will be replaced. He must
weigh both theoretical and practical conditions in determining
which direction to work.
With the true analytical engineer there will be no standardiza-
tion of practice unless such practice has good fundamental reasons
back of it. His tendency is rather toward standardization ac-
cording to certain scientific principles and limitations than by
practices which have insufficient basis. The latest standardiza-
tion rules of the American Institute of Electrical Engineers repre-
sent an attempt along this line, and it is a pretty safe prediction
that the basic features of these new rules will be retained for many
years to come.
Analytical engineering, of a very advanced kind is represented
by the modern research and testing departments and laboratories
of the big engineering concerns who do electrical and other manu-
facturing. Much of the technical data, which the designing,
ENGINEERING BY ANALYSIS 767
developing and manufacturing departments require, is a direct
product of such departments. No progressive industrial estab-
lishment of the present time can get along without extensive
research departments. Recently Congress has approved of a large
Naval Laboratory for research and experimental work, in line with
other engineering and industrial organizations.
A good example of modern electrical design work of a highly
analytical character, is the present turbo generator. The present
huge capacity high speed machines are almost beyond the dreams of
ten years ago. These machines are almost entirely the product of
the analytical designing engineer. In these machines nearly all pre-
vious developments and experience in other lines of apparatus have
ountcd for little. New methods, new materials, new practices and
new limitations have been established in these machines, and for
these reasons, the turbo generator engineer has been compelled to
work ahead of his data and experience much of the time. For ex-
ample: the twenty thousand kilowatt, 1800 r.p.m., 60-cycle, turbo
generator was undertaken when the ten thousand kilowatt ma-
chine of the same speed and frequency was the nearest size from
which to obtain data, and this smaller size unit had already been
carried up to what were considered as the permissible limits, in
many ways. ,In such case the designer had to overstep his data and
limits, and depend largely upon analysis.
Another good example of analytical engineering is the in-
duction motor. While such motors possibly could have been
developed by cut and try methods, at great expense and with
many failures, yet the present advanced status of this type of
apparatus can be considered only as the product of the analyst.
The production of cage-wound induction motors with good start-
ing torque, suitable for general purposes, was the result of analysis,
not experiment.
In the electrical manufacturing industry the analysts, as repre-
sented by the designing engineers, hold an important place. The
term is here used broadly to include the designers of systems,
applications, methods, etc., as well as apparatus. They form a
very necessary part of the organization, especially so in connection
with those departments where cut-and-try methods have been
largely eliminated. Many of the largest engineering -under-
takings axe on customers' orders, covering apparatus which
has never been built before. In most cases, by the time any tests
of the completed apparatus axe obtainable, the work as a whofe
768 ELECTRICAL ENGINEERING PAPERS
has progressed beyond the point wnere any important changes can
be made. Even such preliminary tests as are obtainable in the
shop are liable not to tell the whole tale, for the real test or
proof of the adequacy of the design comes from duration tests
furnished by ctual service. The real troubles may not show up
until six months or a year after the apparatus has been put in
service. Here is one of the difficulties that the designing engineer
encounters; and, the more progressive he is, the more liable he is
to run into this very difficulty, simply because he is pushing
further into unknown ground. A serious difficulty possibly de-
velops a year or so after the apparatus has been put in service.
Then he is criticised both for not having forseen and for not
having immediately corrected it. Such criticism might be con-
sidered, in one sense, as complimentary, for it is an assumption
that he knows much more than he really does. However, most
engineers are not particularly pleased over such criticism, for they
usually find it hard enough to cure an unknown and unforseen
trouble, without being told that they were careless and did not
use proper foresight. A true engineer has pride in his work, and
a defect or failure, in itself, usually hurts him even more than
criticism. He also feels that when a man has done the best he
can and has attempted something never accomplished before, he
should have sympathy in his trouble, or at least constructive
criticism.
It may be added here that in addition to ability to undertake
and carry through a given design, it is important that the engineer
be able to "let go" of it at the proper time. Each new develop-
ment or test shows the way to still further improvements or de-
velopments, and if each of these is to be incorporated in the de-
sign, then it will never reach completion until absolute perfection
is attained or the designer has reached the ultimate limit of his
ability. Neither of these conditions is practicable in a live
manufacturing business, and, therefore, the engineer should be
able to let go of his design when a sufficiently good practical result
is obtained. Some engineers seem to know just when to stop.
This is to some extent dependent upon a proper appreciation of
commercial requirements.
To be a successful electrical engineer does not mean one is fitted
to be a manufacturing engineer; further, one may be a very good
electrical manufacturing engineer and yet not be fitted for elec-
trical design, for this latter is a branch of the industry which re-
ENGINEERING BY ANALYSIS 769
quires rather special characteristics. Experience shows that the
designing engineer must have a special aptitude for such work
regardless of his education or general abilities, if he is to be thor-
oughly successful. In design work, experience has also shown that
combinations of the requisite natural aptitude and the necessary
technical training are comparatively rare, and the really successful
men in this line of work are but very few in number.
If certain aptitudes and characteristics are essential for the
designing engineer it might be asked — what are these essentials?
However, it is almost impossible to pick out any characteristic
which could be considered as the one essential in the electrical
designing engineer, except, possibly, good common sense; but as
this is at the bottom of all true success, it should not be considered
as peculiarly characteristic of the engineering profession.
As the competent electrical designing engineer must necessarily
be an analyst, obviously analytical ability, in the broad sense,
must be one of his foremost characteristics. He should also have a
certain amount of mathematical ability and training. In general,
skill in the ordinary mathematics, such as in algebra and analytical
trigonometry is of more use than a mere working knowledge of the
higher mathematics. There are certain lines of work in which
the higher mathematics are, of course, very valuable and necessary.
These, however, represent a relatively small percent of the total
field. The young engineer should not become unduly impressed
with the idea that ability to use extremely complicated mathe-
matics is the prime requisite. He should, however, recognize
that without mathematical aptitude of any sort, he is very greatly
handicapped. The "handy man" with mathematics appears to
have a decided advantage over others, in practical work.
The engineer who can develop a mental picture or a *' physical
conception" of what is going on in a machine, in distinction from a
purely mathematical conception, appears to have a very consider-
able advantage over his fellows. The man with both the physical
conception and with good mathematical ability will probably go
further in analysis than any of the others*
Let us return to one of the conditions which is very necessary
in all engineering, namely — a good knowledge of fundamental
principles- The engineer should know the derivation of his var-
ious methods and formulae. Many of these which are now used
by rapid workers are really short cuts or empirical methods which
are primarily based upon correct but more camples
770 ELECTRICAL ENGINEERING PAPERS
Their use, without a proper knowledge of their derivations and,
therefore, their limitations, is dangerous and not infrequently
leads to serious trouble. Above all the electrical designing engi-
neer should have a broad conception of certain fundamental rela-
tionships or laws entirely apart from the mathematics of the case.
With a clear understanding of fundamental principles there is
much less liability of waste of time and effort from following out
impracticable schemes.
There was a time, and not so many years ago, when an elec-
trical engineer could cover almost the entire field. At that time a
fairly complete training in the various branches of electrical engin-
eering was possible, but with the widening of the field, it has become
too great for the single individual to cover, and the problems have
become too difficult for any one man to handle all of them. There-
fore, it has become necessary for individual engineers to devote
themselves to some special field of endeavor and to leave the broad
field to be covered by the co-operation of many specialists. Con-
sequently, the engineering of today is sub-divided into many
groups, each more or less distinct in itself, but each overlapping
and interrelated with many other groups. The engineer of today
is, therefore, always some kind of a specialist, for it is impossible
to be otherwise if he is to lead in anything,
It is on account of this specialization that it is so important
that the young engineer of today obtain a broad knowledge of the
fundamentals of his chosen line of engineering. The same fun-
damentals underlie the whole electrical field, so that a knowledge
of them is about as near as he can come to a broad knowledge of
the whole. Such should be obtained as early as possible in his
career, for, after specialization begins, his own particular field of
endeavor is liable to absorb all of his efforts.
It is now being recognized by the ablest engineers that much
specialization in the schools is not an advantage to the student,
If the colleges could confine themselves to a broad teaching of
fundamental principles they would turn out vastly more effective
men than at present. Analytical ability (not necessarily mathe-
matical) is one of the crying needs of the electrical industry of
today, as regards its young men. And this need exists in spite
of the fact that this industry doubtless gets its full share of the
analytical men turned out by the schools. An analytical man per
se is oae who thinks for himself and, therefore, the problem really
narrows down to the thinking man. If the schools could turn out
ENGINEERING BY ANAL YSIS 77 1
a much higher percentage of thinking men, the engineering pro
fession would be vastly benefited.
There is another quality or characteristic which, while possibly
not as valuable as analytical ability, goes a long way toward suc-
cess, namely — persistency. A brilliant tnind with but little per-
sistency back of it, will usually accomplish less than a much less
brilliant mind backed by great persistency. This latter charac-
teristic has turned many an apparent failure into positive success.
A brilliant man without persistency is liable to pass from scheme
to scheme and perfect none of them. However, persistency alone
usually accomplishes no more than brilliancy alone. Men have
expended years of patient effort along lines which a little common
sense analysis would quickly have shown to be impracticable.
Here is persistency gone to waste.
The emphasis placed upon the above mentioned characteristics
is not intended to belittle other very important ones, such as
initiative, originality, resourcefulness, etc. These qualities might
be classed even higher than analytical ability and persistency by
some persons, and possibly rightly in some lines of effort. But in
the higher electrical work the conditions may be otherwise. Here
one may have strong initiative, but be utterly unable to make any
great progress due to lack of analytical ability; he may have great
originality, but, lacking the fundamentals, be unable to touch on
the higher work; he may be exceedingly resourceful, but be limited
only to lesser things due to lack of knowledge of basic principles,
and, thus, inability to handle advanced work. However, a leader
must have all of these qualities to a certain extent, Now and then
a man is found who has all of them to a fairly high degree, com-
bined with unusual analytical ability and perseverance. Such a
man eventually is liable to become known as a genius, but it should
be remembered that genius is of two kinds, — creative, in the sense
of being able to think in new fields, and constructive, in the sense
of being able to use present known facts and principles to bring
about successful results.
Then there is another feature which may be referred to, name-
ly, the commercial side of engineering. An electrical manufacturing
business lives by tke goods, not the engineering, which it sells.
The successful designer of such goods must, therefore, have con-
siderable knowledge of commercial conditions or he cannot design
adequate or competitive apparatus* This is a feature of the bum-
ness about which the young engineer, fresh from school,
772 ELECTRICAL ENGINEERING PAPERS
nothing. This appears to oe a very difficult thing for some 6Ek
gineers to acquire, while certain of them never really do so. On the
other hand, it has been said of some very good engineers that they
ought to have been salesmen, because they grasped so readily the
customer's conditions and requirements. The broad gauge elec-
trical designer is usually quite successful in aiding the salesman,
because he sees the commercial bearing of his engineering work.
This relation of the engineer to the commercial side of the busi-
ness brings up another point, namely, his ability to talk clearly and
logically in private and in public. It was once supposed that an
engineer never had to talk in public and that all he had to do was
to go off in a corner, by himself, and use a slide-rule. But that
day is long past, for now the man who knows most about the appa-
ratus must be able to tell others what he knows. Presumably in
all large concerns there are men who are seldom or never sent out-
side on account of their inability to make a good presentation of a
subject. Assuming equal ability otherwise such men are of less
value than those who can make a good presentation of any given
matter. In general, a good logical thinker can develop into a
fairly good logical speaker through practice.
The foregoing has had most to do with electrical designing en-
gineers, but while they are a very important part of the industry,
yet they are not the only engineers in the electrical manufacturing
business. In fact, the electrical industry today is managed almost
entirely by men who should be classed as engineers. A large per-
centage of the electrical salesmen of today have had a very good
engineering training of one kind or another. In fact, in many
lines they must have such training in order to be successful. In
the manufacturing part of the business, many of the leading men
are also good engineers. Also many of the high executives
in the industry are trained engineers of high grade.
In conclusion it may be said that this is an age of engineering
construction. It is, or rather it forshadows, the golden age of
the engineer. His successes and attainments have led him to
view hopefully hitherto totally unattainable things, and in conse-
quence his problems are becoming increasingly difficult. At no
time has such boldness been shown in attacking the problems of
nature for the benefit of mankind, and it is the engineer in one
guise or another who is behind the attack, and his aim almost
invariably is something which is ultimately for the advancement
of humanity. Construction, not destruction, is his preference,
ENGINEERING BY ANAL YSIS 773
He is an optimist and not a pessimist. In research work he is
delving into the unknown in search for properties, principles and
laws of nature and of material. He is making vast strides in the
conservation of natural resources, by the economical generation
and utilization of power. In transportation he is bringing the
whole world together. He is making steel and concrete the rule
in constructions, doing away with more perishable materials.
Engineering should be considered of highest rank among the
professions. No engineer need apologize for his calling. He
should feel the greatest pride in it, for it may be said that it is the
very heart and soul of material progress.
Carnegie Institute of Technology
Library
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