GIFT OF
MICHAEL REESE
ELECTEICAL PAPERS.
VOL. II.
ELECTRICAL PAPERS
BY
OLIVER HEAVISIDE
IN TWO VOLUMES
VOL. II.
ifieto gorfe
MACMILLAN AND CO.
AND LONDON
1894
[All rights reserved]
~06
CONTENTS OF VOL. II.
ART. 31. ON THE ELECTEOMAGNETIC WAVE-SUEFACE. A°l
Scalars and Vectors. 4
Scalar Product. - 4
Vector Product. 5
Hamilton's V. 5
Linear Vector Operators. 6
Inverse Operators. 6
Conjugate Property. 6
Theorem. - 7
Transformation-Formula. 7
The Equations of Induction. ... 8
Plane Wave. 3
Index- Surf ace. 9
The Wave-Surface. ..... 11
Some Cartesian Expansions. 16
Directions of B, H, D, and B. 19
Note on Linear Operators and Hamilton's Cubic. - 19
Note on Modification of Index-Equation when c and n are
Eotational. 22
ART. 32. NOTES ON NOMENCLATUEE.
NOTE 1. Ideas, Words, and Symbols. 23
NOTE 2. On the Eise and Progress of Nomenclature. 25
ABT. 33. NOTES ON THE SELF-INDUCTION OF WIEES. 28
ART. 34. ON THE USE OF THE BEIDGE AS AN INDUCTION
BALANCE. 33
ART. 35. ELECTEOMAGNETIC INDUCTION AND ITS PEOPAGA-
TION. (SECOND HALF.)
SECTION 25. Some Notes on Magnetization. 39
SECTION 26. The Transient State in a Eound Wire with a close-
fitting Tube for the Eeturn Current. - 44
vi
ELECTRICAL PAPERS.
PAGE
SECTION 27. The Variable Period in a Round Wire with a Concen-
tric Tube at any Distance for the Return Current. - 50
SECTION 28. Some Special Results relating to the Rise of the
Current in a Wire. 55
SECTION 29. Oscillatory Impressed Force at one End of a Line.
Its Effect. Application to Long-Distance Tele-
phony and Telegraphy. 61
SECTION 30. Impedance Formulas for Short Lines. Resistance of
Tubes. - 67
SECTION 31. The Influence of Electric Capacity. Impedance
Formulae. 71
SECTION 32. The Equations of Propagation along Wires. Ele-
mentary. 76
SECTION 33. The Equations of Propagation. Introduction of
Self-induction. - - 81
SECTION 34. Extension of the Preceding to Include the Propaga-
tion of Current into a Wire from its Boundary. - 86
SECTION 35. The Transfer of Energy and its Application to Wires.
Energy- Current. 91
SECTION 36. Resistance and Self-induction of a Round Wire with
Current Longitudinal. Ditto, with Induction
Longitudinal. Their Observation and Measure-
ment. 97
SECTION 37. General Theory of the Christie Balance. Differential
Equation of a Branch. Balancing by means of
Reduced Copies. 102
SECTION 38. Theory of the Christie as a Balance of Self and
Mutual Electromagnetic Induction. Felici's In-
duction Balance. -..- 106
SECTION 39a. Felici's Balance Disturbed, and the Disturbance
Equilibrated. 112
SECTION 39&. Theory of the Balance of Thick Wires, both in the
Christie and Felici Arrangements. Transformer
with Conducting Core. 115
SECTION 40. Preliminary to Investigations concerning Long-
Distance Telephony and Connected Matters. - - 119
SECTION 41. Nomenclature Scheme. Simple Properties of the
Ideally Perfect Telegraph Circuit. - 124
SECTION 42. Speed of the Current. Effect of Resistance at the
Sending End of the Line. Oscillatory Establish-
ment of the Steady State when both Ends are
short-circuited. 128
CONTENTS.
SECTION 43. Reflection due to any Terminal Resistance, and
Establishment of the Steady State. Insulation.
Reservational Remarks. Effect of varying the
Inductance. Maximum Current. -
SECTION 44. Any Number of Distortionless Circuits radiating from
a Centre, operated upon simultaneously. Effect of
Intermediate Resistance: Transmitted and Reflected
Waves. Effect of a Continuous Distribution of
Resistance. Perfectly Insulated Circuit of no Re-
sistance. Genesis and Development of a Tail due
to Resistance. Equation of a Tail in a Perfectly
Insulated Circuit.
SECTION 45. Effect of a Single Conducting Bridge on an Isolated
Wave. Conservation of Current at the Bridge.
Maximum Loss of Energy in Bridge-Coil, with
Maximum Magnetic Force. Effect of any Number
of Bridges, and of Uniformly Distributed Leakage.
The Negative Tail. The Property of the Persist-
ence of Momentum.
SECTION 46. Cancelling of Reflection by combined Resistance and
Bridge. General Remarks. True Nature of the
Problem of Long-Distance Telephony. How not
to do it. Non-necessity of Leakage to remoye
Distortion under Good Circumstances, and the
Reason. Tails in a Distortional Circuit. Complete
Solutions.
SECTION 47. Two Distortionless Circuits of Different Types in
Sequence. Persistence of Electrification, Momen-
tum, and Energy. Abolition of Reflection by
Equality of Impedances. Division of a Disturbance
between several Circuits. Circuit in which the
Speed of the Current and the Rate of Attenuation
are Variable, without any Tailing or Distortion in
Reception.
ART. 36. SOME NOTES ON THE THEORY OF THE TELEPHONE,
AND ON HYSTERESIS.
ART. 37. ELECTROSTATIC CAPACITY OF OVERGROUND WIRES.
ART. 38. MR. W. H. PREECE ON THE SELF-INDUCTION OF WIRES.
ART. 39. NOTES ON NOMENCLATURE.
NOTE 4. Magnetic Resistance, etc. - - - -
NOTE 5. Magnetic Reluctance.
VII
PAGE
132
137
141
146
151
155
159
160
165
168
vfii ELECTRICAL PAPERS.
PAGE
ART. 40. ON THE SELF-INDUCTION OF WIRES.
PART 1. Remarks on the Propagation of Electromagnetic Waves
along Wires outside them, and the Penetration of
Current into Wires. Tendency to Surface Concen-
tration. Professor Hughes' s Experiments. - - 168
New (Duplex) Method of Treating the Electromagnetic
Equations. The Flux of Energy. 172
Application of the General Equations to a Round Wire
with Coaxial Return-Tube. The Differential Equa-
tions and Normal Solutions. Arbitrary Initial State. 175
Simplifications. Thin Return Tube of Constant Resis-
tance. Also Return of no Resistance. - - - 178
Ignored Dielectric Displacement. Magnetic Theory of
Establishment of Current in a Wire. Viscous Fluid
Analogy. 181
Magnetic Theory of S.H. Variations of Impressed Voltage
and resulting Current. 183
PART 2. Extension of General Theory to two Coaxial Conducting
Tubes. 185
Electrical Interpretation of the Differential Equations.
Practical Simplification in terms of Voltage V and
Current C. - 186
Previous Ways of treating the subject of Propagation
along Wires. - 190
The Effective Resistance and Inductance of Tubes. - 192
Train of Waves due to S.H. Impressed Voltage. Practi-
cal Solution. 194
Effects of Quasi -Resonance. Fluctuations in the Im-
pedance. - - - 195
Derivation of Details from the Solution for the Total
Current. 197
Note on the Investigation of Simple-Harmonic States. - 198
PART 3. Remarks on the Expansion of Arbitrary Functions in
Series. 201
The Conjugate Property U-^- T1Z in a Dynamical System
with Linear Connections. 202
Application to the General Electromagnetic Equations. - 203
Application to any Electromagnetic Arrangements sub-
ject to V = ZC. 204
CONTENTS. ix
PAGE
Determination of Size of Normal Systems of V and G to
express Initial State. Complete Solutions obtainable
with any Terminal Arrangements provided 7?, S, L
are Constants. 206
Complete Solutions obtainable when R, S, L are Func-
tions of z, though not of p. Effect of Energy in
Terminal Arrangements. 207
Case of Coaxial Tubes when the Current is Longitudinal.
Also when the Electric Displacement is Negligible. - 208
Coaxial Tubes with Displacement allowed for. Failure
to obtain Solutions in Terms of Fand (7, except when
Terminal Conditions are F<7 = 0, or when there are
no Terminals, on account of the Longitudinal Energy-
Flux in the Conductors. 210
Verification by Direct Integrations. A Special Initial
State. - 212
The Effect of Longitudinal Impressed Electric Force in
the Circuit. The Condenser Method. - - 215
Special Cases of Impressed Force. 217
How to make a Practical Working System of V and G
Connections. 218
PART 4. Practical Working System in terms of V and G admitting
of Terminal Conditions of the Form V- ZG. 219
Extension to a Pair of Parallel Wires, or to a Single Wire. 220
Effect of Perfect Conductivity of Parallel Straight Con-
ductors. Lines of Electric and Magnetic Force
strictly Orthogonal, irrespective of Form of Section
of Conductors. Constant Speed of Propagation. - 221
Extension of the Practical System to Heterogeneous
Circuits, with "Constants" varying from place to
place. Examination of Energy Properties. - 222
The Solution for V and G due to an Arbitrary Distribu-
tion of e, subject to any Terminal Conditions. - - 225
Explicit Example of a Circuit of Varying Resistance, etc.
Bessel Functions. 229
Homogeneous Circuit. Fourier Functions. Expansion
of Initial State to suit the Terminal Conditions. - 231
Transition from the Case of Eesistance, Inertia, and
Elastic Yielding to the same without Inertia. - - 234
Transition from the Case of Eesistance, Inertia, and
Elastic Yielding to the same without Elastic Yielding. 235
ELECTRICAL PAPERS.
PAGE
On Telephony by Magnetic Influence between Distant
Circuits. - - 237
PART 5. St. Venant's Solutions relating to the Torsion of Prisms
applied to the Problem of Magnetic Induction in
Metal Rods, with the Electric Current longitudinal,
and with close-fitting Return-Current. - - - 240
Subsidence of initially Uniform Current in a Rod of
Rectangular Section, with close-fitting Return-Current. 243
Effect of a Periodic Impressed Force acting at one end
of a Telegraph Circuit with any Terminal Conditions.
The General Solution. 245
Derivation of the General Formula for the Amplitude of
Current at the End remote from the Impressed Force. 248
The Effective Resistance and Inductance of the Terminal
Arrangements. 250
Special Details concerning the above. Quickening Effect
of Leakage. The Long-Cable Solution, with Magnetic
Induction ignored. 252
Some Properties of the Terminal Functions. - 254
PART 6. General Remarks on the Christie considered as an In-
duction Balance. Full- Sized and Reduced Copies. - 256
Conjugacy of Two Conductors in a Connected System.
The Characteristic Function and its Properties. - 258
Theory of the Christie Balance of Self-induction. - 262
Remarks on the Practical Use of Induction Balances,
and the Calibration of an Induetometer. - - - 265
Some Peculiarities of Self-induction Balances. Inad-
equacy of S.H. Variations to represent Intermittences. 269
Disturbances produced by Metal, Magnetic and Non-
magnetic. The Diffusion - Effect. Equivalence of
Nonconducting Iron to Self-induction. - - - 273
Inductance of a Solenoid. The Effective Resistance and
Inductance pf Round Wires at a given Frequency,
with the Current Longitudinal ; and the Correspond-
ing Formulae when the Induction is Longitudinal. - 277
The Christie Balance of Resistance, Permittance, and
Inductance. 280
General Theory of the Christie Balance with Self and
Mutual Induction all over. 281
Examination of Special Cases. Reduction of the Three
Conditions of Balance to Two. 284
CONTENTS. xi
PAGE
Miscellaneous Arrangements. Effects of Mutual Induc-
tion between the Branches. ... . 286
PART 7. Some Notes on Part VI. (1). Condenser and Coil Balance. 289
(2). Similar Systems. 290
(3). The Christie Balance of Kesistance, Self and Mutual
Induction. 291
(4). Reduction of Coils in Parallel to a Single Coil. - 292
(5). Impressed Voltage in the Quadrilateral. General
Property of a Linear Network. - - - 294
Note on Part III. Example of Treatment of Terminal
Conditions. Induction-Coil and Condenser. - - 297
Some Notes on Part IV. Looped Metallic Circuits.
Interferences due to Inequalities, and consequent
Limitations of Application. - ... 302
PART 8. The Transmission of Electromagnetic Waves along Wires
without Distortion. - - 307
Properties of the Distortionless Circuit itself, and Effect
of Terminal Reflection and Absorption. - - - 311
Effect of Resistance and Conducting Bridges Inter-
mediately Inserted. - - 315
Approximate Method of following the Growth of Tails,
and the Transmission of Distorted Waves. - - 318
Conditions Regulating the Improvement of Transmission. 322
ART. 41. ON TELEGRAPH AND TELEPHONE CIRCUITS.
APP. A. On the Measure of the Permittance and Retardation of
Closed Metallic Circuits. - - 323
APP. B. On Telephone Lines (Metallic Circuits) considered as
Induction-Balances. - 334
APP. C. On the Propagation of Signals along Wires of Low
Resistance, especially in reference to Long-Distance
Telephony. 339
ART. 42. ON RESISTANCE AND CONDUCTANCE OPERATORS, AND
THEIR DERIVATIVES, INDUCTANCE AND PERMIT-
TANCE, ESPECIALLY IN CONNECTION WITH ELEC-
TRIC AND MAGNETIC ENERGY.
General Nature of the Operators. - - 355
S.H. Vibrations, and the effective R', L', Kf, and #'. 356
Impulsive Inductance and Permittance. General Theorem relat-
ing to the Electric and Magnetic Energies. - ... 359
xii ELECTRICAL PAPERS.
PAGE
General Theorem of Dependence of Disturbances solely on the
Curl of the Impressed Forcive. - 361
Examples of the Forced Vibrations of Electromagnetic Systems. - 363
Induction-Balances — General, Sinusoidal, and Impulsive. - - 366
The Resistance Operator of a Telegraph Circuit. .... 367
The Distortionless Telegraph Circuit. - 369
The Use of the Resistance-Operator in Normal Solutions. - - 371
ART. 43. ON ELECTROMAGNETIC WAVES, ESPECIALLY IN RE-
LATION TO THE VORTICITY OF THE IMPRESSED
FORCES ; AND THE FORCED VIBRATIONS OF ELEC-
TROMAGNETIC SYSTEMS.
PART 1. Summary of Electromagnetic Connections. - - - 375
Plane Sheets of Impressed Force in a Nonconducting
Dielectric. 376
Waves in a Conducting Dielectric. How to remove the
Distortion due to the Conductivity. .... 378
Undistorted Plane Waves in a Conducting Dielectric. - 379
Practical Application. Imitation of this Effect. - - 379
Distorted Plane Waves in a Conducting Dielectric. - - 381
Effect of Impressed Force. - 384
True Nature of Diffusion in Conductors. - ... 385
Infinite Series of Reflected Waves. Remarkable Identi-
ties. Realized Example. 387
Modifications made by Terminal Apparatus. Certain
Cases easily brought to Full Realization. - - - 390
Note A. The Electromagnetic Theory of Light. - - 392
NoteB. The Beneficial Effect of Self-Induction. - 393
Note C. The Velocity of Electricity. - - - - 393
PART 2. Note on Part 1. The Function of Self-induction in the
Propagation of Waves along Wires. - - 396
PART 3. Spherical Electromagnetic Waves. - - - 402
The Simplest Spherical Waves. - - 403
Construction of the Differential Equations connected with
a Spherical Sheet of Vorticity of Impressed Force. - 406
Practical Problem. Uniform Impressed Force in the
Sphere. 409
Spherical Sheet of Radial Impressed Force. - - - 414
CONTENTS. xiii
PAGE
Single Circular Vortex Line. 414
An Electromotive Impulse. wi = l. - - - - 417
Alternating Impressed Forces. - - 418
Conducting Medium, m = 1. 420
A Conducting Dielectric, m = 1. 422
Current in Sphere constrained to be uniform. - - - 423
PART 4. Spherical "Waves (with Diffusion) in a Conducting
Dielectric. 424
The Steady Magnetic Field due to /Constant. - - 425
Variable State when pj ;= p2. First Case. Subsiding/. - 425
Second Case. / Constant. 425
Unequal p1 and p2. General Case. - - - - - 426
Fuller Development in a Special Case. Theorems
involving Irrational Operators. 427
The Electric Force at the Origin due iofv at r = a. - 429
Effect of uniformly magnetizing a Conducting Sphere
surrounded by a Nonconducting Dielectric. - - 430
Diffusion of Waves from a Centre of Impressed Force in
a Conducting Medium. ....... 432
Conducting Sphere in a Nonconducting Dielectric. Circu-
lar Vorticity of e. Complex Keflexion. Special very
Simple Case. 433
Same Case with Finite Conductivity. Sinusoidal Solution. 435
Resistance at the Front of a Wave sent along a Wire. - 436
Reflecting Barriers. 438
Construction of the Operators y1 and y0. ... 439
Thin Metal Screens. 440
Solution with Outer Screen ; Kx = oo ; /constant. - - 441
Alternating/ with Reflecting Barriers. Forced Vibrations, 442
PART 5. Cylindrical Electromagnetic Waves. .... 443
Mathematical Preliminary. 444
Longitudinal Impressed E.M.F. in a Thin Conducting
Tube. - - 447
Vanishing of External Field. J0a = 0. - - - - 448
Case of Two Coaxial Tubes. - - - - - - 449
xiv ELECTRICAL PAPERS.
PAGE
Perfectly Reflecting Barrier. Its Effects. Vanishing of
Conduction Current. - 451
# = 0 and #=oo. - 451
,9 = 0. Vanishing of E all over, and of F and H also
internally. 452
.s = 0 and #, = 0. 452
Separate Actions of the Two Surfaces of curl e. 453
Circular Impressed Force in Conducting-Tube. - 454
Cylinder of Longitudinal curl of e in a Dielectric. - - 455
Filament of curl e. Calculation of Wave. - - - 456
PART 6. Cylindrical Surface of Circular curl e in a Dielectric. - 457
Jla = 0. Vanishing of External Field. - 458
y = i. Unbounded Medium. 459
s=0. Vanishing of External E. 459
Effect of suddenly Starting a Filament of e. - - - 460
Sudden Starting of e longitudinal in a Cylinder. - - 461
Cylindrical Surface of Longitudinal /, a Function of 0
and*. 466
Conducting Tube, e Circular, a Function of 0 and t. - 467
ART. 44. THE GENERAL SOLUTION OF MAXWELL'S ELECTRO-
MAGNETIC EQUATIONS IN A HOMOGENEOUS ISO-
TROPIC MEDIUM, ESPECIALLY IN REGARD TO THE
DERIVATION OF SPECIAL SOLUTIONS, AND THE
FORMULAE FOR PLANE WAVES.
Equations of the Field. 468
General Solutions. .... 469
Persistence or Subsidence of Polar Fields. - 469
Circuital Distributions. 470
Distortionless Cases. • 470
First Special Case. 471
Second Special Case. - 472
Impressed Forces. 473
Primitive Solutions for Plane Waves. - - - 473
Fourier-Integrals. 474
Transformation of the Primitive Solutions (17). . - - - 475
Special Initial States. 476
CONTENT. xv
PAGE
Arbitrary Initial States. - 477
Evaluation of Fourier-Integrals. - ... 478
Interpretation of Results. 479
POSTCRIPT. On the Metaphysical Nature of the Propagation of the
Potentials. 483
ART. 45. LIGHTNING DISCHARGES, ETC. - 486
ART. 4G. PRACTICE VERSUS THEORY. — ELECTROMAGNETIC
WAVES. - 488
ART. 47. ELECTROMAGNETIC WAVES, THE PROPAGATION OF
POTENTIAL, AND THE ELECTROMAGNETIC EFFECTS
OF A MOVING CHARGE.
PART 1. The Propagation of Potential. 490
PART 2. Convection Currents. Plane Wave. .... 492
PART 3. A Charge moving at any Speed < v. - • • • 494
PART 4. Eolotropic Analogy. - 496
ART. 48. THE MUTUAL ACTION OF A PAIR OF RATIONAL
CURRENT-ELEMENTS. 500
ART. 49. THE INDUCTANCE OF UNCLOSED CONDUCTIVE CIR-
CUITS. 502
ART. 50. ON THE ELECTROMAGNETIC EFFECTS DUE TO THE
MOTION OF ELECTRIFICATION THROUGH A DI-
ELECTRIC.
Theory of the Slow Motion of a Charge. 504
The Energy and Forces in the Case of Slow Motion. - - - 505
General Theory of Convection Currents. 508
Complete Solution in the Case of Steady Rectilinear Motion.
Physical Inanity of ^. - - 510
Limiting Case of Motion at the Speed of Light. Application to
a Telegraph Circuit. - - - 511
Special Tests. The Connecting Equations. - - 513
The Motion of a Charged Sphere. The Condition at a Surface of
Equilibrium (Footnote). - - - 514
The State when the Speed of Light is exceeded. - 515
A Charged Straight Line moving in its own Line. - - - 516
A Charged Straight Line moving Transversely. - - 517
A Charged Plane moving Tranversely. ..... 517
A Charged Plane moving in its own Plane. - ... 519
xvi ELECTRICAL PAPERS.
PAGE
ART. 51. DEFLECTION OF AN ELECTROMAGNETIC WAVE BY
MOTION OF THE MEDIUM. - 519
ABT. 52. ON THE FORCES, STRESSES, AND FLUXES OF ENERGY
IN THE ELECTROMAGNETIC FIELD.
(Abstract). - - 521
General Remarks, especially on the Flux of Energy. - - 524
On the Algebra and Analysis of Vectors without Quaternions.
Outline of Author's System. - 528
On Stresses, irrotational and rotational, and their Activities. - 533
The Electromagnetic Equations in a Moving Medium. 539
The Electromagnetic Flux of Energy in a Stationary Medium. 541
Examination of the Flux of Energy in a Moving Medium, and
Establishment of the Measure of " True " Current. - - 543
Derivation of the Electric and Magnetic Stresses and Forces from
the Flux of Energy. 548
Shorter Way of going from the Circuital Equations to the Flux of
Energy, Stresses, and Forces. 550
Some Remarks on Hertz's Investigation relating to the Stresses. 552
Modified Form of Stress-Vector, and Application to the Surface
separating two Regions. 554
Quaternionic Form of Stress-Vector. 556
Remarks on the Translational Force in Free Ether. ... 557
Static Consideration of the Stresses. — Indeterminateness. . - 558
Special Kinds of Stress Formulae statically suggested. - - 561
Remarks on Maxwell's General Stress 563
A worked-out Example to exhibit the Forcives contained in
Different Stresses. - 565
A Definite Stress only obtainable by Kinetic Consideration of the
Circuital Equations and Storage and Flux of Energy. - 568
APPENDIX. Extension of the Kinetic Method of arriving at the
Stresses to cases of Non-linear Connection between the
Electric and Magnetic Forces and the Fluxes. Preservation
of Type of the Flux of Energy Formula. .... 570
Example of the above, and Remarks on Intrinsic Magnetization
when there is Hysteresis. 573
ABT. 53. THE POSITION OF 4?r IN ELECTROMAGNETIC UNITS. - 575
INDEX, 579
ELECTRICAL PAPERS.
XXXI. ON THE ELECTROMAGNETIC WAVE-SURFACE.
[PhU. May., June, 1885, p. 397, S. 5, vol. 19.]
MAXWELL showed (Electricity and Magnetism, vol. ii., art. 794) that his
equations of electromagnetic disturbances, on the assumption that the
electric capacity varies in different directions in a crystal, lead to the
Fresnel form of wave-surface. There is no obscurity arising from the
ignored wave of normal disturbance, because the very existence of a
plane wave requires that there be none. In fact, the electric displace-
ment and the magnetic induction are both in the wave-front, and are
perpendicular to one another. The magnetic force and induction are
parallel, on account of the constant permeability; whilst the electric
force, though not parallel to the displacement, is yet perpendicular to
the magnetic induction (and force) ; the normal to the wave-front, the
electric force, and the displacement being in one plane. The ray is also
in this plane, perpendicular to the electric force. There are of course
two rays for (in general) every direction of wave-normal, each with
separate electromagnetic variables to which the above remarks apply.
It is easily proved, and it may be legitimately inferred without a
formal demonstration, from a consideration of the equations of induction,
that if we consider the dielectric to be isotropic as regards capacity, but
eolotropic as regards permeability, the same general results will follow,
if we translate capacity to permeability, electric to magnetic force, and
electric displacement to magnetic induction. The three principal
velocities will be (c/Xj)-*, (c/*2)-i, and (cfi3)-t, if c is the constant value
of the capacity, and /xp fj..2, ^ are the three principal permeabilities.
The wave-surface will be of the same character, only differing in the
constants.
But a dielectric may be eolotropic both as regards capacity and
permeability. The electric displacement is then a linear function of
the electric force, and the magnetic induction another linear function
of the magnetic force. The principal axes of capacity, or lines of
parallelism of electric force and displacement, cannot, in the general
case, be assumed to have any necessary relation to the principal axes of
permeability, or lines of parallelism of magnetic force and induction.
H.E.P. — VOL. ii. A
2 ELECTRICAL PAPERS.
Disconnecting the matter altogether from the hypothesis that light
consists of electromagnetic vibrations, we shall inquire into the condi-
tions of propagation of plane electromagnetic waves in a dielectric
which is eolotropic as regards both capacity and permeability, and
determine the equation to the wave-surface.
For any direction of the normal (to the wave-front, understood) there
are in general two normal velocities, i.e., there are two rays differently
inclined to the normal whose ray-velocities and normal wave-velocities
are different. And for any direction of ray there are in general two
ray-velocities, i.e., two parallel rays having different velocities and
wave-fronts.
In any wave (plane) the electric displacement and the magnetic
induction must be always in the wave-front, i.e., perpendicular to the
normal. But they are only exceptionally perpendicular to one another.
In any ray the electric force and the magnetic force are both perpen-
dicular to the direction of the ray. But they are only exceptionally
perpendicular to one another.
The magnetic force is always perpendicular to the electric displace-
ment, and the electric force perpendicular to the magnetic induction.
This of course applies to either wave. If we have to rotate the plane
through the normal and the magnetic force through an angle 0 to bring
it to coincide with the magnetic induction, we must rotate the plane
through the normal and the electric displacement through the same
angle 0 in the same direction to bring it to coincide with the electric
force, the axis of rotation being the normal itself.
In the two waves having a common wave-normal, the displacement
of either is parallel to the induction of the other. And in the two rays
having a common direction, the magnetic force of either is parallel to
the electric force of the other.
Nearly all our equations are symmetrical with respect to capacity and
permeability ; so that for every equation containing some electric
variables there is a corresponding one to be got by exchanging electric
force and magnetic force, etc. And when the forces, inductions, etc.,
are eliminated, leaving only capacities and permeabilities, these may be
exchanged in any formula without altering its meaning, although its
immediate Cartesian expansion after the exchange may be entirely
different, and only convertible to the former expression by long
processes.
If either /* or c be constant, we have the Fresnel wave-surface.
Perhaps the most important case besides these is that in which the
principal axes of permeability are parallel to those of capacity. There
are then six principal velocities instead of only three, for the velocity
of a wave depends upon the capacity in the direction of displacement
as well as upon the permeability in the direction of induction. For
instance, if /x15 ^2, ^ and c1? c2, c3, are the principal permeabilities and
capacities, arid the wave-normal be parallel to the common axis of ^
and Cj, the other principal axes are the directions of induction and dis-
placement, and the two normal velocities are (^3)'* and (c^.2}~^
The principal sections of the wave-surface in this case are all ellipses
ON THE ELECTROMAGNETIC WAVE-SURFACE. 3
(instead of ellipses and circles, as in the one-sided Fresnel-wave) ; and
two of these ellipses always cross, giving two axes of single-ray velocity.
But should the ratio of the capacity to the permeability be the same for
all the axes (/V^ = /*2/c2 = />i3/c3), the wave-surface reduces to a single
ellipsoid, and any line is an optic axis. There is but one velocity, and
no particular polarization. If the ratio is the same for two of the axes,
the third is an optic axis.
Owing to the extraordinary complexity of the investigation when
written out in Cartesian form (which I began doing, but gave up aghast),
some abbreviated method of expression becomes desirable. I may also
add, nearly indispensable, owing to the great difficulty in making out
the meaning and mutual connections of very complex formulae. In fact
the transition from the velocity-equation to the wave-surface by proper
elimination would, I think, baffle any ordinary algebraist, unassisted by
some higher method, or at any rate by some kind of shorthand algebra,
I therefore adopt, with some simplification, the method of vectors,
which seems indeed the only proper method. But some of the principal
results will be fully expanded in Cartesian form, which is easily done.
And since all our equations will be either wholly scalar or wholly vector,
the investigation is made independent of quaternions by simply defining
a scalar product to be so and so, and a vector product so and so. The
investigation is thus a Cartesian one modified by certain simple abbre-
viated modes of expression.
I have long been of opinion that the sooner the much needed intro-
duction of quaternion methods into practical mathematical investigations
in Physics takes place the better. In fact every analyst to a certain
extent adopts them : first, by writing only one of the three Cartesian
scalar equations corresponding to the single vector equation, leaving the
others to be inferred ; and next, by writing the first only of the three
products which occur in the scalar product of two vectors. This,
systematized, is I think the proper and natural way in which quaternion
methods should be gradually brought in. If to this we further add the
use of the vector product of two vectors, immensely increased power is
given, and we have just what is wanted in the tridimensional analytical
investigations of electromagnetism, with its numerous vector magni-
tudes.
It is a matter of great practical importance that the notation should
be such as to harmonize with Cartesian formulse, so that we can pass
from one to the other readily, as is often required in mixed investiga-
tions, without changing notation. This condition does not appear to
me to be attained by Professor Tait's notation, with its numerous letter
prefixes, and especially by the -S before every scalar product, the
negative sign being the cause of the greatest inconvenience in transitions.
I further think that Quaternions, as applied to Physics, should be
established more by definition than at present ; that scalar and vector
products should be defined to mean such or such combinations, thus
avoiding some extremely obscure and quasi-metaphysical reasoning,
which is quite unnecessary.
The first three sections of the following preliminary contain all we
4 ELECTRICAL PAPERS.
want as regards definitions ; most of the rest of the preliminary consists
of developments and reference-formula?, which, were they given later,
in the electromagnetic problem, would inconveniently interrupt the
argument, and much lengthen the work.
Scalars and Vectors. — In a scalar equation every term is a scalar, or
algebraic quantity, a mere magnitude ; and + and - have the ordinary
signification. But in a vector equation eve :y term stands for a vector,
or directed magnitude, and + and -- are to be understood as com-
pounding like velocities, forces, etc. Putting all vectors upon one side,
we have the general form
A + B + C + D+ ... =0;
where A, B, . . . , are any vectors, which, if n in number, may be repre-
sented, since their sum is zero, by the n sides of a polygon. Let Av
Aft A3 be the three ordinary scalar components of A referred to any
set of three rectangular axes, and similarly for the other vectors. This
notation saves multiplication of letters. Then the above equation
stands for the three scalar equations
- ... =o;
- ... =o,
The - sign before a vector simply reverses its direction — that is,
negatives its three components.
According to the above, if i, j, k, be rectangular vectors of unit
length, we have
A = \A^ +JA2 + 1s.A3, ........................... (1)
etc. ; if Av A2, A3 be the components of A referred to the axes of
i, j, k. That is, A is the sum of the three vectors iAlt JA2, kA3, of
lengths Alt A2, A3, parallel to i, j, k respectively.
tiralar Product. — We define AB thus,
p ....................... (2)
and call it the scalar product of the vectors A and B. Its magnitude is
that of A x that of B x the cosine of the angle between them. Thus.
by (1) and (2),
^ = Ai, ^2 = Aj, ^3 = Ak;
and in general, N being any unit vector, AN is the scalar component of
A parallel to N, or, briefly, the N component of A. Similarly,
i2=l, J2 = l, k* = l,
because i and i are parallel and of length unity, etc. And
ij = 0, jk = 0, ki = 0,
because i and j, for instance, are perpendicular. Notice that AB = BA.
We have also
A* A3
and or A"1- .-
A A~ A
ON THE ELECTROMAGNETIC WAVE-SURFACE. 5
Thus A"1 has the same direction as A; its length is the reciprocal of
that of A.
Vector Product,— We define VAB thus,
VAB - i(AJBs - A3B2) + XA& - A&) + k(^£2 - AJ}^ ..... (3)
and call VAB the vector product of A and B. Its magnitude is that of
A x that of B x the sine of the angle between them. Its direction is
perpendicular to A and to B with the usual conventional relation
between positive directions of translation and of rotation (the vine
system). Thus,
Vrj=k, Vjk = i, Vki=j.
Notice that VAB = - VBA, the direction being reversed by reversing the
order of the letters ; for, by exchanging A and B in (3), we negative
each term.
Hamilton's V- — The operator
may, since the differentiations are scalar, be treated as a vector, of
course with either a scalar or a vector to follow it. If it operate on a
scalar P we have the vector
«"*• ......................... <•>
whose three components are dP/dx, etc. If it operate on a vector A,
we have, by (2), the scalar product
and, by (3), the vector product
-
dy dz J ti\ dz dx J \dx dy
The scalar product VA is the divergence of the vector A, the amount
leaving the unit volume, if it be a flux. The vector product (7) is the
curl of A, which will occur below. There are three remarkable theorems
relating to V, viz.,
....................... (8)
(9)
(10)
Starting with P, a single-valued scalar function of position, the rise
in its value from any point to another is expressed in (8) as the line-
integral, along any line joining the points, of VPda, the scalar product
of VP and da, the vector element of the curve.
Then passing from an unclosed to a closed curve, let A be any vector
function of position (single-valued, of course). Its line-integral round
6 ELECTRICAL PAPERS.
the closed curve is expressed in (9) as the surface-integral over any
surface bounded by the curve of another vector B, which = VvA. Bc?S
is the scalar product of B and the vector element of surface f/S, whose
direction is defined by its unit normal.
Finally, passing from an unclosed to a closed surface, (10) expresses
the surface-integral of any vector C over the closed surface (normal
positive outward), as the volume-integral of its divergence within the
included space.
Linear Vector Operators. — If H be the magnetic force at a point, B the
induction, E the electric force, and D the displacement, all vectors, then
B--=/*H, and D = c;E/47r .................... (11)
express the relation of B to H and of D to E in a dielectric medium.
If it be isotropic as regards displacement, c is the electric capacity ; and
if it be isotropic as regards induction, /x is the magnetic permeability ;
c and /x are then constants, if the medium be homogeneous, or scalar
functions of position if it be heterogeneous.
We shall not alter the form of the above equations in the case of
eolotropy, when c and p become linear operators. For instance, the
induction will always be /xH, to be understood as a definite vector, got
from H another vector, in a manner fully defined by (in case we want
the developments) the following equations (not otherwise needed). Let
Hlt ..., and J5j, ..., be the components of H and B referred to any
rectangular axes. Then
Bl
(12)
where /*u, etc., are constants; which may have any values not making
HB negative; with the identities /x12 = /x21, etc. Or,
when the components are those referred to the principal axes of per-
meability, /Xj, /x2, /x3 being the principal permeabilities, all positive.
Inverse Operators. — Since B = /xH, we have H = /x~1B, where /x"1 is the
operator inverse to /x. When referred to the principal axes, we have
*'--, ri = ±, /-,'--
**i /*« th
But when referred to any rectangular axes, we have
x
by solution of (12). The accents belong to the inverse coefficients.
The rest may be written down symmetrically, by cyclical changes of
the figures. In the index-surface the operators are inverse to those in
the wave surface.
Conjugate Property. — The following property will occur frequently.
A and B being any vectors,
................................ (16)
ON THE ELECTROMAGNETIC WAVE-SURFACE. 7
or the scalar product of A and pJB equals that of B and /*A. It only
requires writing out the full scalar products to see its truth, which
results from the identities /x12 = /x91, etc. Similarly,
A/xcB = /zAcB = c/xAB, etc. ,
AB = A/z/x^B = /zA/^B, etc. ,
where in the first line c is another self-conjugate operator.
D is expressed in terms of E similarly to (12) by coefficients cn, cla>
etc. ; or, as in (13), by the principal capacities cv c2, c3.
Theorem. — The following important theorem will be required. A and
B being any vectors,
/y^VAB-^V/iA/iB .......................... (17)
For completeness a proof is now inserted, adapted from that given by
Tait. Since VAB is perpendicular to A and B, by definition of a vector
product, therefore
AVAB = 0, and B VAB = 0,
by definition of a scalar product. Therefore
A/x/*-iVAB = 0, and B/^VAB = 0,
by introducing w~l= 1. Hence
0, and /xB/x-!VAB = 0,
by the conjugate property ; that is, /*~1VAB is perpendicular to /xA and
to /*B. Or
where h is a scalar. Or
by operating by /x. To find h, multiply by any third vector C (not to
be in the same plane as A and B), giving
therefore >'
by the conjugate property. Now expand this quotient of two scalar
products, arid it will be found to be independent of what vectors A, B, C
may be. Choose them then to be i, j, k, three unit vectors parallel to
the principal axes of /x. Then
by the i, j, k properties before mentioned. This proves (17).
Transformation-Formula. — The following is very useful. A, B, C
being any vectors,
VAVBC = B(CA)-C(AB) ........................ (18)
Here CA and AB are scalar products, merely set in brackets to separate
distinctly from the vectors B and C they multiply. This formula is
evident on expansion.
ELECTRICAL PAPERS.
The Equations of Induction. — E and H being the electric and magnetic
forces at a point in a dielectric, the two equations of induction are
[vol. I., p. 449, equations (22), (23)]
/>iH; ................... ........ ,.(20)
c and /z being the capacity and permeability operators, and curl standing
for VV as defined in equation (7). Let T and G be the electric and the
magnetic current, then
r = cE/47r, G = /uH/47r ............... ....... (21)
The dot, as usual, signifies differentiation to the time. The electric
energy is EcE/87r per unit volume, and the magnetic energy H/xH/87r
per unit volume. If A is Maxwell's vector potential of the electric
current, we have also
curlA = /*H, E=-A ..................... (21o)
Similarly, we may make a vector Z the vector potential of the magnetic
current, such that [vol. I., p. 467]
-curlZ = cE, H= -Z ...................... (22)
The complete magnetic energy of any current system may, by a
well-known transformation, be expressed in the two ways
the 2 indicating summation through all space. Similarly, the electric
energy, if there be no electrification, may be written in the two ways
If there be electrification, we have also another term to add, the real
electrostatic energy, in terms of the scalar potential and electrification.
And if there be impressed electric force in the dielectric, part of G will
be imaginary magnetic current, analogous to the imaginary electric
current which may replace a system of intrinsic magnetization.
Plane Wave. — Let there be a plane wave in the medium. Its direction
is defined by its normal. Let then N be the vector normal of unit
length, and z be distance measured along the normal. If v be the
velocity of the wave-front, the rate the disturbance travels along the
normal, or the component parallel to the normal of the actual velocity
of propagation of the disturbance, we have
K=f(z-vt),
if the wave be a positive one, as we shall suppose, giving
<23>
applied to H or E.
Next, examine what the operator VV or curl becomes when, as at
present, the disturbance is assumed not to change direction, but only
ON THE ELECTROMAGNETIC WAVE-SURFACE.
9
magnitude, as we pass along the normal. Apply the theorem of Version
9) to the elementary rectangular area bounded by two sides parallel to
(9
E
of length a, and two sides of length b perpendicular to E and in the
same plane as E and the normal N. Since its area is ab, and b = dz sin 6,
Wave front
and the two sides b contribute nothing to the line-integral, we find that
curl = VN-^, (24)
applied to E or H or other vectors, in the case of a plane wave. Using
this, and (23), in the equations of induction (19), (20), they become
VN = »
dz dz
Here, since the ^-differentiation is scalar, and occurs on both sides, it
may be dropped, giving us
VNH= -wE, .............................. (25)
VNE= «^H ............................... (26)
The induction and the displacement are therefore necessarily in the
wave front, by the definition of a vector product, being perpendicular to
N. Also the displacement is perpendicular to the magnetic force, and
the induction is perpendicular to the electric force.
Index-Surface. — Let *
be a vector parallel to the normal, whose length is the reciprocal of the
normal velocity v. It is the vector of the index-surface. By (25) and
(26) we have
cE = - VsH, therefore
and /xH= VsE, -therefore
Now use the theorem (17). Then, if
- E = c~l VsH ;
(28)
(29)
* [In order to secure the advantage of black letters for vectors, I have changed
the notation thus : — The original <r is now s ; p is r ; £ is b ; y is g ; and a is a.]
10 ELECTRICAL PAPERS.
be the products of the principal permeabilities and capacities, the
theorem gives, applied to (28) and (29),
... ........... . ...... (31)
wH = V/xs/xE ....................... ........ (32)
Putting the value of H given by (32) in (28) first, and then the value
of E given by (31) in (29), we have
......................... (33)
(34)
To these apply the transformation-formula (18), giving
-mcE = /xs(s^E)-/xE(s/xs), ..................... (33a)
and - w/*H = cs(scH) - cH(scs), ...................... (340)
where the bracketed quantities are scalar products. Put in this form,
{(s^s)/x-mc}E = /xs(s/>tE), ........................ (35)
{(scs)c-7i/t*}H=es(scH), ........................ (36)
and perform on them the inverse operations to those contained in the
{}'s, dividing also by the scalar products on the right sides. Then
E (37)
—
s/uE (s/iS)/x - me
JL = __ ^_ (38)
scH (scs)c - np.
Operate by c on (37) and by //, on (38), and transfer all operators to the
denominators on the right. Then
X-** say> ................... (39)
(40)
(It should be noted that, in thus transferring operators, care should
be taken to do it properly, otherwise it had better not be done at all.
Thus, we have by (37),
and the left c and the right //, are to go inside the {}. Operate by
and then again by {}+1, thus cancelling the j}"1, giving
/xs = {(s//.s)//. - mc}c~llor
Here we can move c"1 inside, giving
and now operating by p~lt it may be moved inside, giving
as in (39).)
ON THE ELECTROMAGNETIC WAVE-SURFACE. tl
We can now, by (39) and (40), get as many forms of the index-
equation as we please. We know that the displacement is perpendicular
to the normal, and so is the induction. Hence
8b1 = 0, sb2 = 0, ......................... (41)
where bj and b2 are the above vectors, in (39) and (40), are two
equivalent equations of the index-surface.
Also, operate on (39) by s/wr1, and on (40) by Sty*"1, and the left
members become unity, by the conjugate property ; hence
f*&c-l\ = l, d3/x-ib2=l .................... (42)
are two other forms of the index-equation. (41) and (42) are the
simplest forms. More complex forms are created with that surprising
ease which is characteristic of these operators ; but we do not want any
more. When expanded, the different forms look very different, and no
one would think they represented the same surface. This is also true
of the corresponding Fresnel surface, which is comparatively simple in
expression. In any equation we may exchange the operators /x and c.
Put s = Ni'"1 in any form of index-equation, and we have the velocity-
equation, a quadratic in v2 giving the two velocities of the wave-front.
And if we pub N# = p, thus making p a vector parallel to the normal of
length equal to the velocity, it will be the vector of the surface which is
the locus of the foot of the perpendicular from the origin upon the
tangent-plane to the wave-surface.
By (33ft), remembering that s is parallel to the normal, we see that
<*
/*
and
/xN
are
in
one
plane ;]
or
E,
N,
and
/x-!CE
are
in
one
plane. J
And
by (34a),
—
MH,
df,
and
cH
are
in
one
plane ;
or
H,
N,
and
c-1
/xH
are
in
one
plane.
These conditions expanded, give us the directions of the electric force
and displacement, the magnetic force and induction, for a given normal.
We may write the second of (43) thus,
NV? ? = 0; ................................ (45)
and the second of (44) thus,
NV?? = 0; ....(46)
and as these differ only in the substitution of B for D, we see that the
induction of either ray is parallel to the displacement of the other ; that
is, the two directions of induction in the wave-front are the two
directions of displacement.
The Wave-Surface. — Since the velocity-surface with the vector p = #N
is the locus of the foot of the perpendicular on the tangent-plane to the
wave-surface, we have, if r be the vector of the wave-surface,
pr = p2 ................................... (47)
12 ELECTRICAL PAPERS.
But s the vector of the index-surface being = Nv"1 = p#~2, we have, by
(47), dividing it by ^,
sr=l .................................... (48)
To find the wave-surface, we must therefore let 8 be variable and
eliminate it between (48) and any one of the index-equations. This is
not so easy as it may appear.
General considerations may lead us to the conclusion that the equation
to the wave-surface and that to the index-surface may be turned one
into the other by the simple process of inverting the operators, turning
c into c~l and ^ into p~l. Although this will be verified later, any form
of index-equation giving a corresponding form of wave by inversion of
operators, yet it must be admitted that this requires proof. That it is
true when one of the operators c or p is a constant does not prove
that it is also true when we have the inverse compound operator
{(scs)/*"1 -nc~l}~1 containing both c and /z, neither being constant. I
have not found an easy proof. This will not be wondered at when the
similar investigations of the Fresnel surface are referred to. Professor
Tait, in his "Quaternions," gives two methods of finding the wave-
surface ; one from the velocity-equation, the other from the index-
equation. The latter is rather the easier, but cannot be said to be very
obvious, nor does either of them admit of much simplification. The
difficulty is of course considerably multiplied when we have the two
operators to reckon with. I believe the following transition from index
to wave cannot be made more direct, or shorter, except of course by
omission of steps, which is not a real shortening.
Given
*— -^ ........... (49) = (39) to
1 -1
8^ = 0, ............................ (50) -(41) to
rs=l ............................. (51) = (48) bis
Eliminate s and get an equation in r. We have also
/KSe-1!)^!, .................... (52) = (42) bis
which will assist later.
By (49) we have
S = (s/>ts)c-1b1-w/>i-1b1 ......................... (53)
Multiply by bj and use (50) ; then
0 = (s/>tsXblC-1b1)-m(b1/Jt-ib1) ..................... (54)
By differentiation, s being variable, and therefore bx also,
0 = 20s/>ts)(b1c-1b1)4-2(s/xs)0b1c-1b1) - 2m(db1/*-1b1) ....... (55)
Also, differentiating (53),
da = 2(ds/zs)c~1b1 + (BftB)rfc~1b1 - mdfjL'1^ ;
and multiplying this by 2bx gives
bl). ...(56)
ON THE ELECTROMAGNETIC WAVE-SURFACE. 13
Subtract (55) from (56) and halve the result ; thus obtaining
or {b1-(b1c-1b1)/xs}^s = 0 ....................... (57)
In the last five equations it will be understood that da and db, are
differential vectors, and that da^a is the scalar product of da and /xs,
etc. ; also in getting (56) from the preceding equation we have
\dc~l\ = bjC-^bj = d\c-l\>lt etc.
Equation (57) is the expression of the result of differentiating (50),
with dbx eliminated.
Now (57) shows that the vector in the {} is perpendicular to da, the
variation of a. But by (51) we also have, on differentiation,
rds = 0 ................................... (58)
Hence r and the { } vector in (57) must be parallel. This gives
hr^-^c-^a, ........................... (59)
where k is a scalar. If we multiply this by c~l\ and use (52), we
obtain
rc^b^O; ............................... (60)
or, by (49), giving \ in terms of cE,
rE = 0, ................................... (61)
a very important landmark. The ray is perpendicular to the electric
force.
Similarly, if we had started from — instead of (49), (50), and (52) —
the corresponding H equations, viz.,
with of course the same equation (51) connecting r and a, we should
have arrived at
&'r = b2-(b2/M-ib2)cs; .......................... (62)
h' being a constant, corresponding to (59) ; of this no separate proof is
needed, as it amounts to exchanging /x and c and turning E into H, to
make (39) become (40). And from (62), multiplying it by ft~1b2,
we arrive at
r/A-ib2 = 0, or rH = 0, ..................... (63)
corresponding to (61). The ray is thus perpendicular both to the
electric and to the magnetic force. The first half of the demonstration
is now completed, but before giving the second half we may notice some
other properties.
Thus, to determine the values of the scalar constants h and h'.
Multiply (59) by a, and use (50) and (51) ; then
h = - -
14 ELECTRICAL PAPERS.
the second form following from (54). Insert in (59), then
(64)
gives r explicitly in terms of /*s and b1? the latter of which is known in
terms of the former by (49). Multiply this by fi"1^, using (50) ; then
r/^-ib^ -m-1 ............................... (65)
Similarly we shall find
h'= - ^(bjje-ng, ............................. (66)
' ........................ (67)
and, corresponding to (65), we shall have
Tc-lb2 = -IT1 ............................... (68)
Now to resume the argument, stopped at equation (63). Up to
equation (59) the work is plain and straightforward, according to rule
in fact, being merely the elimination of the differentials, and the getting
of an equation between r and s. What to do next is not at all obvious.
From (59), or from (64), the same with h eliminated, we may obtain all
sorts of scalar products containing r and b1? and if we could put bx
explicitly in terms of r, (60) or (65) would be forms of the wave-surface
equation. From the purely mathematical point of view no direct way
presents itself; but (61) and (63), considered physically as well as
mathematically, guide us at once to the second half of the transforma-
tion from the index- to the wave-equation. As, at the commencement,
we found the induction and the displacement to be perpendicular to the
normal, so now we find that the corresponding forces are perpendicular
to the ray. There was no difficulty in reaching the index-equation
before, when we had a single normal with two values of v the normal
velocity, and two rays differently inclined to the normal. There should
then be no difficulty, by parallel reasoning, in arriving at the wave-
surface equation from analogous equations which express that the ray
is perpendicular to the magnetic and electric forces, considering two
parallel rays travelling with different ray-velocities with two differently
inclined wave-fronts.
Now, as we got the index-equation from
VNH= --roE, ........................... (25) bis
VNE = p/*H, ........................... (26) Us
we must have two corresponding equations for one ray-direction. Let
M be a unit vector defining the direction of the ray, and w be the ray-
velocity, so that
r = wM ................................... (69)
Operate on (25) and (26) by VM, giving
VMVNH= -
VMVNE=
ON THE ELECTROMAGNETIC WAVE-SURFACE. 15
Now use the formula of transformation (18), giving
N(HM) - H(MN) = -
N(EM) - E(MN) = v
But HM = 0 and EM = 0, as proved before. Also v = w(NN), or the
wave-velocity is the normal component of the ray-velocity. Hence
.............................. (70)
.............................. (71)
which are the required analogues of (25) and (26). Or, by (69),
H = VrcE, .................................. (72)
-E = Vr/*H .................................. (73)
are the analogues of (28) and (29). The rest of the work is plain.
Eliminating E and H successively, we obtain
0 = E + Vr/z VrcE,
0 = H + VrcVr/xH;
and, using the theorem (17), these give
0 = E +
which, using the transformation-formula (18), become
0 = E + mfi-lT(
0 = H + wc-1r(c
or, rearranging, after operating by ^ and c respectively,
i)mc - /x}E = mr(ft~1rcE),
Or _^ = r -r=gl, say, (74)
TT _,
-~ — = = 7 — =-r r=&» say (75)
c-lifjR (rcr1!)/* - n~lc
These give us the four simplest forms of equation to the wave. For,
since rE = 0 = rH, we have
rg! = 0, rg2 = 0 (76)
Also, operating on (74) by p~lrc and on (75) by c"1!/* we get
/x~1rcg1 = l, c-1r/>tg2=l, (77)
two other forms.
gl and g2 differ from bx and b2 merely in the change from a to r, and
in the inversion of the operators. The two forms of wave (76) are
analogous to (41), and the two forms (77) analogous to (42), inverting
operators and putting r for s.
Similarly,, if the wave-surface equation be given and we require that
16 ELECTRICAL PAPERS.
of the index-surface, we must impose the same condition rs = 1 as before,
and eliminate r. This will lead us to
scg^O, *P8i=-™> ....................... (78)
corresponding to (60) and (65) ; and
s/*g2 = 0, scg2=-rc, ............. .......... (79)
corresponding to (63) and (68); and the first of (78) and (79) are
equivalent to
or the displacement and the induction are perpendicular to the normal.
This completes the first half of the process ; the second part would be
the repetition of the already given investigation of the index-equation.
The vector rate of transfer of energy being VEH/4?r in general, when
a ray is solitary, its direction is that of the transfer of energy. It seems
reasonable, then, to define the direction of a ray, whether the wave is
plane or not, as perpendicular to the electric and the magnetic forces.
On this understanding, we do not need the preliminary investigation of
the index-surface, but may proceed at once to the wave-surface by the
investigation (69) to (77), following equations (25) and (26).
The following additional useful relations are easily deducible : — From
(25) and (26) we get
^
............................... (
and from (72) and (73),
-s .................................... <">
Also, from either set,
EcE = H/xH, ..................... .....-..-....:. (8-2)
expressing the equality of the electric to the magnetic energy per unit
volume (strictly, at a point).
Some Cartesian Expansions. — In the important case of parallelism of
the principal axes of capacity and permeability, the full expressions for
the index- or the wave-surface equations may be written down at once
from the scalar product abbreviated expressions. Thus, taking any
equation to the wave, as the first of (76), for example, igl = 0t gl being
given in (74), take the axes of coordinates parallel to the common
principal axes of c and /*; so that we can employ cv c2, ca, the principal
capacities, and pv p.2, /*3 the principal permeabilities in the three com-
ponents of gr We then have, xt y^z being the coordinates of r,
X2 I/2 Z2
+ ~l - ~ ~ '
where r/x li = — h — H ---
A*i f*a /*3
In (83) we may exchange the c's and /x's, getting the second of (76).
Similarly the first of (77) gives
ON THE ELECTROMAGNETIC WAVE-SURFACE. 17
as another form, in which, again, the yu's and c's may be exchanged (not
forgetting to change m into n) to give a fourth form.
These reduce to the Fresnel surface if either /zx = /x2 = /*3 or
Ci = c2 = cy
Let x = 0 to find the sections in the plane y, z. The first denominator
in (83) gives
--0- °r
representing an ellipse, semiaxes
% = (%)-* and
The other terms give
Or
an ellipse, semiaxes v31 = (c^) ~ * and % = (ca/^1)~*. Similarly, in the
plane 2, a; the sections are ellipses whose semiaxes are #21, fl23, and v12,
v32, where for brevity vrs = (crfj,s) ~ * ; and in the plane #, y, the ellipses
have semiaxes %, 032, and 013, #12.
In one of the principal planes two of the ellipses intersect, giving
four places where the two members of the double surface unite.
If GJ//ZJ = c2//x2 = c3//A3, we have a single ellipsoidal wave-surface whose
equation is
++=1 .............................. 85)
Now, of course, <y12 = %> etc.
When the p and c axes are not parallel, we cannot immediately write
down the full expansion of the wave-surface equation. Proceed thus : —
Taking Tgl = 0 as the equation, let
R = m(i^-li), and a = m~1g1;
then, by (74) and (76),
r r = 0, or ra = 0,
He- p
where r = (Jfc-/x)a .................................. (86)
R is a scalar. If «15 a2, as are the three components of a referred to
any rectangular axes, and x, y, z the components of r, we have, by (86)
and (12),
x = (Ecu -
y = (Ec21 -
z = (jBc81 -
from which alt ft2, % may be solved in terms of x, y, z \ thus
H.E.P. — VOL. II.
18 ELECTRICAL PAPERS.
where, by using (15),
and the rest by symmetry. Then, since
ra = xa1 + ya.2 + zaB = 0,
we get the full expansion. A need not be written fully, as it goes out.
The equation may be written symmetrically, thus,
0 = 1+ mn(in~ II)(TG~ IT) — < x2(c22pBB + c33/x22 - 2c23/x23) + . . .
where the coefficients of y2, z2, yz, and zx are omitted. Here m =
and n = c-,c9Co • whilst
where c^, ..., are the inverse coefficients. See equation (15). The
expansion of Tp~lT is exactly similar, using the inverse /* coefficients.
If in (87) we for every c or /x write the reciprocal coefficients, we
obtain the equation to the index-surface ; that is, supposing x, y, z then
to be the components of s instead of r. And, since sy = N, the unit
wave-normal, we have the velocity-equation as follows, in the general
case,
3 - cf8/4, - ^Va + ...}, ...... (88)
in which JVlf N2, NB are the components of N, or the direction-cosines
of the normal. To show the dependence of v2 upon the capacity and
permeability perpendicular to N, take ^ = 1, N2 = Q, ^3 = 0, which
does not destroy generality, because in (88) the axes of reference are
arbitrary. Then (88) reduces to
- = o.
When the /x and c axes are parallel, and their principal axes are those
of reference, we have
K + 4)}, (89)
where
with a similar expression for NcN, and %=(c2/*3)~^, etc., as before.
The solution is
...... (90)
where X= Nfuf + Nfu* + NM - 2(JV1W22w1w2 + NiNfu^ + Nf
in which = - ^ = - M = «-«
ON THE ELECTROMAGNETIC WAVE-SURFACE. 19
Take UL = 0, or c2//x2 = c3//*3 ; the two velocities (squared) are then
Nfvj, + M4 + Nffi* and Nfv^ + M«i + N^
reducing to one velocity v23 when Nt = 1.
If, further, u2 = 0, or w3 = 0, making CJ//AJ = £2//u2 = c3//x3, Jf=0
always, and
........................ (92)
is the single value of the square of velocity of wave-front.
Directions of E, H, D, and B. — We may expand (45) to obtain an
equation for the two directions of the induction and displacement.
Thus, since
- = i(c'n A
t/
the determinant of the coefficients of i, j, k equated to zero gives the
required equation. When the principal axes of //, and c are parallel,
the equation greatly simplifies, being then
(93)
where uv ..., are the same differences of squares of principal velocities
as in (91). For Dv etc., write £v etc. ; and we have the same equa-
tion for the induction directions. For A, etc., write c^, etc., and the
resulting equation gives the directions of E. For Dlt etc., write
etc., and the resulting equation gives the directions of H.
Note on Linear Operators and Hamilton's Cubic. (June 12th, 1892.)
[The reason of the ease with which the transformations concerned in
the above can usually be effected is, it will be observed, the symmetrical
property AcB = BcA of the scalar products. But when a linear operator,
say c, is not its own conjugate, some change of treatment is required.
Thus, let
Dl = cuE^ + c12E2 + c13#3, D{
D3 = c81^ + c32E2 + c33^3, Di = c13^ + c2BE2 + c33#3,
where the nine c's are arbitrary. We may then write
D = cE, D^c'E,
where the operator c' only differs from c in the exchange of c12 and c21,
20 ELECTRICAL PAPERS.
etc. It is now D' that is conjugate to D, whilst c' is the operator
conjugate to c. It may be readily seen that
D'=/E-VeE,
where / is the self-conjugate operator obtained by replacing c12 and c21,
etc., in c by half their sums, and e is a certain vector whose components
are half their differences. Thus,
e = Ji(c82 - %) + ij(c13 - csl) + Jk(c21 - c12).
The conjugate property of scalar products is now
= Bc'A.
That is, in transferring the operator from B to A, we must simultane-
ously change it to its conjugate. Another way of regarding the matter
is as follows : — If we put
C2 =
we see, by the above, that
D = cE = i.c1E+
D' = c'E = Cj.iE + c2.jE + c3.kE = (Cj.i + c2.j + c3.k)E,
from which we see that c'E is the same as EC, and cE the same as EC'.
In the case of AcB, therefore, we may regard it either as the scalar
product of A and cB, or as the scalar product of Ac and B. This
is equivalent to Professor Gibbs's way of regarding linear operators.
That is (converted to my notation),
is the type of a linear operator. It assumes the utmost generality when
i, j, k stand for any three independent vectors, instead of a unit
rectangular system. Professor Gibbs has considerably developed the
theory of linear operators in his Vector Analysis.
The generalised form of (17) is got thus: — Let v and w be any
vectors, then, as before, we have
0= vVvw= vcc~1Vvw,
0 = wVvw = wcc^Vvw,
where the last forms assert that c~1Vvw is perpendicular to vc and we,
or parallel to Vvcwc ; that is,
mVvw = cVc'vc'w ', ........................... (A)
from which, by multiplying by a third vector u, we find
c'uWvc'w ,T>\
m = - == -- , ............................. (-D)
uVvw
which is an invariant.
Hamilton's cubic equation in c is obtained by observing that since
(A) is an identity, c being any linear operator, it remains an identity
ON THE ELECTROMAGNETIC WAVE-SURFACE. 21
when c is changed to c - g, which changes c' to c' - #, where g is a
scalar constant. For c - g is also a linear operator. Making this sub-
stitution in (A) and expanding, we obtain
(m - m^ + m2g2 - g*) Vvw
jc'uVc'vc'w - ^(uVc'vc'w + vVc'wc'u + wVc'uc'v)
+ #2(c'uVvw + c'vVwu + c'wVuv) - #3uVvw j
= cVc'vc'w - ^(Vc'vc'w + cVvc'w + cVc'vw)
+ #2(cVvw + Vvc'w + Vc'vw) - #3Vvw,
where m, mv m2 are the coefficients of #°, - g, and g2 in the expansion of
the left member of m given by (B). Comparing coefficients we see that
#° and g3 go out. The others give (remembering that we are dealing
with an identity),
Vc'vc'w + c( Vvc'w + Vc'vw) = ?%Vvw,
cVvw + (Vvc'w + Vcrvw) = w2Vvw.
Operate on the first by c and second by c2, and subtract. This eliminates
the vector in the brackets, and leaves
cVc'vc'w - c3 Vvw = m:cVvw - m2c2 Vvw,
where the first term on the left is mVvw. So we have
m - m^c + m2c2 - c3 = 0, ......................... (C)
which is Hamilton's cubic.
If we start instead with the conjugate operator cf we shall arrive at
m'Vvw = c'Vcvcw, where W' = ^L ^vcw
uVvw
and then, later, to the cubic
ra' - m(c' + m2'c'2 - c/3 = 0,
where m', etc., come from m, etc., by exchanging c and c'. But it may
be easily proved that m = m', and we may infer from this that m1 = m{
and m2 = rti2, on account of the invariantic character of m being pre-
served when c becomes c - g. In fact, putting c =/+ Ve and cf =/- Ve,
where /is self-conjugate, we may independently show that
Vw cuVcvcw c'uVc'vc'w
m -
m - m' -
uVvw uVvw uVvw
w/u + wV/u/v
uVvw
uVcvcw + vVcwcu + wVcucv
uVvw
= / = /n Vvw +/v Vwu +/w Vuv = game with c = same with c,
uVvw
So in Hamilton's cubic (C) we may change c to c', leaving the ra's
22 ELECTRICAL PAPERS.
unchanged ; or else in the m's only ; or make the change in both the c's
and the m's, without affecting its truth.
If the passage from (A) to (C) above be compared with the corre-
sponding transition in Tait's Quaternions (3rd edition, §§ 158 to 160) it
will be seen that that rather difficult proof is simplified (as done above)
by omitting altogether the inverse operations $~l and (^ - g)~l and the
auxiliary operator x ', especially x> perhaps. One is led to think from
Professor Tait's proof that the object of the investigation is to solve
the problem of inverting <£. But the mere inversion can be done by
elementary methods. In Gibbs's language, if a, b, c is one set of
vectors, the reciprocal set is a', b', c', given by
a/_Vbc b/_Vca ,_ Vab
~aVbc' ~bW ~cVa¥
On this understanding, we may expand any vector d in terms of
a, b, c thus : —
d = a . a'd + b . b'd + c . c'd.
Similarly, if 1', m', n' is the set reciprocal to 1, m, n, we have
r = 1'. lr + m'. mr + n'. nr.
If, then, it be given that
d = <£(r) = a.lr + b.mr + c.nr,
we see that lr = a'd, etc., so that
r = ^(d) = 1'. a'd + m'. b'd + n'. c'd
inverts <£. (This is equivalent to Tait, § 173.)
We see by (A) and (B) that the inverts of u, v, W are c' x inverts of
cu, cv, cw; or c x inverts of c'u, c'v, c'w. The cubic (C) may be written
cu cvcw / c_! _ , _ lu/ vc-iy/ + WC-IWA I _ c / c _ /ucu/ + vcv/ + wcw') I
uVvw I 'J I
if u', v', w' are the inverts of u, v, W (or the reciprocal set). In this
identity the operators c and c"1 may be inverted. When that is done
we see that the m of c is the reciprocal of the m of c"1.]
Note on Modification of Index-equation when c and //. are Rotational.
[Let c' and /*' be the conjugates to c and /*. Then, by (A), (B), in
last note,
mVvw = p! V^VfjiW = />tV//v//w,
where m = /^ ^^ + e/*0e,
if /*!, /x2, /AS are the principal permeabilities of yu,0, the self-conjugate
operator such that />t = />t0 + Ye. With this extension of meaning, we
shall have (treating c and n similarly),
- E = c-1 VsH, - ?iE = Vc'sc'H, - mE = c - 1 Vs V/s/E,
H = /x-i VsE, mH = V/s/E, - nE = ^- 1V& Vc'sc'H,
NOTES ON NOMENCLATURE. 23
where the first pair replace (28), (29), the second pair (31), (32), and
the third pair (33), (34). Then
- ?fyuH = c's(sc'H) - c/H(sc/s)
replace (33«) and (34«), and
E p'B H C?B
s//E ~ (s/x's)// - me' sc'H ~~ (sc's)c' - np
replace (37a), (38a) ; from which two forms of index-equation corre-
sponding to (41) are
S 8
(s/x'sjc"1 - lap.'-1 (sc's)/^"1 - nc'~l
We obtain impossible values of the velocity for certain directions of the
normal. That is, there could not be a plane wave under the circum-
stances.]
XXXII. NOTES ON NOMENCLATURE.
[The Electrician, Note 1, Sep. 4, 1885, p. 311 ; Note 2, Jan. 26, 1886, p. 227 ;
Note 3, Feb. 12, 1886, p. 271.]
NOTE 1. IDEAS, WORDS, AND SYMBOLS.
HOWEVER desirable it may be that writers on electrotechnics should
use a common notation, at least as regards the frequently recurring
magnitudes concerned — which notation should not be a difficult matter
to arrange, provided it be kept within practical limits — it is perhaps
more desirable that they should adopt a common language, within the
same practical limits, of course. For whilst the use of certain letters
for certain magnitudes requires no more explanation than, for instance,
"Let us call the currents (7r (72, etc.," it is otherwise with the language
used when speaking of the magnitudes, as more elaborate explanations
are needed to identify the ideas meant to be expressed.
As regards electric conduction currents, there is a tolerably uniform
usage, and a fairly good terminology. It is seldom that any doubt can
arise as to a writer's meaning, unless he be an ignoramus or a para-
doxist, or have unfortunately an indistinct manner of expressing him-
self. I would, however, like to see the word "intensity," as applied to
the electric current, wholly abolished. It was formerly very commonly
used, and there was an equally common vagueness of ideas prevalent.
It is sufficient to speak of the current in a wire (total) as " the current,"
or "the strength of current," and when referred to unit area, the
current-density. (In three dimensions, on the other hand, when every-
thing is referred to the unit volume, and the current-density is meant
as a matter of course, it is equally sufficient to call it the current.)
24 ELECTRICAL PAPERS.
It is a matter of considerable practical advantage to have single words
for names, instead of groups of words, and it is fortunate that the exist-
ing conduction-current terminology admits of very practical adaptation
this way. Thus, " specific resistance " may be well called " resistivity,"
and specific conductance " conductivity," referring to the unit volume.
Resistivity is the reciprocal of conductivity, and resistance of conduct-
ance. When wires are in parallel, their conductances may be more
easy to manage than their resistances. We have also the convenient
adjectives "conductive" and "resistive," to save circumlocution.
Passing to the subject of magnetic induction, there is considerable
looseness prevailing. There is a definite magnitude called by Maxwell
"the magnetic induction," which may well be called simply "the
induction." It is related to the magnetic force in the same manner as
current-density to the electric force. (B = ^H.) The ratio p is the
" magnetic permeability." This may be simply called the permeability,
since the word is not used in any other electrical sense. Induction and
permeability may not be the best names, but (apart from their being
understood by mathematical electricians) they are infinitely better than
the long-winded "number of lines of force" (meaning magnetic) and
" conductivity for lines of force," the use of which, though defensible
enough in merely popular explanations, becomes almost absurd when
the electrotechnical user actually goes so far as to give them quantita-
tive expression. Conductivity should not be used at all, save in point-
ing out an analogy. It has its own definite meaning.
" Permeability," however, does not admit of such easy adaptation to
different circumstances as conductivity. Permeability referring to the
unit volume, the word permeance is suggested for a mass, analogous to
conductance. We have also the adjective "permeable." By adding,
moreover, the prefix "im," we get "impermeable," "impermeability,"
and " impermeance," for the reciprocal ideas, sometimes wanted. Thus
impermeability, the reciprocal of /A, would stand for the long-winded
" specific resistance to lines of magnetic force." (The permeance of a
coil would be Z/47T, if L is its coefficient of self-induction. In the
expression T=^LC* for the magnetic energy of current C in the coil, 4?r
does not appear, whilst it does in the form T= \ magnetomotive force x
total induction through the circuit -f 47r. It is kirC that is the magneto-
motive force, and LC the induction through the circuit. Thus we have
oppositely acting 47r's. I may here remark that it would be not only a
theoretical but a great practical improvement to have the electric and
magnetic units recast on a rational basis. But I suppose there is no
chance of such an extensive change.) It must be confessed, however,
that these various words are not so good as the corresponding con-
duction-current words.
But now, if, thirdly, we pass to electric displacement, the analogue of
magnetic induction (noting by the way that it had better not be called
the electric induction, on account of our already appropriating the word
induction, but be called the displacement), the existing terminology is
extremely unsatisfactory; and, moreover, does not readily admit of
adaptation and extension. Corresponding to conductivity and perme-
NOTES ON NOMENCLATURE. 25
ability we have "specific inductive capacity," or "dielectric constant,"
or whatever it may be called. I usually call it the electric capacity, or
the capacity. It refers to the unit volume. But here it is very unfor-
tunate that it is not this specific capacity c (say), but c/4?r, that is the
capacity of a unit cube condenser (such that charge = difference of
potential x capacity). D, the displacement, is the charge ( + or - ,
according to the end), and we have D = cE/4:7r, E being the electric
force. We may get over this trouble by putting it thus, D = sE, and
calling s (or c/4?r) the specific capacity. Then the capacity in bulk is
got in the same manner as conductance from conductivity.
Supposing we have done this, there is still the trouble that capacity
gives the extremely awkward inverse " incapacity," and the adjectives
"capacious" and "incapacious," besides not giving us any words for
use in bulk, like conductance and resistance. And, in addition, the
word capacity is itself rather objectionable, as likely to give beginners
entirely erroneous notions as to the physical quality involved. It is
not that one dielectric absorbs electricity more readily than another.
Electric displacement is an elastic phenomenon : one dielectric is more
yielding (electrically) than another. The reciprocal of s above is the
electric elasticity, measuring the electric force required to produce the
unit displacement. Thus s should have a name to express the idea of
elastic yielding or distortion, and its reciprocal also a name (not strings
of words), and they should be readily adaptable, like conductivity, etc.
(Perhaps also a better word than permeability might be introduced,
although, as we see, it is tolerably accommodative.) Displacement
itself might also be replaced by another word less suggestive of bodily
translation; although, on the other hand, it harmonises well with
" current," the displacement being the accumulated current, or the
current the time-variation of the displacement.
All these things will get right in time, perhaps. Ideas are of primary
importance, scientifically. Next, suitable language. As for the nota-
tion, it is an important enough matter, but still only takes the third
place.
NOTE 2. ON THE RISE AND PROGRESS OF NOMENCLATURE.
In the beginning was the word. The importance of nomenclature
was recognised in the earliest times. One of the first duties that
devolved upon Adam on his installation as gardener and keeper of the
zoological collection was the naming of the beasts.
The history of the race is repeated in that of the individual. This
grand modern generalisation explains in the most scientific manner the
fondness for calling names displayed by little children.
Passing over the patriarchal period, the fall of the Tower of Babel
and its important effects on nomenclature, the Egyptian sojourn, the
wanderings in the desert, the times of the Kings, of the Babylonian
captivity, of the minor prophets, of early Christianity, of those dreadful
middle ages of monkish learning and ignorance, when evolution worked
backwards, and of the Elizabethan revival, and coming at once to the
middle of the 19th century, we find that Mrs. Gamp was much im-
26 ELECTRICAL PAPERS.
pressed by the importance of nomenclature. " Give it a name, I beg.
Sairey, give it a name ! " cried that esteemed lady. She even went so
far as to give a name to an entirely fictitious personage — Mrs. Harris,
to wit — who has many scientific representatives.
Having thus fortified ourselves by quoting both ancient and modern
instances, let us consider the names of the electrical units.
A really practical name should be short, preferably monosyllabic,
pronounced in nearly the same way by all civilised peoples, and not
mistakable for any other scientific unit. If, in addition, it be the name,
or a part of the name, of an eminent scientist, so much the better.
This is quite a sentimental matter ; but if it does no harm, it is needless
to object to it. But we should never put the sentiment in the first
place, and give an unpractical name to a unit on account of the
sentiment.
Ohm and volt are admirable; farad is nearly as good (but surely it
was unpractical to make it a million times too big — the present micro-
farad should be the farad) ; erg and dyne please me ; watt is not quite
so good, but is tolerable. But what about those remarkable results of
the Paris Congress, the ampere and the coulomb 1 Speaking entirely
for myself, they are very unpractical. Coulomb may be turned into
coul, and is then endurable ; this unit is, however, little used. But
ampere shortened to am or amp is not nice. Better make it pere ;
then it will do. Now an additional bit of sentiment comes in to support
us. Was not Ampere the father of electrodynamics ?
It seems rather unpractical for the B.A. Committee to have selected
108 c.g.s. as the practical unit of E.M.F., instead of 109. This will
hardly be appreciated except by those who make theoretical calculations;
the awkward thing is that the pere is one tenth of the c.g.s. unit of
current. I suppose it was because the present volt was an approxima-
tion to the E.M.F. of a Daniell ; that is, however, a very strong reason
for making the practical unit much smaller; because the E.M.F. of a
cell has now to be given in volts and tenths, or hundredths also. How
awkward it would have been if the ohm had been made 1010 c.g.s., so as to
approximate to the resistance of a mile of iron telegraph wire. The ohm
and volt should be the same multiple of the c.g.s. units, both 109 for
example. Then use the millivolt or centivolt when speaking of the
E.M.F. of cells. The present 1-12 volt would be 112 millivolts. Speak-
ing from memory, Sir W. Thomson did object to the 10s volt at the
Paris Congress.
Mac, torn, bob, and dick are all good names for units. Tom and mac
(plural, max), have sentimental reasons for adoption ; bob and dick may
also at some future time. I have used torn myself (no offence, I hope)
for six years past to denote 109 c.g.s. units of self or mutual electro-
magnetic induction coefficient. (Some reform is wanted here. Co-
efficient of self-induction, or of electromagnetic capacity, is too lengthy.)
The advantage is that L toms divided by K ohms gives L/E, seconds of
time. But it is too big a unit for little coils ; then use the millitom :
or even the microtom for very small coils. This applies to fine-wire
coils. The c.g.s. unit itself would be most suitable for coils of a few
NOTES ON NOMENCLATURE. 27
turns of thick wire. If it is called the torn, then the kilotom or mega-
tom will come in useful for fine-wire coils.
A name should certainly be given to a unit of this quantity, whether
it be torn, or mac, or any other practical name. Also, names to a unit
of magnetic force (intensity of), and of magnetic induction.
There is also the question of the names, not of the units, but of the
physical magnitudes of which they are the units, but it is too large a
question to discuss here except in the most superficial manner. It is
engrained in the British nature to abbreviate, to make one word do for
two or three, or a short for a long word. And quite right too. We
have much to be thankful for ; in the application of this general remark,
consider what frightful names might have been given to the electrical
units by the Germans. But, on account of this national, and also
rational tendency to cut and clip, it is in the highest degree desirable
that as many as possible of the most important physical magnitudes
should be known, not by a long string of words, but by a single word,
or the smallest number possible.
Thus, I find myself frequently saying force, when I mean magnetic
force, and even then, I mean the intensity of magnetic force. The
context will generally make the meaning plain. But it is necessary to
be very careful when there are more forces than one in question.
(This use of force as an abbreviation is, of course, quite distinct from
the frequent positive misuse of the word force, to indicate it may be
momentum, or energy, or activity, or, very often, nothing in particular,
the misuser not being able to say exactly what he means ; nor does it
much matter.) It would be decidedly better if such a quantity as
"intensity of magnetic force" had a one-word name, for people will
abbreviate, and sometimes confusion may step in. This remark applies
to most of the electromagnetic magnitudes.
There is an important magnitude termed the magnetic induction. I
call it often simply "the induction"; but in doing so, carefully avoid
calling any other quantity " the induction " (sometimes the electric dis-
placement is called the electric induction). But there is an unfortunate
thing here, which somewhat militates against "the induction," or even
" the magnetic induction " being a thoroughly good name for the mag-
nitude in question. This is, that besides being a name of a physical
magnitude, the word induction has a widespread use, in a rather vague
manner, in connection with transient states in general, whether of the
electric or of the magnetic field, exemplified, to take an extreme
example, when a man explains something complex by saying it is
caused by "induction," and so settling the matter. If this vague
qualitative use of induction were got rid of, then as a name for a
physical magnitude it would be unobjectionable. As it is, it is a
question whether the physical magnitude should not have a name for
itself alone.
" Resistivity" for specific resistance, and "conductance" for what is
sometimes called the conductibility of a wire, i.e., not its conductivity
(specific conductance), but the reciprocal of its resistance, are, I think,
as I have remarked before, quite practical names.
28 ELECTRICAL PAPERS.
NOTE 3. THE INDUCTANCE OF A CIRCUIT.
IN my first note, amongst other things, I remarked that whilst the
conduction-current terminology admitted of the words resistivity and
conductance being coined to make it more complete, the terminology in
the allied cases of magnetic induction and electric displacement was
unsatisfactory.
As regards the former, the following appears to me to be practical.
First, abolish the word permeability, and substitute Inductivity. We
then have B = pH, when B is the Induction, and /x the Inductivity,
showing how the Induction is related to the magnetic force H by the
specific quality of the medium at the place, its inductivity.
Now conductivity and conductance are mathematically related in the
same manner (except as regards a 4?r) as inductivity and what it is
naturally suggested to call Inductance.
The Inductance of a circuit is what is now called its coefficient of
self-induction, or of electromagnetic capacity.
Thus the quantities induction, inductivity, and inductance are happily
connected in a manner which is at once concise and does justice to their
real relationship. When the mutual coefficient of induction of two
circuits is to be referred to, it will of course be the mutual inductance.
XXXIII. NOTES ON THE SELF-INDUCTION OF WIRES.
[The Electrician, 1886 ; Note 1, April 23, p. 471 ; Note 2, May 7, p. 510.]
NOTE 1. We read in the pages of history of a monarch who was
" supra grammaticam." All truly great men are like that monarch.
They have their own grammars, syntaxes, and dictionaries. They
cannot be judged by ordinary standards, but require interpretation.
Fortunately the liberty of private interpretation is conserved.
No man has a more peculiar grammar than Prof. Hughes. Hence, he
is liable, in a most unusual degree, to be misunderstood, as I venture to
think he has been by many, including Mr. W. Smith, whose interesting
letter appears in The Electrician, April 16, 1886, p. 455, and Prof. H.
Weber, p. 451.
The very first step to the understanding of a writer is to find out what
he means. Before that is done there cannot possibly be a clear com-
prehension of his utterances. One may, by taking his language in its
ordinary significance, hastily conclude that he has either revolutionised
the science of induction, or that he is talking nonsense. But to do this
would not be fair. We must not judge by what a man says if we have
good reason to know that what he means is quite different. To be quite
fair, we must conscientiously endeavour to translate his language and
ideas into those we are ourselves accustomed to use. Then, and then
only, shall we see what is to be seen.
When Prof. Hughes speaks of the resistance of a wire, he does not
NOTES ON THE SELF-INDUCTION OF WIRES. 29
always mean what common men, men of ohms, volts, and farads, mean
by the resistance of a wire — only sometimes. He does not exactly
define what it is to be when the accepted meaning is departed from.
But by a study of the context we may arrive at some notion of its new
meaning. It is not a definite quantity, and must be varied to suit
circumstances. Again, there is his " inductive capacity " of a wire.
We can only find roughly what that means by putting together this,
that, and the other. It, too, is not a definite quantity, but must be
varied to suit circumstances. It is not the coefficient of self-induction,
nor is it any quantity defining a specific quality of the wire, like
conductivity, or inductivity. It is a complex quantity, depending on a
great many things, but which may, to a first rough approximation, be
taken to be proportional to the time-constant of the wire, the quotient
of its coefficient of self-induction by its resistance. Bearing these two
things in mind, we shall be able to approximate to Prof. Hughes's
meaning.
Owing to the mention of discoveries, apparently of the most revolu-
tionary kind, I took great pains in translating Prof. Hughes's language
into my own, trying to imagine that I had made the same experiments
in the same manner (which could not have happened), and then asking
what are their interpretations ? The discoveries I looked for vanished
for the most part into thin air. They became well known facts when
put into common language. The satisfaction of getting verifications,
however, even in so roundabout and rough a manner, is some compen-
sation for the disappointment felt. I venture to think that Prof.
Hughes does not do himself justice in thus deceiving us, however
unwittingly, and that possibly there has been also some misapprehension
on his part as to what the laws of self-induction are generally supposed
to be.
I have failed to find any departure from the known laws of electro-
magnetism. In saying this, however, I should make a reservational
remark. There may be lying latent in Prof. Hughes's results dozens of
discoveries, but it is impossible to get at them. For consider what the
mere existence of ohms, volts, and farads means ? It means that, even
before they were made, the laws of induction in linear circuits were
known, and very precisely. To get, then, at new discoveries requires
very accurate comparison of experiment with theory, by methods which
enable us to see what we are doing and measuring, in terms of the
known electromagnetic quantities. This is practically impossible, on
the basis of Prof. Hughes's papers. We can only make very rough
verifications. I have had myself, for many years past, occasional
experience with induction balances of an exact nature — true balances
of resistance and induction — and always found them work properly.
But, in the modification made by Prof. Hughes, the balance is generally
of a mixed nature, neither a true resistance nor a true induction balance,
and has to be set right by a foreign impressed force, viz., induction
between the battery and telephone branches. By using a strictly
simple harmonic E.M.F., as of a rotating coil, we may exactly formulate
the conditions of the false balance, and then, noting all the resistances,
30 ELECTRICAL PAPERS.
etc., concerned, derive, though in a complex manner, exact information.
Or, if we use true balances, any kind of E.M.F. will answer.
To illustrate the falsity of Prof. Hughes's balances and the difficulty
of getting at exact information, he finds the comparative force of the
extra-currents in two similar coils in series to be 1'74 times that of a
single coil. From the context it would appear that this " comparative
force of the extra-currents " is the same thing as the former " inductive
capacity " of wires. Now, the coefficient of self-induction of two similar
coils in series, not too near one another, is double that of either, whilst
the time-constant of the two is the same as of either. This can be
easily verified by true balances.
The most interesting of the experiments are those relating to the
effect of increased diameter on what Prof. Hughes terms the "inductive
capacity " of wires. My own interpretation is roughly this. That the
time-constant of a wire first increases with the diameter, and then later
decreases rapidly ; and that the decrease sets in the sooner the higher
the conductivity and the higher the inductivity (or magnetic perme-
ability) of the wires. If this be correct, it is exactly what I should have
expected and predicted. In fact, I have already described the pheno-
menon substantially in The Electrician ; or, rather, the phenomenon I
described contains in itself the above interpretation. In The Electrician
for January 10, 1885, I described how the current starts in a wire. It
begins on its boundary and is propagated inward. Thus, during the
rise of the current it is less strong at the centre than at the boundary.
As regards the manner of inward propagation, it takes place according
to the same laws as the propagation of magnetic force and current into
cores from an enveloping coil, which I have described in considerable
detail in The Electrician [Reprint, vol. 1, Art. 28. See especially § 20].
The retardation depends on the conductivity, on the inductivity, and on
the section, under similar boundary conditions. If the conductivity be
high enough, or the inductivity or the section be large enough, to make
the central current appreciably less than the boundary current during
the greater part of the time of rise of the current, there will be an
apparent reduction in the time-constant. Go to an extreme case. Very
rapid short currents, and large retardation to inward transmission.
Here we have the current in layers, strong on the boundary, weak in
the middle. Clearly, then, if we wish to regard the wire as a mere
linear circuit, which it is not, and as we can only do to a first approxi-
mation, we should remove the central part of the wire — that is, increase
its resistance, regarded as a line, or reduce its time-constant. This will
happen the sooner the greater the inductivity and the conductivity, as
the section is continuously increased. It is only thin wires that can be
treated as mere lines, and even they, if the speed be only great enough,
must be treated as solid conductors. I ought also to mention that the
influence of external conductors, as of the return conductor, is of
importance, sometimes of very great importance, in modifying the
distribution of current in the transient state. I have had for years in
MS. some solutions relating to round wires, and hope to publish them
soon.
NOTES ON THE SELF-INDUCTION OF WIRES. 31
As a general assistance to those who go by old methods — a rising
current inducing an opposite current in itself and in parallel conductors
— this may be useful. Parallel currents are said to attract or repel,
according as the currents are together or opposed. This is, however,
mechanical force on the conductors. The distribution of current is not
affected by it. But when currents are increasing or decreasing, there is
an apparent attraction or repulsion between them. Oppositely going
currents repel when they are decreasing, and attract when they are
increasing. Thus, send a current into a loop, one wire the return to
the other, both being close together. During the rise of the current it
will be denser on the sides of the wires nearest one another than on the
remote sides. It is an apparent force, not between currents (on the
distance-action and real motion of electricity views), but between their
accelerations.
NOTE 2. I did not expect to return to the subject, and do so because
Prof. Hughes has apparently misunderstood my statements. On p. 495
of The Electrician for April 30, 1886, he says : — "Mr. Oliver Heaviside
points out that upon a close examination it will be found that all the
effects which I have described are well known to mathematicians, and
consequently old." A regard for accuracy compels me to point out that
I did not make the statement he credits me with ; nor, to avoid any
hypercriticism, is the above a correct summary of the many things that
I pointed out.
I said, "The discoveries I looked for vanished, for the most part,
into thin air. They became well-known facts when put into common
language." Observe here my "for the most part" as against Prof.
Hughes's " all " ; and that I said not a word about mathematicians in
the whole letter. An immediate consequence of my statement is
another, namely, that some, although a minority, of the results were
not well known. There is a material difference between what I said
and what Prof. Hughes makes me say. In another place I said that I
had "failed to find any departure from the known laws of electro-
magnetism," and then proceeded to give my reasons for it. This
statement includes the well-known facts as well as those which are not
well known.
It may be as well that I should illustrate the difference between well-
known facts and those that are less known, or only known theoretically.
The influence of the form of a thin wire (a linear conductor), and of its
length, diameter, conductivity, and inductivity on the phenomena of
self-induction is well known. The various relations involved form the
A B C of the subject. So are the effects of concentration of the current,
and of dividing it, or spreading it out in strips, well known. There is
another influence that is well known, that is scarcely touched upon by
Prof. Hughes. The self-induction depends upon the distribution of
inductivity, that is, in another form, of inductively magnetisable matter,
outside the current, as well as in it, in a manner which is quite definite
when the magnetic properties of the matter are known.
It is not to be inferred that verifications of well-known facts are of no
32 ELECTRICAL PAPERS.
value — that depends upon circumstances. To be of any use, we must
know what we are measuring and verifying. The theory of self and
mutual induction in linear circuits is almost a branch of pure mathe-
matics, so simply are the quantities related, and so exactly. It furnishes
a most remarkable example of the dependence of complex phenomena
on a very small number of independent variables, by ignoring minute
dielectric phenomena. In getting verifications, then, it is first necessary
to employ a correct method. I have elsewhere [The Electrician, April 30,
1886, p. 489; the next Art. 33] shown the approximate character of Prof.
Hughes's method of balancing, and pointed out exact methods. Next,
it is necessary to put results in terms of the quantities in the electro-
magnetic theory which is founded upon the well-known facts; how
else can we know what we are doing, and see how near our verifica-
tions go?
Coming now to results that are not well known, there is the thick-
wire effect, depending on size, conductivity, inductivity, place of return
current, etc. This is, in my opinion, the really important part of Prof.
Hughes's researches, as it, in some respects, goes beyond what was
already experimentally known. Having been, so far as I know, the
first to correctly describe (The Electrician, Jan. 10, 1885, p. 180)
[Reprint, vol. I. pp. 439, 440] the way the current rises in a wire, viz.,
by diffusion from its boundary, and the consequent approximation,
under certain circumstances, to mere surface conduction ; and believing
Prof. Hughes's researches to furnish experimental verifications of my
views, it will be readily understood that I am specially interested in
this effect ; and I can (in anticipation) return thanks to Prof. Hughes
for accurate measures of the same, expressed in an intelligible form, to
render a comparison with theory possible if it be practicable. I send
with this a first instalment of my old core investigations applied to a
round wire with the current longitudinal. [Section 26 of "Electro-
magnetic Induction," later.]
There are also intermediate matters where one can hardly be said to
be either making verifications, except roughly, or discoveries; for
instance, the self-induction of an iron-wire coil. Theory indicates in
the plainest manner that the self-induction coefficient will be a much
smaller multiple of that of a similar copper-wire coil than if the wires
were straightened. Magnetic circuits are now getting quite popularly
understood, by reason of the commercial importance of the dynamo.
But there is really no practical way of carrying out the theory com-
pletely, as the mathematical difficulties are so great. Hence, actual
measurements of the precise amounts in various cases of magnetic
circuits are of value, if they be accompanied by the data necessary for
comparisons.
There is, however, this little difficulty in the way when transient
currents are employed. Iron, by reason of its high iuductivity, is pre-
eminently suited for showing the thick-wire effect. We may not,
therefore, be always measuring what we want, but something else.
USE OF THE BRIDGE AS AN INDUCTION BALANCE.
33
XXXIV. ON THE USE OF THE BRIDGE AS AN INDUCTION
BALANCE.
[The Electrician, April 30, 1886, p. 489.]
IN connection with a paper "On Electromagnets, etc.," that I wrote
about six years ago [Reprint, Art. xvii., vol. 1, p. 95], which paper
dealt mainly with the question of the influence of the electromagnetic
induction of the lines and instruments on the magnitude of the signalling
currents, an influence which is of the greatest importance on short lines,
and which (of the instruments) is, even on long lines, where electro-
static induction is prominent, of importance as a retarding factor, I
made a great many experiments on self-induction, amongst which were
measurements of the inductances of various telegraph instruments, with
a view to ascertaining their practical values, and also the multiplying
powers of the iron cores. It was my intention to write a supplementary
paper giving the results and also further investigations; but, having
got involved, in the course of the experiments, in the difficult subject
of magnetic inductivity, it was postponed, and then dropped out of
mind.
I used, first of all, the Bridge and condenser method described by
Maxwell, with reversals, and a telephone for current indicator. This
was to get results at once, or by simple calculations, in electromagnetic
units. Next, I discarded the condenser, and used the simple Bridge,
balancing coils against standard coils. Thirdly, I have used a differ-
ential telephone with the same object, in a similar manner. The two
last are very sensitive methods, and the verifications of the theory of
induction in linear conductors that I have made by them are numerous.
The whole of this journal would be required to give anything like a
full investigation of the various ways of using the Bridge as an induction
balance. I can, therefore, only touch lightly on the subject of exact
balances, especially as I have to remark upon faulty methods, approxi-
mate balances, and absolutely false balances. Prof. Hughes's balance
is sometimes fairly approximate, sometimes quite false.
Put a telephone in the branch 5, battery and
interrupter in 6. Then, r standing for resistance,
I for inductance (coefficient of self-induction),
and x for l/r, the time-constant of a branch,
the conditions of a true and perfect balance,
however the impressed force in 6 vary, are three
in number, namely,
Their interpretations are as follows : — If the first condition is fulfilled
there will be no final current in 5 when a steady impressed force is put
in 6. This is the condition for a true resistance balance.
H.E.P. — VOL. IT. c
34 ELECTRICAL PAPERS.
If, in addition to this, the second condition be also satisfied, the
integral extra-current in 5 on making or breaking 6 is zero, besides the
steady current being zero. (1) and (2) together therefore give an
approximate induction balance with a true resistance balance.
If, in addition to (1) and (2), the third condition is satisfied, the
extra-current is zero at every moment during the transient state, and
the balance is exact, however the impressed force in 6 vary.
Practically, take
r1 = r& and J1==/2, (4)
that is, let branches 1 and 2 be of equal resistance and inductance.
Then the second and third conditions become identical; and, to get
perfect balances, we need only make
r3 = r4, and Z8 = Z4 (5)
This is the method I have generally used, reducing the three con-
ditions to two, whilst preserving exactness. It is also the simplest
method. The mutual induction, if smy, of 1 and 2, or of 3 and 4, does
not influence the balance when this ratio of equality, i\ = r2, is employed
(whether /x = /2 or not). So branches 1 and 2 may consist of two
similar wires wound together on the same bobbin to keep their temper-
atures equal.
The sensitiveness of the telephone has been greatly exaggerated.
Altogether apart from the question of referring the sensitiveness to the
human ear rather than to the telephone, it is certainly, under ordinary
circumstances, often unable to appreciate the differences of the second
order, which vanish when the third condition is satisfied. Thus (1)
and (2) satisfied, but with (3) unsatisfied, will give silence. Take, for
instance, rl=r% and r3 = r# but ^ different from /2 and /3 from /4, then
silence is given by
ft-y/r.-ft-y/r.j (6)
that is, by making the differences of the inductances on the two sides
of 5 proportional to the resistances. We can therefore get silence by
varying the inductance of any one or more of the four branches 1, 2, 3,
4, to suit equation (6). It is certain that we do get silence this way,
but it does not follow that silence is given by exactly satisfying (6), (and
(1) of course), because it is only a balance of integral extra-currents,
and other balances of this kind are certainly quite false sometimes.
To avoid any doubt, it is of course best to keep to the legitimate and
simpler previously-described method.
There are some other ways of using the Bridge as an induction
balance in an exact manner, but they are less practically useful than
theoretically interesting. Pass, therefore, to other approximate, and to
false balances. Suppose we start with a true balance, and then upset
it by increasing the inductance of the branch 4. It is clear that we
should never alter the already truly established resistance balance.
Now, besides by the exact ways, we can get approximate silence by
allowing mutual induction between 5 and any of the other five branches,
or between 6 and any of the other five branches, that is nine ways, not
USE OF THE BRIDGE AS AN INDUCTION BALANCE. 35
counting combinations. (Put test coils in 5 and 6 with long leading
wires, so that they may be carried about from one branch to another.)
These approximate balances are all of the integral extra-current only,
and therefore imperfect, however nearly there may be silence. But the
silences are of very different values.
I find, using h'ne-wire coils, that mutual induction between 6 and 4
or between 6 and 3 gives silence (to my ear) with the true resistance
balance, just like the approximate balance of equation (6) in which no
mutual induction is allowed.
These are only two out of the nine ways. All the rest are bad. If
the difference in the inductance of 3 and 4 be small, there is very
nearly silence on using any of the other seven ways; but, the larger
this difference is made, the louder becomes the " silence," and sometimes
it is even a very loud noise, quite comparable with the original sound
that was to be destroyed, even when the combinations 6 and 4 or 6 and
3, and the formerly-mentioned method give a silence that can be felt,
with the true resistance balance.
It is certainly a rather remarkable thing that the one method out of
these seven faulty ways which gave the very loudest sound was the 5
and 6 combination, which is Professor Hughes's method. I do not say
that it is always the worst, although it was markedly so in my experi-
ments to test the trustworthiness of the method. And sometimes it is
quite fair. In fact, when the sound to be destroyed is itself weak, all
the seven faulty methods are apparently alike, nearly true. But when
we exaggerate the inequality of inductance between 3 and 4, whilst the
6 to 4 and 6 to 3 combinations keep good, the others get rapidly worse,
and differences appear between them.
I found that by increasing the resistance of the branch whose
inductance was the smaller, the sound was diminished greatly, i.e., in
the seven faulty methods. The coil of greater inductance had apparently
the higher resistance. That is, with a false resistance balance we may
approximate to silence. Such a balance is condemned for scientific
purposes.
Although mutual induction between 6 and 4 or 6 and 3 gave silence,
with true resistance balances, the experiments were not sufficiently
extended to prove their general trustworthiness. There is, however,
some reason to be given for their superiority. For, since the dis-
turbance in the telephone arises from the inequality of the momenta of
the currents in the branches 3 and 4, and of the electric impulses
arising in them when contact is broken in branch 6 (considering the
break only for simplicity), we go nearest to the root of the evil by
generating an additional impulse in 3 or 4 themselves from the battery
branch, of the right amount.
The following is an outline of the theory of these approximate
balances. Let r^r^ = r2r3 first ; so that, C standing for current, we have,
in the steady state,
...... (7)
The momentum of the current in branch 1 is If^ that in 2 is 12C2, and
36 ELECTRICAL PAPERS.
so on. Consider the break, and the integral extra-current that then
arises from /1(71. It is
1& -f {^ + r2 + r6(rs + r4)/(rs + r4 + r5) }, -
and (r3 + r4)/(rs + r4 + r5) is the fraction of this that goes through 5 ; so
that the integral current in 5 due to ^Cj is
hGi(r* + r*) * { (ri + ?<2)('r3 + ?>4) + ?'o(?'i + ?2 + rs + r4> } >
or (7^ - {r3 + r4 + r5 + ^r^},
by making use of equations (1) and (7).
Treat the others similarly. The total extra-current in 5 is
r&fa + x± -x2- x3) 4- {r3 + r4 + r5 + r3r.jrj, ............ (8)
without any mutual induction. So
*C| ~F WA == ^/O "l **^Q
gives approximate balance. This was mentioned before, and becomes
an exact balance with makes and breaks when a ratio of equality is
taken.
Now let there be mutual induction between 6 and 4, 5 and 4, and 5
and 6, the mutual inductances being Af64, etc. Treating these similarly
to before, we shall find the total extra-current in 5 on the break taking
place to be
fato + z4 - x2 - xs) + JlfM(l + rjr3] + MM(l + rjrj
+ M56(l+rB/lrl)(l+rJr2}}C\^(rs + r^ + r5 + r3rJrl) .......... (9)
The theory of the make leads to the same result — that is, as regards
the integral extra-current. Otherwise they are different. So, using
M56 (Hughes's method) the zero integral current is when
r4(x1 + x4-x2-x3) + M,6(l+r3lr1)(l+rJr3) = 0 .......... (10)
Using Jf45 we have
Using M6i we have
}+rJr3) = Q ................ (12)
Practically employ a ratio of equality r^ = r^ ^i = ^> '
branches 1 and 2 equal fixtures. Then these three equations become
= 0, .................... (10a)
^4-^3+ JfwO+ra/r^O, .................... (lla)
1,-1B + 2M,6 = 0 ..................... (12a)
Thus the M46 system has the simplest formula, as well as being
practically perfect. It is the same with M6y Either of these must
equal half the difference of the inductances of 3 and 4.
As (10a), or, more generally, (10) contains resistances, we cannot get
any definite results from Prof. Hughes's numbers without a knowledge
of the resistances concerned. Note, also, that (10) and (11) are faulty
balances ; to improve them, destroy the resistance balance ; of course
then the formula will change, and is likely to .become very complex.
It will be understood that when I speak of false resistance balances
in this paper I do not in any way refer to the thick-wire phenomenon,
USE OF THE BRIDGE AS AN INDUCTION BALANCE. 37
mentioned in my letter [p. 30], which, from its very nature, requires
the resistance balance to be upset, or be different from what it would
be if the wire were thin, but of the same real [i.e., steady] resistance.
The resistance balance must be upset in a perfect arrangement. Nor
can there be a true balance got, but only an approximate one, unless
a similar thick wire be employed to produce balance.
What I refer to here is the upsetting of the true resistance balance
when there is no perceptible departure whatever from the linear theory.
The two effects may be mixed.
To use the Bridge to speedily and accurately measure the inductance
of "a coil, we should have a set of proper standard coils, of known
inductance and resistance, together with a coil of variable inductance,
i.e., two coils in sequence, one of which can be turned round, so as to
vary the inductance from a minimum to a maximum. (The scale of
this variable coil could be calibrated by (12a), first taking care that the
resistance balance did not require to be upset.) This set of coils, in or
out of circuit according to plugs, to form say branch 3, the coil to be
measured to be in branch 4. Ratio of equality. Branches 1 and 2
equal. Of course inductionless, or practically inductionless resistances
are also required, to get and keep the resistance balance.
The only step to this I have made (this was some years ago) in my
experiments, was to have a number of little equal unit coils, and two or
three multiples ; and get exact balance by allowing induction between
two little ones, with no exact measurement of the fraction of a unit.
So long as we keep to coils we can swamp all the irregularities due
to leading wires, etc., or easily neutralise them, and therefore easily
obtain considerable accuracy. With short wires, however, it is a
different matter. The inductance of a circuit is a definite quantity.
So is the mutual inductance of two circuits. Also, when coils are
connected together, each forms so nearly a closed circuit that it can be
taken as such, so that we can add and subtract inductances, and localise
them definitely as "belonging to this or that part of a circuit. But this
simplicity is, to a great extent, lost when we deal with short wires,
unless they are bent round so as to make nearly closed circuits. We
cannot fix the inductance of a straight wire, taken by itself. It has no
meaning, strictly speaking. The return current has to be considered.
Balances can always be got, but as regards the interpretation, that will
depend upon the configuration of the apparatus. [See Section xxxviii.
of " Electromagnetic Induction," later.]
Speaking with diffidence, having little experience with short wires, I
should recommend 1 and 2 to be two equal wires, of any convenient
length, twisted together, joined at one end, of course slightly separated
at the other, where they join the telephone wires, also twisted. The
exact arrangement of 3 and 4 will depend on circumstances. But
always use a long wire rather than a short one (experimental wire).
If this is in branch 4, let branch 3 consist of the standard coils (of
appropriate size), and adjust them, inserting if necessary, coils in series
with 4 also. Of course I regard the matter from the point of view of
getting easily interpretable results.
38 ELECTRICAL PAPERS.
The exact balance (1), (2), (3) above is quite special. If the branches
1 and 3 consist of any combination of conductors and condensers, with
induction in masses of metal allowed, and branches 2 and 4 consist of
an exactly equal combination, in every respect, there will never be any
current in 5 due to impressed force in 6. And, more generally, 2 + 4
may be only a copy of 1 + 3, on a reduced scale, so to speak.
P.S.— (April 27, 1886.) The great exactness with which, when a
ratio of equality is used, the 1T64 and M6S methods conform to the true
resistance balance, as above mentioned, together with the almost per-
sistent departure of the M65 (Hughes's) method from the true resistance
balance, led me to suspect that, as in the use of the simple Bridge
method, with no mutual induction, the three conditions of a true balance
are reduced to two by a ratio of equality, the same thing happens in
the M64: and M6B methods, but not in the M65. This I have verified.
In Hughes's system the three conditions are
............................... (13)
/1+/2+/3+y=o ............... ....(15)
Now take 1-^ = 1^ rl = r2> r3 = ?4; then the second and third are
equivalent to
/4 - 13 + 2M56(l + r3/rj = 0, 2^/33 = 1 + ljly
The second of these is a special relation that must hold before the first
is true. Hence the sound with a true resistance balance, and the
necessity of a false balance to get rid of it.
But in the M method the conditions are
= 0, ............... (17)
(18)
Take Zx = 12, i\ = r2, i 3 = r4, as before, and now the second and third
conditions become identical, viz.,
agreeing with the previously obtained equation
Thus, whilst Hughes's method is inaccurate, sometimes greatly so,
we may employ the M64 and M63 methods without any hesitation, pro-
vided a ratio of equality be kept to. They will be as accurate as the
simple Bridge method, and the choice of the methods will be purely a
matter of convenience.
I have verified experimentally that the Hughes system requires a
false resistance balance when, instead of coils, short wires are used, the
branch of greater inductance having apparently the greater resistance.
I have also verified that this effect is mixed with the thick-wire effect,
which last is completely isolated by using the proper MM method or
the simple Bridge. Its magnitude can now be exactly measured, free
from the errors of a faulty method. That is, it can be estimated for
any particular speed of intermittences or reversals, for it is not a
constant effect. Balance a very thin against a very thick wire, so that
the effect occurs only on me side.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 39
XXXV. ELECTROMAGNETIC INDUCTION AND ITS
PROPAGATION. (SECOND HALF.)
[The Electrician, 1886-7. Section XXV., April 23, 1886, p. 469 ; XXVI., May
14, p. 8 (vol. 17) ; XXVII., June 11, p. 88; XXVIJL, June 25, p. 128; XXIX.,
July 23, p. 212; XXX., August 6, p. 252 ; XXXI., August 20, p. 296; XXXII.,
August 27, p. 316; XXXIII., November 12, p. 10 (vol. 18) ; XXXIV., December
24, 1886, p. 143; XXXV., January 14, 1887, p. 211; XXXVL, February 4,
p. 281 ; XXXVIL, March 11, p. 390; XXXVIIL, April 1, p. 457; XXXIXa.,
May 13, p. 5 (vol. 19); XXX1X6., May 27, p. 50; XL., June 3, p. 79; XLL,
June 17, p. 124 ; XLII., July 1, p. 163 ; XLIIL, July 15, p. 206 ; XLIV., August
12, p. 295; XLV., August 26, p. 340; XLVL, October 7, p. 459; XLVII.,
December 30, 1887, p. 189 (vol. 20).]
SECTION XXV. SOME NOTES ON MAGNETISATION.
ALTHOUGH it is generally believed that magnetism is molecular, yet
it is well to bear in mind that all our knowledge of magnetism is
derived from experiments on masses, not on single molecules, or
molecular structures. We may break up a magnet into the smallest
pieces, and find that they, too. are little magnets. Still, they are
not molecular magnets, but magnets of the same nature as the
original ; solid bodies showing magnetic properties, or intrinsic-
ally magnetised. We are nearly as far away as ever from a mole-
cular magnet. To conclude that molecules are magnets because
dividing a magnet always produces fresh magnets, would clearly be
unsound reasoning. For it involves the assumption that a molecule
has the same magnetic property as a mass, i.e., a large collection of
molecules, having, by reason of their connection, properties not
possessed by the molecules separately. (Of course, I do not define
a molecule to be the smallest part of a substance that has all the
properties of the mass.) If we got down to a mass of iron so small
that it contained few molecules, and therefore certainly not possess-
ing all the properties of a larger mass, what security have we that
its magnetic property would not have begun to disappear, and that
their complete separation would not leave us without any magnetic
field at all surrounding them of the kind we attribute to intrinsic
magnetisation. That there would be magnetic disturbances round
an isolated molecule in motion through a medium, and with its parts
in relative motion, it is difficult not to believe in view of the partial
co-ordination of radiation and electromagnetism made by Maxwell.
But it might be quite different from the magnetic field of a so-called
magnetic molecule — that is, the field of any small magnet. This
evident magnetisation might be essentially conditioned by structure,
not of single molecules, but of a collection, together with relative
motions connected with the structure, this structure and relative
motions conditioning that peculiar state of the medium in which
they are immersed, which, when existent, implies intrinsic magnet-
isation of the collection of molecules, or the little mass. However
this be, two things are deserving of constant remembrance. First,
that the molecular theory of magnetism is a speculation which it is
40 ELECTRICAL PAPERS.
desirable to keep well separated from theoretical embodiments of
known facts, apart from hypothesis. And next, that as the act of
exposing a solid to magnetising influence is, it is scarcely to be
doubted, always accompanied by a changed structure, we should
take into account and endeavour to utilise in theoretical reasoning
on magnetism which is meant to contain the least amount of
hypothesis, the elastic properties of the body, speaking generally,
and without knowing the exact connection between them and the
magnetic property.
Hooke's law, Ut tensio, sic vis, or strain is proportional to stress,
implies perfect elasticity, and is the first approximate law on which
to found the theory of elasticity. But beyond that, we have im-
perfect elasticity, elastic fatigue, imperfect restitution, permanent
set.
When we expose an unmagnetised body to the action of a
magnetic field of unit inductivity, it either draws in the lines of
induction, in which case it is a paramagnetic, is positively magnetised
inductively, and its inductivity is greater than unity ; or it wards oft'
induction, in which case it is a diamagnetic, is negatively magnetised
inductively, and its inductivity is less than unity; or, lastly, it may
not alter the field at all, when it is not magnetised, and its induc-
tivity is unity.
Regarding, as I do, the force and the induction — not the force and
the induced magnetisation — as the most significant quantities, it is
clear that the language in which we describe these effects is some-
what imperfect, and decidedly misleading in so prominently directing
attention to the induced magnetisation, especially in the case of no
induced magnetisation, when the body is still subject to the magnetic
influence, and is as much the seat of magnetic stress and energy as
the surrounding medium. We may, by coining a new word pro-
visionally, put the matter thus. All bodies known, as well as the
so-called vacuum, can be inductized. According to whether the
inductization (which is the same as "the induction," in fact) is
greater or less than in vacuum (the universal magnetic medium) for
the same magnetic force (the other factor of the magnetic energy
product), we have positive or negative induced magnetisation.
To the universal medium, which is the primary seat of the
magnetic energy, we attribute properties implying the absence of
dissipation • of energy, or, on the elastic solid theory, perfect
elasticity. (Dissipation in space is scarcely within a measurable
distance of measurement.) But that the ether, resembling an elastic
solid in some of its properties, is one, is not material here. Induc-
tization in it is of the elastic or quasi-elastic character, and there can
be no intrinsic magnetisation. Nor evidently can there be intrinsic
magnetisation in gases, by reason of their mobility, nor in liquids,
except of the most transient description. But when we come to
solids the case is different.
If we admit that the act of inductization produces a structural
change in a body (this includes the case of no induced magnetisation),
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 41
and if, on removal of the inducing force, the structural change
disappears, the body behaves like ether, so far, or has no inductive
retentiveness. Here we see the advantage of speaking of inductive
rather than of magnetic retentiveness. But if, by reason of im-
perfect elasticity, a portion of the changed structure remains, the
body has inductive retentiveness, and has become an intrinsic
magnet. As for the precise nature of the magnetic structure, that is
an independent question. If we can do without assuming any
particular structure, as for instance, the Weber structure, which is
nothing more than an alignment of the axes of molecules, a structure
which I believe to be, if true at all, only a part of the magnetic
structure, so much the better. It is the danger of a too special
hypothesis, that as, from its definiteness, we can follow up its
consequences, if the latter are partially verified experimentally we
seem to prove its truth (as if there could be no other explanation),
and so rest on the solid ground of nature. The next thing is to
predict unobserved or unobservable phenomena whose only reason
may be the hypothesis itself, one out of many which, within limits,
could explain the same phenomena, though, beyond those limits, of
widely diverging natures.
The retentiveness may be of the most unstable nature, as in soft
iron, a knock being sufficient to greatly upset the intrinsic magnetisa-
tion existing on first removing the magnetising force, and completely
alter its distribution in the iron ; or of a more or less permanent
character, as in steel. But, whether the body be para- or dia-
magnetic, or neutral, the residual or intrinsic magnetisation, if there
be any, must be always of the same character as the inducing force.
That is, any solid, if it have retentiveness, is made into a magnet,
magnetised parallel to the inducing force, like iron.
Until lately only the magnetic metals were known to show reten-
tiveness. Though we should theoretically expect retentiveness in
all solids, the extraordinary feebleness of diamagnetic phenomena
might be expected to be sufficient to prevent its observation. But,
first, Dr. Tumlirz has shown that quartz is inductively retentive, and
next, Dr. Lodge (Nature, March 25th, 1886) has published some
results of his experiments on the retentiveness of a great many
other substances, following up an observation of his assistant, Mr.
Davies.
The mathematical statement of the connections between intrinsic
magnetisation and the state of the magnetic field is just the same
whether the magnet be iron or copper, para- or dia-magnetic, or is
icutral. In fact, it would equally serve for a water or a gas magnet,
rere they possible. That is,
divB = 0
being the magnetic force according to the equation B = /xH, where
is the induction and //. the inductivity, F the electric current, if
y, and h. the magnetic force of the intrinsic magnetisation, or the
ipressed magnetic force, as I have usually called it in previous
-i2 ELECTRICAL PAPERS.
sections where it has occurred, because it enters into all equations as
an impressed force, distinct from the force of the field, whose rotation
measures the electric current. It is h and //. that are the two data
concerned in intrinsic magnetisation and its field ; the quantity I,
the intensity of intrinsic magnetisation, only gives the product, viz.,
I = fjih/^TT. It would not be without some advantage to make h and
/A the objects of attention instead of I and /x, as it simplifies ideas as
well as the formulae. The induced magnetisation, an extremely
artificial and rather unnecessary quantity, is (/* - 1) (H - h)/4*r.
It will be understood that this system, when united with the
corresponding electric equations, so as to completely determine
transient states, requires h to be given, whether constant or variable
with the time. The act of transition of elastic induction into
intrinsic magnetisation, when a body is exposed to a strong field,
cannot be traced in any way by our equations. It is not formulated,
and it would naturally be a matter of considerably difficulty to do it.
In a similar manner, we may expect all solid dielectrics to be
capable of being intrinsically electrized by electric force, as described
in a previous section. I do not know, however, whether any dielectric
has been found whose dielectric capacity is less than that of vacuum, or
whether such a body is, in the nature of things, possible.
As everyone knows nowadays, the old-fashioned rigid magnet is a
myth. Only one datum was required, the intensity of magnetisation I,
assuming /x to be unity in as well as outside the magnet. It is a great
pity, regarded from the point of view of mathematical theory, which
is rendered far more difficult, that the inductivity of intrinsic magnets
is not unity. But we must take nature as we find her, and although
Prof. Bottomley has lately experimented on some very unmagnetisable
steel, which may approximate to /*= 1, yet it is perfectly easy to show
that the inductivity of steel magnets in general is not 1, but a large
number, though much less than the inductivity of soft iron, and we
may use a hard steel bar, whether magnetised intrinsically or not, as
the core of an electromagnet with nearly the same effects, as regards
induced magnetisation, except as regards the amount, as if it were
of soft iron.
Regarding the measure of inductivity, especially in soft iron, this is
really not an easy matter, when we pass beyond the feeble forces of
telegraphy. For all practical purposes ^ is a constant when the
magnetic force is small, and Poisson's assumption of a linear relation
between the induced magnetisation and the magnetic force is abundantly
verified. It is almost mathematically true. But go to larger forces,
and suppose for simplicity we have a closed solenoid with a soft iron
core, and we magnetise it. Let F be the magnetic force of the current.
Then, if the induction were completely elastic, we should have the
induction B = /*F. But in reality we have B = />t(F + h) = /xH. If we
assume the former of these equations, that is, take the magnetic force
of the current as the magnetic force, we shall obtain too large an
estimate of the inductivity, in reckoning which H should be taken as
the magnetic force. This may be several times as large as F. For, the
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 43
softer the iron the more imperfect is its inductive elasticity, and the
more easily is intrinsic magnetisation made by large forces ; although
the retentiveness may be of a very infirm nature, yet whilst the force
F is on, there is h on also. This over-estimate of the inductivity may
be partially corrected by separately measuring h after the original
magnetising force has been removed, by then destroying h. But this
h may be considerably less than the former. For one reason, when we
take off F by stopping the coil-current, the molecular agitation of the
heat of the induced currents in the core, although they are in such a
direction as to keep up the induced magnetisation whilst they last,
is sufficient to partially destroy the intrinsic magnetisation, owing to
the infirm retentiveness. We should take off F by small instalments,
or slowly and continuously, if we want h to be left.
Another quantity of some importance is the ratio of the increment in
the elastic induction to the increment in the magnetic force of the
current. This ratio is the same as /x when the magnetic force is small,
but is, of course, quite different when it is large.
As regards another connected matter, the possible existence of
magnetic friction, I have been examining the matter experimentally.
Although the results are not yet quite decisive, yet there does appear
to be something of the kind in steel. That is, during the act of in-
ductively magnetising steel by weak magnetic force, there is a reaction
on the magnetising current very closely resembling that arising from
eddy currents in the steel, but produced under circumstances which
would render the real eddy currents of quite insensible significance.
In soft iron, on the other hand, I have failed to observe the effect. It
has nothing to do with the intrinsic magnetisation, if any, of the steel.
But as no hard and fast line can be drawn between one kind of iron
and another, it is likely, if there be such an effect in steel, where, by the
way, we should naturally most expect to find it, that it would be, in a
smaller degree, also existent in soft iron. Its existence, however, will
not alter the fact materially that the dissipation of energy in iron when
it is being weakly magnetised is to be wholly ascribed to the electric
currents induced in it.
P.S. (April 13, 1886.) — As the last paragraph, owing to the hypothesis
involved in magnetic friction, may be somewhat obscure, I add this in
explanation. The law, long and generally accepted, that the induced
magnetisation is simply proportional to the magnetic force, when small,
is of such importance in the theory of electromagnetism, that I wished
to see whether it was minutely accurate. That is, that the curve of
magnetisation is, at the origin, a straight line inclined at a definite
angle to the axis of abscissae, along which magnetic force is reckoned.
I employed a differential arrangement (differential telephone) admitting
of being made, by proper means, of considerable sensitiveness. The
law is easily verified roughly. When, however, we increase the sensi-
tiveness, its accuracy becomes, at first sight, doubtful ; and besides,
differences appear between iron and steel, differences of kind, not of
mere magnitude. But as the sensitiveness to disturbing influences
44 ELECTRICAL PAPERS.
is also increased, it is necessary to carefully study and eliminate
them. The principal disturbances are due to eddy currents, and to the
variation in the resistance of the experimental coil with temperature.
For instance, as regards the latter, the approach of the hand to the coil
may produce an effect larger than that under examination. The
general result is that the law is very closely true in iron and steel,
it being doubtful whether there is any effect that can be really traced
to a departure from the law, when rapidly intermittent currents are
employed, and that the supposed difference between iron and steel is
unverified.
Of course it will be understood by scientific electricians that it is
necessary, if we are to get results of scientific definiteness, to have
true balances, both of resistance and of induction, and not to employ an
arrangement giving neither one nor the other. He will also understand
that, quite apart from the question of experimental ability, the theorist
sometimes labours under great disadvantages from which the pure
experimentalist is free. For whereas the latter may not be bound by
theoretical requirements, and can employ himself in making discoveries,
and can put down numbers, really standing for complex quantities, as
representing the specific this or that, the former is hampered by his
theoretical restrictions, and is employed, in the best part of his time, in
the poor work of making mere verifications.
SECTION XXVI. THE TRANSIENT STATE IN A ROUND WIRE WITH A
CLOSE-FITTING TUBE FOR THE RETURN CURRENT.
The propagation of magnetic force and of electric current (a function
of the former) in conductors takes place according to the mathematical
laws of diffusion, as of heat by conduction, allowing for the fact of the
electric quantities being vectors. This conclusion may perhaps be
considered very doubtful, as depending upon some hypothesis. Since,
however, it is what we arrive at immediately by the application of the
laws for linear conductors to infinitely small circuits (with a tacit
assumption to be presently mentioned), it seems to me more necessary
for an objector to show that the laws are not those of diffusion, rather
than for me to prove that they are.
We may pass continuously, without any break, from transient states
in linear circuits to those in masses of metal, by multiplying the
number of, whilst diminishing the section of, the " linear " conductors
indefinitely, and packing them closely. Thus we may pass from linear
circuits to a hollow, core ; from ordinary linear differential equations to
a partial differential equation ; from a set of constants, one for each
circuit, to a continuous function, viz., a compound of the J0 function
and its complementary function containing the logarithm. This I have
worked out. Though very interesting mathematically, it would occupy
some space, as it is rather lengthy. I therefore start from the partial
differential equation itself.
Our fundamental equations are, in the form I give to them,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 45
E and H being the electric and magnetic forces, C the conduction
current, k and p. the conductivity and the inductivity. The assumption
I referred to is that the conductor has no dielectric capacity. Bad
conductors have. We are concerned with good conductors, whose
dielectric capacity is quite unknown.
We are concerned with a special application, and therefore choose the
suitable coordinates. All equations referring to this matter will be
marked b. The investigations are almost identical with those given in
my paper on " The Induction of Currents in Cores," in The Electrician
for 1884. [Reprint, vol. I., p. 353, art. XXVIIL] The magnetic force
was then longitudinal, the current circular ; now it is the current that
is longitudinal, and the magnetic force circular.
The distribution of current in a wire in the transient state depends
materially upon the position of the return conductor, when it is near.
The nature of the transient state is also dependent thereon. Now, if
the return conductor be a wire, the distributions in the two wires are
rendered unsymmetrical, and are thereby made difficult of treatment.
We, therefore, distribute the return current equally all round the wire,
by employing a tube, with the wire along its axis. This makes the
distribution symmetrical, and renders a comparatively easy mathematical
analysis possible. At the same time we may take the tube near the
wire or far away, and so investigate the effect of proximity. The
present example is a comparatively elementary one, the tube being
supposed to be close-fitting. As I entered into some detail on the
method of obtaining the solutions in " Induction in Cores," I shall not
enter into much detail now. The application to round wires with the
current longitudinal was made by me in The Electrician for Jan. 10, 1885,
p. 180, so far as a general description of the phenomenon is concerned.
See also my letter of April 23, 1886. [Reprint, vol. I., p. 440; vol. IL,
p. 30.]
Let there be a wire of radius a, surrounded by a tube of outer radius
b, and thickness b — a. In the steady state, if the current-density is F
in the wire, it is - Ta2/(b2 - a2) in the tube, if both be of uniform con-
ductivity, and the tube or sheath be the return conductor of the wire.
Let HI be the intensity of magnetic force in the wire, and H2 in the
tube. The direction of the magnetic force is circular about the axis in
both, and the current is longitudinal. We shall have
H! = 2uTr, H2 = - 2*rIV(^ - b2)/r(b'2 - a2), (2b)
where r is the distance of the point considered from the axis. Test by
the first of equations (15). We have
curl = i ir,
r dr
when applied to H.
Now let this steady current be left to itself, without impressed force
to keep it up, so that the " extra-current " phenomena set in, and the
magnetic field subsides, the circuit being left closed. At the time t
later, if the current-density be 7 at distance r from the axis, it will be
represented by y = Z AJ0(nr)<>* (»)
46 ELECTRICAL PAPERS.
where 2 is the sign of summation. The actual current is the sum of an
infinite series of little current distributions of the type represented, in
which A, n, and p are constants, and JQ(nr) is the Fourier cylinder
function. We have
- ...(45)
r dr dr
Let d/dt=p, a constant, then n is given in terms of p by
ri2 = - ^TTjjikp ............................... (5b)
We suppose that k and /x are the same in the wire as in the sheath.
Differences will be brought in in the subsequent investigation with the
sheath at any distance.
In (3b) there are two sets of constants, the A's fixing the size of the
normal systems, and the ris or p's, since these are connected by (5&).
To find the ris, we ignore dielectric displacement, since it is electro-
magnetic induction that is in question. This gives the condition
#2 = 0, at r = 6; ........................ (66)
i.e., no magnetic force outside the tube. This gives us
(U)
as the determinantal equation of the ris, which are therefore known by
inspection of a Table of values of the J^ function.
Find the A's by the conjugate property. Thus,
A
o
The full solution is, therefore,
2aT
rfV0(»r)rrfr - [YaV^arJnfr/^ - a?)
= Jo __ J. _ = ™L Ji(na)
~
giving the current at time t anywhere.
The equation of the magnetic force is obtained by applying the
second of equations (15) ; it is
„. SiraT JmJnr4*
and the expression for the vector-potential of the current (for its scalar
magnitude A^ that is to say, as its direction, parallel to the current,
does not vary, and need not be considered), is
This may be tested by
/xH; .............................. (126)
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 47
curl being now= -d/dr. In the steady state (initial), £ = 0,
2/
in the wire, and A0 - ^/ - V* + r* + 262 log£\
(136)
in the sheath. Test by (126) applied to (136) to obtain (26).
The magnetic energy being puBP/Qir per unit volume, the amount in
length / of wire and sheath is, by (106),
2 d
n*Jt(nb)
To verify, this should equal the space-integral of ^A0y, using (116)
and (96). This need not be written. They are identical because
[j!(nr) rdr = {*J*(nr)rdr = J6V0>6),
Jo Jo
so that we may write the expression for T thus,
The dissipativity being y2/& per unit volume, the total heat in length
I of wire and sheath is, if p = k~l, the resistivity, and the complete
variable period be included,
Q-PiWIV-W^ff**1 .......... <!»>
When t = Q, either by (146) or by easy direct investigation, the
initial magnetic energy in length I is
giving the inductance of length I as
<""
which may be got in other ways. This refers to the steady state. In
the transient state there cannot be said to be a definite inductance, as
the distribution varies with the time. The expression in (156) for the
total heat may be shown to be equivalent to that in (166) for the initial
magnetic energy, thus verifying the conservation of energy in our
system.
I should remark that it is the same formula (96) that gives us the
current both in the wire and tube, and the same formula (106) that
gives us the magnetic force. They are distributed continuously in the
variable period. It is at the first moment only that they are dis-
continuous, requiring then separate formulae for the wire and tube, i.e.,
separate finite formulae, although only a single infinite series.
The first term of (96) is, of course, the most important, representing
48
ELECTRICAL PAPERS.
the normal system of slowest subsidence. In fact, there is an extremely
rapid subsidence of the higher normal systems ; only three or four need
be considered to obtain almost a complete curve ; and, at a compara-
tively early stage of the subsidence, the first normal system has become
far greater than the rest. In fact, on leaving the current without
impressed force, there is at first a rapid change in the distribution of
the current (and magnetic force), besides a rapid subsidence. It tends
to settle down to be represented by the first normal system ; a certain
nearly fixed distribution, subsiding according to the exponential law of
a linear circuit.
To see the nature of the rapid change, and of the first normal system,
refer to The Electrician of Aug. 23, 1884 [vol. L, p. 387], where is a
representation of the /0 and Jj curves. In Fig. 1, take the distance
OC.2 to be the outer radius of the tube, 0 being on the axis. Then the
curve marked J^ is the curve of the magnetic force, showing its com-
parative strength from the centre of the wire to the outside of the tube,
in the first normal system. And, to correspond, the curve w from 0
up to C2 is the curve of the current, showing its distribution in the first
normal system.
We see that the position of the point J5: with respect to the inner
radius of the sheath determines whether the current is transferred from
the wire to the sheath, or vice versa, in the early part of the subsidence.
If the sheath is very thin, so that the radius of the wire extends nearly
up to (72, there is transfer of the sheath -current (initial) from the sheath
a long way into the wire. On the other hand, if the wire be of small
radius compared with the outer radius of the tube, so that the tube's
depth extends from C2 nearly up to 0, there is a transfer of the original
wire-current a long way into the thick sheath. In Fig. 2 [vol. I., p. 388]
are shown the first four normal systems, all on the same scale as regards
the vertical ordinate, but we are not concerned with them at present.
Since - v~l
by (56), and -p~l is the time-constant of subsidence of a normal
system, we have, for the value of the time-constant of the first system,
because the value of the first nb, say n-^b, is 3-83. Compare this with
the linear-theory time-constant L/B, where L is given by (\lb\ and E
is the resistance of length / of the wire and sheath (sum of resistances,
as the current is oppositely directed in them). Let a = \b. Then
L = M28 id.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 49
We have also
E = 1 Ql/3-n-kb'2, therefore L/R ='211 irfjjtf,
so that the time-constant of the first normal system is to that of the
current in wire and tube on the linear theory as *27 to '21. But it is
only after the first stage of the subsidence is over that this larger time-
constant is valid.
We may write the expression for L thus. Let x = b/a, then
r fda* (M log X ,\
"rfTiiVS^r
nearly the same as 2/zZ log x when x is large. The minimum is when
b = a; then L = ^l. This is the least value of the inductance of a round
wire, viz., when it has a very thin and close-fitting sheath for the return
current, so that the magnetic energy is confined to the wire.
When b/a is only a little over unity,
3fr2 - a* - 2ab
_
b*-a*' (b + a)2
We have also R = WjvMl)? - a2),
and therefore L/R - dfc^
Irrespective of b/a being only a little over unity, we have,
with a/b = ^, L/R = "009 (47r/*&&2),
55 > 55
10 -090
55 TT» "
whilst the time-constant of the first normal system in all three cases is
•068 (47r^62).
The maximum of L/R with b/a variable is when
x being b/a. This value of x is not much different from the ratio of the
nodes in the first normal system, or the ratio of the value of nr making
J^nr) = 0 for the first time, to that making J0(nr) = 0. For the latter
value makes log# = -4'65, and makes the other side of the last equation
be -486.
In the subsidence from the steady state, the central part of the wire
is the last to get rid of its current. But the steady state has to be first
set up. Then it is the central part of the wire that is the last to get
its full current. To obtain the equations showing the rise of the
current and of the magnetic force in the wire and the tube, we have to
reverse or negative the preceding solutions, and superpose the final
steady states. As these are discontinuous, there are two solutions, one
for the wire, the other for the sheath ; but the transient part of them,
which ultimately disappears, is the same in both. There is no occasion
to write these out.
If the steady state is not fully set up before the impressed force is
removed, we see that the central part of the wire is less useful as a con-
II. E. P. VOL. TT. D
50 ELECTRICAL PAPERS.
ductor than the outer part, as the current is there the least. If there
are short contacts, as sufficiently rapid reversals, or intermittences, the
central part of the wire is practically inoperative, and might be removed,
so far as conducting the current is concerned. Immediately after the
impressed force is put on, there is set up a positive current on the out-
side of the wire, and a negative on the inside of the sheath, which are
then propagated inward and outward respectively. If the sheath be
thin, the initial (surface) wire-current is of greater and the initial
sheath-current of less density than the values finally reached by keeping
on the impressed force; whilst if it be the sheath that is thick the
reverse behaviour obtains.
This case of a close-fitting tube is rather an extreme example of
departure from the linear theory ; the return current is as close as
possible and wholly envelops the wire-current. Except as regards dura-
tion, the distributions of current and magnetic force are independent of
the dimensions, i.e., in the smallest possible round wire closely sur-
rounded by the return current the phenomena are the same as in a big
wire similarly surrounded, except as regards the duration of the variable
period. The retardation is proportional to the conductivity, to the
inductivity, and to the square of the outer radius of the tube.
When, as in our next Section, we remove the tube to a distance, we
shall find great changes.
SECTION XXVII. THE VARIABLE PERIOD IN A EOUND WIRE WITH
A CONCENTRIC, TUBE AT ANY DISTANCE FOR THE RETURN
CURRENT.
The case considered in the last Section was an extreme one of
departure from the linear theory. This arose, not from mere size,
but from the closeness of the return to the main conductor, and to
its completely enclosing it. Practically we must separate the two
conductors by a thickness of dielectric. The departure from the linear
theory is then less pronounced ; and when we widely separate the
conductors it tends to be confined to a small portion only of the
variable period. The size of the wire is then also of importance.
Let there be a straight round wire of radius av conductivity klt and
inductivity /Zj, surrounded by a non-conducting dielectric of specific
capacity c and inductivity /x2 to radius a2, beyond which is a tube of
conductivity ky and inductivity /*3, inner radius a.2 and outer «3. The
object of taking c into account, temporarily, will appear later.
Let the current be longitudinal and the magnetic force circular.
Then, by (1&), if y is the current-density at distance r from the axis,
we shall have
in the conductors, and in the dielectric respectively ; the latter form
being got by taking y = cj£/47r, the rate of increase of the elastic
displacement.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 51
A normal system of longitudinal current-density may therefore be
represented by
7j = -^j«^o(wir)j from r = 0 to
yi = AJt(njr) + BsKt(nj), „ r = al to
7s = ^s^o( V) + •# A( V)> » r * "2 to
in the wire, in the insulator, and in the sheath, respectively, at a given
moment. In subsiding, free from impressed force, each of these
expressions, when multiplied by the time-factor tpt, gives the state at
the time t later.
•/"„(/»•) is the Fourier cylinder function, and KQ(nr) the complementary
function. [For their expansions see vol. L, p. 387, equations (70) and
(71)]. The ^4's and H's are constants, fixing the size of the normal
functions ; the n's are constants showing the nature of the distributions,
and p determines the rapidity of the subsidence.
By applying (186) to (196) we find
n? = - lirnfap, nl = - n#p\ //,r - - 4*17*3^ : ...... (206)
expressing all the n's in terms of the p.
Corresponding to the expressions (196) for the current, we have the
following for the magnetic force : —
where, as is usual, the negative of the differential coefficient of JQ(z)
with respect to z is denoted by J^z) ; and, in addition, the negative of
the differential coefficient of KQ(z) with respect to z is denoted by K^(z).
These equations (216) are got by the second and third equations (16),
in the case of H^ and H3 ; and in the case of H^ by using, instead of
Ohm's law, the dielectric equation, giving
in the dielectric, E being the electric force. Of course d/dt=p, in a
normal system.
We have next to find the relations between the five A's and ^'s, to
make the three solutions fit one another, or harmonize. This we must
do by means of the boundary conditions. These are nothing more than
the surface interpretations of the ordinary equations referring to space
distributions. In the present case the appropriate conditions are con-
tinuity of the magnetic and of the electric force at the boundaries,
because the two forces are tangential ; the conditions of continuity of
the normal components of the electric current and of magnetic induc-
tion are not applicable, because there are no normal components in
question. If the magnetic or the electric force were discontinuous, we
should have electric or magnetic current-sheets.
Thus HI and H2 are equal at r = alt and H2 and H^ are equal at
?' = «2. These give, by (216),
52 ELECTRICAL PAPERS.
and (4:Trn2/n.2cp2
"
l(n^} ....... (236.
Similarly, El and E0 are equal at r = av and E.2 and E* are equal at
a.2. These give, by (196),
and
(47r/cp){^2/0(n2a2) + jB2JST0(»2fl2)} =^1{^3/0(%«2) + £sKQ(i¥t2)}. (256)
Thus, starting with ^ given, (225) and (245) give ^2 and 7>0 in terms
of Av and then (236) and (256) give Az and J53 in terms of AY
Similarly we might carry the system further, by putting more con-
centric tubes of conductors and dielectrics, or both, outside the first
tube, using similar expressions for the magnetic and electric forces;
every fresh boundary giving us two boundary conditions of continuity
to connect the solution in one tube with that in the next. But at
present we may stop at the first tube. Ignore the dielectric displace-
ment beyond it, i.e., put c = 0 beyond r = cf-3, because our tube is to
be the return conductor to the wire inside it. We may merely remark
in passing that although when such is the case, there is, in the steady
state, absolutely no magnetic force outside the tube, yet this is not
exactly true in a transient state. To make it true, take e = 0 beyond
r = a3; requiring -£T3 = 0 at r-—as. This gives, by (216),
JgJr1(«8os)+l?3Jri(»3a8) = 0 ...................... (266)
Now A% and J23 are, by the previous, known in terms of Ar Make
the substitution, and we find, first, that Ai is arbitrary, so that it,
when given, fixes the size of the whole normal system of electric and
magnetic force; and next, that the n'a are subject to the following
equation : —
(n a 13213 ~ 13312 _ / (n a \
OV 2 2 1 2 2/
where, on the left side, to save trouble, the dots represent the same
fraction that appears in the numerator immediately over them.
Now, the w's are known in terms of p, hence (276) is the deter-
minantal equation of the j?'s, determining the rates of subsidence of
all the possible normal systems. We have, therefore, all the informa-
tion required in order to solve the problem of finding how any initially
given state of circular magnetic force and longitudinal electric force in
the wire, insulator, and sheath subsides when left to itself. We merely
require to decompose the initial states into normal systems of the above
types, and then multiply each term by its proper time-factor tpt to let
it subside at its proper rate. To effect the decomposition, make use of
the universal conjugate property of the equality of the mutual potential
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 53
and the mutual kinetic energy of two complete normal systems, U12 = Tu
[vol. I., p. 523], which results from the equation of activity. We start
with a given amount of electric energy in the dielectric, and of magnetic
energy in the wire, dielectric and sheath, which are finally used up in
heating the wire and sheath, according to Joule's law.
It would be useless to write out the expressions, for I have no
intention of discussing them in the above general form, especially as
regards the influence of c. Knowing from experience in other similar
cases that I have examined, that the effect of the dielectric displace-
ment on the wire and sheath phenomena is very minute, we may put
c = 0 at once between the wire and the sheath. We might have done
this at the beginning; but it happens that although the results are
more complex, yet the reasoning is simpler, by taking c into account.
The question may be asked, how set up a state of purely longitudinal
electric force in the tube, sheath, and intermediate dielectric? As
regards the wire and sheath, it is simple enough ; a steady impressed
force in any part of the circuit will do it (acting equally over a complete
section). But it is not so easy as regards the dielectric. It requires
the impressed force to be so distributed in the conductors as to support
the current on the spot without causing difference of potential. There
will then be no dielectric displacement either (unless there be impressed
force in the dielectric to cause it). Now, if we remove the impressed
force in the conductors, the subsequent electric force will be purely
longitudinal in the dielectric as well as in the conductors.
But practical^ we do not set up currents in this way, but by means
of localised impressed forces. Then, although the steady state is one of
longitudinal electric force in the wire and sheath, in the dielectric there
is normal or outward electric force as well as tangential or longitudinal,
and the normal component is, in general, far greater than the tangential.
In fact, the electrostatic retardation depends upon the normal displace-
ment. But electrostatic retardation, which is of such immense import-
ance on long lines, is quite insignificant in comparison with electro-
magnetic on short lines, and in ordinary laboratory experiments with
closed circuits (no condensers allowed) is usually quite insensible. We
see, therefore, that when we put c = 0, and have purely longitudinal
electric force, we get the proper solutions suitable for such cases where
the influence of electrostatic charge is negligible, irrespective of the
distribution of the original impressed force. Our use of the longitudinal
displacement in the dielectric, then, was merely to establish a connec-
tion in time between the wire and the sheath, and to simplify the
conditions.
(In passing, I may give a little bit of another investigation. Take
both electric and magnetic induction into consideration in this wire and
sheath problem, treating them as solids in which the current distribution
varies with the time. The magnetic force is circular, so is fully specified
by its intensity, say H, at distance r from the axis. Its equation is, if
z be measured along the axis,
54 ELECTRICAL PAPERS.
in which discard the last term when the wire or sheath is in question ;
or retain it and discard the previous when the dielectric is considered.
The form of the normal H solution is
H= Ji(sr)(A sin + B cos)mz e*',
for the wire, where s2 = - (iirfdsp + m2). The current has a longitudinal
and a radial component, say T and y, given by
F = sJ0(sr) (A sin + L cos)mz ept,
y= — mJ^sr^A cos - B sm)mz €*".
In the dielectric and sheath the KQ and K-^ functions have, of course,
to be counted with the «70 and Jr)
Now put c = 0 in (27 b). We shall have
JQ(n2r) = 1 ; - %7i(v) = 0 ; KQ(n2r) = log (n.2r) ; - n./K^r) = 1 ;
which will bring (:27b) down to
the determinantal equation in the case of ignored dielectric displace-
ment.
To obtain this directly, establish a rigid connection between the
magnetic and electric forces at r = a^ and at r = a2, thus. Since there is
no current in the insulating space, the magnetic force varies inversely
as the distance from the axis of the wire. Therefore, instead of the
second of (216), we shall have
#2 = - (ni/^Ap)^iJi(niai)(ai/r\
by the first of (216). Thus H2 at r = a2 is known, and, equated to H3
at r = a2, gives us one equation between Alt A3, and B3. Next we have
H^ meaning, temporarily, the value of H^ at r = ar This, when
multiplied by /*2, is the amount of induction through a rectangular
portion of a plane through the axis, bounded by straight lines of unit
length parallel to the axis at distances a-^ and r from it; or the line-
integral of the vector-potential round the rectangle ; or the excess of the
vector-potential at distance r over that at distance ax ; so, when
multiplied by p, it is the excess of the electric force at a^ over that
at r. Thus the electric force is known in the insulating space in terms
of that at the boundary of the wire. Its value at r = a2 equated to E5
at r — a2 gives us a second equation between Alt A%, and Bz. The third
is equation (266) over again, and the union of the three gives us (286)
again.
We now have, if y1 and y3 are the actual current-densities at time t in
the wire and the sheath respectively,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 55
where
.
in which only the ^4 requires to be found, so that when t = Q, the initial
state may be expressed. The decomposition of the initial state into
normal systems may be effected by the conjugate property of the
vanishing of the mutual kinetic energy, or of the mutual dissipativity
of a pair of normal systems. Thus, in the latter case, writing (296)
thus, y = ^Au, = 2^r, we shall have
fa, p<.;
u1tf^tfr/&1 + I v
0 J <«2
Wj, -fr'j, and u2, v2 being a pair of normal solutions.
We can only get rid of those disagreeable customers, the K0 and ^
functions, by taking the sheath so thin that it can be regarded as a
linear conductor — i.e., neglect variations of current-density in it, and
consider instead the integral current. (Except when the sheath and
wire are in contact and of the same material, as in the last section.)
Let a4 be the very small thickness of the sheath, and evaluate (286) on
the supposition that a4 is infinitely small, so that a2 and as are equal
ultimately. The result is
/oK«i) = «i^iKai)((?h/x2//xi) lo§ (a2/ai) -
the determinantal equation in the case of a round wire of radius c^ with a
return conductor in the form of a very thin concentric sheath, radius a.2.
Notice that /*3, the inductivity of the sheath itself, has gone out
altogether ; that is, an iron sheath for the return, if it be thin enough,
does not alter the retardation as compared with a copper sheath,
provided the difference of conductivity be allowed for.
We may get (306) directly, easily enough, by considering that the
total sheath-current must be the negative of the total wire-current,
which last is, by integrating the first of (296) throughout the wire,
= (^/n1)2ro12«71(n1a1) tpt.
This, divided by the volume of the sheath per unit length, that is,
by 27r«2r/4, gives us the sheath current-density, and this, again, divided
by &3 gives us the electric force at r = a2. Another expression for the
electric force at the sheath is given by the previous method (the
rectangle business). Equate them, and (306) results.
We have now got the heavy work over, and some results of special
cases will follow, in which we shall be materially assisted by the analogy
of the eddy currents in long cores inserted in long solenoidal coils.
SECTION XXVIII. SOME SPECIAL RESULTS RELATING TO THE RISE
OF THE CURRENT IN A WIRE.
Premising that the wire is of radius alt conductivity kv inductivity
f4 ; that the dielectric displacement outside is ignored ; and that the
sheath for the return current is at distance «2, and is so thin that
56 ELECTRICAL PAPERS.
variations of current-density in it may be ignored, so that merely the
total return current need be considered ; that a4 is the small thickness
of the sheath, and k3 its conductivity, we have the determinantal equa-
tion (306). Let now
LQ = 2/x2 log( fl2/«i), A = ( ViT1, -#2 = O^/'A)"1-
LQ is the external inductance per unit length, i.e., the inductance per
unit length of surface-ciiTTent, ignoring the internal magnetic field. Rl
and E.2 are the resistances per unit length of the wire and sheath
respectively, and |^ is the internal inductance per unit length, i.e., the
inductance per unit length of uniformly distributed wire-current when
the return current is on its surface, thus cancelling the external
magnetic field. We can now write (306) thus : —
and, in this, we have
= 4vpikjpOi — 4&l*i/Ri,
...(326)
From (316) we see that the two important quantities are the ratio of
the external to the internal inductance, and the ratio of the external to
the internal resistance, i.e., the ratios LJ^ and R^jR^.
Suppose, first, the return has no resistance. Draw the curves
yi = Jo(z)/Ji(x) < and */2 = KA)//*iK
the ordinates y, abscissae x, which stands for n^. Their intersections
show the required values of x. The JJJl curve is something like the
curve of cotangent. If LJ^ is large, the first intersection occurs with
a small value of x, so small that J0(x) is very little less than unity, so
that a uniform distribution of current is nearly represented by the first
normal distribution, whose time-constant is a little greater than that of
the linear theory. The remaining intersections will be nearly given by
J^x) = 0. On the other hand, decreasing LQ/^ increases the value of
the first x ; in the limit it will be the first root of J^x) = 0. Thus, if
the wire be of copper, and the return distant (compared with radius of
wire), the linear theory is approximated to. If of iron, on the other
hand, it is not practicable to have the return sufficiently distant, on
account of the large value of /x15 unless the wire be exceedingly fine.
Even if of copper, bringing the return closer has the same effect of
rendering the first normal system widely different from representing a
uniform distribution of current. It is the external magnetic field that
gives stability, and reduces differences of current-density.
Next, let the return have resistance. The curve y2 must now be
The effect of increasing R.2 from zero is the opposite of that of increas-
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 57
ing LQ. It increases the first x, and tends to increase it up to that given
by J^x) = 0 (not counting the zero root of this equation). Thus there
is a double effect produced. Whilst on the one hand the rapidity of
subsidence is increased by the resistance of the sheath, on the other the
wire-current in subsiding is made to depart more from the uniform
distribution of the linear theory. The physical explanation is, that as
the external field in the case of sheath of no resistance cannot dissipate
its energy in the sheath it must go to the wire. But when the sheath
has great resistance the external field is killed by it ; then the internal
field is self-contained, or the wire-current subsides as if Jl(x) = Q, with a
wide departure from uniform distribution. This must be marked when
the wire-circuit is suddenly interrupted, making the return-resistance
infinite.
Now, let there be no current at the time £ = 0, when, put on, and
keep on, a steady impressed force, of such strength that the final
current-density in the wire is F0. At time t the current-density F at
distance r from the axis is given by
_ _ i,t
l\ ^nlal ' I - Kjptf + {/0( Vi)AA( Vi) }2
where the n^'a are the roots of equation (316). And the total current
in the wire, say Cl} and with it the equal and opposite sheath-current,
will rise thus to the final value G'0,
C ^ 4 (1
It will give remarkably different results according as we take the
resistance of the wire very small and that of the sheath great, or con-
versely, or as we vary the ratio LJfj^. Infinite conductivity shuts out
the current from the wire altogether, and so does infinite inductivity;
the retardation to the inward transmission of the current being pro-
portional to the product fij^af. Similarly, if the sheath has no resist-
ance, the return current is shut out from it. In either of these shutting-
out cases the current becomes a mere surface-current, what it always is
in the initial stage, or when we cannot get beyond the initial stage, by
reason of rapidly reversing the impressed force, when the current will
be oppositely directed in concentric layers, decreasing in strength with
great rapidity as we pass inward from the boundary. But if both the
sheath and the wire have no resistance, there will be no current at all,
except the dielectric current, which is here ignored, and the two
surface-currents.
The way the current rises in the wire, at its boundary, and at its
centre, is illustrated in " Induction in Cores." For the characteristic
equation of the longitudinal magnetic force in a core placed within a
long solenoid, and that of the longitudinal current in our present case,
are identical. The boundary equations are also identical. That is,
(316) is the boundary equation of the magnetic force in the core, except-
ing that the constants LQ/^ and B2/E1 have entirely different meanings,
depending upon the number of turns of wire in the coil, and its
58
ELECTRICAL PAPERS.
dimensions, and resistance. If, then, we adjust the constants to be
equal in both cases, it follows that when any varying impressed force
acts in the circuit of the wire and sheath, the current in the wire will
be made to vary in identically the same manner as the magnetic force
in the core, at a corresponding distance from the axis, when a similarly
varying impressed force acts in the coil-circuit (which, however, must
have only resistance in circuit with it. not external self-induction as
well). Thus, we can translate our core-solutions into round-straight-
wire solutions, and save the trouble of independent investigation, in
case a detailed solution has been already arrived at in either case.
Refer to Fig. 3 [p. 398, vol. I., here reproduced]. It represents the
curves of subsidence from the steady state. The "arrival" curves are
got by perversion and inversion, i.e., turn the figure upside down and
look at it from behind. The case we now refer to is when the sheath
has negligible resistance, and when we take the constant Z0 = 2/>i1,
which requires a near return when the wire is of copper, but a very
distant one if it is iron.
•6 -8 1-0 1-2 1-4
Regarding them as arrival-curves, the curve h-Ji^ is the linear-theory
curve, showing how the current-density would rise in all parts of the
wire if it followed the ordinarily assumed law (so nearly true in common
fine-wire coils).
The curve HaHa shows what it really becomes, at the boundary, and
near to it. The current rises much more rapidly there in the first part
of the variable period, and much more slowly in the later part. From
this we may conclude that, when very rapid reversals are sent, the
amplitude of the boundary current-density will be far greater than
according to the linear theory ; whereas if they be made much slower
it may become weaker. This is also verified by the separate calculation
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 59
in " Induction in Cores " of the reaction on the coil-current of the core-
currents when the impressed force is simple-harmonic, the amplitude of
the coil-current being lowered at a low frequency, and greatly increased
at high frequencies [p. 370, vol. I.].
The curve ff0ff0 shows how the current rises at the axis of the wire.
It is very far more slowly than at the boundary. But the important
characteristic is the preliminary retardation. For an appreciable
interval of time, whilst the boundary-current has reached a considerable
fraction of its final strength, the central current is infinitesimal. In fact
the theory is similar to that of the submarine cable ; when a battery is
put on at one end, there is only infinitesimal current at the far end for
a certain time, after which comes a rapid rise.
Between the axis and the boundary the curves are intermediate
between HaHa at the boundary and H0H0 at the axis, there being pre-
liminary retardation in all, which is zero at the boundary, a maximum
at the axis. It is easy to understand, from the existence of this practi-
cally dead period, how infinitesimally small the axial current can be,
compared with the boundary current, when very rapid reversals are
sent. The formulae will follow.
The fourth curve liJiQ shows the way the current rises at the axis
when the return has no resistance, but when at the same time there is
no external magnetic field, or LJ^ — 0. The return must fit closely
over the wire. We may approximate to this by using an iron wire and
a close-fitting copper sheath of much lower resistance. There is pre-
liminary retardation, after which the current rises far more rapidly
than when Z0//x1 is finite.
That is, the effect of changing LJ^ from the value 2 to the value 0
is to change the axial arrival-curve from H0H0 to h0h0. Suppose it is a
copper wire. Then L0 = 2 means Iog(a2/a1) = 1, or a2/a^ = 2-718. Thus,
removing the sheath from contact to a distance equal to 2-7 times the
radius of the wire alters the axial arrival-curve from h0hQ to H^H^
Now this great alteration does not signify an increased departure from
the linear theory (equal current-density over all the wire). It is
exactly the reverse. We have increased the magnetic energy by adding
the external field, and, therefore, make the current rise more slowly.
But the shape of the curve H^H^ if the horizontal (time) scale be suit-
ably altered, will approximate more closely to the linear-theory curve
h-Ji^ By taking the sheath further and further away, continuously
increasing the slowness of rise of the current, we (altering the scale)
approximate as nearly as we please to the linear-theory curve, and
gradually wipe out the preliminary axial retardation, and make the
current rise nearly uniformly all over the section of the wire, except at
the first moment. In fact, we have to distinguish between the absolute
and the relative. When the sheath is most distant the current rises
the most slowly, but also the most regularly. On the other hand, when
the sheath is nearest, and the current rises most rapidly, it does so with
the greatest possible departure from uniformity of distribution.
If the wire is of iron, say ^ = 200, the distance to which the sheath
would have to be moved would be impracticably great, so that, except
GO ELECTRICAL PAPERS.
in an iron wire of very low inductivity, or of exceedingly small radius,
we cannot get the current to rise according to the linear theory.
The simple-harmonic solutions I must leave to another Section. We
may, however, here notice the water-pipe analogy [p. 384, vol. i.]. The
current starts in the wire in the same manner as water starts into
motion in a pipe, when it is acted upon hy a longitudinal dragging force
applied to its boundary. Let the water be at rest in the first place.
Then, by applying tangential force of uniform amount per unit area of
the boundary we drag the outermost layer into motion instantly ; it, by
the internal friction, sets the next layer moving, and so on, up to the
centre. The final state will be one of steady motion resisted by surface
friction, and kept up by surface force.
The analogy is useful in two ways. First, because any one can form
an idea of this communication of motion into the mass of water from its
boundary, as it takes place so slowly, and is an everyday fact in one
form or another ; also, it enables us to readily perceive the manner of
propagation of waves of current into wires when a rapidly varying im-
pressed force acts in the circuit, and the rapid decrease in the amplitude
of these waves from the boundary inward.
Next, it is useful in illustrating how radically wrong the analogy
really is which compares the electric current in a wire to the current of
water in a pipe, and impressed E.M.F. to bodily acting impressed force
on the water. For we have to apply the force to the boundary of the
water, not to the water itself in mass, to make it start into motion so
that its velocity can be compared with the electric current-density.
The inertia, in the electromagnetic case, is that of the magnetic field,
not of the electricity, which, the more it is searched for, the more un-
substantial it becomes. It may perhaps be abolished altogether when
we have a really good mechanical theory to work with, of a sufficiently
simple nature to be generally understood and appreciated.
In our fundamental equations of motion
curl (e - E) = /xH, curl H =
suppose we have, in the first place, no electric or magnetic energy, so
that E = 0, H = 0, everywhere, and then suddenly start an impressed
force e. The initial state is
E = 0, H = 0,
Thus the first effect of e is to set up, not electric current (for that
requires there to be magnetic force), but magnetic current, or the rate
of increase of the magnetic induction, and this is done, not by e, but by
its rotation, and at the places of its rotation. [A general demonstration
will be given later that disturbances due to impressed e or h always
have curl e and curl h for sources.]
Now, imagine e to be uniformly distributed throughout a wire. Its
rotation is zero, except on the boundary, where it is numerically e,
directed perpendicularly to the axis of the wire. Thus the first effect
is magnetic current on the boundary of the wire, and this is propagated
inward and outward through the conductor and the dielectric respec-
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 61
lively. Magnetic current, of course, leads to magnetic induction and
electric current.
Now, in purely electromagnetic investigations relating to wires, in
which we ignore dielectric displacement, we may, for purposes of
calculation, transfer our impressed forces from wherever they may be
in the circuit to any other part of the circuit, or distribute them uni-
formly, so as to get rid of difference of potential, which is much the
best plan. It is well, however, to remember that this is only a device,
similar in reason and in effect to the devices employed in the statics and
dynamics of supposed rigid bodies, shifting applied forces from their
points of application to other points, completely ignoring how forces
are really transmitted. The effect of an impressed force in one part of
the circuit is assumed to be the same as if it were spread all round the
circuit. It would be identically the same were there no dielectric
displacement, but only the magnetic force in question. When, however,
we enlarge the field of view, and allow the dielectric displacement, it is
not permissible to shift the impressed forces in the above manner, for
every special arrangement has its own special distribution of electric
energy. The transfer of energy is, of course, always from the source,
wherever it may be. The first effect of starting a current in a wire is
the dielectric disturbance, directed in space by the wire, because it is a
sink of energy where it can be dissipated. But the dielectric disturb-
ance travels with such great speed that we may, unless the line is long,
regard it as affecting the wire at a given moment equally in every part
of its length ; and this is substantially what we do when we ignore
dielectric displacement in our electromagnetic investigations, distribute
the impressed force as we please, and regard a long wire in which a
current is being set up from outside as similar to a long core in a
magnetising helix, when we ignore any difference in action at different
distances along the core.
SECTION XXIX. OSCILLATORY IMPRESSED FORCE AT ONE END OF
A LINE. ITS EFFECT. APPLICATION TO LONG-DISTANCE TELE-
PHONY AND TELEGRAPHY.
Given that there is an oscillatory impressed force in a circuit, if this
question be asked — what is the effect produced 1 the answer will vary
greatly according to the conditions assumed to prevail. I therefore
make the conditions very comprehensive, taking into account frictional
resistance, forces of inertia, forces of elasticity, and also the approxima-
tion to surface conduction that the great frequency of telephonic
currents makes of importance.
Space does not permit a detailed proof from beginning to end. The
results may, however, be tested for accuracy by their satisfying all the
conditions laid down, most of which I have given in the last three
Sections.
The electrical system consists of a round wire of radius alt conduc-
tivity kv and inductivity ^ ; surrounded by an insulator of inductivity
62 ELECTRICAL PAPERS.
/x2 and specific dielectric capacity c, to radius a.2; surrounded by the
return of conductivity ky inoluctivity /*3, and outer radius ay The wire
and return to be each of length I, and to be joined at the ends to make
a closed conductive circuit.
Let S be the electrostatic capacity, and LQ the inductance of the
dielectric per unit length of the line. That is,
LQ = 2^log(a.2/al\ S = c{2 .og^A)}"1 ......... (335)
We have L0S = Cfj,2 = v~'2:, if v is the speed of undissipated waves through
the dielectric.
Let V be the surface-potential of the wire, and C the wire-current, or
total current in the wire, at distance x from one end, at time /. The
differential equation of F'is
where R' and 1J are certain even functions of p, whose structure will
be explained later, and p stands for d/dt. That of C is the same. The
connection between G and V is given by
........................... (356)
Both (346) and (356) assume that there is no impressed force at the
place considered. If there be impressed force e per unit length, add e
to the left side of (356), and make the necessary change in (346), which
is connected with (356) through the equation of continuity
. ...(366)
ax
But as we shall only have e at one end of the line, we shall not
require to consider e elsewhere.
Now, given (346) and (356), and that there is an impressed force
F0 sin nt at the x = 0 end, find V and C everywhere. Owing to Rf and
Lf containing only even powers of p, and to the property p2 = - n2
possessed by p in simple-harmonic arrangements, Rf and Lf become
constants. The solution is therefore got readily enough. Let
Q - (4^)1 { (R'* + lW)i + L'n}*.
These are very important constants concerned. Let also
tan 0X = (UnP - B'Q)/(B'P + I/n
U
*. '
tan 02 = sin 2Ql/(c-*n - cos 2QI). '
These make Ol and 02 angles less than 90°. Then the potential V at
distance x at time t is
. (396)
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 63
and the current C is
_ ep* sin (nt + Qx - 6l + <92) + e~px sin (nt -Qx-0l
€«e*« + €-*« I 2 cos "
2H
J
Each of these consists of the sum of three waves, two positive, or from
x — Q to ./• = /, and one negative, or the reverse way. If the line were
infinitely long, we should have only the first wave. But this wave is
reflected at x = lt and the result is the second term. Reflection at the
x = 0 end produces the third and least important term.
The wave-speed is n/Q, and the wave-length 2ir/Q. As the waves
travel their amplitudes diminish at a rate depending upon the magni-
tude of P. The angles Ol and 02 merely settle the phase-differences.
The limiting case is wave-speed = i\ and no dissipation.
The amplitude of the current (half its range) is important. It is
c ro(Sn)* ryt'-*) + c-^1-" + 2 cos 2Q(l - x)~\*
(R* + LV}*\_~~ ?pl + €-*» - 2 cos 2QI J '
at any distance .r. At the extreme end x = l it is
1" + g'"" - 2 cos
As it is only the current at the distant end that can be utilised there,
it is clear that (416) is the equation from which valuable information is
to be drawn.
It must now be explained how to get Ef and Lf, and their meanings.
Go back to equation (286), Section xxvii. [p. 54], which is the deter-
minantal or differential equation when dielectric displacement is ignored.
We may write it
When p is d/dt it is the differential equation of the boundary magnetic
force, or of C, since they are proportional. Separating into even and
odd powers of p it will take the form, if we operate on (7,
where R* and Lf are functions of p2. To suit the oscillatory state, put
- ??.2 for p*2, making Rf and Lf constants. They will be of the form
I4; ............... (436)
where R{ depends on the wire, R( on the return ; L{ on the wire, L(
on the return, and L0 on the intermediate insulator. The forms of R{
and L{ have been given by Lord Rayleigh. They are, if g2
where Rl = steady resistance of the wire per unit length,
64 ELECTRICAL PAPERS.
11#3
(446)
77 = i „ f i _ JL + iov~ to<J"
o^t-ioaon !2-'.28.80
to the last of which I have added an additional term. The getting ot
the forms of Rt, and U2, depending upon the return, is less easy,
though only a question of long division. I shall give the formula
later. At present I give their ultimate forms at very high frequencies.
Let p = resistivity, and q = frequency = n/'2ir, then
(456)
These are also Lord Rayleigh's. For the return we have
^/ = (Wsg)* 74 = m/n (466)
I express R{ and R( in terms of the resistivity rather than the
resistance of the wire and return because their resistances have really
nothing to do with it, as we see in especial from the It?2 formula. The
Rfz of the tube depends upon its inner radius only, no matter how thick
it may be, that is to say upon extent of conducting surface, varying
inversely as the area, which is 2;r«2 per unit length. The proof of (466)
will follow.
Now, as regards the meanings. Let us call the ratio of the impressed
force to the current in a line when electrostatic induction is ignorable
the Impedance of the line, from the verb impede. It seems as good a
term as Resistance, from resist. (Put the accent on the middle e in
impedance.) When the flow is steady, the impedance is wholly con-
ditioned by the dissipation of energy, and is then simply the resistance
Rl of the line. This is also sensibly the case when the frequency is
very low ; but with greater frequency inertia becomes sensible. Then
(Pi'2 + Lrri2)^ is the impedance. Here fi and L are, in the ordinary
sense, the resistance and inductance of unit length of line, including
wire and return. When, further, differences of current-density are
sensible, the impedance is (Rf2 + U-n^l. This is greater or less than
the former, according to the frequency, becoming ultimately less,
especially if the wire is of iron, owing to the then large reduction in the
value of U as compared with L.
Now, when we further take electrostatic induction into account we
shall have the above equations (346) and (356), in which PJ and Lf are
the same as if there were no static charge. The proof of this I must
also postpone. It is the only thing to be proved to make the above
quite complete, excepting (466), which is a mere matter of detail. The
proof arises out of the short sketch I gave in Section xxvu. of the
general electrostatic investigation, used there for illustration.
The impedance is made variable ; it is no longer the same all along
the line, simply because the current-amplitude decreases from the place
of impressed force, where it is greatest, to the far end of the line,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 65
where it is least. The question arises whether we shall confine imped-
ance according to the above definition to the place of impressed force,
or extend its meaning. If we confine the use, a new word must be
invented. I therefore, at least temporarily, extend the meaning to
signify the ratio of F"0 to 6'0 anywhere.
It is very convenient to express impedance in ohms, whatever may be
its ultimate structure. Thus the greatest impedance of a line is what
its resistance would have to be in order that in steady-flow the current
should equal that arriving at the far end under the given circumstances.
It will usually be far greater than the resistance. But there is this
remarkable thing about the joint action offerees of inertia and elasticity.
The impedance may be far less than in the electromagnetic theory.
That is, F0/(70 according to (41ft) may be far less than (/2'2 + JW)k
This is clearly of great importance in connection with the future of
long-distance telegraphy ana telephony.
(In passing I will give an illustration of reduction of impedance pro-
duced by inertia. Let an oscillatory current be kept up in a submarine
cable and in the receiving coils. Insert an iron core in them. The
result is to increase the amplitude of the current-waves. More fully,
increasing the inductance of the coil continuously from zero, whilst
keeping its resistance constant, increases the amplitude up to a certain
point, after which it decreases. The theory will follow.)
To get the submarine cable formulae, ignoring inertia, take U = 0 and
PJ — 11. To get the more correct formulae, not allowing for variations
of current-density, but including inertia, take Lf = L the steady induct-
ance, and Rf = R. To get the linear magnetic theory formulae, take
£ = 0, arid L' = L, R' = R. Finally, using R' and J7, but with £=0, we
have the complete magnetic formulae suitable for short lines. Thus
S=0 in (4:11) brings it to
Equations (34ft) to (36ft) are true generally, that is, with Rf and U the
proper functions of d/dt. The solution in the case of steady impressed
force will follow, including the interior state of the wire. Also the
interior state in the oscillatory case.
A great deal may be dug out of (41ft). In the remainder of this
Section, however, we may merely notice the form it takes at very high
frequencies, so high as to bring surface conduction into play, and show
how much less the impedance is than according to the magnetic theory.
Let n be so great as to make B'/L'n small. Then we may also take
Q = n/v.
Also, if f.~pl is small, as it will be on increasing the frequency, we
need only consider the first term under the radical sign in (41ft),
which becomes
(£*
Take for R' its ultimate form
H.E.P. — VOL. II.
ELECTRICAL PAPERS.
got from (455) and (46&) by supposing wire and sheath of the same
material, and 2/a = l/a1 + l/a2.
Then the impedance is
where exp is defined by e* = exp x, convenient when x is complex. Here
LQ is a numeric, and 0 = 30 ohms (i.e., when we reckon the impedance
in ohms); ^ = 1600 and /*=!, if the conductors are copper; and
/ = 105^, if ^ is the length of the line in kilom. ; therefore
= 15Z0 x
To see how it works out, take LQ = 1, a = 1 cm, and q = 104 ; then
F0/(70 = 1 5 x exp 4^/300 ohms.
If the line is 100 kilom., PI is made 1-J, which is too small for our
approximate formula. If 1,000 kilom., it is made 13J, which is rather
large. Pl= 10 is large. If it is 500 kilom., then
jrQ/C0= 15 x exp 6f = 1,178 ohms.
So the impedance is only 1,178 ohms at 500 kilom. distance at the
enormous frequency of 10,000 waves per second. It is of course much
less at a lower frequency, but the more complete formula will have to be
used if it be much lower.
Now compare this real impedance with the resistance of the line in the
steady state, its effective resistance according to the magnetic theory,
and the impedance according to the same. The resistance of the line
we may take to be twice that of the wire, by choosing the return of a
proper thickness, or
Rl= 2 x 500 x 105 x 1600/7r = 50 ohms, say.
L will be a little more than 1J, say 1-6, therefore
Lln='8x27rx 104 = 5060,
so that the linear-theory impedance is nearly 5,100 ohms. •
But, owing to the high frequency, we should use R' and U instead
of R and L ; here take L' = L0 + P/jn, then
This large increase of resistance is more than counterbalanced by the
reduction of inductance, so that the impedance is brought down from
the above 5,100 to about 3,500 ohms, the magnetic theory impedance;
and this is about three times the real impedance at its greatest, viz., at
the distant end of the line.
It is further to be noted that the wire and return need not be solid,
as we see from the value of R! compared with R. What is needed at
very high frequencies is two conducting sheets of small thickness, of
the highest conductivity and lowest inductivity ; i.e., of copper.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 67
SECTION XXX. IMPEDANCE FORMULA FOR SHORT LINES.
RESISTANCE OF TUBES.
In the case of a short line, a very high frequency is needed in general
to make it necessary to take electrostatic induction into account in
estimating the impedance. Keeping below such a frequency, the
impedance per unit length is simply
This is greater than the common (R2 + L2n2)% at first, when the
frequency is low, equal to it at some higher frequency, and less than it
for still higher frequencies. Thus, for simplicity, let the return con-
tribute nothing to the resistance or the inductance ; then, using (446),
we shall have
- <»"
R and L being the steady resistance and inductance of the line per unit
length (the latter to include L0 for the external medium), Rf and U the
real values at frequency w/27r per second, p the inductivity of the wire,
and g = (pn/It)*.
Thus the first increase in the square of the impedance over that of
the linear theory is J/^%2, independent of resistance; large in iron,
small in copper. But as the frequency is raised, the g2 term becomes
sensible ; being negative, it puts a stop to the increase. We can get a
rough idea of the frequency required to bring the impedance down to
that of the linear theory by ignoring the g3 term. This gives
(48i)
The real frequency required must be greater than this, and taking
the gs term into account, we shall obtain, as a higher limit,
........................ (496)
approximately. We see that the simpler (486) is near enough.
If the wire is of copper of a resistance of 1 ohm per kilom., making
R= 104, we shall have, using (486),
If the return is distant, we can easily have L0 = 9. Then the
frequency required is about 100 waves per second. This is a low
telephonic frequency, so that we see that telephonic signalling is
somewhat assisted by the approximation to surface conduction.
If the wire is of iron, then, on account of the large value of /x, a much
lower frequency is sufficient to reduce the impedance below that of the
linear theory ; that is, an iron wire is not by any means so disadvan-
68 ELECTRICAL PAPERS.
tageous, compared with a copper wire of the same diameter, as its
higher resistivity and far higher inductivity would lead one to expect.
But it is not to be inferred that there is any advantage in using iron,
electrically speaking, from the fact that the impedance is so easily made
much less than that of the linear theory. Copper is, of course, the best
to use, in general, being of the highest conductivity, and lowest induc-
tivity. Nor is any great importance to be attached to the matter in
any case, for, on a short line, to which we at present refer, it will
usually happen that the telephones themselves are of more importance
than the line in retarding changes of current.
We also see that in electric-light mains with alternating currents
there may easily be a reduction of impedance if the wires be thick and
the returns not too close. On the other hand, the closer they are
brought the less is the impedance, according to the ordinary formula.
It should be borne in mind that we are merely dealing with a correction,
not with the absolute value of the impedance, which is really the
important thing.
Now take the frequency midway between 0 and the second frequency
w^hich gives the linear-theory impedance. Then IF + L-ifi becomes
wherein use the value of n2 given by (486). The increase of impedance
is not, therefore, in a copper wire, anything of a startling nature.
Impedances are not additive, in general. We cannot say that the
impedance of a wire is so much, that of a coil so much more, and then
that their sum is the impedance when they are put in sequence, at the
same frequency.
In passing, I may as well caution the reader against the false idea
somewhere prevalent. The increased resistance of a wire is not in any
way caused or evidenced by the weakness of the current in the variable
period compared with its final strength, a result due to the back E.M.F.
of inertia. No matter how great the inertia, and how slowly it makes
the current rise, there is no change of resistance, unless there be
changed distribution of current. There must always be some change,
but it is usually negligible. When, however, as notably in the case of
iron, the central part of the wire is inoperative, of course this changed
distribution of current means a large increase of resistance, though not
of impedance, which is reduced. It is a hollow tube, not a solid wire,
that must, to a first approximation, be regarded as the conductor.
There cannot be said to be any definite resistance unless the current
distribution is definite.
Thus, in the rise of the current from zero to the steady state there is,
presuming that there is large departure from the regular final distribu-
tion, no definite resistance, and it is clearly not possible to balance a
wire in which the above takes place against a thin wire, a conclusion
that is easily verified. But the case of simple-harmonic impressed force
is peculiar. The distribution of current, though not constant, goes
through the same regular changes over and over again in such a manner
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 69
that the total current at every moment is the same as if a true linear
circuit of definite resistance and inductance were substituted. This is
very considerably departed from when mere rapid makes and breaks
are employed.
Consider now the resistance of a tube at a given frequency. It
depends materially upon whether the return-current be within it or
outside it. Let there be two tubes, «0 and ^ the inner and outer radii
of the inner, and a.2 and a3 of the outer. By an easy extension of
equation (286), the form quoted in the last Section, the differential
equation of the total current is
the dots indicating repetition of what is above them. The first term
is for the insulator between tubes, the second for the inner tube, the
third for the outer. Or,
where R(, 1&, L{, U2 are functions of p2, and therefore constants when
the current is simple-harmonic. The division of the numerators by
the denominators, a simple matter in the case of a solid wire, becomes
a very complex matter in the tube case. I give the results as far as p2.
It is not necessary to do the work separately for the two tubes, for,
if we compare the expressions carefully, we shall see that they only
differ in the exchange of the inner and outer radii, and in changed
sign of the whole.
For the inner tube we have
where 11^ is the steady resistance per unit length. This is the coefficient
of p, and is therefore nothing more than the inductance per unit length
of the tube in steady flow, the first correction to which depends on p3.
This may be immediately verified by the square- of-force method.
The resistance of the inner tube per unit length is
To obtain, from (516) and (526), the corresponding expressions for
the outer tube, change 7?x to Rv pl to pB, /^ to /A3, ax to «2, and a0 to aB.
The change of $ign is not necessary, because it is involved in the
substitution of E^ for Ev Or, simply, (516) and (526) holding good
when the return is outside the tube, exchange a^ and a0, and we have
the corresponding formulae when the return is inside it.
70 ELECTRICAL PAPERS.
Let &0 = Jftj. This removes a fourth part of the material from the
central part of a solid wire of radius ar The return being outside,
the resistance is
x '01 2.
If solid, the '012 would be *083 ; or the correction is reduced seven
times by removing only a fourth part of the material.
But if the return is inside, all else being the same, the resistance is
R{ = R,+ B^nftiraHfr) x -503 = ^ + P^n^iraf/p,) x -031,
so now the correction is reduced less than three times instead of seven
times, as when the return was outside.
This difference will be, of course, greatly magnified when the ratio
di/ctQ is large ; for instance, consider a solid wire surrounded by a very
thick tube for return ; the steady resistance of the return will be only a
small fraction of that of the wire, but the percentage increase of resist-
ance of the outer conductor will be a large multiple of that of the wire.
Thus the earth's resistance, which, in spite of the low conductivity, is
so small to a steady current, will be largely multiplied when the current
is a periodic function of the time.
Now, as regards the resistance of the tube at high frequencies. If
the return is outside it is
q being the frequency. But if the return is inside, it is
thus depending upon the inner radius when the return is inside, and
on the outer when it is outside, for an obvious reason, when the position
of the magnetic field where the primary transfer of energy takes place
is considered.
Suppose we fix the outer radius, and then thin the tube from a solid
wire down to a mere skin. In doing so we increase the steady resist-
ance as much as we please. But the high-frequency formula (536)
remains the same. Now, as it would involve an absurdity for the
resistance to be less than that in steady flow, it is clear that (536)
cannot be valid until the frequency is so high as to make R{ much greater
than Rlt which is itself very great when the tube is thin. That is to
say, removing the central part of a wire, when the return is outside it,
makes it become more a linear conductor, so that a much higher
frequency is required to change its resistance ; and when the tube is
very thin the frequency must be enormous. Practically, then, a thin
tube is always a linear conductor, although it is only a matter of raising
the frequency to make (536) or (546) applicable.
To get them, use in (506) the appropriate J0(x), etc., formulae when x
is very large. They are
J0(x) = - KI(X) = (sin x + cos x) -f
J^x) = KQ(x) = (sin x - cos x) + (TTX)%. )
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 71
These, used in (50&), putting the circular functions in the exponential
forms, reduce it to
where i = (- l)i Here
— sfai = ^iTfaJcflfp, therefore
and similarly for ss ; so we get
Here, since p2 = - n2, pl = (Jw)*(l +i) ; which brings us to
where ^'M*!1' f! = fM <«i)
as before given, except that the inner tube was a solid wire.
If, however, the frequency were really so high as to make these high-
frequency formulae applicable when the conductors are thin tubes, it is
clear that we should, by reason of the high frequency, need, at least in
general, to take electrostatic induction into account even on a short
line, and therefore not estimate the impedance by the magnetic formulae,
but by the more general of the last Section, in which the same Rf and
Lr occur. As for long lines, it is imperative to consider electrostatic
induction. There is no fixed boundary between a "short" and a
"long" line; we must take into account in a particular case the
circumstances which control it, and judge whether we may treat it as a
short or a long-line question. To the more general formula I shall
return in the following Section, merely remarking at present that there
is a curious effect arising from the to-and-fro reflection of the electro-
magnetic waves in the dielectric, which causes the impedance to have
maxima and minima values as the speed continuously increases ; and
that when the period of a wave is somewhere about equal to the time
taken to travel to the distant end and back, the amplitude of the
received current may easily be greater than the steady current from the
same impressed force. And, in correction of the definition in Section
xxix. of V as the surface potential of the wire, substitute this defini-
tion, Q = SF, where Q is the charge and S the electrostatic capacity,
both per unit length of wire.
SECTION XXXI. THE INFLUENCE OF ELECTRIC CAPACITY.
IMPEDANCE FORMULAE.
Let us now return to the more general case of Section XXIX., the
amplitude of the current due to a simple-harmonic impressed force at one
end of a line. Although the formula (416) for the amplitude at the
distant end is very compact, yet the exponential form of the functions
does not allow us to readily perceive the nature of the change made by
lengthening the line, or making any other alteration that will cause the
72 ELECTRICAL PAPERS,
effect of the electric charge to be no longer negligible, by causing the
magnetic formula to be sensibly departed from. Let us, therefore, put
(416) in the form F"0/(70 = etc., and then expand the right member in an
infinite series of which the first term shall be the magnetic impedance
itself, whilst the others depend on the electric capacity as well as on the
resistance and inductance.
On expanding the exponentials and the cosine in (416), we obtain a
series in which the quantities P4 - Q,\ P6 - ^6, etc., occur, all divided by
To put these in terms of the resistance, etc., we have, by (376),
P* + Q* = SnI, 2PQ = SnR', Q2-pi = Sn*L', ...(586)
where /=(£'2 + Z'%2)i ........................... (596)
/ being the short-line impedance per unit length. Using these, we
convert (416) to the following form,
* ...... (606)
Here we may repeat that VQ and G'0 are the amplitudes of the impressed
force at one end and of the current in the wire at the other end of the
double wire of length Z, whose "constants" are Rf, Z/, and S, the
resistance, inductance, and electric capacity per unit length, Rf and
Lf being functions of the frequency already given. I do not give more
terms than are above expressed, owing to the complexity of the co-
efficients of the subsequent powers of S. To go further, it will be
desirable to modify the notation, and also to entirely separate the
terms depending upon resistance in the [ ] from the others. Let
SLf = v-\ f=(Bf/I/n)*, h = nljv. ../. ..... (616)
Here v is a velocity, / and h numerics. The least value of the velocity
is (SL)~t, at zero frequency, L being the full steady inductance per
unit length, as before. As the frequency increases, so does v. Its
limiting value is (£L0)"* or (/*2c.2)~£, the speed of undissipated waves
through the dielectric. The ratio / falls from infinity at zero fre-
quency, to zero at infinite frequency. See equations (436) to (466).
The ratio h is such that lift* is the ratio of the time a wave travelling
at speed v takes to traverse the line, to the wave-period.
In terms of /, /, and h, our formula (416), or rather (606), when
extended, becomes
From this, seeing that in the [], resistance appears in / only, we see
that the corresponding no-resistance formula is simply
Vsia-> ..................... (636)
where, of course, v is the speed corresponding to L0, or the speed of un-
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 73
dissipated waves. The sine must be reckoned positive always. To
check (636), derive it immediately from (416) by taking 11 = 0. We shall
find the following form of (416) in terms of/ and h useful later : —
F0/C'0 = \Vv(\ +/)<{<2/v + *-'-"'' - 2 cos 2$}*, (646)
where Pl = h(W{(l +/)*- 1}*, 1
W-MJWO +/)*+!}*- /"
Let us now dig something out of the above formulae. This arith-
metical digging is dreadful work, only suited for very robust intellects.
I shall therefore be glad to receive any corrections the following may
require, if they are of any importance.
It will be as well to commence with the unreal, but easily imaginable
case of no resistance. Let the wire and return be of infinite conductivity.
We have then merely wave propagation through the dielectric, without
any dissipation of energy, at the wave-speed 0 = (/*2c2)~*» which is, in
air, that of light-waves. Any disturbances originating at one end
travel unchanged in form ; but owing to reflection at the other end,
and then again at the first end, and the consequent coexistence of
oppositely travelling waves, the result is rather complex in general.
Now, if we introduce a simple-harmonic impressed force at one end, and
adjust its frequency until the wave-period is nearly equal to the time
taken by a wave to travel to the other end and back again at the speed
r, it is clear that the amplitude of the disturbance will be enormously
augmented by the to-and-fro reflections nearly timing with the impressed
force. This will explain (636), according to which the distant-end
impedance falls to zero when
nl/v = IT, or 27r, or STT, etc.
Here '27r/n is the wave-period, and 21 /v the time of a to-and-fro journey.
The current-amplitude goes up to infinity.
If, next, we introduce only a very small amount of resistance, we may
easily conclude that, although the impedance can never fall to zero, yet,
at particular frequencies, it will fall to a minimum, and, at others, go
up to a maximum ; and that the range between the consecutive maxi-
mum and minimum impedance will be very large, if only the resistance
be low enough.
Increasing the resistance will tend to reduce the range between the
maximum and minimum, but cannot altogether obliterate the fluctua-
tions in the value of the impedance as the frequency continuously
increases. In practical cases, starting from frequency zero, and raising
it continuously, the impedance, which is simply M, the resistance of the
line, in the first place, rises to a maximum, then falls to a minimum,
then rises to a second maximum greater than the first, and falls to a
second minimum greater than the first, and so on, there being a regular
increase in the impedance on the whole, if we disregard the fluctuations,
whilst the fluctuations themselves get smaller and smaller, so that the
real maxima and minima ultimately become false, or only tendencies
towards maxima and minima at certain frequencies.
By this to-and-fro reflection, or electrical reverberation or resonance,
74 ELECTRICAL PAPERS,
the amplitude of the received current may be made far greater than the
strength of the steady current from the same impressed force, even
when the electrical data are not remote from, but coincide with, or
resemble, what may occur in practice. To show this, let us work out
some results numerically.
As this matter has no particular concern with variations of current-
density in the conductors, ignore them altogether; or, what comes to
the same thing, let the conductors be sheets, so that Rf = R, the steady
resistance, and Lf = LQ very nearly, the dielectric inductance, both per
unit length. Then, in (646), let
/=!, QI = TT, v = 30ohms .............. (665)
Then, by the second of (656), we find that
h = 2-85;
and, by (646), that
ro/ao = iV-2i[€'8284ir + €"8284T-2? = 60'6^o ohms ....... (676)
The ratio of the distant-end impedance to the resistance is therefore
60-6 x 109£0_60-6 x 1 Q9_ 20-2 _ 202 .
~1T~ nl = 107* ~285'
by making use of the data (666). That is, the amplitude of the
received current is 42 per cent, greater than the steady current, when
(666) is enforced.
But let 6Z = j7r, then
To/Co = JV.21^' + €-™*]J = 28 LQ ohms ;
and the ratio of impedance to resistance is
-- -*•
or the amplitude of current is only 3/4 of the steady current.
And if Ql = JTT, we shall find
F0/<70 = 43-5 ohms,
and that the impedance is slightly greater than the resistance. Whilst,
if Ql = ITT, we shall have
ro/ao = 47-8 ohms,
and find the ratio of impedance to resistance to be 63/85, making the
received current 35 per cent, stronger than the steady current.
The above data of/= 1, and Ql = JTT, JTT, JTT, and TT, have been chosen
in order to get near the first maximum and minimum of impedance.
The range, it will be seen, is very great. Let us next see how these
data resemble practical data in respect to resistance, etc. Remember
that 1 ohm per kilom. makes .R=104, (resistance per cm. of double
conductor). Also, that/= 1 means R = nl= 105nlv if /j is in kilometres.
Then, in the case to which (666) to (686) refer, we shall have, first
assuming a given value of fi, then varying Z-0, and deducing the values
of n and /,, the following results : —
£0=1, Z0 = 10,
^=103, n= 103, /z = 102,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 75
Tin's is an excessively low resistance, T\j- ohm per kilom. ; the frequen-
cies are rather low, and the lengths great. Next, 1 ohm per kilom. : —
£0=1, Z0 = 10, £0=100,
R = W, n=W\ ?t = 103, n = 102,
/1 = 85. /1 = 856. ^ = 8568.
The L0 = 100 case is extravagant, requiring such a very distant return
current (therefore very low electric capacity). Next, 10 ohms per
kilom. : —
£0=1, L0=10, £0
Lastly, very high resistance of 100 ohms per kilom. :—
E=IW, L0=10, n=l&, /1 = 8-5.
In all these cases the amplitude of received current is 42 per cent.
greater than the steady current.
In the next case, Ql = JTT, the quantity nl/v has a value one-fourth of
that assumed in the above ; hence, with the same R and jL0, and same
frequency, the above values of ^ require to be quartered. Then, in all
cases, the current-amplitude will be three-fourths of the steady current.
Similarly, to meet the ()/ = i?r .case, use the above figures, with the l^s
halved ; and in the Ql = JTT case, with the l^a multiplied by f .
A consideration of the above figures will show that there must be, in
telephony, a good deal of this reinforcement of current strength some-
times ; not merely that the electrostatic influence tends to increase the
amplitude all round, from what it would be were only magnetic
induction concerned, but that there must be special reinforcement of
certain tones, and weakening of others. It will be remembered that
good reproduction of human speech is not a mere question of getting
the lower tones transmitted well, but also the upper tones, through a
long range ; the preservation of the latter is required for good articula-
tion. The ultimate effect of electrostatic retardation, when the line is
long enough, is to kill the upper tones, and convert human speech into
mere murmuring.
The formula (625) is the most useful if we wish to see readily to
what extent the magnetic formula is departed from. In this, two
quantities only are concerned, / and h, or (IV / L'n)2 and nl/v; and if both
/and h are small, it is readily seen that the first form of (636) applies,
the factor by which the magnetic impedance is multiplied being
(amh)/h. Even when h is not small the /terms in (626) may be negli-
gible, and the first form of (636) apply. For example, suppose h = -yt
and /small, then (sin h) /h = 3 x '3272 = -9816, showing a reduction of
2 per cent, from the magnetic impedance.
Now, this /i = i means nll = 105, or the high frequency of 105/2?r on a
line of one kilom., 104/2;r on 10 kilom., and so on, down to 10/2?r on
10,000 kilom., always provided the / terms are still negligible. This
may easily be the case when the line is short, but will cease to be true
76 ELECTRICAL PAPERS.
as the line is lengthened, owing to the n in / getting smaller and
smaller. Thus, in the just-used example, if the resistance is 10 ohms
per kilom., and L= 10, we shall have /=TJT on the line of 1 kilom.,
and /= 1 on 10 kiloms. So far, the / terms are negligible, and the
first form of (636) applies. But / becomes 100 on 100 kiloms., which
will make an appreciable, though not large, difference ; and /= 10,000
on 1,000 kilom. will make a large difference and cause the first (636)
formula to fail. It is remarkable, however, that this formula should
have so wide a range of validity.
In the above we have always referred to the distant-end impedance.
But at the seat of impressed force there is a large increase of current on
account of the "charge." Thus, at # = 0, by the formula preceding
(416), we have
-
The term impedance is of course strictly applicable at the seat of
impressed force. As the frequency is raised, this impedance tends to be
represented by
and, ultimately, by ^o/^o = A>v = 30 L0 ohms, .................. (706)
if the dielectric be air. L0 is usually a small number.
SECTION XXXII. THE EQUATIONS OF PROPAGATION ALONG WIRES.
ELEMENTARY.
In another place (Phil. Mag., Aug., 1886, and later) the method
adopted by me in establishing the equations of Fand C, Section xxix.,
was to work down from a system exactly fulfilling the conditions
involved in Maxwell's scheme, to simpler systems nearly equivalent,
but more easily worked. Remembering that Maxwell's is the only
complete scheme in existence that will work, there is some advantage
in this ; also, wre can see the degree of approximation when a change is
made. In the following I adopt the reverse plan of rising from the first
rough representation of fact up to the more complete. This plan has,
of course, the advantage of greater intelligibility to those who have not
studied Maxwell's scheme in its complete form ; besides being, from an
educational point of view, the more natural plan.
Whenever the solution of a so-called physical problem has been
obtained, according to which, under such or such conditions, such or
such effects must happen, what has really been done has been to solve
another problem, which resembles the real one more or less in those
features we wish to study, which we regard as essential, whilst it is of
such a greatly simplified nature that its solution is, in comparison with
that of the real problem, quite elementary. This remark, which is of
rather an obvious nature, conveys a lesson that is not always remem-
bered ; that the difference between theory and empiricism is only one
of degree, even when the word theory is used in its highest sense, and
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 77
is applied to legitimate deductions from laws which are known to be
very true indeed, within wide limits.
It is quite possible to imagine the solution of the general problem of
the universe. There does not seem to be anything against it except its
possible infinite extent. Stop the extension of the universe somewhere ;
then, if its laws be fully known, and be either invariable or known to
vary in some definite manner, and if its state be known at a given
moment, it is difficult to see how it can be indefinite at any later time,
even in the minutest particulars in the history of nations or of animal-
cule, or in the development of a human soul (which is certainly im-
mortal, for the good and evil worked by a soul in this life live for ever,
in the permanent impress they make on the future course of events).
But if this be imagined to be all done, and the universe made a
machine, no one would be a bit the wiser as to the reason why of it.
(Even if we ask what we mean by the reason why, we shall in all pro-
bability get into a vicious circle of reasoning, from which there is no
escape.) All that would be done would be the formulation of facts in
a complete manner. This naturally brings us to the subject of the
equations of propagation, for they are merely the instruments used in
attempts to formulate facts in a more or less complete manner.
The first to solve a problem in the propagation of signals was Ohm,
whose investigation is a very curious chapter in the history of electricity,
as he arrived at results which are, under certain conditions, nearly
correct, by entirely erroneous reasoning. Ohm followed the theory of
the conduction of heat in wires, as developed by Fourier. Up to a
certain point there is a resemblance between the flow of heat and the
electric conduction current, but after that a wide dissimilarity.
Let a wire be surrounded by a non-conductor of heat, in imagination ;
let the heat it contains be indestructible when in the wire, and be in
a state of steady flow along it. If C is the heat-current across a given
section, and V the temperature there, C will be proportional to the rate
of decrease of V alon the wire. Or
if ./• be length measured along the wire. The ratio R of the fall of
temperature per unit length, to the current, is the "resistance" per
unit length, and is, more or less, a constant. Or, the current is pro-
portional to the difference of temperature between any two sections, and
is the same all the way between.
The law which Ohm discovered and correctly applied to steady con-
duction currents in wires is similar to this. Make C the electric
current in the wire, and Fthe potential at a certain place. The current,
which is the same all the way between any two sections, is proportional
to their difference of potential. The ratio of the fall of potential to the
current is the electrical resistance, and is constant (at the same tem-
perature). But Kis, in Ohm's memoir, an indistinctly defined quantity,
called electroscopic force, I believe. Even using the modern equivalent
potential, there is not a perfect parallel between the temperature V and
the potential V. For a given temperature appears to involve a definite
78 ELECTRICAL PAPERS.
physical state of the conductor at the place considered, whereas
potential has no such meaning. The real parallel is between the tem-
perature gradient, or slope, and the potential slope.
Now, returning to the conduction of heat, suppose that the heat-
current is not uniform, or that the temperature-gradient changes as we
pass along the wire. If the current entering a given portion of the
wire at one end be greater than that leaving it at the other, then, since
the heat cannot escape laterally, it must accumulate. Applying this to
the unit length of wire, we have the equation of continuity,
t being the time, and q the quantity of heat in the unit length. But
the temperature is a function of j, say
i-sr,
where S is the capacity for heat per unit length of wire, here regarded,
for simplicity of reasoning, as a constant, independent of the tempera-
ture. This makes the equation of continuity become
Between this and the former equation between C and the variation of
F, we may eliminate C and obtain the characteristic equation of the
temperature,
which, when the initial state of temperature along the wire is known,
enables us to find how it changes as time goes on, under the influence
of given conditions of temperature and supply of heat at its ends.
Ohm applied this theory to electricity in a manner which is sub-
stantially equivalent to supposing that electricity (when prevented from
leaving the wire) flows like heat, and so must accumulate in a given
portion of the wire if the current entering at one end exceeds that
leaving at the other. The quantity q is the amount of electricity in the
unit length, and is proportional to F", their ratio S being the capacity
per unit length. With the same formal relations we arrive, of course,
at the same characteristic equation, now of the potential, so that elec-
tricity diffuses itself along a wire, by difference of potential, in the same
way as heat by difference of temperature.
A generation later, Sir W. Thomson arrived at a system which is
formally the same, but having a quite different physical significance.
Between the times of Ohm and Thomson great advances had been made
in electrical science, both in electrostatics and electromagnetism, and
the quantities in the system of the latter are quite distinct. We have
mb]
(nb)
where on the left appear the elementary relations, and on the right the
resultant characteristic equation of V.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 79
Here C is the current in the wire, E its resistance per unit length,
and V the electrostatic potential. So far there is little change. But S
is the electrostatic capacity per unit length of the condenser formed
by the dielectric outside the wire, whose two coatings are the surface of
the wire and that of some external conductor, as water, for instance,
which serves as the return conductor. Thus S, from being in Ohm's theory
a hypothetical quantity depending upon the nature of the conducting
wire, its size and shape, has become a definitely known quantity depend-
ing on the nature of the dielectric, and its size and shape. Here is the
first step towards getting out of the wire into the dielectric, to be fol-
lowed up later. The equation q = SF is the electrostatic law expressing
the relation between the charge of a condenser and its potential-differ-
ence, q being the charge on the wire per unit length, and £rits potential.
It is assumed that V— 0 at the outer conductor, which requires that its
resistance must be very small, theoretically nothing. This makes V
definitely the potential at the surface of the wire, and it must be the
potential all over its section at a given distance x, if the current is uni-
formly distributed across the section.
The meaning of the equation of continuity is now, that when the cur-
rent entering a given length of wire on one side is greater than that
leaving it on the other, the excess is employed in increasing the charge
of the condenser formed by the given length of wire, the dielectric, and
the outer conductor. In the wire, therefore, comparing the electric cur-
rent to the motion of a fluid, such fluid must be incompressible. It
can, however, accumulate on the boundary of the wire, where it makes
the surface-charge. This is exceedingly difficult to understand. But
in any case, whether electricity accumulates in the wire or only on its
boundary, is quite immaterial as regards the form of the equation of con-
tinuity, and of the characteristic equation. (Of course it is the equa-
tions which give rise to it, and their interpretation, that are of the
greatest importance.)
There is very little hypothesis in this system. We unite the con-
denser-law with Ohm's law of the conduction current, on the hypothesis,
which is supported by experiments with condensers and conductors,
that the equation of continuity is of the kind supposed. But it is assumed
that the electric force is entirely due to difference of potential. As,
when the current is changing in strength, this is not true, there being
then also the electric force of inertia, or of magnetic induction, this
should also be taken into account in the Ohm's law equation, making a
corresponding change in the characteristic equation. What difference
this will make in the manner of the propagation will depend upon the
relative magnitude of the electric force of inertia and of the charge, and
materially upon the length of the line. The necessary change will be
made in the next Section. At present we may only remark that elec-
trostatic induction is most important on long submarine cables, and that
the (715) equations are those to be used for them for general purposes, as
the first approximate representation of the facts of the case.
Now, as regards the accumulation difficulty. This is entirely re-
moved in a beautifully simple manner in Maxwell's theory. The line-
80 ELECTRICAL PAPERS.
integral of the magnetic force round a wire measures the current in it,
a fact that cannot be too often repeated, until it is impressed upon
people that the electric current is a function of the magnetic field, which
is in fact what we generally make observations upon, the electricity in
motion through the wire being a pure hypothesis. Maxwell made this
the universal definition of electric current anywhere. There is no
difference between a current in a conductor or in a dielectric ,as a func-
tion of the magnetic field, though there is great difference in the effect
produced, according to the nature of the matter. All currents are
closed, either in conductors alone or in dielectrics alone, or partly in
one and partly in the other. In a conductor heat is the universal result
of electric current, and energy is wasted ; in a dielectric, on the other
hand, the energy which would be wasted were it conducting is stored
temporarily, becoming the electric energy, which is recoverable. In a
conductor, the time-integral of the current is not a quantity of any
physical significance ; but in a dielectric it is a very important quantity,
the electric displacement, which can only be removed by an equal
reverse current. The electric displacement involves a back electric
force, which will cause the displacement to subside when it is permitted
by the removal of the cause that produced it. Put a condenser in
circuit with a conductor and battery. The current goes right through
the condenser. But it cannot continue, on account of the back force of
the displacement ; when this equals the impressed force of the battery,
there is equilibrium. Eemove the battery, and leave the circuit closed.
The back force of the displacement can now act, and discharges the con-
denser. As for the positive and negative charges, they are numerically
equal to the total displacement through the condenser. They are
located at the places of, and measure the amount of discontinuity of the
elastic displacement, and that is all.
If we must have a fluid to assist (keep it well in the back-ground),
then this fluid must be everywhere, and be incompressible, and accumu-
late nowhere. I am no believer in this fluid. Its only utility is to
hang facts together. But when one has obtained an accurate idea of
the facts it has to hang together, it has served its purpose. A fluid has
mass, and when in motion, momentum and kinetic energy. But the
facts of electromagnetism decidedly negative the idea that the electric
current ^<?r se has momentum or energy, or anything of that kind; these
really belong to the magnetic field. It is therefore well to dispense with
the fluid behind the scenes.
But when one thinks of the old fluids (of surprising vitality), and of
their absurd and wholly incomprehensible behaviour, their miraculous
powers of attracting and repelling one another, of combining together
and of separating, and all the rest of that nonsense, one is struck with
the extremely rational behaviour of the Maxwell fluid. When, further,
one thinks of the greatly superior simplicity of the manner in which it
hangs the facts together (it is remarkably good in advanced electro-
statics, impressed forces in dielectric, etc.), one wonders why it does not
take the place of the commonly used two-fluid hypothesis, merely as a
working hypothesis, and nothing more.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 81
Returning to the wire. It is important to remember that there are
two conductors, not one only, with a dielectric between. When we put
an impressed, force in the wire we send current across the dielectric as
well as round the conducting circuit. The dielectric current ceases as soon
as the back force of the elastic displacement supplies that difference
of potential which is appropriate to the distribution of impressed force
(which difference of potential depends entirely on the conductivity con-
ditions). The equation of continuity means that when the current enter-
ing a unit length of wire on one side is greater than that leaving it on
the other, the excess goes across the dielectric to the outer conductor, in
which there is a precisely equal variation in the current. The time-in-
tegral of this dielectric current q is q, which is the total displacement
outward per unit length of wire. The quantity V is the back E.M.F. of
the displacement. On removing the impressed force, there is left the
electric energy of the displacement, which is \Vq per unit length of
wire ; the back forces act, discharge the dielectric, and this energy is
used up as heat in the conductors.
We can now make some easy extensions of the system (71J). R
must be the sum of the resistances of the wire and return, per unit
length, thus removing the restriction that the return has no resistance.
S, of course, remains the same. But V cannot be the potential of the
wire, because V cannot = 0 all along the return. We may, however,
call V the difference of potential (although that is not exactly true, on
account of inertia, unless we agree to include a part of the E.M.F. of in-
ertia in V). It is, however, definitely the E.M.F. of the condenser, given
by q = SV. We need not restrict ourselves, in these first approxima-
tions, to round wires, or to symmetrically-arranged returns. The
return may be a parallel wire. Of course the proper change must then
be made in the value of S.
SECTION XXXIII. THE EQUATIONS OF PROPAGATION.
INTRODUCTION OF SELF-INDUCTION.
The next step to a correct formulation of the laws of propagation
along wires is, obviously, to take account of the electric force of inertia
in the expression of Ohm's law. This appears to have been first
attempted by Kirchhoff in 1857. According to J. J. Thomson
("Electrical Theories," The Electrician, June 25, 1886, p. 138) this
was his system. Let
e = Xsinns,
where e is the charge per unit length, and s is length measured along
the wire. The equation of X is
2 ds*
where r is the resistance of the wire in electrostatic units, / its length,
y = log(//ft), where a is its radius, and c is a quantity occurring in
Weber's hypothesis, the velocity with which two particles of electricity
H.E.P. — VOL. n. F
82 ELECTRICAL PAPERS.
must move in order that the electrostatic repulsion and the electro-
magnetic attraction may balance.
As it stands, I can make neither head nor tail of it. But, by
extensive alterations, it may be converted to something intelligible.
Turn X into e, in the second equation ; or, what will come to the
same thing, take V as the variable, since e and V are proportional.
Then ignore the first equation altogether. Turn s into our variable x.
&r_j_dv_ ^d^r
dafl-"&ij dt + #W
Clearly this should reduce to (716) by ignoring the last term. There-
fore ' r/Sly = XS.
Here r/l is the resistance per unit length. Therefore (Sy)'1 should
be the capacity per unit length, or {Slog (//a)}"1. This is clearly
wrong. The / should be a2, the resistance of the return, a far smaller
quantity than I ; and the 8 should be 2, if the dielectric is air. This
last correction may, however, be merely required by a change of
units. Making it, we get this result
in our previous notation, with the addition that LQ is the inductance
per unit length of the dielectric only. That is,
with unit inductivity ; a2 distance of return, ax radius of wire. This
estimate of the inductance is, of course, too low. The change of units
makes it doubtful whether L0 or some multiple of it was meant, but
it is clearly a wrong estimate. Notice that L0S is the reciprocal of the
square of a velocity, which is numerically equal to the ratio of the
electromagnetic and electrostatic units, and is the velocity of light, or
close to it.
It is clear that there is room for considerable improvement here in
several ways, such as the establishment of the equations independently
of such a very special hypothesis as Weber's ; also in the estimation
of L; and, in interpretation, to modernise it in accordance with
Maxwell's ideas. Having observed that Maxwell, in his treatise,
described the system (716) of the last section, with no allowance for
self-induction, and knowing this system to be quite inapplicable to
short lines, I (in ignorance of Kirchhoff's investigation) made the
necessary change of bringing in the electric force of inertia (Phil. Mag.,
August, 1876), [vol. I., p. 53], converting the system (716) to the
following : —
_==
dx dt dt'
The equations on the left side show the elementary relations, and that
on the right the resultant equation of V.
ELECTROMAGNETIC INDUCTION AND ITS PKOPAGATION. 83
The difference from (716) is only in the first equation of electric
force, and in the characteristic equation of V. To the electric force
due to V is added the electric force of inertia - LC, where L is the
inductance of the circuit per unit length, according to Maxwell's
system of coefficients of electromagnetic induction. That is, L consists
of three parts, say L0 for the dielectric, Ll for the wire, and L2 for the
return. Their expressions will vary according to the size and shape of
the conductors and their distance apart. In case of symmetry about
an axis, their determination is very easy by the square-of-force method.
The magnetic energy per unit length is ^LC2. It is also 2/xH'2/87r, if
. H is the magnetic force, and the 'summation extends over the region of
space belonging to the unit length. As H is a simple function of C
and of the distance from the axis, the integration is very easily
effected.
L is calculated on the hypothesis that the current-density has always
the steady distribution, just as R is the steady resistance. As it is,
strictly speaking, impossible to have the Faraday-law of induction true
in all parts of the conductors without some departure from the steady
distributions, it is satisfactory to know that more exhaustive investi-
gation shows that L, not LQ) should be used in a first approximation.
In connection with this matter 1 may mention that, rather singularly,
just as I was investigating it, my brother, Mr. A. W. Heaviside, called
my attention to certain effects observed on telegraph lines, which could
be explained by the combined action of the electrostatic and electro-
magnetic induction, causing electrical oscillations which made the
pointers of the old alphabetical indicators jump several steps instead of
one. When freed from practical complications, and worked down to
the simplest form, the matter reduced to this, that the discharge of a
condenser through a coil is of an oscillatory character, under certain
circumstances, and I described the theory in the paper I have mentioned.
It had been given by Sir W. Thomson in 1853, but it is a singular
circumstance that this very remarkable and instructive phenomenon
should not be so much as mentioned in the whole of Maxwell's treatise
(first edition), though it is scarcely possible that he was unacquainted
with it ; if for no other reason, because it is so simple a deduction from
his equations. I lay stress on the word simple, because it is not to be
supposed that Maxwell was fully acquainted with the whole of the
consequences of his important scheme.
Mr. Webb, the author of a suggestive little book on "Electrical
Accumulation and Conduction," had very early practical experience of
electrical oscillations in submarine cables, when they were coiled up on
board ship, ceasing, more or less, as they were submerged.
It is far more difficult to obtain a satisfying mental representation
of the electric force of inertia - LC than of that due to the potential,
or -dF/dx, as described in the last section. The water-pipe analogy
is, however, simple enough. Let L be the mass of the fluid per unit
length, C its velocity, then \LC'2 is its kinetic energy, LC its momentum,
LC the force that must be applied to increase it, - LC the force of
84 ELECTRICAL PAPERS.
reaction. A mental representation of many of the phenomena con-
nected with electrical oscillations is also very simply got by the use of
the fluid analogy. It is, however, certainly wrong, as we find by
carrying it out more fully into detail. Eemark, however, that, as
\LC'2 is the magnetic energy per unit length, LC is the generalised
momentum corresponding to C as a generalised velocity, LC the
generalised externally applied force, an electric force, of course, and
- LC the force of reaction — that is, the electric force of inertia. This
is by the simple principles of dynamics, disconnected from- any
hypothesis as to the mechanism concerned.
The magnetic energy must be definitely localised in space, to the
amount |//,H2/47r per unit volume, and be regarded as the kinetic
energy of some kind of motion in the magnetic field. When steady,
there is no force of inertia. But when H changes, and with it (7,
since these are rigidly connected (in our first approximation) there
is necessarily a force of inertia, which, reckoned as an electric force
appropriate to C as a generalised velocity, is - LC per unit length.
In the discharge of a condenser through a coil, if we start with a
charge, but no current, there is in the first place only the potential
energy of the displacement in the condenser. The discharge cannot
take place without setting up a magnetic field, proportional in intensity
to the current at any moment, so that the original electrical energy
is employed in heating the wire, and also in setting up the magnetic
energy. When the condenser is wholly discharged, the inertia of the
magnetic field keeps the current going, and it will continue until the
whole energy of the magnetic field is restored to the condenser (less
the part wasted in the wire) in the form of the energy of the negative
displacement there produced. Except that the charge is smaller, and
of the opposite sign, everything is now as when we started, so that we
may begin again and have a reverse current, continuing until the
condenser is again charged in the same sense as at first, with no
magnetic field. This is the course of a complete oscillation. But if
the resistance be of or above a certain amount, depending on the
capacity of the condenser and the inductance of the coil, the oscillations
cease, and the discharge is completed in a single current which does not
reverse itself.
Similar effects take place, in general, in any circuit, when a change is
made which involves a redistribution of electric displacement, or its
total discharge, but the full theory is usually very difficult to follow in
detail. The so-called " false discharge " of a submarine cable is, how-
ever, easily comprehensible by the last paragraph.
If, in the characteristic equation of V in (72&), we take L = 0,
reducing it to that of (715), we have simple diffusion of the static
charge. If, for instance, the ends of the lines be insulated, any initial
state of charge will settle down to be a uniform distribution, in a
non-oscillatory manner, the smaller inequalities (smaller as regards
length of line over which they extend) being wiped out rapidly, the
larger more slowly ; the law being that similar distributions subside
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 85
similarly, but in times which are proportional to the squares of the
lengths concerned.
If, on the other hand, we take JR = Q in the characteristic equation
of Fin (72b), we have an entirely different order of events. As there
is no waste in the wire, it is clear that the total energy of any initial
state, electric and magnetic, remains undiminished. We can definitely
divide the initial state into two distinct states travelling in the manner
of waves in opposite directions, and being continuously reflected at the
ends. Or, more simply, set up a charge at a single point of the line.
It will divide into two, which will go on travelling backwards and
forwards for ever. But into details of this kind we must not be
tempted to enter at present, the immediate object being to lay the
foundations for a more general theory.
When both terms on the right side of the characteristic equation
are counted, propagation takes place by a mixture of diffusion and
wave-transfer. A wave sent from one end of the line which would,
were there no resistance, travel unchanged in form, and be reflected
over and over again at the ends, in reality spreads out or diffuses
itself, as well as, to a certain extent, being carried forward as a wave.
The length of the line is an important factor. Wave characteristics get
rapidly wiped out in the transmission of signals on a very long submarine
cable, so that the manner of variation of the current at the distant end
approximates to what it would be in the case of mere diffusion.
On the other hand, coming to a very short line, there are, every
time a signal is made, immensely rapid dielectric oscillations, before
the steady state is reached, due to to-and-fro reflection. As a general
rule, this oscillatory phenomenon is unobservable, but it is none the
less existent. It is customary to ignore it altogether in formulation,
regarding the matter as one in which magnetic induction alone is
concerned. Of course the magnetic energy is then far more important
than the electric, and the current in the wire rises nearly in accordance
with the magnetic theory.
The immense rapidity of the dielectric vibrations is one reason why
they are unobservable, except indirectly, and under peculiar circum-
stances. Sometimes, however, they become prominent, especially when
a circuit is suddenly interrupted, when we shall have large differences
of potential. Mr. Edison discovered a new force. The enthusiasm
displayed by his followers in investigating its properties was most
edifying, and thoroughly characteristic of a vigorous and youthful
nation. But it was only the dielectric oscillations, it is to be pre-
sumed ; unless indeed it be really true, as has been reported, that the
renowned inventor has kept the new force concealed on his person
ever since.
How is it, it may be asked, that in the rise of the current in a short
wire, according to the simple magnetic theory, the potential at any
point in the wire is regarded as a constant, viz., its final value when the
current has reached the steady state 1 Thus, as we have
e dV dC , d'2F
and
86 ELECTRICAL PAPERS.
if e is the total impressed force in the circuit, and I the length, the
potential variation dF/dx must be constant. Supposing then e to exist
only at x = 0, the current will rise thus : —
and the value of -dVjdx must be e/'l, from the very moment e is
started, and so long as it is kept on.
When we seek the interpretation, in the more general theory, we
find that although the current oscillations become so insignificant on
shortening the line that the well-known last formula becomes valid,
practically, yet the potential oscillations remain in full force during the
variable period. A wave of potential travels to and fro at the velocity
(LS)~*, making the potential at any one spot rapidly vibrate between
a higher and a lower limit, though not according to the S. H. law, but
in such a manner that its mean value is the final value, whilst the
limits between which the vibration occurs continuously approach one
another ; the vibration, on the whole, subsiding according to the
exponential law, with 2L/E as time:constant. The quantity e/l, which
in the above rudimentary theory is taken to be the actual potential
variation, is really the mean value of the real rapidly vibrating potential
variation, at every point of the circuit and during the whole variable
period, at whose termination, on subsidence of the vibrations, it be-
comes the real potential variation. [See vol. L, pp. 57 and 132 for
details.]
To get rid of this vibration, we have merely to distribute the im-
pressed force so as to do away with the potential variation.
Having now got the elementary relations established, we can proceed
to the simplest manner of extending them to include the phenomena
attending the propagation of current into the conductors from the
dielectric.
SECTION XXXIV. EXTENSION OF THE PRECEDING TO INCLUDE THE
PROPAGATION OF CURRENT INTO A WIRE FROM ITS BOUNDARY.
The first step to getting out of the wire into the dielectric occurs in
Sir W. Thomson's theory, Section xxxii. We certainly get as far as
the boundary of the wire. To some extent we make progress in
adopting (same Section) Maxwell's idea of the continuity of the con-
duction and the dielectric current, when the conduction current is
discontinuous itself. Further progress is made (Section xxxni.) in
introducing the electric force of inertia and the magnetic energy, so
far as dependent on the first differential coefficient of the current with
respect to the time, assuming the magnetic field to be fixed by the
single quantity C, the wire-current, just as the electric field is fixed by
the single quantity Vt the potential-difference of the two wires at a
given distance.
But the magnetic machinery does not move in rigid connection with
the wire-current, as is implied in the specifications of the magnetic
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 87
energy by %LC'2, like that of the electric energy by J*ST2, L and S
being the inductance and the electric capacity, per unit length of line.
In going further, I believe the following to be the most elementary
method possible, as well as being pretty comprehensive. To fix ideas,
and simplify the nature of the magnetic field, let the line consist of
two concentric tubes, separated by a dielectric nonconducting tube.
The dielectric is to occupy our attention mainly, in the first place. Let
rtj and a.2 be its inner and outer radii, a-0 the inner radius of the inner
tube, and a3 the outer radius of the outer. Find the connection
between the longitudinal electric force at the inner and outer boun-
daries of the dielectric tube, and the E.M.F. of the condenser, and the
K.M.F. of inertia, so far as it depends upon the magnetic field in the
dielectric.
Let ABCD in the figure be a rectangle in a plane through the
common axis of the tubes, AB being on the inner and CD on the outer
boundary of the dielectric, both of unit
length. Let the current be from A to B D r = fl2 C
in the inner tube, in which direction x is
measured, and therefore from C to D in the
outer tube. These currents are not precisely
equal under all circumstances, but are so
nearly equal that we can ignore the longi-
tudinal current in the dielectric in com-
parison with them ; then the current C in
the inner necessitates the same current C in the outer tube. The lines
of magnetic force are directed upward through the paper, and the
intensity of force is 2C/r at distance r from the common axis of the
tubes.
The total induction through the rectangle is therefore
if /j,.2 be the inductivity of the dielectric, and LQ the inductance of the
dielectric per unit length of line.
Now, the rate of decrease of the induction with the time, or - L0C,
is the E.M.F. of inertia in the circuit ABCD in the order of the letters.
But if E and F are the longitudinal electric forces in AB and DC, and
V and W the radial forces in BC and AD, another expression for the
E.M.F. in the circuit is E - F+ V- W. But as AB and CD are of unit
length, V- W=dV\dx. Hence
E-F+dF/dx=-L0C, or -drfdx = L$+E-F. (736)
Next, let Tl and F2 be the longitudinal current-densities at the
boundaries of the conductors, p: and p2 their resistivities, and elt ez the
impressed forces, if any, in them. Then, by Ohm's law,
and therefore E -F=plTl- p^-e, ....................... (746)
if e = e^ - e2. Thus e is the impressed force in the circuit per unit
88 ELECTRICAL PAPERS.
length, irrespective of how it is divided between the inner and the
outer conductor. Also, e is supposed to be longitudinal.
Now use (746) in (736), making it become
We now require to connect I\ and F2, the current-densities at the
boundaries of the conductors, with the total currents in them. Repre-
senting these connections thus,
................. (766)
we require to find the forms of 1% and J2£', one for the inner, the other
for the outer conductor. If this be imagined to be done, and we put
the equation (756) becomes
e-dF/dx = R"C=L()C + Rf{C+I%C, ............... (776)
wherein R" is known. The complete scheme will therefore be,
e -dF/dx = R"C, q = SF, - dC/dx = dq/dt = SF, (786)
which should be compared with (716) and (726). As for the equations
of Fand of C, they may be obtained by elimination, but it is unneces-
sary to write them at present.
We have supposed R'{ and R" to be known. The question is, then,
how to find them. We know that in steady-flow they must be R^ and
R2, the steady resistances of the conductors. We know, further, that
they are R-^ + L^d/dt) and R% + L2(d/dt), when only the first derivative
C of the current is allowed for. Now, we know that, under all ordi-
nary circumstances, the length of a wire must be a very large multiple
of its diameter before the influence of the electric charge becomes
sensible. When it does become sensible, the current is of a different
strength in different parts of the line during the setting up of a steady
current. But in a section of the line which, though long compared
with the diameter of the wire, is short compared with its length, the
current changes insensibly, even when the change is very great between
the current-strength in that section and in another, which, by contrast,
may be called distant from the first.
It is, clear, therefore, that we shall come exceedingly near the truth
if, in the investigation of the function R'{ we altogether disregard the
change in strength of the current in passing along the line. This
amounts to ignoring the small radial component of the current in the
conductors, and making the current quite longitudinal. This is only
done for purposes of simplification, and does not involve any physical
assumption in contradiction of the continuity of the current; for we
join on the dielectric current to that in the conductors, by means of the
equation of continuity, the third of (786).
The determination of R'{ and B% is thus made a magnetic problem,
of which I have already given the solution. See equation (506),
Section xxx., where the first big fraction represents R" for the inner
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 89
conductor, and the second R" for the outer. The separation of these
into even and odd differential coefficients, thus,
is of principal utility in the periodic applications. It may, perhaps, be
as well pointed out that the first equation (786) should, in strict-
ness, be cleared of fractions to obtain the rational differential equation.
But the advantages of the form (786) are too great to be lightly
sacrificed to formal accuracy.
We have now the means of fully investigating the transmission of
disturbances along the line, including the retardation to inward trans-
mission from the dielectric into the conductors as well as the effects of
the electrostatic charge. The system is a practical working one ; for,
the electrical variables being J^and C, we are enabled to submit the line
to any terminal conditions arising from the attachment of apparatus,
the effect of which is fully determinable, because the differential equa-
tion of the apparatus itself is one between V and C. Both the ratio of
V to C and their product are important quantities. The first is, in
steady-flow, a mere resistance. In variable states it becomes a complex
operator of great importance in the theoretical treatment. The second,
F(7, is the energy-current, concerning which more in the next Section.
In the meantime I will briefly indicate the nature of the changes
made when we go further towards a complete representation of Maxwell's
electric and magnetic connections. First, as regards the small radial
component of current in the conductors. The quantity s that appears
in the expression for R" is given by
/Xj being the inductivity and ^ the conductivity of the inner conductor,
whilst p is, when we are dealing with a normal system of subsidence, a
constant ; thus, *pt is the time-factor showing how it subsides, p being
always negative in an electromagnetic problem, and also always negative
in an electrostatic problem, whilst in a combined electrostatic and
magnetic case it is either negative and real, or negative with an
imaginary part, when its term must be paired with a companion to
make a real oscillatorily subsiding system. Now the simplest form of
terminal condition possible is F=0 at both ends of the line, i.e., short-
circuits. Then
F = ^sinOVz//),
where j is any integer, represents a V system, satisfying the condition
of vanishing at both ends. Let the factor of x, which is jir/l, be denoted
by m. Only the first few/s are of much importance, 1, 2, 3, etc. Now,
if we change the connection between sl and p above-given to
s* = - lirpfap + ra^,
we shall be able to take the radial component of current in the
conductors into account ; but the change made is usually very insigni-
ficant. There are four other cases in which we can work similarly —
viz., when the line is insulated at both ends, or (7=0; when it is
90 ELECTRICAL PAPERS.
insulated at either end and short-circuited at the other — two cases; and
when the line is closed upon itself, each conductor making a closed
circuit without interposed resistances, etc. In all except the last case,
when the line has no ends, the quantity VG vanishes at both ends of
the line, either V or C being zero at these places, so that no energy can
enter or leave the line (dielectric and two conductors). Nor can this
happen in the last case. But if we join on terminal apparatus, thus
making VC finite at one or both ends, the system breaks down, and we
require to fall back upon the preceding.
But if we keep to the five cases mentioned, we may make a further
refinement, by taking the longitudinal current in the dielectric into
account, which we have previously considered negligible in comparison
with the current C. We cannot do this in terms of F, which is
inadequate to express the electric energy. But we may do it in terms
of the electric and magnetic forces, and then obtain a full representation
of Maxwell's connections, instead of an approximate. But even in this
it is assumed that there is no magnetic disturbance outside the outer
conducting tube or inside the inner, which there must really be, for we
must have continuity of the tangential electric force, which necessitates
electric force, and therefore also electric displacement and current and
magnetic force, outside the outer tube and inside the inner, having
some minute disturbing effect on the current in the conductors.
We may, however, leave these refinements to take care of themselves,
and return to the /^and C system of representation. The advantage
of dealing with concentric tubes is due to the circularity of the lines of
magnetic force, which produces considerable mathematical simplifica-
tions, as well as physical. Suppose, however, the tubes are not con-
centric, although the dielectric is still shut in by them. Here, clearly,
to a first approximation, we have merely to give changed values to the
constants S and Z, whilst R is unchanged. But to go further, the
determination of R" and R% will present great difficulties. This, how-
ever, is clear: that the full Lf will have for its minimum value,
approached with very rapid oscillations, Z,0, such that SLQ = v~2, where
v is the speed of propagation of undissipated disturbances through the
dielectric. This follows by regarding the conductors as infinitely con-
ducting, so that there is no waste in them, when the equation of V
becomes
«j /7QM
^_, or =^ow, ............... (796)
showing wave propagation with velocity v.
But if the two conductors be parallel solid wires or tubes (not
concentric), and be placed at a sufficient distance from one another, the
lines of magnetic force in and close round the conductors will be very
nearly circles, so that we may regard R" and R% as known by the pre-
ceding ; and we can therefore go beyond the approximate method of
representation founded upon R, S, and L only. Even if we bring the
conductors so close that there is considerable disturbance from the
assumed state, we should still, in reckoning R" and R'l in the same way,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 91
go a long distance in the direction required, especially in the case of
iron wires, in which, by reason of the high inductivity, the magnetic
retardation is so great.
The effect of leakage has not been allowed for in the preceding.
The making of the necessary changes is, however, quite an elementary
matter in comparison with those connected with magnetic retardation.
We require to change the form of the equation of continuity. If
there be a leakage-fault on an otherwise perfectly insulated line, we
have the line divided into two sections, in each of which the former
equations hold good ; whilst at the place of the leak there is continuity
of J^and discontinuity of C, the current arriving at the leak on the one
side exceeding that leaving it on the other by the current in the leak
itself, which is the quotient of V by the resistance of the leak, if it be
representable as a resistance merely. But when the leakage is widely
distributed it must be allowed for in the line-equations. Even in the
case of leakage over the surface of the insulators of a suspended wire,
the proper and rational course is to substitute continuously distributed
leakage for the large number of separate leaks ; which amounts to the
same thing as substituting a continuous curve for a large number of
short straight lines joined together so as to closely resemble the curve.
The equation of continuity becomes
-dCjdx = Kr+Sr, (SOb)
where the fresh quantity K is the conductance, or reciprocal of the
insulation resistance, per unit length of line. ^That is, the true current
leaving the line is the sum of the former SP] the condenser-current,
and of KV, the leakage-current, both of which co-operate to make the
current in the line vary along its length, although in the steady state it
is the leakage alone that thus operates. But as regards retardation,
their effects are opposed. The setting up of the permanent state is
greatly facilitated by leakage, as is most easily seen by considering the
converse, viz., the subsidence of the previously set-up steady state to
zero when the impressed force is removed. If, then, we wish to
increase the clearness of definition of current-changes at the distant end
of a line on which electrostatic retardation is important, we can do it
by lowering the insulation-resistance as far as is practicable.
SECTION XXXV. THE TRANSFER OF ENERGY AND ITS APPLICATION
TO WIRES. ENERGY-CURRENT.
When the sage sits down to write an elementary work he naturally
devotes Chapter I. to his views concerning the very foundation of
things, as they present themselves to his matured intellect. It may be
questioned whether this is to the advantage of the learner, who may be
well advised to " skip the Latin," as the old dame used to say to her
pupils when they came to a polysyllable, and begin at Chapter n. If
this be done, Prof. Tait's " Properties of Matter " is such an excellent
scientific work as might be expected from its author. But Chapter i.
is metaphysics. There are only two Things going, Matter and Energy.
92 ELECTRICAL PAPERS.
Nothing else is a thing at all ; all the rest are Moonshine, considered as
Things.
However this be, the transfer of energy is a fact well known to all,
even when we put the statement in such a form that the energy seems
to lose its thinginess, by calling it the transfer of the power of doing
work. Thus, after transfer of energy from the sun ages ago, followed
by long storage underground and convection to the stove or furnace,
we set free the imprisoned energy, to be generally diffused by the most
varied paths. The transfer from place to place can be, in great
measure, traced so far as quantity and time are concerned ; but it does
not seem possible to definitely follow the motion of an atom of energy,
so to speak, or to give a fixed individuality to any definite quantity of
energy.
Whenever the dynamical connections are known, the transfer of
energy can be found, subject to a certain reservation. In the element-
ary case of a force, F, acting on a particle of mass m and velocity v, F
is measured by the rate of acceleration of momentum, or F=mv; and,
to obtain the equation of activity, we merely multiply this equation by
the velocity, getting Fv = mw = T, the rate of increase of the kinetic
energy T, or ±mv2, which is the amount of work the particle can do
against resistance in coming to rest. Where the energy came from is
here left unspecified. In a case of impact, we may clearly understand
that the transfer of kinetic energy is from one of the colliding bodies
to the other through the forces of elasticity brought into play, thus
making potential energy an intermediary, though what the potential
energy may be, and whether it is not itself kinetic, or partly kinetic,
we are not able to decide.
It is much more difficult in the case of gravity. As the stone falls
to the ground, it acquires kinetic energy truly ; and if energy moves
continuously, as its indestructibility seems to imply, it must receive its
energy from the surrounding medium ; or the energy of gravitation
must be in space generally, wholly or in part, and be transferred
through space by definite paths through stresses in the medium, by
which means Maxwell endeavoured to account for gravitation. In
general, we have only to frame the equations of motion of a continuous
system of forces, and it stands to reason that the transfer of energy
is to be got by forming the equation of activity, not of the system
as a whole, but of a unit volume.
Now, in the admirable electromagnetic scheme framed by Maxwell,
continuous action through space is involved, and the kinetic and
potential energies (or magnetic and electric) are definitely located, as
well as the seat and amount of dissipation of energy. We therefore
need only form the equation of activity to find the transfer-of-energy
vector. Of course impressed forces are subject to the energy definition.
No other is possible in a dynamical system.
But if we take Maxwell's equations and endeavour to immediately
form the equation of activity (like Fv = T from F=mv), it will be found
to be impossible. They will not work in the manner proposed. But
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 93
we may consider the energy, electric and magnetic, entering and
leaving a given space, and that dissipated within it, and by laborious
transformations evolve the expression for the vector transfer. This
was first done by Prof. Poynting for a homogeneous isotropic medium
(Phil. Trans., 1884). In my independent investigation of this matter,
I also followed this method in the first place (The Electrician, June 21,
1884) [p. 377, vol. I.] in the case of conductors. But the roundabout
nature of the process to obtain what ought to follow immediately from
the equations of motion, led me to remodel Maxwell's equations in
some important particulars, as in the commencing Sections of this
Article (Jan., 1885) with the result of producing important simplifica-
tions, and bringing to immediate view useful analogies which are in
Maxwell's equations hidden from sight by the intervention of his
vector-potential. This done, the equation of activity is at once deriv-
able from the two cross-connections of electric force and magnetic
current, magnetic force and electric current, in a manner analogous to
Fv = f, without roundabout work, and applicable without change to
heterogeneous and heterotropic media, with distinct exhibition of what
are to be regarded as impressed forces, electric and magnetic.
(Electrician, Feb. 21, 1885) [p. 449, vol. I.]
Knowing the electric field and the magnetic field everywhere, the
transfer of energy becomes known. The vector transfer at any place
is perpendicular to both the electric and the magnetic forces there, not
counting impressed forces. Its amount per unit area equals the
product of the intensities of the two forces and the sine of their
included angle.
But I mentioned that there is a reservation to be made. It is like
this. If a person is in a room at one moment, and the door is open,
and we find that he is- gone the next moment, the irresistible con-
clusion is that he has left the room by the door. But he might have
got under the table. If you look there you can make sure. But if you
are prevented from looking there, then there is clearly a doubt whether
the person left the room by the door or got under the table hurriedly.
There is a similar doubt in the electromagnetic case in question, and in
other cases. Thus, we can unhesitatingly conclude from the properties
of the magnetic field of magnets that the mechanical force on a complete
closed circuit supporting a current is the sum of the electromagnetic
forces per unit volume (vector-product of current and induction), but
it does not follow strictly that the so-called electromagnetic force is
the force really acting per unit volume, for any system of forces
might be superadded which cancel when summed up round a closed
circuit.
So, in the transfer-of-energy case, there may be any amount of
circulation of energy in closed paths going on (as pointed out in another
manner by Prof. J. J. Thomson), besides the obviously suggested
transfer, provided this superposed closed circulation is without dissipa-
tion of energy. Or, if W be the vector energy-current density, accord-
ing to the above-mentioned rule, we may add to it another vector, say
W, provided w have no convergence anywhere. The existence of w is
94 ELECTRICAL PAPERS.
possible, but there does not appear to be any present means of finding
whether it is real, and how it is to be expressed.
Its consideration may seem quite useless, in fact. But it is forced
upon us in quite another way, by the fact that, when w = 0, we are
sometimes led to the circuital flux of energy. Let, for instance, a
magnet be placed in the field of an electrified body ; or, more simply,
let a magnet be itself electrified. There is no waste of energy ; hence
the flux of energy caused by the coexistence of the two fields, electric
and magnetic, is entirely circuital. E.g,, in the case of a spherical
uniformly magnetised body, uniformly superficially electrified, it takes
place in circles in parallel planes perpendicular to the axis of magnetisa-
tion, the circles being centred on this axis. This circuital flux is
entirely through the air or other dielectric. What is the use of it?
On the other hand, what harm does it do ? And if the medium is
really strained by coexistent electric and magnetic stresses, why should
there not be this circuital flux ? But, if we like, we may cancel it by
introducing the auxiliary w.
There is yet another kind of closed circulation, according to W alone,
not existing by itself, but set going by impressed forces causing a
useful transfer of energy, and ceasing when the useful transfer ceases.
If, for instance, we close a conductive circuit containing a battery, we
set up a useful transfer from the battery to all parts of the wire,
through the dielectric usually. Suppose there is also impressed electric
force in the dielectric, or electrification, or any stationary electric field.
If the battery does not work there is no transfer of energy. But when
it does, there is, besides the regular first-mentioned transfer from the
battery to the wire, a closed circulation due to the coexistence of the
stationary electric field and the magnetic field of the wire-current, the
resultant transfer being got by superposing the regular flux and the
closed circulation. Here again, by introducing w, we may reduce it to
the regular undisturbed transfer. It is clear, then, in considering the
nature of the transfer in a useful problem, that it is of advantage to
entirely ignore the useless transfer, and confine our attention to the
undisturbed.
A general description of the transfer along a straight wire was given
in Section n. [vol. L, p. 434]. It takes place, in the vicinity of the
wire, very nearly parallel to it, with a slight slope towards the wire, as
there described. Prof. Poynting, on the other hand (Royal Society,
Transactions, February 12, 1885), holds a different view, representing
the transfer as nearly perpendicular to a wire, i.e., with a slight
departure from the vertical. This difference of a quadrant can, I think,
only arise from what seems to be a misconception on his part as to the
nature of the electric field in the vicinity of a wire supporting electric
current.
The lines of electric force are nearly perpendicular to the wire. The
departure from perpendicularity is usually so small that I have some-
times spoken of them as being perpendicular to it, as they practically
are, before I recognised the great physical importance of the slight
departure. It causes the convergence of energy into the wire. To
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 95
estimate the amount of departure, we may compare the normal and
tangential components of electric force. Let there be a steady current
in a straight wire, and the fall of potential from beginning to end be
V^-V^\ the tangential component is then (F"0-^)-f/, if / be the
length of wire. On the other hand, the fall of potential from the wire
to its return — of no resistance, for simplicity — at any distance from the
beginning of the line, is F, which is VQ at one end and V-^ at the other.
It is clear at once that the tangential is an exceedingly small fraction
of the normal component of electric force, if the wire be long, and that
it is only under quite exceptional circumstances anything but a small
fraction. Prof. Poynting should therefore, I think, make his tubes of
displacement stick nearly straight up as they travel along the wire,
instead of having them nearly horizontal, unless 1 have greatly mis-
understood him.
But if we distribute the impressed force uniformly throughout the
circuit, so that there shall be, in the steady state, no difference of
potential and no transfer of energy, owing to the impressed force at any
place being just sufficient to support the current there then, on start-
ing the impressed force, the transfer of energy will be perpendicular to
the wire outward, ceasing when the steady state is reached ; and, on
the other hand, on stopping the impressed force the transfer will be
perpendicular to the wire inward, the magnetic energy travelling back
again (assisted by temporary longitudinal electric force, which has no
existence in the steady state) to be dissipated in the wire. But this
case, though imaginable, is not practically realisable.
In the vicinity of the wire the radial electric force varies inversely as
the distance, and so does the intensity of magnetic force. The density
of the energy-current therefore varies inversely as the square of the
distance approximately. This does not continue indefinitely. Thus, if
the return be a parallel wire the middle distance is the place of mini-
mum density of the energy-current, in the plane of the two wires. As
regards the total energy-current, this is FU, the product of the fall of
potential from one wire to the other into the current in each. One
factor, V, is the line-integral of the electric force across the dielectric.
The other, (7, is the line-integral ( -f 4?r) of the magnetic force round
either wire.
In the figure, AB and CD are the two wires, enormously shortened in
length compared with their distance apart, joined through terminal
resistances E0 and Rlt in the former of which alone is the impressed
force e. The fall of potential from A to C is F0, from B to D is V^
and at any intermediate distance is V. The total activity of the source
is eC, of which (e - V^C is wasted in J?0. What is left, or VQC, is the
energy-current at AC, entering the line. By regular waste into the
wires, its strength falls to V$ at BD, where the line is left, and the
96 ELECTRICAL PAPERS.
terminal arrangement entered, to be wasted in frictional heat-genera-
tion Eft2 therein, or otherwise disposed of. The curved lines and
arrows perpendicular to them show lines of electric force and the
direction of the energy-flux at a certain place, the inclination of the lines
of force to the perpendicular being greatly exaggerated, as well as that
of the lines of flux of energy to the horizontal, in order to show the
convergence of energy upon the wires, there to be wasted. Its further
transfer belongs to another science.
The rate of decrease of VG as we travel along the line is the waste
per unit length. Thus,
-~
Rl and R2 being the resistances of the wires per unit length. This is
in steady-flow, with no leakage. But if there be leakage, we have the
equation of continuity
making ,VC) = K^ + (Rl + R.2}C\ ................... (826)
where KV'1 is the waste-heat per second due to the leakage-resistance.
But when the state is not steady, we have the equation of continuity
V, ..................... (806) bis.
ctx
and the equation of electric force
F, ................. (736) bis.
dx
so that -(FC) = K^ + aSF^ + L0C2) + EC-FC. ...... (836)
dx ctt dt
Here we account for the leakage-heat, for the increase of electric
energy, and for the increase of magnetic energy in the dielectric by the
first, second, and third terms on the right side. EG, the fourth term,
represents the energy entering the first wire per second, E being the
tangential electric force; and - FC, the last term, represents the
energy entering the second wire per second, F being the tangential
electric force at its boundary reckoned the same way as E. The
energy-flux is now perpendicular to the current, i.e., after entering the
wires, ceasing when the axes are reached. And,
-FC=Q2 + Tv ................ (846)
if Cj, (J2, are the dissipativities, Tl and T2 the magnetic energies in the
two wires, per unit length of line.
If the impressed force is a S.H. function of the time, so is the
current, etc., everywhere, and
E = R(C+L{C, -F=R'2C+L2C, ............. (856)
where R{, Jft£, LJ(, and L2 are constants depending upon the frequency,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 97
reducing to the steady resistances and inductances when the frequency
is infinitely low. In this S.H. case
are the mean dissipativities and magnetic energies in the wires, 6'0
being the amplitude of the current ; the halving arising from the mean
value of the square of a sinusoidal function being half the square of its
amplitude. But in no other case is there anything of the nature of a
definite resistance, although, if the magnetic retardation to inward
transmission is small, we may ignore it altogether, and drop the accents
in (856).
SECTION XXXVI. RESISTANCE AND SELF-INDUCTION OF A ROUND
WIRE WITH CURRENT LONGITUDINAL. DITTO, WITH INDUCTION
LONGITUDINAL. THEIR OBSERVATION AND MEASUREMENT.
When the effective resistance to sinusoidal currents is not much
greater than the steady resistance, we may employ the formulae (445)
[p. 64], to estimate the effective resistance and inductance. On the
other hand, when it is a considerable multiple of the steady resistance,
we may employ the simple formulae (455). But in intermediate cases,
neither pair of formulae is suitable, and it therefore happens that in
some practically realisable cases we require the fully developed formulae
which are equivalent to (445), but are always convergent.
Let R be the steady resistance per unit length of round wire of radius
«, conductivity k, inductivity //, ; and Rf its effective resistance to sinu-
soidal currents of frequency q — njlir. Let also
(865)
Then the formula required for Rf is
*
*2 / ?2 /
z (1+ Z (1
4.3U4V 5.42.18V
(8U)
The law of formation of the terms is plainly shown, so that the series
may be continued as far as is necessary to ensure accuracy. But so far
as is written is quite sufficient up to z= 10.
The corresponding formula for L', what the L of the wire becomes at
the frequency q, is
Same denominator as in (875).
(888)
Here L = J/x, simply. R'jR increases continuously, and U/L decreases
continuously, as the frequency increases.
H.E.P. — VOL. n. a
98 ELECTRICAL PAPERS.
The following are the values of R'jR for values of z from J to 10 :—
z. R'IR. z. RjB.
i ............ 1-02 6 ............ 2-01
1 ............ 1-08 7 ............ 2-14
2 ............ 1-26 8 ............ 2-27
3 ........... 1-48 9 ............ 2-39
4 ............ 1-68 10 ............ 2-51
5 ............ 1-85
The curve, whose ordinate is R!\R - 1 and abscissa z, is convex to
the axis of abscissae up to about 2 = 2J, and then concave later.
Let us take the case of an iron wire of one-eighth of an inch in radius
(about No. 4 B.W.G.), of resistivity 10,000, and inductivity 100. These
data give us z = q/5I, by (866). Take, then, z = q/5Q. Each unit of z
means 50 vibrations per second. Then q — 50 makes R'jR = 1 -08 ;
th
= 500 makes 3=10 and B'/B = 2'51, or the effective resistance 2J
times the steady.
To obtain similar results in copper, with /*=!, ^*~1=1600, making
fjJc to be Jg- part of its former value, we require the radius to be four
times as great, or the wire to be 1 in. in diameter. But if it be of the
same diameter, q = 5QQ will only make £ = y§, and there will be only a
slight increase in the effective resistance.
In the present notation the very-high-frequency formulae are
R' = L'n = R(&y-t ......................... (896)
and, by comparison with the table, we shall be able to see how large z
must be before these are sensibly true. Using (896), £=4 gives R'jR
= 1*41, much less than the real value; 2 = 8 gives 2 instead of 2-274;
2=10 gives 2-234 instead of 2-507. On the other hand, (896) makes
L' too big, but not so much as it makes Rf too small. Thus q=W
makes L'n]R = 2-234 instead of 2-21, which is what the correct formula
(886; gives.
Probably z = 20 would make (896) fairly well represent the resistance,
as it nearly does the inductance when z= 10. In the case of the iron
wire above mentioned, 3 = 50, or <?=2500, will make the effective
resistance five times the steady.
If the wire be exposed to sinusoidal variations of longitudinal mag-
netic force by insertion within a long solenoidal coil, the effect, when
small, on the coil -current, is the same as if the resistance of the coil-
circuit were increased by the amount lR(t given by
(906)
[Reprint, vol. I., p. 369, the last equation. Also p. 364, equation (36).]
Here / is the length of the core and coil, having N turns of wire per
unit length, and
is the steady inductance, due to the core only, per unit of its length.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 99
If (70 be the amplitude of the coil-current, the mean rate of generation
of heat in the core is £/£'C70-, per unit of its length.
When the effect is large, use the formula
[vol. I., p. 364, equation (36), and the next one.] (I have slightly
changed the notation to suit present convenience, and show the law of
formation of the terms. The old y equals the new 16^2.)
I did not give any separately developed expression for the L{ corre-
sponding to LI ; being only a portion of the L of the circuit it was
merged in the expression for the tangent of the phase-difference. [Vol.
i., pp. 369 to 374, §§ 16, 17.] Exhibiting now L{ by itself, we have
this formula : —
L(
L^ Same denominator as in (916).
Notice that the numerators in (916) and (886) are the same, and that
those of (926) and (876) are the same.
At the frequency 500, using the same iron wire above described, we
have, taking z= 10 in (916) and (926),
^'=-188J>, ^ = -225^ ................ (936)
Or, with a little development,
^' = 622^ = 243,000 N*, ..................... (946)
i.e., the extra resistance is 243 microhms multiplied by the length of
the core, and by the square of the number of windings per unit length.
At this particular frequency the amplitude of the magnetic force
oscillations at the axis of the core is only one-fourteenth of the
amplitude at the boundary. When it is the current that is longitudinal,
it is the current-density at the axis that is only ^ its boundary -value.
Now, as cores may be so easily taken thicker, it is also desirable to
have the high-frequency formulae corresponding to (916) and (926),
which I now give. They are
(956)
The value 2=10 is scarcely large enough for their applicability.
Thus (956) give (same iron wire),
R! = L{n = "2'23Llnt ......................... (966)
instead of (936), making E{ too big, and L{ too small, although the
latter is nearly correct.
In one respect the reaction of metal in the magnetic field on a coil-
current is far simpler than the reaction on itself when it contains the
impressed force in its own circuit. If we have a sinusoidal current in
a coil, subject to >
100 ELECTRICAL PAPERS.
e being the sinusoidal impressed force, C the current, R and L the steady
resistance and inductance of the circuit ; and we, by putting metal in
its magnetic field, induce currents in it, and waste energy there, we
know that the new state is also sinusoidal, subject to
where Er and U have some other values. So far is elementary. This,
however, is also elementary, that R' must be greater than R. For the
heat in the coil per second is \RG$, and the total heat per second is
\R,'Gl. As the latter includes the heat externally generated, Rf is
necessarily greater than R. But this simple reasoning, without any
appeal to abstrusities, breaks down when it is the wire itself in which
the change from R to Rf takes place, and we then require to use
reasoning based upon the changed distribution of current.
To observe these changes qualitatively is easy enough. But to do so
quantitatively and accurately is another matter. It cannot be done with
intermittences. A convenient little machine giving a strictly sinusoidal
impressed force of good working strength, adjustable from zero up to
very high frequencies, is a thing to be desired. But we may employ
very rapid intermittences with an approximation to the theoretical
results. I have obtained the best results with a microphonic contact,
without interruptions, but it was difficult to keep it going uniformly.
Slow intermittences give widely erroneous results, i.e., according to the
sinusoidal theory, which does not apply, making the changes in resistance
and induction much too large. Here, of course, the silence — the best
minimum to be got — is a loud sound.
I should observe, by the way, that a correct method of balancing is
presumed. In Prof. Hughes's researches, which led him to such re-
markable conclusions, the method of balancing was not such as to ensure,
save exceptionally, either a true resistance or a true induction balance.
Hence, the complete mixing up of resistance and induction effects, due
to false balances. And hidden away in the mixture was what I termed
the " thick-wire effect," causing a true change in resistance and inductance
[vol. II., p. 30]. In fact, if I had not, in my experiments on cores and
similar things, been already familiar with real changes in resistance and
inductance, and had not already worked out the theory of the pheno-
menon of approximation to surface conduction [first general description
in vol. L, Art. 30, p. 440 ; vol. II., p. 30], on which these effects in a
wire with the current longitudinal depend, it is quite likely that I should
have put down all anomalous results to the false balances.
Of course, we should separate inductance from resistance. Perhaps
the simplest way is that I described [vol. n., p. 33, Art. xxxiv.] of
using a ratio of equality, reducing the three conditions to two, ensuring
independence of the mutual induction of sides 1 and 2, and also of
sides 3 and 4 (allowing us to wind wires 1 and 2 together, and so
remove the source of error due to temperature inequality which is so
annoying in fine work), and requiring us merely to equalise the resist-
ances and the inductances of sides 3 and 4, varying the inductance to
the required amount by means of a coil of variable inductance, con-
ELECTROMAGNETIC INDUCTION AN# ITS-'P^OtAXrA'TlON. 101
sisting of two coils joined in sequence, one of which is movable with
respect to the other, thus varying the inductance from a minimum to a
maximum — an arrangement which I now call an Inductometer, since it
is for the measurement of induction. The oddly-named Sonometer
will do just as well, if of suitable size, and its coils be joined in
sequence. The only essential peculiarity of the inductometer is the
way it is joined and used. This method of equal ratio was adopted by
Prof. Hughes in his later researches (Royal Society, May 27, 1886) ; he,
however, varies his induction by a flexible coil, which I hardly like.
Lord Rayleigh has also adopted this method of separating induction
from resistance, and of varying the inductance. (Phil. Mag., Dec.,
1886.) I found that the calibration could be expeditiously effected
with a condenser, dividing the scale into intervals representing equal
amounts of inductance. Lord Kayleigh does, indeed, seem to approve
somewhat of Prof. Hughes's method, with its extraordinary complica-
tions in theoretical interpretation (very dubious at the best, owing to
intermittences not being sinusoidal). But if it be wished to employ
mutual induction between two branches to obtain a balance, there is
the M63 or MM method I described [vol. IL, Art. xxxiv.], which is,
like the method of equal ratio, exact in its separation of resistance and
inductance, with simple interpretation. I have since found that there
are no other ways than these, except the duplications which arise from
the exchange of the source of electricity and the current indicator.
Using any of these methods, we completely eliminate the false balances ;
now we shall have perfect silences, independent of the manner of
variation of the currents, whenever the side 4 [in figure, p. 33, vol.
II.], containing the experimental arrangement, is equivalent to a coil,
with the two constants R and L, and can therefore equalise a coil in side
3 (presuming that the equal-ratio method is employed). But if in the
equation V=ZG of the experimental wire, Z is not reducible to the
form of R + L(d/dt), it is not possible to make the currents vary in the
same manner in the sides 3 and 4, and so secure a balance. That is,
we cannot balance merely by resistance and self-induction, the departure
of the nearest approach to a balance from a true balance being little or
great, as the manner of variation of the current in side 4 differs little
or much from that of the current in its ought-to-be equivalent side 3.
The difference is great when a coil with a big core is compared with a
coil without a core ; and, as in all similar cases, as before remarked, at a
moderate rate of intermittence, we must not apply the sinusoidal theory
to the interpretation. If we want to have true balances when there is
departure from coil-equivalence, we must specialise the currents, making
them sinusoidal. Then we can have silences, and correctly interpret
results. We appear to have false balances. But they are quite dif-
ferent from the before-mentioned false balances, as they indicate true
changes in resistance and inductance, owing to the reduction of Z to
the required form, in which, however, the two "constants " are functions
of the frequency.
102 ELECTRICAL PAPERS.
SECTION XXXVII. GENERAL THEORY OF THE CHRISTIE BALANCE.
DIFFERENTIAL EQUATION OF A BRANCH. BALANCING BY MEANS
OF REDUCED COPIES.
It is not easy to find a good name for Mr. S. H. Christie's differential
arrangement. There are objections to all the names bridge, balance,
lozenge, parallelogram, quadrangle, quadrilateral, and pans asinorum,
which have been used. It seems to be a nearly universal rule for
words, used correctly in the first place, to gradually change their
meaning, and finally cause us to talk nonsense, according to their
original signification. Thus the Bridge is the conductor which bridges
across two others. But it has become usual to speak of the differential
arrangement as a whole as the Bridge ; and then we have the four
sides of the bridge, which is absurd. Quadrilateral is the latest fashion.
It has four sides, truly. But there are six conductors concerned ; so
we should not call the differential arrangement itself the quadrilateral.
I propose to simply call it the Christie, without any addition, just as
telegraphers speak of the Morse, or the Wheatstone, meaning the
apparatus taken as a whole. Thus we can refer to the Christie, the
quadrilateral, and the bridge, the latter two being parts of the former.
This will suppress the farrago.
In the usual form of the Christie we have four points, A, Bj, B2, C,
united by six conductors, numbered from 1 to 6 in the figure. The
Quadrilateral has the four sides, 1, 2, 3, 4. The bridge-wire is 5,
joining Bx to B2, and 6 is the battery-wire. The battery-current goes
from A to C by the two distinct routes ABjC and AB2C. Some of it
crosses the bridge, up or down ; except under special circumstances,
when the bridge-wire is free from current, which is the useful property.
Let us generalise the Christie thus : — Let the sole characteristics of
a branch be that the current entering it at one end equals that leaving
it at the other, with the additional property that the electromagnetic
conditions prevailing in it are stationary, so that the branch becomes
quite definite, independent of the time.
Thus, all six branches may be any complex combinations of con-
ductors and condensers satisfying these conditions. The communica-
tion between the two ends of a branch need not be conductive at all ;
for example, a condenser may be inserted. As an example of a complex
combination, let branch 3 consist of a long telegraphic circuit, symbolised
by the two parallel lines starting from 3 and ending at Y3, where they
are connected through terminal apparatus. This branch then consists
of a long series of small condensers, whose + poles are all connected
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 103
together by one wire, and the - poles by the other wire. There is
also conductive connection (by leakage) between the two wires. There
is also electromagnetic induction all along the line. But, as the
current entering the line from Bx to 3, and that leaving it, from 3 to
C, are equal, the telegraphic line comes under our definition, provided
it be stationary in its properties. Observe that this does not exclude
the presence of other conductors, between which and the line in branch
3 there is mutual induction, providing this does not disturb our
fundamental property of a branch. We may, indeed, remove the
original restriction, but then it will no longer be the Christie, for more
than four points will be in question. Suppose, for example, there is
mutual induction of the electrostatic kind between branches 1 and 2,
which is most simply got by connecting the middles of 1 and 2, taken
as resistances, through a condenser. Then there are six points, or
junctions, concerned, and a slight enlargement of the theory is required.
Let us now inquire into the general condition of a balance, or of no
current in the bridge-wire due to current in 6, which, therefore, enters
the quadrilateral at A and leaves at C, and which may arise from
impressed force in 6 itself, or be induced in it by external causes.
First, as regards the self-induction balance in the extended sense.
This does not mean that each side of the quadrilateral must be
equivalent to a coil, but merely that the four sides are independent of
one another in every respect, except in being connected at A, BI} B2, C.
Thus we can have electrostatic and electromagnetic induction in all six
branches, but independently of one another. Under these circumstances
it is always possible to write the differential equation of a branch in the
form V=ZC, where C is the current (at the ends), V the fall of
potential from end to end, and Z a differential operator in which time
is the independent variable. When the branch is a mere resistance R,
then Z=R, simply. When it is a coil, independent of all other con-
ductors, then
where L is the inductance of the coil, and p stands for d/dt. When it is
a condenser, then Z=(Sp)~l, where Sis the capacity. If the condenser
have also conductance K, or be shunted by a mere resistance, then
Z=(K+Sp)-\
These are merely the simplest cases. In general, Z is a, function of
p, p2, etc., and electrical constants.
Now let the positive direction of current be from left to right in
sides 1, 2, 3, 4, and suppose we know their differential equations
V^ = Z£v V^Zfiy etc.
To have a balance, so far as the current from 6 is concerned, the
potentials at Bj and B2 must be always equal, except as regards
inequalities arising from impressed forces in other branches than 6,
with which we are not concerned. Therefore
Fi = F2, and K3=F4,
or, ZCZV and Z, = Z
104 ELECTRICAL PAPERS.
But, c^Cy a2=c4.
So, using these in (Ic), we get
Eliminate the currents by cross-multiplication, and we get
ZJ^Z^, .............................. (3c)
which is the condition required. It has to be identically satisfied, so
that, on expansion, the coefficient of every power of p must vanish.
If we take Z=E + Lp (as when each side is a coil, or equivalent to
one), we obtain the three conditions given in my paper " On the Use
of the Bridge as an Induction Balance, equations (1), (2), (3) [vol. IL,
Art. xxxiv., p. 33].
As another example, take Z = (K + Sp) ~ l (shunted condensers), and
we obtain three similar conditions. But it is needless to multiply
examples here. We have only to find the forms of the four Z*s, expand
equation (3c), and equate to zero separately the coefficient of every
power of p. It does not follow that a balance is possible in a particular
case, but our results will always tell us how to make it possible, as by
giving zero values to some of the constants concerned, when one branch
is too complex to be balanced by simpler arrangements in other
branches.
The theory of a balance of self and mutual electromagnetic induction
I propose to give by a different and very simple method in the next
Section. At present, in connection with the above generalised self-
induction balance, let us inquire how to balance telegraph lines of
different types, or when they can be simply balanced. It is clear, in
the first place, that if we choose sides 1 and 3 quite arbitrarily, we
have merely to make side 2 an exact copy of side 1, and 4 an exact
copy of side 3, in order to ensure a perfect balance. Imagine the
bridge- wire to be removed ; then we have points A and C joined by
two identical arrangements. The disturbances produced in these by
the current from 6 must be equal in similar parts • hence, if Bl and B2
be corresponding points, their potentials will be always equal, so that
no current will pass in the bridge-wire when they are connected. But
we can also get a true balance when the " line " AB2C is not a full-
sized, but a reduced copy of the line AB1C. It is not the most general
balance, of course, but is still a great extension upon the balance by
means of full-sized copies. The general principle is this :—
Starting with sides 1 and 3 arbitrary, make 2 and 4 copies of them,
first simply qualitatively, as it were ; thus, a resistance for a resistance,
a condenser for a condenser, and so on. This is like constructing an
artificial man with all organs complete, but in no particular proportion.
Then, make every resistance in sides 2 and 4 any multiple, say s times
the corresponding resistance in sides 1 and 3. Make every condenser
in sides 2 and 4 have, not s times, but s~l times the capacity of the
corresponding condenser in sides 1 and 3. And, lastly, make every
inductance in sides 2 and 4 be s times the corresponding inductance in
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 105
sides 1 and 3. This done, s being any numeric, AB2C is made a
reduced (or enlarged) copy of ABTC, and there will be a true balance.
That is, the potentials at corresponding points will be equal, so that
the bridge-wire may connect any pair of them, without causing any
disturbance.
Now let a telegraph line be defined by its length I, and by four
electrical constants R the resistance, S the electrostatic capacity, L the
inductance, and K the leakage-conductance, all per unit length. It is
not by any means the most general way of representation of a telegraph
line, but is sufficient for our purpose. Let C be the current, and /^the
potential-difference at distance x from its beginning. We require the
form of Z in V=ZC at its beginning. This will depend somewhat
upon the terminal conditions at the distant end, so, in the first place
let V= 0 there. Take
(4e)
- cosmx.B), ............ (5c)
(6c)
p standing for djdt as before. These are general, subject to no im-
pressed forces in the line. A and B are arbitrary so far. But at the
end x = lt we have V= 0 imposed, which gives, by (5c),
B/A=tznml, .............................. (7c)
so that at the x = Q end, we have, by (4c), (5c), and (7c),
...(8.)
.
C m A ml
This is the Z required. From the form of m2, we see that if the total
resistance El and total inductance LI in one line be, say, s times those
in a second, whilst the total capacity SI and total leakage-conductance
Kl in the second line are s times those in the first, then the values of
ml are identical for the two lines. If these lines be in branches 3 and
4, we therefore have
so that we may balance by making sides 1 and 2 resistances whose
ratio jRj/jRj is s ; or, if coils be used, by having, additionally, LJL2 = s ;
or, if condensers are used, (K2 + S2p)/(K1 + Slp)=s; and so on.
But if there be apparatus at the distant end of the line, it must also
be allowed for. Let V— YC\)e the equation of the terminal apparatus;
that is, this equation connects (4c) and (5c) when x = L Using it,
instead of the former V= 0, we shall arrive at
tan ml + mYj(R + Lp) /10 ,
m
instead of (8c). Now, just as before, adjust the constants of lines 3
and 4, so that w3/3 = w4/4, and, in addition, make YJY4 = s. Then,
106 ELECTRICAL PAPERS.
supposing each side of the quadrilateral to be a telegraph line, the full
conditions of balance by this kind of reduced copies are
O0'o -**2 2 1
"~ ~v'T ~ ~v~9
r/,1 Y* \ ("")
J- Q
Z,4/4 $3/3 £3/3 F4
The difference from the former case is that we now have in sides 2
and 4 reduced copies of the terminal apparatus of lines 1 and 3. It
will be observed that the equalities in the first line of (lie) make side
2 a reduced copy of side 1, and that those in the second line make side
4 a reduced copy of 3, whilst the equalisation of the two lines of (He)
makes the scale of reduction the same, so that AB2C is made a reduced
copy of ABjC.
If one of the four sides, say side 3, of the quadrilateral be a telegraph
line, we must have at least one other telegraph line, or imitation
line, namely, in side 4. But, of course, sides 1 and 2 may be electrical
arrangements of a quite different type. Further, notice that only two
of the sides, either 1 and 2, or 3 and 4, can be single wires with return
through earth, so that if the other two are also to be telegraph lines
they must be looped, or double wires. In certain cases precisely the
same form of Z as that above used will be valid, but this is quite
immaterial as regards balancing by means of a reduced copy.
The balance expressed by equation (3c) is exact- -that is, it is inde-
pendent of the manner of variation of the current. The balance by
means of reduced copies is also exact, but is only a special case of the
former. But there is always, in addition, the periodic or S.H. balance,
when the currents are undulatory. Then merely two conditions are
required, to be got by putting p2= -n2, where n/'2ir is the frequency,
in Z^Z± - Z2Z3. which will reduce it to the form a + bp, in which a and b
contain the frequency. Now, a = 0 and b - 0 specify this peculiar kind
of balance, which is, generally speaking, useless. Whilst, however, the
balance of ABXC and AB2C by making the latter a reduced copy of the
former is, when applied to the Christie, only a special case of (3c), it is,
in another respect, far more general ; for it will be observed that any
pair of corresponding points may be joined by the bridge-wire, although
the result may be an arrangement which is not the Christie.
SECTION XXXVIII. THEORY OF THE CHRISTIE AS A BALANCE OF
SELF AND MUTUAL ELECTROMAGNETIC INDUCTION. FELICI'S
INDUCTION BALANCE.
As promised in the last Section, I now give a simple, and, I
believe, the very simplest, investigation of the conditions of balance
when all six branches of the Christie have self and mutual induction.
Referring to the same figure (in which we may ignore the extensions
of branches 3 and 4 to Y3 and Y4), we see that as there are six branches
there are twenty -one inductances, viz., six self and fifteen mutual.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 107
This looks formidable. But since there are only three independent
currents possible there can really be only six independent inductances
concerned, viz., three self and three mutual, each of which is a com-
bination of those of the branches separately.
Thus, let Gj, C3, and C6 be the currents that are taken as independent,
and let them exist in the three circuits ABXB2A, CB2B1C, and AB2CA
(via branch 6), with right-handed circulation when positive. Then the
other three real currents Gy2, GY4, and C5 are given by
if the positive direction be from left to right in sides 1, 2, 3, and 4,
from right to left in 6, and down in 5, which harmonises with the
positive directions of the cyclical currents C\, GY3, and G'6.
B,
Next, let mv m3, m6, and m13, w36, m61 be the inductances, self and
mutual, of the three circuits. Thus, m1 — induction through ABjB2A
due to unit current in this circuit; and m13 = the induction through
CBgBjC due to the same, etc. We have to find what relations must
exist amongst the resistances and the inductances in order that there
may never be any current in the bridge-wire, provided there be no
impressed forces in 1, 2, 3, 4 or 5.
We obtain them by writing down the equations of E.M.F. in the two
circuits ABjB2A and CB^C on the assumption that there is no
current in the bridge-wire, which requires Cl = C3; and this we do
by equating the E.M.F. of induction in a circuit, or the rate of decrease
of the induction through the circuit, to the E.M.F supporting current,
which is the sum of the products of the real currents into the resistances,
taken round the circuit.
Thus,
-pim^ + ml5C3 + m1QC6] = E1Cl - R2(C6 - C'1),| (1 g ,
-p(m3C3 + ro81Ci + m63<76) = R3C3 - R4(C6 - CB)J' '
where p stands for d/dt. But Cl = Cg, which, substituted, makes
x + mlB)p} C'1 = (5a - ml6p)C6^
{ (E3 + E,) + (m, + ml3)p} C, = (R, - m36p}CJ' '
which have to be identically satisfied. Eliminate the currents by cross-
multiplication, and then equate to zero separately the coefficients of
the powers of p. This gives us
(m, + ml3 + ml6)fi4 - m^ = (m3 + m3l
108 ELECTRICAL PAPERS.
which are the conditions required. First the resistance balance ; next
the vanishing of integral extra-current due to putting on a steady
impressed force in branch 6 ; and the third condition to wipe out all
trace of current, and make branches 5 arid 6 perfectly conjugate under
all circumstances.
If the Christie consists of short wires, which are not nearly closed in
themselves, then, as I pointed out before [vol. IL, Art. 34, p. 37], the
theory of the balance expressed in terms of the self and mutual in-
ductances of the different branches becomes meaningless, because the
inductances themselves are meaningless. Under these circumstances,
equations (14c) are the conditions of a balance, from which alone can
accurate deductions be made. Even if we have the full equations in
terms of the twenty-one inductances of the branches, they will express
no more than ( 1 4c) do. We could not, for instance, generally assume
any one of the inductances to vanish, as it would produce an absurdity,
viz., the consideration of the amount of induction passing through an
open circuit. Hence it is quite possible that (14c) may be useful in
certain experiments, in which such short wires are used that terminal
connections become not insignificant.
At the same time it is to be remarked that such cases are quite
exceptional. I would not think, for example, of measuring the in-
ductance of a wire a few inches long, in which case (14c) would,
at least in part, be applicable, if I could get a long wire and swamp the
terminal connections. Still, however, equations ( 1 4c) and the way they
are established are useful in another respect. In general, I have not
found any particular advantage in Maxwell's method of cycles.* It has
seemed to me to often lead to very roundabout ways of doing simple
work, from what I have seen of it. This applies both when the steady
distribution of current in a network of conductors is considered, due to
steady impressed forces, as in the original application ; and also when
the branches are not treated as mere resistances, but transient states
are considered, provided the branches be independent, so that, as I
remarked before, the equation of a branch may be represented by
V=ZC, where Z takes the place of R, the resistance in the
elementary case. But in our present problem there is such a large
number of inductances that there is a real advantage in using the
above method, an advantage which is non-existent in a problem
relating to steady states. We greatly simplify the preliminary
work by reducing the number of inductances from 21 to 6. But,
of course, on ultimate expansion of results we shall come to the
same end.
If we use the first and third of (14c) in the second, it becomes
and, as either of these factors may vanish, we have in general two
entirely distinct solutions. If the second factor vanish, the whole
* [Not given in his treatise, but described by Dr. Fleming in the Phil. Mag. ]
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 109
set of conditions may be written
-Lv-t Xt;) Wl/l a ills-\ \ 'Tils-to /IS* \
ft=£=:itl m •' ( ^
whilst, if it be the first factor that vanishes, we shall have
RZ ^4 "V.l W«8
expressing the full conditions. Both (16c) and (17 c) are included
in (14f).
Suppose now that we make the branches long wires, or coils of wire,
or many coils in sequence, etc., and can therefore localise inductances
in and between the branches. We require to expand the six wi's.
Their full expressions will vary according to circumstances. When all
the twenty-one inductances are counted, they are given by
//<•! = Zrj + Z»5 + L2 + 2(Jtfu - M25 - M12), \
ms = L3 + L4 + Lr0+ 2(M45 — M34 - M^),
•///,., = L6 + L2 + L/i + 2(Jf62 + ^64 + ^34)1
m!3 = " ^5 + (^13 ~ -^14 " ^15 " ^23 + ^24 + ^25 + ^53 ~ -^54)
Here L stands for the inductance of a branch, and M for the mutual
inductance of two branches. These are got by inspection of the figure,
with careful attention to the assumed positive directions of both the
cyclical and the real currents.
In the use of these, for insertion in (14c), we shall of course equate
to zero all negligible inductances. As an example of a very simple
case, let coils be put in branches 4 and 6, between which there is
mutual induction, and let the other four branches be double-wound or
of negligible inductance. Then all except L4, LQ, and M46 are zero,
giving
ml =0, ra3 =Z4, w6 = Z4 + 2M64,
ml3 = 0, m16 = 0, mm = - Z4 - M^.
Insert these in the second of (14c), and we get
R^L± + M^)=-M^R» or -L, = (l +JKJSl)M4A. ...(19c)
The third condition is nugatory. Hence (19c), with a resistance
balance, but without the need of measuring 7?3 (or, equivalently, 7?4),
gives us the ratio of the M of two coils to the L of one of them in terms
of the ratio of two resistances.
As another example, let all the M' s be zero except M12 and M3±,
whilst all the Z's are finite. We shall then have, besides the resistance
balances, the two conditions
0 = (L,L, - L2L3) + (L, - LJMu + (LB - Lt)Mw \
0 = - - - - ^
If we now take R^ = AJ2, L^ = L2 ; that is, let sides 1 and 2 be equal,
110 ELECTRICAL PAPEKS.
we reduce the three conditions (14c) to RZ = R±, Z3 = Z4. This is
obvious enough in the absence of mutual induction ; but we also see
that induction between sides 1 and 2, and between 3 and 4, does not in
the least interfere with the self-induction balance Whilst remarkable,
this property is of great utility. For it allows us to have the equal
wires 1 and 2 close together, preferably twisted, and then this double
wire may be doubled on itself, and the result wound on a bobbin. We
ensure the equality of the wires at all times, doing away with the
troublesome source of error arising from the disturbance of the resist-
ance balance from temperature changes, which occur when 1 and 2 are
separated, and also doing away with interferences from induction
between 1 and 2 and the rest. We also do away with the necessity of
keeping coils 3 and 4 widely separated from one another.
Passing to a connected matter, Maxwell, Vol. II., Art. 536, describes
the well-known mutual induction balance with which Felici made such
instructive experiments, that may be made the basis of the science of
electromagnetic induction. It is very simple and obvious. The figure
explains itself. If the M of the two circuits is nil, there is no current
in the secondary on making or breaking the primary. This is secured
when the M of coils 1 and 2 is cancelled by the M of coils 3 and 4, pre-
suming that the pair 1, 2 is well-removed from the pair 3, 4.
The balance is independent of the self-inductions of the four coils,
and also of the resistance of the two circuits, and may be made very
sensitive. In fact, Felici's balance is unique, and should be used when-
ever possible. To exhibit its merits fully, we should use a telephone
and automatic intermitter, giving a steady tone. It is then doubly
unique, and it is difficult to imagine anything better. Compared with
the galvanometer, the use of the telephone is a real pleasure. It is
science made amusing.
But if we want not merely to balance Mlz against M34, but to know the
value of the Mu of a given pair of coils, Mu should be both variable and
known. Coils 3 and 4 may be the coils of an inductometer [vol. II., p.
101] calibrated once for all. There are many ways of doing it, in terms of
the capacity of a condenser, or in terms of the inductance of a coil, etc.,
none of which methods has the merits of Felici's balance. Suppose it
done by Maxwell's condenser method (using a telephone, of course).
It is, perhaps, as good as any (certainly better than many) for the par-
ticular purpose, as we have only to give particular values to the time-
constant of the condenser — a series of values with a common difference —
and get silence at once by moving the pointer to a series of particular
places, which is very different from dodging about to find the value of
the time-constant when the M of the coils is fixed. We should also
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. HI
measure the L of each coil by itself, and it is well to previously adjust
the coils to have equal L and R. But the present use of the inducto-
meter is not to measure self induction, but mutual induction. There-
fore make 1 and 2 the coils whose M is wanted, 3 and 4 the coils of the
inductometer. If within range (it is well to have inductometers of
different sizes, for various purposes), we immediately measure M12, and
have the full advantages of Felici's balance.
But if there is metal about the coils 1 and 2 (of course there should
be none, or very little, about the inductometer, or it should be carefully
divided), we cannot get telephone balances. If the departure from
balance is serious, and it is not practicable to remove the metal, we may
give up the telephone and use a suitable galvanometer, one whose
needle will not move till all the current due to a make has passed, and
then move if it can. But if the metal be iron, and we want to measure
the steady M in presence of the iron (not finely divided), of course we
must not remove the iron and measure something else than what we
want to know. Then the galvanometer is indispensable. We lose the
advantage of the telephone, but Felici's balance has still its peculiar
merits left, in a very great measure.
Apart from the question of measurement, Felici's balance is highly
instructive, as to which see Maxwell's treatise, to which we should add
that the telephone should always be used if possible. Besides the
experiments referred to, the balance is useful for studying the influence
of iron in the field on the M of two coils, increasing or decreasing it,
according to position. Use non-conducting iron [vol. II., Art. 36, later].
Here we have another proof to that there mentioned, that there is no
appreciable waste of energy in finely divided iron when the range of
the magnetic force is moderate, although very perfect silences, like those
when there are no F. currents, and no iron, are not always obtainable.
As regards Felici's balance when employed for observing differential
effects, e.g., Prof. Hughes's magical experiments with coins, and so
forth, I cannot recommend it, for several reasons. The theory is com-
plex, in the first place, so that scientific interpretation of results is
difficult. Next, considerable accuracy in adjustment of the coils, in
two equal pairs, similarly placed, is required. Lastly, the independence
of resistance, etc., ceases when there are F. currents to disturb ; and as
we are not able to trace the variations of resistance, we may, in
sensitive arrangements, when balancing one set of F. currents and
reactions against another set, be interfered with by unknown tempera-
ture variations.
Perhaps the easiest way is to take a long wire, double it on itself and
then double again, giving four equal wires. Wind two side by side to
make one pair of coils (1 and 2), and the others in the same manner, to
make the other pair. Of course we have increased sensitiveness by
the closeness of the wires.
But it is far better not to use four coils, but only two, viz., coils 3
and 4 in the equal-sided se//-induction balance, with 1 and 2 made per-
manently equal, as before described. The temperature error is then
under constant observation, and we know at once when the resistance
112 ELECTRICAL PAPERS.
balance of coils 3 and 4 (apart from F. currents) is upset. Inter-
pretation is also an easier matter, both in general reasoning and in
calculations.
SECTION XXXIXa. FELICI'S BALANCE DISTURBED, AND THE
DISTURBANCE EQUILIBRATED.
Referring to the last figure, in which imagine the galvanometer to be
replaced by a telephone, and the key by an automatic intermitter, let
us start with a perfect balance due to the M of one pair of coils being-
cancelled by the M of the other pair, and consider the nature of the
effects produced by the presence of metal in or near either pair of coils.
First, let 3 and 4 be the coils of an inductometer, and 1, 2 other
coils of any kind, separate from one another. The simplest action is
that caused by non-conducting iron. It acts to increase or decrease
the M of either or both pairs of coils according to its position with
respect to them, and its effect can be perfectly balanced by a suitable
increase or decrease of the M (mutual inductance) of the inductometer
coils. Suppose, for example, the disturber is a non-conducting iron
bullet, and is brought into the field of the coils 1, 2. If it be inserted
in either coil, it increases their M. This is mainly because it increases
the L of the coil in which it is inserted. If the two coils have their
axes coincident, as in the figure, the bullet will cause their M to be
increased by placing it anywhere on the axis, or near it. But if the
bullet be brought between the coils laterally, so as to be, for instance,
between the numerals 1 and 2 in the figure, the result is a decreased M.
Here the L of each coil is little altered, and the decrease of M results
from the lateral diversion of the magnetic induction by the bullet from
its normal distribution. By pushing it in towards the axis a position
of minimum M is reached, after which further approach to the axis
causes M to increase, ending finally on the axis with being greater than
the normal amount.
If the disturber be a non-conducting core (round cylinder), the
greatest increase of M is, of course, when it is pushed through both
coils, which are themselves brought as close together as possible, and
when the core itself is several times as long as the depth of the coils.
M is then multiplied about four times when the coils are about of the
shape shown, with internal aperture about J the diameter of the coils.
If the coils be wound parallel on the same bobbin, the increase is much
greater. If the whole space surrounding the coils be embedded in iron
to a considerable distance, we shall approach the maximum M possible.
The effective inductivity of the non-conducting iron is considerably
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 113
less than that of solid iron, which counterbalances the freedom from
F. currents.
Using solid iron, no silence is possible, owing to the F. currents,
although there is a more or less distinctly marked minimum sound
for a particular value of M. The substitution of a bundle of iron
wires reduces this minimum sound, and when the wires are very
fine, it is brought to comparative insignificance ; but only by very fine
division of iron are the F. currents rendered of insensible effect. It
will be, of course, remembered that the range of the magnetic force
variations must be moderate, so as to render the variations in the
magnetic induction strictly proportional to them, otherwise no perfect
balance is possible with non-conducting iron.
On the other hand, non-conducting (i.e., very finely divided) brass
(or presumably any other non-magnetic metal) does nothing. Dia-
magnetic effects are insensible. The above remarks apply, for the most
part, equally well to the self-induction balance, except that iron always
increases the L of a coil.
So far is very simple. It is the effect of the conductivity (in mass)
of the disturbing matter that makes the interpretation of results
troublesome. If the disturber be non-magnetic, we have a secondary
current due to the action on the secondary circuit of the current induced
in the disturber by the primary current ; at least I suppose that this is
the way it might be popularly explained. If the disturber be not too
big, the M of the inductometer which gives the least sound (instead of
silence) is sensibly the old value which gave silence before its intro-
duction. If it be magnetic, there is usually increased M also. Changing
the M of the inductometer to suit this, the minimum sound is still far
louder than with an equally large non-magnetic disturbing mass
(metallic) because the F. currents are so much stronger in iron. To
this an exception is Prof. Bottomley's manganese-steel of nearly unit
inductivity, in which the F. currents should be, and no doubt are, far
weaker than in copper, on account of the comparatively low conduc-
tivity. If this be not so, then it must be found out why not. Again,
if the iron be independently magnetised so intensely as to reduce the
effective inductivity sufficiently, then, as I pointed out in 1884, the F.
currents should be made less than in copper.
To obtain an idea of the disturbance in the secondary circuit due to
a conducting mass, let it be a simple linear circuit, and call it the
tertiary. Let the suffixes l and 2 refer to the primary and secondary
circuits, and 3 to the tertiary. Then the equations of E.M.F. are
0= Z2C2 + M23pC3, V (21c)
where Z=R + Lp, and e is the impressed force in the primary. Here
M12 is missing, it being supposed to be properly adjusted to be zero.
From these,
alVJ.-tnlVJ.nnp 6 /99/»\
2== Z (Z Z -M*v% " lt/r9-9
H.E.P. — VOL. II. H
114 ELECTRICAL PAPERS.
is the secondary current's equation. The secondary current therefore
varies as the product of the M of the tertiary and primary into the M
of the tertiary and secondary. It is therefore made greatest by making
coils 1 and 2 in the figure coincident (practically) by double-winding,
and putting the disturber in their centre. In this case, let R and L be
the resistance and inductance of the primary and also of the secondary
circuit, r and / those of the tertiary, and m the former MIB or 3f23, now
equal. Then (22c) becomes, if z = r + Ip,
m v
But m is very small compared with L, so
C*-^
Let the impressed force be sinusoidal ; then p2 = - w2, making
Let R = Ln, which condition is readily reached approximately. Then
/9A v
(2<
gives the secondary current in amplitude, (m*n/2EL)(r2 + I2n2)~^ per unit
impressed force, and phase. If the tertiary could have no resistance,
the secondary current would be of amplitude m2/2RLl per unit impressed
force, and in the same phase with it.
Now seek the conditions of balance by means of a fourth linear
circuit placed between coils 3 and 4 in the figure, supposed to be
exactly like coils 1 and 2. Let the suffix 4 relate to this fourth
circuit. Then (21c) become
Here, besides Mlv M^ is also missing, because of the distance between
the two disturbers. From these,
(28c)
is the euation of (7 where ^ is the determinant of the coefficients in
gives
/9Q/.\
is the equation of (72, where ^ is the determinant of the coef
(27c). For a balance, the coefficient of e must vanish. This
tlt
If the coils of each " transformer" are coincident and equal, M3l
and M41 = - 3f42 ; and, the M' s being small, (28c) becomes
where Z is that of either the primary or secondary circuit.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. H5
We do not need to balance the disturber in one pair of coils by means
of a precise copy of it in the other pair, similarly placed. It may be a
reduced copy, according to (29c).
SECTION XXXIX6. THEORY OF THE BALANCE or THICK WIRES,
BOTH IN THE CHRISTIE AND FELICI ARRANGEMENTS. TRANS-
FORMER WITH CONDUCTING CORE.
This brings me to the subject of balancing rods against one another,
either in the Christie or in the Felici differential arrangements, when
placed in long solenoids ; and to the similar question of balancing thick
wires in the Christie, when the current in them is longitudinal. As I
pointed out before [vol. II., p. 37], if a wire be so thick that the effect of
diffusion is sensible, it cannot be balanced in the Christie against a fine
wire, but requires another thick wire in which the diffusion effect also
occurs. I refer to true balances, independent of the manner of variation
of the current, in which, therefore, the resistance of the one wire,
though different at every moment, is yet precisely that of the other
wire (or any constant multiple of it). Perhaps the best way to define
the resistance is by Joule's EC'2. In the sinusoidal case a mean value
is taken. According to this heat-generation formula, there always is a
definite resistance at a particular moment, but what it may be will
require elaborate calculation to find. This definition of the resistance
to suit the instantaneous value of the dissipativity does not agree pre-
cisely with the sinusoidal R', which represents a mean value ; but the
sinusoidal R' has important recommendations which outweigh this
disadvantage.
B.
Suppose, now, we want to balance an iron wire against a copper wire,
the wires being straight and long, though not so long as to require the
consideration of electrostatic capacity. For simplicity, first let the
ratio be one of equality, so that sides 1 and 2 in the Christie are any
precisely equal admissible arrangements, which may be mere resistances.
Let the iron wire be in side 3, the copper wire in side 4. We have to
make side 3 an electrical full -sized copy of side 4. For definiteness,
imagine F3 and F4 to be short-circuits, that one of the two parallel
lines leading to either is the wire under test, whilst the other is a
return tube, thin and concentric.
First, in accordance with the description of how to make copies
[vol. ii., p. 104], make the resistances of the two returns equal. Next,
make the inductances due to the magnetic field in the space between
wires and returns equal, by proper distance of returns, or by inducto-
116 ELECTRICAL PAPERS.
meters in sequence with sides 3 and 4. There is now left only the
wires themselves to be equalised. First, their steady resistances
require to be equal. Next, their steady inductances (|yx, x length).
These two conditions will give balance to infinitely slow variations of
current, and can be satisfied with wires of all sorts of sizes and lengths.
But we require to make them balance during rapid variations of any
kind. For instance, a very short impulse will cause a mere surface
current in the wires, that is, in appreciable strength, if they be thick ;
and still the wires must balance. The full balance is secured by a
third condition, viz., that the time-constants of diffusion shall be equal.
This time-constant is /xforc2, where p is the inductivity, k the con-
ductivity, and c the radius of a wire. Or, fd/R, the quotient of the
inductivity by the resistance per unit length (or any multiple that we
may find convenient of this quotient).
Thus, if the iron has inductivity 100, that of copper being 1, whilst
Jc for copper is about six times the value for iron, the copper wire must
have a radius of about four times that of the iron. This is indis-
pensable. Fixing thus the relative diameters, the rest is easy, by
properly choosing the lengths. In a similar manner, we may have the
resistances in any proportion ; as, for instance, to obviate the necessity
of having wires of very different lengths, keeping, however, the proper
ratio of diameters.
The following will be more satisfactory as a demonstration. If Z is
the V\C operator, then Z^Z^ — Z^Z^ is the condition of balance [vol. n.,
p. 104]. So we have merely to examine the form of the Z of a straight
wire. This is [vol. n., p. 63].
Z=LQp + Rf, ............................ (31c)
where / is the operator given by
\(SC)
L0 is the inductance other than that due to the wire itself, and R is its
steady resistance. Using this form of Z in our general equation of
balance, we see that if we take S3c3 = s4c4, that is, make the diffusion
time-constants equal, we make /3 =/4, so that the balance is given by
^3 ...(33c)
' V *
where the additional r3 and r4 are for the two return-sheaths, or other
resistances that may be in sides 3 and 4. Of course Zl and Z% may be
Rl and R2, the resistances of sides 1 and 2, when they are mere
resistances. In virtue of the equality of the diffusion time-constants,
we may express the full conditions by adding to (33c) this : —
= -3, ................................ (34c)
where /3 and 14 are the lengths of the two wires.
Although this balance is true, yet there will be one practical difficulty
in the way. As is very easily shown by sliding a coil along an iron
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 117
wire or rod, the inductivity often varies from place to place. But if
the wire be made homogeneous, the evil is cured.
Next, let it be required to balance a long iron against a long copper
rod in long magnetising solenoids forming sides 3 and 4. Here the
form of Z for the circuit of the solenoid is
Z=R + LQp + Lpf~\ ........................ (35c)
where R is the total resistance (as ordinarily understood) of the circuit
of the solenoid, L0 the total inductance ditto, due to the magnetic field
everywhere except in the core, L that due to the core itself when the
field is steady, and /as before, in (32c).
To balance the iron against the copper we therefore require, first,
the equality of time-constants of diffusion, or the iron rod should be
one-fourth the radius of the copper ; this being done,
^ = ^3 = ^3 = ^3 .......................... (36C)
Z2 ^4 L0i L±
will complete the balance. The value of L (i.e., L3 or £4) is
........................... (37c)
if N is the number of turns per unit length, and I the length of the
solenoid. As for Z0, that is adjustible ad lib. nearly. The only
failure will be due to want of homogeneity.
Lastly, balance two rods, one of iron, the other of copper, against one
another in Felici's arrangement, when each pair of coils consists of long
coaxial solenoids, making two primaries and two secondaries, properly
connected together. Let Rv R2 be the total resistances of the primary
and the secondary circuits ; LQV L02, the total inductances, not counting
the parts due to cores ; M0 the total mutual inductance, not counting
the parts due to cores ; Lv Lv and M those parts of the inductances,
self and mutual, of the first pair of coils, due to the cores ; and llt 1% m
the same for the second pair. The equations of E.M.F. in the primary
and secondary are then, if F and / are the two core-operators, as per
(32c), and Clt C2 the primary and secondary currents,
e = R^ + LolpC1 + MQpC2 + F^L^ + MC2) +f~lp(l1
0 = R2C2 + L02pC2 + M^ + F~lp(L2C2 + MCJ +f~1p(l2C2
The first terms on the right are the KM.F.'S used in the solenoid
circuits against their resistance; the two following terms taken nega-
tively the KM.F.'S of induction not counting cores; and the last two
taken negatively those due to the cores. To have a balance, C2 must
vanish. The second equation then gives
M0 + MF-l + mf-l = 0 ..................... (39c)
So M0 = Q, or the mutual inductance of the circuits due to other
causes than the cores, must vanish. Then, further,
F=f, and M= -m .................... (40c)
So the diffusion time-constants of the cores must be equal, and the
steady mutual inductance of one pair be cancelled by that of the other
pair of coils, so far as depends on the cores, as well, as before said, as
118 ELECTRICAL PAPERS.
depends on the rest of the system. (When not counting cores is
spoken of, it is not meant that air must be substituted. Nothing must
be substituted.) The latter part is capable of external balancing. The
balancing of the former part requires the value of
.......................... (41c)
where Nlt N2 are the turns per unit length in the two coils of a trans-
former of length /, to be the same for the two transformers.
The condition (39c) of course makes the primary equation independent
of the secondary. It is then the same as if the secondary coils were
removed.
This leads us to show the modification made in the equation of a
transformer by the conductivity of its core. In (38c) we have merely
to ignore the /terms, thus confining ourselves to one transformer, when
the equations are given by the first lines. Now if the solenoids be of
small depth, and there be no L externally, Lol and L02 become insigni-
ficant, and also MQ, provided the cores fill the coils. We have then
2)>1 (toti
0 = K2C2 + F~lp(L2C2 + MCJ, ] ' '
which only differ from the equations when cores are non-conducting by
the introduction of F. The first approximation to F is unity (when
very slow variations take place). It may be written thus :—
F~l = A-Bp, ............................ (43c)
when A and B are positive functions of p2, whose initial values are
A = l, B = Q. When the impressed force is sinusoidal, p2 — - n2, and
A and B are constants. Then (42c) become
e = R& + (L& + MC2)Bn2 + Ap^C, + MC2\\
0 = R2C2 + (L2C2 + MCJBn* + Ap(L2C2 + MCJ. J ' '
From these, by elimination, we have
e - S + L S
~ l + LI
showing the effective resistance and inductance of the primary as
modified by the secondary and conducting core.
But it is very easy with iron cores, without excessive frequency, to
make simpler formulae suit. Let z = 7rc2kfjin; then, if this is 10 or over
[see vol. IL, p. 99], we have
A=Bn = (2z)-l .......................... (46c)
approximately, which may be used in (44c), (45c) at once.
In an iron rod of only 1 cm. radius, and /i=100, £=1/10,000, the
value of z is one-fifth of the frequency. If of 10 cm. radius, it equals
twenty times the frequency. With large values of z we have
+ I2n)2
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 119
if Lv L2, and M, when divided by (2z)l, become llt /2, and m. This
gives the primary current. And
gives the secondary current.
We can predict beforehand what these should lead to ultimately,
from the general property that a secondary circuit, at sufficiently high
frequencies, shuts out induction, or tends to bring L2C2 + MC\ to zero,
giving the ratio of the currents at every moment. The coefficients of p
in (47c) and (48c) tend to zero, and the current in the primary to be
the same as if its resistance were increased by the amount
The core need not be solid. A cylinder will do as well, since the
magnetisation does not penetrate deep. It should, however, be re-
membered that although at low frequencies it is the core that con-
tributes the greater part of the inductance, so that the rest is then
negligible, yet when that due to the core actually becomes negligible,
the rest becomes relatively important, and should therefore be allowed
for.
SECTION XL. PRELIMINARY TO INVESTIGATIONS CONCERNING LONG-
DISTANCE TELEPHONY AND CONNECTED MATTERS.
Although there is more to be said on the subject of induction-
balances, I put the matter on the shelf now, on account of the pressure
of a load of matter that has come back to me under rather curious
circumstances. In the present Section I shall take a brief survey of the
question of long-distance telephony and its prospects, and of signalling
in general. In a sense, it is an account of some of the investigations to
follow.
Sir W. Thomson's theory of the submarine cable is a splendid thing.
His paper on the subject marks a distinct step in the development of
electrical theory. Mr. Preece is much to be congratulated upon having
assisted at the experiments upon which (so he tells us) Sir W. Thomson
based his theory; he should therefore have an unusually complete
knowledge of it. But the theory of the eminent scientist does not
resemble very closely that of the eminent practician.
But all telegraph circuits are not submarine cables, for one thing ;
and, even if they were, they would behave very differently according
to the way they were worked, and especially as regards the rapidity
with which electrical waves were sent into them. It is, I believe, a
generally admitted fact that the laws of Nature are immutable, and
everywhere the same. A consequence of this fact, if it be granted, is
that all circuits whatsoever always behave in exactly the same manner.
This conclusion, which is perfectly correct when suitably interpreted,
appears to contradict a former statement ; but further examination will
show that they may be reconciled. The mistake made by Mr. Preece
was in arguing from the particular to the general. If we wish to be
accurate, we must go the other way to work, and branch out from the
120 ELECTRICAL PAPERS.
general to the particular. It is true, to answer a possible objection,
that the want of omniscience prevents the literal carrying out of this
process ; we shall never know the most general theory of anything in
Nature ; but we may at least take the general theor}7 so far as it is
known, and work with that, finding out in special cases whether a more
limited theory will not be sufficient, and keeping within bounds
accordingly. In any case, the boundaries of the general theory are not
unlimited themselves, as our knowledge of Nature only extends through
a limited part of a much greater possible range.
Now a telegraph circuit, when reduced to its simplest elements,
ignoring all interferences, and some corrections due to the diffusion of
current in the wires in time, still has no less than four electrical con-
stants, which may be most conveniently reckoned per unit length of
circuit — viz., its resistance, inductance, permittance, or electrostatic
capacity, and leakage-conductance. These connect together the two
electric variables, the potential-difference and the current, in a certain
way, so as to constitute a complete dynamical system, which is, be it
remembered, not the real but a simpler one, copying the essential
features of the real. The potential-difference and the permittance settle
the electric field, the current and the inductance settle the magnetic
field, the current and resistance settle the dissipation of energy in, and
the leakage-conductance and potential-difference that without the wires.
Now, according to the relative values of these four constants it is con-
ceivable, I should think, by the eminent engineer, that the results of
the theory, taking all these things into account, will, under different
circumstances, take different forms. The greater includes the lesser,
but the lesser does not include the greater.
In the case of an Atlantic cable it is only possible (at present) to get
a small number of waves through per second, because, first, the attenua-
tion is so great, and next it increases so fast with the frequency, thus
leading to a most prodigious distortion in the shape of irregular waves
as they travel along. Of course we may send as many waves as we
please per second, but they will not be utilisable at the distant end.
This distortion is a rather important matter. Mere attenuation, if not
carried too far, would not do any harm. Now the distortion and the
attenuation, though different things, are intimately connected. The
more rapidly the attenuation varies with the frequency, the greater is
the distortion of arbitrary waves ; and if the attenuation could be the
same for all frequencies, there would be no distortion. This can be
realised, very nearly, as will appear later.
Now when there are only a very few waves per second, the influence
of inertia in altering the shape of received signals becomes small, and
this is why the cable-theory of Sir W. Thomson, which wholly ignores
inertia, works as a substituted approximate theory. But suppose we
shorten the cable continuously, and at the same time raise the fre-
quency. Inertia becomes more and more important ; the theory which
ignores it will not suffice ; and carrying this further, we at length arrive
at a state of things in which the old cable-theory gives results which
have no resemblance whatever to the real. This is usually the case in
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 121
telephony, as I have before proved. It is always partly the case, viz.,
for the very high frequencies, and it may be true, and practically is
sometimes, down to the low frequencies also. I have shown that the
attenuation tends to constancy as the frequency is raised, except in so
far as the resistance of the wire increases, and that at the same time the
speed of the waves tends to approximate to the speed of light, or to a
speed of the same order of magnitude, which is the only speed which
can, I think, be said, even in a restricted sense, to be the " speed of
electricity." But if the dielectric be solid, there must be some un-
certainty about what this speed is, for obvious reasons, with very high
frequencies. The speed of the current is never proportional to the
square of the length of the line.
Within the limits of approximately constant attenuation the dis-
tortion is small. This is what is wanted in telephony, to be good.
Lowering the resistance is perhaps the most important thing of all.
Other means I will mention later. What the limiting distance of long-
distance telephony may be, who can tell 1 We must find out by trial.
We know that human speech admits of an extraordinary amount of
distortion (never mind the attenuation) before it becomes quite un-
recognisable. The "perfect articulation," "even different voices could
be distinguished," etc., etc., mean really a large amount of distortion,
of which little may be due to the circuit. There is the transmitter, the
receiver, and several transformations between the speaker and the
listener, besides the telephone line. What additional amount of dis-
tortion is permissible clearly must depend upon what is already
existent due to other causes. Even if that be fixed, I see no legitimate
way of fixing its amount by theoretical principles ; the matter is too
involved, and includes too many unknown data, including " personal
equation." But this is certain, in my opinion — that good telephony is
possible through a circuit whose electrostatic time-constant, the product
of the total resistance into the total permittance, is several times as big
as the recent estimate of Mr. W. H. Preece, and I shall give my
reasons for this conclusion.
Increasing the inductance is another way of improving things. Hang
your wires wider apart. The longer the circuit, the wider apart they
should be ; besides this, they may be advantageously raised higher.
You can then telephone further, with similar attenuation and distortion.
There is a critical value of the inductance for minimum attenuation-
ratio. It is from L = Rlftv to L = Rljv, according to circumstances to
be later explained ; L being the inductance and R the resistance per
unit length, I the length, and v the speed of waves which are not, or
are only slightly dissipated, which is (LS)~t, if S be the permittance per
unit length. The resulting attenuation may be an enlargement, as I
have before explained, due to to-and-fro reflections. This is to be
avoided. I shall explain its laws, and how to prevent it. By this
method, carrying it out to an impracticable extent, however, we could
make the amplitude of sinusoidal currents received at the distant end of
an Atlantic cable greater than the greatest possible steady current from
the same impressed force — an unbelievable result. And, without alter-
122 ELECTRICAL PAPERS.
ing the permittance or the resistance, we could make the distortion
quite small.
There is some experimental evidence in favour of increasing the
inductance (apart from lessening the permittance) ; though, owing to
want of sufficient information, I do not wish to magnify its importance.
I refer to the statement that excellent results have been obtained in
long-distance telephony with copper-covered steel wires. Here the
copper covering practically decides the greatest resistance of the wire ;
what current penetrates into the steel lowers the resistance and increases
the inductance. Clearly, we should magnify this effect, and, electrically
speaking, it would seem that a bundle of soft-iron wires with a covering
of copper is the thing, as this will allow the current to penetrate more
readily, lower the resistance the most, and increase the inductance the
most. But it is too complex a matter for hasty decision. We also see
that the iron sheathing of a cable may be beneficial.
When we have little distortion, we get into the regions of radiation.
The dielectric should be the central object of attention, the wires
subsidiary, determining the rate of attenuation. The waves are waves
of light, in all save wave-length, which is great, and gradual attenuation
as they travel, by dissipation of energy in the wires. There is the
electric disturbance and the magnetic disturbance keeping time with it,
and perpendicular to it, and both perpendicular to the transfer of
energy, which is parallel to the wire, very nearly. A tube of energy-
current may be regarded as a ray of light (dark, of course).
It is to such long waves that I attribute the magnetic disturbances
that come from the sun occasionally, and simultaneously show them-
selves all over the world ; arising from violent motions of large
quantities of matter, giving shocks to the ether, and causing the
passage from the sun of waves of enormous length. On such a wave
passing the earth, there are immediately induced currents in the sea,
earth's crust, telegraph lines, etc.
But to return to the circuit. The attenuation-ratio per unit length
is represented by e-^/2^ this being the ratio of the transmitted to the
original intensity of the wave. This is when the insulation is perfect.
These waves are subject to reflection, refraction, absorption, etc.,
according to laws I shall give. Of these the simplest cases are reflection
by short-circuiting, when the potential-difference is reversed by reflec-
tion, but not the current, and in the act of reflection the former is
annulled, the latter doubled. Also reflection by insulation, when it is
the current that is reversed, and potential-difference unchanged ; or, in
the act of reflection, the first cancelled, the second doubled. But there
are many other cases I have investigated.
I have also examined leakage. This is an old subject with me. An
Atlantic cable is worked under the worst conditions (electrical) possible
with high insulation; there is the greatest possible distortion. One
megohm per mile or less instead of hundreds or thousands would vastly
accelerate signalling. The attenuation-factor is now t-K<"*Lv. €-zi**>t if ]£
be the leakage-conductance, and 8 the permittance per unit length.
The attenuation is increased, but the distortion is reduced. This has
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 123
led me to a theoretically perfect arrangement. Make E/L = K/S, and
the distortion is annihilated (save corrections for increased resistances,
etc.). The solution is so simple I may as well give it now. Let V and
C be the potential-difference and current at distance x, subject to
-~
ax
then, with equality of time-constants as described, the complete solu-
tion consists of two oppositely travelling trains of waves, of which we
need only write one ; thus,
7=f(x-vt)e-atlL,
where f(x) is the state when / = 0. The current is C=F/Lv. The
energy is half electric, half magnetic; the dissipation is half in the
wire, half outside. Change the sign of v in a negative wave. There is
a perfect correspondence of properties, when this unique state of things
is not satisfied, between V solutions with K= 0, and C solutions with
jR = 0. This perfect system would require very great leakage in an
Atlantic cable, and cause too much attenuation ; but this perfect state
may be aimed at, and partly reached. Are there really any hopes for
Atlantic telegraphy ? Without any desire to be over sanguine, I think
we may expect great advances in the future. Thus, without reducing
the resistance or reducing the permittance (obvious ways of increasing
speed), increase the leakage as far as is consistent with other things,
and increase the inductance greatly. One way is with my non-conduct-
ing iron, which I have referred to more than once, an insulator impreg-
nated with plenty of iron-dust. Use this to cover the conductor. It
will raise the inductance greatly, and so greatly diminish the attenua-
tion ; whilst the insulation-resistance will be lowered, somewhat increas-
ing the attenuation, but assisting to diminish the distortion, which the
increased inductance does. The change in the permittance must also
be allowed for. But I shall show that we can have practical approxi-
mations to almost negligible distortion in telephony, and that it is the
reduction of RjL that is most important.
I have also examined the question of apparatus. We must stop the
reflection, if possible, to prevent interference. In the perfect system
this is also quite easy. The receiver must have resistance Lv and zero
inductance. All waves arriving are then wholly absorbed. Similarly,
to make the transmitted waves agree with the impressed force, Lv
should be the resistance there, (or else zero). Another remarkable
property is that if the receiving coil be fixed in size and shape, whilst
its resistance varies, then this same Lv is the resistance that makes the
magnetic force of the coil a maximum. We cannot imagine anything
more perfect. No distortion, and maximum effect. I shall show that
these things may be fairly approximated to in telephonj'. It should be
understood that in the perfect system we have nothing to do with
what the frequency may be, whilst in telephony it is the high frequency
that allows us to approximate to the ideal state.
Then there is the matter of bridges, and the nature of the reflected,
transmitted, and absorbed waves. The phenomena formally resemble
124 ELECTRICAL PAPERS.
those due to the insertion of resistance in the main circuit, except that
the potential-difference and the current change places. Thus if R^ be
an inserted resistance, when there is no leakage and no resistance in
the line (l+RJSLv)'1 is the ratio of transmitted to incident wave.
Now let there be no resistance inserted, but a bridge of conductance K^ ;
then the substitution of Kt for Jff1, and S for L gives us the correspond-
ing formula. In the first case the reflected current is reversed, in the
second case it is the potential-difference of the reflected wave that is
reversed. Now let there be both a resistance inserted and a conducting
bridge, and choose R^L = KJS ; then the reflected wave is abolished.
Part of the original wave is absorbed in the bridge, and the rest is
transmitted unchanged. This explains the perfect system above
described.
I have also examined the changes made when the state is not perfect.
The result is that a wave throws out a long slender tail behind it ; and
whilst the nucleus goes forward at speed v, the tail goes backwards at
this speed. In time, if the line be long enough, the nucleus, which
changes shape as it progresses, diminishes so as to come to be a part of
the tail itself. It is then all tail. I will give the equation of the
nucleus and tail. It is the mixing up of these tails that causes arbitrary
waves to be distorted as they travel from beginning to end of the line.
(But I have, in the above, usually referred to distortion as the change
in the shape of the curve of current at a single spot.) There is residual
reflection due to the self-induction of the receiver, even when the
resistance is of the proper amount. The effect of diffusion in the wires
is to make a wave with an abrupt front, which would continue abrupt,
have a curved front, and thus mitigate that perfection which only
exists on paper. I shall also describe graphical methods of following
the progress of waves, and of calculating arrival-curves of various kinds,
the submarine cable and oscillatory ; approximate only, but very easy
to follow. Other matters, perhaps more practical, but certainly duller,
will find their place, if space allow.
SECTION XLI. NOMENCLATURE SCHEME. SIMPLE PROPERTIES OF
THE IDEALLY PERFECT TELEGRAPH CIRCUIT.
To explain the word " permittance " that I used in the last Section,
I may remark that in stating my views in 1885 in several communications
to this journal on the subject of a systematic and convenient electrical
nomenclature based upon the explicit recognition of the three fluxes,
conduction-current, magnetic induction, and electric displacement, pro-
posing several new words, some of which have found partial acceptance,
I remarked upon the unadaptable character of the word "capacity."
It must be the capacity of something or other, as of permitting dis-
placement. I did not then go further in connection with the flux
displacement than to use " elastance," for the reciprocal of electrostatic
capacity. The following shows the scheme so far as it is at present
developed : —
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 125
FLUX. FORCE/FLUX. FLUX/FORCE. FORCE.
Conduction-Current { £g£- ££%%. } Electric.
**>»*»• ........... { i IntS (Magnetic.
Electric-
Why elastivity ? Maxwell called the reciprocal of the permittance of a
unit cube "the electric elasticity." By making it simply elastivity, we
first get rid of the qualifying adjective ; next, we avoid confusion with
any other sort of elasticity ; and, thirdly, we produce harmony with the
rest of the scheme. There are now only two gaps. " Resistance to
lines of force," or "magnetic resistance," now used, will not do for
permanent employment. Besides the above, there is Impedance, to
express the ratio of force to flux in the very important case of sinusoidal
current. Impedance is at present known by various names that seem
to be founded upon entirely false ideas. The impedance (which, derived
from impede, need not be mispronounced) of a coil is the ratio of the
amplitude of the impressed force to that of the current. A coil used
for impeding may be called an impeder. The same definition obviously
applies in any case that admits of reduction to one circuit (even though
parts of it may be multiple), e.g., any number of coils in sequence, in
sequence with any number in parallel (to be regarded as one), in sequence
with a condenser, or arrangement reducible to a condenser. The im-
pedance is always reducible to (R2 + L2n2)l, where R is the effective
resistance, which is real, and L the effective inductance, or sometimes
gmtse-inductance. It is not necessary to exclude inductive action on
other circuits, although the heat corresponding to R may be partly in
them. As for resistance, it is very desirable to confine its use to the
established meaning in connection with Joule's law.
Now let R, L, S and K be the resistance, inductance, permittance
and leakage-conductance per unit length of a circuit ; and let V and C
be the potential-difference (an awkward term) and current at distance
x. We have the following fundamental equations of connection : —
, ............ (U)
p standing for d/dt. Observe that the space-variation of C is related to
V in the same manner (formally) as the space-variation of V is related
to (7, so that we can translate solutions in an obvious manner by ex-
changing V and (7, R and K, L and S, which are reciprocally related, in
a manner.
To fix ideas, the circuit may be the common pair of parallel wires.
There is one case in which the four constants are all finite that is
characterised by such extreme simplicity that it is desirable to begin
* [The two blanks were filled up later by the words Reluctance and Reluctivity
or Reluctancy.]
126 ELECTRICAL PAPERS.
with it, especially as it casts a flood of light upon all the other cases,
which may be simpler in appearance, and yet are immensely more com-
plex in results. Let
s. and LStf = l ................... (2d)
The number of circuit-constants is now virtually three, owing to the
fixing of the fourth constant. The equation of V is now
or, which is equivalent,
if J/r=u€~st. Since (4e?) is the equation of undissipated waves, with
constant speed v, whose solution consists of two oppositely travelling
arbitrary waves, the complete solution of (3d) consists of such waves
attenuated as they progress at the rate s (logarithmic). Thus,
r=f(x-vt)c-'t (5d)
is the complete expression of the positive wave, if/(£) be the state when
t = 0. Shift the wave bodily a distance vt to the right, and attenuate it
from 1 to €~", and we obtain the state at time t. The corresponding
current is
C=Pr/Lv = SvF', (Qd)
in every part of the wave. To express a negative wave, change the
sign of v in (5d) and (6d). The second form of (6d) says that a charge
Q moving at speed v is equivalent to a current Qv.
Since F"is an E.M.F., it is convenient to reckon Lv in ohms, as was
done before ; v is 30 ohms, in air, when it has its greatest value (speed
of light, 30 earth-quadrants per second) and L is a convenient numeric.
L = 20 is a common value (copper suspended wires) ; in this case our
"resistance" is 600 ohms. But it is not "ohmic" or "joulic" resist-
ance ; the current and E.M.F. are perpendicular. V is the line-integral
of the electric force across the dielectric from wire to wire, and (7 is the
line-integral ( -r 4?r) of the magnetic force round either wire. The
electric and magnetic forces are perpendicular, and so are V and 0
regarded as vectors, [i.e., their elements E and H are perpendicular].
The product VG is the energy-current; their ratio is the important
quantity Lv, the impedance.
In a positive wave V and G are similarly signed, and in a negative
wave are oppositely signed. Thus, if the electrification be positive, the
direction of the current is the direction of motion of the wave ; whilst
if it be negative, the current is against the motion of the wave.
When oppositely travelling waves meet, the resultant Vis the sum
of the two F°s, and the resultant C the sum of the two C"s.
Thus, if the waves be so shaped as to fit, then, on coincidence, V is
doubled and C is annulled. The energy is then all electric. But if the
electrifications be opposite, Fis annulled and G is doubled, on coincidence.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 127
The energy is then all magnetic. On emergence, however, the two
waves are unaltered, save in the attenuation that is always going on.
The electric energy is \SV'2 per unit length of circuit, and the mag-
netic energy is %LC'2. From this, by (Qd) and the second of (2d), we
see that the electric and magnetic energies are equal in a solitary wave,
either positive or negative. The dissipativity in the wires is EC2, and
outside them KF2, per unit length of circuit. These are also equal, for
the same reason.
Should the disturbance be given arbitrarily, i.e., V and C any
functions of x, the division into the positive wave V^ and the negative
wave F2 is effected thus : —
T^^F+LvC), F2 = ^(F-LvC) ............. (Id)
Notice that SV^V^ - LC^^ so that the total energy per unit length
is always
S(F-?+F*)=L(C? + C*) ...................... (Sd)
Similarly, the total dissipativity is always
Similarly the total energy-current is always
snce
If, at a given moment, V— F0 through unit distance anywhere, with
no Ct this immediately breaks into two equally big waves, one positive,
the other negative, which at once separate. If initially there be no F,
but only C, the same is true for the current-waves ; i.e., the result is two
equal but oppositely signed V waves, which at once separate.
What happens when disturbances reach the end of the circuit depends
upon the nature of the terminal connections there. At present only
one case — the simplest — will be noticed. Let there be a resistance of
amount Lv at the distant end B of the circuit. The terminal condition
is then V=LvC. But this is the property of a positive wave. Hence
all waves travelling towards B are immediately absorbed on reaching B.
The electricity is all gobbled up at once, so to speak. Similarly, if
there be a resistance Lv at the end A (where z = 0) it imposes the
condition V— - LvC, which is the property of a negative wave, so that
all disturbances on arrival at A are absorbed immediately. Thus, given
the circuit in any state of electrification and current, without impressed
force, it is wholly cleared in the time l/v at the most, I being the length
of the circuit.
Now, let the circuit be short-circuited at A, and have a resistance Lv
at B. Insert an impressed force e at A momentarily, producing V= e
through unit distance, say. This will travel towards B at speed v,
attenuating as it goes, and on arrival at B, what is left will be at once-
absorbed. This being true for every momentary impressed force, we
see that if it be put on at time t = 0, and kept steadily on thereafter, the
full solution is
128 ELECTRICAL PAPERS.
from x = 0 to x = vt, and zero beyond. Thus the steady state at a given
point is instantly assumed the moment the wave-front reaches it. After
that, there is still transfer of energy going on there, viz., to supply the
waste in the part of the wave that has passed the spot under considera-
tion, and to increase the energy at the front of the wave. The current
is F/Lv, as before. On reaching B, the current is
r — ^ e-MlLv — ^ v ™ --W>lLv /I 9/7\
V p-« TM * T"~* \L*JU>I
Lv Rl Lv
If we let El, the resistance of the circuit, be 3,000 ohms, which is 5
times the before-assumed value of Lv, then the received current is
150 Lv 90,000 30 Rt
The attenuation is such that the current is one-thirtieth part of the
full steady current with perfect insulation.
The electrostatic time-constant of the circuit is
RSPJ1-*®-, . ..(Ud)
v Lv
or, in our example, five times the time of a journey from A to B. It
may have any value we please. If we want it to be *1 second, l/v must
be '02 second, and therefore £ = 6,000 kilometres, which requires R = '5
ohm per kilom. This is lower than that of any telephone line yet erected.
But to make the electrostatic time-constant *05 second, with the same
attenuation, it must be 3,000 kilom. at 1 ohm per kilom.
If e vary in any manner at A, the current at B is given by (I2d), in
which e varies in the same way at a time l/v later. As there is no dis-
tortion, it becomes a question of suitable instruments. With proper
instruments, no doubt the permissible attenuation could be much greater,
and the circuit much longer. Again, if we raise the insulation we lessen
the attenuation. We bring on distortion, but a good deal is allowable,
so that again we can work further. The insulation-resistance should be
•36 megohm per kilom. in the 3,000 kilom. example ; the product of the
resistance of any portion of the circuit (wires) into the insulation-
resistance of the corresponding part is (Lv)2. In the 6,000 kilom.
example it should be '72 megohm per kilom. But if it be not arbitrary
waves, but only waves of high frequency that are in question, then we
may approximate to the distortionless transmission without attending
to the exactly-required leakage.
SECTION XLII. SPEED OF THE CURRENT. EFFECT OF RESISTANCE
AT THE SENDING END OF THE LINE. OSCILLATORY ESTABLISH-
MENT OF THE STEADY STATE WHEN BOTH ENDS ARE SHORT-
CIRCUITED.
Although the speed of the current is not quite so fast as the square of
the length of the line, yet, on the other hand, it is not quite so slow as
the inverse-square of the length, as a writer in a contemporary (Electri-
cal Review, June 17, 1887, p. 569) assures us has been proved by recent
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 129
researches. However, if we strike a sort of mean, not an arithmetic
mean, nor yet a harmonic mean, but what we may call a scienticulistic
mean (whatever that may mean), and make the speed of the current
altogether independent of the length of the line, we shall probably come
as near to the truth as the present state of electromagnetic science will
allow us to go. But, apart from this, there is some & priori evidence to
be submitted. Is it possible to conceive that the current, when it first
sets out to go, say, to Edinburgh, knows where it is going, how long
a journey it has to make, and where it has to stop, so that it can
adjust its speed (scienticulistic speed) accordingly? Of course not;
it is infinitely more probable that the current has no choice at all in the
matter, that it goes just as fast as the laws of Nature, preordained from
time immemorial, will let it ; and if the circuit be so constructed that the
conditions prevailing are constant, there is every reason to expect that
the speed will be constant, whether the line be long or short. Q.E.D.
Now, a great and striking thing about the distortionless system,
whose elementary properties were discussed in the last Section, is the
distinct manner in which it brings the speed of the current into full
view. Another and very important thing is this. When the leakage
is not so adjusted as to remove the distortion altogether, solutions
become difficult of interpretation, owing to the almost necessary em-
ployment of Fourier or other transcendental series to express results.
But by a proper adjustment of the leakage so as to abolish the tailing,
which is the cause of the mathematical difficulties, we are enabled to
follow with ease the whole course of events, say, in the setting up of
the final state, due to a steady impressed force, without laborious cal-
culations. Arid, although the state of things supposed to exist in the
distortionless system is rather an ideal one, yet it allows us to obtain a
very fair idea of what happens when there is distortion, e.g., in the
oscillatory establishment of the steady state in a well-insulated circuit.
When we speak of a charge travelling along a wire at speed v, it
should be always remembered what this implies. There are two con-
ductors, parallel to one another, and the positive charge on the one is
accompanied by its complementary negative charge on the other (correc-
tions due to parallel wires, etc., are ignored here). The two charges
move together. More comprehensively, the whole electromagnetic field,
of which the charges are a feature only, is moving along at speed v, in
the space between the wires, into which it also penetrates to a greater
or less extent. In the distortionless system this penetration is assumed
to be perfect and instantaneous, so that the resistance and the inductance
are strictly constants ; and, by the ratio RjL being made equal to K/S,
we make any isolated disturbance travel on without spreading out behind.
In travelling it attenuates by loss of energy in the conductors and by
leakage in such a way that if it attenuate from 1,000 to 900 in the first 50
kilometres, it will attenuate to 810 in the second, to 729 in the third,
and so on; multiplying by 9/10 in every 50 kilometres.
In the last Section was considered the uniquely simple case of a short-
circuit at A, the beginning of the circuit, where any impressed force is
placed, sending any-shaped waves into the circuit, travelling undistorted,
H.E.P. — VOL. II. I
130 ELECTRICAL PAPERS.
with uniform attenuation, and completely absorbed on arrival at the
distant end B by a terminal resistance of amount Lv. Of course this
complete absorption at B of all waves arriving there is independent of
the nature of the terminal arrangements at A. But these will materially
influence the magnitude of the waves leaving A. Keeping at present
entirely to simple cases, if we insert a resistance Lv at A we can make a
safe guess that the current will be just halved, because when there is a
short-circuit there, the line itself behaves just as if it were a resistance
Lv. That is, the current at A is then e/Lv, however e may vary, pro-
vided there be a resistance Lv at B ; or, which is equivalent, the circuit
be continued indefinitely beyond B unchanged in its properties. This
guess may be easily justified. That the current is zero when we insulate,
or insert an infinite resistance at A, is also evident. In general, the
insertion of a resistance £Q at A causes the potential-difference F0 there,
due to an impressed force e, to be
and the current to match to be V^ILv. The transmission to the distant
end, and the attenuation are as before.
But if the place of e be shifted along the circuit from A, interferences
will result whenever the resistance at A has not the value Lv. Imagine
f to be at distance xl from A. When put on, the result is to send a
positive wave ^e to the right, and a negative wave - \e to the left, both
travelling at speed -y, and attenuating similarly. Thus the circuit
behaves towards e as a resistance 2Lv, half to the right, half to the
left. Now, when the negative wave arrives at A, if there be a resistance
Lv there to absorb it, there will be no interference with the positive
wave, which will go on to B and be absorbed there. The current at B
will therefore be
CB = i(e/Lv)€-w-*^°, ........................ (IQd)
the value of e to be taken at a given moment being that at xv at the
time (I - x-^/v earlier. But if there be a resistance at A of any other
amount than Lv, there will be a reflected wave from A, which will run
after the original positive wave, and so make every signal at B have a
double or familiar following it after an interval of time 2^/v, which is
that required to go from xl to A, and back again. Now the closer the
seat of e is shifted towards A, the more closely will the familiar follow the
original positive wave ; and when e is at A itself, they will be coincident
in front. Now, the current at A corresponding to (16rf) is
and (as will be explained in the Section on Reflections) the reflected
wave is got by multiplying by />0, where
Now make ^ = 0, and we shall verif}T (15^), and, by the union of the
positive and the reflected (also positive) wave, show that J^at x at time
t due to e =f(t)t any function of t, at A, is
and the current there is V/Lv.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 131
The most simple case after these of complete absorption at B, with
complete absorption, or short-circuit, or any resistance at A, is perhaps
that in which we short-circuit at both A and B. If a charge be then
moving towards B, it is wholly reflected with reversal of electrification.
We must have V= 0 at B, and this requires every disturbance arriving
at B to be at once reversed and sent back again. The same thing hap-
pens at the short-circuit at A. Perhaps, however, the easiest way to
follow events is to imagine the two charges, positive and negative, which
always travel together, to pass through one another when they come to
the short-circuit, so as to exchange wires. Thus one charge goes round
and round the circuit one way, whilst the other, just opposite, goes
round and round the other way. There is the usual attenuation. On
this view of the matter, we may imagine the effect of a terminal resist-
ance Lv to be simply to bring the charges to rest against friction. It
need scarcely be said, however, that the day has gone by for any such
fanciful explanation to be taken seriously.
Since the current in a negative wave (from B to A) is of the opposite
sign to the electrification, there is no reversal of current by reflection at
a short-circuit. As, therefore, the reflected wave is to be superimposed
upon the incident wave, we see that the current is doubled at B from
what it would be were the circuit to be continued beyond B, or the
critical resistance Lv were inserted in place of the continuation.
The process of setting up the permanent state due to a steady e at A
is now this : — First the positive wave
if x<vtt which would be the complete solution were there no reflection
at B. Now B is reached by F"x in the time l/v, and the value of K3 at B
just on arrival is ep, if p = e~Ji'11", which is the attenuation in the circuit.
The reflected wave F"2 now begins. This is
which travels towards A at speed v. In the meantime the first wave V^
is still going on, for the battery at A does not know what is going on at
B. Thus, from t = l/v to t = 2l/v, the state of the circuit is given by the
sum of J7! and P2 so far as F2 has reached, and by F\ alone in the rest.
On arrival of F"2 at A it is attenuated to - ep2, and reflection then pro-
duces a positive wave
which is a copy of F"T, only smaller to the extent produced by the
multiplication by p2. This wave reaches B when t - 31 /v, and then there
commences the reflected wave, F"4, given by
F4 = -ep*.e**IL; ........................... (23d)
going from B to A. This is a copy of F2. And so on. Thus we have
an infinite series of reflected waves, coming into existence one after the
other ; the state at any moment is expressed by the sum of the waves
already existent ; the final state is the sum of them all. Since the sizes
of the positive waves form a geometrical series, and also those of the
132 ELECTRICAL PAPERS.
negative waves, they are easily summed. The positive waves Vlt
etc., come to
and the negative come to
so that the sum of (24c?) and (256?) expresses the final J-^of the circuit.
And, since the current is got by dividing bv Lv in a positive wave and
by - Lv in a negative, the final current is the excess of (24d) over (25d),
divided by Lv. Notice that whilst it is a process of settling down to
the final state of electrification, it is a process of rising up to the final
state of current. More strictly, whilst the potential-difference .at any
spot oscillates about its final value, being alternately above and below
it, the excursions getting smaller and smaller as time goes on, the
current-increments are all positive, though they get smaller and smaller.
Now if the time l/v of a journey be exceedingly small, so that there may
be thousands of journeys performed in getting up to say 99 per cent, of
the final current, the current will appear to rise continuously, and the
potential-difference to have its final value from the first moment, which
is in reality its mean value during the oscillatory period. This is the
explanation I have before given of how it comes about that there is no
sign of oscillation in any purely electromagnetic formulae, such as are
universally employed when such short circuits are in question that the
current seems to have the same strength (when no leakage) everywhere.
It is really rising by little jumps, and differently timed at different
places, but the jumps are too small to be perceived, and too rapidly
executed. And the electrification at any spot is really (unless the
vibrations are specially checked) vibrating about its mean value, which
is its final value, though this mean value is assumed (in electromagnetic
formulae) to be the actual value. But if the resistance in circuit be
great, so that the final current is small, we have an oscillatory settling
down of the current, instead of a rise.
The solution (24d), (25d) is what we may at once get by considering
the differential equation of the steady state and its solution to satisfy
the terminal conditions. But our solution gives us the whole history
of the establishment of this final state, and allows us to readily follow
the oscillatory phenomenon into minute detail. When there is distor-
tion there is difference in detail, which is then difficult to follow ; but
there is no substantial difference in the general results. We cannot
make or break a circuit without a similar action in general. But we
cannot expect to be able to formularise the results simply when the
circuit is of an irregular type, e.g., a laboratory circuit.
SECTION XLIII. REFLECTION DUE TO ANY TERMINAL RESISTANCE,
AND ESTABLISHMENT OF THE STEADY STATE. INSULATION.
RESERVATIONAL REMARKS. EFFECT OF VARYING THE IN-
DUCTANCE. MAXIMUM CURRENT.
If there be a resistance 7?x at the end B of a distortionless circuit, its
presence imposes the condition Pr=BlC at B permanently. If, then,
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 133
there be a wave travelling towards B, we find the nature of the reflected
wave from B by applying the above terminal condition to the actual V
and C, which are the sum of V^ V^ the potential-differences in corre-
sponding portions of the incident and reflected waves, and of Clf C2 the
currents in these portions. Thus we have
to represent the full connections. From these we find
rzI^ = (Rl-Lv)(Rl + LvY^Pl say, ...... (26d)
giving the reflected in terms of the incident wave. This ratio is posi-
tive if Kl be greater, and negative if it be less than the critical Lv. In
the former case there is reversal of current, in the latter of electrifica-
tion, produced by the reflection. The three most striking cases are
when JKl = 0, oo , or Lv, i.e. short-circuit, insulation, and the critical
resistance of complete absorption, making pl = - 1, + 1, or zero. There
is partial absorption and loss of energy whenever El is finite, but none
whatever in the two extreme cases. The loss of energy is accounted
for by the Joule-heat in the terminal resistance.
In a similar manner, if there be a resistance E0 at the near end A,
the transforming factor is
If there be given an isolated charge moving towards B at a certain
time, it will, after reflection at B, be replaced by another charge moving
towards A, which may be of the same or of the opposite kind, according
as the reflecting resistance is greater or less than the critical. On
arrival at A it is transformed into a third charge moving towards B,
and so on. There is the usual attenuation p in each journey, where
p = e~a'IL". If there be complete insulation at both ends, there is no
other attenuation than this due to the circuit ; and, similarly, if the
ends be short-circuited ; but in all other cases it has to be remembered
that the act of reflection attenuates, besides causing a reversal of either
the electrification or the current.
The complete history of the establishment of the steady state due to
a steady impressed force at A is now expressible in terms of the three
constants /t>0, p, and pl ; with, of course, x the distance, t the time, and
e the impressed force. There is first the positive wave
due, as mentioned in the last Section, to the union of the initial posi-
tive wave of half strength and of the positive wave which is the re-
flection of the initial negative wave of half strength, which latter is
rendered visible by shifting the seat of e towards B. The solution
(2Sd) applies to all values of x less than vt, which is the extreme
distance reached by the wave at time t after starting. On arrival at B
we have to introduce the transforming factor pv above defined. The
reflected wave is therefore
134 ELECTRICAL PAPERS.
which is to be superimposed on the former wave to obtain the real
state during the second journey, from B to A. The region over which
FO extends grows at a uniform rate with the time, from B to A. On
arrival of F2 at A we must introduce the transforming factor />0 to
obtain the third wave, which is
This reaches B at time t = 31 /vt when th^ fourth wave commences,
which is to be found by introducing the transforming factor p1 ; thus
It is unnecessary to proceed further, as it would only produce repeti-
tions. The positive waves Fv V& etc., have the common ratio p2plp0,
and are otherwise similar. Their sum is therefore
Similarly the sum of the negative waves is
Wl-^Wl-pVo)-1-^' ................. (33d)
The final state of Fis therefore expressed by the sum of (32d) and
(33d). In all the positive waves the current is from A to B, and in the
negative from B to A ; hence the excess of (32d) over (33d), divided by
Lv, expresses the final state of current.
The solution of the above problem by means of Fourier-series is
extremely difficult. It expresses the whole history of the variable
period by a single formula. But this exceedingly remarkable property
of comprehensiveness, which is also possessed by an infinite number of
other kinds of series, has its disadvantages. The analysis of the for-
mula into its finite representatives, so that during one period of time
it shall represent (28d), then in another period represent the sum of
(28d) and (29d), and so on, ad inf., is trying work. And the getting
of the formula itself is not child's play. Considering this, and also the
fact that a large number of other cases besides the above can be fully
solved by common algebra (with a little common-sense added), the
importance of a full study of the distortionless system will, I think, be
readily admitted by all who are dissatisfied with official views on the
subject of the speed of the current. The important thing is to let in
the daylight on a subject which it was difficult to believe could ever be
freed from mathematical complications.
There is a rather important remark to be made concerning the two
extremes, 7^ = 0 and lll = co , at the end of the line, in the above
solution. Although described as short-circuiting and insulation, they
do not really represent the state of things existent when we actually
terminate a long circuit of two parallel wires by a thick cross-wire (the
short-circuit) or leave the ends disconnected in the air. Every theory
that ever was made is more or less a paper theory ; we must simplify
the real conditions to make a theory workable. Now a theory may
very closely represent reality (when pursued into numerical detail)
through a wide range, and yet go quite wrong at extremes. The
justification for making the constants of the circuit independent of its
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. j#5
length is that the length is an enormous multiple of the distance
between the wires. But if we terminate the circuit somewhere, it is no
longer true that the permittance and the inductance per unit length
are constants, near and at the termination. The theory, to be correct,
must wholly change its nature, as may be seen at once on thinking of
the changed nature of the electromagnetic field as the termination is
reached. Now our theory says that when the circuit is insulated at B,
every charge arriving there is at once sent back again unchanged ; and
that during the period of reflection, the potential-difference is doubled
and the current annulled. The doubling of the potential-difference is
obviously due to there being a double charge with the same assumed
permittance. But the permittance is not the same, nor anything like
the same, at the termination as it is far away from it. The theory
therefore wholly fails to represent the case of insulation, so far as the
potential-difference at the termination is concerned, though there does
not seem to be any reason to suppose that this will affect matters else-
where ; for when the reflected wave gets away from the termination,
the old state of things is restored. There is a similar want of corre-
spondence between the theory and reality when we make a real short-
circuit, which we have supposed to be represented by Rl - 0.
Now the question may suggest itself : Since this failure is due to the
assumption that the permittance and inductance continue constants
right up to the termination, and this assumption being made in all
cases, may there not also be a failure when Rl is finite 1 The following
reasoning will show that this is not to be expected. For if the terminal
resistance (although it may be small) be equal to that of a considerable
length of the circuit, the influence of this resistance on the course of
events must be much greater than that due to the changed nature of
the circuit near its end. We therefore swamp the terminal corrections,
which become so important themselves when the terminal resistance is
quite negligible.
The general principle that may be recognised is this. If the transfer
of energy between the circuit and the terminal apparatus (of any kind)
be of sensible amount, we may wholly disregard the fact that the circuit
changes its nature as the termination is approached. But should it be
insensible, then we fail to represent matters correctly at and near the
termination.
Again, if the ends of the circuit, supposed insulated, be brought
sufficiently close together, there may be a spark or disruptive discharge
there when a charge arrives, involving a loss of energy and attenuation.
It is scarcely necessary to remark that effects of this kind have no place
in the theory.
In the same connection it may be remarked that when we are
following the history of an isolated charge, which may, in the theory,
be confined to the shortest piece of the circuit imaginable, we should
really spread it over a length which is several times as big as the
distance between the two wires. This is to make the element of length
have the same properties as a great length. Similar assumptions are
made (though seldom, if ever, mentioned) in most theories in mathe-
136 ELECTRICAL PAPERS.
matical physics. An element of volume, for instance, must be large
enough to contain such an immense number of molecules as to impart
to it the properties of the mass.
Returning now to the study of the properties of the circuit, let us
examine the effect of varying the constants. For simplicity, insert the
critical resistance at B, and let there be none at A, where the impressed
force is. The current at B is then
CB = (elLv)t-Rl>Lv = («//%*-», (Ud)
if y = RlfLv. The value of e to be taken in the formula at a given
moment should be that at A at the time l/v earlier. Now, with the
resistance of the circuit kept constant, vary y to make the current a
maximum. We require y = l, or the critical resistance should equal
the resistance of the circuit (without leakage). It then also equals the
insulation-resistance (KI)'1. If the resistance at A be any constant
multiple of Lv, we shall have the same property y = 1 to get maximum
current. (But should the resistance at A be kept constant, we shall
have y2(fiQ/fll)+y = It which it is unnecessary to discuss.) The re-
ceived current is therefore
CB = e (2-718 Rl)~\ (35d)
when no resistance at A ; and if there be resistance of amount zLv, we
must divide the right side of (35d) by (1 +z) to obtain the current at B.
Thus the result is the same as if the circuit were a mere resistance
whose value is a small multiple of the true resistance, with abolition of
the leakage, permittance, and inductance, but with a retardation of
amount I/k This is not the electrostatic retardation, of course ; it
merely means the interval of time that elapses between sending and
receiving, whereas electrostatic retardation, as formerly understood, is
quite another thing. Neither is it the speed of the current ; that is r.
But singularly enough, the value of the electrostatic time- constant £Sl2
is now l/v itself, proportional to the first power of the length, and
inversely proportional to the speed of the current.
Example. 1,200 kilometres at 2 ohms per kilom. Lv should be
2,400. If it be an air-circuit, of copper, with v practically = 30 ohms
(the formulae for permittance, inductance, etc., will be given later), we
require L = 80. This is much too great. The inductance must be
artificially increased, if we are to have so little attenuation as above on
a circuit of that length. Or the resistance may be reduced. If 1 ohm
per kilom., L — 40 is wanted. If J ohm per kilom, L = 20.
The shorter the circuit, the smaller is the value of L needed to get
the maximum current ; and the longer the circuit, the greater L should
be. If L could be made large enough, without altering the resistance,
the circuit could be of any length we pleased. The lower the resistance
of the circuit, the less leakage is needed to prevent distortion, and the
less attenuation there is. The higher the resistance, the more leakage
is needed, and the greater is the attenuation. We see, by inspection of
(34d), that without varying either the resistance or the permittance,
but solely by increasing L (remembering that Lv = (L/S)l), we could
make Atlantic fast-speed telegraphy possible, with little attenuation
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 137
and distortion. But the speed of the current would be very low.
This I shall return to in connection with the sinusoidal solution.
SECTION XLIV. ANY NUMBER OF DISTORTIONLESS CIRCUITS
RADIATING FROM A CENTRE, OPERATED UPON SIMULTANEOUSLY.
EFFECT OF INTERMEDIATE KESISTANCE: TRANSMITTED AND
REFLECTED WAVES. EFFECT OF A CONTINUOUS DISTRIBUTION
OF RESISTANCE. PERFECTLY INSULATED CIRCUIT OF NO RE-
SISTANCE. GENESIS AND DEVELOPMENT OF A TAIL DUE TO
RESISTANCE. EQUATION OF A TAIL IN A PERFECTLY INSULATED
CIRCUIT.
If the ends of the two conductors of a distortionless circuit at its
termination at A be caused to have a difference of potential V0, vary-
ing in any manner with the time, and if there be an absorbing resistance
inserted at the other termination B, we know that the impedance of
the circuit to FQ is Lv, a constant, at every moment, so that the
current there is VQjLv. We also know how the potential-difference
and current are transmitted, attenuating to T0p and V^pfLv on arrival
atB.
If there be a second distortionless circuit starting from A, and we
simultaneously maintain the same difference of potential F0 on it, we
know what happens on it, viz., as above described, merely changing, if
necessary, the values of p and Lv. That is, if the circuit be not of the
same type as the first one, and of the same length, we require to use
different values of p and Lv.
This obviously leads to the working of any number of distortionless
circuits in parallel by a common impressed force at A. Call the wires
of a circuit the right and the left wires, merely for distinction. Join
all the right wires to one terminal Ap and all the left wires to another,
A2, and then maintain a difference of potential F0 between Al and A2.
Then, provided every circuit has its proper absorbing resistance at the
distant end, we know what happens. The reciprocal of the sum of the
reciprocals of the impedances of the various circuits is the effective
impedance to V^. Next, V0 divided by the effective impedance (say /)
is the total current. Finally the total current divides amongst the
circuits in the inverse ratio of their impedances. The current at the
distant end B of any circuit is the current entering it at A at the time
l/v earlier, multiplied by the attenuation-factor p of the circuit. I do
not write out the equations, as the description is fully equivalent.
In order that VQ should be strictly proportional to an impressed
force e in the branch joining the two common terminals Alf A2 of the
circuits, it is necessary that it should be a mere resistance, which may
have any value. Let it be £Q ; then, MQ added to the previous effective
impedance to V^ is the impedance to e ; so that the total current is
e/(2tQ + I), and the value of F0 is eI/(H0 + I). In practice, it is not
possible to fully realise this simplicity. Suppose, for instance, the
secondary of the transformer, in the circuit of whose primary a micro-
phone is placed, is joined across the common terminals of the circuits.
138 ELECTRICAL PAPERS.
Even if the circuits be distortionless, we see that there must be terminal
distortion, or F"0 will not vary as it should for the accurate transmission
of speech. There are several causes of distortion here. At the distant
end, one cause of further distortion will be the inductance of the re-
ceiving telephone, and an additional and very important one will be
the mechanical troubles that will prevent the disc from copying
accurately, in its motion, the magnetic-force variations.
After this example of a complex arrangement of circuits admitting of
simple treatment, let us return to a single circuit. Examine the effect
of inserting any resistance r intermediately. This should be put half
in each wire, if the circuit consist of a pair of equal wires, to prevent
interferences. Let there be a wave travelling from left to right to-
wards r. Let Fp F"2, Fg be the potential-differences in corresponding
portions of the incident, reflected, and transmitted waves, so that, at a
certain moment, they are coincident, viz. at r itself, where let V be the
actual potential-difference on the left side of r. Then we have
These are the full connections. From them,
Particularly notice that
as this is an important property. Every element of electrification in the
incident wave arriving at the resistance is split into two (without any
loss), one part o-Fj (in terms of potential-difference) is transmitted, the
remainder is reflected.
As we have, by (37d),
r = '2Lv o--1-!
we see that if 1 per cent, of the incident wave be reflected, and 99 per
cent, transmitted, we require r = -/-wLv. If 10 per cent, be reflected and
90 per cent, transmitted, then r = f Lv. There is no transmitted wave
if r be infinite. Half is transmitted and half reflected when r = 2Lv.
There is always a loss of energy by this division of the charge, which
is accounted for by the Joule-heat in the resistance. This is rC.f per
second ; and since a wave of unit length takes v~l second to pass,
rCy/v is the loss of energy per unit length of the incident wave, which
loss, if added to the sum of the energies in the reflected and trans-
mitted waves, makes up the energy per unit length in the incident.
Another expression for the loss of energy is given by
There is the greatest possible loss of energy when r = 2Lv, making
<r = J, and the loss = \SV?. That is, when the intermediate resistance
is twice the critical, and the incident wave is consequently half trans-
mitted, half reflected, then half the energy is wasted in the resistance.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 139
As the resistance is further increased, the transmitted wave gets
smaller, and when it is infinite, we fall back upon the case already
considered of total reflection without reversal of electrification or loss
of energy.
If we have the absorbing resistance at A and at B, and any resistance
r at an intermediate point C, we have a very simple result when any
waves are sent from A to B, or from B to A. Suppose e acts at A, and
that pv p2 are the attenuations in the two sections AC and CB. Then
T7^ = e at A becomes Fj = epl on arriving at C. The reflected wave is
F'9 = epl(l - o-), where <r is given by (37d). On arrival (multiplied by p^
SL{ A it is absorbed, so there is an end of it. The transmitted wave
at C is ^3 = cpjcr, which attenuates to Prs = epla-p.2 = eo-p on arrival at B,
where it is absorbed. The last equation therefore gives the potential-
difference at B in terms of that at A at the time l/v earlier. In the
first section of the circuit F is the sum of two oppositely travelling
waves, and the current is their difference divided by Lv ; but in the
second section there is but one wave.
We are also able to solve by algebra alone the following problem.
Given a distortionless circuit with any terminal resistances and any
intermediate resistances at different places, find the effect due to a
steady impressed force inserted anywhere in the circuit (half in each
wire, pointing oppositely in space, to avoid interferences). For we
have the circuit divided into sections, for each of which the attenuation
is known (i.e., /^ = tr1**^ jn a section of length a^) ; we also know the
transforming factors of the terminal resistances (/t>0 and pl of the last
Section) ; and we also now know the factors o- and 1 — <r for any
intermediate resistance, by which we express how a wave divides there.
So, starting when e is first put on, with the initial waves \e to the
right, and - \e to the left, we can follow the whole course of events
until we arrive (asymptotically) at the steady state. But it is no part
of my intention to enter into the details, as nothing new would be
contained therein.
But the effect of a great number of equal intermediate resistances
equidistantly situated is of importance. Let pl be the attenuation due
to the circuit between two consecutive resistances, and o- the attenuation
due to each resistance, that is, the attenuation of the transmitted wave.
Let an isolated disturbance go from A to B. If it be initially F"0, it
becomes Vtf-p one section further on, ^(Pi0")2 a^ter another section is
passed, and so on, becoming Vtf"a* after passing n sections. If these
n sections make up the whole circuit, then p? — p, the attenuation in
the circuit due to itself only, as before, so that in passing through the
circuit, F0 is attenuated to F0/xrn.
Now let the sum of the inserted resistances be nr = Rl. Increase n
indefinitely, whilst reducing r in the same ratio, thus keeping ^ con-
stant. In the limit the resistance Rl becomes uniformly distributed in
the circuit, and the attenuation due to it becomes, by (37d),
<r" = (1 + R^Lm}-n, with n = oo ,
140 ELECTRICAL PAPERS.
Observe the presence of the 2. From this we may conclude certainly
(as will be shown later), that if this uniformly distributed resistance E^
in addition to the original El, be accompanied by uniformly distributed
leakage-conductance of total amount Klt such that Rl/L=Kl/S) the
attenuation due to both E^ and K^ together is expressed by the square
of (4:ld). For what we do is to make the circuit distortionless again,
by the additional leakage to compensate the additional resistance of the
wires.
But the simplest way of viewing the matter is to start with a
perfectly insulated circuit of no resistance. This is a distortionless
circuit, of course, since it obeys the law E/L = K/S. The only difference
from a real distortionless circuit is that there is no attenuation at all.
All the preceding results therefore apply, remembering that />=!, or
any waves are transmitted, not merely undistorted, but also unattenu-
ated. They are, in fact, purely plane waves of light (very long waves
practically) travelling through a perfectly non-conducting dielectric.
They are merely guided through space in a definite manner by the
conductors, imagined to have no resistance, so that, to use a very gross
simile, the electricity slips along like greased lightning. There is no
penetration of the electromagnetic field into the conductors, but purely
surface-conduction, where we may use the word in a popular sense
(conduct = to lead). Some curious consequences of the absence of re-
sistance I will notice later ; at present I may observe that owing to
the relative simplicity produced by the absence of attenuation, the
imaginary circuit of no resistance is useful for investigating the effect
of inserting resistances, bridges, etc., and the action of a real distortion-
less circuit itself.
Thus, imagine an isolated charge moving from left to right in the
circuit of no resistance. Introduce anywhere a resistance r ; this will
cause an attenuation from 1 to cr in passing the resistance (equation
(37c?)), and the remainder 1 - a- will be reflected back. Next let there
be a great number of equidistant small equal resistances ; every one of
these will attenuate in the ratio 1 : cr, and throw back the fraction
1 - cr. The result is that the original isolated charge, as it travels
along, becomes a nucleus with a long slender tail behind it ; the nucleus
travelling forward at speed v and attenuating in the manner described ;
the tail stretching out the other way at speed v. If these isolated
resistances be packed together very closely, and be each very small, we
approximate to the effect of continuously distributed resistance, that is,
the resistance of the wires in a real circuit. In the limit, the result is,
by (41c£), that the nucleus, if originally represented by F"0a, that is,
the potential-difference VQ through the very small distance a, with
current to match, viz., VtfLto through the same distance a, and there-
fore moving entirely to the right at that particular moment, becomes
attenuated to
in the time t = x/v, during which it has moved through the distance x to
the right, if the resistance per unit length be E.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. Ul
Since there is here no leakage, the rest of the original charge must be
in the tail. The amount of electricity in the tail is therefore
Sx *>(! -€-*/"), ......................... (43d)
when the circuit is perfectly insulated. The length of the tail is 2#,
half being to the right and half to the left of the position of the
original isolated charge, it being of course supposed that neither the
head nor the tail has suffered any extraneous operations, as terminal
reflections, etc.
In a similar manner, it' initially the isolated charge SV^a be without
current, so that it would, were there no resistance, at once divide into
equal halves, travelling in opposite directions without attenuation,
what will really happen will be an immediate splitting into halves and
separation of two nuclei, travelling in opposite directions at speed v,
attenuating as they progress according to (42rf), and joined by a band,
consisting of the two tails superimposed. The equation of this double-
tail is
in a finite form (as usually understood, by a convention that a solution
in terms of a sine or JQ function, etc., is in a finite form, though it is
really an infinite series), true from x = -vttox= + vt, it being supposed
that the origin of x was the original position of the charge. At the
ends of this tail the two nuclei, each represented by
through the very small distance a, must be placed, to make up the
complete solution. I shall later illustrate this graphically, and also
explain the other kind of tail.
SECTION XLV. EFFECT OF A SINGLE CONDUCTING BRIDGE ON AN
ISOLATED WAVE. CONSERVATION OF CURRENT AT THE BRIDGE.
MAXIMUM Loss OF ENERGY IN BRIDGE-COIL, WITH MAXIMUM
MAGNETIC FORCE. EFFECT OF ANY NUMBER OF BRIDGES, AND
OF UNIFORMLY DISTRIBUTED LEAKAGE. THE NEGATIVE TAIL.
THE PROPERTY OF THE PERSISTENCE OF MOMENTUM.
Let a distortionless circuit be bridged across anywhere by a wire
whose conductance is k, and let us examine its effect on a wave passing
along the circuit. In the first place, we may remark that we have
already solved one bridge-problem, viz., the result due to an impressed
force in the bridge itself, this being made a special case of the first part
of the last Section, by limiting the number of radial circuits to two of
the same type.
Now let Fy Vy and V3 be the potential-differences in corresponding
parts of an incident, reflected, and transmitted wave ; V^ going from
left to right on the left side of the bridge, F2 from right to left on the
same side, and V^ from left to right on the further side of the bridge.
142 ELECTRICAL PAPERS.
At a certain moment these are coincident, viz., at the bridge itself.
Then, by the properties of positive and negative waves and elementary
principles, we have the following full connections :—
3- 1ttf ••
From these we find
_.
Fx Ct k+2Sv
Particularly notice that
01 = 02 + 0,, .............................. (48d)
which, though extremely simple, is not by any means obvious at first
sight, whilst it is an extremely important property. It is an example
of the persistence of momentum ; though this may not be immediately
recognised, it will be made plain enough later on.
These equations should be compared with (36d), (37d), the corre-
sponding ones relating to the effect of a resistance r inserted in the
circuit. We see that this resistance is replaced by the conductance of
the bridge, that L becomes S, and that Fand C change places in the
expressions for the ratios of the transmitted and reflected waves to the
incident.
If we fix our attention upon the current, we see that every element
of current, when it arrives at the bridge, is split into two, in the ratio
of k to 2Sv, or of ^Lv to k~l, half the critical resistance to the resistance
of the bridge. The first part is reflected, increasing the current on the
left side, and lowering the potential-difference ; whilst the other part is
transmitted. The electrification in the reflected wave is negative, if
that in the incident wave be positive ; and conversely.
It may be as well here to remind the reader that from left to right is
the arbitrarily assumed positive direction along the circuit, which is
the direction of motion of a positive wave (therefore so-called) ; whilst
a negative wave goes from right to left. Also, that the sign of the
current, whether positive or negative, is a quite different thing. That
is, the current in a positive wave may be negative, and the current in a
negative wave may be positive, or the reverse. What is a possible
source of some preliminary confusion is the fact that the vector we term
the current, and the vector direction of motion of a wave, are in the
same straight line, one way or the other. These connections are all
summed up in Fj = LvCv the property of a positive, and F2 = - LvC2,
the property of a negative wave. If the first of these relations be true,
the wave must move from left to right, whether V and C be both
positive or both negative; whilst if the second be true, the wave must
move from right to left. I can also recommend the reader to take the
advice before given to fix his attention upon the electromagnetic field
which is implied by a stated Fand a stated C, viz., a field of electric
displacement across the dielectric from one conductor to the other, and
a field of magnetic induction round the conductors. A very useful
purpose may perhaps be served by a careful study of the properties of
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 143
the distortionless circuit, viz., to assist in abolishing the time-honoured
but (in my opinion) essentially vicious practice of associating the
electric current in a wire with the motion through the wire of a hypo-
thetical <?wrtsi-substance, which is a pure invention that may well be
dispensed with.
Keturning to the effect of a bridge, notice that by the union of (48d)
with the last of (46d), we produce
That is, the current in the bridge equals twice the current in the
reflected wave. The corresponding property when it is a resistance r
inserted in the circuit that is in question is, by (36d),
that is, the fall of potential through the resistance equals twice the
difference of potential of the reflected wave.
If the bridge have no resistance, making a short-circuit (subject to
reservations that need not be repeated), there is no transmitted wave.
In fact, the case becomes identical with that of a terminal short-circuit,
producing total reflection with reversal of electrification. If, on the
other hand, the bridge have no conductance, it does nothing. If the
conductance of the bridge be 2Svt or its resistance be ^Lv, the trans-
mitted wave is half the incident, or the attenuation due to the bridge
is J. Then, by superim position, the current on the left side is increased
in the ratio 2 to 3, and is therefore made three times the transmitted
current.
The current in the bridge being kV& and the corresponding heat
per second divided by v being the heat due to the bridge per unit length
of the incident wave, this amounts to
kF!/v = 4,S2F^kv/(k+2Sv)^ .................... (51d)
by (47d). If & be variable, we make the quantity in question a maxi-
mum when k = 2Sv, which is the above case of attenuation £. The
heat in the bridge per unit length of the incident wave is then ^SF?,
which is half its energy ; the other half is equally divided between the
transmitted and reflected waves.
If this bridge-wire be a coil of a given size and shape, the variation
of k implies a variation of the thickness of the wire and of the number
of turns. Whence, in a well-known manner, the magnetic force of the
coil varies as the current in it and as the square root of its resistance ;
in another form, the square of the magnetic force varies as the product
of the resistance of the coil into the square of the current, that is, as
the heat per second. Hence, by what has just been said, the magnetic
force is also a maximum when the resistance of the coil is \Lv. Notice
that this is the impedance of the circuit as viewed from the coil itself.
A correction is required for the inductance of the coil. It ought not,
however, to be a very large correction, if it be a telephone that is in
question, and of a really good type, having the smallest possible time-
constant consistent with other necessary conditions. We require the
magnetic force to be a maximum (i.e., due to the current coming from
144 ELECTRICAL PAPERS.
the circuit) to make the stress-variations the greatest possible, and act
most strongly on the disc. [See "Theory of Telephone," Art. xxxvi.,
vol. ii.] Allowing for the inductance of the coil, if the currents be
sinusoidal, we require equality of its impedance to that external to it,
which is the general law.
Now let there be any number of bridges at different parts of the
circuit, and let the ratio V^V^ of a transmitted to an incident wave be
denoted by s, its value being given by (47d), separately for each bridge.
Let also plt p2, etc., be the attenuations due to the circuit in the different
sections into which it is divided by the bridges, and start with an
isolated positive wave V^ at A, the beginning of the first section. On
arrival at the first bridge, it has attenuated to Fi/»r What passes the
bridge (not what crosses it) is V^s^ which attenuates to P^p^p^ on
arrival at the second bridge. Then there is another sudden attenuation,
to Pi/Dj/DgSjSg, followed by a gradual attenuation in the third section, to
ViPiP2P3sis2 ') and so on, to the end of the circuit, at B. The disturbance
is then attenuated to Prlps1s2...sn') where p is the product of all the
former p's, or the attenuation due to the circuit from A to B, and sn is
the last s, belonging to the bridge next to B. If the absorbing resistance
Lv be put at B, it will at once absorb the wave just described ; but
after that there will come dribbling in and be absorbed the dregs of
the original disturbance at A, arising from the complex system of small
reflected waves due to the bridges across the circuit, much attenuated
by the many to-and-fro journeys. But if there be but one bridge, and
the absorbing resistance be put at A, to get rid of the wave reflected
from the bridge, then there is no dribbling in at B.
However many bridges there be, there is, by (486?), no attenuation
of current due to them, when its integral amount is considered, but
only a redistribution of current. This exactly corresponds to the
absence of any alteration of the total charge by inserting resistances in
the circuit. They merely redistribute the charge.
If there be n bridges in the distance x, each of conductance k, the
total attenuation produced by them is, by (47d),
f = {l+k/2Sv}-H (52d)
Now place the bridges at equal distances apart, and increase the num-
ber n in the distance x indefinitely, keeping the total conductance
constant, =K^ say. In the limit we shall arrive at a uniform dis-
tribution of leakage, K^ being its conductance per unit length, and the
attenuation due to it will be the limit of
with w = oo,
(53d)
This is therefore the attenuation of the nucleus, when an initially
isolated disturbance travels through the distance x, due to the extra
leakage Kl per unit length. There is, in addition, the regular attenua-
tion due to the circuit. Disregard this for the present, by letting the
circuit have no resistance and no leakage, that is, no leakage before the
leakage represented by K^ was introduced. Then we see that if there
be initially an isolated disturbance represented by F0 = LvC0, extending
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. H5
through the very small distance a, it becomes, at the time x/v later,
removed a distance x to the right, attenuated to (writing K for the
leakage-conductance per unit length)
extending through the distance a, with a tail of length 2x behind it.
This tail is of the negative kind, the electrification being opposite in
kind to that in the head, and is such that the line-integral of the
current in it amounts to
because this, when added to the corresponding line-integral for the head,
according to (54d), makes up CQa, the initial value of the line-integral.
This tail is, as regards current, of the same shape as the correspond-
ing tail due to resistance, as regards electrification, so its equation may
be derived from (44d). But I shall consider the tails all together in a
later Section.
The property involved in (486?), which leads to the deduction of
(55d) from (54c?), is worthy of notice. It is the persistence (or con-
servation) of momentum. If a circuit have no resistance, then, as
Maxwell showed, we cannot change its momentum, the amount of
induction passing through it. This was a linear circuit, with the
current of the same strength all round it. Now our example is a
remarkable extension of this property. Our circuit is linear and of no
resistance, but it has any number of leaks, or conducting bridges, as
well as what is equivalent to a series of condensers. The current in
the circuit may be varied indefinitely in its distribution, but we cannot
change its momentum. The line-integral of LC expresses the momen-
tum, but since L is here a constant, of course the line-integral of C
cannot change either. This property only continues true so long as
there is no resistance bounding the magnetic field; therefore, if the
circuit be of finite length, we must not insert resistances at the terminals.
For instance, short-circuit at A and B, and we can at once say what
will ultimately happen due to any initial distribution of current. It
will settle down to uniformity of distribution, i.e., making a uniform
magnetic field, so that the strength of current will equal the original
total momentum divided by the total inductance. There is, of course,
a loss of energy in the settling down, due to the leakage. If the circuit
be infinitely long, so that the disturbance can spread out infinitely, the
total energy will decrease asymptotically to zero, in spite of the per-
sistence of the momentum, which indeed tends to zero in any finite
length, but keeps its total amount unchanged.
If the circuit have resistance, the total momentum decreases according
to the time-factor c~mlL, whatever be the initial distribution, if it be
short-circuited at A and B, or be infinitely long. On the other hand,
the total charge subsides according to the time-factor t~*tls, if the circuit
be insulated at A and B, or else be infinitely long. The meaning of
terminal short-circuit or of insulation may clearly be extended to various
other cases not involving loss of charge in the latter case (e.g. a terminal
condenser) or of momentum in the former, with appropriate correspond-
ing changes in the measure of S or L respectively.
H.E.P. — VOL. ii. K
UG ELECTRICAL PAPERS.
SECTION XL VI. CANCELLING OF REFLECTION BY COMBINED RESIST-
ANCE AND BRIDGE. GENERAL REMARKS. TRUE NATURE OF THE
PROBLEM OF LONG-DISTANCE TELEPHONY. How NOT TO DO IT.
NON-NECESSITY OF LEAKAGE TO REMOVE DISTORTION UNDER GOOD
CIRCUMSTANCES, AND THE REASON. TAILS IN A DISTORTIOXAL
CIRCUIT. COMPLETE SOLUTIONS.
Having in Sections XLIY and XLV discussed in some detail the effects
due to resistances inserted in, and also those due to conducting "bridges
across, a distortionless circuit, which are of fundamental importance,
and which lead to the development of a positive tail by a continuous
distribution of resistance in excess of the distortionless amount, and of
a negative tail by an excess of leakage, the full investigation of the case
of resistance and leakage combined in any proportions presents no
difficulty.
Start with a circuit having no resistance and no leakage, which is
therefore both distortionless and conservative (or characterised by the
absence of attenuation), and let there be an isolated disturbance going
from left to right, defined by V^ = LvCr Also, let there be, at a certain
place X, a bridge across the circuit, of conductance k ', and, at the same
place, a resistance r inserted in the circuit. When our incident wave
V-^ arrives at X, there result a reflected wave represented by
V^= - LvCft and a transmitted wave V% = LvCB.
Now, considering the moment when these are all at X together
(corresponding elements, of course), we have the following two equations
connecting the three Vs : —
(57<7)
The first is simply the expression of Ohm's law applied to the
resistance r, and the second expresses the continuity of the current at
X. (Remember that Lv and Sv are reciprocal, so that the sum of the
second and third terms on the right of (57 d) expresses the bridge-
current.) The equation (57 d) may also be written
.................. (5Sd)
so that, by adding this to (56d) first, and then subtracting it, we obtain
the desired ratios. Thus,
when written in the simplest manner. Of course the ratio VjV^ if
wanted, is the quotient of (QOd) by (5$d).
We see that the reflected wave may be either of the same or of the
opposite electrification to the incident ; and that, in order to completely
abolish the reflected wave, we require, by (QQd),
.......................... (Qld)
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 147
and that we then have, by
simply. The reciprocal V^V^ expresses the attenuation suffered by the
incident wave in passing X.
The above equations are not in any way altered when we start with a
real distortionless circuit instead of an imaginary one of no resistance.
But by adopting the latter course we are directed to the nearest
approach to a physical explanation of the properties of the real dis-
tortionless circuit itself. For, in the case of the circuit of no resistance
we are dealing merely with progressive waves in a conservative medium,
and we cannot expect to come to anything simpler than this. They
simply carry their energy and all their properties forward at speed v
unchanged, this speed being (/*c)~£, if //, be the inductivity and c the
permittivity of the medium ; which expression is equivalent to the
other, (LS)~t, where L is the inductance and AS' the permittance, which
is more convenient in the practical application concerned. Except in
the matter of wave-length, these waves are identical with light-waves,
with the peculiarity that the two (supposed) perfect conductors of our
circuit prevent the waves from spreading in space generally, by guiding
them definitely along the circuit. (The simplest case is that of a
tubular dielectric bounded by perfect conductors, say an internal wire
and an external sheath.) Now we prove by elementary principles,
(Ohm's law, etc.) that an inserted resistance, causing tangential dissipa-
tion of energy, produces a reflected wave of the positive kind, involving
a redistribution, without loss, of the electrification on the bounding
conductors ; and a redistribution, with loss, of the corresponding mag-
netic quantity, the momentum. On the other hand, we show that a
bridge causes a reflected wave of the negative kind, involving a re-
distribution, without loss, of the momentum ; and a redistribution,
with loss, of the electrification. (In speaking of redistribution, the mere
translatory motion of waves is disregarded.) And by having both the
bridge and the inserted resistance so proportioned as to make the loss
of energy in each be. of the same amount (when small enough), we
abolish the reflected wave, so that there is no redistribution, but merely
attenuation produced by the resistance and bridge. This applies to
any number of resistances inserted in the main circuit, each with its
corresponding bridge ; so that when we pack them infinitely closely
together to represent continuously distributed resistance and leakage,
we arrive at a real circuit, along which waves are propagated unchanged
except in size. Thus any circuit (apart from interferences) may be
made distortionless by adding a suitable amount of leakage. This
amount is usually too great for practical purposes. Nor is it required.
In the very important problem of long-distance telephony, employing
circuits of low resistance (which are the only proper things to use),
making the well-known ratio RILn of the two components of the
electromagnetic impedance small, say J or J, which may be easily
done without using an extravagant amount of copper, we tend naturally,
by bringing the inductance into relative importance, or equivalently,
H8 ELECTRICAL PAPERS.
reducing the importance of the factor resistance, to a state of things
resembling that which obtains in the truly distortionless circuit (inde-
pendent of frequency of variations), and approximate to distortionless
transmission. These statements may be proved by an inspection of
the sinusoidal solutions I have given, but it would enlarge the subject
too greatly to discuss them at present. I may, however, repeat that
the problem of long-distance telephony is very remote from that of a
long submarine cable which can only be worked slowly, unless we
should unknowingly create a parallelism by employing quite unsuitable
conductors ; as, for instance, was done by the Post Office a few years
since when they put down conductors having a resistance of 45 ohms
per mile of circuit, combined with large permittance and small in-
ductance ; and then, to make the violation of electromagnetic principles
more complete, put the intermediate apparatus in sequence, so as to
introduce as much additional impedance as possible. The proper place
for intermediate apparatus is in bridge, removing all their impedance
completely. This method was invented and introduced into the Post
Office by Mr. A. W. Heaviside. It makes a wonderful difference in the
capabilities of a circuit, as is now pretty well known.
The theory of tails allows us to give an intelligible physical explana-
tion of how it comes to pass that a perfectly insulated circuit violating
the distortionless condition completely, will yet tend to behave in a
distortionless manner to waves of great frequency, provided the circuit
be of a suitable nature, as above described. For let the circuit be so
long that we can get several waves into it at once, when telephoning.
They divide the circuit into regions of opposite electrification, each of
which may (very roughly) represent what I have termed an isolated
disturbance. Every one of them has its tail, but as they are alternately
of opposite kinds, their residual effect in producing distortion becomes
quite small. We can see clearly that the greater the frequency the less
is the distortion, unless the increased frequency should bring with it
increased resistance, which is very much to be avoided, and is what
renders iron wire so unsuitable for /^-distance telephony. By this
mutual cancelling of the effects of the tails, we simulate the effect of the
leakage which would wholly remove distortion, even of the biggest
waves, without the disadvantage of the extra attenuation thereby intro-
duced. I am induced to make these remarks rather out of their proper
place, as they illustrate the importance of the distortionless circuit from
the scientific point of view, in casting light upon the obscurities of dis-
tortional circuits.
From (59d) we can get some results relating to the tails of waves in
a distortional circuit. Thus, let there be n bridges in the distance x,
equidistantly placed, and each of conductance Kxjnt with a corresponding
resistance Rxjn in the main circuit. Let a disturbance pass from
.beginning to end of the length x. If cr be the attenuation at each
bridge, the total attenuation of the head of the disturbance produced by
all the bridges and resistances is <rn. Now make n infinite, keeping E
and K finite. The total attenuation becomes, by (59d),
<rn = { 1 + Ex/2Lvn + Kx/2Svn + EKx*/2n2}-" = c-**^-**** (63d)
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. H9
This is therefore the attenuation of the head suffered by every
element in traversing the distance x, when R and K are the resist-
ance and the leakage-conductance per unit length in any uniform
circuit.
It will now be convenient to introduce a simpler mode of expressing
the exponentials. Let
f=E/2L, g = K/2S, h=f-g, q=f+g, ...... (64d)
all four being reciprocals of time-constants. Now (63d) becomes e~qt
simply, if t = x/v be the time of the journey over the length x. If,
therefore, we have initially a disturbance F"0 = LvCQ extending through
the small distance a, possessing the charge SV^a and the momentum
LC0a, then, at the time t later, when the disturbance extends over the
distance 2x, half on each side of its initial position, being a nucleus of
length a and a tail of length 2x, the charge and momentum in the
nucleus become
-* and £(€-*
We have next to examine to what extent the total charge has
attenuated by the leakage, and the total momentum by the resistance.
This we can ascertain by (59d) and (60d), applied to find the loss of
electrification caused by a single bridge, and of momentum by a single
resistance. Those equations give
+ r/2Lv - k/2Sv - rk/2
2 + 3_
Ct '
These fractions, multiplied into the values of the charge and
momentum respectively before the splitting, give their total values
after the splitting. We can, therefore, apply the previous method of
equidistant resistances and bridges, to ascertain the method of sub-
sidence of the total charge and momentum, in the infinitely numerous
splittings that occur in a finite time, when we pass to the limit and
have uniform R and K. Putting r = Ex/n, etc., as before, and finding
the limit of the rtth powers of (6Qd) and (67d), we arrive at e~Rt/L and
€-Kt/s respectively.
We thus see that a moving charge, no matter how it redistributes
itself, subsides at the same rate as if it were at rest ; for, obviously,
S/K is the time-constant of the circuit regarded as a condenser, when
uniformly charged and insulated at its terminations. It is as if
electricity were atomic, so that we could follow the course of every
particle. Then, . no matter how it moves about, it shrinks at the same
rate as if it were at rest. Similarly as regards the momentum of the
moving disturbance. Could we identify its elements, each would shrink
in a manner independent of its translatory motions along the
circuit. Notice, also, that the attenuation of the total charge equals the
square of the attenuation of the nucleus due to leakage alone ; whilst
150 ELECTRICAL PAPERS.
the attenuation of the total momentum equals the square of the
attenuation of the nucleus due to resistance alone.
Thus, corresponding to (65^), we have
Sr<p. e-*(e-* - e-*) and ££>.€-*(€-•* - e-*) . . . (QSd)
to express the charge and momentum in the tail ; since these, when
added to (656?), make up the actual values otherwise found, viz.,
If f>g, or the resistance be in excess, the current in the tail is from
head to tip, if that in the head be positive. But as time goes on, if the
circuit be long enough, the head attenuates practically to nothing,
leaving the big tail to work with. The region of positive current now
extends from the vanishing nucleus a long way towards the middle of
the tail ; and, in the limit, the disturbance tends to become symmetrically
arranged with respect to the origin from which it started as a positive
wave, tailing off on both sides, with the current positive on one side
and negative on the other.
But if /< g, or the leakage be in excess, a quite anomalous state of
affairs occurs, which may be inferred from the preceding by changing
rto C, etc.
The full solutions of all tail-problems (shape, growth, etc.) are con-
tained in the following four equations. Let a charge SVtfi be at the
origin at time t — 0, without any current. At time t we shall have, if
............ ......... <7M>
to express the double-tail or band connecting the two nuclei at its ends,
which are already known. Similarly, if there be initially a current at
the origin, of momentum LC0a9 without charge, then at time t we shall
have
As before, put on the two nuclei at the ends. Since the «70 function is
a simple one, viz.,
2242
it is quite easy to follow the changes of shape by these formulae, except
when t has become large and the nuclei small, when other formula may
be derived from the above which will approximately suit. [For further
information, see Part vin. of Art. XL., Part I. of " Electromagnetic
Waves," and " The General Solution of Maxwell's Equations."]
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 151
SECTION XLVII. Two DISTORTIONLESS CIRCUITS OF DIFFERENT
TYPES IN SEQUENCE. PERSISTENCE OF ELECTRIFICATION,
MOMENTUM, AND ENERGY. ABOLITION OF REFLECTION BY
EQUALITY OF IMPEDANCES. DIVISION OF A DISTURBANCE
BETWEEN SEVERAL CIRCUITS. CIRCUIT IN WHICH THE SPEED
OF THE CURRENT AND THE RATE OF ATTENUATION ARE
VARIABLE, WITHOUT ANY TAILING OR DISTORTION IN RECEP-
TION.
If two distortionless circuits of different types be joined in sequence,
a wave passing along one of them will, on arrival at the junction, be
usually split into two, a transmitted and a reflected wave. Let, in the
former notation, V^ F2, Vz denote the potential-differences in corre-
sponding elements of the incident wave in the first circuit, the reflected
wave in the same, and the transmitted wave in the second circuit.
The sole conditions at the junction are that V and C shall not change
in passing through it. Thus,
Now let ijflj and L2v2 be the impedances of the two circuits, L± and L2
being the inductances per unit length, and vv v2 the speeds of the
current. Put the first of (73d) in terms of the currents. Thus,
Llv1(Cl-C2)=Lzv2CB'f ....................... (74d)
showing that the momentum of the incident disturbance equals the
sum of the momenta of the reflected and transmitted disturbances.
Corresponding lengths are compared, of course, proportional to the
speed of the current. The condition of continuity of V is therefore
identical with that of persistence of momentum.
Next, put the second of (73d) in terms of potential-differences. Thus,
which expresses that the electrification suffers no loss by the splitting.
The condition of continuity of C is therefore equivalent to that of the
persistence of electrification.
Multiply the first of (73d) into (75d) ; the second of (73d) into (74d) ;
the two members of (73d) together; and (74d) into (75d). The
results are
? - Of) = Lfft,
•
which are equivalent expressions of the fact of persistence of energy,
while the last of (76d) is the equation of transfer of energy. That it
should be equivalent to the others will be understood on remembering
that the energy is transferred at speed vl or v2, according to position.
We have, therefore, three things that persist, electrification, momen-
tum, and energy, and these are expressed most simply by the two
equations (73d) and by their product. If the continuity of V could be
violated at the surface across the dielectric common to the two circuits
152 ELECTRICAL PAPERS.
at their junction, there would be a surface magnetic-current ; and if the
continuity of C could be violated, there would be a surface electric-
current. These statements are implied in the general equations
-curlE = 47rG, curlH = 47rr, ................ (lid)
where E and H are the electric and magnetic forces, T and G the
electric arid magnetic currents. That is, tangential continuity of E
implies normal continuity of G- (or of the induction, since it, like G, can
have no divergence) ; and tangential continuity of H implies normal
continuity of F, and therefore, in our special case, of electrification. In
fact (73d) express the same facts as (lid) do generally.
Now the continuity of V and C is violated at the boundaries of an
isolated disturbance (e.g., T= constant in a certain part of the circuit,
and zero before and behind). Then we do have the surface electric and
magnetic currents on the front and back of the disturbance. It should,
however, be stated that the conception of an isolated disturbance is
merely employed for convenience of description and argument. Practi-
cally, there cannot be abrupt discontinuities ; we must make them
gradual. Then the surface-currents become real, with finite volume-
densities.
The ratio of the reflected to the incident wave is given by
and is positive or negative according as the impedance of the second
circuit is greater or less than that of the first. The abolition of
reflection is therefore secured by equality of impedances, irrespective of
any change of type that does not conflict with this equality. Every
element of the transmitted wave therefore carries forward, in passing
the junction, its potential-difference, current, electrification, momentum
and energy unchanged, but is changed in length in the same ratio (in-
versely) as the speed of the current is changed.
In a similar manner, we can determine fully what happens when a
disturbance travelling along one distortionless circuit is caused to
divide between any number of others, of any types. We have merely
to ascertain the magnitude of the reflected wave in the first circuit.
Let V^ and Ul be the incident and reflected waves. Then, correspond-
ing to (78d), we shall have
where / is the resultant impedance of all the other circuits (instead of
L2v2, that of one only), viz. the reciprocal of the sum of the reciprocals
of their separate impedances. Knowing thus U^ in terms of V^ we
know their sum. But this is the common potential-difference in all the
transmitted waves, which are therefore known, since by dividing by
the impedance of any circuit we find the current. As regards the
attenuation as the disturbances travel away from the junction, that
must be separately reckoned for each circuit, according to the value of
RfL, in the way before described. There will be found to be the
previously-mentioned persistences, provided all the waves are counted,
including the reflected in the first circuit.
ELECTROMAGNETIC INDUCTION AND ITS PROPAGATION. 153
Now put any number of distortionless circuits in sequence. If their
impedances be equal, we know, by the above, that a disturbance will
travel from end to end without any reflection at the junctions. It will
vary in its length and in its speed, and also in the rate at which it
attenuates, but there will be no tailing, however many changes there
may be in the values of R and L. By pushing this to the limit, we
arrive at a circuit in which li and L vary in an arbitrary manner
(functions of #), whilst K varies in the same way as It, and S in the
same way as L. The impedance is a constant, but the rate of attenua-
tion and the speed vary in different parts of the circuit.
If we start an isolated disturbance at one end, it will travel to the
other without tailing. But it will be distorted on the journey, owing
to the variable speed of its different parts and the variable attenuation.
But as regards the reception of the wave, there is no distortion what-
ever. For, on arrival at the distant end, where we may place the
absorbing resistance, every element of the wave has gone through the
same ordeal precisely, passing over the same resistances in the same
sequence and at the same speed at corresponding places, so as to arrive
at the distant end in the same time, attenuated to the same extent.
Similarly there is no intermediate distortion as regards the succession
of values of V and C at any one spot. There is only distortion when
it is the wave as a whole that is looked at, comparing its state at one
instant with that at another. And if we should cause this wave to
start in a uniform circuit, then pass into an irregular one as just
described, and finally emerge in a uniform circuit again, it will then
have recovered its original shape, every part being attenuated to the
same extent.
As regards the time taken to pass over a distance x in the variable
circuit, we have to solve the kinematical problem : given the path of a
particle, and its speed at every point, find the time t taken. Thus,
. . .
taken between the proper limits, wherein v is to be a function of x.
The attenuation suffered in this journey is more easily expressed. Go
back to the former case of any number of uniform distortionless circuits
of equal impedance joined in sequence. The attenuation produced in
passing through any number of them is the product of their separate
attenuations, i.e.,
where Rv j?2, ..., are the resistances of the separate sections, and Lv
the common value of the impedances. As this is independent of the
number of sections or their closeness, we see that in our variable circuit
the attenuation in any distance is expressed by the right member of
wherein 2 R represents the total resistance of the circuit in that
distance, or \Rdx between the proper limits, R being a function of x.
The above-given demonstration of the properties of the variable
distortionless circuit, which is rather a curiosity, depends entirely upon
154 ELECTRICAL PAPERS.
our previous proof that the abolition of reflection at the junction of a
pair of simple distortionless circuits is obtained by equality of imped-
ances, irrespective of any change that may take place in the resistances.
The following is also of some use. Go back to the fundamental
equations
......... (Bid)
wherein V means d/dx, and p means d/dt. Now assume Pr=LvC,
makin them become
-VC = S(K/S+p)(LvC). )"
If our assumption can be justified, these equations must become
identical. They do become identical if 1!/L = K/S, and Lv = constant ;
becoming
-vVF=(E/L+p)K ........................ (83d)
This is for the positive wave. The assumption V= - LrC again makes
(Sid) identical under the same conditions, the resulting equation being
(83f/) with the sign of v changed. The necessary conditions may be
written
R/K=L/S=(Lv)2 = constant; ................... (Bid)
and since we have made no assumption as to the constancy of JR, L, K,
and S, we see that R and L are left arbitrary, any functions of x. Or,
what comes to the same thing, RJL and v are arbitrary, making the
attenuation and the speed variable, but without any tailing.
A third way is to examine what happens when we place a bridge of
conductance k across the junction of two distortionless circuits of
different types, but of the same impedance, along with a resistance r in
the circuit at the same place. The two conditions, using the former
notation, are
1
; /"
from which, Pi/ r3 = 1 + r/2Lv + (k/2Sv)(l + r/Lv), \
J ............. (b
= r/2Lv - (k/2Sv)(l + r/Lv),
which give the ratios of incident and reflected to transmitted wave.
We destroy the reflection by
r/Lv = k/
and then the attenuation is
due to r and k. An infinite number of these r's and &'s in succession,
placed infinitely close together, leads to the expression (BOd).
We can also go a little way towards finding what occurs when the
only condition is Lv = constant, so that there is tailing. For we then
have, at a single junction,
F^ = (1 + r/2Lv) ~l(l +k/2Sv)-1 ;
and therefore, when the distribution of r and k is made continuous,
SOME NOTES ON THE TELEPHONE AND ON HYSTERESIS. 155
the attenuation of the head of a disturbance in passing through any
distance is
e-R\iZL» ,. ^-AY'J.s'/.
j
if 7^ be the total resistance and Kt the total conductance of the leakage
in that part of the circuit. But we cannot similarly estimate to what
extent the total charge and momentum have attenuated, as we could
when the circuit was uniform, because the attenuation now occurs at a
different rate in different parts of the tail, and we are not able to trace
the paths followed by the different parts of a charge as it splits up
repeatedly. The determination of the exact shape of the tail is of
course an infinitely more difficult matter. But an approximation may
be obtained by easy numerical calculations, if we concentrate the resist-
ance and leakage in a succession of points.
NOTE (Nov. 30, 1887). — The author much regrets to be unable to
continue these articles in fulfilment of Section XL., having been
requested to discontinue them.
XXXVI. SOME NOTES ON THE THEORY OF THE
TELEPHONE, AND ON HYSTERESIS.
[The Electrician, Feb. 11, 1887, p. 302.]
As was found in the early days of the telephone, its cores need to be
permanently magnetised before it becomes efficient. I refer, of course,
to the ordinary magnetic telephone, in which an iron disc is attracted
by an electromagnet, which does not differ essentially from a common
Morse instrument with a flexible armature, with the important addition
that the electromagnet is permanently polarised. The permanent
magnetisation may be communicated by a permanent current in the
circuit, or, in the usual way, by employing a permanent magnet on
whose pole or poles the coils are placed. But the permanent magnetisa-
tion, except of the iron disc, is not essential. Thus we may abolish the
magnet and core from the telephone, leaving only the coil and disc, and
produce the necessary permanent field of force by means of an external
magnet suitably placed. The efficiency is then greatly increased by
inserting a soft-iron core in the coil. Similarly, we may destroy the
efficiency of a complete telephone by an external magnet, or we may
increase it, by suitably placing the external magnet so as to, in the first
place decrease, and in the second increase the strength of the permanent
magnetic field. And if we carry the destruction of the magnetic field
by the external magnet so far as to reverse it, and bring it on again
strongly enough, we restore the efficiency of the telephone. That is, the
permanent polarity may be of either kind. The disc is strongly
magnetically attracted in either case, and that is the really essential
thing. Most of these facts, if not all, are pretty well known, but it
appears to be different as regards their explanation.
156 ELECTRICAL PAPERS.
A good many years ago I read in Mr. Prescott's work on " The Tele-
phone," an article by Mr. Elisha Gray on the subject, containing some
of the above facts, and, in particular, describing the effect of a permanent
current in the circuit. He looked upon the necessity of a permanent
field of force as a great mystery, and suggested some reasons for its
necessity that appeared to me to be unwarranted and inadequate. I
now observe that Professor S. P. Thompson, in his recent paper, " Tele-
phonic Investigations," remarks upon this question (The Electrician, Feb.
4, 1887, pp. 290, 291). Whilst not explaining the necessity of a per-
manent field, he brings in to complicate the thing such matters as
hysteresis and the curve of induction referred to magnetic force, which
do not appear to be materially concerned. I have very little acquaint-
ance with telephonic literature, and, therefore, it may happen that the
following explanation has been already well threshed out, and accepted
or proved to be erroneous, as the case may be ; but the perusal of the
remarks of the above authority has suggested to me that the following
explanation may be not only generally useful, but even absolutely novel
to many of my readers.
The stress between the iron disc and the poles of the electromagnet
varies, under similar circumstances, as the square of the intensity of
magnetic force in the space between them. There is no occasion to
consider the relative intensity in different places, or to perform integra-
tions, as we have merely to deal with the fundamental fact of the stress
on the diaphragm varying as the square of the magnetic force. Now, as
we cause this diaphragm to execute forced vibrations by varying the
stress upon it, we should make the variations of stress as great as pos-
sible in order to obtain the greatest amplitude of vibration, and the
greatest intensity of sound from it.
Suppose, then, that there is a permanent field of intensity H, produc-
ing a steady stress proportional to H'2, and that we vary the stress by-
means of the magnetic force of undulatory currents in the coils. Let h
be the amplitude of the undulations of magnetic force, small in com-
parison with H, so that we vary the real magnetic force from H - h to
H+h, through the range 2h, This is quite independent of H, so
that if it were a mere question of the intensity of magnetic force,
we could just as well do without the permanent field, except for a
reason to be mentioned later. But the stress varies from being pro-
portional to (H-lif to (H+h)2; or the range is 4:Hh, not troubling
about any constant multiplier. That is, the stress-variation is pro-
portional to the product of the intensity of the permanent magnetic
force into that of the undulatory magnetic force. This contains the
explanation.
We see at once that it is in at least approximate agreement with facts.
For, with the same weak undulatory current passing, which keeps h
constant, we know that the intensity of sound continuously increases as
we increase the intensity of the permanent field. And, keeping the
permanent field the same, we know that the intensity of sound con-
tinuously increases as we increase the amplitude of the current-undula-
tions, and therefore h. The question of exact proportionality is an
SOME NOTES ON THE TELEPHONE AND ON HYSTERESIS. 157
independent one. We have got already what appears to be the main
explanation.
Now to consider some other points. It has been assumed for
simplicity that H was several times //. In a telephone U is a very large
multiple of h under ordinary circumstances. But as H is reduced, or h
increased sufficiently, the effects change. Thus, if H=h, the magnetic
force varies from 0 to 2k, and the stress from 0 to (2h)2. And if// is
less than h, the magnetic force varies from a negative to a positive value,
whilst the stress varies from a positive value through zero to another
positive value. In the extreme, when the permanent field is altogether
abolished, whilst the magnetic force varies from -h to + h, the stress
varies from W through zero to k'2 again. The disc is therefore urged to
execute vibrations of double the frequency of the current-undulations.
It is similar to sending reversals through a Morse instrument, when
the armature will make a rap for every current, positive or negative,
or two raps for every complete wave. This alone would be, I think,
a serious hindrance to getting good speech from a magnetic tele-
phone without a permanent field. But, with ordinary speaking
currents, the double vibrations, in the absence of the permanent
field, are insensible. On the other hand, when we put on the strong
permanent field they are non-existent, i.e., in the stress-variations,
as there is no reversal of the magnetic field, but only a change in
its intensity.
But we may easily examine the effect of h alone, or in combination
with H of a similar strength, by means of a vibrating microphone
sensitively set, producing a very large variation of current in the circuit
of battery, microphone, and telephone. Here the current is equivalent
to the co-existence of a permanent current and of an undulatory current,
and the latter may be made not insignificant compared with the former,
but even J or J its strength. It is not a matter of indifference now
which way the current goes. In one case the permanent current
increases, and in the other it decreases the permanent magnetic field of
the magnet, producing corresponding changes in the intensity of the
sound. We may cancel the permanent field by an external strong
magnet, approximately, or make H small compared with h. Then the
disc is attracted both when the current is above and when it is below
its mean strength.
We cannot increase the efficiency of a telephone indefinitely by multi-
plying the intensity of the permanent field. In the first place, the disc
becomes stiffened under strong attraction, so that ultimately a large
increase in the stress makes little difference in its displacement. Again,
when the core is very strongly magnetised, we may expect that the
effective inductivity of the core, so far as variations in the magnetic
force are concerned, will be reduced, so that undulations of current of
given amplitude will not continue to produce stress-variations propor-
tional to the amplitude of the current.
There are many other things concerned, of course, between the stress-
variation and the intensity of sound, especially mechanical; as, for
instance, the multiplication in the intensity of certain tones, especially
158 ELECTRICAL PAPERS.
the fundamental of the disc, which has also the disagreeable result or
keeping up a sound after it should have ceased.
The application of the preceding is not merely to the telephone, but
to various electromagnetic, instruments. I frequently make use of the
multiplying power of a permanent magnetic field. For example, to
make a trembler-bell go with a weak current • or to make an electro-
magnetic intermitter go firmly with a current that, unassisted, would do
nothing. Then a strong permanent magnet takes the place of a strong
permanent current. It should be so placed as to increase the strength
of field due to the electromagnet.
In the other way of getting power, by having a movable coil in a
strong permanent field, first done, I believe, by Mr. Gott in 1877
(Journal S.T.E., Vol. V., p. 500), the action is different, as it is the
electromagnetic force on the moving coil that is operative. There
is no stress on the coil when no current passes in it. But when a
current passes, the torque may be taken to be proportional to the
intensity of the permanent field and to the current passing, as in
the other case.
In conclusion, a few words, from my own point of view, of course, on
the subject of the hysteresis which has lately become prominent, and
which has been, perhaps, rather overdone by some writers. It is, sub-
stantially, an old thing in a new dress. Iron exposed to magnetising
force usually, perhaps always, more or less, becomes magnetised intrinsi-
cally as well as elastically, just as ductility is probably always in action
to some extent in a strained elastic spring. Thus, in changing the
elastic magnetisation, which does not involve any recognised or as yet
recognisable dissipation of energy, we change the intrinsic magnetisation,
which does. But that there is no sensible dissipation of energy in an
iron core placed in a rapidly intermittent or undulatory magnetic field
of moderate strength I assured myself of experimentally some years ago,
as I mentioned in The Electrician for June 14, 1884 [vol. I., p. 370]. 1
repeated the experiments in a far more effective form last year (The
Electrician, April 23, 1886), [vol. IL, p. 43]. The method is very simple
and obvious, being merely to show that iron, when sufficiently divided,
is exactly equivalent to self-induction. Use the differential telephone,
or the Bridge. The former is a handy little thing, but the latter is
much more adaptable and generally useful. Take two coils of the same
resistance but of widely different inductances, and complete the balance
by making up the deficit with iron. If sufficiently divided, the changed
resistance due to dissipation in the iron vanishes or becomes exceedingly
small. I formerly used a bundle of the finest iron wires I could get,
and the residual effect was small.
In the repetition I used iron dust, worked up with wax into solid
cores (1 wax to 5 or 6 iron by bulk), and the residual effect is far
smaller, scarcely recognisable. But if the magnetising force be made
stronger there is a small increased resistance, which can hardly be due
to the Foucault or Farrago currents in the insulated dust. It is possibly
due to hysteresis. But at the same time the variation in the inductivity
is recognisable, so that the effect is complex. It is clear that in the
ELECTROSTATIC CAPACITY OF OVERGROUND WIRES. 159
case of telephone-speaking currents, dissipation (except F.) is nowhere,
whether the core be permanently magnetised or not.
We require strong forces to make hysteresis important. Even then
it is probable that when the variations of force are very rapid (undula-
tory, not with jerks) dissipation due to hysteresis may be considerably
reduced, and the results of Ewing and Hopkinson not be applicable.
XXXVII. ELECTROSTATIC CAPACITY OF OVERGROUND
WIRES.
[The Electrician, Sept. 25, 1885, p. 375.]
IN the late Prof. F. Jenkin's "Electricity and Magnetism" (p. 332,
first edition) is a formula for the capacity of an overhead wire. Owing
to the remark there made, that experiment gave results nearly double
as great as the formula, which was attributed by him to induction
between the wires and the posts and insulating supports, and thinking
that the presence of neighbouring wires should have a marked influence
in increasing the capacity, owing to the neighbouring wires being
earthed, I verified this by working out the theoretical formulae for the
capacities (self and mutual) of overground parallel wires, and applying
them numerically in a special case. [Vol. I., Art. xii., p. 42.] With
one additional parallel wire the increase of the capacity of the first was
1 1 per cent. ; with three additional it was 24 per cent. As to further
increase by more wires, it would not be very great, as they would be
practically much further away. As a guess, it might run up to 50 or
60 per cent., with a large number of wires, but of course it would
depend materially upon their mutual distances and height above the
ground.
The recent measurements of capacities of wires in the North of
England supply some definite information. Taking the case of a wire
20 feet above the ground, of diameter '08 inch, the calculated capacity,
supposing there to be no other wires (nor trees, etc.), is '0095 mcf. per
mile. The average result observed is given in Mr. Preece's paper (The
Electrician, Sept. 18, 1885, p. 348) as -0120 with the other wires in-
sulated, and '0142 when earthed. And for the iron wire, '171 inch
diameter, supposed 20. feet above the ground, the similar three results
are -0103, -0131, and '0169. I take v = 3010 instead of the 28808
centim. used in the paper referred to [vol. I., p. 44].
In both cases we may observe that the experimental result with
wires insulated is about midway between the calculated result and the
experimental result with wires earthed ; so that it would appear that
the influence of surrounding objects (other than neighbouring wires
earthed) in increasing the capacity was about equal to that of the
neighbouring wires themselves. This might, of course, be true in some
particular case, but we cannot safely conclude it from the above, on
account of leakage, as may be seen thus. If the wire experimented on
160 ELECTRICAL PAPERS.
were perfectly insulated from earth through the poles, whilst the other
wires (though insulated at the ends) were so very badly insulated at
the poles that they could be considered as connected to earth, it is clear
that a measurement of capacity of the first wire would give the highest
result. And this would be true with fair insulation, if the total charge
could be observed. But when the observation is made by throw of
needle, only a part of the charge is observed, the remainder (due to the
leakage of the neighbouring wires) going in slowly, or coming out
slowly when discharge is taken. In any case, however, the effect of
the imperfect insulation of the neighbouring wires is to make the
apparent capacity greater, and so reduce the difference between the
capacity with wires insulated and to earth. Thus, bettering the insula-
tion would shift the middle results above given towards the lower.
How far this operates might perhaps be experimentally determined
by charging the first wire with the others insulated, then waiting a
little, and observing the extra charge produced by suddenly earthing
the other wires. If the insulation be bad, the extra charge will be nil \
if first-rate, it might amount to nearly the full difference.
XXXVIII. MR. W. H. PREECE ON THE SELF-INDUCTION
OF WIRES.
[Sept. 24, 1887 ; but now first published.]
A VERY remarkable paper "On the Coefficient of Self-Induction of
Iron and Copper Telegraph Wires " was read at the recent meeting of
the B. A. by William Henry Preece, F.R.S., the eminent electrician.
This paper will be found in The Electrician, Sept. 16, 1887, p. 400. It
contains an account of the latest researches of this scientist on this
important subject, and of his conclusions therefrom. The fact that it
emanates from one who is — as the Daily News happily expressed it in
its preliminary announcement of Mr. Preece's papers — one of the
acknowledged masters of his subject, would alone be sufficient to
recommend this paper to the attention of all electricians. But there is
an additional reason of even greater weight. The results and the
reasoning are of so surprising a character that one of two things must
follow. Either, firstly, the accepted theory of electromagnetism must
be most profoundly modified ; or, secondly, the views expressed by
Mr. Preece in his paper are profoundly erroneous. Which of these
alternatives to adopt has been to me a matter of the most serious and
even anxious consideration. I have been forced finally to the con-
clusion that electromagnetic theory is right, and consequently, that
Mr. Preece is wrong, not merely in some points of detail, but radically
wrong, generally speaking, in methods, reasoning, results, and con-
clusions. To show that this is the case, I propose to make a few
remarks on the paper.
It will be remembered that Mr. Preece, in spite of the well-known
MR. W. H. PREECE ON THE SELF-INDUCTION OF WIRES. 161
influence of resistance in lowering the speed of signalling, was formerly
an advocate of thin wires of high resistance for telephony ; but that,
perhaps taught by costly failures in his own department, and by the
experience of more advanced Americans and Continentals who had
signally succeeded with wires of low resistance, he recently signified
his conversion. Along with this, however, it will be remembered that,
although it had been previously shown how very different the theory
of the rapid undulatory currents of telephony is from the electrostatic
theory of the submarine cable, he adopted rather pronouncedly what
should, it appears, be understood to be the electrostatic theory, with
full application to telephony. It is not to be presumed that Mr.
Preece meant to deny the existence of magnetic induction, but that he
meant to assert that it was of so little moment as to be negligible. It
will also be remembered that his views were rather severely criticised
by Prof. S. P. Thompson, and that Prof. Ayrton and others pointed
out that he had not treated the telephonic problem at all. More
recently still, it may be remembered by the readers of this journal that
it has been endeavoured to explain how and why the electrostatic
theory has so limited an application to telephony. (E. M. I. and its P.,
Section XL. et seq.) [vol. IL, pp. 119 to 155.] Nothing daunted, however,
Mr. Preece now, although to some extent modifying his views as
regards iron wires, maintains that self-induction is negligible in copper-
wire circuits ; and in fact, on the basis of his latest researches, asks us
to believe that the inductance of a copper circuit is several hundred
times smaller than what it is maintained to be by experimental theorists,
and is really quite negligible in consequence. His paper is devoted to
proving this. It is necessary to examine it in detail.
(1). Mr. Preece finds the inductance of a certain iron wire to be
•00504 macs per mile. The unit employed is inconveniently large.
It is so large that, even for use with coils, I have proposed that y^^
part, or 106 centim. would be a convenient size. As regards straight
wires, however, I find that it saves much useless figuring to reckon the
inductance per centim. simply, with the result that we have a con-
veniently-sized numeric to deal with. Thus, in the present case, we
have L - 31, if L be the inductance per centim.
Now Mr. Preece tells us that the inductance of a copper circuit will
be approximately got by dividing by /*, the inductivity of the iron,
which he reckons at from 300 to 1000. This gives
L='l to '031 in copper circuits.
Let us compare with theory. The least value of the L of a copper
wire of radius r at height h above the ground is
on the assumption that the return-current is on the surface of the
ground, and that the wire-current is on its surface, so that the real
value of L is greater than this formula states. The value ranges from
10 to 30, roughly speaking, according to radius and height. Thus, as
a copper wire of 6-3 ohms per kilom. must be of radius '091 centim..
if it be only 318 centim. above the ground, the inductance is 17 '7 per
H.E.P. — VOL. n. L
162 ELECTRICAL PAPERS.
centim. This is 177 times as big as Mr. Preece's biggest estimate.
Even if we assume //-= 100, which is more in accordance with my own
measurements, Mr. Preece's estimate would be 60 times too small.
In the presence of such stupendous errors it is of course useless to take
account of the small corrections to which the above formula is subject.
A proof will be found in my paper "On Electromagnets," Journal
S. T. E. and R, vol. vn., p. 303 [vol. I., p. 101]. It is derived from
Maxwell's formula for the inductance of a pair of parallel wires by the
method of images.
(2). Mr. Preece does not seem to have observed that in measuring
the permittance of his copper-circuits he was virtually measuring their
inductance, though very roughly. Thus, if L and S be the inductance
and the permittance of a solitary suspended copper wire, per unit
length, and v be the speed of light in air, or 30 ohms, then on the
assumption of return-current on the surface of the ground, we have
LS$ = \. This gives L = (9s)~l, if s be the permittance per kilom.
in microfarads. Since Mr. Preece's copper wire was 7 '44 microf. per
261 miles, or 420 kilom., we have s=-018, and therefore L = 6 -2.
Although it is a considerable underestimate, yet we see that Mr.
Preece's enormous error has disappeared. Why it is underestimated
is mainly because the permittance is so greatly increased by the
presence of neighbouring wires, as is explained in my paper " On the
Electrostatic Capacity of Suspended Wires," Journal S. T. E. and E.,
vol. IX., p. 115 [vol. I, p. 46]. Allowing for this influence, we shall
certainly come near to the true magnitude of L. It is possible that
very carefully executed measurements by correct methods might reveal
some quite new correction, but wTe cannot expect anything amounting
to several hundred cent, per cent.
(3). Let us now briefly examine Mr. Preece's methods. First, he
tried to measure the L of a copper circuit by a differential arrange-
ment, and could not find that there was any to measure. But it will
be clear to those who are acquainted with the properties of electrical
balances that he did not go the right way to work. He supposed that
the balancing resistance balances the quantity he calls the throttling or
spurious resistance (R2 + L2n2)*, if R be the resistance, L the inductance,
and n/'2ir the frequency. This would be the impedance of the circuit
if the effect of its permittance were ignorable. But it was not, as the
permittance was, say 7 microfarads, so that the impedance formula is
quite different. But, in any case, it is not the impedance that is balanced
by resistance, but the resistance of the circuit. It is well known that
the resistance of a copper wire is not sensibly increased, unless the
undulations be excessively rapid, or the wire be very thick. And it
was not increased. Whilst corroborating theory to some extent there-
fore, Mr. Preece's argument fails completely, as his experiment proved
nothing about the impedance or the inductance, except in the indirect
way I mentioned in (2) above, which is wholly against his conclusion
that L = 0 nearly.
I should remark, however, that the proper way to observe and
measure the inductance of a copper-wire circuit is to shorten it until
MR. W. H. PREECE ON THE SELF-INDUCTION OF WIRES. 163
the effect of its permittance is insensible. The L will be found to be
about what I have stated. Why it should be shortened in this way
will be obvious when it is remembered what a very rough business the
P. 0. duplex balancing with condensers is. In fact, no attempt seems
to have been made to balance the L, nor would it be practicable under
the circumstances.
(4). " It is, however, quite another matter with iron," as Mr. Preece
remarks. It is known that the resistance of, say, a No. 4 iron wire can
easily be 2 or 3 times its steady value, when currents of telephonic
frequency are passed. But, as before, Mr. Preece supposed that he
was measuring the impedance, or rather, what it would have been had
there been no permittance, which makes a material difference. Con-
sequently Mr. Preece's results are wrong. The value of L deduced is
not related to the quantity observed in the manner he supposes. It is
not a question of small corrections, but of an entire change of method.
(5). Coming next to the " direct measurement of the time-constant
L/&" we are involved in further mysteries. How the chronograph
was made to indicate the values of L/R is not stated. But let us
assume that it did do this, and that '0044 sec. and *00667 sec. were
really the values of L/R for the copper and the iron circuits. Now one
is half as great again as the other. The resistances, too, are not widely
different. It follows that the L's are of the same order of magnitude.
But Mr. Preece argues in quite another manner. He assumes that
self-induction is negligible first, and then reasons that the time-constant
of the iron circuit would have been less than the measured '00667 sec.
in the ratio of the electrostatic time-constant of the iron to that of the
copper circuit, and should therefore have been -00624 sec.; and that the
difference -00043 was due to self-induction in the iron wire ; from which
he finds L. It is scarcely necessary to say that there is no warrant for
this singular reasoning from the point of view of electromagnetic
theory. These questions have been pretty fully worked out, but there
is no resemblance to be found between Mr. Preece's methods and those
which are, I believe, generally admitted to be correct.
The values of L come out 277 copper, 540 iron, per centim., taking
the given -0044 and '0066 sec. as the values of L/R given by the
chronograph. These values of L and L/R are much too great. It is
suggested that the chronograph figures represent something quite
different from LjR. If they represent the time of transit, the reason-
ing is equally erroneous.
(6). Mr. Preece next gives a table of the values of the impedance on
the assumptions of no permittance, and that L had the value he had
erroneously deduced, and that it was a constant. The table is quite
inapplicable, because there is permittance, a great deal. If there were
not, the figures would not represent the resistance. Nor do they
represent the impedance, which does not run up in the way Mr. Preece
makes it do as the frequency is raised. In fact, I may remark that Mr.
Preece employs such entirely novel and unintelligible methods, that it-
would surely be right that he should give some reason for the faith that
is in him.
164 ELECTRICAL PAPERS.
(7). In conclusion, I would point out what is perhaps the most
striking thing of all, in its ultimate consequences. Mr. Preece wants
to prove that L is negligible in copper circuits, being under the idea
that self-induction is prejudicial to long-distance telephony (and also
very rapid telegraphy, of course, if rapid enough). Mr. Preece has
spoken through a copper circuit of 270 x 2 miles with a clearness of
articulation that is " entirely opposed to the idea of any measurable
magnitude of L" As regards the speaking, it has been done over a
thousand (1000 x 2) miles in America. But the important thing is the
vital error involved in the reasoning. So far from being prejudicial,
precisely the contrary is the case, as I have proved in considerable
detail in this journal. [The Electrician is referred to.] Increasing
L increases the amplitude and diminishes the distortion, and therefore
renders long-distance telephony possible under circumstances that
would preclude possibility were there no inductance.
The following examples will serve to show the importance of this
matter. Take a circuit 100 kilom. long, 4 ohms and J microf. per
kilom., and no inductance in the first place. Short-circuit at both ends.
Introduce at end A a sinusoidal impressed force, and calculate the
current-amplitude at the other end B by the formula of the electrostatic
theory which Mr. Preece believes in. Let the ratio of the full steady
current to the amplitude of the actual current be p, and let the
frequency range through 4 octaves, from n — 1250 to n = 20,000, where
n - 2-rr x frequency. The values of p are
1-723, 3-431, 10-49, 58-87, 778.
It is barely credible that any kind of speaking would be possible,
owing to the extraordinarily rapid increase of attenuation with the
frequency. Nothing but murmuring would result.
Now introduce the additional datum that L has the very low value
of 2 J per centim., without other change, and calculate the corresponding
results. They are
1-567, 2-649, 5-587, 10-496, 16-607.
The change is marvellous. It is by the preservation of the currents
of great frequency that good articulation is possible, and we see that
a very little inductance immensely improves matters. There is no
" dominant " frequency in telephony. What is wanted is to have
currents of all frequencies reproduced at the distant end in proper
proportion, attenuated as nearly as may be to the same degree.
Change L to 5, which is a more probable value. Results :—
1-437, 2-251, 3-176, 4-169, 4-670.
We see that good telephony is now possible, though much distortion
remains.
Finally, increase L to 10. Results : —
1-235, 1-510, 1-729, 1-825, 1-854,
showing splendid articulation. In fact we have approximated very
considerably towards a distortionless circuit.
NOTES ON NOMENCLATURE. 165
Now, this is all done by the inductance which Mr. Preece dreads so
much, and would make out to be 0. It is the very essence of good
long-distance telephony that inductance should not be negligible.
R/Ln must be made small, a fraction. The bigger L is the better
(cceteris paribus). It is proved, not merely by theory but by the
experimental facts, especially with copper wires of low resistance. It
is not the inductance of iron that is prejudicial, nor yet its impedance,
but its high resistance. R is increased whilst L is reduced, which
is exactly the opposite to what is required for good articulation over
long circuits.
But it is impossible to treat these questions by the electrostatic
theory. Nor yet, as Mr. Preece attempts, by a mixed process, a little
bit of the electromagnetic theory put into the electrostatic. The true
theory takes both the static and the magnetic effects into consideration
simultaneously. No particular exactness need be attributed to the
above figures. What is important is the nature of the effect of self-
induction, and that it is, without entering into refined calculations, of
great magnitude. The permittance has been purposely chosen lai
XXXIX. NOTES ON NOMENCLATURE.
[The. Electrician ; Note 4, June 24, 1887, p. 143 ; Note 5, May 11, 1888, p. 27.]
NOTE 4. MAGNETIC RESISTANCE, ETC.
As there is at the present time at least a possibility of the various
words I have proposed coming into general use, I take the opportunity
of making a few casual remarks upon the subject supplementary to
those of 1885 and since. First, I observe (The Electrician, June 17,
1887, p. 114) it mentioned that I disapprove of "magnetic resistance."
This is only a part of the fact. To illustrate this, I may say that were I
investigating the theory of the dynamo, I think I should make use of
the term myself, provisionally. What is really my objection is to its
permanent use. There must always be a certain latitude allowed to in-
vestigators who do not find words ready to meet their wants. Were it
an isolated question, there would be little difficulty in finding a
perfectly unobjectionable word; but it is not an isolated question. My
aim has been to make a scheme which shall be at once theoretically
defensible and yet thoroughly practical. Bearing this in mind, I prefer
to leave a blank in the place of "magnetic resistance" at present [vol.
n. p. 125].
To illustrate the difficulties connected with nomenclature I may
mention that, last summer, I was extremely in want of a term which
should be an extension of impedance. The impedance of a circuit at a
given frequency (under stated external conditions) is quite definite
(with occasional departures due to want of proportionality between
forces and fluxes), if it be a simple circuit, or reducible to a simple
166 ELECTRICAL PAPERS.
circuit, so that the strength of the current does not vary in different
parts. But when it does, we can certainly only apply the term impedance
legitimately at the seat of the impressed force, if at a single spot ; or
else, if it be wholly localised in a part of the main circuit in which the
current does not vary, then the term impedance is again applicable. Now,
I used impedance in an extended sense, but expressly stated that it wras
only done provisionally [vol. II., p. 65]. I have since found a far better
way of expressing results, viz., in terms of "attenuation " and " distor-
tion," both very important things. The idea of attenuation, expressed
in a more roundabout manner in terms such as " diminution of ampli-
tude," and so forth, is nothing new ; the ivord " attenuation " I found
Lord Eayleigh use, and at once adopted it myself as the very thing I
wanted. " Distortion," on the other hand, I chose myself as preferable
to "mutilation" and similar words. Its meaning is obvious. Make
current-variations in a certain way at one place. If the current-varia-
tions at another place are similar, no matter how much attenuated they
may be, there is no distortion. The extremest kind of distortion is to
be found on Atlantic cables. Drawn on the same scale, there is little
resemblance between the curves at one end and at the other. Tele-
phony would obviously be impossible even were the frequency allow-
able to be sufficiently great, which is of course out of the question
under present conditions. But, only make the distortion reasonably
small at a sufficiently great frequency, and telephony is at once
possible, provided the attenuation be not of unreasonable amount.
(Frequency is Lord Rayleigh's word for " pitch," number of waves per
second.)
Referring to magnetic resistance again. A certain person once
declared that E = RC, to express Ohm's law, was nonsense ; it must be
C = EjR. This eminent scienticulist could not see the force of Max-
well's argument, that electricity could not be a form of energy because
it was only one of the factors of energy. Now, however, by the
development of the electric light rendering energy a marketable com-
modity through electric agency, there is little fear of converts being
made to these views. So we may return to E = JRC, or C = KE, if K
be the conductance. One is just as good as the other, theoretically,
and is just as meaningful. Which to use (including the ideas) is purely
a matter of convenience in the particular application that is in question.
As a general rule, resistances are more useful, because we usually deal
with wires in sequence. But if they be in parallel, conductances are the
proper things to use. With condensers, on the other hand, permit-
tances are more useful ; should, however, we join in sequence, then
elastances are the proper things. In theoretical investigations discon-
nected from special applications, the unit-volume properties conductiv-
ity, inductivity, and permittivity, are generally much more useful than
their reciprocals, resistivity ('?), [reluctivity], and elastivity. Now, in
late years, there has been some development of practical applications in
connection with the flux magnetic induction ; in theory, inductivity
would be the more convenient basis ; but several practicians find that
the reciprocal ideas, say, provisionally, "magnetic resistivity" and
NOTES ON NOMENCLATURE. 167
"magnetic resistance," are more useful. I think their choice has been
a wise one, whilst at the same time I recognise the difficulties with
which they have to contend, through " magnetic leakage," and so forth.
It is for the practicians to find practical ways of getting a round peg to
fit a square hole. They know best what they want, and whether
empirical formulae will not suit them better than more elaborate
empiricism, which could, perhaps, be scientifically better defended. For
it is clear that, beyond the region of proportionality of force to flux,
the science of magnetic induction must continue very empirical for some
time to come. 1 do not think the time has yet arrived for laying down
the law by conventions or committees in this matter (as it may have
come in more definite parts of electrical science) ; but that practical and
theoretical investigators should be allowed to develop their ideas freely.
In short, Conventions or Committees should not meddle with matters
(save very lightly) which are in a provisional stage. And I may add
that, just as treaties are made to be broken, so the laws of Conventions
will be broken as soon as ever it is found inconvenient to obey them.
The introduction of anything of the nature of officialism into scientific
matters should be strenuously opposed — in this country. It would be as
bad as the passport system. The utility of a Convention seems to
consist in the formation of a temporary consensus of opinion from
which to make fresh departures. There cannot be any finality.
Mac. — Here we are on firmer ground. There cannot, I think, be any
question that this is the right name for the practical unit of inductance,
in honour of the man who knew something about self-induction, and
whose ideas on the subject are not yet fully appreciated. This was
very much his own fault. He had the most splendid and thoroughly
philosophical ideas on electromagnetism all round, but kept them too
much in the background. Maxwell's treatise requires to be studied, not
read, before the inner meaning of his scheme can be appreciated. Had
he lived, he would probably, in some future edition, have brought his
views prominently forth ab initio, and developed the whole treatise on
their basis exclusively. Should the mac be 109 or 106 centimetres 1 If
109, which has great recommendations, then millimac will be practically
wanted, to avoid decimals. It is quite a euphonious and unobjectionable
word.
Inductometer. — Naturally, in accordance with induction, inductivity,
and inductance, this is a measurer of inductance (self or mutual) in
terms of units of inductance — macs, or millimacs. I would apply the
term to any instrument that measured inductance at once in terms of
known inductances, as resistances are compared with known resistances.
Some practical acquaintance with self and mutual induction, desultory,
but of long continuance, has gradually forced upon me the idea (not to
be easily displaced) that really practical ways of measuring inductances
should be in terms of standard inductances — or, which is the same thing,
by a properly calibrated inductometer — and not absolute measurements.
What particular method of making the comparisons is best I do not
know, nor yet how best to calibrate the inductometer. If it were a
mere question of coils of fine wire, nothing is simpler, or more expedi-
168 ELECTRICAL PAPERS.
tious, or more accurate, or more sensitive, than the immediate balancing of
the self-induction against that of an inductometer of variable inductance,
using the telephone [vol. II., p. 37 and p. 100]. The advantages and
the simplicity are so great that I think practical men might well turn
their attention to practical ways of extending the method to cases other
than those in which mere coils are alone concerned.
" Absolutism." — The most absolute of all ways of finding the in-
ductance of a coil is with a tape. Herein lies a moral of very wide
application.
NOTE 5. MAGNETIC EELUCTANCE.
There is a tendency at the present time among some writers to
greatly extend the application of the word resistance in electro-
magnetism, so as to signify cause/effect. This seems a pity, because the
term resistance has already become thoroughly specialised in electro-
magnetism in strict relationship to frictional dissipation of energy.
What the popular meaning of resistance may be is beside the point ;
ditto dimensions, etc.
I would suggest that what is now called magnetic resistance be
called the magnetic reluctance ; and when referred to unit volume, the
reluctancy [or reluctivity].
XL. ON THE SELF-INDUCTION OF WIRES.
(Phil. Mag., 1886-7. Part 1, August, 1886, p. 118 ; Part 2, Sept., 1886, p. 273;
t 3, Oct., 1886, p. 332 ; Part 4, Nov., 1886, p. 419 ; Part 5, Jan., 1887, p. 10 ;
t 6, Feb., 1887, p. 173 ; Part 7, July, 1887, p. 63 ; Part 8, now first published.]
PART I.
Remarks on the Propagation of Electromagnetic Waves along Wires outside
them, and the Penetration of Current into Wires. Tendency to Surface
Concentration. Professor Hughes 's experiments.
A SERIES of experiments made some years ago, in which I used the
Wheatstone-bridge and the differential telephone as balances of induc-
tion as well as of resistance, led me to undertake a theoretical investi-
gation of the phenomena occurring when conducting-cores are placed in
long solenoidal coils, in which impressed electromotive force is made to
act, in order to explain the disturbances of balance which are produced
by the dissipation of energy in the cores. The simpler portions of this
investigation, leaving out those of greater mathematical difficulty and
less practical interest, relating to hollow cores and the effect of allowing
dielectric displacement, were published in The Electrician, May 3, 1884,
and after [vol. I., Art. xxviii., p. 353].
This investigation led me to the mathematically similar investigation
of the transmission of current into wires. I say into wires, instead of
through wires, because the current is really transmitted by diffusion
ON THE SELF-INDUCTION OF WIRES. PART I. 169
from the boundary into a wire from the external dielectric, under all
ordinarily occurring circumstances. In the case of a core placed in a
coil, the magnetic force is longitudinal and the current circular ; in the
case of a straight round wire, the current is longitudinal and the mag-
netic force circular. The transmission of the longitudinal current into
the wire takes place, however, exactly in the same manner as the trans-
mission of the longitudinal magnetic force into the core within the coil,
when the boundary conditions are made similar, which is easily realiz-
able. Similarly, we may compare the circular electric current in the
core with the circular magnetic flux in the wire.
I also found the transfer of energy to be similar in both cases, viz.,
radially inward or outward, to or from the axis of the core or the wire.
It was therefore necessary to consider the dielectric, in order to com-
plete the course of the transfer of energy from its source, say a voltaic
cell, to its sink, the wire or the core where it is finally dissipated in the
form of heat, with temporary storage as electric and magnetic energy
in the field generally, including the conductors.
Terminating the paper above referred to, having so much other
matter, I started a fresh one under the title of "Electromagnetic Induc-
tion and its Propagation," [vol. I., Art. xxx., p. 429 ; and vol. II., Art.
xxxv., p. 39]. Having, according to my sketched plan, to get rid of
general matter first, before proceeding to special solutions, I took occa-
sion near the commencement of the paper to give a general account of
some of my results regarding the propagation of current, in which the
following occurs, describing the way the current rises in a wire, and the
consequent approximation, under certain circumstances, to mere surface-
conduction. It was meant to illustrate the previously-mentioned stop-
page of current-conduction by high conductivity. After an account of
the transfer of energy through the dielectric (concerning which I shall
say a few words later) I continue [vol. I., p. 440] : —
" Since, on starting a current, the energy reaches the wire from the
medium without, it may be expected that the electric current is first set
up in the outer part, and takes time to penetrate to the middle. This
I have verified by investigating some special cases.
"Increase the conductivity enormously, still keeping it finite, how-
ever. Let it, for instance, take minutes to set up a current at the axis.
Then ordinary rapid signalling * through the wire ' would be accom-
panied by a surface-current only, penetrating to but a small depth.
The disturbance is then propagated parallel to the wire in the manner
of waves, with reflection at the end, and hardly any tailing off. With
infinite conductivity, there can be no current set up in the wire at all.
There is no dissipation ; wave-propagation is perfect. The wire-current
is wholly superficial, an abstraction, yet it is nearly the same with very
high conductivity. This illustrates the impenetrability of a perfect con-
ductor to magnetic induction (and similarly to electric current) applied
by Maxwell to the molecular theory of magnetism. ..."
Attention has recently been forcibly directed towards the phenomenon
above described of the inward transmission of current into wires
Professor Hughes's Inaugural Address to the Society of
170 ELECTRICAL PAPERS.
Engineers and Electricians, January, 1886. This paper was, for many
reasons, very remarkable. It was remarkable for the ignoration of well-
known facts, thoroughly worked out already ; also for the mixing up of
the effects due to induction and to resistance, and the author's apparent
inability to separate them, or to see the real meaning of his results; one
might indeed imagine that an entirely new science of induction was in
its earliest stages. It was remarkable that the great experimental skill
of the author should have led him to employ a method which was in
itself objectionable, being capable of giving, in general, neither a true
resistance nor a true induction-balance (as may be easily seen by simple
experiments with coils, without mathematical examination of the theory)
— a method which does not therefore admit of exact interpretation of
results without full particulars being given and subjected to laborious
calculations. Finally, it was remarkable as containing, so far as could
be safely guessed at, many verifications of the approximation towards
mere surface-conduction in wires. This is, after all, the really important
matter, against which all the rest is insignificant.
As regards the method employed, I have shown its inaccuracy in my
paper "On the Use of the Bridge as an Induction-balance" [vol. II., p.
33], wherein I also described correct methods, including the simple
Bridge without mutual induction, and also methods in which mutual
induction is employed to get balance, giving the requisite formulae,
which are of the simplest character.
As regards the interpretation of Professor Hughes's thick-wire results,
showing departure from the linear theory, by which I mean the theory
that ignores differences in the current-density in wires, I have before
made the following remarks [vol. IL, p. 30]. After commenting upon
the difficulty of exact interpretation, I proceed :—
" The most interesting of the experiments are those relating to the
effect of increased diameter on what Prof. Hughes terms the inductive
capacity of wires. My own interpretation is roughly this. That the
time-constant of a wire first increases with the diameter " (this is of
course what the linear theory shows), "and, then, later, decreases
rapidly ; and that the decrease sets in the sooner the higher the con-
ductivity and the higher the inductivity (or magnetic permeability) of
the wires. If this be correct, it is exactly what I should have expected
and predicted. In fact, I have already described the phenomenon in
this Journal ; or, rather, the phenomenon I described contains in itself
the above interpretation. In The Electrician for January 10, 1885, I
described how the current starts in a wire. It begins on its boundary,
and is propagated inward. Thus, during the rise of the current it is
less strong at the centre than at the boundary. As regards the manner
of inward propagation, it takes place according to the same laws as the
propagation of magnetic force and current into cores from an enveloping
coil, which I have described in considerable detail in The Electrician
[vol. I., Art. xxviii. ; see especially § 20]. The retardation depends
upon the conductivity, upon the inductivity, and upon the section,
under similar boundary-conditions. If the conductivity be high enough,
or the inductivity, or the section, be large enough to make the central
ON THE SELF-INDUCTION OF WIRES. PART I. 171
current appreciably less than the boundary-current during the greater
part of the time of rise of the current, there will be an apparent reduc-
tion in the time-constant. Go to an extreme case — very rapid short
currents, and large retardation to inward transmission. Here we have
the current in layers, strong on the boundary, weak in the middle.
Clearly then, if we wish to regard the wire as a mere linear circuit,
which it is not, and as we can only do to a first approximation, we
should remove the central part of the wire — that is, increase its resist-
ance, regarded as a line, or reduce its time-constant. This will happen
the sooner, the greater the inductivity and the conductivity, as the sec-
tion is continuously increased. It is only thin wires that can be treated
as mere lines, and even they, if the speed be only great enough, must
be treated as solid conductors. I ought also to mention that the influ-
ence of external conductors, as of the return conductor, is of importance,
sometimes of very great importance, in modifying the distribution of
current in the transient state. I have had for years in manuscript some
solutions relating to round wires, and hope to publish them soon.
" As a general assistance to those who go by old methods, a rising
current inducing an opposite current in itself and in parallel conductors,
this may be useful. Parallel currents are said to attract or repel,
according as the currents are together or opposed. This is, however,
mechanical force on the conductors. The distribution of current is not
aifected by it. But when currents are increasing or decreasing, there is
an apparent attraction or repulsion between them. Oppositely-going
currents repel when they are decreasing and attract when they are
increasing. Thus, send a current into a loop, one wire the return to
the other, both being close together. During the rise of the current it
will be denser on the sides of the wires nearest one another than on the
remote sides. ..."
An iron wire, through which rapid reversals are sent, should afterwards
be found, by reason of its magnetic retentiveness, magnetized in con-
centric cylindrical shells, of alternately positive and negative magnetiza-
tion. This would only occur superficially. The thickness of the layers
•would give information regarding the amount of retardation, from which
the inductivity could be deduced. The case is similar to that of the
superficial layers of magnetization produced in a core placed in a coil
through which reversals are sent, the magnetization being then, however,
longitudinal instead of circular.
The linear theory is departed from in the most extreme manner,
when the return-current closely envelops the wire. The theory of the
rise of the current in this case I have given before [vol. n., p. 44], and
also the case of the return-current at any distance [vol. IL, p. 50]. The
investigation following in this paper is more comprehensive, taking into
account both electrostatic and magnetic induction, working down to the
magnetic theory on the one hand, and approximating towards the
electrostatic theory (long submarine cable) on the other; with this
difference, that inertia is not so wholly ignorable in the long-line case as
is elastic yielding in the case of a short wire. Nor is the variation of
current-density wholly ignorable.
172 ELECTRICAL PAPERS.
New (Duplex) Method of Treating the Electromagnetic Equations.
The Flux of Energy.
But first as regards the transfer of energy in the electromagnetic
field. This is a very important matter theoretically. It is a necessity
of a rationally intelligible scheme (even if it be only on paper) that the
transfer of energy should be explicitly definable. It is the absence of
this definiteness that makes the German methods so repulsive to a plain
man who likes to see where he is going and what he is doing, and hates
metaphysics in science.
I found that I had been anticipated by Prof. Poynting [Phil. Trans.,
1884] in the deduction of the transfer-of-energy formula appropriate to
Maxwell's electromagnetic scheme, in the main. It is, therefore, only
as having given the equation of activity in a more general form, the
most general that Maxwell's scheme admits of, and having deduced it
in a simple manner, that I can attach myself to the matter. In connec-
tion with it, however, there is another matter of some importance, viz.,
the use of a certain fundamental equation. That I should have been
able to arrive at the most general form, taking into account intrinsic
magnetization, as well as not confining myself to media homogeneous
and isotropic as regards the three quantities conductivity, inductivity,
and dielectric capacity, in a simple and direct manner, without any
volume-integrations or complications, arose from my method of treating
the general equations. I here sketch out the scheme, in the form I
give it.
Let H1 be the magnetic force and F the current. (Thick letters here
for vectors. The later investigation is wholly scalar.) Then, "curl"
denoting the well-known rotatory operator, Maxwell's fundamental
current-equation is
curlH^TrF, .............................. (1)
and is his definition of electric current in terms of magnetic force. It
necessitates closure of the electric current, and, at a surface, tangential
continuity of Hj and normal continuity of F. The electric current may
be conductive, or the variation of the elastic " displacement," say
F=C+D,
where C is the conduction-current, and D the displacement, linear func-
tions of the electric force E, thus,
k being the conductivity, and c the dielectric capacity (or CJ^TT the con-
denser-capacity per unit-volume). Equation (1) thus connects the
electric and the magnetic forces one way. But this is not enough to
make a complete system. A second relation between E: and Hx is
wanted.
Maxwell's second relation is his equation of electric force in terms of
two highly artificial quantities, a vector and a scalar potential, say A and
P, thus
E^-A-VP, ............................. (2)
ON THE SELF-INDUCTION OF WIRES. PART I. 173
ignoring impressed force for the present. From A we get down to Hj
again, thus,
curlA = B, B = /*Hi;
B being the magnetic induction, and //, the inductivity. (Here we
ignore intrinsic magnetization.)
The equation (2) is arrived at through a rather complex investigation.
From these equations are deduced the general equations of electromag-
netic disturbances in vol. ii., art. 783. They contain both A and P.
One or other must go before we can practically work the equations,
which are, independently of this, rather unmanageable, although they
are not really general, for impressed forces are omitted, and the intrinsic
magnetization must be zero, and the medium isotropic. Again — and this
is an objection of some magnitude — the two potentials A and P, if given
everywhere, are not sufficient to specify the state of the electromagnetic
-field. Try it; and fail.
Even without using these complex general equations referred to, but
those on which they are based, (1) and (2), the very artificial nature of
A and P greatly obscures and complicates many investigations. Not
being able to work practically in terms of A and P in a general manner,
and yet knowing there was nothing absolutely wrong, I went to the
root of the evil, and cured it, thus : —
As a companion to equation (1) use this,
............................. (3)
where G- is the magnetic current, or B/^TT. That this may be derived
at once from (2) is obvious. But what is of greater importance in view
of the difficult establishment of (2), is that (3) can be got immediately
independently, and that (2) is its consequence. Equation (3) is, in fact,
the mathematical expression of the Faraday law of induction, that the
electromotive force of induction in any closed circuit is to be measured
by the rate of decrease of the induction through it.
Now make (1) and (3) the fundamental equations, and ignore (2)
altogether, except for special purposes. There are several great advan-
tages in the use of (3). First, the abolition of the two potentials.
Next, we are brought into immediate contact with Ex and Hj, which
have physical significance in really defining the state of the medium
anywhere (k, ^ and c of course to be known), which A and P do not,
and cannot, even if given over all space. Thirdly, by reason of the
close parallelism between (1) and (3), electric force being related to
magnetic current, as magnetic force to electric current, we are enabled
to perceive easily many important relations which are not at all obvious
when the potentials A and P are used, and (3) ignored. Fourthly, we
are enabled with considerable ease, if we have obtained solutions relating
to variable states in which the lines of Ex and Hj are related in one way,
to at once get the solutions of problems of quite different physical mean-
ing, in which Ej and H15 or quantities directly related to them, change
places. For example, the variation of magnetic force in a core placed in
a coil, and of electric current in a round wire ; and many others.
That the advantages attending the use of (3) as a fundamental equa-
174 ELECTRICAL PAPERS.
tion are not imaginary, I have repeatedly verified. The establishment
of the general equation of activity, however, which I now reproduce
[vol. i., p. 449], shows that (3) is really the proper and natural funda-
mental equation to use. But we must first introduce impressed forces,
allowing energy to be taken in by the electric and magnetic currents.
In (1) and (3), \ and HJ are not the effective electric and magnetic
forces concerned in producing the fluxes conduction-current, displace-
ment, and induction, but require impressed forces, say e and h, to be
added. Let E = E: + e, and H = HT + h ; then we shall have
B = /xH, C = £E, D = cE/47r, ................ (4)
as the three linear relations between forces and fluxes ; two equations,
r = C + D, G = B/47r, ....................... (5)
showing the structure of the currents ; and two equations of cross-
connection,
curl(H-h) = 47rr, ............................ (6)
- curl (E - e) = 4?rG ............................. (7)
Next, let Q be the dissipativity, U the electric energy, and T the mag-
netic energy per unit volume, defined thus :
Q = EC, U = iBD, T = JHB/47r, .............. (8)
(according to the notation of scalar products used in my paper in the
Philosophical Magazine, June, 1885 [vol. ii., p. 4]; c, k, and p are in
general the operators appropriate to linear connection between forces
and fluxes). Then we get the full equation of activity at once, by
multiplying (6) by E, and (7) by H, and adding the results. It is
er + hG = EF + HG + div V(E - e)(H - ,
= Q+U+ r+divV(E-e)(H-h)/4ir,j"
where div stands for divergence, the negative of Maxwell's convergence.
The left side showing the energy taken in per second per unit volume
by reason of impressed forces, and Q+ U+T being expended on the
spot in heating, and in increasing the electric and magnetic energies, we
see that V(E - e)(H - h)/4?r is the vector flux of energy per unit area
per second, or the energy-current density. The appropriateness of (7)
as a companion to (6) is very clearly shown.
The scheme expressed by (4), (5), (6), (7) is, however, in one respect
too general. The magnetic current is closed, by (7) ; but that does not
necessitate the closure of the magnetic induction, which is necessary to
avoid having unipolar magnets. Hence
divB = 0 ................................ (10)
is required to meet facts, in addition to (4), (5), (6), (7). There is no
magnetic conduction-current with dissipation of energy, analogous to
the electric conduction-current.
As regards the ir.eunings of e and h, in the light of dynamics they
define themselves in the equation of activity ; that is, so far as the
ON THE SELF-INDUCTION OF WIRES. PART I. 175
mere measure of impressed forces is concerned, apart from physical
causation. Thus, e is the amount of energy taken in by the electro-
magnetic field per second per unit volume per unit electric current, and
h is similarly related to magnetic current. Under e have to be included
the recognised voltaic and thermoelectric forces. But besides them, e
has to include the impressed electric force due to motion in a magnetic
field, or VvB, if v is the vector velocity, necessitating a mechanical
force VFB. It has also to include intrinsic electrization, the state
which is set up in solid dielectrics under the continued application of
electric force. Thus,
J = ce/4?r
connects the intensity of intrinsic electrization J with the correspond-
ing e.
I can find only two kinds of h. First, due to motion in an electric
field, viz., 47rVDv, necessitating a mechanical force 47rVDG ; and,
secondly, much more importantly, intrinsic magnetization I, connected
with the corresponding h thus,
As regards potentials, there are, to match the two electric potentials
A and P, two magnetic potentials, say Z and 12 ; 0, being the single-
valued scalar magnetic potential, and Z the vector-potential of the
magnetic current, some of whose properties in relation to dielectric and
conductive displacement I have worked out in the paper referred to
before.
As regards the general equations of disturbances, like Maxwell's (7),
chapter xx. vol. ii., they are far more a hindrance than an assistance in
general investigations. But when we come to a special investigation,
and need to know the forms of the functions involved, then we may
eliminate either E or H between (6) and (7), and use the suitable
coordinates.
Application of the General Equations to a Bound Wire with Coaxial Return-
Tube. The Differential Equations and Normal Solutions. Arbitrary
Initial State.
We may make use of the above equations at the start, in passing to
the question of the propagation of disturbances along a wire, after
which the investigation will be wholly scalar. Put e = 0 in (7); then
we see that we cannot alter the magnetic force at a point without
giving rotation to the electric force. Now, as in a steady state the
electric force has no rotation (away from the seat of impressed force), it
follows that under no circumstances (except by artificial arrangements
of impressed force) can we set up the steady state in a conductor
strictly according to the linear theory. We may approximate to it very
closely throughout the greater part of the variable period, but it will be
widely departed from in the very early stages.
Let there be a straight round wire of radius alt conductivity &„
inductivity pv and dielectric capacity c: ; surrounded up to radius a2
by a dielectric of conductivity k% inductivity /*2, and dielectric capacity
176 ELECTRICAL PAPERS.
C2 • in its turn surrounded to radius a3 by a conductor of &3, /x3, and c3.
This might be carried on to any extent ; but we stop at r = ag, r being
distance from the axis of the wire, as the outer conductor is to be the
return to the inner wire.
Let the magnetic lines be such as would be produced by longitudinal
impressed electric force, viz. circles in planes perpendicular to the axis
of the wire, and centred thereon. Let H be the intensity of mag-
netic force at distance r from the axis, and distance z along it from a
fixed point. Use (6), with h = 0, to find the electric current. It has
two components, say F longitudinal, or parallel to z, and y radial, or
parallel to r, given by
.
r dr dz
We have also E = />r, if p is a generalised resistivity, or
Now use equation (7), with e = 0. The curl of the longitudinal and
of the radial electric force are both circular, like H, giving
%L\ .......................... (13)
dz J
In this use (11), and we get the H equation, which is
d 1 d TT d'2H A T TT ff /i ^\
-j --- j- rH+^nr = 4:TriikH+iicH. ................. (14)
dr r dr dz2
The suffixes 15 2, and 3 are to be used, according as the wire, dielectric,
or sheath, is in question.
In a normal state of free subsidence, d/dt =p, a constant. Let also
d2/dz* = -m2, where m? is a constant, depending upon the terminal
conditions. Also, let
(15)
Then .(14) becomes j-~irH+fff=0; ........................... (16)
which is the equation of the JI(ST) and its complementary function,
which call K^ (sr). Thus, for reference,
s4?4
ON THE SELF-INDUCTION OF WIRES. PART I.
177
We have therefore the following sets of solutions, in the wire,
dielectric, and sheath respectively, the A's and B's being constants : —
Hl = AJ^s^r) cos (mz + 0)ept,
AlJl(slr)m sin (mz + 6)ept,
l = A1J0(sLr)sl cos (mz + 6)tpt,
cos
1 (S27') )
{ A2J0(s2r
f V)
lV COS
^s./} }m sin
(18)
To harmonise these, we have the boundary conditions of continuity
of tangential electric and magnetic forces, and of normal electric and
magnetic currents (or of magnetic induction). Thus, yl = y2 and
Us
i
- (PiSjp^J^a^K^s^), I
iXw) = (/>i51//>252)/0(^i)^i(^i)
- J^aJJ^aJ. ]
As there is to be no current beyond the sheath, y3 = 0, or H3 = 0, at
'/• = ay This gives
^=-(^3) ............................ (20)
This, and the conditions y3 = y2, and /)3F3 = />2r2, at r = a2, give us
(A A + B
....(21)
whence, eliminating ^3 by division, and putting for ^42 and B2 their
values in terms of Av through (19), we obtain the determinantal equa-
tion of the p's for a particular value of m2. It is
....(22)
where the dots indicate repetition of the fraction immediately over
them.
Before proceeding to practical simplifications, we may in outline
continue the process of finding the complete solution to correspond to
any given initial state. The m's must be found from the terminal
conditions. Suppose, for example, that the wire, of length I, forms a
closed circuit, and that the sheath and the dielectric are similarly
H.E.P. — VOL. II. M
178 ELECTRICAL PAPERS.
closed on themselves. Then, clearly, we shall have Fourier periodic
series, with
m = 0, 27T/J, 47r//, GTT/I, etc.
If, again, we desire to make the sheath the return to the wire, with-
out external resistance, join them at the end z = 0 by a conducting-
plate of no resistance, placed perpendicular to the axis ; and do the
same at the other end, where z = I. This will make
y = 0 at z = 0, and at z = l;
will make the 0's vanish, and make
m = 0, TT/I, Sir/I, STT//, etc.
Each of these ??i's has its infinite series of p's, by the equation (22).
Now, as regards the initial state, the electric field and the magnetic
field must be both given. For, although the quantity H, fully
expressed, alone settles the complete state of the system after the first
moment, yet at the first moment (when the previously acting impressed
forces finally cease) the electric field and the magnetic field are inde-
pendent. The energy which is dissipated according to Joule's law has
two sources, the electric and the magnetic energies. Now we may, by
longitudinal impressed force, set up a certain distribution of magnetic
energy, without electric energy. Or, having set up a certain magnetic
and a certain electric field by a particular distribution of impressed
force, we may alter it in various ways, so as to keep the magnetic field
the same whilst we vary the electric field. So both fields require to be
known, or equivalent information given.
We may then decompose them into the proper normal systems by
means of the universal conjugate property derived from the equation of
activity, that of the equality of the mutual electric energy of two com-
plete normal systems to their mutual magnetic energy [vol. I., p. 523.]
Thus, if Un and Tn are the doubles of the complete electric and
magnetic energies of any normal system, and U01 is the mutual electric
energy of the initial electric field and the normal electric field in ques-
tion, and TQl is the mutual magnetic energy of the initial magnetic field
and the normal magnetic field, we shall have
^=7r-r01 (23)
uu~ Jn
as the expression for the value of the coefficient Av which settles the
actual size of the normal system in question. Equal roots require
further investigation. This would complete the theoretical treatment.
It is best to use the electric and magnetic forces as initial data in the
general case. As regards potentials, we cannot express the electric
energy in terms of merely the electric potential and the electrification,
but require to use also the vector-potential Z and the magnetic current.
Simplifications. Thin Return Tube of Constant Resistance. Also fietum
of no Resistance.
Now there are several important practical simplifications. Suppose,
first, that the thickness of the sheath is only a small fraction of its
ON THE SELF-INDUCTION OF WIRES. PART I. 179
distance from the axis. Then it may be treated as if it were infinitely
thin, making the sheath a linear conductor; of course its resistance
may remain the same as if of finite thickness. Let a4 be the very small
thickness of the sheath, then the big fraction on the left side of (22)
will become
(/0 + WjJJKj - (K0 + s^K^J,, , _ 1 J^-JfiKu }_ J_.
(J, +W2)^l - (*! + WJWl ' *3«4 Jfl - W 3 3 " «A '
wherein J2 and K2 are derived from Jl and Kt as the latter are derived
from J0 and KQ. So the left side of (22) will become
(24)
The inductivity of the sheath is now of no importance. Being on the
outer edge of the magnetic field, the thinness of the sheath makes its
contribution to the magnetic energy be diminished indefinitely.
Again, in' important practical cases, the resistance of the return is
next to nothing in comparison with that of the wire. Then put p3 = 0
in (22). This makes the left side vanish, and then we sweep away the
denominator on the right side, and get the determinantal or differential
equation
"MpMs^J^
Although we may have the return of nearly no resistance and yet of
low conductivity (as in the case of the earth), yet it cannot be quite
zero without infinite conductivity, which is what is here assumed. The
result is that we shut out the return-conductor from participation,
except superficially, in the phenomena. (25) will result from the
condition />2F2 = 0, or F2 = 0, at r = az; that is, no tangential current,
or electric force, in the dielectric close to the sheath. If there could be
any, it would involve infinite current-density in the sheath. As it is,
there is none, and the return-current has become a mere abstraction, to
be measured by the tangential magnetic force divided by 47r, and turned
round through a right angle on the inner boundary of the sheath. In
a similar manner, if we make the wire infinitely conducting (or of in-
finitely great inductivity * either) the wire will be shut out. Then the
magnetic and electric fields are confined to the dielectric only, and we
shall have purely wave-propagation, unless it be a conductor as well.
Now, with the return of no resistance, let the dielectric be non-
conducting and the wire non-dielectric, or ^ = 0, &2 = 0. The most
important simplification arises from the smallness of S2«2. For we have
- s22
* [The case, parenthetically mentioned, of infinite inductivity, though resem-
bling that of infinite conductivity in excluding magnetic disturbances from the
body of the conductors, differs widely from it in other respects. Considering here
only the effect on a train of waves sent along the conductors, the effect of increas-
ing conductivity with constant inductivity is a tendency to surface-concentration
and also to a state of perfect slip, without attenuation. But the effect of increas-
ing inductivity is a tendency to surface-concentration together with large attenua-
tion in transit. The S.H. solutions will give more details on this point.]
180 ELECTRICAL PAPERS.
If the length I of the line is a large multiple of the greatest transverse
length «., we are concerned with, m2 is made a small quantity — very
small when the line is miles in length, except in case of the insignificant
terms involving large multiples of TT in m = mr/L Again, (/*/)"* is the
speed of light through the dielectric, so that unless p be extravagantly
large /*2cp2 is exceedingly small also. Thus, with moderate distance of
return-current, s.2a2 is in general exceedingly small.
Therefore, in the expressions (17), take first terms only, making
(26)
V = - V-
These, used in (25), bring it down to
(27)
concerning which, so far as substantial accuracy is concerned, the only
assumption made is that the return has no resistance.
We have now the following complete normal system : —
•) cos(mz+6)cpt,
)m sin (mz + 0)ept,
')slcos(mz+0)€pt) r
47ry2 = B(sjr)-lm sin (mz + 6)<.pt,
where B = A(p1sl/p.2)J()(s1al) +
The longitudinal current and electric force in the dielectric vary as
the logarithm of the ratio a.2fr, vanishing at /• = a.,. The radial com-
ponents vary inversely as the distance. Numerically considered, the
longitudinal electric force is negligible against the radial, which is
important as causing the electrostatic retardation on long lines. But,
theoretically, the longitudinal component of the electric force is very
important when we look to the physical actions that take place, as it
determines the passage of energy from the dielectric, its seat of trans-
mission along the wire, into the conductor, where it is dissipated.
"Regarding (28), however, it is to be remarked that, on account of the
approximations, the dielectric solutions do not satisfy the fundamental
equation (6). Applying it, we get F = 0. But the other fundamental
(7) is satisfied. To satisfy (6), take
^i(v) = - (V)'1 + JV (log s.2r - 1 ) :
leading to the determinantal equation
and requiring us to substitute
(«,V)-14-
for (SoV)"1 in the H2 and y2 formulae in (28). Then (6) is nearly
ON THE SELF-INDUCTION OF WIRES. PART I. 181
satisfied, and is quite satisfied if we change the last term in the last
expression to \r. But the other fundamental is violated.
Ignored Dielectric Displacement. Magnetic Theory of Establishment of
Current in a Wire.. Viscous Fluid Analogy.
Now take ni = 0 in (27), making - s£ = f*2cp'2, and bringing (27)
down to
j*,Vo(Vi)- -WA«i); ........................ (29)
where L0 = 2/*2log (ajaj,
the coefficient of self-induction of the surface-current, and
the resistance of the wire, both per unit length of wire ; so that
is the time-constant of the linear theory, on the supposition that the
resistance of the wire fully operates, although the current is confined
to the surface. This case of m = 0 is appropriate when the line is so
short that the electrostatic induction is really negligible in its effects on
the wire-current. In fact we shall arrive at (29) from purely electro-
magnetic considerations, with e = 0 everywhere. But it is also the
proper equation in the ra = 0 case when the electrostatic retardation
is not negligible. It must be taken into account, for instance, in the
subsidence of an initially steady current, independently of the electro-
static charge.
Expanding (29) in powers of p, by means of ±s?a? = - fJ^p/R0, we get
(30)
Taking first powers only, we get
which is greater than the linear-theory time-constant of the wire by the
amount J/^/^o, since J/^ is the inductance per unit length of wire
when the return-current is upon its surface.
But taking second powers as well, we get, if L = J/^ + Z/0,
and
of which the first is exactly the linear-theory value. The real time-
constant of the first normal system of current, therefore, exceeds the
linear-theory value by an amount which is less than J/>4/720, when the
return is so distant, or the retardation (p-Jc^a,*) of the wire is so small
that a steady current subsides with very nearly uniform current-
density, being very slightly less at the boundary than at the axis. It
is not, however, to be inferred that the subsidence of the " current in
the wire " is delayed. It is accelerated, at least at first.
Equation (29) may be written
....................... (31)
182 ELECTRICAL PAPERS.
the appropriate form when a full investigation is desired. Draw the
curves y^ = right member, and ?/2 = left member, the abscissa being s^.
Their intersections will give the values of s^ satisfying (31). The
first root has been already considered, when ^/LQ is very small. The
rest, under the same circumstances, will be nearly those of J^s-fa) = 0.
But if the wire is of iron, ^/L^ may be very large, and there will
be no approach to the linear theory. Many normal systems must
be taken into account to get numerical solutions. Similarly if the
sheath be close to the wire, whether it be magnetic or not.
Electrostatic charge being ignored, join the wire and sheath to make
a closed circuit, in which insert a steady impressed force e at time t--=Q.
Let F be the current at distance r from the axis at time t. (There is
no y now.) The rise of F to the final steady value, say F0, is given by
(32)
where q = 1^/2^. The values of s^ are to be got by (31).
The total current C, or the current in the wire, in ordinary language,
rises thus to its final value C0: —
(33)
The boundary -condition of F is that, at r = av
F + ^ = 0, therefore ^faih)-*,? ............ (34)
uT tJ -i
Considering the first term only in the summation in (33), as may be
done when the linear theory is nearly followed, that is, after the first
stage of the rise, put - p~l = (L + L^jPi^ where L-^ must be very small
compared with L ; then
When the current is started, by a steady impressed force in the coil-
circuit, in a long solenoidal coil of small thickness, containing a solid
conducting core, the magnetic force in the core rises in the same manner
as the current in the wire, according to (32) ; because the boundary-
condition of the magnetic force is of the same form as (34), q being
then a function of the number of windings, etc.
There is also the water-pipe analogy, which is always turning up.
This I have before made use of [vol. L, p. 384]. Water in a round
pipe is started from rest and set into a state of steady motion by the
sudden and continued application of a steady longitudinal dragging or
shearing-force applied to its boundary, according to the equation (32).-
This analogy is useful because every one is familiar with the setting
of water in motion by friction on its boundary, transmitted inward by
viscosity.
Graphically representing (32), abscissae the time, and ordinates F, at
the centre, intermediate points, and the boundary, by what we may
call the arrival -curves of the current, and comparing them with
ON THE SELF-INDUCTION OF WIRES. PART I. 183
the linear theory arrival curve at all parts of the wire, we may notice
these characteristics. The current rises much more rapidly at the
boundary than according to the linear theory, at first, but much more
slowly in the later stages. Going inward from the boundary we find
that an inflection is produced in the arrival-curve near its commence-
ment ; the rapid rise being delayed for an appreciable interval of time.
This dead period is, of course, very marked at the axis of the wire,
there being practically no current at all there until a certain time has
elapsed. That the central part of the wire is nearly inoperative when
rapid reversals are sent is easily understood from this, or perhaps more
easily by the use of the water-pipe analogue. Some curves of (32), for
two special values of q, I have already given [vol. I., p. 398 ; vol. II.,
p. 58].
Magnetic Theory of S.H. Variations of Impressed Voltage and
resulting Current.
Let there be a simple-harmonic impressed force e sin nt in the circuit
of wire and sheath, with no external resistance, making a total circuit-
resistance R. (I translate the core-solution into the wire-solution.)
The boundary condition is
and the solution is
r^^(P^ + QS)-^(PQM+QQN)smnt + (PQN-Q0M)CoSnt^ ; ...(36)
where M and N are the following functions,
M= i/0(WO + |/0(W^), 1
tf-j^WT) - Ji/0(W-t)J '
standing for v/ - 1, and x for /v/W/A^w. Also
P = M+qM', Q = N+qN', ..................... (38)
le ' denoting differentiation to r. In (36), M and N have the values
distance r, and P0, Q0 the values at r = a1} the boundary.
We have
P2 + £2 = M* + N2 + 2q(MM' + NN') + <f(M'* + N'*) ........ (39)
If y — (ay)4 = (47r/x1^1?>27i)2, we have the following series : —
- y A , 8y /
PV 4262v
y
16
(40)
184 ELECTRICAL PAPERS.
These are suitable for calculating the amplitude of F or of C when y is
not a very large quantity. The wire-current C is given by
where P, Q, M, N, Mf, N' have the boundary values. As for M and N
themselves, their expansions are
M=l-JL ^
2242 ~22426282
('*-')
22 224252 "22
But these series are quite unsuitable when y is very large. Then
use the approximate formulae
'- '
which make, if/-yi,
M* + N2 = .
'27rr2, • (44)
, \trji
In the extreme, very high frequency, or large retardation, or both
combined, making y very great, the amplitude of the wire-current C
tends to be represented by
e/L0ln; (45)
showing that the current is stronger than according to the linear theory,
and far stronger in the case of an iron wire, or very close return.
The amplitude of the current-density at the axis, under the same
circumstances, with r = aA in /, is
I*, «... .-(46)
wrhich is of course excessively small. On the other hand, the boundary
current-density amplitude is
TT1I
which may be greater than the linear-theory amplitude.
Analogous to this, the amplitude of the current in a coil due to a S.H.
impressed force in the coil-circuit is greatly increased by allowing dissi-
pation of energy by conduction in a core placed in the coil, when the
corresponding y is great, a large core, high inductivity, etc. ; that is, the
inertia or retarding-power of the electromagnet is greatly reduced, so
far as the coil-current is concerned. This is, in a great measure, done
away with by dividing the core to stop the electric currents, when the
linear theory is approximated to.
OX THK SELF-INDUCTION OF WIRES. PART II. 185
If // = 1600, the axial is about one-fourteenth of the boundary-current
amplitude. To get this in a thick copper wire of 1 centim. radius, a
frequency of about 850 waves per second would be required. But in
an iron rod of the same size, if we take /^ = 500, only about 8 J waves
per second would suffice.
Returning to the former expressions, if we go only as far as n6, the
amplitude GY0 of the wire-current is given by CQ = e/Rrrl; where the
square of R", which is the "apparent resistance," or the impedance, per
unit length of wire, is given by
where g = (^w/A^)2, and R0 and L have the former meanings.
When only the total current is under investigation, the method
followed by Lord Rayleigh (Phil. Mag., May, 1886) possesses advan-
tages. I find it difficult, however, to understand how the increased
resistance can become of serious moment. For, above a certain fre-
quency, the current-amplitude is increased ; whilst, below that frequency,
its reduction, from that given by the linear theory, appears to be, in
copper wires, quite insignificant in general [vol. 1 1., p. 67 j.
PART II.
Extension of General Theory to two Coaxial Conducting Tubes.
In Part I. the inner conductor was solid. Let now the central
portion be removed, making it a hollow tube of outer radius a1 and
inner a0. The reason for this modification is that the theory of a tube
is not the same when the return-conductor is outside as when it is
inside it ; that is to say, it depends upon the position of the dielectric,
the primary seat of the transfer of energy. The expression for Hv the
magnetic force at distance r from the axis, will now be
^ = Ki(V-)-W^i)(¥^i(¥')Mi; (49)
instead of the former A^far), of the first of equations (18); if we
impose the condition H^ = 0 at the inner boundary of the wire (as we
may still call the inner tube). This means that there is to be no
current from r = 0 to r = aQ ; we therefore ignore the minute longitudinal
dielectric-current in this space, just as we ignored that beyond r = as
previously. If we wish to necessitate that this shall be rigidly true,
we may suppose that within r = aQt and beyond r = as, we have not
merely k = 0, but also c = 0, thus preventing current, either conducting
or dielectric. In any case, with only k = Q, the dielectric disturbance
must be exceedingly small. On this point I may mention that my
brother, Mr. A. W. Heaviside, experimenting with a wire and outer
tube for the return, using a (for telegraphic purposes) very strong
current, rapidly interrupted, and a sensitive telephone in circuit with a
parallel outer wire, could not detect the least sign of any inductive
186 ELECTRICAL PAPERS.
action outside the tube, at least when the source of energy (the battery)
was kept at a distance from the telephone. In explanation of the last
remark, we need only consider that, although the transfer of energy is
from the battery along the tubular space between the wire and return,
yet, before getting to this confined space, there is a spreading out of
the disturbances, so that in the neighbourhood of the battery the disk
of a telephone may be strongly influenced by the variations of the
magnetic field. On the other hand, the induction between parallel
wires whose circuits are completed through the earth, is perceptible
with the telephone at hundreds of miles distance, or practically at any
distance, if the proper means be taken which theory points out. His
direct experiments have, so far, only gone as far as forty miles, quite
recently ; but this distance may easily be extended.
Corresponding to (49) we shall have
............ (50)
omitting, in both, the z and t factors. Now, to obtain the corresponding
development of the general equation (22), we have only to change the
Jo(siai) in ft k° the quantity in the { } in (50), and the /1(s1a1) to that in
the {} in (49), with r = a1 in both cases.
Electrical Interpretation of the Differential Equations. Practical Simplifica-
tion in Terms of Voltage V and Current C.
The method by which (22) was got was the simplest possible, reducing
to mere algebra the work that would otherwise involve much thinking
out; and, in particular, avoiding some extremely difficult reasoning
relating to potentials, scalar and vector, that would occur were they
considered ab initio. But, having got (22), the interpretation is com-
paratively easy. Starting with the inner tube, (49) is the general
solution of (14), with the limitation Hl = Q at r = aQ ; if, in s, given by
- Sj2 = kirnfap + m2,
we let p mean d/dt and m2 mean- d'2/dz'2, instead of the constants in a
normal system of subsidence, and let Al be an arbitrary function of
z and t. Similarly, (50) gives us the connection between I\ and Av
From it we may see what Al means. For, put r = a0 in (50); then,
since
we see that Al= — 47ra0X1(s1a0)F0,
if F0 is the current-density at r = a0. When the tube is solid,
^1 = 47iT0/s1. But, without knowing Av (49) and (50) connect H-^
and Fj directly, when Al is eliminated by division. Also, H1 = C1* (2/r),
if Cl be the total longitudinal current from r = a0 to r ; hence
r =L oi
27Tf ^ ..... - ............... JEi ..... ]
connects the current-density and the integral current.
ON THE SELF-INDUCTION OF WIRES. PART II. 187
Now pass to the outer tube. Quite similarly, remembering that
H3 = 0 at r = «3, we shall arrive at
r _ °s
27JT J~... - ^
connecting F3, the longitudinal current density at distance r in the
outer tube, with (73, the current through the circle of radius r in the
plane perpendicular to the axis.
Next, let there be longitudinal impressed electric forces in the wire
and return, of uniform intensities el and e.2 over the sections of the two
conductors. We shall have
if El and E3 are the longitudinal electric forces "of the field."
Therefore
T~1 ~T! / 777 7VT \ / e A \
where e is the impressed force per unit length in the circuit at the place
considered : the positive direction in the circuit being along the wire in
the direction of increasing z, and oppositely in the return.
If we take r = al in (51), and r = a2 in (52), and use them in (54),
then, since C± becomes C, the wire-current, and C? becomes the same
plus the longitudinal dielectric-current, we see that if we agree to ignore
the latter, and can put El-E3 in terms of C, (54) will become an
equation between e and C.
To obtain the required El - E3, consider a rectangular circuit in a
plane through the axis, two of whose sides are of unit
length parallel to z at distances a^ and a2 from the axis,
and the other two sides parallel to r, and calculate the
E.M.F. of the field in this circuit in the direction of the
circular arrow. If z be positive from left to right, the
positive direction of the magnetic force through the circuit
is upward through the paper. Therefore, if V be the line-
integral of the radial electric force from r = al to r = a<i,
so that dVjdz is the part of the E.M.F. in the rectangular
circuit due to the radial force, we shall have
. dV
o
by the Faraday law, or equation (7) ; Hz being the magnetic force in the
dielectric. This being 2C/r, on account of our neglect of F2, we get, on
performing the integration, - L0C, on the right side, where LQ is the
previously-used inductance of the dielectric per unit length. This
brings (54) to
27T0!
188 ELECTRICAL PAPERS.
which, for brevity, write thus,
e-^=L&C+lS?C+I%C, .................... (56)
where E" and R% define themselves in (55). They are generalised
resistances of wire and return respectively, per unit length. But of
their structure, later. Equation (56) is what we get from (22) by
treating szr as a small quantity and using ^26) ; remembering also the
extension from a solid to a hollow wire.
By more complex reasoning we may similarly put the right member
of (54) in terms of C without the neglect of T2, and arrive at (22) itself,
in a form similar to (55) or (56). But we may get it from (22) at once
by a proper arrangement of the terms. It becomes
#+#S+«+3)a .................. (57)
/% J'oi /
Here R" and T?" are as before, whilst //0" and B^ are similar expressions
for the dielectric, on the assumption that H = 0 at r = al or at r = a2
respectively ; thus,
03 has a different structure, being given by
Jo(s2ai) ~
In these take s2r small ; they will become
7?" _ 7?" _
that is, if p2 be imagined to be resistivity, the steady resistance per
unit length of the dielectric tube (fully, p.2 is the reciprocal of k2 +
and, with k2 = 0,
if S is the electric capacity per unit length, such that Z0$ = /x2c2. Then,
introducing e, (57) reduces to
e = (LQp + m2/Sp + E? + tiZ)C, .................... (58)
which is really the same as (56). For, by continuity, or by the second
of (11),
................. (59)
if a- is the time-integral of the radial current at r = alt or, in other
words, the electrification surface-density there, when the conductors
ON THE SELF-INDUCTION OF WIRES. PART II. 189
are non-dielectric. (There is equal - a- at the r = <t.y surface.) Therefore
1 &C_m*c_dV (60)
"tip dz*~S~p dz'
which establishes the equivalence.
Particular attention to the meaning of the quantity Fis needed. It
is the line-integral of the radial force in the dielectric from r = «j to
r = a... Or it may be defined by
Sr=2lTUl<r=Q,
if Q be the charge per unit length of wire. But it is not the electric
potential at the surface of the wire. It is not even the excess of the
potential at the wire-boundary over that at the inner boundary of the
return. For, as it is the line-integral of the electric force from end to
end of the tubes of displacement, it includes the line-integral of the
electric force of inertia. It has, however, the obvious property of
allowing us to express the electric energy in the dielectric in the form
of a surface-integral, thus, J V<r per unit area of wire-surface, or J FQ per
unit length of wire, instead of by a volume-integration throughout the
dielectric. Hence the utility of V. The possibility of this property
depends upon the comparative insignificance of the longitudinal current
in the dielectric, which we ignore. It may happen, however, that the
longitudinal displacement is far greater than the radial ; but then it
will be of so little moment that the problem could be taken to be a
purely electromagnetic one. We need not use V at all, (58) being the
equation between e and C without it. It is, however, useful in electro-
static problems, for the above-mentioned reason. Again, instead of V^
we may use o- or Q, which are definitely localized.
The physical interpretation of the force - dF/dz, in terms of Maxwell's
inimitable dielectric theory, is sufficiently clear, especially when we assist
ourselves by imagining the dielectric displacement to be a real displace-
ment, elastically resisted, or any similar elastically resisted generalized
displacement of a vector character. When there is current from the
wire into the dielectric there is necessarily a back electric force in it
due to the elastic displacement ; and if it vary in amount along the wire,
its variation constitutes a longitudinal electric force.
(58) being a differential equation previously, let m2 be a constant in it.
Then R" and E" may be thus expressed : —
.................. (61)
where R{ and B'2, L{ and Lfz are functions of p2. The utility of this
notation arises from R{ etc. becoming mere constants in simple-harmoni-
cally vibrating systems. Let em, Fm, and Cm be the corresponding
quantities for the particular m ; then, by (56),
+ (R(m + L'mp)Cm + (B,L + LLp)Cm ....... (62)
Or em-dJ^ = (R'm + L'mp)Cm, ........................ (63)
where Ii'm = B'lm + R^, L'm = LQ + L{m + LL ............ (64)
190 ELECTRICAL PAPERS.
R'm and L'm are functions of p2. Therefore, by (62), summing up,
. ........... (65)
Now, although Rfm and L'm are really different functions of p2 for
every different value of m, since they contain m2, yet if, in changing
from one m to another, through a great many TTI'S, from m = 0 upward,
they should not materially change, we may i egard E'm and Lfm as having
the 7ft = 0 expressions, as in the purely electromagnetic case, and denote
them by Rf and Lf simply. Then (65) becomes
(66)
U/.3
simply. The equation of ^is now
and. that of Cm being
..................... (68)
in the m case, that of C becomes now simply
...................... (69)
/
The assumption above made is, in general, justifiable.
Previous Ways of treating the subject of Propagation along Wires.
Let us now compare these equations with the principal ways that
have been previously employed to express the conditions of propagation
of signals along wires. For simplicity, leave out the impressed force e.
First, we have Ohm's system, which may be thus written : —
J-f=RC, -d°=spr, %%-BSpr. ........ (TO)
dz dz dz2
Here the first equation expresses Ohm's law. C is the wire-current, E
the resistance per unit length, and V is a quantity whose meaning is
rather indistinct in Ohm's memoir, but which would be now called the
potential. The second equation is of continuity. Misled by an entirely
erroneous analogy, Ohm supposed electricity could accumulate in the
wire in a manner expressed by the second of (70), wherein S therefore
depends upon a specific quality of the conductor. The third equation
results from the two previous, and shows that V, or (7, or Q = SV diffuse
themselves through the wire as heat does by difference of temperature
when there is no surface-loss. This system has at present only historical
interest. The most remarkable thing about it is the getting of equations
correct in form, at least approximately, by entirely erroneous reasoning.
The matter was not set straight till a generation later, when Sir W.
Thomson arrived at a system which is formally the same as (70), but in
which V is precisely defined, whilst S changes its meaning entirely. V
is now to be the electrostatic potential, and S is the electrostatic capacity
ON THE SELF-INDUCTION OF WIRES. PART II. 191
of the condenser formed by the opposed surfaces of the wire and return
with dielectric between. The continuity of the current in the wire is
asserted ; but it can be discontinuous at its surface, where electricity
accumulates and charges the condenser. In short, we simply unite
Ohm's law (with continuity of current in the conductor) and the similar
condenser law. The return is supposed to have no resistance, and V= 0
at its boundary.
The next obvious step is to bring the electric force of inertia into
the Ohm's law equation, and make the corresponding change in that
of V't that is, if we decide to accept the law of quasi-incompressibility
of electricity in the conductor, which is implied by the second of
(70), when Sir W. Thomson's meanings of S and V are accepted.
Kirchhoff seems to have been the first to take inertia into account,
arriving at an equation which is reducible to the form
I am, unfortunately, not acquainted with his views regarding the con-
tinuity of the current, so that, translated into physical ideas, his equa-
tion may not be conformable to Maxwell's ideas, even as regards the
conductor. Also, as his estimation of the quantity L was founded upon
Weber's hypothesis, it may possibly turn out to be different in value
from that in the next following system. In ignorance of Kirchhoff's
investigation, I made the necessary change of bringing in the electric
force of inertia in a paper "On the Extra Current" (Phil. Mag.,
August, 1876), [Art. xiv., vol. I., p. 53] getting this system,
wherein everything is the same as in Sir W. Thomson's system, with
the addition of the electric force of inertia - LpC, where L is the co-
efficient of self-induction, or, as I now prefer to call it [vol. II., p. 281,
the inductance, per unit length of the wire, according to Maxwells
system, being numerically equal to twice the energy, per unit length of
wire, of the unit current in the wire, uniformly distributed.
The system (71) is amply sufficient for all ordinary purposes, with
exceptions to be later mentioned. It applies to short lines as well as to
long ones; whereas the omission of L, reducing (71) to (70), renders
the system quite inapplicable to lines of moderate length, as the influ-
ence of S tends to diminish as the line is shortened, relatively to that of
L. An easily-made extension of (71) is to regard 11 as the sum of the
steady resistances of wire and return, and V as the quantity Q/S, Q
being the charge per unit length of wire. Nor are we, in this approxi-
mate system (71), obliged to have the return equidistant from the
wire. It may, for instance, be the earth, or a parallel wire, with the
corresponding changes in the formulae for the electric capacity and
inductance.
But there are extreme cases when (71) is not sufficient. For example,
an iron wire, unless very fine, by reason of its high inductivity ; a very
thick copper wire, by reason of thickness and high conductivity ; or, a
very close return-current, in which case, no matter how fine a wire may
192 ELECTRICAL PAPERS.
be, there is extreme departure from uniformity of current-distribution
in the variable period ; or, extremely rapid reversals of current, for, no
matter what the conductors may be, by sufficiently increasing the fre-
quency we approximate to surface-conduction.
We must then, in the system (71), with the extension of meaning of
R and V just mentioned, change R and L to Rf and L', as in (67), and
other equations. In a S.H. problem, this simply changes R and L from
certain constants to others, depending on the frequency. But, in
general, it would, I imagine, be of no use developing R" etc. in powers of
p, so that we must regard ( R{ + L(p) etc. merely as a convenient abbrevia-
tion for the E[r etc. defined by (56) and (55).
A further refinement is to recognise the differences between R' and
L' in one m system and another, instead of assuming m = 0 in R"n. And
lastly, to obtain a complete development, and exact solutions of Max-
well's equations, so as to be able to fully trace the transfer of energy
from source to sink, fall back upon (57), or (22), and the normal
systems (18) of Part I.
The Effective Resistance and Inductance of Tubes.
Now, as regards our obtaining the expansions of R{ etc. in powers of
p2, we have to expand the numerators and the denominators of R" and
R% in powers of p, perform the divisions, and then separate into odd
and even powers. When the wire is solid, the division is merely of
\xJQ(x) by J^x), a comparatively easy matter. The solid wire Rf and
L' expansions were given by Lord Eayleigh (Phil. Mag., May, 1886).
I should mention that my abbreviated notation was suggested by his.
But in the tubular case, the work is very heavy, so, on account of pos-
sible mistakes, I go only as far as p2, or three terms in the quotient.
The work does not need to be done separately for the inner and the
outer tube, as a simple change converts one R' or L1 into the other.
Thus, in the case of the inner tube, we shall have
(73)
where ri2 is written for -p2, for the S.H. application.
As for LI, it is simply the inductance of the tube per unit length (of
the tube only), as may be at once verified by the square-of-force method.
The first correction depends upon p*. But R{ gives us the first correc-
tion to Elt which is the steady resistance, so it is of some use. To
obtain P4 and L( from these, change E1 to E^ ^ and ^ to /z3 and &3, a0
to a3, and a^ to a2. Or, more simply, (72) and (73) being the tube-
formulae when the return is outside it, if we simply exchange «0 and al
we shall get the formulae for the same tube when the return is inside it.
ON THE SELF-INDUCTION OF WIRES. PART II. 193
If the tube is thin, there is little change made by thus shifting the
locality of the return. But if a^/a0 be large, there is a large change.
This will be readily understood by considering the case of a wire whose
return is outside it, and of great bulk. Although the steady resistance
of the return may be very low, yet the percentage correction will be
very large, compared with that for the wire.
Taking rtj/</0 = 2 only, we shall find
when the return is outside, and
2 x -503]
when the return is inside. In the case of a solid wire, the decimals are
•083, so that whilst the correction is reduced, in this aJctQ = 2 example,
the reduction is far greater when the return is outside than when it is
inside.
The high-frequency tube-formulae are readily obtained. Those for
the inner tube are the same as for a solid wire, and those for the outer
tube depend not on its bulk, but on its inner radius. That is, in both
cases it is the extent of surface that is in question, next the dielectric,
from which the current is transmitted into the conductors. Let
GQ(x) = (2/7r)KQ(x)) and G^x) = (2/ir)K1(x) ; then, when x is very large,
J0(x)= -G1(x) = (ainx + coBx) + (irx)*,\^ ^ ...(74)
J^x) = £0(.'e) = (sin x - cos x) + (irx)l. } ' '
Use these in the R" fraction, and put in the exponential form. We
shall obtain
But JSiV = (""^i/*!^)**!* therefore B(f
Also, p2 = - n\ therefore pi = ($n)*(l +i) = ( Jw)* +jp( Jw"1)*,
so that, finally, R( = (w^\ L{ = -\ ............... (75)
&! n
where q = n/27r is the frequency. To get R( and Z£, change the //, and p
of course, and also a^ to a2.
It is clear that the thinner the tube, the greater must be the fre-
quency before these formula? can be applicable. For the steady
resistance is increased indefinitely by reducing the thickness of the
tube, whilst the high-frequency resistance is independent of the steady
resistance, and must be much greater than it. In (75) then, q must be
great enough to make E' several times R, itself very large when the
tube is very thin. Consequently thin tubes, as is otherwise clear, may
be treated as linear conductors, subject to the equations (71), with no
corrections, except under extreme circumstances. The L may be taken
as LQ, except in the case of iron.
H.E.P. — VOL. n. N
194 ELECTRICAL PAPERS.
Train of Waves due to S.H. Impressed Voliage. Practical Solution.
I will now give the S.H. solution in the general case, subject to (58).
Let there be any distribution of e (longitudinal, and of uniform
intensity over cross-sections). Expand it in the Fourier-series appro-
priate to the terminal conditions at z = 0 and I. For definiteness, let
wire and return be joined direct, without any terminal resistances.
Then, e0 sin nt being e at distance zt the proper expansion is
eo = «oo + eoi cos m\z + eo2 cos m& + • • • >
where ml = ir/l, m2 = 2ir/l, etc. (It should be remembered that e is the
el - e2 of (54) and (53). Shifting impressed force from the wire to the
return, with a simultaneous reversal of its direction, makes no difference
in e. Thus two e's directed the same way in space, of equal amounts,
and in the same plane z = constant, one in the inner, the other in the
outer conductor, cancel. This will clearly become departed from as the
distance of the return from the wire is increased.) Then, in the equa-
tion
we know em ; whilst R'm and L'm are constants. The complete solution
is obtained by adding together the separate solutions for eW) e01, etc.,
and is
n - 1 f goo sin (** - go) + o V e°™ sin (nt ~ 6m) cos mz
I \ (R'* + U*n*)t ^[R% + (L'm -
where the summation includes all the m's, and
A practical case is, no impressed force anywhere except at z = 0, one end
of the line, where it is V§ sin nt. Then, imagining it to be V^z^ from
2 = 0 to z = zlt and zero elsewhere, and diminishing zl indefinitely, the
expansion required is
j going from 1 , 2, ... to GO . This makes the current-solution become
c_Vof sin (nt - 00) . o -y sin (nt - 0 J cos mz 1 ,-„.
/ * 2 '
If the line is short, neglect the summation altogether, unless the fre-
quency is excessive. Now (77) may perhaps be put in a finite form
when R'm is allowed to be different from fi', though I do not see how to
do it. But when Rfm = R' and L'm = L' it can of course be done, for
we may then use the finite solutions of (66) and (67). Thus, given
V— F0 sin nt at z = 0, and no impressed force elsewhere, find V and C
everywhere subject to (66) and (67) with e = Q, and F = Q at z — l.
Let
P = (±Sn)*{(R'* + L'W)* - L'n}*,
tan 02 = sin 2QI -r («-2W - cos 2$), \ /79)
tan Ol = (L'nP - R'Q) -r (R'P + UnQ) ;J "
ON THE SELF-INDUCTION OF WIRES. PART II. 195
then the finite Fund C solutions are
€pz sin (nt + Qz - Ol + 02) + e~fz sin (nt -Qz-6l +
If we expand the last in cosines of mz we shall obtain (77), with R'm = R'.
There are three waves ; the first is what would represent the solution
if the line were of infinite length ; but, being of finite length, there is a
reflected wave (the e^ term), and another reflected at z = 0, the third
and least important.
The amplitude of G anywhere is
At the distant (z = I) end it is
~ 2 cos 8Q°"* ........... <82)
o/ Quasi-Resonance. Fluctuations in the Impedance.
I have already spoken of the apparent resistance of a line as its
impedance (from impede). The steady impedance is the resistance.
The short-line impedance is (E2 + L2n2)*l or (£*+ISW)M> at the fre-
quency 7i/27r, according as current-density differences are, or are not,
ignorable. The impedance according to the latter formula increases
with the frequency, but is greater or less than that of the former
formula (linear theory) according as the frequency is below or above a
certain value.
But if the frequency is sufficiently increased, even on a short line,
the formula ceases to represent the impedance, whilst, if the line be
long, it will not do so at any frequency except zero. According to (82),
we have
............. (83)
as the distant-end impedance of the line. That is, we have extended
the meaning of impedance, as we must (or else have a new word), since
the current-amplitude varies as we pass from beginning to end of the
line. (83) will, roughly speaking, on the average, give the greatest
value of the impedance. It is what the resistance of the line would
have to be in order that when an S.H. impressed force acts at one end,
the current-amplitude at the distant-end should be, without any
magnetic and electrostatic induction, what it really is. The distant-end
impedance may easily be less than the impedance according to the
magnetic reckoning. What is more remarkable, however, is that it
196 ELECTRICAL PAPERS.
may be much less than the steady resistance of the line. This is due
to the to-and-fro reflection of the dielectric waves, which is a pheno-
menon similar to resonance.
To show this, take R' — 0 in the first place, which requires the con-
ductors to be of infinite conductivity. Then U = L0, the dielectric
inductance. We shall have, by (83) and (78),
.......................... (84)
where v = (LQS)-z = (/*2c2)-*, the speed of waves through the dielectric
when undissipated. The sine is to be taken positive ahvays. If
nl/v = Tr, 27r, etc., the impedance is zero, and the current-amplitude
infinite. Here nl/v - TT means that the period of a wave equals the time
taken to travel to the distant end and back again. This accounts for
the infinite accumulation, which is, of course, quite unrealizable.
Now, giving resistance to the line, it is clear that although the
impedance can never vanish, it will be subject to maxima and minima
values as the speed increases continuously, itself increasing, on the
whole. We may transform (83) to
rjc,
where t/ = (L'S) ~ *, and h --
The factor outside the [ ] is the electromagnetic impedance ; and, if we
take only the first term within the [ ], we shall obtain the former infinite-
conductivity formula (84). The effect of resistance is shown by the
terms containing h.
With this vf and h notation (83) becomes
€-*"- 2 COB 2QI}*-, ............ (86)
where
PI = (nl/v')(JT+h- - 1)* -5- N/2.
Choose Q so that 2Ql = ZTT, and let h = 1. This requires nljtf = 2-85.
Then
F0/C0 = \LW . 2i[Y82847r + €-•••- 2]*,
= 60-6 U ohms,
if we take v = 3010 cm. = 30 ohms. This implies U = LQ, and the
dielectric air. Without making use of current-density differences, we
may suppose that the conductors are thin tubes. Therefore
Impedance 60 -6 L' . 109_ , 202
Resistance " R'l 285'
by making use of the above values of h and nl/v'.
ON THE SELF-INDUCTION OF WIRES. PART II. 197
But taking 2QI = £TT, or one fourth of the above value. Then
F0/C0 = 28L' ohms,
and Impedance 4
Resistance
Thus the amplitude of the current, from being less than the steady
strength in the last case, becomes 42 per cent, greater than the steady
current by quadrupling nl/i/t and keeping h = 1 . We have evidently
ranged from somewhere near the first maximum to the first minimum
value of the impedance. These figures suit lines of any length, if we
choose the resistances, etc., properly. The following will show how the
above apply practically. Remember that 1 ohm per kilom. = 104 per
cm. Then, if /x = length of line in kilom.,
If R' = 103, and U = 1, . •. n = 103, and ^ - 856,
,,7?= 10s, „ 7/ = 10, ,,rt = 102, „ ^ = 8568,
,,72' =10*, „ 7/ = 1, ,,/i=104, „ ^ = 85,
„ 72' =10*, „ U= 10, ,,?^103, „ ^ = 856,
,,7j!'=104, „ 77=100, „ % = 102, „ ^ = 8568,
,,72' =105, „ L'= 1, ,,7i=105, „ ^ = 8-5,
,,72' =105, >f jj= 10, „ w = io*, „ /1 = 85,
„ R' = 105, jf // = ioo, „ w = 103, „ ^ = 856,
,,72'=106, „ L'= 10, ,,w = 105, „ ^ = 8-5.
The resistances vary from TV to 100 ohms per kilom., the inductances
from 1 to 100 per cm., the frequencies from 102/2n- to 105/2w, and the
lengths from 8-5 to 8568 kilom. In all cases § is the ratio of the
distance-end impedance to the resistance. The common value of nl± is
856800.
In the other case, nl/i/ has one fourth of the value just used, so that,
with the same Rf and 7/, /x has values one fourth of those in the above
series.
Telephonic currents are so rapidly undulatory (it is the upper tones
that go to make articulation, and convert mumblings and murmurs into
something like human speech) that it is evident there must be a con-
siderable amount of this dielectric resonance, if a tone last through the
time of several wave-periods.
Derivation of Details from the Solution for the Total Current.
Having got the solution for C, the wire-current, we may obtain those
for H, F, and y from it. Thus, Hr being the same as ('2/r)Cr, where Cr
is the longitudinal current through the circle of radius r, we may first
derive Cr or Hr from C, and then derive F and y from either by (11).
Thus, make use of (49) and (50), and the value of Al there given.
Then we shall obtain
Cr= — //rV \ rr~Tr^TVVJ \ V- t\ ~ \fi • • (®^)
198 ELECTRICAL PAPERS.
where, in the slt p and m2 are to be d/dt and - d2/dz2. Similarly for
the return-tube.
In a comprehensive investigation, the C-solution would be only a
special result. As this special result is more easily got by itself, it might
appear that there would be some saving of labour by first getting the C-
solution and then deriving the general from it. But this does not stand
examination ; the work has to be done, whether we derive the special
results from the general, or conversely.
In the solid-wire case
C = rji(sir) Q
Vi(sitti) '
or
Or, use the M and N functions of Part L, equations (42). For we
have
where sxni takes the place of the y in those equations. M contains the
even, and N the odd powers of (p + m
We have also
F0 being F at r = 0 ; and, since by the first of these,
connects the boundary and axial current-densities, we see that the ratio
of their amplitudes in the S.H. case is
using the r = al expressions, with m = 0.
Note on the Investigation of Simple-Harmonic States. (July, 1892.)
[I have been asked by more than one correspondent how the above
solutions (80) and (81) are obtained, and therefore add some details,
giving the working rather fully, as it will serve to show the procedure
in other cases.
We have an impressed force acting at one spot, and desire to know
the effect produced there and elsewhere. The first step is to form the
differential equation connecting the impressed force with the effect pro-
duced. Now we have
ON THE SELF-INDUCTION OF WIRES. PART II. 199
in the line generally, if we introduce K the leakage-conductance per
unit length (as in Parts IV. and V.), and therefore
V=<.F*.A + i-F*.B, ........................... (2A)
where A and E are undetermined. To suit the present case, we find
them by the terminal conditions
F=0 at s = /, therefore Q = *fl.A + e~fl.£,
V= e at z = 0, therefore e = A + B ;
which give A and B and develop (2 A) to
This is the differential equation connecting V at z with e at z = 0, the
latter being any function of the time. It may also be regarded as the
solution of the problem of finding V due to e. For the march of V is
strictly connected with that of e through the operator in (3 A) and by
nothing else, all indefiniteness having been removed by the previous
work. But, whilst (3A) is the solution, it is (usually) in a very con-
densed form, needing development to more immediately interpretable
forms. If, however, F be constant, as happens when p = Q, (3A) needs
no development. It then represents the ultimate steady state of V due
to steady e. But the primitive solution in general requires a good deal
of development. Thus, if we wish to find the ultimate simple-harmonic
state of V due to simple-harmonic e of frequency w/27r, we know that
p2 = - n2, or p — ni, making F=P + Qi, where P and Q are given in the
text (when K=0). This substitution made in (3A) will make it be
convertible to the simple form
F=(a + bp)e, ............................... (4A)
expressing V fully when e is given fully in any amplitude and phase.
The work is now to turn (3A) to (4A). First put F=P+Qi, then (3A)
becomes, when the real and imaginary parts in the numerator and
denominator are separated,
y_ (cui-i _ c-m-*) cos Q(l - Z) + i(*p(l-z) + c-1*-') sin Q(l - z)
e («« _ €-«) Cos Ql + i(<?1 + €~pl) sin Ql
To rationalise the denominator, multiply it and the numerator by the
denominator with the sign of i changed, producing
cos Qi - z . ei - e-« cos Qn
in... J
)sn .......... ... + .... sn
)cos .......... (... + ....) sin
)sin .......... (...-....) cos
(6A)
This is in rational form, since i —p/n. But it can be simplified. The
denominator, say D, is evidently
....................... (7A)
200 ELECTRICAL PAPERS.
and we may easily reduce (6 A) to
V= fcos Cs/c'V*" + €-*€*« - (€ft + e-ft) cos 2
+ sin #a/ - €* + e-* sin 2
•*•» COS * + - e-z sn
+ t Sin
the full solution with e simple-harmonic, but left arbitrary in amplitude
and phase. If it is F"0 sin nt, then the terms in the first two lines of
(8A) receive sin nt as a factor, whilst the next two lines receive cos nt
(by the operation of the differentiator i on e), giving the result, after
rearrangement,
sin 2$[V* cos(nt + Qz)-e-pf cos(nt - Qz)~]
-cos2Q/[~... sin( ........ )+ .... sin( ....... )"j
sir\(nt - Qz) + €-2Vzsin(nt + Qz)\ ....... (9 A)
This differs in form from (80), which was arranged to show the solution
for an infinitely long line (obtainable by the same process, only greatly
simplified) explicitly, with the additions caused by the reflection at
z = l and the subsequent complex minor reflections at beginning and
end of the line. To get (80) from (9A) observe the form of D in (7A),
and add and substract from (9 A) terms so as to isolate the solution for
an infinitely long line. Thus
F= F0e-P2sm(^ - Qz) + F0slr/cpzcos(^ + Qz) - e~p*
The transition to the shorter form (80) is now obvious, by taking
cos 0 - €"2"-CQs2^ sin e - sin2Ql (i LO
2~ ~pl — ' 2 ~ ~pl ........... ^ '
Some of the above work may be saved, perhaps, by taking e = V^nt at
the beginning, that is, a special complex form of impressed force. The
result is a complex solution, divisible into one due to J^cos?^ and
another due to F"0 sin nt, either of which may be selected, or any com-
bination made. But I find the above method more generally useful.
We may derive G from V thus,
n -dV\dz _ R'-L'p
- -
This process may be applied to the final form of solution for V or to
any previous form, as the primitive (3 A). The easiest way will depend
ON THE SELF-INDUCTION OF WIRES. PART III. 201
on circumstances. Similarly we may derive the ^-solution from the
(7-solution, by
v_ -dC/th_ K-Sp dC
~
The above details will also serve to illustrate the working of the
problem in Part V., for it is the same problem as above, but with
arbitrary terminal connections (instead of short-circuits), and is done
in the same way. Its complexity arises from the reactions between the
terminal apparatus and the main circuit.]
PART III.
r/cx on the Expansion of Arbitrary Functions in Series.
The subject of the decomposition of an arbitrary function into the sum
of functions of special types has many fascinations. No student of
mathematical physics, if he possess any soul at all, can fail to recognise
the poetry that pervades this branch of mathematics. The great work
of Fourier is full of it, although there only the mere fringe of the
subject is reached. For that very reason, and because the solutions can
be fully realised, the poetry is more plainly evident than in cases of
greater complexity. Another remarkable thing to be observed is the
way the principle of conservation of energy and its transfer, or the
equation of activity, governs the whole subject, in dynamical applica-
tions, as regards the possibility of effecting certain expansions, the
forms of the functions involved, the manner of effecting the expansions,
and the possible nature of the " terminal conditions " which may be
imposed.
Special proofs of the possibility of certain expansions are sometimes
very vexatious. They are frequently long, complex, difficult to follow,
unconvincing, and, after all, quite special ; whilst there is an infinite
number of functions equally deserving. Something is clearly wanted
of a quite general nature, and simple in its generality, to cover the
whole field. This will, I believe, be ultimately found in the principle
of energy, at least as regards the functions of mathematical physics.
But in the present place only a small part of the question will be
touched upon, with special reference to the physical problem of the
propagation of electromagnetic disturbances through a dielectric tube,
bounded by conductors.
It will be, perhaps, in the recollection of some readers that Professor
Sylvester, a few years since, in the course of his learned paper on the
Bipotential, poked fun at Professor Maxwell for having, in his investi-
gation of the conjugate properties possessed by complete spherical-
surface harmonics, made use of Green's Theorem concerning the mutual
energy of two electrified systems. He said (in effect, for the quotation
is from memory) that one might as well prove the rule of three by the
laws of hydrostatics — or something similar to that. In the second
edition of his treatise, Prof. Maxwell made some remarks that appear
202 ELECTRICAL PAPERS.
to be meant for a reply to this ; to the effect that although names,
involving physical ideas, are given to certain quantities, yet, as the
reasoning is purely mathematical, the physicist has a right to assist
himself by the physical ideas.
Certainly ; but there is much more in it than that. For not only the
conjugate properties of spherical harmonics, but those of all other
functions of the fluctuating character, which present themselves in
physical problems, including the infinitely undiscoverable, are involved
in the principle of energy, and are most simply and immediately proved
by it, and predicted beforehand. We may indeed get rid of the prin-
ciple of energy, and treat the matter as a question of the properties of
quadratic functions ; a method which may commend itself to the pure
mathematician. But by the use of the principle of energy, and assisted
by the physical ideas involved, we are enabled to go straight to the
mark at once, and avoid the unnecessary complexities connected with
the use of the special functions in question, which may be so great as to
wholly prevent the recognition of the properties which, through the
principle of energy, are necessitated.
The Conjugate Property Ui2 = T12 in a Dynamical System with Linear
Connections.
Considering only a dynamical system in which the forces of reaction
are proportional to displacements, and the forces of resistance to
velocities, there are three important quantities — the potential energy,
the kinetic energy, and the dissipativity, say U, T, and Q, which are
quadratic functions of the variables or their velocities. When there is
no kinetic energy, the conjugate properties of normal systems are U12 — 0
and (X2 = 0; these standing for the mutual potential energy and the
mutual dissipativity of a pair of normal systems. When there is no
potential energy, we have T12 = 0 and Q12 = 0. When there is no
dissipation of energy, Z712 = 0 and T12 = 0. And in general, U12 = Tl2i
which covers all cases, and has two equivalents, £613+ &u — 0, and
\ Q12 + T12 = Q', for, as the mutual potential and kinetic energies are
equal, the mutual dissipativity is derived half from each.
Let the variables be xv x2, •••> tneip velocities v1 = ^1, ..., and the
equations of motion
^ = (Au + B^ + (V2)Zj + (A12
(A2l + B2lp + C^P^X! + (A?* + BOOP + C<x,P2}Xo + • • •, r (®^)
where Fv F2, ..., are impressed forces, and^? stands for d/dt. Forming
the equation of total activity, we obtain
2Fv=Q+U+f; ........................... (89)
where
2 U=
(90)
So far will define, in the briefest manner, U, T, Q, and activity.
ON THE SELF-INDUCTION OF WIRES. PART III. 203
Now let the F's vanish, so that no energy can be communicated to
the system, whilst it can only leave it irreversibly, through Q. Then
let pv p2 be any two values of p satisfying (88) regarded as algebraic.
Let Qv 17V 2\ belong to the system pl existing alone ; then, by (89)
and (90),
or =
0 = <?2+£72 + 2'2, or 0 =
But when existing simultaneously, so that
where Z712, T12, Q12 depend upon products from both systems, thus : —
612 = 2( Ai^
the accents distinguishing one system from the other, we shall find, by
forming the equations of mutual activity 2^V=..., and 2_Fv=...,
that is, with the F's of one system, and the 0's of the other, in turn,
adding which, there results the equation of mutual activity,
0 = ^2 + (Pi +*2)( Ui2 + ^12)1 or ° = Qi2 + &
and, on subtraction, there results
0 = (Pi -ft)( ^12-^12) ......................... (91)
giving Ul<2 = Tly if the ^?'s are unequal. But this property is true
whether the ^'s be equal or not ; that is. Uu = T^ when^j is a repeated
root. I have before discussed various cases of the above, with special
reference to the dynamical system expressed by Maxwell's electro-
magnetic equations. [Vol. i., pp. 520 to 531.]
Application to the General Electromagnetic Equations.
The following applies to Maxwell's system, using the equations (4)
to (10) of Part. I. [vol. ii., p. 174]. A comparison with the above is
instructive. Let Ej, Hx and E2, H2 be any two systems satisfying these
equations, with no impressed forces, or e = 0, h = 0. Then the energy
entering the unit volume per second by the action of the first system on
the second is
conv VEjH^Tr = (Ej curl H2 - H2 curl E1)/47r,
H2B1/47r ................. (92)
Similarly, by the action of the second system on the first,
conv VEcjH^Tr = E^ + E^ + H1B2/4;r ............... (93)
204 ELECTRICAL PAPERS.
Addition gives the equation of mutual activity. And, subtracting (93)
from (92), we find
conv (VEA - VEL,H1)/47r = (E - E) - (H - RJ/i* ; ..(94)
since E^ = E^E2 = Eg&Ej = E^, if there be no rotatory power, or C be
a symmetrical linear function of E. Similarly for D and E, and B and
H. Hence, if the systems are normal, making d/dt —p^ in one, and p.?
in the other, (94) becomes
conT(VE1H,-Vl2HJ/4ir«<|>i-3>1XKrJ>3-H1Ba/4ir) ........ (95)
Therefore, by the well-known theorem of Convergence, if we inte-
grate through any region, and U12) Tu be the mutual electric energy
and the mutual magnetic energy of the two systems in that region, we
obtain
P\~
where N is the unit normal drawn inward from the boundary of the
region, over which the summation extends. And if the region include
the whole space through which the systems extend, the right member
will vanish, giving U^ = Tu, when these are complete.
From (96) we obtain, by differentiation, the value of twice the excess
of the electric over the magnetic energy of a single normal system in
any region ; thus
(97)
This formula, or some special representative of the same, is very useful
in saving labour in investigations relating to normal systems of sub-
sidence.
Application to any Electromagnetic Arrangements subject toV = ZC.
The quantity that appears in the numerator in (96) is the excess of
the energy entering the region through its boundary per second by the
action of the second system on the first, over that similarly entering
due to the action of the first on the second system. Bearing this in
mind, we can easily form the corresponding formula in a less general
case. Suppose, for example, we have two fine-wire terminals, a and b,
that are joined through any electromagnetic and electrostatic combina-
tion which does not contain impressed forces, nor receives energy from
without except by means of the current, say C, entering it at a and
leaving it at 6. Let also V be the excess of the potential of a over that
of b. Then VG is the energy-current, or the amount of energy added
per second to the combination through the terminal connections with,
necessarily, some other combination. (In the previous thick-letter
vector investigation V was the symbol of vector product. There will,
however, be no confusion with the following use of Vt as in Part II., to
express the line-integral of an electric force. One of the awkward
things about the notation in Prof. Tait's " Quaternions " is the employ-
ON THE SELF-INDUCTION OF WIRES. PART III. 205
ment of a number of most useful letters, as S, T, U, V, K, wanted for
other purposes, as mere symbols of operations, putting another barrier
in the way of practically combining vector methods with ordinary
scalar methods, besides the perpetual negative sign before scalar pro-
ducts.) The combination need not be of mere linear circuits, in which
differences of current-density are insensible ; there may, for example, be
induction of currents in a mass of metal either connected conductively
or not with a and b • but in any case it is necessary that the arrange-
ment should terminate in fine wires at a and b, in order that the two
quantities V and C may suffice to specify, by their product, the energy-
current at the terminals. Even in this we completely ignore the
dielectric currents and also the displacement, in the neighbourhood of
the terminals, i.e., we assume c = 0, to stop displacement. This is, of
course, what is always done, unless specially allowed for.
Now, supposing the structure of the combination to be given, we
can always, by writing out the equations of its different parts, arrive
at the characteristic equation connecting the terminal V and C. For
instance,
r=ZC, .................................. (98)
where Z is a function of d/dt. In the simplest case Z is a mere resist-
ance. A common form of this equation is
where the /'s and g's are constants. But there is no restriction to such
simple forms. All that is necessary is that the equation should be
linear, so that Z may be a function of p. If, for example, (dC/dt)2 oc-
curred, we could not do it.
Now this combination must necessarily be joined on to another,
however elementary, to make a complete system, unless V is to be zero
always. The complete system, without impressed forces in it, has its
proper normal modes of subsidence, corresponding to definite values
of p. Consequently, by (96),
(Pl-pj, ................. (99)
if Fi, Cl belong to p^ and F2, C2 to p2, whilst the left member refers to
the combination given by V= ZC, Or,
ult - Ta = <?!<?, - + (P, -Pl) = c,c;p ...... (ioo)
\V1 °2/ Pz~Pl
and the value of 2(U- T) in a single normal system is
...(101)
dp dp dp C ' dp'
In a similar manner we can write down the energy-differences
for the complementary combination, whose equation is, say, V— YC'}
remembering that - VC is the energy entering it per second, we get
and 6'2-7-> respectively.
Pi-Pi
206 ELECTRICAL PAPERS.
By addition, the complete Z712 - T12 is
g1C2ri"rg"^ + ^ = 0«CyiC'/i"*2; , ...(102)
Pi-Pz Pi-P*
and the complete 2(T7- T) is
.................. (103)
where <£ = 0, or Y-Z=0, is the determinantal equation of the complete
system (both combinations which join on at a and b, where J^and C are
reckoned), expressed in such a form that every term in <£ is of the
dimensions of a resistance.
Determination of Size of Normal Systems of V and C to express Initial State.
Complete Solutions obtainable with any Terminal Arrangements provided
R, S, L are Constants.
If the complete system depends only upon a finite number of vari-
ables, it is clear that the number of independent normal systems is also
finite, and there is no difficulty whatever in understanding how any
possible initial state is decomposable into the finite number of normal
states ; nor is any proof needed that it is possible to do it. The con-
stant Av fixing the size of a particular normal system plt will be
given by
by the previous, if U01 be the mutual electric energy of the given
initial state and the normal system, and T01, similarly, the mutual
magnetic energy.
And, when we increase the number of variables infinitely, and pass to
partial differential equations and continuously varying normal functions,
it is, by continuity, equally clear that the decomposition of the initial
state into the now infinite series of normal functions is not only possible,
but necessary. Provided always, that we have the whole series of
normal functions at command. Therein lies the difficulty, when there
is any.
In such a case as the system (71) of Part II., involving the partial
differential equation
wherein R, S, and L are constants, to hold good between the limits
z = 0 and z = l, subject to
V=Z0C at * = 0, and F=Z1C at z = l,
there is no possible missing of the true normal functions which arise by
treating d/dt as a constant ; so that we can be sure of the possibility of
ON THE SELF-INDUCTION OF WIRES. PART III. 207
the expansions. Thus, denoting ESp + LSp2 by - m2, we may take the
normal K-function as
u = sin (mz + 0), ............................. (106)
and the corresponding normal C-f unction as
„_ + & d»= + *cos (mz+0). ...(107)
m2 dz m
Here 0 will be determined by the terminal conditions
- = Z, at s = 0, - = £, at z=l, ...(108)
W IV
and the complete V and G solutions are
F=2^«e* C=2Awf ................... (109)
at time / ; where any A is to be found from the initial state, say F0, (70,
functions of zt by
provided there be no energy initially in the terminal arrangements. If
there be, we must make corresponding additions to the numerator,
without changing the denominator of A. The expression to be used
for u/w is, by (106) and (107),
........................ (Ill)
W bp
remembering that m is a function of p. There are four components in
the denominator of (110), as there are three electrical systems; viz.,
the terminal arrangements, which can only receive energy from the
" line," and the line itself, which can receive or part with energy at
both ends.
Complete Solutions obtainable when E, S, L are Functions of z, though not
of p. Effect of Energy in Terminal Arrangements.
In a similar manner, if we make R, 5, and L any single-valued
functions of z, subject to the elementary relations of (71), Part II., or
--8, ............... (112)
getting this characteristic equation of C,
d, after putting w for C and p for -p this equation for the current-
nction,
an
function,
208 ELECTRICAL PAPERS.
and finding the w -function by the second of (112), giving
-*•-£ ............................... <115>
we see that the expansions of the initial states F"0 and C'0 can be effected,
subject to the terminal conditions (108). For the normal potential- and
current-functions will be perfectly definite (singularities, of course, to
receive special attention), given by (115) and (114), each as the sum of
two independent functions, and the terminal conditions will settle in
what ratio they must be taken. (109) and (110) will constitute the
solution, except as regards the initial energy beyond the terminals.
It is, however, remarkable, that we can often, perhaps universally,
find the expression for the part of the numerator of (110) to be added
for the terminal arrangements, except as regards arbitrary multipliers,
from the mere form of the ^-functions, without knowing in detail what
electrical combinations they represent. This is to be done by first
decomposing the expression for C'2(dZjdp) into the sum of squares, for
instance,
.................... (116)
where rv r^ ... are constants. The terminal arbitraries are then
*2,Afi(p), 2 j(/2(p), etc.: calling these Ev E2, ..., the additions to the
numerator of (110) are
wherein the E's may have any values. This must be done separately
for each terminal arrangement. The matter is best studied in the con-
crete application, which I may consider under a separate heading.
It is also remarkable that, as regards the obtaining of correct expan-
sions of functions, there is no occasion to impose upon E, S, and L the
physical necessity of being positive quantities, or real. This will be
understandable by going back to a finite number of variables, and then
passing to continuous functions. [See Art. XX., vol. I., p. 141, for
examples.]
Case of Coaxial Tubes when the Current is Longitudinal. Also when the
Electric Displacement is Negligible.
Let us now proceed to the far more difficult problems connected with
propagation along a dielectric tube bounded by concentric conducting
tubes, and examine how the preceding results apply, and in what cases
we can be sure of getting correct solutions. Start with the general
system, equations (11) to (14), Part I, with the extension mentioned
at the commencement of Part II. from a solid to a tubular inner con-
ductor. Suppose that the initial state is of purely longitudinal electric
force, independent of z, so that the longitudinal E and circular H are
functions of r only, How can we secure that they shall, in subsiding,
remain functions of r only, so that any short length is representative of
the whole ? Since E is to be longitudinal, there must be no longitudinal
ON THE SELF-INDUCTION OF WIRES. PART III. 209
energy current, or it must be entirely radial. Therefore no energy
must be communicated to the system at £ = 0 or z = l, or leave it at
those places. This seems to be securable in only five cases. Put
infinitely conducting plates across the section at either or both ends of
the line. This will make F^Q there, if Fis the line-integral of the
radial electric force across the dielectric. Or put nonconducting and
non-dielectric plates there similarly. This will make (7 = 0. Or, which
is the fifth case, let the inner and the outer conductors be closed upon
themselves. In any of these cases, the electric force will remain longi-
tudinal during the subsidence, which will take place similarly all along
the line. By (14), the equation of H will be
f* \ ^H^fakuA+ucB}
dr r dr
and it is clear that the normal functions are quite definite, so that the
expansion of the initial state of E and H can be truly effected. In the
already-given normal functions, take m = 0.
But if we were to join the conductors at one end of the line through
a resistance, we should, to some extent, upset this regular subsidence
everywhere alike. For energy would leave the line ; this would cause
radial displacement, first at the end where the resistance was attached,
and later all along the line. (By " the line " is meant, for brevity, the
system of tubes extending from z = Q to z = l.)
Now in short-wire problems the electric energy is of insignificant
importance, as compared with the magnetic. It is usual to ignore it
altogether. This we can do by assuming c = 0. This necessitates
equality of wire- and return-current, for one thing; but, more im-
portantly, it prevents current leaving the conductors, so that C and H,
and F the current-density, are independent of z. There will be no
radial electric force in the conductors, in which, therefore, the energy-
current will be radial. But there will be radial force in the dielectric,
and therefore longitudinal energy-current. Since the radial electric
force and also the magnetic force in the dielectric vary inversely as the
distance from the axis, the longitudinal energy-current density will vary
inversely as the square of the distance. But, on account of symmetry,
we are only concerned with its total amount over the complete section
of the dielectric. This is
2.Er.2irrdr=rC, ..................... (118)
r
if V is the line-integral of Er the radial force, and C the wire-current.
It is clear, then, that we can now allow terminal .connections of the
form VjC = Z before used, and still have correct expansions of the
initial magnetic field, giving correct subsidence-solutions.
But it is simpler to ignore V altogether. For the equation of
E.M.F. will be
eQ=(ZQ + Zl + lLQp + lR'{ + lE'l)C, ..................... (119)
if eQ is the total impressed force in the circuit, Rf and R" the wire- and
sheath-functions of equations (55) and (56), Part II., on the assumption
H.E.P. — VOL. II 0
1 P
*-Jai
210 ELECTRICAL PAPERS.
m = 0, and Z0, Zl the terminal functions, such that V/C = Zl at z = l,
and = - ZQ at z = 0. It does not matter how e0 is distributed so far as
the magnetic field and the current are concerned. Let it then be
distributed in such a way as to do away with the radial electric field,
for simplicity of reasoning. The simple-harmonic solution of (119) is
obviously tc be got by expanding Z0 and Zl in the form R + Lp, where
E and L are functions of £>2, and adding them on to the l(R' + Up]
equivalent of l(LQp + R" + R"), as in equation (66), Part II.
Regarding the free subsidence, putting eQ~0 in (119) gives us the
determinantal equation of the _p's ; and as the normal //-functions are
definitely known, the expansion of the magnetic field can be effected.
The influence of the terminal arrangements must not be forgotten in
reckoning A.
Coaxial Tubes with Displacement allowed for. Failure to obtain Solutions in
Terms of V and C, except when Terminal Conditions are VC = 0, or
when there are no Terminals, on account of the Longitudinal Energy-
Flux in the Conductors.
In coming, next, to the more general case of equation (56), but
without restriction to exactly longitudinal current in the conductors,
it is necessary to consider the transfer of energy more fully. In the
dielectric the longitudinal energy-current is still VC. The rate of
decrease of this quantity with z is to be accounted for by increase of
electric and magnetic energy in the dielectric, and by the transfer of
energy into the conductors which bound it. Thus,
d ™_ dV ~r dCv
— — — y {j — -- — -\j -- - y .
dz dz dz
But here,
-^ = SF, and -~=L0C+E-F) ............ (120)
dz dz
by (59) and (56), Part II., E and F being the longitudinal electric forces
at the inner and outer boundaries of the dielectric (when there is no
impressed force). So
FC. ................. (121)
The first term on the right side is the rate of increase of the electric
energy, the second term the rate of increase of the magnetic energy in
the dielectric, the third is the energy entering the inner conductor per
second, the fourth that entering the outer conductor; all per unit
length.
If the electric current in the conductors were exactly longitudinal,
the energy-transfer in them would be exactly radial, and EC and - FC
would be precisely equal to the Joule-heat per second plus the rate of
increase of the magnetic energy, in the inner and outer conductor,
respectively. But as there is a small radial current, there is also a
small longitudinal transfer of energy in the conductors. Thus, Er and
Et being the radial and longitudinal components of the electric force,
ON THE SELF-INDUCTION OF WIRES. PART III. 21 1
in the inner conductor, for example, the longitudinal and the radial
components of the energy-current per unit area are
ErH/±7r and EJI/47T,
the latter being inward. Their convergences are
*M, and l£r*-7/,
az 4?r r dr 4?r
£(-'"/\-XW and M+£*ff+*^
47r\ az / 4?r dz 4?r 4?r dr 4?r dr
or ErPr - — ^, and EZTZ + — ^,
if Fr and Fz are the components of the electric current-density. The
sum of the first terms is clearly the dissipativity per unit volume ; and
that of the second terms is, by equation (13), Part. I., 5ftfi/4ir, the
rate of increase of the magnetic energy.
The longitudinal transfer of energy in either conductor per unit area
is also expressed by - (47rk)-lH(dH/dz) ; or, by - (4^) - \dTJdz)
across the complete section, if Tl temporarily denotes the magnetic
energy in the conductor per unit length.
Now let Elt Fv Cv Fi, and E2, F2, C2, F2, refer to two distinct
normal systems. Then, if we could neglect the longitudinal transfer in
the conductors, we should have
d,rrn rr n x ^ ^ _ ^ (122)
the left side referring to unit length of line ; and, in the whole line,
Z/18-2'1, = [FiC,-F,C1]J + (ft-A) ........ . ......... (123)
Similarly, for a single normal system,
per unit length ; and, in the whole line,
(125)
We have to see how far these are affected by the longitudinal transfer.
We have
therefore, if the systems are normal,
It will be found that we cannot make the parts depending upon E
and F exactly represent the U12 - Tu in the conductors except when
212 ELECTRICAL PAPERS.
m2 is the same in both systems pl and p2. In that case, the parts
(£rr)1(^T)2 and (E^Z(H\ of the longitudinal transfer of energy in the
conductors, depending upon the mutual action of the two systems, are
equal ; (Er}l and (Er).2 being proportional to sin mz, and H-^ and H.2
proportional to cos mz. So, in case pl and p% are values of p belonging
to the same ??i2, the influence of the longitudinal energy -transfer in the
conductors goes out from (122) and (123), which are therefore true in
spite of it. Similarly, provided the m's can be settled independently
of the p's, equations (124) and (125) are true.
Now the normal V and C functions, say u and w, as before, may be
taken to be
u =
w= f ............................................ \co$(mz+0)J
so that V=Auept, C = Aw€ptt and
J.5.«t«(«+»); ........................ (127)
and the complete equations for the determination of m, 6, and p are
- tan 0 = ^ -iw(ml+e)=Zl, 0 = + R'm + Ump -, (128)
the first two of these being the terminal conditions, and Rfm + L'mp being
merely a convenient way of writing the real complex expressions;
(equation (68), with em = 0). It is clear that the only cases in which
the m's become clear of the p's are the before-mentioned five cases,
equivalent to ZQ and Zl being zero or infinite, and the line closed upon
itself, which is a sort of combination of both. Considering only the
four, they are summed up in this, F"(7 = 0 at the terminals, or the line
cut off from receiving or losing energy at the ends. We have then the
series of m's, 0, ir/l, 2ir/lt etc.; or JTT//, fir/Z, |TT//, etc.; and every m2 has
its own infinite series of ^'s through the third equation (128). These,
though very special, are certainly important cases, as well as being the
most simple. We can definitely effect the expansions of the initial
states in the normal functions, and obtain the complete solutions in
every particular.
Verification by Direct Integrations. A Special Initial State.
Although rather laborious, it is well to verify the above results by
direct integration of the proper expressions for the electric and magnetic
energies of normal systems throughout the whole line. Thus, let
-T- fill + s?Hi = 0, where — s? = 47ru1&1 p.. + m?.
dr r dr
did,
-j- j 2 = 0, where - s| = 47r/t1&1^2 + m|,
ON THE SELF-INDUCTION OF WIRES. PART III. 213
in the inner conductor. We shall find
(s? - si) r^H^dr - 87r((7ir2 - CfJ,
as Hl = 0 = //2 at r = a0; T1 and F2 being the longitudinal current-
densities at r = ar Similarly, for the outer conductor,
/ r»/2 o'*\
V51 - S2 )
if Cp C2 still be the currents in the inner conductor; the accents
merely meaning changes produced by the altered //- and k in the outer
conductor. We have 77' = 0 = H^ at r — ay in this case. Then, thirdly,
for the intermediate space,
*Ci<78*41ogS.
ai
Therefore the total mutual magnetic energy of the two distributions per
unit length is
—
47r
which, by using the above expressions, becomes, provided m} = m£,
Pi -P* Pi -P*
E and F being T/k, or the longitudinal electric forces at r = a^ or r = a2.
But
E-F=R"C,
where 72"= the jR? + JRf of equation (56), Part II. ; and
so (126) becomes
The mutual electric energy is obviously $ J^ Fg per unit length. By
summation with respect to z from 0 to /, subject to ^(7=0 at both ends,
we verify that the total mutual magnetic energy equals the total
mutual electric energy. The value of 2T in a single normal system is,
by (126a) and the next equation,
per unit length ; and that of 2 U is SV*. Hence, per unit length,
............ (129)
214 ELECTRICAL PAPERS.
In this use V=u and C = w, equations (126), and we shall obtain, for
the complete energy-difference in the whole line,
M say, ........... (130)
which is the expanded form of
or
as may be verified by performing the differentiations, using the expres-
sion for u/w in (127), remembering that m- in it is a function of p ; or,
more explicitly, put J - Sp(Rr + Up) for m, and then differentiate to p.
Given, then, the initial state to be V= F0, a function of z, and H = Hol
in the inner conductor, H02 in the dielectric, and H03 in the outer con-
ductor, functions of r and z, and that the system is left without
impressed force, subject to TC = 0 at both ends, the state at time t later
will be given by
the summations to include every p, with similar expressions for H, F,
y, etc., the magnetic force and two components of current, by substitut-
ing for u or w the proper corresponding normal functions ; the coefficient
A being given by the fraction whose denominator is the expression M.
in (130), and whose numerator is the excess of the mutual electric
energy of the initial and the normal system over their mutual magnetic
energy, expressed by
- £cos (mz+0) &*^£*+£^ ...(131)
where & -
and C{ is the same with r put for a^ and C£ is the same with r put
for alt a3 for a0, and s3 for sr It should not be forgotten that in the
case m = 0, the denominator (130) requires to be doubled, \l becoming
/. Also that R"t or Rf + L'p, contains m2, and must not be the m = 0
expression for the same.
To check, take the initial state to be e^l-z/l), with no magnetic
force, and let F=0 at both ends. We find immediately, by (130) and
(131), that at time/,
......... (132)
dp\Sp
where the m's are to be -n-jl, 2,7r/l, 3ir/l9 etc. ; the first summation being
with respect to m, and the second for the p's of a particular m.
But, initially,
ON THE SELF-INDUCTION OF WIRES. PART III. 215
Therefore we must have
• d (
-4
Simplified, it makes this theorem : —
1 ^/ d<f>\~1
-wr^vdp) '
if the p'a are the roots of $(p) = 0. This is correct.
The Effect of Longitudinal Impressed Electric Foi'ce in the Circuit.
The Condenser Method.
To determine the effect of longitudinal impressed force, keeping to
the case of uniform intensity over the cross-section of either conductor.
Let a steady impressed force of integral amount e0 be introduced in
the line at distance zl ; it may be partly in one and partly in the other
conductor, as in Part II. By elementary methods, we can find the
steady state of F, C it will set up. If, then, we remove e0, we can, by
the preceding, find the transient state that will result. Let F"0 be the
steady state of F set up, and /^ what it becomes at time t after removal
of e0 • then F0 - Fj represents the state at time t after e0 is put on. So,
if 2 Au represent the F" set up by the unit impressed force at zlt
will give the distribution of F* at time t after e0 is put on, being zero
when t = 0, and VQ when t = <x> . No zero value of p is admissible here.
From this we deduce that the effect of e0, lasting from t = t^ to
t = /j + dtv at the later time t, is
therefore, by time-integration, the effect due to an impressed force eQ at
one spot, variable with the time, starting at time tQt is
in which e0 is a function of tr
By integrating along the line, we find the effect of a continuously dis-
tributed impressed force, e per unit length, to be
(133)
wherein e is a function of both zl and tv and starts at time /0 ; whilst A
is a function of zv the position of the elementary impressed force edzr
To find A as a function of zv we might, since *2Au is the J^set up by
unit e at zv expand this state by the former process of integration.
But the following method, though unnecessary for the present purpose,
has the advantage of being applicable to cases in which VC is not zero
at the terminals, but F= ZC instead. It is clear that the integration
process, including the energy in the terminal apparatus, would be very
216 ELECTRICAL PAPERS.
lengthy, and would require a detailed knowledge of the terminal com-
binations. This is avoided by replacing the impressed force at zl by a
charged condenser; when, clearly, the integration is confined to one
spot. Let Sl be the capacity, and VQ the difference of potential, of
a condenser inserted at ZY If we increase S-^ infinitely it becomes
mathematically equivalent to an impressed force FQ, without the con-
denser.
Suppose 2 Awftpt is the current at z at time t after the introduction
of the condenser, of finite capacity ; then, since - S-^ V is the current
leaving the condenser, or the current at zv we have
being the value of w' at zr The expansion of F0 is therefore
initially ; and the mutual potential energy of the initial charge of the
condenser and of the normal u' corresponding to w' must be
But since there is, initially, electric energy only at zv and magnetic
energy nowhere at all, the only term in the numerator of A will be
that due to the condenser, or this - V^jp ; hence
A = -
where M is the 2( U - T) of the complete normal system, as modified by
the presence of the condenser, is the value of A in V=^Auftp\ making
expressing the effect at time t after the introduction of the condenser,
and due to its initial charge.
So far Sl has been finite, and consequently u', wf, M, and p depend
on its capacity as well as on the line and terminal conditions. But on
infinitely increasing its capacity, u' and u/ become u and w, the same as
if the condenser were non-existent. Therefore
...................... (134)
expresses the effect due to the steady impressed force F"0 at zlt at time I
after it was started. This will have a term corresponding to a zero p
(due to the infinite increase of Sl in the previous problem), expressing
the final state. Hence, leaving out this term, the summation (134),
with sign changed, and £ = 0, expresses the final state itself. Thus,
2 Au = 2
is the expansion required to be applied to (133). Put A = wJpM in it,
and it becomes
<135)
fully expressing the effect at z, t, due to the impressed force e, a function
of zl and tlt starting at time t0. To obtain the current, change u to w
ON THE SELF-INDUCTION OF WIRES. PART III.
217
outside the double integral. The M, when the condition VG - 0 at the
ends is imposed, is that of (130) ; the u and w expressions those of (126).
But if we regard S, Rf, and L' as constants (or functions of z), then
(135) holds good when terminal conditions V '•— ZC are imposed, pro-
vided the impressed force be in the line only, as supposed in (135).
Special Cases of Impressed Force.
When the impressed force is steady, and is confined to the place
2 = 0, and is of integral amount eQ) (135) gives
................ (136)
w0 being the value of w at z - 0, as the effect at time t after starting eQ.
The first summation expresses the state finally arrived at.
Again, in (135) let the impressed force be a simple-harmonic function
of the time. I have already given the solution in this case, so far as
the formula for C is concerned, in the case V= 0 at both ends, in
equation (76), Part II., which may be derived from (135) by using in
it w instead of u at its commencement, putting e = e0 sin nt, and effecting
some reductions. The F-formula may be got in a similar manner to
that used in getting (76), but it is instructive to derive it from (135), as
showing the inner meaning of that formula. Let e = e0 sin (nt + a) in it,
where e0 is a function of z. Effect the ^ integration, with t0 = 0 for
simplicity. The result is
*
(137)
The first summation cancels the second at the first moment, and
ultimately vanishes, leaving the second part to represent the final
periodic solution. Take a = 0; and use the u, w, M expressions of (126)
and (130), and let $m stand for ra2 + Sp(R'm + L'mp), so that <£w = 0
gives the p'a for a particular m2. Then we obtain, (with F= 0 at both
ends),
cos mz
I cos mz1 . eQdz1 . (p sin nt + n cos nt)
Jo
cos mz\ cos mzl . e0 sin nt . dz1
mse d'2/dt2 = - n2. But, if e0 = 2 em, the equation of Vm is
218 ELECTRICAL PAPERS.
(by (60) and (63), Part II. ), so that
-de d N esinnt
U '
by a well-known algebraical theorem, the summation being with respect
to the p's which are the roots of $m = 0, considered as algebraic. We
have also
mz\ cosmz1e0dzv ................ (140)
Jo
the summation being with respect to m.
Uniting (139) and (140), there results the previous equation (138),
in which the summation is with respect to all the ^»'s belonging to all
the m's. In the case m = 0, the 2/1 must be halved. In the form of a
summation with respect to m, similar to (77) for C, the corresponding
F"-solution is
_ _ 2F"0 > m sin mz{ (L'm - m2/Sn2)n sin nt + Erm cos nt}
~~
the impressed force being F0 sin nt, at z = 0. This, on the assumption
R'm = Rf, L'm = Z/, will be found to be the expansion of the form (80),
Part II.
How to make a Practical Working System of V and C Connections.
Now to make some remarks on the impossibility of joining on ter-
minal apparatus without altering the normal functions, the terminal
arrangements being made to impose conditions of the form V= ZC. It
is clear, in the first place, that if the quantity VG at z = Q and z = I
really represents the energy-transfer in or out of the line at those
places, then the equation
will be valid, provided u and w be .the correct normal functions. But
to make VG be the energy-transfer at the ends, requires us to stop the
longitudinal transfer in the conductors there, or make the current in
the conductors longitudinal. This condition is violated when the
current-function w is proportional to cos (mz + 0), as in the previous,
except in the special cases, because the radial current y in the conduc-
tors is proportional to sin (mz + 6), and y has to vanish. Not in the
dielectric, but merely in the conductors.
We can ensure that VG is the energy-transfer at the ends, by coating
the conductors over their exposed sections with infinitely conducting
material, and joining the terminal apparatus on to the latter. The
current in the conductors will be made strictly longitudinal, close up to
the infinitely conducting material, and y will vanish in the conductors.
But y in the dielectric at the same place will be continuous with the
radial surface-current on the infinitely conducting ends, due to the
ON THE SELF-INDUCTION OF WIRES. PART IV. 219
sudden discontinuity in the magnetic force. Thus the energy-transfer,
at the ends, is confined to the dielectric.
It is clear, however, that the normal current-functions in the two
conductors must be such as to have no radial components at the ter-
minals, so that they cannot be what have been used, such that d2/dz* =
constant. They require alteration, of sensible amount, it may be, only
near the terminals, but, theoretically, all along the line. It would
therefore appear that only the five cases of V— 0 at either or both ends,
or C= 0 ditto, or the line closed upon itself, admit of full solution in the
above manner. The only practical way out of the difficulty is to
abolish the radial electric current in the conductors, making (66) the
equation of V, and VC the longitudinal energy- transfer, with full appli-
cability of the V— ZC terminal conditions.
PART IV.
Practical Working System in terms of V and C admitting of Terminal
Conditions of the Form V = ZC.
As mentioned at the close of Part III., it would appear that the only
>racticable way of making a workable system, which will allow us to
itroduce the terminal conditions that always occur in practice, in the
form of linear differential equations connecting C and V, the current
id potential-difference at the terminals, is to abolish the very small
idial component of current in the conductors. This does not involve
ic abolition of the radial dielectric current which produces the electric
Lisplacement, or alter the equation of continuity to which the total
current in the wires is subject. The dielectric current, which is Sf^per
unit length of line, and which must be physically continuous with the
radial current in the conductors at their boundaries, may, when the
latter is abolished, be imagined to be joined on to that part of the longi-
tudinal current in the conductors that goes out of existence by some
secret method with which we are not concerned.
We assume, therefore, that the propagation of magnetic induction and
electric current into the conductors takes place, at any part of the line,
i if it were taking place in the same manner at the same moment at all
irts (as when the dielectric displacement is ignored, making it only a
juestion of inertia and resistance), instead of its being in different
stages of progress at the same moment in different parts of the line,
lis requires that a small fraction of its length, along which the change
C is insensible, shall be a large multiple of the radius of the wire,
'he current may be widely different in strength at places distant, say,
mile, and yet the variation in a few yards be so small that this
;tion, so far as the propagation of magnetic induction into it is con-
;rned, may be regarded as independent of the rest of the line ; the
variation of the boundary magnetic-force, or of (7, fully determining the
iternal state of the conductors, exactly as it would do were there no
brostatic induction.
220 ELECTRICAL PAPERS.
In a copper wire, in which ft=l, and &= 1/1700, the value of the
quantity ^ir^lcp is p/135. On the other hand, the quantity m in
- s2 = 47r/4p + m2 has values 0, a-//, 2?r//, etc., or a similar series, in
which / is the length of the line in centimetres, so that^V/J is a minute
fraction, unless j be excessively large. But then it would correspond to
an utterly insignificant normal system. We may therefore take
It will be as well to repeat the system that results, from Part II.
The line-integral of the radial electric force across the dielectric being
F, from the inner to the outer conductor (concentric tubes), and the
line-integral of the magnetic force round the inner conductor being
4?r(7, so that C is the total current in it, accompanied by an oppositely
directed current of equal strength in the outer conductor, V and C are
connected by two equations, one of continuity of 6', the other the
equation of electric force, thus : —
.......... (141)
Here e is impressed force, S the electric capacity, and L0 the inductance
of the dielectric, all per unit length of line ; and R" and R" are certain
functions of d/dt and constants such that R"C and - R"C are the longi-
tudinal electric forces of the field at the inner and outer boundaries of
the dielectric, which, when only the first differential coefficient dC/dt is
counted, become
respectively, where JRV L^ and R% L2 are the steady resistances and
inductances of the two conductors.
Extension to a Pair of Parallel Wires, or to a Single Wire.
The forms of R'{ and R% are known when the conductors are concen-
tric circular tubes, of which the inner may be solid, making it an
ordinary round wire. Now if the return-conductor be a parallel wire or
tube externally placed, it is clear that we may regard R'{ and R" as
known in the same manner, provided their distance apart be sufficiently
great to make the departure of the distribution of current in them from
symmetry insensible. We have merely to remember that it is now the
inner boundary of the return-tube that corresponds to the former outer
boundary, i.e. when it surrounded the inner wire concentrically.
The quantity V will still be the line-integral of the electric force
across the dielectric by any path that keeps in one plane perpendicular
to the axes of the conductors, in which plane lie the lines of magnetic
force. Also, the product VG will still represent the total longitudinal
transfer of energy per second in the dielectric at that plane, or, in short,
the energy-current. As regards the modified forms of S and Z0, there
is, in strictness, some little difficulty, on account of the dielectric being
necessarily bounded by other conductors than the pair under considera-
tion, in which others energy is wasted, to a certain extent. This can
ON THE SELF-INDUCTION OF WIRES. PART IV. 221
only be allowed for by the equations of mutual induction of the various
conductors, which are not now in question. But if our pair, for instance,
be suspended alone at a uniform height above the ground, so that only
the very small dissipation of energy in the earth interferes, it would
seem, so far as the wire-current is concerned, to be an unnecessary re-
finement to take the earth into consideration. There are, then, two or
three practical courses open to us ; as to suppose the earth to be a per-
fect nonconductor and behave as if it were replaced by air, or to treat it
as a perfect conductor. In neither case will there be dissipation of
energy except in our looped wires, which have no connection with the
earth, but there will be a different estimation of the quantities LQ and
S required. For, when we suppose the earth is perfectly conducting, we
shut it out from the magnetic field as well as from the electric field.
The electric capacity S is that of the condenser formed by the two wires
and intermediate dielectric, as modified by the presence of the earth
(the method of images gives the formula at once), and the value of L0
is such that L^S = fj.c = v~z, where v is the velocity of undissipated waves
through the dielectric ; that is, as before, LQ is simply the inductance of
the dielectric, per unit length of line. On the ground, there will be
both electrification and electric current, due to the discontinuity in the
electric displacement and the magnetic force respectively ; but with
these we have no concern. In the other case, with extension of the
magnetic and electric fields, the product L0S still equals v~2. Neither
course is quite satisfactory ; perhaps it would be best to sacrifice con-
sistency and let the magnetic field extend unimpeded into the earth,
considered as nonconducting, with consequently no electric current and
waste of energy, whilst, as regards the external electric field, we treat it
as a conductor. We must compromise in some way, unless we take the
earth into account fully as an ordinary conductor. Similarly, if the
line consist of a single wire whose circuit is completed through the
earth, by regarding it as infinitely conducting we replace the true
variably distributed return-current by a surface-current, and, termi-
nating the magnetic field there, have L0S = v~2; but if we allow the
magnetic field to extend into it, though with insignificant loss of energy
by electric current, we shall no longer have this property.
Effect of Perfect Conductivity of Parallel Straight Conductors. Lines of
Electric and Magnetic Force strictly Orthogonal, irrespective of Form
of Section of Conductors. Constant Speed of Propagation.
The property is intimately connected with the influence of perfect
conductivity on the state of the dielectric. For perfect conductivity
will make the lines of electric force normal to the conducting bound-
aries, will make them cut perpendicularly the magnetic-force lines,
which lie in the planes z = const, and are tangential at the boundaries,
and will make LQS = v~2, irrespective of the shape of section of the con-
ductors. Now, at the first moment of putting on an impressed force,
wires always behave as if they were infinitely conducting, so that, by
the above, the initial effect is simply a dielectric disturbance, travelling
222 ELECTRICAL PAPERS.
along the dielectric, guided by the conductors, with velocity v, irre-
spective of the form of section. Of course dissipation of energy in the
conductors immediately begins, and finally completely alters the state
of things, which would be, in the absence of dissipation, the to-and-fro
passage of a wave through the dielectric for ever. Except the extension
to other than round conductors, this does not add to the knowledge
already derived from their study. The effect of alternating currents in
tending to become mere surface-currents as the frequency is raised
(Part I.) may be derived from, or furnish itself a proof of, the property
above mentioned — that at the first moment there is merely a dielectric
disturbance. For in rapid alternations of impressed force, we are con-
tinually stopping the establishment of the steady state at its very com-
mencement, and substituting the establishment of a steady state of the
opposite kind, to be itself immediately stopped, and so on.
When the dielectric is unbounded — not enclosed within conductors —
there is also the outward propagation of disturbances to be considered ;
but it would appear, by general reasoning, that this is, relatively to the
main effect, or propagation parallel to the wires, a secondary phe-
nomenon.
Extension of the Practical System to Heterogeneous Circuits, with " Con-
stants" varying from place to place. Examination of Energy Pro-
perties.
It is clear that the same principles apply to conductors having other
forms of section than circular, when V and C are made the variables,
provided the functions R" and R% can be properly determined. The
quantity VC being in all cases the energy-current, its rate of decrease as
we pass along the line is accounted for (as in Part III.), thus, by making
use of (141), with e = 0,
........ (142)
that is, in increasing the electric and magnetic energies in the dielectric,
and in transfer of energy into the conductors, to the amounts CR'{C and
CR"C per second respectively ; which are, in their turn, accounted for
by the rate of increase of the magnetic energy, and the dissipativity, or
Joule-heat per second in the two conductors ; or
CR{fc=Ql+Tv CRzc=Q2+f2, ............ (us)
Q being the dissipativity and T the magnetic energy per unit length of
conductor.
These equations (143) must therefore contain the enlarged definition
of the meaning of the functions R(' and fi%. For it is no longer true
that R"C is, as it was in the tubular case, the longitudinal electric
force at the boundary of the conductor to which R'{ belongs. It is a
sort of mean value of the longitudinal electric force. Thus, we must
have
...................... (144)
J4T-*
ON THE SELF-INDUCTION OF WIRES. PART IV. 223
if E be the longitudinal electric force and H the component of the
magnetic force along the line of integration, which is the circuital
boundary of the section of the conductor perpendicular to its length.
But no extension of the meaning of V is required from that last stated.
Let us, then, assume that R'{ and II'.', can be found, their actual dis-
covery being the subject of independent investigation. We can always
fall back upon round wires or tubes if required. They are functions of
d/dt and constants, if the line is homogeneous. But, as we have got
rid of the radial component of current in the conductors, and its diffi-
culties, the constancy of the constants in R" and li'i (as the conductivity
and the inductivity, or the steady resistance, or the diameter) need no
longer be preserved. Provided the conductors may be regarded as
homogeneous along any few yards of length, they may be of widely
diHerent resistances, etc., at places miles apart. Then Rf, R% become
functions of z as well as of d/dt, and S a function of z. Let our system be
e-~ = B"C, ...(145)
dz dz
where both R" and S" are functions of d/dt and z. As regards £", it is
simply S(d/dt) when the dielectric is quite nonconducting. But when
leakage is allowed for, it becomes K+S(d/dt), where K is the con-
ductance, or reciprocal of the resistance, of the dielectric across from
one conductor to the other. Then both K and S are functions of z.
The conduction-current is KV, and the displacement-current SV> whilst
their sum, or S"Vt is the true current across the dielectric per unit
length of line. We have now, by (145), with e = 0,
. ....(146)
dz dt
The additional quantity KT2 is the dissipativity in the dielectric per
unit length, whilst now GR'C includes the whole magnetic-energy
increase, and the dissipativity (rate of dissipation of energy) in the
conductors.
Let Vlt Cly and V^ C2 be two systems satisfying (145) with e = 0.
Then
from which we see that if the systems be normal, d/dt becoming^ and
p2 respectively, we shall have
...... <i47)
R" and R% being what R" becomes with pl and p2 for d/dt. As the
quantity in the {} is the U^-T^ of Part III., and the first term is
{712, we see that the mutual magnetic energy is
J'u-^C'.Cfir-.RW + Cft-ft) .................. (148)
The division by pl -p2 can be effected, and the right member of (148)
put in the form
224 ELECTRICAL PAPERS.
When this is done, we can find the mutual magnetic energy of any
magnetic field (proper to our system) and a normal field, in terms of
the total current in the wire and its differential coefficients with respect
to t ; so that, in the expansion of an arbitrary initial state, C, (7, C, etc.,
may be the data of the magnetic energy, instead of the magnetic field
itself.
We see also, from (148), that if T be the magnetic energy of any
normal system per unit length of line, then
2r=C^'; ............................ (149)
and therefore, if Q be the dissipativity in the conductors,
(150)
Now consider the connection of the two solutions for the normal
functions. Since the equation of C in general is, by (145),
a£\o az /
the normal (7-function, say w, is to be got from
d f 1 dw\ r,,,
__{ ) = H w, 0^2)
with d/dt =p in 72" and £", making them functions of z and £>. Let JT
and Y be the two solutions, making
w = X+qY, (153)
where q is a constant. The normal F"-function, say u, is got from w by
the first of (145), giving
if X' = dX/dz, Y' = dY/dz.
In X and F, which together make up the w in (153), p has the same
value. Therefore, in (147), supposing (7X to be X and C2 to be F, we
have disappearance of the right member, making
jg J) = 0, or FjOj - F2tfi = constant,
or XY' -YX' = S"* constant = hS", say, ........ (155)
leading to the well-known equation
connecting the two solutions of the class of equations (152); which we
see expresses the reciprocity of the mutual activities of the two parts
into which we may divide the electromagnetic state represented by a
single normal solution.
ON THE SELF-INDUCTION OF WIRES. PART IV. 225
Also, by (147), integrating with respect to z from 0 to /,
(l
Jo
SUlu.2dz - lA- ...(156)
o Jo Pi-P* Pi -Pt
either member of which represents the complete U12 - T12 of the line.
The negative of this quantity, as in Part III., is the corresponding
£712- T12 in the terminal arrangements; so that the value of 2(U— T)
in a complete normal system, including the apparatus, is
2(U-T) = Stfdz- u?dz-w? + w*, ...(157)
Jo JoqP dp dp
if Pr/C = Zl at z = l and Z0 at 2 = 0, (these being functions of p and
constants), and wv WQ are the values of w at z = l and 0. Or, which is
the same,
(158)
as before used.
The Solution for V and C due to an Arbitrary Distribution of e, subject
to any Terminal Conditions.
There is naturally some difficulty in expressing the state at time t
in this form : —
due to an arbitrary initial state, on account of the difficulty connected
with
(JZf-BfHCft-ft),
and the unstated form of R". But when the initial state is such as can
be set up by any steadily-acting distribution of longitudinal impressed
force (e an arbitrary function of 2), so that whilst r is arbitrary, C is
only in a very limited sense arbitrary, and C, C, etc., are initially zero,
and certain definite distributions of electric and magnetic energy in the
terminal apparatus are also necessarily involved ; in this case we may
readily find the full solutions, and therefore also determine the effect of
any distribution of e varying anyhow with the time. In fact, by the
condenser-method of Part III., we shall arrive at the solution (135);
we have merely to employ the present u and w, and let M be the value
of the right member of (158). The following establishment, however,
is quite direct, and less mixed up with physical considerations.
To determine how V and C rise from zero everywhere to the final
state due to a steadily-acting arbitrary distribution of e put on at
the time 2 = 0. Start with e2 at 2 = 22 and none elsewhere, and let
(X + qQY)AQ and (X+qlY)Al be the currents on the left (nearest 2=0)
and right sides of the seat of impressed force. We have to find qQ, ql}
AQt and Ar The condition F=ZQC at 2 = 0 gives us, by (153), 154),
therefore q0 = - (X'0 + S{ZQX0) + (Yl + S!ZQYJ. .. .......... (159)
H.E.P.— VOL. II. P
226 ELECTRICAL PAPERS.
Similarly, V— Zfi at z = /, gives us
l)^(Y[ + S'{ZlYl} ............. (160)
Here the numbers 0 and l mean that the values of X, etc., and S" at
z = 0 and atz = l are to be taken.
Now, at the place z = £2» the current is continuous, whilst the V rises
by the amount e2 suddenly in passing through it. These two con-
ditions give us
where the 2 means that the values at z = zz are to be taken. These
determine A0 and A^ to be
or A -* i or a oa /161\
A*----
Now use (155), making the denominator in (161) be ^(<?0-!?i)- We
have then, if G'0 and Gl are the currents on the left and right sides of
the seat of impressed force,
These are, when the p is throughout treated as d/dt, the ordinary
differential equations of GO and C\ arising out of the partial differential
equation of C by subjecting it to the terminal conditions and to the
impressed-force discontinuity.
Now make use of the algebraical expansion *
/(?„> = v_JW ..(163)
* [The limitations to which this expansion is subject render its use in the above
manner undesirable even when it gives correct results, and, of course, when it
gives incorrect results, as when the initial G is not zero, the manner of application
should necessarily be changed. We should rather proceed thus : — Let
. ,...(1)
be the differential equation connecting G with e, where p0 stands for d/dt, and
0(2>) = 0 is the determinantal equation of the system, that is, <p(p) may be either
the characteristic function in fully developed form, or the same multiplied by any
function that does not conflict with its use in the determinantal equation. Then
we shall have, by the algebraical theorem,
(2\
where <f>f means d^/dp, and the summation includes all the roots of <j>(p) =
Therefore, by (1), using (2) and integrating,
e being zero before, and constant after t = 0. But also, by (2),
1 = 2 1 > —(4)
ON THE SELF-INDUCTION OF WIRES. PART IV. 227
the summation being with respect to the p's which are the roots of
<j>(.p) = 0, without inquiring too curiously into its strict applicability, or
troubling about equal roots. Here pQ has to be d/dt, and the p'a the
roots of
<£ = %o-?i) = °;
so that (162) expands to
e2 (164)
where the single q takes the place of the previous qQ or qv which have
now equal values, and C has the same expression on both sides of the
seat of impressed force. But e2 is constant with respect to /, whilst C
is initially zero ; hence
d/dt —p
where 00 means 0 with p - 0, so that (3) becomes
o P<t>
(5)
Now perform the operations indicated by J\p^ and we get
0 = 8^+6^-^1.6^, ...(6)
0o P<t>'
where f0 means / with p = 0. (See also the investigation at the end of the (later)
paper on "Resistance and Conductance Operators.") Here e/"0/0o is the
steady current, when there is such a thing.
Thus, if we take 0 = h(q0 - qj, and use (6), (162) lead to
e*><, .............. , ............... (7)
0o
instead of (165). In the first terms the p = 0 values must be taken, with
w2 = X,> + q1 F2 in (7), and w2 = X2 + q0 F2 in (8).
Here q0 and ql are not the same, but they are the same in the summation ; because
then 0 = 0. We may write (165) thus :—
^=^0 + 2^- «", .................................... 0)
where <70 is the final steady current, to be got direct from the first or second of
(162) as the case may be. Therefore (166) should be
where C0 is the final steady current at z due to the whole impressed force.
In accordance with the above (167) is not always applicable, and in accordance
with the text (168) is incorrect. But the substituted method of finding (70, viz.
(169), will do when (164) is applicable, and fail otherwise. The result (170),
however, is independent of this restriction, as it is immediately obtainable from
the differential equations (162).
So up to (162) inclusive the text is correct. Then pass on to (170), (172), as the
next clear results. Between these places modify the method as in the present
note.]
228 ELECTRICAL PAPERS.
which brings (164) to
065)
which is the complete solution. By integration with respect to z we
find the effect due to a steady arbitrary distribution of e put on at
£ = 0; thus
Ji
ewdz
a66)
where <// = d(J>/dp, and w is the normal current-function X-t-qY. To
express the F"-solution, turn the first w into u. The extension to e
variable with t, as in Part III., is obvious. But as the only practical
case of e variable with t is the case of periodic e, whose solution can be
got immediate!}7 from the equations (162) by putting p2 = - ?i2, constant,
the extension is useless. Note that qQ and ql are not equal in (162),
and therefore in the periodic solution obtained from (162) direct they
must be both used.
The quantity - <$>' which occurs here is identical with the former
complete '2(U - T) of the line and terminal apparatus of (157) or (!58).
Let C0 be the finally-reached steady current. By (166) it is
(167)
To this apply (163), with pQ = 0. Then a finite expression for CQ is
CQ = ew0dz, ........................... (168)
<PoJo
where WQ and <f>Q are what w and </> become when p = 0 in them. Or,
rather, it would be so if qQ and q1 taken as identical could be consistent
with /> = 0. But this is not generally true, so that (168) is wrong. To
suit our present purpose, we must write, by (162),
(169)
the q0 being used in w0, and the ql in wr Now we can take p = 0, and
get the correct formula to replace (168), viz.
o\
the second 0 meaning that p = 0 in w0 and wr
If there is no leakage (K= 0 in S"), C0 becomes a constant, given by
C0= edz-r Rdz + RQ + R, .................. (171)
o
ON THE SELF-INDUCTION OF WIRES. PART IV. 229
where the numerator is the total impressed force, and the denominator
the total steady resistance ; R, H0, and R^ being what E", - Z0, and Zl
become when^? = 0 in them.
But when there is leakage (170) must be used; it would require a
very special distribution of impressed force to make C0 the same every-
where. To find the corresponding distribution of F", say V& in the
steady state, we have then
so that a single differentiation applied to (170) finds
Knowing thus C0 finitely, we may write (166) thus,
where C0 is given in (170). The summation here, with / = 0, is there-
fore the expansion of CQ.
The internal state of the wire is to be got by multiplying the first w
by such a function of r, distance from the axis, and of whatever other
variables may be necessary, as satisfies the conditions relating to inward
propagation of magnetic force, and whose value at the boundary is
unity. In the simple case of a round solid wire, (172) becomes, by
(87), Part II,
w\ewdz
r ^sr
This gives Cn the current through the circle of radius r, less than at
the radius of the wire, C0r being the final value. The value of sl is
( - 47iY*1&1^)i. Here of course we give to /xa, &j, and a-^ their proper
values for the particular value of z. As before remarked, they must
only vary slowly along z.
In the case of a wire of elliptical section it is naturally suggested
that the closed curves taking the place of the concentric circles defined
by r = constant in (173) are also ellipses; and that in a wire of square
section they vary between the square at the boundary and the circle at
the axis. The propagation of current into a wire of rectangular sec-
tion, to be considered later, may easily be investigated by means of
Fourier-series, at least when the return-current closely envelops it.
Explicit Example of a Circuit of Varying Resistance, etc. Bessel Functions.
As an explicit example of the previous, let us, to avoid introducing
new functions, choose the electrical data so that the current-functions
A' and Y are the /0 and K0 functions. This can be done by letting R"
be proportional and S" inversely proportional to the distance from
one end of the line. Let there be no leakage, and
where S0 is a constant, and R'f a function of d/dt, but not of z. The
electromagnetic and electrostatic time-constants do not vary from one
230 ELECTRICAL PAPERS.
part of the line to another. The equation of the current-function is
-!&•©-*«*•" ....................... (152a)
from which we see that
X= JJ(fz), Y= K0(fz), where /= ( -
But, owing to the infinite conductivity a* the 2 = 0 end of the line,
making KQ(fz) = GO there, we shall only be concerned with the JQ
function, that is, on the left side of the impressed force, in the first
place. Since V is made permanently zero at z — 0, the terminal condi-
tion there is nugatory. So
w = JQ(fz), and w = JQ(fz) + q&tfz) ;
and u
on the left and right sides of an impressed force, say at z = z2. The
value of qv got from the V= Zfi condition at z = l, is
We have also
and the (7-solution (166) becomes *
l -«*), ......... (166a)
where <f> = - qJSop, and q1 is given by
If we short-circuit at z = l, making ^i = 0, we introduce peculiarities
connected with the presence of the series of j^'s belonging to /= 0.
The expression of ^ is then, by (160a), q^ = — J^fl) / K^fl). It seems
rather singular that we should have anything to do with the K-^
function, seeing that C and V are expanded in series of the /0 and
«/! functions. But" on performing the differentiation of <j> with respect
it turns out to be all right, the denominator in (166a) becoming
in general ; whilst in the / = 0 case, which makes </> = J-KJ' /2, we have
The value of <f> when p = 0 in it is, by inspection of the expansions of
Jl and Klt simply %RJP, the steady resistance of the line ; EQ being the
* [In accordance with the remarks in the footnote on page 226, we should write
the equation (166a) thus : —
where O0 is the expression for the steady current at z due to e.]
ON THE SELF-INDUCTION OF WIRES. PART IV. 231
constant that fig becomes with p = 0. We may therefore write (166a)
thus : —
**•*
dp dp^
where the first term is (70, the finally-reached current ; the following
summation, extending over them's belonging to/=0, is its expansion,
and therefore cancels the first term at the first moment ; and the third
part is a double summation, extending over all the/s except /= 0, each
/-term having its following infinite series of p-terms. This quantity
(the third part) is zero initially as well as finally. If there were no
elastic displacement permitted (S0 = 0), the solution would be repre-
sented by the remainder of (172a), for we should then have C inde-
pendent of z, and
P edz=\ R"dz.C=lR'W.C
[
Jo
for the differential equation of (7, whose solution is plainly given by the
first two terms. The third part of (Ilia} is therefore entirely due
to the combined action of the electrostatic and magnetic induction.
When the impressed force is entirely at z - 1, and of such strength as
to produce the steady current (70, and if we take R" = R + Lp, where R
and L are constants, there will be only two ^>'s to each /, given by
/2^= -S0p(E + Lp). The subsidence from the steady state, on removal
of the impressed force, is represented by
V J0(fi) S7p
where the summations range over the ^'s, not counting the p = - RjL
whose G'-term is exhibited separately; there is no corresponding F-term.
A comparatively simple solution of this nature may be of course inde-
pendently obtained in a more elementary manner. On the other hand,
great power is gained by the use of more advanced symbolical methods,
which, besides, seem to give us some view of the inner meaning of the
expansions and of the operations producing them, that is wanting in the
treatment of a special problem on its own merits, by the easiest way
that presents itself.
Homogeneous Circuit. Fourier Functions. Expansion of Initial State to
suit the Terminal Conditions.
Leaving, now, the question of variable electrical constants, let the line
homogeneous from beginning to end, so that R" and S" are functions
p, but not of z. The normal current-functions are then simply
X = cos mz, Y= sin mz,
'here ra is the function of p given by - m? = R"S", so that
w = cos mz + q sin mz, u = (m/S") (sin mz - q cos mz). ( 1 74)
232 ELECTRICAL PAPERS.
Let there be a single impressed force e2 at z = z2 ; then the differen-
tial equations of the currents on the left and right sides of the same,
corresponding to (162), will be
where g0 and ql are given by
<?0=-^X (
m °' Zl (
As before, in the case of an arbitrary distribution of e we are led to the
solution (165), wherein for w (and for u in the corresponding F'-formula)
use the expressions (174), in which q is to be the common value of the
qQ and ql of (1606), and
<HKS%o-ffi) = 0 ........................ (175)
is the determinantal equation of the p's.
Use (170) to find the final steady current-distribution. Thus, now,
CQ = (cos mz + ql sin mz) I (cos mz + qQ sin mz)edz
+ (cos mz + qQ sin mz) I (cos mz + ql sin mz)edz -f —(^ - ^), (176)
in which m, <?0, #15 and S'f have the /> = 0 values. They are, if
= g say,
if .R is the steady resistance of line (both conductors), and K is the
conductance of the insulator, both per unit length of line ;
if RQ = effective steady resistance at the z = 0 terminals, and
_ gi sin gli - KR-^ cos gli
1 gi cos gli + KRl sin gli9
if Rl = effective steady resistance at the z = I terminals.
The expression on the right side of (176) is, of course, real in the
exponential form, and the steady distribution of V is got by
KF0 = - dCJdz.
Using the thus-obtained expressions, we reach the (172) form of C-
solution, and the corresponding
The value of <£' here, got by differentiation with respect to p, may be
written in many ways, of which one of the most useful, for expansions
in Fourier series, is the following. Let
w = (l+qrf cos(mz+0);
ON THE SELF-INDUCTION OF WIRES. PART IV. 233
d<t> m d f, ,/m
then
(m Z^-Z« \-l\ (177)
dp d(ml)\S" (m/S")* + Z^~J J
Corresponding to this,
finds the angles ml ; it is got by the union of
tan(9 = £%/w, tan (ml + 6) = Sf'ZJm, .......... (179)
which are equivalent to (160&).
For example, if we take Rff = R, constant, thus abolishing inertia,
and S" = Sp, no leakage, and S constant (R and S not containing p, that
is to say), the expansion of F0 (an arbitrary function of z) is [see also
vol. i., p. 123, and p. 152]
sin (mz + 0) I V^ sin (mz + 6)dz
Jo _, ....... (180)
L m ZI~ZQ \
d(ml) ty (m/Spf + Z.zJ
subject to (178). Here p = - m?/ES, so that the state of the line at
time t after it was V^ when left to itself, is got by multiplying each
term in the expansion by ^-r^tiRS. The corresponding current is given
by RC = - dF/dz. But the solution thus got will usually only be
correct, although (180) is correct, when there is, initially, no energy in
the terminal apparatus. If there be, additional terms in the numerator
of (180) are required, to be found by the energy-difference method of
Part III. They will not alter the value of the right member of (180) at
all ; they only come into effect after the subsidence has commenced.
Similar remarks apply whatever be the nature of the line. It is,
however, easy to arrange matters so that the energy in the terminal
apparatus shall produce no effect in the line. For example, join the
two conductors at one end of the line through two equal coils in
parallel ; if the currents in these coils be equal and similarly directed
in the circuit they form by themselves, they will not, in subsiding,
affect the line at all.
Returning to (177), or other equivalent expression, it is to be
observed that particular attention must be paid to the roots ml = 0,
which may occur, or to the series of roots p belonging to the m = 0 case,
when we are working down from the general to the special, and happen
to bring in m = 0. Take ^ = 0 for instance, making, by (175) and
(1606),
<£= -ZQ-^
Up
rhere m2 = - SpR". Then
_-
dp dp 2m \dp p ) 2
234 ELECTRICAL PAPERS.
Now, as long as Z^ is finite, m cannot vanish ; but when Z0 is zero,
giving ml = any integral multiple of IT, m = 0 is one case. Then we
have, when m is finite,
and
dp 2\dp p *dp 2 dp^
but when m is zero the middle term on the right of the preceding
equation becomes finite, making
The result is that the current-solution contains a term, or infinite
series, apparently following a different law to the rest, with no corre-
sponding terms in the F-solution. This merely means that the mean
current subsides without causing any electric displacement across the
dielectric, when the ends are short-circuited (z?=0); so that if, in the
first place, the current is steady, and there is no displacement, there
will be none during the subsidence.
Transition from tJie Case of Resistance, Inertia, and Elastic Yielding
to the same without Inertia.
The transition from the combined inertia-and-elasticity solutions to
elasticity alone is very curious. Thus, let Z=0 at both ends, and
R" = R + Lp, where R and L are constants not containing p. The rise
of current due to e is shown by
the m's in the summation being ir/lt 2ir/l, etc. ; and each having two
»'s, given by
The m = 0 part is exhibited separately, and is what the solution would
be if e were a constant (owing to the constancy of R). But, whatever e
be, as a function of z, the summation comes to nothing initially, on
account of the doubleness of the p'st just as in (I72a) the double
summation vanishes by reason of every ^-summation vanishing when
Now, in (183), let L be exceedingly small. The two p's approximate
to - m?/BS, the electrostatic one, and to - B/L, the magnetic one,
which goes up to oo , the storehouse for roots. The current then rises
thus :—
C-
Fed? H -f-m/L\ 2 ^— , Cl
: Mz'^ * J + ^Vcoswwl
Jo R* M Jo
--Ri2j™ mz]oe(
But the first line on the right side is equivalent to
Vcosrascosm^^l-e-"^) (184)
ON THE SELF-INDUCTION OF WIRES. PART IV. 235
and here the exponential term vanishes instantly, on L being made
exactly zero, so that (184) becomes
I _ €-'»2«/fls\ (185}
R Rl J0
except at the very first moment, when it gives C=e/Ii, which is quite
wrong, although the preceding formula, giving 0=0 at the first
moment, is correct. Or, (185) is equivalent to
from which inertia has disappeared. Here V is given by (188) below.
The process amounts to taking one half the terms of the summation in
(183), and joining them on to the preceding term to make up e/fi,
which is quite arbitrary. An alternative form of (185) is
C= 7edz + y]cosmzecosmzdz.€-m2t/«s ........ (186)
jKijo m*- J0
On the other hand, there is no such peculiarity connected with the
^-solution in the act of abolishing inertia. The m = 0 term is
- (sin mz I edz\ which =0,
ffl\8p Jo /
because m is zero and p finite. Therefore V rises thus,
inwzl ecosmzdz
-
before abolition of inertia. But as L is made zero, the denominator
becomes m2 for the electrostatic p, and oo for the other ; thus one half
the terms vanish, leaving
€-«*/™), ............ (188)
" Jo
when £ = 0, without any of the curious manipulation to which the
current-formula was subjected.
Transition from the Case of Resistance, Inertia, and Elastic Yielding
to the same without Elastic Yielding.
Next, let us consider the transition from the combined elasticity-and-
inertia solution to inertia alone (of course with resistance in both cases,
as in the preceding transition). It is usual to wholly ignore electro-
static induction in investigations relating to linear circuits. This is
equivalent to taking $ = 0, stopping elastic displacement, and compelling
the current to keep in the wires always, i.e. when the insulation is
perfect, as will be here assumed. We then have, by (145),
-as-0' -Ts-^ .................. (189>
236 ELECTRICAL PAPERS.
By integrating the second of these with respect to z we get rid of F",
and obtain the differential equation of (7,
say, ........... (190)
whence follows this manner of rise of the current, when e is steady
and put on everywhere at the time t = 0, reaching the final value (70,
............... (191)
<£j = 0 finding them's. We can find V at distance z by integrating the
second of (189) with respect to z from 0 to z; thus,
................... (192)
wherein C is to be the right member of (191). This finds V by
differentiations with respect to t performed on C. In the final state
put EQ for R", and - E0 for Z01 steady resistances. V will usually
vary with the time until the steady state is reached ; but if the line is
homogeneous, with only the two constants E and L, and if also ZQ and
Zl are zero, F"will be independent of t, and instantly assume its final
distribution.
Then, on these assumptions, we shall have
r=[edz-(f\\ledz, ..... (193)
Jo v/Jo
showing the current to rise independently of the distribution of e, and
V to have its final distribution from the first moment, which, when the
impressed force is wholly at 2 = 0, of amount e0, is eQ(l — z/l). This
infinitely rapid propagation of V is common-sense according to the
prescribed conditions, but absolute nonsense physically considered,
especially in view of the transfer of energy. The question then arises,
How does V really set itself up, when the line is so short that the
current rises sensibly according to the magnetic theory 1
To examine this, let the line-constants be E, St L (independent of
djdt\ and Z-l = Z^ 0. Put on e0 at z = 0 at time t = 0. V and C will
rise thus (a special case of (183) and (187)),
(1*
where m has the values ir/l, 2ir/l, etc., and
It is clear that when S is made to vanish, making m' = oo-, the
current-oscillations wholly vanish, reducing the (7-solntion to the first
of (193). But the F-oscillations remain in full force, though of in-
finitely short period, and subside at a definite rate. This means that
ON THE SELF-INDUCTION OP WIRES. PART IV. 237
the mean value of V at any place has to be taken to represent its actual
value, and this mean value is its final value. That is, if V denote the
mean value about which /^oscillates, we have
Introduce LS = v~2, where v is constant, making
very nearly, when the line is short; then the second of (194) becomes
jr. Ji _ *\ _ 2v-«* v~ cos mot, . ..(195)
\ I / I *—* m
which must very nearly show the subsidence of the oscillations. First
ignore the subsidence-factor, replacing it by unity, then (195) represents
a wave of /^travelling to and fro at velocity v, as thus expressed,
r-e. from *-0 to * =
F=0 beyond z = vt,
When vt = I, the whole line is charged to V— eQt The wave then moves
back in the same manner as it advanced, so that the state of things at
time t = l/v±r is the same, until t reaches 2l/v, when we have V=Q as
at first. This would be repeated over and over again if there were no
resistance, which, through the exponential factor, causes the range of
the oscillations of V at any place about the final value to diminish
according to the time-constant 2L/E. Also, the resistance has the
effect of rounding off the abrupt discontinuity in the wave of V.
I have given a fuller description of this case elsewhere [vol. I., p. 132],
and only bring it in here in connection with the interpretation accord-
ing to my present views regarding the transfer of energy. As it is
clear that this oscillatory phenomenon is, primarily, a dielectric phen-
omenon, and only affects the conductor secondarily, it is necessary
that the L in the above should not at the beginning be the full L of
dielectric and wires, but only L0, that of the dielectric, making v the
velocity of undissipated waves, although as the oscillations subside the
velocity must diminish, tending towards v = (LS)~l, which may, how-
ever, be far from being reached, especially in the case of an iron wire.
The nature of the dielectric wave is far more simply studied graphically
than by means of Fourier series, on the assumption of infinite con-
ductivity, which allows us to represent things by means of two oppo-
sitely travelling waves. To this I may return in the next Part.
On Telephony by Magnetic Influence between Distant Circuits.
I will conclude the present Part with a brief outline of the reasoning
hich guided me six months ago, when my brother's experiments on
iduction between distant circuits (mentioned in Part II.) in the north
>f England commenced, to the conclusion that long-distance signalling
(i.e. hundreds of miles) was possible by induction, a conclusion which
las been somewhat supported by results, so far as the experiments have
238 ELECTRICAL PAPERS.
yet gone. Recognising the great complexity of the problem, and the
difficulty of hitting the exact conditions, I made no special calculations,
but preferred to be guided by general considerations; for, in the en-
deavour to be precise when the data are uncertain and very variable,
one is in great danger of swallowing the camel.
One may be fairly well acquainted with electromagnetism, and also
with the capabilities of the telephone, and yet receive the idea of
signalling by induction long distances with utter incredulity, or at
least in the same way as one might accept the truth of the statement,
that when one stamps one's foot the universe is shaken to its founda-
tions. Quite true, but insensible a few yards away. The incredulity
will probably be based upon the notion of rapid decrease with distance
of inductive effects. This, however, leaves out of consideration an im-
portant element, namely the size of the circuits.
The coefficients of electromagnetic induction of linear circuits are
proportional to their linear dimensions. If, then, we increase the size
of two circuits n times, and also their distance apart n times, the mutual
inductance M is increased n times. Let R^ and R.2 be the resistances
of primary and secondary. The induced current (integral) in the
secondary due to starting or stopping a current C\ in the primary is
MCJUft or Me^R^Ry if el be the impressed force in the primary. Now
increasing the linear dimensions, and the distance, in the ratio n (with
the same kind of wire) increases M, Rly and R.2 all n times. So only
el remains to be increased n times to get the same secondary-current
impulse. We can therefore ensure success in long-distance experiments
on the basis of the success of short-distance experiments, with elements
of uncertainty arising from new conditions coming into operation at the
long distances.
But practically the result must be far more favourable to the long
than to the short distances than the above asserts. For no one, when
multiplying the distance and size of circuits, say ten times, would think
of putting ten telephones in circuit to keep rigidly to the rule. Thus
it may be that only a slight increase of e1 is required, on account of M
being multiplied in a far greater ratio than the resistances, or the self-
inductances. Thus, it is not uncommon for the R and L of a telephone
to be 100 ohms and 12 million centim. These form the principal parts
of the R and L of a circuit of moderate size, and of course do not in-
crease when we enlarge the circuit. It is therefore certain that we can
signal long distances on the above basis, with a margin in favour of the
long distances, which will be large or small according as the circuits are
small or large.
Again, if el in the primary be periodic, of frequency W/^TT, the ratio of
the amplitude of the current in the secondary to that in the primary
willbe '
Now, without any statement of the magnitude of the current in the
primary, if it be largely in excess of requirements for signalling in the
primary, so that -^ part, say, would be sufficient for the purpose, then
we shall have enough current in the secondary if the above ratio is only
ON THE SELF-INDUCTION OF WIRES. PART IV. 239
y^. But, without going to precise formulae, it may be easily seen that
the above ratio may be made quite a considerable fraction, in com-
parison with TJ^, with closed metallic circuits whose linear dimensions
and distance are increased in the same ratio. But we should expect a
rapid decrease of effect when the mean distance between the circuits
exceeds their diameter, keeping the circuits unchanged. (It should be
understood that squares, circles, etc., are referred to.)
The theory seems so very clear (though it is only the first approxi-
mation to the theory), that it would be matter for wonder and special
inquiry if we found that we could not signal long distances by induction
between closed metallic circuits, starting on the basis of a short-distance
experiment, and following up the theory.
As a matter of fact, my brother found it was possible to speak by
telephone between two metallic circuits of J mile square, J mile between
centres, using two bichros with the microphone.
Now, coming to metallic lines whose circuits are closed through the
earth, the theory is rendered far more difficult on account of there
being a conduction-current from the primary to the secondary due
to the earth's imperfect conductivity. We therefore have, to say
nothing of electrostatic induction, a superposition of effects due to
induction and conduction, the latter being far more difficult to theo-
retically estimate than the former. But the reasoning regarding the
magnetic induction is not very greatly changed, although not so
favourable to long-distance signalling. If the return-currents diffused
themselves uniformly in all directions from the ends of the line, the
same property of n-fold increase of M with %-fold lengthening of the
lines and their distance would still be true. But the diffusion is one-
sided only, and is even then only partial, especially when exceedingly
rapid alternations of current take place. But we have the power of
counterbalancing this by the multiplication of the variations of current
in the primary that we can get by making and breaking the circuit,
with a considerable battery-power if necessary, getting something
enormous compared with the feeble variations of current in the micro-
phonic circuit, or that can work a telephone. Electrostatic induction
also comes in to assist, as it increases the activity of the battery, and
therefore the current in the secondary also.
But, as regards wires connected to earth, this does not profess to be
more than the very roughest reasoning, though in my opinion quite
plain enough to show that we may ascribe the signalling across 40 miles
of country between lines about 50 miles long mainly to induction, as we
should be necessitated to do if we carried the experiment further and
closed the circuits metallically by roundabout courses, for then the
plain arguments relating to induction will become valid. Experiments
of this kind are of the greatest value from the theoretical point of view,
and it is to be hoped that they will be greatly extended.
240 ELECTRICAL PAPERS.
PART V.
St. tenant's Solutions relating to the Torsion of Prisms . applied to the
Problem of Magnetic Induction in Metal Rods, with the Electric
Current longitudinal, and with close-fitting Return-Current.
The mathematical difficulties in the way of the discovery of exact
solutions of problems concerning the propagation of electromagnetic
disturbances into wires of other than circular section — or, even^ if of
circular section, when the return-current is not equidistantly distributed
as regards the wire, or is not so distant that its influence on the dis-
tribution of the wire-current throughout its section may be disregarded
— are very considerable. As soon as we depart from the simple type
of magnetic field which occurs in the case of a straight wire of circular
section, we require at least two geometrical variables in place of the
one, distance from the axis of the wire, which served before ; and we
may have to supplement the magnetic force " of the current," as usually
understood, by a polar force, or a force which is the space-variation of
a single-valued scalar, the magnetic potential, in order to make up the
real magnetic force.
There are, however, some simplified cases which can be fully solved,
viz., when the external magnetic field, that in the dielectric, is abolished,
by enclosing the wire in a sheath of infinite conductivity. It is true
that we must practically separate the wire from the sheath by some
thickness of dielectric, in order to be able to set up current in the
circuit by means of impressed force, so that we cannot entirely abolish
the external magnetic field ; but we may approximate in a great
measure to the state of things we want for purposes of investigation.
The wire, of course, need not be a wire in the ordinary sense, but a
large bar or prism. The electrostatic induction will be ignored,
requiring the wire to be not of great length ; thus making the problem
a magnetic one.
Consider, then, a straight wire or rod or prism of any symmetrical
form of section, so that, when a uniformly distributed current passes
through it, its axis is the axis of the magnetic field, where the intensity
offeree is zero. Let a steady current exist in the wire, longitudinal
of course, and let the return-conductor be a close-fitting infinitely-
conducting sheath. This stops the magnetic field at the boundary of
the wire. The sudden discontinuity of the boundary magnetic-force is
then the measure and representative of the return-current.
The magnetic energy per unit length is JLC2, where C is the current
in the wire and L the inductance per unit length. As regards the
diminution of the L of a circuit in general, by . spreading out the
current, as in a strip, instead of concentrating it in a wire, that is a
matter of elementary reasoning founded on the general structure of L.
If we draw apart currents, keeping the currents constant, thus doing
work against their mutual attraction, we diminish their energy at the
same time by the amount of work done against the attraction. Thus
the quantity ^LC* of a circuit is the amount of work that must be done
ON THE SELF-INDUCTION OF WIRES. PART V. 241
to take a current to pieces, so to speak ; that is, supposing it divided
into infinitely fine filamentary closed currents, to separate them against
their attractions to an infinite distance from one another. We do not
need, therefore, any examination of special formulae to see that the
inductance of a flat strip is far less than that of a round wire of the
same sectional area; their difference being proportional to the differ-
ence of the amounts of the magnetic energy per unit current in the
two cases. The inductance of a circuit can, similarly, be indefinitely
increased by fining the wire ; that of a mere line being infinitely great.
But we can no more have a finite current in an infinitely thin wire
than we can have a finite charge of electricity at a point, in which case
the electrostatic energy would also be infinitely great, for a similar
reason ; although by a useful and almost necessary convention we may
regard fine-wire circuits as linear, whilst their inductances are finite.
Now, as regards our enclosed rod with no external magnetic field, we
can in several cases estimate L exactly, as the work is already done, in
a different field of Physics. The nature of the problem is most simply
stated in terms of vectors. Thus, let h be the vector magnetic force
when the boundary of the section perpendicular to the length is circular,
and H what it becomes with another form of boundary ; then
H = h + F, and F=-Vfi ......................... (la)
That is, the field of magnetic force differs from the simple circular type
by a polar force F, whose potential is ft. This must be so because the
curl of H and of h are identical, requiring the curl of F to be zero. To
find F we have the datum that the magnetic force must be tangential
to the boundary, and therefore have no normal component ; or, if N be
the unit vector-normal drawn outward,
-FN = hN ................................. (2a)
is the boundary-condition. This gives F, when it is remembered that
F must have no convergence within the wire.
In another form, since we have h circular about the axis, and of
intensity 27nT0 at distance r from it, the current-density being F0 ; or
h = 27rroVkr, .... ............................. (3o)
if r is the vector distance from the axis in a plane perpendicular to it,
and k a unit vector parallel to the current ; we have
CI
if s be length measured along the bounding curve, in the direction of
the magnetic force. The boundary-condition (2a) therefore becomes,
in terms of the magnetic potential,
«
which, with V212 = 0, finds the magnetic potential. Here pl is length
measured outward along the normal to the boundary.
H.E.P. — VOL. ii. Q
242 ELECTRICAL PAPERS.
Or, we may use the vector-potential A. It is parallel to the current,
and consists of two parts ; thus,
where the second part on the right side is, except as regards a constant,
what it would be if the boundary were circular, its curl being /xh. To
find A', let its tensor be A' ; then
V2-^' = 0, and Af = fj.irT0r2t ..................... (7a)
the latter being the boundary-condition, expressing that A is zero at
the boundary. Comparing with (5a), we see that (7 a) is the simpler.
The magnetic energy per unit length of rod, say I7, is
the summation extending over the section. But 2 FH = 0, because F is
polar and H is closed ; so that
T= 2 /zh2/87r - 2 /xF2/87r = 2 /xh2/87r + 2 /xhF/87r ............. (9a)
Or, in Cartesian coordinates, let H^ and H2 be the x and y com-
ponents of the magnetic force H, z being parallel to the current ; then
express (la), and (Sa) is represented by
the latter form expressing
It will be observed that the mathematical conditions are identical
with those existing in St. Tenant's torsion problems. Thus, if a and ft
are the y and x tangential strain-components in the plane x, y in a
twisted prism, and y the longitudinal displacement along z, parallel to
the length of the prism, we have
where T is the twist (Thomson and Tait, Part II., § 706, equation (9) ).
The corresponding forces are n times as great, if n is the rigidity (loc. cit.
equation (10) ) ; so that the energy per unit length is
fc2) over section ...................... (13a)
Also, to find y, we have
(loc. cit. equations (12) and (18)). Comparing (14a) with (5a), (1
with (10a), and (13a) with the first of (lift), we see that there is
perfect correspondence, except, of course, as regards the constan
concerned. The lines of tangential stress in the torsion-problem and
the lines of magnetic force in our problem are identical, and the energy
is similarly reckoned. We may therefore make use of all St. Venant'
results.
•
ON THE SELF-INDUCTION OF WIRES. PART V. 243
It will be sufficient here to point out that the ratio of the inductance
of wires of different sections is the same as the ratio of their torsional
rigidities. Thus, as L — \^ in the case of a round wire, that of a wire
of elliptical section, semiaxes a and b, is L = {jab/ (a2 + b2) ; when the
section is a square, it is -4417/x; when it is an equilateral triangle,
•3627/x, etc. [Remember the limitation of close-fitting return, above
mentioned.] That of a rectangle will be given later in the course of
the following subsidence-solution.
Subsidence of Initially Uniform Current in a Rod of Rectangular Section,
with close-fitting Return-Current.
Consider the subsidence from the initial state of steady flow to zero,
when the impressed force that supported the current is removed, in a
prism of rectangular section. Let 2a and 26 be its sides, parallel to x
and y respectively, the origin being taken at the centre. Let H-^ and
H2 be the x and y components of the magnetic force at the time /. Let
E be the intensity of the magnetic-force vector E, which is parallel to
z; then the two equations of induction ( (6), (7), Part L), or
curl H = 47rF, - curl E = /^H,
are reduced to
(15a)
_
dx dy
if F is the current-density, lc the conductivity, //. the inductivity. (I
speak of the intensity of a "force" and of the "density" of a flux,
believing a distinction desirable.) The equation of F is therefore
of which an elementary solution is
F = cosm« cosny €**, ........................ (I8a)
if 4:7r^Jcp= -(m2 + rc2) ......................... (190)
At the boundary we have, during the subsidence, E = 0, or F = 0;
therefore
cos mx cos ny = Q at the boundary,
or cos ma = 0, cosnb = Q, ........... ......... (20a)
or ma = \TT, f TT, |TT, etc. ; nb = ditto. The general solution is therefore
the double summation over m and n,
F = 22 A cos mx cos ny tpt,
if we find A to make the right member represent the initial state.
This has to be F = F0, a constant. Now
1 = 2 (2 /ma) sin ma cos mx, from x= -a to + #,
1 = 2(2/7i&) siunb cosny, from y= -b to +6.
244 ELECTRICAL PAPERS
Hence the required solution is
.
ab ~ m *-J n
or T = iro V V gjn^8in^ cos mx cos ny 4*. . ..(21a)
ab °<^^ mn
From this derive the magnetic force by (15a). Thus
m
— - sin Wft sin mx cos *y
n y
The total current in the prism, say C, is given by
4*7= 2* ff/^rt - 2
.^ .
by line-integration round the boundary. Or
4
if CQ = 4^&ro, the initial current in the prism.
Since the current is longitudinal, and there is no potential-difference,
the vector-potential is given by E = - A ; or, A being the tensor of A,
A is got by dividing the general term in the F-solution (21a) by -pk;
giving
A 167ru^-v>:-\sinmasm nb nf
A = — J~y V — 7-^— r-cosTwacoswye^ .......... (24a)
^^ 2
Since the magnetic energy is to be got by summing up the product
F over the section, we find, by integrating the square of F, that the
amount per unit length is
2 **•
'
By the square-of-the-force method the same result is reached, of
course. We may also verify that Q + f=0 during the subsidence, Q
being the dissipativity per unit length of prism.
The steady inductance per unit length is the L in T=^LC^ which
(25a) becomes when t = 0 ; this gives
(26a)
-y
-(ma)2 1
The lines of magnetic current are also the lines of equal electric
current-density. That is, a line drawn in the plane x, y through the
points where F has the same value is a line of magnetic current. For,
if s be any line in the plane x, y,
— = component of /xH perpendicular to s,
ON THE SELF-INDUCTION OF WIRES. PART V. 245
so that H is parallel to 8, when dE/ds = 0. The transfer of energy is,
as usual, perpendicular to the lines of magnetic force and electric force.
The above expression (26a) for L may be summed up either with
respect to ma or to nb, but not to both, by any way I know. Thus,
writing it
r(nb)2 + -(ma)2
we may effect the second summation, with respect to nb, regarding ma
as constant in every term. Use the identity
l-x_ €»P-*» - 6-**1-*' _ 2^ cos(tmg/2Q
""
where i has the values 1, 3, 5, etc. Take x = Q, iirl'2l = nb, h = (b/a)(ma),
1 = 1, and apply to (27a), giving
...(28a)
where the quantity in the {} is the value of the second 2 in (27a).
The first part of (28a) is again easily summed up, and the result is
in which summation, we may repeat, ma has the values JTT, |TT, |TT, etc.
The quantities a and b may be exchanged ; that is, a/b changed to b/a,
without altering the value of L. This follows by effecting the ma
summation in (2Qa) instead of the nb, as was done.
When the rod is made a flat sheet, or a/b is very small, we have
L = ^7Tfj,(a/b).
Compare (29ft) with Thomson and Tait's equation (46) § 707, Part
II. Turn the nab2 outside the [ ] to nabB, and multiply the 2 by 2.
These corrections have been pointed out by Ayrton and Perry. When
made, the result is in agreement with the above (29a), allowing, of
course, for changed multiplier. (I also observe that the - T in their
equation (44) should be +T, and the +T in (45), (the second T) should
be -T.) Such little errors will find their way into mathematical
treatises ; there is nothing astonishing in that ; but a certain collateral
circumstance renders the errors in their equation (46) worthy of being
long remembered. For the distinguished authors pointedly called
attention to the astonishing theorems in pure mathematics to be got by
the exchange of a and b, such as rarely fall to the lot of pure mathe-
maticians. They were miraculous.
Effect of a Periodic Impressed Force acting at one end of a Telegraph Circuit
with any Terminal Conditions. The General Solution.
I now pass to a different problem, viz., the solution in the case of a
periodic impressed force situated at one end of a homogeneous line,
246 ELECTRICAL PAPERS.
when subjected to any terminal conditions of the kind arising from the
attachment of apparatus. The conditions that obtain in practice are
very various, but valuable information may be arrived at from the
study of the comparatively simple problem of a periodic impressed
force, of which the full solution may always be found. In Part II. I
gave the fully developed solution when the line has the three electrical
constants E, L, and S (resistance, inductance, and electric capacity), of
which the first two may be functions of the frequency, but without any
allowance for the effect of terminal apparatus. If we take L = 0 we
get the submarine-cable formula of Sir W. Thomson's theorj7 ; but,
although the effect of L on the amplitude of the current at the distant
end becomes insignificant when the line is an Atlantic cable, its omis-
sion would in general give quite misleading results.
There are some & priori reasons against formulating the effect of the
terminal apparatus. They complicate the formulas considerably in the
first place ; next, they are various in arrangement, so that it might
seem impracticable to formulate generally ; and, again, in the case of a
very long submarine cable, we may divide the expression of the current-
amplitude into factors, one for the line and two more for the terminal
apparatus, of which the first, for the line, is always the same, whilst
the apparatus-factors vary, and are less important than the line-factor.
But in other cases the terminal apparatus may be of far greater import-
ance than the line, in their influence on the current-amplitude, whilst
the resolution into independent factors is no longer possible.
The only serious attempt to formulate the effect of the terminal
apparatus with which I am acquainted is that of the late Mr. C. Hockin
(Journal S. T. E. and E., vol. v. p. 432). His apparatus arrangement
resembled that usually occurring then in connection with long sub-
marine cables, including, of course, many derived simpler arrange-
ments ; and from his results much interesting information is obtainable.
But the results are only applicable to long submarine cables, on account
of the omission of the influence of the self-induction of the line. The
work must, therefore, be done again in a more general manner. It is,
besides, independently of this, not easy to adapt his formulae, in so far
as they show the influence of terminal apparatus, to cases that cannot
be derived from his. For instance, the effect of magnetic induction in
the terminal arrangements was omitted. I have therefore thought it
worth while to take a far more general case as regards the line, and at
the same time have endeavoured to put it in such a form that it can be
readily reduced to simpler cases, whilst at the same time the results
apply to any terminal arrangements we choose to use.
The general statement of the problem is this. A homogeneous line,
of length I, whose steady resistance is R, inductance L, electric capacity
S, and conductance of insulator K, all per unit length of line, is acted
upon by an impressed force FQ sin nt at one end, or in the wire attached
to it ; whilst any terminal arrangements exist. Find the effect pro-
duced; in particular, the amplitude of the current at the end remote
from the impressed force. If the line consists of two parallel wires, R
must be the sum of their resistances per unit length.
ON THE SELF-INDUCTION OF WIRES. PART V. 247
Let C be the current in the line and V the potential-difference at
distance z from the end where the impressed force is situated. Then
are our fundamental line-equations. Here R" = B + L(d/dt) to a first
approximation, and =R' + L'(d/dt) in the periodic case, where Rf and
U are what R and L become at the given frequency. Let the terminal
conditions be
V=Z£ at z = l end,\ ,„„
-F0sin^+F=^0<7 at * = 0 end,/
so that P"= ^0(7 would be the z = 0 terminal condition if there were no
impressed force.
The solution is a special case of the second of (1626), Part IV., which
we may quote. In it take
S" = K+Sp, ll'' = R' + I/pt ................... (36)
meaning d/dt so far. Also put z2 = 0, <?2 = F0 sin nt, and
-m* = F* = (K+Sp)(B' + I/p), ................... (46)
ind put the equation referred to in the exponential form. Thus,
„_ - T
"" " Z0) - €-"(F/ff' - ZJ (F/S" + Z0) ^ SI
This is the differential equation of C in the line. Now in F^ S", Z0,
and Zlt let d2/dt'2= - n*. It is then reducible to
d (A'Pf + B'Q>n*) + (A'Qf - B'
giving the amplitude and phase-difference anywhere ; and the ampli-
ide is
(76)
Here Pr and Qf are functions of z, whilst A' and Bf are constants.
Put
=
wh0r :l-m
The values of P and Q are
P =
,
, ..... .................. ; ........... .................. M"
ssing the following properties, to be used later,
................ (106)
I
248 ELECTRICAL PAPERS.
The expressions of Mb R(, L'0, L{ can only be stated when the terminal
conditions are fully given. Their structure will be considered later.
P and Q depend only upon the line.
Let
A=Rf- Sn\R&{ + I%Ll) + K(RW - UJW\ ]
B = Un + Sn(R',R{ - L'QL(n*) + Kn(RfJL{ -P R(Lf,\ I
The effect of making the substitutions (86) in (56) is to express C in
terms of the P, Q of (96) and the A, B, a, b of (116); thus :—
»'{-(... + ........ - ...... ) .............. +(«.- ....... - ....... ) .............. }€-«'->]
........... -(5-6) ......... \... + (A + a) .......... + (A-a) ............
The dots indicate repetition of what is immediately above them. Here
we see the expressions for the four quantities A', Bf, Pf, Qf of (66),
which we require. (126) therefore fully serves to find the phase-differ-
ence, if required. I shall only develope the amplitude-expression (76).
It becomes, by (126),
+ 2 cos 2Q(l-
.......................... (136)
in terms of A, B, a, b of (116).
Derivation of the General Formula for the Amplitude of Current
at the End remote from the Impressed Force.
This referring to any point between 2 = 0 and I, a very important
simplification occurs when we take z = l. It reduces the numerator to
It only remains to simplify the denominator as far as
ON THE SELF-INDUCTION OF WIRES. PART V. 249
possible, to show as explicitly as we can the effect of the terminal
apparatus, which is at present buried away in the functions of A, J5,
a, 6 occurring in (136).
First of all, we may show that the product of the coefficients of €2W
and €~'2PI equals one-fourth the square of the amplitude of the circular
part in the denominator. This is an identity, independent of what
A, B, a, b are. (136) therefore takes the form
£0 = 2 F0(P2 + g2)* -f \_G<?Pl + Ht-~pl - 2(GH)l cos 2(Ql + 0)J. (146)
The following are the expansions of the quantities occurring in the
denominator of (136) : —
Let
P = Rf* + LV, /02 = ^2 + Z£V, l{ = R? + Lfn* (156)
Then
A2 + & = P + (K* + &tf)I*I? + 2(Rf0R{ - Lf0L{n2)(KRf + L'Stf)
+ 2(R{L'Q + R'QL{)n\KL' - R'S),
a2 + 62 = (P2 + Q2) { (R'Q + Rff + (L'Q + Z()V } ,
Aa + 3b = (R>0 + R()(R'P + L'nQ) + (U, + L()n(UnP - R'Q) \...( 1 66)
+ (R'0I? + R(I$)(KP + SnQ) + (LJ/« + L(I%)n(KQ - SnP),
Ab-aB= (R'0 + R()(RfQ - LfnP) + (ZJ + L{)n(R'P + L'nQ}
+ (R'0I? + R{1%)(KQ - SnP) - (L'QI? + L(I*)n(KP + SnQ). >
These may be used direct in the denominator of (146), which is the
same as that of (136). But G and H may be each resolved into the
product of two factors, each containing the apparatus-constants of one
end only. Noting therefore that the B in (146) is given by
whose numerator and denominator are given in (166) [the numerator
being (GH)* sin 20, and the denominator (GH)* cos 201 it will clearly be
of advantage to develop these factors. First observe that the expansion
of H is to be got from that of G, using (166), by merely turning P to
- P and Q to - Q. We have therefore merely to split up one of them,
say G. If we put R{ = 0, L{ = 0 in G it becomes
/2 + (P2 + Q-2)/02 + 2P(RIR' + LiL'n*) + 2 Q(L'nRf> - R'nLQ. ( 1 86)
If, on the other hand, we put .#£ = 0, Z£ = 0 in G, it becomes the same
function of R{, L{ as (186) is of jR£, L'Q. It is then suggested that G is
really the product of (186) into the similar function of R{, L(; when
the result is divided by I2. This may be verified by carrying out the
operation described. But I should mention that it is not immediately
evident, and requires some laborious transformations to establish it,
making use of the three equations (106). When done, the final result
is that (146) becomes
(196)
250 ELECTRICAL PAPERS.
wherein 6?0 and H0 contain only constants belonging to the apparatus
at z = Q, and 6^ and Hl those belonging to z = l, besides the line-
constants. Only one of the four need be written ; thus
(206)
From this get H0 by changing the signs of P and Q. Then, to obtain
G1 and Hlt the corresponding functions for the z = I end, change R'Q to
E{ and LfQ to L{. These functions have the value unity when the line
is short-circuited at the ends, (Z0 = 0, Zl = 0). They may therefore be
referred to as the terminal functions. Their form is invariable. We
only require to find the Rf and L', or the effective resistance and
inductance of the terminal arrangements, and insert in (206) and its
companions.
The Effective Resistance and Inductance of the Terminal Arrangements.
Thus, let the two conductors at the z = I end be joined through a
coil. Then R{ is its resistance, L( its inductance, the steady values,
and the accents may be dropped, except under very unusual circum-
stances, and 7j is its impedance at the given frequency, when on short-
circuit. But if the coil contain a core, especially if it be of iron,
neither Rl nor .Lj can have the steady values, on account of the
induction of currents in the core. Their approximate values at a given
frequency may be experimentally determined by means of the Wheat-
stone Bridge. Of course R^ and L^ are really somewhat changed in a
similar manner by allowing any induction between the coil and external
conductors, the brass parts of a galvanometer, for instance ; L going
down and R going up, though this does not materially affect I.
If, instead of a coil, it be a condenser of capacity S1 that is inserted
at z = I ; then, since
'
we have Zl =
Therefore take R{ = 0, and L{ = - (fy*2)"1-
The condenser behaves, so far as the current is concerned, as a coil of
no resistance and negative inductance, the latter decreasing as the
frequency is raised, and as the capacity is increased; tending to become
equivalent to a short-circuit, though this would require a great fre-
quency in general, as the gwsi-negative inductance is large. (Thus,
^=100, £=10-15 = one microfarad, make L(= - 1011. To make the
inductance of a coil be 1011 it must contain a very large number of
turns of fine wire.) Thus, whilst the condenser stops slowly periodic
or steady currents, it tends to readily pass rapidly periodic currents, a
property which is very useful in telephony, as in V"an Rysselberghe's
system.
On the other hand, the coil passes the slowly periodic, and tends to
stop the rapidly periodic, a property which is also very useful in tele-
phony. A very extensive application of this principle occurs in the
system of telephonic intercommunication invented and carried out by
ON THE SELF-INDUCTION OF WIRES. PART V. 251
Mr. A. W. Heaviside, known as the Bridge System, from the telephones
at the various offices being connected up as bridges across from one to
the other of the two conductors which form the line. Whilst all
stations are in direct communication with one another, one important
desideratum, there is no overhearing, which is another. For all
stations except the two which are in correspondence at a certain time
have electromagnets of high inductance inserted in their bridges, which
electromagnets will not pass the rapid telephonic currents in appreci-
able strength, so that it is nearly as if the non-working bridges were
non-existent ; and, in consequence, a far greater length of buried wire
can be worked through than on the Sequence system, wherein the
various stations have their apparatus in sequence with the line ; whilst
at the same time (in the Bridge system) a balance is preserved against
inductive interferences. When the two stations have finished corre-
spondence, they insert their own electromagnets in their bridges. As
these electromagnets are used as call-instruments, responding to slowly
periodic currents, we have the direct intercommunication. Of course
there are various other details, but the above sufficiently describes the
principle.
As regards the property of the self-induction of a coil in stopping or
greatly decreasing the amplitude of rapidly periodic currents, or acting
as an insulation at the first moment of starting a current, its influence
was entirely overlooked by most writers on telegraphic technics before
1878, when I wrote on the subject [vol. I., p. 95J. A knowledge of the
important quantity (A>2 4- L2n2)$, which is now the common property of
all electrical schoolboys (especially by reason of the great impetus
given to the spread of a scientific knowledge of electromagnetism by
the commercial importance of the dynamo), was, before then, confined
to a few theorists.
If the coil R, L, and the condenser Sl be in parallel, we have
TV-*- - f-ia^^f.
Tri-r. °F THE "
U3STIVEH
or _= • i~ — -i^- — • ' tJ. - X /^ OF
C (\-LSln2Y + (RSlnf '
which show the expressions of R{ and L{, the second being the co-
efficient of p, the first the rest.
Similarly in other simple cases. And, in general, from the detailed
nature of the combination inserted at the end of the line, write out the
connections between the current and potential-difference in each branch,
id eliminate the intermediates so as to arrive at F=Z1Ct the differ-
ential equation of the combination, wherein Zl is a function of p or djdt.
~^2= -n2, and it takes the form Zl = R{-\-L(p, wherein R{ and L{
functions of the electrical constants and of n\ and are the required
effective R[ and L{ of the combination, to be used in (206), or rather, in
its z = l equivalent 6rr
As regards the z = 0 end, it is to be remarked that, owing to the
current being reckoned positive the same way at both ends, when we
252 ELECTRICAL PAPERS.
write V— Z0C as the terminal equation, it is - ZQ that corresponds to
Zr Thus - ZQ = RQ + L'0p, where, in the simplest case, E'Q and L[ are
the resistance and inductance of a coil.
Special Details concerning the above. Quickening Effect of Leakage. The
Long-Cable Solution, with Magnetic Induction ignored.
So far sufficiently describing how to develope the effective resistance
and inductance expressions to be used in the terminal functions G and
H, we may now notice some other peculiarities in connection with the
solution (19&). First short-circuit the line at both ends, making the
terminal functions unity, and 0 = 0. The solution then differs from
that given in Part II. , equation (82), in the presence of the quantity K,
the former Sn now becoming (K'2 + S'2ri2)%, whilst P and Q differ from
the former P and Q of (78), Part II., by reason of K, whose evan-
escence makes them identical. If we compare the old with the new
P and ft we find that
U becomes U-KR'l&tf,\
E' becomes R' + KL'/S, J"
in passing from the old to the new. Then the function
E'* + L'W , ao (R'
-W~~
or is unaltered by the leakage. It follows that the equation (85),
Part II., is still true, with leakage, if we make the changes (216) just
mentioned in it, or put
instead of using the 1/ and h expressions of Part II.
At the particular frequency given by n2 = KE'/L'S, we shall have
P = Q = (%)*(R'* + U*n*)l(K* + S*»2)* = Q)*(R'S + KU}n, ... (23b)
making
...(246)
If we should regard the leakage as merely affecting the amplitude of
the current at the distant end of a line, we should be overlooking an
important thing, viz., its remarkable effect in accelerating changes in
the current, and thereby lessening the distortion that a group of signals
suffers in its transmission along the line. If there is only a sufficient
strength of current received for signalling purposes, the signals can be
far more distinct and rapid than with perfect insulation, as I have
pointed out and illustrated in previous papers. Thus the theoretical
desideratum for an Atlantic cable is not high, but low insulation — the
lowest possible consistent with having enough current to work with.
Any practical difficulties in the way form a separate question.
Eegarding this quickening effect, or partial abolition of electrostatic
retardation, I have [vol. I., pp. 531 and 536] pushed it to its extreme
ON THE SELF-INDUCTION OF WIRES. PART V. 253
in the electromagnetic scheme of Maxwell. In a medium whose con-
ductivity varies in any manner from point to point, possessed of
dielectric capacity which varies in the same manner (so that their ratio,
or the electrostatic time-constant, is everywhere the same), but destitute
of magnetic inertia (^ = 0, no magnetic energy), I have shown that
electrostatic retardation is entirely done away with, except as regards
imaginable preexisting electrification, which subsides everywhere accord-
ing to the common time-constant, without true electric current, by the
discharge of every elementary condenser through its own resistance.
This being over, if any impressed force act, varying in any manner in
distribution and with the time, the corresponding current will every-
where have the steady distribution appropriate to the impressed force
at any moment, in spite of the electric displacement and energy ; and,
on removal of the impressed force, there will be instantaneous dis-
appearance of the current and the displacement. This seems impossible ;
but the same theory applies to combinations of shunted condensers,
arranged in a suitable manner, as described in the paper referred to.
Of course this extreme state of things is quite imaginary, as we
cannot really overlook the magnetic induction in such a case. If we
regard it as the limiting form of a real problem, in which inertia occurs,
to be afterwards made zero, we find that the instantaneous subsidence
of the electrostatic problem becomes [with reflecting barriers] an
oscillatory subsidence of infinite frequency but finite time-constant,
about the mean value zero ; which is mathematically equivalent to
instantaneous non-oscillatory subsidence.
The following will serve to show the relative importance of E, S, K,
and L in determining the amplitude of periodic currents at the distant
end of a long submarine cable, of fairly high insulation-resistance :—
4 ohms per kilom. makes 72 = 404,
imicrof. „ „ S
100 megohms,, „ #=10-22.
Here, it should be remembered, K is the conductance of the insulator
per centim. The least possible value of L would be such that LS = v~2,
where v = 3010; this would make L = ± only. But it is really much
greater, requiring to be multiplied by the dielectric constant of the
insulator in the first place, making L=2say. It is still further
increased by the wire, and considerably by the sheath and by the
extension of the magnetic field beyond the sheath, to an extent which
is very difficult to estimate, especially as it is a variable quantity ; but
it would seem never to become a very large number, as of course an
iron wire for the conductor is out of the question. But leaving it
unstated, we have, by (96), taking Rf = B, L' = L,
Yl*
VJ
254 ELECTRICAL PAPERS.
Now 71/27T is the frequency, necessarily very low on an Atlantic cable.
We see then that the first L2n2 is quite negligible in its effect upon P,
even when we allow L to increase greatly from the above L = 2. The
high insulation also makes the (BK-LSn2) part negligible, making
approximately
P= £ = (1^.1 0-8,
P being a little greater than Q, at least when L is small. Now this is
equivalent to taking L = Q, K=Q, when
P=e = (pS»)i, (256)
reducing (196) to
C0 = 2F0(*/JB)J * {00<V + H0H1fal - 2(G0(?1fl0tf1)i cos 2«}1, (266)
which is, except as regards the terminal functions I introduce, quite an
old formula. It is what we get by regarding the line as having only
resistance and electrostatic capacity. But, still regarding the line as an
Atlantic or similar cable, worked nearly up to its limit of speed, PI is
large, say 10 at most, so that we may take this approximation to (266),
C0 = 2F0(Sn/E)^-plxG^^G^ (27ft)
where the first of the three factors is the line-factor, the second that
due to the apparatus at the 2 = 0 end, and the third to that at the
z = l end of the line; thus, by (206) and (256), with L' = Q and R' = R
in the former,
R? + L»n*)} , )
(286)
{ - L(n)
This reduction to (276) is of course not possible when the line is very
far from being worked up to its possible limit ; in fact, all three terms
in the { } of (266), or, more generally, of (196), require to be used in
general. For this reason a full examination of the effect of terminal
apparatus is very laborious. Most interesting results may be got out
of (196), especially as regards the relative importance of the line and
terminal apparatus at different speeds, complete reversals taking place
as the speed is varied whilst the line and apparatus are kept the same.
The general effect is that, as the speed is raised, the influence of the
apparatus increases much faster than that of the line. For instance, to
work a land-line of, say, 400 miles up to its limit, we must reduce the
inertia of the instruments greatly to make it even possible. In fact,
.electromagnets seem unsuitable for the purpose, unless quite small, and
chemical recording has probably a great future before it. But it
would be too lengthy a digression to go into the necessarily trouble-
some details.
Same Properties of the Terminal Functions.
The following relates to some properties of the terminal function G,
which have application when (276) is valid. Consider the Gt of (286).
Let it be simply a coil that is in question. Then Rl is its resistance
ON THE SELF-INDUCTION OF WIRES. PART V. 255
and Zj its inductance, dropping the accent. Keep the resistance con-
stant, whilst varying the inductance so as to make Gl a minimum,
and therefore the current-amplitude a maximum. The required value
of L is
.............................. (296)
depending only upon the line-constants and the frequency, independently
of the resistance of the coil. Taking PI =10, this makes Ll = Rl/2Qn,
where El is the resistance of the line. The relation (296) makes
If the coil had no inductance, but the same resistance, Gl would have
the same expression, but with 1 instead of J in (306). The effect of
the inductance has therefore increased the amplitude of the current,
and it is conceivable that Gl could be made less than unity, though it
may not be practicable.
Now the G^R^ of (306) is a minimum, with Rl variable, when
R = 2PJRV and this will make Gl = 2, or make the terminal factor be
6rfi=7. Now if we vary the number of turns of wire in the coil,
keeping it of the same size and shape, the magnetic force will vary as
(Ri/G)*, so it at first sight appears that R1 = R/2P and L^ = Rj'2Pn make
the magnetic force a maximum for a fixed size and shape of coil. There
is, however, a fallacy here, because varying the size of the wire as
stated varies L^ nearly in the same ratio as Rv whilst (306) assumes L^
to be a constant, given by (296). It is perhaps conceivable to keep L^
constant during the variation of Elt by means of iron, and so get
(Ri/G)t to be a maximum; but then, on account of the iron, this
quantity will not represent the magnetic force.
If, on the other hand, we vary Rt in the original Gl of (286), keep-
ing LJ&L constant (size and shape of coil fixed, size of wire variable),
G-ifR-^ is made a minimum by
........................... (316)
giving a definite resistance to the coil, of stated size and shape, to make
the magnetic force a maximum. Now G1 becomes
ff1 = 2 + ?'(JR1-V), ........................ (326)
where Ll/R1 has been constant. If this constant have the value n~l,
we have G^ = 2 again, and Mv Zx have the same values as before. There
is thus some magic about Gl = 2.
Again, if the terminal arrangement consist of a coil Rv Lv and a
condenser of capacity *SX and conductance Kv joined in sequence, we
shall have
(33i>
say
256 ELECTRICAL PAPERS.
if R{, L{ are the effective resistance and inductance, to be used in
making
,7-2 »2, o- , ,.
++ .......... (3
Variation of L^ alone makes Gl a minimum when
T &-,n . R
and if we take K^ = 0 (condenser non-leaky, and not shunted), we have
the value of G1 given by (30&) again, independent of the condenser.
Similarly we can come round to the same Gl = 2 again. These rela-
tions are singular enough, but it is difficult to give them more than a
very limited practical application to the question of making the mag-
netic force of the coil a maximum, although the (305) relation is not
subject to any indefiniteness.
PART VI.
General Remarks on the Christie considered as an Induction Balance.
Full-Sized and Reduced Copies.
The most important as well as most frequent application of Mr. S. H.
Christie's differential arrangement, known at various times under the
names of Wheatstone's parallelogram, lozenge, balance, bridge, quad-
rangle, and quadrilateral, is to balance the resistances of four conductors,
when supporting steady currents due to an impressed force in a fifth,
and this is done by observing the absence of steady current in a sixth.
But its use in other ways and for other purposes has not been neglected.
Thus, Maxwell described three ways of using the Christie to obtain
exact balances with transient currents (these will be mentioned later in
connection with other methods) ; Sir W. Thomson has used it for
balancing the capacities of condensers* ; and it has been used for other
purposes. But the most extensive additional use has been probably in
connection with duplex telegraphy ; and here, along with the Christie,
we may include the analogous differential-coil system of balancing, which
is in many respects a simplified form of the Christie.
On the revival of duplex telegraphy some fifteen years ago, it was
soon recognised that " the line " required to be balanced by a similar
line, or artificial line, not merely as regards its resistance, but also as
regards its electrostatic capacity — approximately by a single condenser;
better by a series of smaller condensers separated by resistances ; and,
best of all, by a more continuous distribution of electrostatic capacity
along the artificial line. The effect of the unbalanced self-induction
was also observed. This general principle also became clearly recog-
nised, at least by some, — that no matter how complex a line may be,
* Journal S. T. E. and E., vol. I., p. 394.
ON THE SELF-INDUCTION OF WIRES. PART VI. 257
considered as an electrostatic and magnetic arrangement, it could be per-
fectly balanced by means of a precisely similar independent arrange-
ment ; that, in fact, the complex condition of a perfect balance is
identity of the two lines throughout. The great comprehensiveness of
this principle, together with its extreme simplicity, furnish a strong
reason why it does not require formal demonstration. It is sufficient
to merely state the nature of the case to see, from the absence of all
reason to the contrary, that the principle is correct.
Thus, if ABjC and AB2C [see figure on p. 263] be two identically
similar independent lines (which of course includes similarity of
environment in the electrical sense in similar parts), joined in parallel,
having the A ends connected, and also the C ends, and we join A to C
by an external independent conductor in which is an impressed force e,
the two lines must, from their similarity, be equally influenced by it, so
that similar parts, as Bx in one line and B2 in the other, must be in the
same state at the same moment. In particular, their potentials must
always be equal, so that, if the points BT and B2 be joined by another
conductor, there will be no current in it at any moment, so far as the
above-mentioned impressed force is concerned, however it vary. The
same applies when it is not mere variation of the impressed force e, but
of the resistance of the branch in which it is placed. And, more gener-
ally, Bj and B2 will be always at the same potential as regards disturb-
ances originating in the independent electrical arrangement joining
A to C externally, however complex it may be.
There is, however, this point to be attended to, that might be over-
looked at first. Connecting the bridge-conductor from Bx to B2 must
not produce current in it from other causes than difference of potential ;
for instance, there should be, at least in general, no induction between
the bridge-wire and the lines, or some special relation will be required
to keep a balance. This case might perhaps be virtually included under
similarity of environment.
If we had sufficiently sensitive methods of observation, the statement
that one line must be an exact copy of the other would sometimes have
to be taken literally. But the word copy may practically be often used
to mean copy only as regards certain properties, either owing to the
balance being independent of other properties, or owing to our inability
to recognise the effects of differences in other properties. Thus, in the
steady resistance-balance we only require ABX and AB2 to have equal
total resistances, and likewise BjC and B2C ; resistances in sequence
being additive. But evidently, if the balance is to be kept whilst Bx
and B2 are shifted together from end to end of the two lines, the resist-
ance must be similarly distributed along them.
If, now, condensers be attached to the lines, imitating a submarine
cable, though of discontinuous capacity, we require that the resistance
of corresponding sections shall be equal, as well as the capacities of
corresponding condensers, in order that we shall have balance in the
variable period as well as in the steady state ; and the two properties,
resistance and capacity, are the elements involved in making one line a
copy of the other.
H.E.P. — VOL. n. R
258 ELECTRICAL PAPERS.
In case of magnetic induction again, if ABXC and AB2C each consist
of a number of coils in sequence, they will balance if the" coils are alike,
each for each, in the two lines, and are similarly placed with respect to
one another. But the lines will easily balance under simpler conditions,
inductances being additive, like resistances ; and it is only necessary
that the total self-inductions of ABX and AB9 (including mutual induc-
tion of their parts) be equal, and likewise of BXC and B2C. Again, if a
coil al in the branch ABX have another coil ^ in its neighbourhood (not
in either line, but independent), and a2, in the branch AB2, be a copy of
«!, we can complete the balance by placing a coil 62 (which is a copy of
&j) in the neighbourhood of the coil «2, so that the action between al
and &j is the same as that between «2 and b2. But it is not necessary
for 'bl and 62 to be copies of one another except in the two particulars
of resistance and inductance ; whilst as regards their positions with
respect to a-^ and #2, we only require the mutual inductance of al and 6X
to equal that of a2 and by
On the other hand, if 6X be not a coil of fine wire, but a piece of
metal that is placed near the coil «15 many more specifications are
required to make a copy of it. The piece of metal is not a linear
conductor ; and, although no doubt only a small number (instead of an
infinite number) of degrees of freedom allowed for, would be sufficient
to make a practical balance, yet, as we have not the means of simply
analyzing pieces of metal (like coils) into a few distinct elements, we
must generally make a copy of 6X by means of a similar piece, 52, of the
same metal, and place it with respect to a2 as \ is to av to secure a
good balance. But very near balances may be sometimes obtained by
using quite dissimilar pieces of metal, dissimilarly placed.
So far, copy signifies equality in certain properties. But one line
need be merely a reduced copy of the other. It is only when we
inquire into what makes one line a reduced copy of another, that we
require to examine fully the mathematical conditions of the case in
question. In the state of steady flow the matter is simple enough. If
ABX has n times the resistance of AB2, then must BjC have n times the
resistance of B2C to keep the potentials of Bx and B2 equal. If con-
densers be connected to the lines, as before mentioned, we require,
first, the resistance-balance of the last sentence applied to every section
between a pair of condensers; and next, that the capacity of a condenser
in the line ABXC shall be, not n times (as patented by Mr. Muirhead, I
believe), but l/n of the capacity of the corresponding condenser in the
line AB2C [vol. I., p. 25]. If the lines are representable by resistance,
inductance, electrostatic capacity, and leakage-conductance (E, L, S, K of
Parts IV. and V., per unit length), one line will be a reduced copy of the
other if, when R and L in the first line are n times those in the second,
S and K in the second are n times those in the first, in similar parts.
Conjugacy of Two Conductors in a Connected System. The Characteristic
Function and its Properties.
After these general remarks, and preliminary to a closer consideration
of the Christie, let us briefly consider the general theory of the conjugacy
ON THE SELF-INDUCTION OF WIRES. PART VI. 259
of a pair of conductors in a connected system, when an impressed force
in either can cause no current in the other, either transient or per-
manent. The direct way is to seek the full differential equation of the
current in either, when under the influence of impressed force in the
other alone. Let V=ZG be the differential equation of any one branch,
C being the current in it, V the fall of potential in the direction of (7,
and Z the differential operator concerned, according to the notation of
Parts III., IV., and V. If there be impressed force e in the branch, it
becomes e+ V=ZG. We have 2 F~=0 in any circuit, by the potential-
property ; therefore 2e = 2ZC in any circuit. Also the currents are
connected by conditions of continuity at the junctions. These, together
with the former circuit-equations, lead us to a set of equations :—
Cv C'2, ..., being the currents, and elt e.2, ... the impressed forces in
branches 1, 2, etc. ; F being common to all, and it and the /'s being
differential operators. We arrive at similar equations when the
differential equation of a branch is not merely between the V and C of
that branch, but between those of many branches ; for instance, when
is the form of the differential equation of branch 1.
Now let there be impressed force e in one branch only, and C be the
current in a second, dropping the numbers as no longer necessary. We
then have
FC=fe ................................... (3c)
Conjugacy is therefore secured by fe = 0, making C independent of
e. Therefore fe — 0 is the complex condition of conjugacy. If, for
example,
fe = a0e + a^e + a2e + . . . , ........................ (4c)
where the a' s are constants, functions of the electrical constants con-
cerned, then, to ensure conjugacy, we require
ff0 = 0, «i = 0, ^2 = 0, etc., ............... (5c)
separately ; and if these a's cannot all vanish together we cannot have
conjugacy.
What C may be then depends only upon the initial state of the
system in subsiding, or upon other impressed forces that we have nothing
to do with. As depending upon the initial state, the solution is
C^Ac**; ................................ (6c)
the summation being with respect to the p's which are the roots of
F(j>) = 0, p being put for d/dt in F ; and the A belonging to a certain p
is to be obtained by the conjugate property of the equality of the
mutual electric to the mutual magnetic energy of the normal systems of
any pair of p's.
As depending upon <?, the impressed force in the conductor which is
260 ELECTRICAL PAPERS.
to be conjugate to the one in which the current is (7, let e be zero before
time £ = 0, and constant after. Then, by (3c),
...(7e)
if C0 is the final steady current, and F/ = dF/dp, the summation being
with respect to the p's.*
If there is a resistance-balance, «0 = 0, C'0 = 0, and
Now, subject to (4c), calculate the integral transient current :—
= value of f(p)e/pF(p) when ^> = 0,
if jF0 is the p = 0 value of F. If then 04 = 0 also, we prove that the
integral transient current is zero.
Supposing both aQ = 0, 0^ = 0, then
therefore
andtherefore <ftc0* = Vii^ ................... (lOc)
o Jo
Thus, if a2 = 0 also, we have
r
Jo
Similarly, if a3 = 0 also, then
tfdt?Cdt = 0, ........................... (12c)
o Jo Jo
and so on. The physical interpretation of a0 = 0 and ax = 0 is obvious,
but after that it is less easy.
If F contain inverse powers of p, the steady current may be zero.
But in spite of that, it will be found that to secure perfect conjugacy
for transient currents we must have a true resistance-balance, or that
relation amongst the resistances which would make the steady current
zero, if we were to allow the possibility of a steady current by changing
the value of other electrical quantities concerned. I will give an
example of this later.
I have elsewhere [vol. I., p. 412] pointed out these properties of the
* [In these equations (7c) to (lOc) modify as in the footnote on p. 226, vol. n., if
necessary.]
ON THE SELF-INDUCTION OF WIRES. PART VI. 261
function F, in the case where there is no mutual induction, or V=ZC
is the form of the differential equation of a branch. Let n points be
united by ^n(n-l) conductors, whose conductances are Ku, K13, etc.,
it being the points that are numbered 1, 2, etc. Then the determinant
ii» ^i2» •••) KIU
K •••' -"-2
is zero, and its first minors are numerically equal, if any K with equal
double suffixes be the negative of the sum of the real K's in the same
row or column.* Remove the last row and column, and call the deter-
minant that is left F. It is the F required, and is the characteristic
function of the combination, expressed in terms of the conductances.
If every branch have self-induction, so that R+L(d/dt) takes the place
of A7""1, then F=Q is the differential equation of the combination,
without impressed forces; and ^=0 is always the differential equation
subject to the condition of no mutual induction. In the paper referred
to cores are placed in the coils, giving a special form to K.
When K is conductance merely, the characteristic function contains
within itself expressions for the resistance between every two points in
the combination, which can therefore be written down quite mechani-
cally. For it is the sum of products each containing first powers of the
K's, and therefore may be written
F-K^+ru-KvXa + ra-..., ............... (14e)
where JT23, F23 do not contain K2y and Xlz, Y12 do not contain KIZ. (It
is to be understood that the diagonal Ku, A22, ..., are got rid of.)
Then R'Vi = XIZ/Y^ = resistance between points 1 and 2,^ ,-- ^
„ „ „ 2 and 3, 1"
etc., it being understood that these resistances are not J?12, 7223, etc., but
the resistances complementary to them, the combined resistance of the
rest of the combination ; thus, if el2 be the impressed force in the con-
ductor 1, 2, the current (steady) in it is
The proof by determinants is rather troublesome, using the K's, but, in
terms of their reciprocals, and extending the problem, it becomes simple
enough. Thus, if we turn K to R~l in F, and then clear of fractions,
we may write F= 0 as
#]2Jr/2+ 7/0 = 0, RnXL+Yi^O, etc., ......... (17c)
where Jf/2, F/2, do not contain R^ ; etc. From this we see that the
differential equation of the current G'12 in 1, 2, subject to e12 only, is
As in Maxwell, vol. i., art. 280.
262 ELECTRICAL PAPERS.
if fib = YlJXf*. For this make the dimensions correct, and that is the
only additional thing required, when we observe that it makes the
steady current be
tfl2 = «12/(£l2 + ^i)» (19C)
so that M2l is the resistance complementary to Ii12.
Although it is generally best to work in terms of resistances, yet
there are times when conductances are preferable, and, to say nothing
of conductors in parallel arc, the above is a case in point, as will be
seen by the way the characteristic function is made up out of the K's.
There is also less work in another way. Thus, Jw(n-l) conductors
uniting n points give %(n— !)(?&- 2) degrees of freedom to the currents.
It is the least number of branches in which, when the currents in them
are given, those in all the rest follow. Thus, if 10 conductors unite
5 points, the currents in at least 6 conductors must be given, and no
four of them should meet at one point. The remaining conductors are
7i - 1 in number, or one less than the number of points, and n - 1 is the
degree of the characteristic function in terms of the conductances. Now
put F=0 in terms of the resistances, by multiplying by the product of
all the resistances. It is then made of degree %(n- l)(n- 2) in terms
of the resistances, which is the number of curre"nt-freedoms. If n = 4,
the degree is the same, viz., three, whether in terms of conductances or
resistances ; but if n = 5, it is of the sixth degree in terms of resistances
and only of the fourth in terms of the conductances ; and if n = 6, it is
of the tenth degree in terms of the resistances, but only of the fifth in
terms of the conductances ; and so on, so that F becomes greatly more
complex in terms of resistances than conductances.
When every branch has self-induction, Z — E + Ip, and the degree of
p in F= 0 is the number of freedoms, so that there are n-l fewer roots
than the number of branches. It is the same when there is mutual
induction. The missing roots belong to terms, in the solutions for
subsidence from an arbitrary initial state, which instantaneously vanish,
producing a jump from the initial state to another, which subsides in
time.
On the other hand, if every branch (without self-induction) is shunted
by a condenser of capacity Sv S2, etc., K becomes K+Sp, so that the
degree of p in F=Q is the same as that of K, or J(TI - l)(n-2) fewer
than the number of condensers. [Vol. I., p. 540.]
Theory of the Christie Balance of Self-Induction.
Coming next to the Christie as a self-induction balance, let there be
six conductors, 1, 2, etc., uniting the four points A, B1? B2, C in the
figure. ABXC and AB2C are " the lines " referred to in the beginning.
Let R be the resistance and L the inductance of a branch in which the
current is 0, reckoned positive in the direction of the arrow, and the
fall of potential F in the same direction ; thus Rlt Lv P\, Cl for the
first branch. The six branches may be conjugate in pairs, thus : 1 and
4, or 2 and 3, or 5 and 6. In the following 5 and 6 are selected always,
the battery or other source being in 6, and the telephone or other
ON THE SELF-INDUCTION OF WIRES. PART VI.
263
indicator in 5. Mutual inductances will be denoted by M '• thus,
Mlfl is the electromotive impulse in 2 due to the stoppage of the
current C\ in 1 ; similarly Mlf)C2
is the impulse in 1 due to stop-
ping C.2. ^
Deferring mutual induction for
the present, though not confining
. self-induction to be of the mag- A
netic kind only, but to include
electrostatic if required, the condi-
tion of conjugacy is that the poten-
tials at Bx and B2 be always equal.
Therefore
V^V» and F3=r4; (20c)
so, if V=ZG,
Zf^Zfy and ZJQ^ZJdi ................. (21c)
But, by continuity, 0-^ = 0^ and 0^=0^ at every moment (including
equality of all their differential coefficients) ; so that (21c) becomes
i = Z&\ ..................... (22c)
0=/ ........................... (23c)
consequently
is the complex condition of conjugacy. This function is the / of the
previous investigation.
When the self-induction is of the magnetic kind, Z = R + Lp; so that,
arranging /in powers of p,
0 - (B& - It2R6) + (R.L, + E,L, - JK2L3 - E3L2)p + (L,L, - L2L3)p*. (24c)
Therefore, if x = L/R, the time-constant of a branch, we have three
conditions to satisfy, namely,
................................. (25c)
................................. (26c)
(27 c)
" If the first condition is fulfilled, there will be no final current in
5 when a steady impressed force is put in 6. This is the condition for
a true resistance-balance.
" If, in addition to this, the second condition is also satisfied, the
integral extra-current in 5 on making or breaking 6 is zero, besides
the steady current being zero; (25c) and (26c) together therefore give
an approximate induction-balance with a true resistance-balance.
" If, in addition to (25c) and (26c), the third condition is satisfied,
the extra-current is zero at every moment during the transient state,
and the balance is exact however the impressed force in 6 vary.
" Practically, take
^ = ^2, and 4 = 4; ........................ (28c)
that is, let branches 1 and 2 be of equal resistance and inductance.
264 ELECTRICAL PAPERS.
Then the second and third conditions become identical ; and, to get
perfect balance, we need only make
Rs = Rv and L3^=L4 (29c)
" This is the method I have generally used, reducing the three con-
ditions to two, whilst preserving exactness. It is also the simplest
method. The mutual induction, if any, of 1 and 2, or of 3 and 4, does
not influence the balance when this ratio of ^quality J?1 = E2 is employed
(whether Ll = L2 or not).* So branches 1 and 2 may consist of two
similar wires wound together on the same bobbin, to keep their
temperatures equal." [Vol. n., p. 33].
Of the eight quantities, four Rs and four L's, only five can be stated
arbitrarily, of which not more than three may be E's, and not more
than three may be L's. We may state the matter thus : — There must
first be a resistance-balance. Then, if we give definite values to two
of the .L's, the corresponding time-constants usually become fixed, and
it is required that the other two time-constants shall be equal to them ;
thus
either XI = XB and x2 — x^,
or else x1 = x2 and x3 = %
Thus the remaining two L's become usually fixed. In fact, elimi-
nating R± and Li from (26c) by (25c) and (27c), the second condition
may be written
fo-4X4-4t)-Qi
Suppose Ely E2, E3 given, then R± is fixed by (25c). Two of the
inductances may then be given, fixing the corresponding time-constants.
If these inductances be L1 and Z2, then we must have (unless xl = x2)
Xl ~ ®& ^2 ~ ^4
But if L^ and L3 be given, then we require (unless xl = xs)
These two cases present a remarkable difference in one respect. The
absence of current in 5 allowing us to remove 5 altogether, we see by
(18c) that the differential equation of G'6 is
e =
manipulating the Z's like resistances. The absence of branch 5 thus
reduces the number of free-subsidence systems to two. [In the last
equation we may eliminate one of the Z's by (23c), and then again
eliminate one of the remaining three L's.] Now, if we choose x1 = x2,
we shall make
/ T i 7" \ // 7") i Z? \ / 7" i 7" N
(.L/J + L%) I \II-L + Ji3) = \L2 + Li±}
* The words in the ( ) should be cancelled. The independence of J/12 and J/a4,
which is exact when L1 = L%, L3=L^ and sensibly true when the inequalities are
small, becomes sensibly untrue when the inequalities Ll - L% and L3 - L± are great.
ON THE SELF-INDUCTION OF WIRES. PART VI. 265
or the time-constants of the two branches 1 + 3 and 2 + 4 equal. Then
one of the p's is
= _ A'j + 11, .
and this is only concerned in the free subsidence of current in the
circuit ABjCB^. Consequently the second p, which is
ft8" -7]
is alone concerned in the setting-up of current by the impressed force
in 6 ; and the current divides between ABjC and AB2C in the ratio of
their conductances, in the variable period as well as finally. In fact,
the fraction in the above equation of C6 will be found to contain Zl + Z%
as a factor in its numerator and denominator, thus excluding the pl root,
so far as e is concerned. On the other hand, if we choose xl = x.# we do
not have equality of time-constants of ABXC and AB2C, so that there
are two p's concerned, which are not those given ; and the current C6
does not, in the variable period, divide between ABXC and AB2C in the
ratio of their conductances, but only fin all}''.
In the above statement it was assumed that when Lt and L2 were
chosen, it was not so as to make a^ = x2. When this happens, however,
it is only the ratio of L3 to L4 that becomes fixed, for we have x2 = x±
= anything.
Similarly, when Ll and L3 are so chosen that xl = x3, we shall have
= #4 = any thing, so that only the ratio of L2 to L4 is fixed.
And if Z3, L± be so chosen that x3 = #4, then a^ = x2 = anything, only
ixing the ratio of L^ to L2. But should x3 not =&4, then we require
xl = x3 and x2 = ,i'4, thus fixing L^ and L2.
And if L2, L4 be so chosen that x2 = x4, then x1 = x3 = anything, only
fixing the ratio of L^ to LB. But if so that x2 uot =z4, then x1 = x2 and
x3 = x± fix L: and L3.
There are yet two other pairs that may be initially chosen, and with
miewhat different results. Let it be L^ and L± that are chosen ; if not
as to make xl = x4, there are two ways of fixing L2 and Z3, viz., either
)y xl = x3 and x.2 = «4, or by xl = x2 and x3 = x4 ; but if so that a^ = x± in
the first place, then they must also = x2 = x3.
Similarly the choice of L2 and L3 so as not to make x2 = x3, gives two
ways of fixing L^ and Z-4, by vertical or by horizontal equality of time-
jonstants, as before; whilst x2 = x3 produces equality all round.
The special case of all four sides equal in resistance may be also
loticed. Balance is given in two ways, either by horizontal or by
vertical equality in the L's.
Remarks on the Practical Use of Induction Balances, and the Calibration
of an Inductometer.
Leaving the mathematical treatment for a little while, I proceed to
jive a short general account of my experience of induction-balances. I
lid not originally arrive at the method of equal-ratio just described
266 ELECTRICAL PAPERS.
through the general theory (20c) to (27c), but simply by means of the
general principle of balancing by making one line a copy of the other,
of which I obtained knowledge through duplex telegraphy, and inves-
tigated the conditions (25c) to (27c) more from curiosity than anything
else, though the investigation came in useful at last. In 1881 I wished
to know what practical values to give to the inductances of various
electromagnets used for telegraphic purposes, and to get this knowledge
went to the Christie. Not having coils of known inductance to start
with, I employed Maxwell's condenser-method,* with an automatic
intermitter and telephone. Let 1 , 2, and 3 be inductionless resistances,
and 4 a coil having self-induction. Put the telephone in 5, the battery
and intermitter in 6. We require first the ordinary resistance-balance,
R-^E^RJR^ But the self-induction of the coil will cause current in 5
when 6 is made or broken. This will be completely annulled by
shunting 1 by a condenser of capacity Sv such that
signifying that the time-constant of the coil on short-circuit and that of
the condenser on short-circuit with the resistance 1^ are equal.
The method is, in itself, a good one. But the double adjustment is
sometimes very troublesome, especially if the capacity of the condenser
be not adjustable. For when we vary Ev to approximate to the correct
value of .K1$1, we upset the resistance-balance, and have, therefore, to
make simultaneous variations in some of the other resistances to restore
it. But the method has the remarkable recommendation of giving us
the value of the inductance of a coil at once in electromagnetic units.
In the course of these experiments I observed the upsetting of the
resistance and induction-balance by the presence of metal in the neigh-
bourhood of the coils, which is manifested in an exaggerated form in
electromagnets with solid cores. So, having got the information I
wanted in the first place, I discarded the condenser-method with its
troublesome adjustments, and, to study these effects with greater ease,
went to the equal-ratio method, with the assistance that I had obtained
(by the condenser-method), the values of the inductances of various coils,
to be used as standards.
" To use the Bridge to speedily and accurately measure the inductance
of a coil, we should have a set of proper standard coils, of known
inductance and resistance, together with a coil of variable inductance,
i.e. two coils in sequence, one of which can be turned round, so as to
vary the inductance from a minimum to a maximum. t The scale of
this coil could be calibrated b}^ (12a), first taking care that the resistance-
balance did not require to be upset. This set of coils, in or out of
circuit according to plugs, to form say branch 3, the coil to be measured
to be in branch 4. Ratio of equality. Branches 1 and 2 equal. Of
course inductionless, or practically inductionless, resistances are also
* Maxwell, vol. IL, art. 778.
t Prof. Hughes's oddly named Sonometer will do just as well, if of suitable size
and properly connected up. It is the manner of connection and use that give
individuality to my inductometer.
ON THE SELF-INDUCTION OF WIRES. PART VI. 267
required to get and keep the resistance-balance. The only step to this
I have made (this was some years ago) . . . was to have a number of
little equal coils, arid two or three multiples ; and get exact balance by
allowing induction between two little ones, with no exact measurement
of the fraction of a unit" [vol. II., p. 37].
Although rather out of order, it will be convenient to mention here
that although I have not had a regular inductance-box made (the coils,
if close together, would have to be closed solenoids), yet shortly after
making these remarks, I returned to my earlier experiments by cali-
brating the scale of the coil of variable inductance. As it then becomes
an instrument of precision, it deserves a name ; and as it is for the
measurement of induction it may, I think, be appropriately termed an
Inductometer. Of course, for many purposes no calibration is needed.
I found that the calibration could be effected with ease and rapidity
by the condenser-method more conveniently than by comparisons with
coils. Thus, first ascertain the minimum and the maximum inductance,
and that of the coils separately. Suppose the range is from 20 to 50
units (hundreds, thousands, millions, etc., of centimetres, according to
the quite arbitrary size of the instrument). It will then be sufficient
to find the places on the scale corresponding to 20, 21, 22, etc., 49, 50.
Starting at 21, set the resistance-balance so that Z4 should be 21 units ;
turn the moveable coil till silence is reached, and mark the place 21.
Then set the balance to suit 22, turn again till silence comes, and mark
again; repeat throughout the whole range. Why this can be done
rapidly is because the resistance-balance is at every step altered in the
same manner. We have .thus an instrument of constant resistance and
variable known inductance, ranging from
/x + 1.2 - 2w0 to ^ + 12 + 2mQ,
if ^ and L2 are the separate inductances and ra0 the maximum mutual
inductance. The calibration is thoroughly practical, as no table has to
be referred to to find the value of a certain deflection.
I formerly chose 109 centim. as a practical unit of inductance, and
called it a torn ; the attraction this had for me arose from L toms + R ohms
equalling LfR seconds of time. But it was too big a unit, and millitoms
and microtoms were wanted. Another good name is mac. 106 centim.
might be called a mac. Since Maxwell made the subject of self-induc-
tion his own, and described methods of correctty measuring it, there is
some appropriateness in the name, which, as a mere name, is short and
distinctive.
The two coils of the inductometer need not be equal ; but it is very
convenient to make them so, before calibration, by the equal-ratio
method, which, of course, merely requires us to get a balance, not to
measure the values. Let 1 and 2 be any equal coils ; put one coil of
the inductometer in 3, the other in 4, and balance. It happened by
mere accident that my inductometer had nearly equal coils ; so I made
them quite equal, to secure two advantages. First, there is facility in
calculations; next, the inductometer may be used with its coils in
parallel or in sequence, as desired. When in parallel, the effective
268 ELECTRICAL PAPERS.
resistance and inductance are each one fourth of the sequence-values.
Thus, let V= ZC be the differential equation of the coils in parallel, C
being the total current, and V the common potential-fall ; it is easily
shown that
when the coils are unequal ; ^ and r2 being their resistances, ^ and 12
their inductances, and m their mutual inductance in any position.
Now make 1\ = r2, and ^ = /2 ; this reduces Z to
Z=%r + l(l + m)p; ......................... (31c)
whilst, when in sequence, we have
Z=2r+2(l + m)p, .......................... (32c)
thus proving the property stated. We may therefore make one in-
ductometer serve as two distinct ones, of low or high resistance.
There does not seem to be any other way of making the two coils in
parallel behave as a single coil as regards external electromotive force.
Any number of coils whose time-constants are equal will, when joined
up in parallel, behave as a single coil of the same time-constant ; but
there must be no mutual induction. (This is an example of the pro-
perty* that any linear combination whose parts have the same time-
constant has only that one time-constant.) This seriously impairs the
utility of the property, but the reservation does not apply in the case of
the equal-coil inductometer.
Having got the inductometer calibrated, we may find the inductance
of a given coil, or of a combination of coils in sequence, with or with-
out mutual induction, nearly as rapidly as the resistance. Thus, 1 and
2 being equal, put the coil to be measured in 3, and the inductometer
in 4. We have to make E3 = R± and L3 = Z4, or to get a resistance-
balance, and then turn the inductometer till silence is reached, when
the scale- reading tells us the inductance. This assumes that L3 lies
within the range of the inductometer. If not, we may vary the limits
as we please by putting a coil of known inductance in sequence with
branch 3 or 4 as required, putting at the same time equal resistance in
the other branch.
Or, the inductometer being in 4, and 1, 2 being inductionless resist-
ances, put the coil to be measured in 3. If it has a larger time-constant
than the inductometer's greatest, insert resistance along with it to
bring the time-constants to equality. The conditions of silence are
RJi^RxRs and L3/E3 = LJR4. Here a ratio of equality is not
required. The method is essentially the same as one of Maxwell's f,
and is a good one for certain purposes.
* This property supplies us with induction-balances of a peculiar kind. Let
there be any network of conductors, every branch having the same time-constant.
Set up current in the combination, and then remove the impressed force. During
the subsidence all the junctions will be at the same potential, and any pair of
them may consequently be joined by an external conductor without producing
current in it.
t Maxwell, vol. ii. art. 757.
ON THE SELF-INDUCTION OF WIRES. PART VI. 269
Or, 1 and 2 being any equal coils, put one coil of the inductometer in
6 and the other in 4, the coil to be measured being in 3. Then
L3 = Lt-'2Mi(, (33,)
gives the induction-balance, L± being here the inductance of the coil of
the inductometer in 4, and M46 the mutual inductance of the two coils,
in the position giving silence. This is known in all positions, because
the scale-reading gives the value of /1 + /2 + 2m (or else 2(l + m) if the
coils are equal), and /x + /2 is known. If the range is not suitable, we
may, as before, insert other coils of known inductance.
There are other ways ; but these are the simplest, and the equal-ratio
method is preferable for general purposes. I have spoken of coils
always, where inductances are large and small errors unimportant.
When, however, it is a question of small inductances, or of experiments
of a philosophical nature, needing very careful balancing, then the equal-
ratio method acquires so many advantages as to become the method.
" So long as we keep to coils we can swamp all the irregularities due
to leading wires, etc., or easily neutralize them, and can therefore easily
obtain considerable accuracy. With short wires, however, it is a diffe-
rent matter. The inductance of a circuit is a definite quantity : so is
the mutual inductance of two circuits. Also, when coils are connected
together, each forms so nearly a closed circuit that it can be taken as
such ; so that we can add and subtract inductances, and localise them
definitely as belonging to this or that part of a circuit. But this
simplicity is, to a great extent, lost when we deal with short wires,
unless they are bent round so as to make nearly closed circuits. We
cannot fix the inductance of a straight wire, taken by itself. It has no
meaning, strictly speaking. The return-current has to be considered.
Balances can always be got, but as regards the interpretation, that will
depend upon the configuration of the apparatus.
" Speaking with diffidence, having little experience with short wires,
I should recommend 1 and 2 to be two equal wires, of any convenient
length, twisted together, joined at one end, of course slightly separated
at the other, where they join the telephone-wires, also twisted. The
exact arrangement of 3 and 4 will depend on circumstances. But
always use a long wire rather than a short one (experimental wire). If
this is in branch 4, let branch 3 consist of the standard coils (of appro-
priate size), and adjust them, inserting, if necessary, coils in series with
4 also. Of course I regard the matter from the point of view of getting
easily interpretable results " [vol. n. p. 37].
Some Peculiarities of Self-induction Balances. Inadequacy of S.H.
Variations to represent Intermittences.
Consider the equations (24c) to (27c). Three conditions have to be
satisfied, in general, the resistance-balance (25c) and the balance of
integral extra-current (26c) not being sufficient. To illustrate this in a
simple manner, let 2 and 3 be equal coils, by previous adjustment, and
1 and 4 coils having the same resistance as the others, but of lower
inductance, or else two coils whose total resistance in sequence is that
270 ELECTRICAL PAPERS.
of each of the others, but of lower inductance when separated. The
resistance-balance is satisfied, of course. Now, if the next condition
were sufficient to make an induction-balance, all we should have to do
would be to make L^ + L4 = 2L3. For instance, if L^ is first adjusted to
equal L2 and L3, then, by increasing either L± or L4 to the right
amount, silence would result. It does result when it is L4 that is
increased, but not when it is Lr If the sound to be quenched is slight,
the residual sound in the Zx case is feeble and might be overlooked ;
but if it be loud, then the residual sound in the L-^ case is loud and is
comparable with that to be destroyed, whilst in the L4 case there is
perfect silence.
The reason of this is that in the L^ case we satisfy only the second
condition, whilst in the L4 case we satisfy the third as well.
Another way to make the experiment is to make 1, 2, and 3 equal,
and 4 of the same resistance but of lower inductance — much lower.
Then the insertion of a non-conducting iron core in 1 will lead to a loud
minimum sound, but if put in 4 will bring us to silence, except as
regards something to be mentioned later.
Supposing, however, we should endeavour to get silence by operating
upon Lv although we cannot do it exactly, yet by destroying the
resistance-balance we may approximate to it. Thus we have a false
resistance- and a false induction-balance, and the question would
present itself, If we were to wilfully go to work in this way in the
presence of exact methods, how should we interpret the results 1 As
neither (25c) nor (26c) is true, it is suggested that we make use of the
formula based upon the assumption that the currents are sinusoidal or
pendulous, or S.H. functions of the time. Take ^»2= - n2 in (24c), the
frequency being n/2-n-, and we find
...................... (34c)
are the two conditions to be satisfied ; and we can undoubtedly, if we
take enough trouble, correctly interpret the results, if the assumption
that has been made is justifiable.
I should have been fully inclined to admit (and have no doubt it is
sometimes true) that, with an intermitter making regular vibrations,
we might regard the residual sound as due to the upper partials, and
that 71/27T could be taken as the frequency of the intermitter, and (34c),
(35c) employed safely, though not with any pretensions to minute
accuracy, if circumstances compelled us to ignore the exact methods of
true balances, were it not for the fact that this hypothesis sometimes
leads to utterly absurd results when experimentally tested. Of this I
will give an illustration, and, as we have only to test that intermittences
may be regarded as S.H. reversals, simplify by taking R^R^ Ll = L2,
which makes an exact equal-ratio balance, fi3 = J?4, L3 = L4.
Since a steady or slowly varying current does not produce sound in
the telephone, if a battery could be treated as an ordinary conductor,
we could put it in one of the sides of the quadrilateral and balance it,
just like a coil, in spite of its electromotive force. So, let 1 and 2 be
ON THE SELF-INDUCTION OF WIRES. PART VI. 271
equal coils, 3 the battery to be tested, and 4 the balancing coils. I find
that a good battery can be very well balanced, though not perfectly,
with intermittences, as regards resistance, which is, however, far less
with rapid intermittences than with a steady current.* Thus : steady,
2J ohms; intermittent (about 500), 1J ohm. Another battery: steady,
166 ohms; intermittent, 126 ohms. The steady resistances are got by
cutting out the intermitter, using a make-and break instead; the
deflection of a galvanometer in 5 must be the same whether 6 is in or
out. If we leave out the battery in 6, it becomes Mance's method.
The sensitiveness is, however, far greater when the battery is not left
out, although other effects are then produced.
So far regarding the resistance. As regards the inductance, or
apparent inductance, of batteries, that is, I find, usually negative.
That is to say, after bringing the sound to a minimum by means of
resistance-adjustment, the residual sound (sometimes considerable) may
be quenched by inserting equal coils in branches 3 and 4, and then
increasing the inductance of the one containing the battery under test.
I selected the battery which showed the greatest negative inductance,
about | mac, or 500,000 centim., got the best possible silence by
adjustment of resistance and inductance, and then found the residual
sound could be nearly quenched by allowing induction between the
coil in 3 and a silver coin, provided, at the same time, R4 were a little
increased.
It was naturally suggested by the negative inductance and lower
resistance that the battery behaved as a shunted condenser, or as a
shunted condenser with resistance in sequence, or something similar ;
and I examined the influence of the frequency on the values of the
effective resistance and inductance. The change in the latter was
uncertain, owing to the complex balancing, but the apparent resistance
was notably increased by increasing the frequency, viz., from 125 to
130 ohms, when the frequency was raised from about 500 to about 800,
whilst there was a small reduction in the amount of the negative in-
ductance. The effect was distinct, under various changes of frequency,
but was the opposite (as regards resistance) of what I expected on the
S.H. assumption. To see whereabouts the minimum apparent resist-
ance was (being 165 steady), I lowered the frequency by steps. The
resistance went down to 113 with a slow rattle, and so there was no
minimum at all. The S.H. assumption had not the least application to
the apparent resistance, as regards the values 165 steady, 113 slow
intermittences, although it no doubt is concerned in the rise from 113
to 130 at frequency 800. The balance (approximate) was some com-
plex compromise, but was principally due to a vanishing of the integral
extra-current. Of course in such a case as this we should employ a
strictly S.H. impressed force; a remark that applies more or less in all
cases where the combination tested does not behave as a mere coil of
constant 11 and L.
* I am aware that Kohlrauseh employs the telephone with intermittences to
find the resistance of electrolytes, but have no knowledge of how he gets at the
true resistance.
272 ELECTRICAL PAPERS.
The other effects, due to using a battery in branch 6 as well, are
complex. It made little difference when the current in the cell was in
its natural direction ; but on reversal (by reversing the battery in 6)
there was a rapid fall in the resistance — for instance, from 46 ohms to
18 ohms in half a minute in the case of a rather used-up battery, but a
comparatively small fall when the battery was good.
Besides the advantage of independence of the manner of variation of
the impressed force (in all cases where the lesistance and inductance do
not vary with the frequency), and the great ease of interpretation, the
equal-ratio method gives us independence of the mutual induction of 1
and 2 and of 3 and 4 ; and this, again, leads to another advantage of
an important kind. If the arrangement is at all sensitive, the balance
will continually vary, on account of temperature inequalities occurring
in experimenting, caused by the breath, heat of hands, lamps, etc.
Now, if the four sides of the quadrilateral consist of four coils, equal in
pairs, it is a difficult matter to follow the temperature-changes. To
restore a resistance-balance is easy enough ; but more than that is
needed, viz. the preservation of the ratio of equality. But, by reason
of the independence of the self-induction balance of M12, we may, as
before mentioned, wind them together, and thus ensure their equality
at every moment. There is then only left the inequality between
branches 3 and 4, which must, of course, be separated for experimental
purposes, and that is very easily followed and set right. When a sound
comes on, holding a coin over the coil of lower resistance will quench it,
if it be slight and due to resistance-inequality, and tell us which way
the inequality lies. If it be louder, the cancelling will be still further
assisted by an iron wire over or in the same coil, or by a thicker iron
wire alone, for reasons to be presently mentioned.
On the other hand, a small inequality in the inductance may be at
once detected by a fine iron wire, quenching the sound when over or
in the coil of lower inductance ; and when the resistance and induct-
ance-balances are both slightly wrong, a combination of these two ways
will show us the directions of departure. These facts are usefully
borne in mind when adjusting a pair of coils to equality, during which
process it is also desirable to handle them as little as possible, otherwise
the heating will upset our conclusions and cause waste of time. But a
pair of coils once adjusted to equality, and not distorted in shape after-
wards, will practically keep equal in inductance ; for the effect of
temperature-variation on the inductance is small, compared with the
resistance-change.
Regarding the intermitter, I find that it is extremely desirable to
have one that will give a pure tone, free from harsh irregularities, for
two reasons : first, it is extremely irritating to the ear, especially when
experiments are prolonged, to have to listen to irregular noises, or
grating and fribbling sounds; next, there is a considerable gain in
sensitiveness when the tone is pure.*
* I.e., pure in the common acceptation, not in the scientific sense of having a
definite single frequency, which is only needed in a special class of cases, when no
true balance could be got without it.
ON THE SELF-INDUCTION OF WIRES. PART VI. 273
Disturbances produced by Metal, Magnetic and Non-magnetic. The Diffusion-
Effect. Equivalence of Nonconducting Iron to Self-induction.
Coming now to the effects of metal in the magnetic field of a coil,
the matter is more easily understood from the theoretical point of view,
in the first instance, than by the more laborious course of noting facts
and evolving a theory out of them— a quite unnecessary procedure,
seeing that we have a good theory already, and, guided by it, have
merely to see whether it is obeyed and what the departures are, if any,
that may require us to modify it.
First, there is the effect of inductive magnetisation in increasing the
inductance of a coil. Diamagnetic decrease is quite insensible, or
masked by another effect, so that we are confined to iron and the other
strongly magnetic bodies. The foundation of the theory is Poisson's
assumption (no matter what his hypothesis underlying it was) that the
induced magnetisation varies as the magnetic force ; and when this is
put into a more modern form, we see that impressed magnetic force is
related to a flux, the magnetic induction, through a specific quality, the
inductivity, in the same manner as impressed electric force is related to
electric conduction-current through that other specific quality, the con-
ductivity of a body. Increasing the inductivity in any part of the
magnetic field of a coil, therefore, always increases the inductance Z, or
the amount of induction through the coil per unit current in it, and the
magnetic energy, ^LC2. The effect of iron therefore is, in the steady
state, merely to increase the inductance of a coil, without influence on
its resistance. I have, indeed, speculated [vol. I. p. 441] upon the
existence of a magnetic conduction- current, which is required to com-
plete the analogy between the electric and magnetic sides of electro-
magnetism ; but whilst there does not appear to be any more reason for
its existence than its suggestion by analogy, its existence would lead to
phenomena which are not observed.
But this increase of L by a determinable amount — determinable, that
is, when the distribution of inductivity is known, on the assumption
that the only electric current is that in the coil — breaks down when
there are other currents, connected with that in the coil, such as occur
when the latter is varying, the induced currents in whatever conducting
matter there may be in the field. L then ceases to have any definite
value. But in one case, that of S.H. variation, the mean value of the
magnetic energy becomes definite, viz., \L'C^ where V is the effective
L, and (70 the amplitude of the coil-current, the change from J to \
being by reason of the mean of the square of a sine or cosine being \.
There must be this definiteness, because the variation of the coil-current
is S.H., as well as that of the whole field. That Lf is less than L, the
steady value, may be concluded in a general though vague manner from
the opposite direction of an induced current to that of an increasing
primary, and its magnetic field in the region of the primary ; or, more
distinctly, from the power of conducting-matter to temporarily exclude
magnetic induction.
In a similar manner, the resistance of a coil, if regarded as the R in
H.E.P. — VOL. ii s
274 ELECTRICAL PAPERS.
RC'2, the Joulean generation of heat per second, ceases to have a definite
value when the current is varying, if C be taken to be the coil-current,
on account of the external generation of heat. But in the S.H. case, as
before, the mean value is necessarily a definite quantity (at a given
frequency), making ^R'C* the heat per second, where B' is the effective
resistance. That PJ is always greater than E is certain and obvious
without mathematics ; for the coil -heat is JJ?(702, and there is the external
heat as well. It is suggested that, in a similar manner, a non-mathe-
matical and equally clear demonstration of the reduction of L is possible.
The magnetic energy of the coil-current alone is \LCl, and we have to
show non-mathematically, but quite as clear as in the argument relating
to the heat, that the existence of induced external current reduces
the energy, without any reference to a particular kind of coil or kind
of distribution of the external conductivity. Perhaps Lord Rayleigh's
dynamical generalisation * might be made to furnish what is required.
When the matter is treated in an inverse manner, not regarding
electric current as causing magnetic force, but as caused by or being an
affection of the magnetic force, there is some advantage gained, inasmuch
as we come closer to the facts as a whole, apart from the details relating
to the reaction on the coil-current. Magnetic force, and with it electric
current, a certain function of the former, are propagated with such
immense rapidity through air that we may, for present purposes,
regard it as an instantaneous action. On the other hand, they are
diffused through conductors in quite another manner, quite slowly in
comparison, according to the same laws as the diffusion of heat, allowing
for their being vector magnitudes, and for the closure of the current,
thus producing lateral propagation. The greater the conductivity and
the inductivity, the slower the diffusion. Hence a conductor brought
with sufficient rapidity into a magnetic field is, at the first moment,
only superficially penetrated by the magnetic disturbance to an appreci-
able extent ; and a certain time — which is considerable in the case of a
large mass of metal, especially copper, by reason of high conductivity,
and more especially iron, by reason of high inductivity more than
counteracting the effect of its lower conductivity — is required before the
steady state is reached, in which the magnetic field is calculable from
the coil-current and the distribution of inductivity. And hence, a
sufficiently rapidly oscillatory impressed force in the coil-circuit
induces only superficial currents in a piece of metal in the field of the
coil, the interior being comparatively free from the magnetic induction.
The same applies to the conductor forming the coil-circuit itself; it,
also, may be regarded as having the magnetic disturbance diffused into
its interior from the boundary, and we have only to make the coil-wire
thick enough to make the effect of the approximation to surface-con-
duction experimentally sensible. But in common fine-wire coils it may
be wholly ignored, and the wires regarded as linear circuits. There is
no distinction between the theory for magnetic and for non-magnetic
conductors ; we pass from one to the other by changing the values of
* Phil. Mag., May, 1886.
ON THE SELF-INDUCTION OF WIRES. PART VI. 275
the two constants, conductivity and inductivity. Nor is there any
difference in the phenomena produced, if the steady state be taken in
each case as the basis of comparison. But, owing to copper having
practically the same inductivity as air, there seems to be a difference in
the theory which does not really exist.
A fine copper wire placed in one (say in branch 3) of a pair of
balanced coils in the quadrilateral, under the influence of intermittent
currents, produces no effect on the balance. Its inductivity is that of
the air it replaces, so that the steady magnetic-field is the same ; and it
is too small for the diffusion-effect to sensibly influence the balance.
On the other hand, a fine iron wire, by reason of high inductivity,
requires the inductance of the balancing-coil (say in 4) to be increased.
The other effect is small in comparison, but quite sensible, and requires
a small increase of the resistance of branch 4 to balance it. A thicker
copper wire shows the diffusion-effect ; and if we raise the frequency
and increase the sensitiveness of the balance, its thickness may be
decreased as much as we please, if other things do not interfere, and
still show the diffusion-effect. If thick, so that the disturbance is con-
siderable, the approximate balancing of it by change of resistance is
insufficient, and the inductance of coil 4 requires a slight decrease, or
that of 3 a slight increase. A thick iron wire shows both effects
strongly : the inductance and the resistance of branch 4 must be
increased. These effects are greatly multiplied when big cores are
used ; then the balancing, with intermittences, at the best leaves a
considerable residual sound. The influence of pole-pieces and of
armatures outside coils in increasing the inductance, which is so great
in the steady state, becomes relatively feeble with rapid intermittences.
This will be understood when the diffusion-effect is borne in mind.
If the metal is divided so that the main induced conduction-currents
cannot flow, but only residual minor currents, we destroy the diffusion-
effect more or less, according to the fineness of the division, and leave
only the inductivity effect. In my early experiments I was sufficiently
satisfied by finding that the substitution of a bundle of iron wires for a
solid iron core, with a continuous reduction in the diameter of the wires,
reduced the diffusion-effect to something quite insignificant in com-
parison with the effect when the core was solid, to conclude that we had
only to stop the flow of currents to make iron, under weak magnetising
forces, behave merely as an inductor. More recently, on account of
some remarks of Prof. Ewing on the nature of the curve of induction
under weak forces, I immensely improved the test by making and using
nonconducting cores, containing as much iron as a bundle of round
wires of the same diameter as the cores. I take the finest iron filings
(siftings) and mix them with a black wax in the proportion of 1 of wax
to 5 or 6 of iron filings by bulk. After careful mixture I roll the
resulting compound, when in a slightly yielding state, under consider-
able pressure, into the form of solid round cylinders, somewhat
resembling pieces of black poker in appearance. (J inch diameter, 4 to
6 inches long.) That the diffusion-effect was quite gone was my first
conclusion, Next, that there was a slight effect, though of doubtful
276 ELECTRICAL PAPERS.
amount and character. The resistance-balance had to be very carefully
attended to. But, more recently, by using coils containing a much
greater number of windings, and thereby increasing the sensitiveness
considerably, as well as the magnetising force, I find there is a distinct
effect of the kind required. Though small, it is much greater than the
least effect that might be detected ; but whether it should be ascribed
to the cause mentioned or to other causes, as dissipation of energy due
to variations in the intrinsic magnetisation, or to slight curvature in
the line of induction, so far as the quasi-elastic induction is concerned,
is quite debateable. To show it, let 1 and 2 be equal coils wound
together (L=3 macs, J? = 47 ohms), 3 and 4 equal in resistance
(723 = 724 = 93 ohms), but of very unequal inductances, that of coil 3
(L3 = 24 macs) being so much greater than that of coil 4 that the iron
core must be fully inserted in the latter to make L± = Ly (Coils 3 and
4; 1J inch external, J inch internal diameter, and f inch in depth.
Frequency 500.) The balancing of induction is completed by means of
an external core. Resistance of branch 6 a few ohms, E.M.F. 6 volts.
There is, of course, an immense sound in the telephone when the core
is out of coil 3, but when it is in, there is merely a faint residual sound,
which is nearly destroyed by increasing JK3 by about -^j part, a
relatively considerable change. On the other hand, pure self-induction
of copper wires gives perfect silence, and so does M6i, a method I have
shown to be exact [vol. II., p. 38]. (I may, however, here mention
that in experiments with mere fine copper-wire coils there are sometimes
to be found traces of variations of resistance-balance with the frequency
of intermittence, of very small amount, and difficult to elucidate owing
to temperature-variations.) Balancing partly by Jf64, and partly by the
iron cores, the residual sound increases from zero with M64: only, to the
maximum with the cores only. Halving the strength of current upsets
the induction-balance in this way : — the auxiliary core must be set a
little closer when the current is reduced. This would indicate a slightly
lower inductivity with the smaller magnetising force, and proves slight
curvature in the line of induction. But, graphically represented, it
would be invisible except in a large diagram.
It is confidently to be expected, from our knowledge of the variation
of /*, that when the range of the magnetising force is made much greater,
the ability of nonconducting iron to act merely as an increaser of
inductance will become considerably modified, and that the dissipation
of energy by variations in the intrinsic magnetisation will cease to be
insensible. But, so far as weak magnetising oscillatory forces are con-
cerned, we need not trouble ourselves in the least about minute effects
due to these causes. Under the influence of regular intermittences, the
iron gets into a stationary condition, in which the variations in the
intrinsic magnetisation are insensible. It seems probable that n must
have a distinctly lower value under rapid oscillations than when they
are slow. The values of /* calculated from my experiments on cores
have been usually from 50 to 200, seldom higher. I should state that
I define /x to be the ratio B/H, if B is the induction and H the magnetic
force, which is to include h, the impressed force of intrinsic magnetisa-
ON THE SELF-INDUCTION OF WIRES. PART VI. 277
tion. (See the general equations in Part I.) It is with this /A, not with
the ratio of the induction to the magnetising force as ordinarily under-
stood, that we are concerned with in experiments of the present kind.
Inductance of a Solenoid. The Effective Resistance and Inductance of Round
Wires at a given Frequency, with the Current Longitudinal; and the
Corresponding Formulae when the Induction is Longitudinal.
Knowing, then, that iron when made a nonconductor acts merely as
an inductor, when we remove the insulation and make the iron a solid
mass, it requires to be treated as both a conductor and inductor, just
like a copper mass, in fact, of changed conductivity and inductivity.
When the coil is a solenoid whose length is a large multiple of its
diameter, and the core is placed axially, the phenomena in the core
become amenable to rigorous mathematical treatment in a comparatively
simple manner.
In passing, I may mention that on comparing the measured with the
calculated value of the inductance of a long solenoid according to
Maxwell's formula (vol. II., art. 678, equations (21) and (23)) in the
first edition of his treatise, I found a far greater difference than could
be accounted for by any reasonable error in the ohm (reputed) or in the
capacity of the condenser, and therefore recalculated the formula. The
result was to correct it, and reduce the difference to a reasonable one.
On reference to the second edition (not published at the time referred
to) I find that the formula has been corrected. I will therefore only
give my extension of it. Let M be the mutual inductance of two long
coaxial solenoids of length I, outer diameter c2, inner clt having n± and
n2 turns per unit length. Then
where, if p = cl/c2,
^^KK^K^tC+t* ......... <««>
When
As regards Maxwell's previous formula (22), art. 678, however, there is
disagreement still.
References to authors who have written on the subject of induction
of currents in cores other than, and unknown to, and less comprehen-
sively than, myself, are contained in Lord Rayleigh's recent paper.* So
far as the effect on an induction-balance is concerned, when oscillatory
currents are employed, it is to be found, as he remarks, by calculating
the reaction of the core on the coil-current. This I have fully done in
my article on the subject. Another method is to calculate the heat in
the core, to obtain the increased resistance. This I have also done.
When the diffusion-effect is small, its influence on the amplitude and
* Phil. Mag., December, 1886.
278 ELECTRICAL PAPERS.
phase of the coil-current is the same as if the resistance of the coil-
circuit were increased from the steady value R to [vol. I., p. 369]
= E + 2/7r£(7r^VcV)2 = R + BI say.
" Many phenomena which may be experimentally observed when rods
are inserted in coils may be usefully explained in this manner." Here
H and k are the inductivity and conductivity of the core, of length I,
the same as that of the coil, n/2ir the frequency, c the core's radius,
and N the number of turns of wire in the coil per unit length ; whilst
is that part of the steady inductance of the coil-circuit which is con-
tributed by the core.
The full expression for the increased resistance due to the dissipation
of energy in the core is to be got by multiplying the above Rl by Yt
which is given by [vol. I., p. 364]
_ _
2.6.8* V 3.10. 4.14.
where y = (lirpknc*)*. The value of R' is therefore R + R^. The
series being convergent, the formula is generally applicable. The law
of the coefficients is obvious. I have slightly changed the arrangement
of the figures in the original to show it. We may easily make the
core-heat a large multiple of the coil-heat, especially in the case of iron,
in which the induced currents are so strong. When y is small enough,
we may use the series obtained by division of the numerator by the
denominator in (49c), which is
16.24 15. 163. 9
Corresponding to this, I find from my investigation [vol. I., p. 370]
of the phase-difference, that the decrease of the effective inductance
from the steady value is expressed by
y /« 19?/ , 229w2 , \
-
When the same core is used as a wire with current longitudinal, and
again as core in a solenoid with induction longitudinal, the effects are
thus connected. Let Ll be the above steady inductance of the coil so
far as is due to the core, and L{ its value at frequency ?i/27r, when it
also adds resistance R{ to the coil. Also let E2 be the steady resistance
of the same when used as a wire, and R( and Li its resistance and
inductance at frequency w/2w, the latter being what ^ then becomes.
Then
J TITOT.1 /7 T"fc T T~>/ T t . T\l T t "\
(52o)
ON THE SELF-INDUCTION OF WIRES. PART VI. 279
I did not give any separate development of the L( of the core, cor-
responding to (48c) and (49c) above for Bf, but merged it in the ex-
pression for the tangent of the difference in phase between the impressed
force and the current in the coil-circuit. The full development of L{ is
same denominator as in (49c)
The high-frequency formulae for E{ and L{ are
(2*)*'
if y = IQz2. When z is as large as 10, this gives
#( = ^=•2234 L&,
whereas the correct values by the complete formulae are
#{ = •198^, £{=-225 Lr
It is therefore clear that we may advantageously use the high-
frequency formulae when z is over 10, which is easily reached with iron
cores at moderate frequencies.
The corresponding fully developed formulae for R( and Lf2, when the
current is longitudinal, are
_ __
6.16V 23.10.16 3*. 14. 16
_
2.6.16V 3. 22. 10.16V 4.32.14.16
showing the laws of formation of the terms, and
I4= +22.6.16V1 + 2.32.10.16V1+3.42.'l4.r6V
5" ............................................................... '
the denominator being as in the preceding formula. At z =10, or
y=1600, these give
whereas Lord Rayleigh's high-frequency formulae, which are
^ = 2-234^2, £5 = J/*x -447.
is particular frequency makes the amplitude of the magnetic force in
e case of the core, and of the electric current in the other case,
fourteen times as great at the boundary as at the axis of the wire or
core (see Part I.). As, however, we do not ordinarily have very thick
wires for use with the current longitudinal, the high-frequency formulae
are not so generally applicable as in the case of cores, which may be as
280 ELECTRICAL PAPERS.
thick as we please, whilst by also increasing the number of windings
the core-heating per unit amplitude of coil-current may be greatly
increased.
If the core is hollow, of inner radius c0, else the same, the equation
of the coil-current is, if e be the impressed force and G the current in
the coil-circuit whose complete steady resistance and inductance are R
and L, whilst L^ is the part of L due to the core and contained hollow
(dielectric current in it ignored),
........... (53c)
sc J0(sc)-qK0(sc)
when q depends upon the inner radius, being given by
(whose value is zero when the core is solid), and
There may be a tubular space between the core and coil, and E, L may
include the whole circuit. In reference to this equation (53c), how-
ever, it is to be remarked that there is considerable labour involved in
working it out to obtain what may be termed practical formulae,
admitting of immediate numerical calculation. The same applies to a
considerable number of unpublished investigations concerning coils and
cores that I made, including the effects of dielectric displacement ; the
analysis is all very well, and is interesting enough for educational pur-
poses, but the interpretations are so difficult in general that it is
questionable whether it is worth while publishing the investigations, or
even making them.
The Christie Balance of Resistance, Permittance, and Inductance.
Leaving now the question of cores and the balance of purely magnetic
self-induction, and returning to the general condition of a self-induction
balance, Z1Z4t = Z2Z3) equation (23e), let the four sides of the quadri-
lateral consist of coils shunted by condensers. Then R, L, and S
denoting the resistance, inductance, and capacity of a branch, we have
Z={Sp + (R + Ip)-1}-1; ..................... (55c)
so that the conjugacy of branches 5 and 6 requires that
{Sl
}, ............ (56c)
wherein the coefficient of every power of p must vanish, giving seven
conditions, of which two are identical by having a common factor. It
is unnecessary to write them out, as such a complex balance would be
useless ; but some simpler cases may be derived. Thus, if all the Z/s
ON THE SELF-INDUCTION OF WIRES. PART VI. 281
vanish, leaving condensers shunted by mere resistances, we have the
three conditions
I (57c)
which may be compared with the three self-induction conditions (25c)
to (27 c).
If we put ES=y, the time-constant, the second of (57c) may be
written
which corresponds to (26c). If $2 = 0 = $4, the single condition in
addition to the resistance-balance is i/1 = yy If Sl = 0 = /SL it is y3 = y4.
Next, let each side consist of a condenser and coil in sequence.
Then the expression for Z is
Z=R + Lp + (Sp)-\ ......................... (59c)
which gives rise to five conditions,
~ L1S1 ~
1111
— + — = —+-,
1 <t *l 9
Here it looks as if the resistance-balance were unnecessary ; and, as
there can be no steady current, this seems a sufficient reason for its not
being required. But, in fact, the third condition, by union with the
others, eliminating $3, X3, «S4, and L± by means of the other four con-
ditions, becomes
0 -
So the obvious way of satisfying it is by the true resistance-balance.
[But see, on this point, the beginning of the next Part VII.]
If there are condensers only, without resistance-shunts, we have
Z=(SpY\ ................................. (62c)
so that #A = £& ................................. (63c)
is the sole condition of balance.
If two sides are resistances, P^ and Ry and two are condensers, $3
and $4, we obtain
BjRi-SJSs ................................. (64c)
as the sole condition. The multiplication of special kinds of balance is
a quite mechanical operation, presenting no difficulties.
:
General Theory of the Christie Balance with Self and Mutual
Induction all over.
Passing now to balances in which induction between different
branches is employed, suppose we have, in the first place, a true
resistance-balance, R1R^ = R2EBJ but not an induction-balance, so that
282 ELECTRICAL PAPERS.
there is sound produced in the telephone. Then, by means of small
test-coils placed in the different branches, we find that we may reduce
the sound to a minimum in a great many ways by allowing induction
between different branches. If the sound to be destroyed is feeble, we
may think that we have got a true induction-balance ; but if it is
loud, then the minimum sound is also loud, and may be comparable
to the original in intensity. We may also, by upsetting the resistance-
balance by trial, still further approximate to silence, and it may be a
very good silence, with a false resistance-balance. The question
arises, Can these balances, or any of them, be made of service and be
as exact as the previously described exact balances ? and are the
balances easily interpretable, so that we may know what we are doing
when we employ them ?
There are fifteen ATs concerned, and therefore fifteen ways of
balancing by mutual induction when only two branches at a time are
allowed to influence one another, and in every case three conditions are
involved, because there are three degrees of current-freedom in the six
conductors involved. Owing to this, and the fact that in allowing
induction between a pair of branches we use only one condition (i.e.
giving a certain value to the M concerned), whilst the resistance-balance
makes a second condition, I was of opinion, in writing on this subject
before [vol. IL, p. 35], that all the balances by mutual induction, using
a true resistance-balance, were imperfect, although some of them were
far better than others. Thus, I observed experimentally that when a
ratio of equality (Rl = R& ^ = L.J was taken, the balances by means of
M63 or MM were very good, whilst that by M65 was usually very bad,
the minimum sound being sometimes comparable in intensity to that
which was to be destroyed.
I investigated the matter by direct calculation of the integral extra-
current in branch 5 arising on breaking or making branch 6, due to the
momenta of the currents in the various branches, making use of a
principle I had previously deduced from Maxwell's equations [vol. I.,
p. 105], that when a coil is discharged through various paths, the
integral current divides as in steady flow, in spite of the electromotive
forces of induction set up during the discharge. This method gives us
the second condition of a true balance.
But more careful observation, under various conditions, showing a
persistent departure from the true resistance-balance in the MQ5 method
(due to Professor Hughes), and that the M^ and M6i methods were
persistently good and were not to be distinguished from true balances,
led me to suspect that the second and third conditions united to form
one condition when a ratio of equality was used (just as in (28c), (29c)
above) in the M69 and M64c methods, but not in the M65 method. So I
did what I should have done at the beginning; investigated the
differential equations concerned, verified my suspicions, and gave the
results in a Postscript [vol. II., p. 38]. I have since further found
that, when using the only practical method of equal-ratio, there are no
other ways than those described in the paper referred to of getting a
true balance of induction by variation of a single L or M, after the
ON THE SELF-INDUCTION OP WIRES. PART VI.
283
resistance-balance has been secured. This will appear in the following
investigation, which, though it may look complex, is quite mechanical
in its simplicity.
Write down the equations of electromotive force in the three circuits
6 + 1 + 3, 1 + 5-2, and 3-4-5, when there is impressed force in
branch 6 only. They are (p standing for d/dt),
+ L3p)C3
4 + 7J/65(75)
1 + MQ2C2 + M63C3
+P(M12C2 + M13C3
+P(M31C1 + M32C2
+ 7!f36(76),
0 =
+p(M5lCl
2 A + ^"23^3 + ^2 A + ^5^5
0 =
+P(M31C1
+ M36C6)
- P(M5lCl
Now, eliminate Cf1, C2, C6 by the continuity conditions
(71 = C'3 + Cr5, (72 = 64—(75, ^ = (73 + 6*
giving us
,(65c)
(66c)
(67.)
= 31 3 ' 32 4 33 5' •
where the X's are functions of p and constants. Solve for (75. Then
we see that
^22^31
.(68e)
is the complex condition of conjugacy of branches 5 and 6. This could
be more simply deduced by assuming C5 = 0 at the beginning, but it
may be as well to give the values of all the JT's, although we want but
four of them. Thus
+ 2M3l)p,
+ M
15
- M12 + Mu + M3l -
- M21 -
X22 = - R.2 + ( - L2 + 7I/12
X3l =
+ .J/;
+ M36)p,
+ M35)p,
- M26)p,
54
+ 7l/
31
- 7l/24 -
- M53 -
...(69c)
284 ELECTRICAL PAPERS.
Now, using the required four of these in (68c), and arranging in
powers of p, it becomes
O^AQ + Atf + A^ ...................... (70c)
So A0 = 0 gives the resistance-balance ; A1 = 0, in addition, makes the
integral transient current vanish ; and A2 = 0, in addition, wipes out all
trace of current.
There is also the periodic balance,
^ = 0, A, = A2ri\ ..................... (71c)
if the frequency is w/2ir.
The values of A0 and Al are
2, + M2Q - M12 - M14 - M16 - M52 - MM
, (M32 + M3i + M36 - Mi2 - MM - M52 - MU - My.)
+ R,(M21 + M2B + M2Q-MIB-M16-M15-M5B-M,6) .......... (73c)
In this last, let the coefficients of R2, Rz, Rv R± in the brackets be
q2, qy qv q±. Then the value of A 2 is
It is with the object of substituting one investigation for a large
number of simpler ones that the above full expressions for Al and A2
are written out.
Examination of Special Cases. Reduction of the Three Conditions of
Balance to Two.
If we take all the IPs as zero, we fall back upon the self-induction
balance (25c) to (27c). Next, by taking all the M 's as zero except one,
we arrive at the fifteen sets of three conditions. Of these we may
write out three sets, or, rather, the two conditions in each case besides
the condition of resistance-balance, which is always the same.
Ally's = 0, except M36.
4 - x2 - x3) = (R! + R2)M36, } ,
, except Jf46.
+ x,-x2-x3)=- (R,
As these only differ in the sign of the M, we may unite these two
cases, allowing induction between 6 and 3, and 6 and 4. The two con-
ditions will be got by writing M36 - M^ for M36 in (75c).
All M's = 0, except M5Q (Prof. Hughes's method).
0 = R + X-x- x + M + R + R + R
'"
ON THE SELF-INDUCTION OF WIRES. PART VI. 285
Now choose a ratio of equality, Rl = Rv L1 = L2, which is the really
practical way of using induction-balances in general. In the M3Q case
the two conditions (75c) unite to form the single condition
Lt-LB = 2M3Q, ............................ (78c)
and in the M^ case (76c) unite to form the single condition
Z4-£3=-2Jf46 ............................ (79c)
We know already that the same occurs in the case of the simple Christie,
as in (29c), making
4 = 4: ................................. (80e)
so that we have three ways of uniting the second and third conditions.
Now examine all the other M 's, one at a time, on the same assumption,
Bl = E2, LI = L2. With M12 we obtain
(L,-L.)(L1-M12) = Q) and L, = Ly
But Ll - M12 cannot vanish ; so that
4 = 4 .................................. (81«)
is the single condition. Similarly, in case of M^,
L, = L3 .................................. (82c)
again. All these, (77c) to (82c), were given in the paper referred to;
the last two mean that M12 and Af34 have absolutely no influence on the
balance of self-induction.
All the rest are double conditions. Thus, in A1 and A2 put Bl = M2,
Ez = E^ and Ll = L2') then the two conditions are
0 = L± - LB + (1 + BJB1)(MU - M2B + Mbl + MM + MW + M^ + 2M56)
+ 2(MM - M3Q) + (1 - JtJEMMu - Mu) + ^(EJE^M^ - M26) ; (83c)
0 = Ltfi - LB) + LB(M12 + Mu + M16
+ Lt(Mu + Mu
56 - M3l - M3Q)
- M12 - Mu - M16 - MM - MM - M,&) ; (84c)
which are convenient for deriving the conditions when several M 's are
operative at the same time. Thus, one at a time, excepting the few
already examined :—
(85)
(86)
'
JO = L, - L3 + M53(l + BJRJ \ (87 }
" )
286 ELECTRICAL PAPERS.
l . .
'
(0 = Li-L3-
(0 = 4-4-
m.
.......
9,.
13 ..... 0 = 4-4-^3(1-^)'
fO = 4 -4 + Mn(\-RJRJ\ ,M)
24 ..... io=4-4+jif24(i-4/4)>
fO = L4-is + Af14(l+JJ4/^) 1 ,94.
' ' \o = 4 - 4 + jif14(i + 4/4) - jif «/4 f '
(0=4-4-^(1+^) \ ,95.
' ' |o = 4 - 4 - irji + 4/4) + jft/ij'
If we compare the two general conditions (83c), (84c), we shall see
that whenever
we may obtain the reduced forms of the conditions by adding together
the values of L% — L4 given by every one of the M' s concerned. We
may therefore bracket together certain sets of the M' s. To illustrate
this, suppose that M13 and M24 are existent together, and all the other
IT's are zero. Then (92c) and (93c) give, by addition,
which are the conditions required.
Similarly M12 and Jf34 may be bracketed. Also M6V M62, M63, M^t
and M65. Also M51, M^, M^, M54, and M56. But Mu and M23 will
not bracket.
Miscellaneous Arrangements. Effects of Mutual Induction between the
Branches.
As already observed, the self-induction balance (28c), (29c) is inde-
pendent of M12 and 1T34, when these are the sole mutual inductances
concerned; that is, when R^R^, L^L^, R^ = R^ L3 = L±. By (92c)
and (93c) we see that independence of M13 and M24 is secured by
making all four branches 1, 2, 3, 4 equal in resistance and inductance.
But it is unsafe to draw conclusions relating to independence when
several coils mutually influence, from the conditions securing balance
when only two of the coils at a time influence one another. Let us
examine what (83c) and (84c) reduce to when there is induction between
ON THE SELF-INDUCTION OF WIRES. PART VI. 287
all the four branches 1, 2, 3, 4, but none between 5 and the rest or
between 6 and the rest. Put all M' s = 0 which have either 5 or 6 in
their double suffixes, and put L± = Ly Then we may write the con-
ditions thus : —
-M^ .................. (96c)
0 = (L, + L,)(MU - M2,) + (L, - L,)(M2, - M13) + M%3 - M\,
+ (M2, - Jf13)( J/34 - M12) + (Mu - M23)(M2, + MIB - M12 - M,,}. (97c)
The simplest way of satisfying these is by making
MU = M23 and M24 = M13 ................. (98c)
If these equalities be satisfied, we have independence of M12 and MM.
Now, if we make the four branches 1, 2, 3, 4 equal in resistance and
inductance, so that in (96c) and (97c) we have R^ = R^ and L^ = L^ the
first reduces to
Q = M14-M23, ............................ (99c)
so that it is first of all absolutely necessary that MU = M2# if the
balance is to be preserved ; whilst, subject to this, the second condition
reduces to
0 = (l/24-Jf13)(Jf34-Jlf12), .................. (lOOc)
so that either MZ4 = M ,3, or else MM = M12. Thus there are two ways
of preserving the balance when all four branches are equal, viz.,
Jf14 = l/23 and M24: = M13, independent of the values of M12 and If34;
and Mu = 3/23 and Af34 = M 12, independent of the values of Jf24 and M13.
The verification of these properties, (98c) and later, makes some very
pretty experiments, especially when the four branches consist, not
merely of one coil each, but of two or more. The meanings of some of
the simpler balances are easily reasoned out without mathematical
examination "of the theory ; but this is not the case when there is
simultaneous induction between many coils, and their resultant action
on the telephone-branch is required.
Returning to (96c) and (97c), the nearest approach we can possibly
make to independence of the self-induction balance of the values of all
the W s therein concerned, consistent with keeping wires 3 and 4 away
from one another for experimental purposes, is by winding the equal
wires 1 and 2 together. Then, whether they be joined up straight,
which makes M13 = M23 and Mu = M<,± identically, or reversed, making
M^ — - M23 and Mu = - Jf24, we shall find that
MU-M*
is the necessary and sufficient condition of preservation of balance.
At first sight it looks as if M3l and M32 must cancel one another
when wires 1 and 2 are reversed. But although 1 and 2 cancel on 3,
yet 3 does not cancel on 1 and 2 as regards the telephone in 5. The
effects are added. On the other hand, when wires 1 and 2 are straight,
3 cancels on them as regards the telephone, but 1 and 2 add their-
effects on 3. Similar remarks apply to the action between 4 and the
equal wires 1 and 2 when straight or reversed ; hence the necessity of
the condition represented by the last equation.
288 ELECTRICAL PAPERS.
On the other hand, M6l and M62 cancel when 1 and 2 are straight,
and add their effects when they are reversed: whilst M6l and M52
cancel when 1 and 2 are reversed, and add their effects when they are
straight, results which are immediately evident. But wires 1 and 2
must be thoroughly well twisted, before being wound into a coil, if it is
desired to get rid of the influence of, say, MG1 and M62, when it is a coil
that operates in 6, and this coil is brought near to 1 and 2.
This leads me to remark that a simple way of proving that the
mutual induction between iron and copper (fine wires) is the same as
between copper and copper, which is immensely more sensitive than
the comparison of separate measurements of the induction in the two
cases, is to take two fine wires of equal length, one of iron, the other of
copper, twist them together carefully, wind into a coil, and connect up
with a telephone differentially. On exposure of the double coil to the
action of an external coil in which strong intermittent currents or
reversals are passing, there will be hardly the slightest sound in the
telephone, if the twisting be well done, with several twists in every
turn. But if it be not well done, there will be a residual sound,
which can be cancelled by allowing induction between the external or
primary coil and a turn of wire in the telephone-circuit. A rather
curious effect takes place when we exaggerate the differential action by
winding the wires into a coil without twists, in a certain short part of
its length. The now comparatively loud sound in the telephone may
be cancelled by inserting a nonconducting iron core in the secondary
coil, provided it be not pushed in too far, or go too near or into the
primary coil. This paradoxical result appears to arise from the secondary
coil being equivalent to two coils close together, so that insertion
of the iron core does not increase the mutual inductance of the primary
and secondary in the first place, but first decreases it to a minimum,
which may be zero, and later increases it, when the core is further
inserted. Reversing the secondary coil with respect to the primary
makes no difference. Of course insertion of the core into the primary
always increases the mutual inductance and multiplies the sound. The
fact that one of the wires in the secondary happens to be iron has
nothing to do with the effect.
Another way of getting unions of the two conditions of the induction-
balance is by having branches 1 and 3 equal, instead of 1 and 2. Thus,
if we take E1 = E3, L^ = L^ R2 = R± in A^ and A2, (73c) and (74c), we
obtain fifteen sets of double conditions similar to those already given,
out of which just four (as before) unite the two conditions. Thus,
using MIB only, we have
L2=L» (lOlc)
and the same if we use M24: only, and the same when both MIB and M24
are operative. That is, the self-induction balance is independent of M 13
and M24. This corresponds to (81c) and (82c).
The other two are MZ5 and M45. With M2b we have
0 = L2-Lt-2M25 (102e)
and with ^T45, 0 = L2 - Z4 - 27lf45 (103c)
ON THE SELF-INDUCTION OF WIRES. PART VII. 289
The remaining eleven double conditions corresponding to (85c) to
(95c) need not be written down.
Several special balances of a comparatively simple kind can be
obtained from the preceding by means of inductionless resistances,
double-wound coils whose self-induction is negligible under certain cir-
cumstances, allowing us to put the L's of one, two, or three of the four
branches 1, 2, 3, 4 equal to zero. We may then usefully remove the
ratio-of-equality restriction if required. This vanishing of the L of a
branch of course also makes the induction between it and any other
branch vanish.
For instance, let Ll = L% = L4 = 0 ; then
0 = #2L3 + 71/36(^ + ^2) (104c)
gives the induction-balance when M3(] is used, subject to R^R^R^Ry
And
0 = R2L3-MBb(R2 + ^) (105c)
is the corresponding condition when M^ is used. But M56 will not give
balance, except in the special case of S.H. currents, with a false resist-
ance-balance. The method (104c) is one of Maxwell's. His other two
have been already described.
In the general theory of reciprocity, it is a force at one place that
produces the same flux at a second as the same force at the second place
does at the first. That the reciprocity is between the force and the
flux, it is sometimes useful to remember in induction-balances. Thus
the above-mentioned second way of having a ratio of equality is merely
equivalent to exchanging the places of the force and the vanishing flux.
We must not, in making the exchange, transfer a coil that is operative.
For example, in the M6i method (79c), there is induction between
branches 6 and 4; M45 (equation (88c)), on the other hand, fails to give
balance. But if we exchange the branches 5 and 6, it is the battery
and telephone that have to be exchanged ; so that we now use M^
which gives silence, whilst M6i will not.
I have also employed the differential telephone sometimes, having
had one made some five years ago. But it is not so adaptable as the
quadrilateral to various circumstances. I need say nothing as to its
theory, that having been, I understand, treated by Prof. Chrystal.
Using a pair of equal coils, it is very similar to that of the equal-ratio
quadrilateral.
PART VII.
Some Notes on Part VI. , (1). Condenser and Coil Balance.
After my statement [p. 260, vol. n.] of the general condition of con-
jugacy of a pair of conductors, and the interpretation of the set of
equations into which it breaks up, I stated that in cases where, by the
presence of inverse powers of p, there could not be any steady current
in either of the to-be conjugate conductors due to impressed voltage in
the other, a true resistance-balance was still wanted to ensure con-
H.E.P. — VOL. ii. T
290 ELECTRICAL PAPERS.
jugacy when the currents vary. I am unable to maintain this hasty
generalisation. In the example I gave, equations (59c) to (61c), in
which each side of the quadrilateral consists of a condenser and a coil
in sequence, so that there can be no steady current in the bridge-wire,
it is true that the obvious simple way of getting conjugacy is to have a
true resistance-balance. The conditions may then be written
23 '
and either
?:?• and ;>:j'. ore.se ^ and *-*>}
XB ~ X& y%—y±> X2~ ^ y<L—y±>}
where R stands for the resistance and L for the inductance of a coil.
S for the permittance of the corresponding condenser, x for the coil
time-constant L/fi, and y for the condenser time-constant ES ; that is,
we require either vertical or else horizontal equality of time-constants,
electrostatic and magnetic, subject to certain exceptional peculiarities
similar to those mentioned in connection with the self-induction balance.
It is also the case that on first testing the power of evanescence of the
other factor on the right of equation (61c), it seemed to always require
negative values to be given to some of the necessarily positive quanti-
ties concerned. But a closer examination shows that this is not neces-
sary. As an example, choose
^ = 1, £2 = 2, R. = 3, tf^HVj
A = -\°, £2 = 5, L3 = ^ Z4 = f, I ...... (3d)
S1==7, S2 = 5, S3 = f|, fli-trJ
It will be found that these values satisfy the whole of equations (61c),
and yet the resistance-balance is not established. No doubt simpler
illustrations can be found. We must therefore remove the requirement
of a resistance-balance when there can be no steady current, although
the condition of a resistance-balance, when fulfilled, leads to the simple
way of satisfying all the conditions.
(2). Similar Systems.
If V=Zfi be the characteristic equation of one system and F=Z2C
that of a second, V being the voltage and C the current at the terminals,
they are similar when
Z-JZ2 = n, any numeric
Here Z is the symbol of the generalised resistance of a system between
its terminals, when it is, save for its terminal connexions, independent
of all other systems ; a condition which is necessary to allow of the
form V= ZC being the full expression of the relation between V and C,
Z being a function of constants and of p,p2, pB, etc., and p being d/dt.
To ensure the possession of the property (46?), we require first of all
that one system should have the same arrangement as the other, as a
coil for a coil, a condenser for a condenser, or equivalence (as, for
instance, by two condensers in sequence being equivalent to one) ; and,
ON THE SELF-INDUCTION OF WIRES. PART VII. 291
next, that every resistance and inductance in the first system be n
times the corresponding resistance and inductance in the second
system, and every permittance in the second system be n times the
corresponding one in the first.
Then, if the two systems be joined in parallel, and exposed to the
same external impressed voltage at the terminals, the potentials and
voltages will be equal in corresponding parts, whilst the current in any
part of the second system will be n times that in the corresponding
part of the first. Also the electric energy, the magnetic energy, the
dissipativity, and the energy-current in any part of the second system
are n times those in the corresponding part of the first.
The induction-balance got by joining together corresponding points
through a telephone is, of course, far more general than the Christie
balance, limited to four branches, each subject to V=ZG\ at the same
time, however, it is less general than the conditions which result when
the full differential equation is worked out.*
By the above, any number of similar systems may be joined in
parallel, having then equal voltages, and their currents in the ratio of
the conductances. They will behave as a single similar system, the
conductance of any part of which is the sum of the conductances of the
corresponding parts in the real systems; and similarly for the per-
mittances and for the reciprocals of the inductances. If, on the other
hand, they be put in sequence, the resultant Z is the sum of the separate
Z's, the current in all is the same, and the voltages are proportional to
the resistances.
When the systems are not independent the above simplicity is lost ;
and I have not formulated the necessary conditions of similarity in an
extended sense except in some simple cases, of which a very simple
one will occur later in connexion with another matter.
(3). The Christie Balance of Resistance, Self and Mutual Induction.
The three general conditions of this are given in equations (72c) to
(74c). If, now, we introduce the following abbreviations,
m3 = S + I
m6 = Z,2 + Z4 +L6
m13 = - L5 + M13 - M
the conditions mentioned reduce simply to
R\R± = ^^
(mj + ml3 + m16)#4 - 7%^ = (msl
(m, + m]3)m36 =
* This general property is, it will be seen, of great value in enabling us to avoid
useless and lengthy mathematical investigations. In another place [p. 115, vol.
II.], I have shown how to apply it to the at first sight impossible feat of balancing
iron against copper.
292
ELECTRICAL PAPERS.
The interpretation is, that as there are only three independent
currents in the Christie arrangement, there can be only six independent
inductances, viz., three self and three mutual ; and these maybe chosen
to be the above ra's, whose meanings are as follows. Let the three
circuits be AB^A, CB2B,C, and
AB2CA in the figure, so that the
currents in them are Cv CB, and C6.
Then mp ra3, and m6 are the self,
and m13, m
m6l the mutual induct-
ances of the three circuits.
Now if the four sides of the
quadrilateral consist merely of short
pieces of wire, which are not bent
into nearly closed curves, it is clear
that (Qd) are the true conditions, to
which alone can definite meaning be
attached ; the inductance of a short
wire being an indefinite quantity,
depending upon the position of other wires. We may therefore start
ab initio with only these six inductances, and immediately deduce
[p. 107, vol. II.] the conditions (Qd), saving a great deal of preliminary
work. But, on coming to practical cases, in which the inductances do
admit of being definitely localised in and between the six branches of
the Christie, we have to expand the m's properly, using (5d) or as
much of them as may be wanted, and so obtain the various results in
Part VI. Therefore equations (6d) are only useful as a short registra-
tion of results, subject to (5d), and in the remarkably short way in
which they may be got; a method which is, of course, applicable to
an)7 network, which can only have as many independent inductances
as there are independent circuits, plus the number of pairs of the same.
(4). Reduction of Coils in Parallel to a Single Coil.
In Part VI. [p. 267, vol. II.], in speaking of the inductometer, I
referred to the most useful property that a pair of equal coils in parallel
behave as one coil to external voltage, whatever be the amount of
mutual induction between them ; a property which, excepting in the
mention of mutual induction, I had pointed out in 1878 [p. Ill, vol. I.].
But, although there appears to be no other case in which this property
is true for any value of the mutual inductance, which is the property
wanted, yet, if a special value be given to it, any two coils in parallel
will be made equivalent to one.
The condition required is obviously that Z, the generalized resistance
of the two coils in parallel, should reduce to the form R + Lp. Equa-
tion (30c) gives Z\ to make the reduction possible, on dividing the
denominator into the numerator, the second remainder must vanish.
Performing this work, we find
LL-m2 /^7X
-- -'
z
- 2m J
ON THE SELF-INDUCTION OF WIRES. PART VII. 293
which shows the effective resistance and inductance of the coils in
parallel, rl and r2 being their resistances, and llt /2, m the inductances \
subject to
giving a special value to m, which, if it be possible, will allow the coils
to behave as one coil, so that, when put in one side of the Christie, the
self-induction balance can be made. This equation (Sd) is the expression
of the making of coils 1 and 2 similar, in the extended sense, being the
simple case to which I referred above. Let a unit current flow in the
circuit of the two coils. Then ^ - m and l2-m are the inductions
through them, and these must be proportional to the resistances,
making therefore the actual inductions through them always the same.
Similarly, if any number of coils be in parallel, exposed to the same
impressed voltage V, with the equations
we have, by solution,
if D be the determinant of the coefficients of the C"s in (9rf), and Nrs the
coefficient of mn in D. So, if C = Cl + C2 + . . . be the total current, we
have
<7=r(2Jv~)/£; therefore Z=D/(2N), .......... (lid)
where the summation includes all the JV's. To reduce Z to the single-
coil form, we require the satisfaction of a set of conditions whose num-
ber is one less than the number of coils.
The simplest way to obtain these conditions is to take advantage of
the fact that, if any number of coils in parallel behave as one, the
currents in them must at any moment be in the ratio of their conduct-
ances. Then, since by
V- T
F-rA=P(m31Cl
are the equations of voltage, when we introduce
into them, we obtain the required conditions : —
The induction through every coil at any moment is the same in amount;
also the voltage due to its variation, and the voltage supporting current,
and the impressed voltage.
294 ELECTRICAL PAPERS.
(5). Impressed Voltage in the Quadrilateral. General Property of a
Linear Network
In my remarks on [p. 271, vol. II.], relating to the behaviour of
batteries when put in the quadrilateral, I, for brevity in an already
long article, left out any reference to the theory. As is well known, in
the usual Christie arrangement (see figure, above) the steady current in
5, due to an impressed voltage in any one of 1, 2, 3, 4, is the same
whether 6 be open or closed, if a steady impressed voltage in 6 give no
current in 5. But the distribution of current is not the same in the
two cases ; so that, when we change from one to the other, the current
in 5 changes temporarily ; as may be seen in making Mance's test of
the resistance of a battery, or by simply measuring the resistance of the
battery in the same way as if it had no E.M.F., using another battery in
6, but taking the galvanometer-zero differently. We, in either case,
have not to observe the absence of a deflection ; or, which is similar,
the absence of any change in the deflection ; but the equivalence of two
deflections at different moments of time, between which the deflection
changes. Hence Mance's method is not a true mil method, unless it be
made one by having an induction-balance as well as one of resistance ;
in which case, if the battery behave as a mere coil or resistance, which
is sometimes nearly true, especially if the battery be fresh, we may
employ the telephone instead of the galvanometer.
The proof that the complete self-induction condition, Z1Z4 = Z2Z3,
where the Z's stand for the generalised resistances of the four sides of
the quadrilateral, when satisfied, makes the current in the bridge-wire
due to impressed force in, for example, side 1, the same whether branch
6 be opened or closed, without any transient disturbance, is, formally,
a mere reproduction of the proof in the problem relating to steady
currents. Thus, suppose
B
where ^ is a steady impressed force in side 1, and A and B the proper
functions of the resistances, in the case of the common Christie, but
without the special condition E^ = R2R3 which makes a resistance-
balance. Then we know that if we introduce this condition into A
and B, the resistance RQ can be altogether eliminated from the quotient
A/B, making C5 due to el independent of J?6.
Now, in the extended problem, in which it is still possible to repre-
sent the equation of a branch by V=ZC, wherein Z is no longer a
resistance, we have merely to write Z for R in the expansion of A/B to
obtain the differential equation of (75; and consequently, on making
Z^4 = Z^ZB, we make A/B independent of ZG. Hence, the current in
the bridge-wire is independent of branch 6 altogether when the general
condition of an induction-balance is satisfied, making branches 5 and 6
conjugate.
But, as is known to all who have had occasion to work out problems
concerning the steady distribution of current in a network, there is a
great deal of labour involved, which, when it is the special state
ON THE SELF-INDUCTION OF WIRES. PART VII. 295
involved in a resistance-balance, is wholly unnecessary. This remark
applies with immensely greater force when the balance is to be a uni-
versal one, for transient as well as permanent currents ; so that the
proper course is either to assume the existence of the property required
at the beginning, and so avoid the reductions from the complex general
to the simple special state, or else to purposely arrange so that the
reductions shall be of the simplest character. Thus, to show that C5 is
independent of branch 6, when there is an impressed voltage in (say)
side 1, making no assumptions concerning the nature of branch 6, we
may ask this question, Under what circumstances is C5 independent of
C6 ? And, to answer it, solve for C5 in terms of e1 and (7C, and equate
the coefficient of C6 to zero.
Thus, writing down the equations of voltage in the circuits
and BjCBgBj in the above figure, we have
el = Z1C1
/ , g ,v
when there is no mutual induction between different branches, but not
restricting Z to a particular form ; and now putting
<74 =
we obtain
which give
C -
(Z,
making C'5 independent of CQ when the condition of conjugacy of
branches 5 and 6 is satisfied.
If there are impressed voltages in all four sides of the quadrilateral,
then (ISd) obviously becomes
c - (
which makes C5 always zero if e^ = e^ e3 = e^ and Z^Z± — Z^Zy As an
example, let e2 = Q, <?4 = 0; then, if there is conjugacy of 5 and 6, and
also
the impressed forces are also balanced. Putting, therefore, batteries in
sides 1 and 3, and letting them work an intermitter in branch 6, we
obtain a simultaneous balance of their resistances and voltages, and
know the ratio of the latter. If self-induction be negligible, we may
take Z as E, the resistance ; if not negligible, it must be separately
balanced.
But should there be mutual induction between different branches,
this working-out of problems relating to transient states by merely
turning R to Z partly fails. We may then proceed thus : — As before,
write down the equations of voltage in the circuits AB1B2A and
296 ELECTRICAL PAPEES.
CB^C, using the six independent inductances of these and of the
circuit CAB2C. Thus,
b - R2C2 +p(m1C1
if there is an impressed voltage in side 1. As before, eliminate C2,
and (74 by (16d), and we obtain
[Hi + E2 +p(ml
which, by solution for C5, gives its differential equation at once in
terms of el and C6. To be independent of (76, we require
(^2-^m16){£3+£4+Xm3+m13)} = (^-pm36){El + E2+p(m1+m.13)}, (23d)
which, expanded, gives us the three equations (6d) again, showing that
C5 depends upon e1 and the nature of sides 1, 2, 3, and 4, subject to
(23d), and of 5, but is independent of the nature of (76 altogether,
except in the fact that the mutual induction between branch 6 and
other parts of the system must be of the proper amounts to satisfy
(23d) or (6d).
The extension that is naturally suggested of this property to any
network whose branches may be complex, and not independent, is
briefly as follows. The equations of voltage of the branches will be of
the form
wherein the Z's are differentiation-operators.
Suppose branches ra and n are to be conjugate, so that a voltage in
m can cause no current in n. First exclude m's equation from (24d)
altogether, and, with it, Zmm. Then write down the equations of
voltage in all the independent circuits of the remaining branches, by
adding together equations (24d) in the proper order ; this excludes the
Ps, and leaves us equations between the e's and all the independent
(7's, but one fewer in number than them. Put the Cm terms on the left
side, then we can solve for all the currents (except Cm) in terms of Cm
and the e's. That the coefficient of Cm in the Cn solution shall vanish
is the condition of conjugacy, and when this happens, Cn is not merely
independent of em but also of Zmm, though not of Zml, Zm^ etc.
I have dwelt somewhat upon this property, and how to prove it for
transient states, because, although it is easy enough to understand how
the current in one of the conjugate branches, say n, is independent of
current arising from causes in the other conjugate branch, m, yet it is
far less easy to understand how, when m is varied in its nature, and
therefore wholly changes the distribution of current in all the branches
(except one of the conjugate ones) due to impressed forces in them, it
does not also change the current in the excepted branch n. Conscien-
tious learners always need to work out the full results in a problem
ON THE SELF-INDUCTION OF WIRES. PART VII. 297
relating to the steady-flow of current before they can completely satisfy
themselves that the property is true.
Note on Part III. Example of Treatment of Terminal Conditions.
Induction-Coil and Condenser.
One of the side-matters left over for separate examination when
giving the main investigation of Parts I. to IV. was the manner of
treatment of terminal conditions when normal solutions are in question,
especially with reference to the finding of the terms in the complete
solution arising from an arbitrary initial state which are due to the
terminal apparatus, concerning which I remarked in Part III. that the
matter was best studied in the concrete application. There is also the
question of finding the nature of the terminal arbitraries from the mere
form of the terminal equation, without knowledge of the nature of the
arrangement in detail, except what can be derived from the terminal
equation.
Let, for example, in the figure, the thick line to the right be the
beginning of the telegraph-line, and what is to the left of it the terminal
apparatus, consisting of an induction-coil and a shunted condenser.
The line is joined through the primary of the induction-coil, of resist-
ance Rv to the condenser of permittance SQJ whose shunt has the con-
ductance /t0, and whose further side is connected to earth, as symbolised
by the arrow-head.* Let R% be the resistance of the secondary coil,
and Lv L^ M the inductances, self and mutual, of the primary and the
secondary. At the distant end of the line, where z = l, we may have
r\AAA/\A
another arrangement of apparatus, also joined through to earth, though
this is not necessary. The line and the two terminal arrangements
form the complete system, supposed to be independent of all other
systems.
Now suppose there to be no impressed voltage in any part of the
system, so that its state at a given moment depends entirely upon its
initial state at the time of removal of the impressed voltage ; after
which, owing to the existence of resistance, it must subside to a state
of zero electric force and zero magnetic force everywhere (with some
* It is not altogether improbable that the arrangement shown in the figure,
with the receiving instrument placed in the secondary circuit, would be of advan-
tage. A preliminary examination of the form of the arrival-curve when this
arrangement is used for receiving at the end of a long cable, with K0=0, yields a
favourable result. But the examination did not wholly include the influence of
the resistances on the form of the curve.
298 ELECTRICAL PAPERS.
exceptional cases in which there is ultimately electric force, though not
magnetic force), the manner of the subsidence to the final state
depending upon the connexions of the system. The course of events
at any place depends upon the initial state of every part, including the
terminal apparatus, which may be arbitrary, since any values may be
given to the electrical variables which serve to fully specify the amount
and distribution of the electric and magnetic energies.
Suppose that F", the transverse voltage, and U, the current in the
line, are sufficient to define its state, i.e. as electrical variables, when
the nature of the line is given, and that u and w are the normal
functions of V and C in a normal system of subsidence. Then, at time
t, we have
r=VAue*, C=2Awept, ..................... (le)
wherein the p'& are known from the connexions of the whole system ;
each normal system having its own p, and also a constant A to fix its
magnitude. The value of A is thus what depends upon the initial
state, and is to be found by an integration extending over every part
of the system. In one case, viz., when the initial state is what could
be set up finally by any distribution of steadily acting impressed force,
we do not need to perform this complex integration, since we may
obtain what we want by solving the inverse problem of the setting up
of the final state due to the impressed force, as done by one method in
Part III., and by another in Part IV. If also the initial state of the
apparatus be neutral, so that it is the state of the line only that
determines the subsequent state, we can pretty easily represent matters,
viz., by giving to A the value
wherein U and W are the initial V and G in the line, whose per-
mittance and inductance per unit length are S and L; so that the
numerator of A is the excess of the mutual electric over the mutual
magnetic energy of the initial and a normal state, whilst the
denominator A is twice the excess of the electric over the magnetic
energy of the normal state itself, which quantity may be either
expressed in the form of an integration extending over the whole
system, or, more simply, and without any of the labour this in-
volves, in the form of a differentiation with respect to p of the deter-
minantal equation. For instance, when we assume L = 0, and we make
the line-constants to be simply Pi and S, its resistance and permittance
per unit length (constants), as we may approximately do in the case of
a submarine cable that is worked sufficiently slowly to make the effects
of inertia insensible, in which case we have
-?-«* -£-•*
so that we may take
- cos
XI
ON THE SELF-INDUCTION OF WIRES. PART VII. 299
if —m2 — RSp] then equation (2e) becomes
where the undefined terms F0 and Yl in the numerator depend upon
the terminal apparatus, and F in the denominator is defined by
which is the determinantal equation arising out of the terminal
conditions
F=ZQC at 2 = 0, and V=Z£ at z = l ..... ....(7e)
(See equations (177) to (180), Part IV.) We have now to add on to
the numerator of A the terms corresponding to the initial state of the
terminal apparatus, when it is not neutral. As the process is the
same at both ends of the line, -we may confine ourselves to the 2 = 0
apparatus, according to the figure. First we require the form of ZQt the
negative of the generalized resistance of the terminal apparatus. It
consists of three parts, one due to the condenser, a second to the
primary coil, and a third to the presence of the secondary ; thus,
-Z^(KQ + S()p)^ + (Rl+L1p)-MY(R2 + L2p)-\ ......... (Se)
showing the three parts in the order stated. Now as shown in Part
III., dZQ/dp expresses twice the excess of the electric over the magnetic
energy in a normal system (when jp becomes a constant), per unit square-
of-current. Performing the differentiation, we have
o_ o r /O.A
dp' (ffo l
Here we may at once recognise that the first term represents twice the
electric energy of the condenser per unit square-of-current, that the
second term is the negative of twice the magnetic energy of the
unit primary current, and that the fourth is similarly the negative of
twice the magnetic energy of the secondary current per unit primary
current; whilst the third, which at first sight appears anomalous, is
the negative of twice the mutual magnetic energy of the unit primary
and corresponding secondary current. Thus, if w0 be the normal
current-function, that is, by (4e), WQ— - (m/R) cos 6, we have
............... <"•>
as the expressions for the normal voltage of the condenser, for the
primary current, and for the secondary current. If then VQ, Cv and
C2 are the initial quite arbitrary values of the voltage of the condenser,
and of the primary and secondary currents, their expansions must be
C -^Aw 0 - y-o (\\e\
fci-M* °2-
300 ELECTRICAL PAPERS.
Also, the excess of the mutual electric over the mutual magnetic energy
of the initial state F0, Cv (72, and the normal state represented by
(We) is
and this is what must be added to the numerator in (5e) to obtain the
complete value of A, if we also add the corresponding expression Yl
for the apparatus at the other end, if it be not initially neutral. Using
this value of A in (\e) and in (lie) with the time-factor e** attached,
and in the corresponding expansions for the other end, we thus express
the state of the whole system at any time.
Since, initially, V is U, and independent of the state of the terminal
apparatus, it follows that in the expansion
the parts of A depending on the apparatus contribute nothing to U, so
that, by (5e) and (12e), we have the identities
for all the values of z from 0 to I.
It may have been observed in the above that the use of (9e) was
quite unnecessary, owing to the forms of the normal functions in (100)
being independently obtainable from our h-priori knowledge of the
terminal apparatus in detail, from which knowledge the form of ZQ in
(Se) was deduced ; so that, without using (9e), we could form (lie) and
(12e). I have, however, introduced (9e) in order to illustrate how we
can find the complete solution, without knowing the detailed terminal
connexions, from a given form of Z. We must either decompose
dZ0/dp into the sum of squares of admissible functions of p, multiplied
by constants, say,
where av a2, etc., are the constants, and /], /2, ... the functions of p-y
or else into the form of the sum of squares and products, thus
When this is done, we know that the terminal arbitraries are
F^VAfw, F2 = ?Af2w» F3 = ?AfBw0, ...(16*)
and that ro = wo{fli^i/i + ^2/2 + ^3/8+ »•} (17e)
in the case (I4e) of sums of squares, wherein the F's may have any
values, assuming that we have satisfied ourselves that they are all
independent ; with the identities
0 = 2X/>, 0 = 2,</>, etc (ISe)
Thus, in the case (9e), the first, second, and fourth terms are of the
proper form for reduction to (14e), but the third is not. We are
ON THE SELF-INDUCTION OF WIRES. PART VII. 301
certain, therefore, that there cannot be more than three arbitraries, if
there be so many. Now, if we do not recognise the connection between
the third term and those which precede and follow it (as may easily
happen in some other case), we should rearrange the terms to bring it
to the form (14e); for instance, thus : —
,lg,
which is what we require. We may then take
Further, we can certainly conclude, provided ax is positive, and a2 and
fl3 are negative, that the first term on the right of (19e) stands for
electric (or potential) energy, and the remainder for magnetic (or
kinetic). It is clear that we may assume any form of Z that we please
of an admissible kind (e.g., there must be no such thing as|>*), find the
arbitraries, and fully solve the problem that our data represent, whether
it be or be not capable of a real physical interpretation on electrical
principles. I have pursued this subject in some detail for the sake of
verifications ; it is an enormous and endless subject, admitting of in-
finite development. Owing, however, to the abstractly mathematical
nature of the investigations — to say nothing of the length to which
they expand, although when carried on upon electrical principles they
are much simplified, and made to have meaning — I merely propose to
give later one or two examples in which circular functions of p are
taken to represent Z.
Although, however, the state of the line at any moment is fully
determinable for any form of the terminal Z's, when they alone are
given, from the initial state of the line, provided the initial values of
the terminal arbitraries be taken to be zero, and although it is similarly
determinable when particular values are given to the arbitraries, whose
later values also are determinable by affixing the time-factor, it does
not appear that this determinateness of the later values of the terminal
arbitraries is always of a complete character, when the sole data relating
to them are the form of Z and their initial values. For it is possible
for a terminal arrangement to have a certain portion conjugate with
respect to the line ; and although the state of the line will not be
affected by initial energy in that portion, yet it will influence the later
values of the other terminal arbitraries. This might wholly escape
notice in an investigation founded upon a given form of Z with un-
detailed connections, owing to the disappearance from Z of terms
depending upon the conjugate portion. In such a case the reduced
form of Z cannot give us the least information concerning the influence
of the portion conjugate to the line. It is as if it were non-existent.
If, however, Z be made more general, so as to contain terms depending
upon the conjugate portion, although they be capable of immediate
elimination from Z, it would seem that the indeterminateness must be
removed.
302
ELECTRICAL PAPERS.
Some Notes on Part IV. Looped Metallic Circuits. Interferences due to
Inequalities, and consequent Limitations of Application.
It is scarcely necessary to remark that, in the investigation of Parts
I. and II. , the choice of a round wire or tube surrounded by a coaxial
tube for return-conductor was practically necessitated in order to allow
of the use of the well-known J0 and JL functions and their complements,
because it was not merely the total current in the wire with which we
were concerned, but also with its distribution. Next, in order that it
should be a question of self-induction, and not one of mutual induction
also, with fearful complications, it was necessary to impose the con-
dition that the wire, tubular dielectric, and outer tube should be a
self-contained system, making the magnetic force zero at the outer
boundary. It is true that no external inductive effect is observable
when the double-tube circuit is of moderate length. But electrostatic
induction is cumulative ; and it is certain that, by sufficiently lengthen-
ing the double tube, we should ultimately obtain observable inductive
interferences. Our investigation, then, only applies strictly when the
double tube is surrounded on all sides, to an infinite distance, by a
medium of infinite elastivity and resistivity.
(Maxwell termed 4?r/c, when c is the dielectric constant, the electric
elasticity. I make this the elastivity : first, to have one word for two ;
next, to avoid confusion with mechanical elasticity; and, thirdly, to
harmonise with the nomenclature I have used for some time past.
Thus :—
Flux.
Conduction-Current
Induction . . .
Displacement . .
Resistivity.
Conductivity.
Inductivity.
Elastivity.
Permittivity.
Resistance.
Conductance.
Inductance.
Elastance.
Permittance.
Force.
Electric.
Magnetic.
Electric.
The elastance of a condenser is the reciprocal of its permittance, and
elastivity is the elastance of unit volume, as resistivity is the resistance
of unit volume, and conductivity the conductance of unit volume.
As for "permittivity" and "permittance," there are not wanting
reasons for their use instead of " specific inductive capacity " (electric),
and " electrostatic capacity." The word capacity alone is too general ;
it must be capacity for something, as electrostatic capacity. It is an
essential part of my scheme to always use single and unmistakable
words, because people will abbreviate. Again, capacity is an unadapt-
able word, and is altogether out of harmony with the rest of the
scheme. Now the flux concerned is the electric displacement, involving
elastic resistance to yielding from one point of view, and a capacity for
permitting the yielding from the inverse ; hence elastance and permit-
tance, the latter being the electrostatic capacity of a condenser. There
are now only two gaps left, viz. for the reciprocals of inductivity and
inductance. " Resistance to lines of force " and " magnetic resistance "
will obviously not do for permanent use.)
ON THE SELF-INDUCTION OF WIRES. PART VII. 303
If this restriction be removed, we have self- and mutual-induction
concerned, and interferences ; or, even if there be no external con-
ductors, we have still the electric current of elastic displacement, and
with it electric and magnetic energy outside the double tube. But,
ignoring these, we have the following striking peculiarities : — Putting
on one side the question of the propagation of disturbances into the
conductors, which is so interesting a one in itself, we find that the
electrical constants are three in number — the resistance, permittance,
and inductance of the double-tube per unit of its length ; whilst the
electrical variables are two — the current in each conductor, and the
transverse voltage. The effective resistance per unit length is the sum
of their resistances, which may be divided between the two conductors
in any ratio ; the permittance is that of the dielectric between them ;
and the inductance is the sum of that of the dielectric, inner, and outer
conductors. Another remarkable peculiarity is, that equal impressed
forces, similarly directed in the two conductors at corresponding places,
can do nothing; from which it follows that the effective impressed
force may, like the effective resistance, be divided between the con-
ductors in any proportion we please.
In Part IV., having in view the rapidly extending use of metallic
circuits of double wires looped, excluding the earth, consequent upon
the development of telephonic communication in a manner to eliminate
inductive interferences, I extended the above-described method to a
looped circuit consisting of a pair of parallel wires. So far as propaga-
tion into the wires is concerned, it is merely necessary that they should
not be too close to one another, to allow of the application of the JQ and
/! functions to them separately. Now suspended wires are usually of
iron, and are not set too close, so that the application is justified. On
the other hand, buried twin wires, though very near one another, are
of copper, and also considerably smaller than the iron suspended wires;
so that the diffusion-effect, though not so well representable \>y the
above-named functions, is made insignificant. Dismissing, as before,
this question of inward propagation, we have, just as in the tubular
case, two electrical variables and three constants, viz. the transverse
voltage, the current in each wire, and the effective resistance, permit-
tance, and inductance.
First of all, let the wires be alone in an infinite dielectric. Then we
have similar results to those concerning the double-tube. The effective
resistance, which is the sum of the resistances of the wires, may be
divided between them in any proportions ; and so may be the effective
impressed voltage. The effective permittance is that of the condenser
consisting of the dielectric bounded by the two wires, the surface of one
being the positive, and that of the other the negative coating. Or, in
another form, the effective permittance is the reciprocal of the elastance
from one wire to the other. In the standard medium, this elastance is,
in electrostatic units, the same as the inductance of the dielectric in
electromagnetic units. Thus,
-, (If)
304 ELECTRICAL PAPERS.
if ?\ and r2 be the radii of the wires, and r12 their distance apart
(between axes), and ^ the inductivity of the dielectric. And
Their product, when in the same units, is v~2, the reciprocal of the
square of the speed of undissipated waves through the dielectric. The
two variables, transverse voltage and current, fully define the state of
the wires, except as regards the diffusion-effect in them, of course, and
an effect due to outward propagation into the unbounded dielectric from
the seat of impressed force, which is made insignificant by the limitation
of the magnetic field (in sensible intensity) due to the nearness of the
wires as compared with their length. To LQ has to be added a variable
quantity, whose greatest value is J/^ + |/x2, if /^ and /x2 are the inducti-
vities of the wires, to obtain the complete inductance per unit length.
So far, then, there is a perfect correspondence between the double-
tube and the double-wire problem. But when we proceed to make
allowance for the presence of neighbouring conductors, as, for instance,
the earth, although there is a formal resemblance between the results in
the two cases, when proper values are given to the constants concerned,
yet the fact that in one case the outer conductor encloses the inner,
whilst in the other this is not so, causes practical differences to exist.
For example, there are two constants of permittance concerned in the
coaxial tube case, that of the dielectric between them, and that of the
dielectric outside the outer tube. But in the case of looped wires there
are three, which may be chosen to be the permittance of each wire with
respect to earth including the other wire, and a coefficient of mutual
permittance. There are, similarly, three constants of inductance, and
two of resistance, and at least two of leakage, viz. from each wire to
earth, with a possible third direct from wire to wire. This is when the
wires are treated in a quite general manner, and arbitrarily operated
upon ; so that there must be four electrical variables, viz., two currents
and two potential-differences or voltages. I have somewhat developed
this matter in my paper " On Induction between Parallel Wires "
[p. 116, vol. I.]; and as regards the values of the constants of capacity
concerned, in my paper " On the Electrostatic Capacity of Suspended
Wires" [p. 42, vol. I.]. As may be expected, the solutions tend to
become very complex, except in certain simple cases. If, then, we can
abolish this complexity, and treat the double wire as if it were a single
one, having special electrical constants, we make a very important
improvement. I have at present to point out certain peculiarities
connected with the looped-wire problem in addition to those described
in Part IV., and to make the necessary limitations of application of the
method and the results which are required by the presence of the earth.
First of all, even though the wires be not connected to earth, if they
be charged and currented in the most arbitrary manner possible, we
must employ the four electrical variables and the ten or eleven electrical
constants as above mentioned. On the other hand, going back to the
looped wires far removed from other conductors, there are but two
ON THE SELF-INDUCTION OF WIRES. PART VII. 305
electrical variables and four constants (counting one for leakage). Now
bring these parallel wires to a distance above the earth which is a large
multiple of their distance apart. The constant S of permittance is a
little increased. The method of images gives
where rlt r.2 are the radii of the wires, r12 their distance apart, sv s2 their
distances from their images, and s12 the distance from either to the
image of the other; but, owing to s^/s^ being nearly unity, the per-
mittance S does not sensibly differ from the value in an infinite
dielectric, or the earth has scarcely anything to do with the matter.*
If, however, the wires be brought close to the earth, the increase of
permittance will become considerable ; this is also the case when the
wires are buried. The extreme is reached when each wire is surrounded
by dielectric to a certain distance, and the space between and surround-
ing the two dielectrics is wholly filled up with well-conducting matter.
Then the permittance S becomes the reciprocal of the sum of the
elastances of the two wires with respect to the enveloping conductive
matter; in another form, the effective elastance is the sum of the
elastances of the two dielectrics. Returning to the suspended wires, if
the earth were infinitely conducting, the effective inductance would be
the reciprocal of S in (3/) with //, written for c, in electromagnetic units,
with ^(/Xj + /x2) added ; whilst, allowing for the full extension of the
magnetic field into the earth, we should have the formula (I/), giving a
slightly greater value. The effective resistance is of course the sum of
the resistances, and the effective leakage-resistance would be the sum of
the leakage-resistances of the two wires with respect to earth, if that were
the only way of getting leakage between the wires, but it must be
modified in its measure by leakage being mostly from wire to wire over
the insulators, arms, and only a part of the poles.
But if there be any inequalities between the wires, differential effects
will result, due to the presence of the earth, in spite of its little influence
on the value of the effective permittance ; whereby the current in one
wire is made not of the same strength as in the other, and the
charge on one wire not the negative of that on the other. The
propagation of signals from end to end of the looped-circuit will not
then take place exactly in the same manner as in a single wire. To
allow for this, we may either bring in the full, comprehensive system of
electrical constants and variables; or, perhaps better, exhibit the
differential effects separately by taking for variables the sum of the
* On the other hand, Mr. W. H. Preece, F.R.S., assures us that the capacity is
half that of either wire (Proc. Roy. Soc. March 3, 1887, and Journal S. T. E. and
E., Jan. 27 and Febr. 10, 1887). This is simple, but inaccurate. It is, however,
a mere trifle in comparison with Mr. Preece's other errors ; he does not fairly
appreciate the theory of the transmission of signals, even keeping to the quite
special case of a long and slowly worked submarine cable, whose theory, or what
he imagines it to be, he applies, in the most confident manner possible, universally.
There is hardly any resemblance between the manner of transmission of currents
of great frequency and slow signals. [See also p. 160, vol. n.]
H.K.P. — VOL. n. u
306 ELECTRICAL PAPERS.
potentials of the wires (taking earth at zero potential) and half the
difference of the strength of current in them, in addition to the differ-
ence of potential of the wires and half the sum of the current-strengths,
which last are the sole variables when the wires are in an infinite
dielectric, or else are quite equal. By adopting the latter course our
solutions will consist of two parts, one expressing very nearly the same
results as if the differential effects did not exist, the other the differ-
ential effects by themselves.
Another result of inequalities is to produce inductive interferences
from parallel wires which would not exist were the wires equal. As
an example, let an iron and a parallel copper wire be looped, and tele-
phones be placed at the ends of the circuit. Even if the wires be well
twisted, there is current in the telephones caused by rapid reversals in
a parallel wire whose circuit is completed through the earth. Again, if
two precisely equal wires be twisted, and telephones placed at the ends
as before, the insertion of a resistance into either wire intermediately
will upset the induction-balance and cause current in the terminal tele-
phones when exposed to interference from a parallel wire. This inter-
ference can be removed by the insertion of an equal resistance in the
companion-wire at the same place. In the working of telephone
metallic circuits with intermediate stations and apparatus, we not only
introduce great impedance by the insertion of the intermediate apparatus,
thus greatly shortening the length of line that can be worked through,
but we produce inductive interferences from parallel wires, unless the
intermediate apparatus be double, one part being in circuit with one
wire, the other part (quite similar) in circuit with the other. In
mentioning my brother's system of bridge-working of telephones (in
Part V.), whereby the intermediate impedance is wholly removed, I
mentioned, without explanation, the cancelling of inductive interfer-
ences. The present and preceding paragraphs supply the needed
explanation of that remark. The intermediate apparatus, being in
bridges across from one wire to the other, do not in the least disturb
the induction-balance, so that transmission of speech is not interfered
with by foreign sounds.
But theory goes much further than the above in predicting inter-
ferences than practice up to the present time verifies. For instance, if
two perfectly equal wires be suspended at the same height above the
ground and be looped at the ends, terminal telephones will not be
interfered with by variations of current in a parallel wire equidistant
from both wires of the loop-circuit, having its own circuit completed
through the earth. But if the loop-circuit be in a vertical plane, so
that one wire is at a greater height above the ground than the other,
there must be terminal disturbance produced, even when the disturbing
wire is equidistant. Similarly in the many other cases of inequality
that can be mentioned.
The two matters, preservation of the induction-balance, and trans-
mission of signals in the same manner as on a single wire, are intimately
connected. If we have one, we also have the other. The limitations
of application of the method of Part IY. may be summed up in saying
ON THE SELF-INDUCTION OF WIRES. PART VIII. 307
that the loop-circuit must either be far removed from all conductors, in
which case equivalence of the wires is quite needless ; or else they must
be equal in their electrical constants. In the latter case the effective
resistance R is the double of that of either wire, and the effective
permittance, inductance, and leakage are to be measured as before
described, whilst the variables are the transverse voltage from wire to
wire and the current in each. But the four electrical constants may
vary in any (not too rapid) manner along the line. And the impressed
force (in the investigations of Part IV.) may also be an arbitrary func-
tion of the distance, provided it be put, half in one wire, half in the
other, oppositely directed in space. For, although equal, similarly
directed impressed forces will cause no terminal disturbance (and none
anywhere if other conductors be sufficiently distant), yet disturbances
at intermediate parts of the line will result. It is true that the most
practical case of impressed voltage is when it is situated at one end
only of the circuit, when it is of course equally in both wires, or not in
them at all ; but there is such a great gain in the theoretical treatment
of these problems by generalising, that it is worth while to point out
the above restriction.
Besides this case of equality of wires, which is precisely the one that
obtains in practice, there are other cases in which, by proper propor-
tioning of the electrical constants of the two looped wires, the induction-
balance is preserved ; and, simultaneously, we obtain transmission of
signals as on a single wire. [But this is not an invariable rule.] Their
investigation is a matter of scientific interest, though scarcely of prac-
tical importance.
I have yet to add investigations by* the method of waves (mentioned
in Part IV.), by which I have reached interesting results in a simple
manner.
PART VIII.
The Transmission of Electromagnetic Waves along Wires without Distortion.
One feature of solutions of physical problems by expansions in
infinite series of normal solutions is the very artificial nature of the
process. If it be a case of subsidence towards a state of equilibrium,
then, if a sufficient time has elapsed since the commencement of the
subsidence to allow the great mass of (singly) insignificant systems to
nearly vanish, leaving only two or three important systems, which may
be readily examined — or merely one, the most important — then the
process is natural enough. It is the early stage of the subsidence
that is so artificially represented, when the resultant of a very large
number of normal solutions must be found before we come to what we
want. Sometimes, too, the full investigation of the normal systems in
detail is prevented by mathematical difficulties connected with the
roots of transcendental equations. This goes very far to neutralise the
advantage presented by the ease with which solutions in terms of
normal functions may be obtained.
308 ELECTRICAL PAPERS.
In some respects these difficulties are evaded by the consideration of
the solution due to a sinusoidal impressed force. The method is very
powerful ; and, by considering the nature of the results through a
sufficiently wide range of frequencies, we may indirectly gain, with
comparatively little trouble, knowledge that is unattainable by the
method of normal systems.
But the real desideratum, which, if it can be reached, is of paramount
importance, is to get solutions which can be understood and appreciated
at first sight, and followed into detail with ease, presenting to us, as
nearly as possible, the effects as they really occur in the physical
problem, disconnected from the often unavoidable complications due to
the form of mathematical expression. To illustrate this, it is sufficient
to refer to the elementary theory of the transmission of waves without
dissipation along a stretched flexible cord. If we employ Fourier-series,
we are doing mathematical exercises. But only use the other method,
in which arbitrary disturbances are transferred bodily in either direction
at constant speed, e.g., u= ,, _ ^
and we get rid of the mathematical complications, and can interpret
results as we see their physical representatives in reality — for instance,
when we agitate one end of a long cord.
Now there is one case, and, so far as I know at present, only one, in
the many-sided question of the transmission of electromagnetic disturb-
ances along wires, which admits of this simple and straightforward
method of treatment. Singularly enough, it is not by the simplifying
process of equating to zero certain constants, and so ignoring certain
effects, that we reach this unique state of things, but rather the other
way, generalising to some extent. It is usual to ignore the leakage of
conductors, sometimes also the inductance, and sometimes the per-
mittance. But we must take all the four properties into account which
are symbolised by resistance, leakage-conductance, inductance, and per-
mittance, to reach the much-desired result. Briefly stated, the effects
are these, roughly speaking. If there be only resistance and per-
mittance, there is, when disturbances of an irregular character are sent
along a long circuit, both very great attenuation and very great dis-
tortion produced. The distortion at the end of an Atlantic cable is
enormous. Now if we introduce leakage, we shall lessen the distortion
considerably, but at the same time increase the attenuation. On the
other hand, if we introduce inductance (instead of leakage) we shall
lessen the attenuation as well as the distortion. And, finally, if we
have both leakage and inductance, in addition to resistance and per-
mittance, we may so adjust matters, by the effects of inductance and of
leakage being opposite as regards distortion, as to annihilate the dis-
tortion altogether, leaving only attenuation. The solutions can now be
followed into detail in various cases without any laborious and round-
about calculations. Besides this, they cast much light upon the more
difficult problems which occur when not so many physical actions are
in question.
In my usual notation, let E, L, S, and K be the resistance, inductance,
ON THE SELF-INDUCTION OF WIRES. PART VIII. 309
permittance, and leakage-conductance of a circuit, per unit length, all
to be treated, in the present theory, as constants ; and let V and C be
the transverse voltage and the current at distance z. The fundamental
equations are
............. (Ig)
p standing for d/dt. Here C is related to the space-variation of Vir\
the same formal manner as is V to the space-variation of C. This
property allows us to translate solutions in an obvious manner, and
gives rise to the distortionless state of things. Let
LStf = l, and E/L = K/S=q ................ (20
The equation of Fis then
and the complete solution consists of waves travelling at speed v with
attenuation but without distortion. Thus, if the wave be positive, or
travel in the direction of increasing z, we shall have, iff^z) be the state
of V initially,
(5g)
If Vy C2 be a negative wave, travelling the other way,
(70
Thus, any initial state being the sum of V^ and V^ to make Vt and of
Cl and (?2 to make (7, the decomposition of an arbitrarily given initial
state of V and C into the waves is effected by
r^Mr+LvC), V^\(V-LvV) ................ (80
We have now merely to move V^ bodily to the right at speed v, and F"2
bodily to the left at speed 0, and attenuate them to the extent e~gt, to
obtain the state at time t later, provided no changes of conditions have
occurred. The solution is therefore true for all future time in an
infinitely long circuit. But when the end of a circuit is reached,
a reflected wave usually results, which must be added on to obtain the
real result.
In any portion of a solitary wave, positive or negative, the electric
and magnetic energies are equal, thus
|iC? = JffF? ............................... (90
The dissipation of energy is half in the wires and half without, thus
(100
When a positive and a negative wave coexist, and energies are added,
cross-products disappear. Thus the total energy is always
or L(C! + CS); ............... (110
310 ELECTRICAL PAPERS.
the total dissipativity is always
, or
and the total energy-flux is always
The relation V^LvC^ is equivalent to C1 = SvFl; i.e., a charge SF
moving at speed v is the equivalent of a current C of strength equal to
their product. But it is practically best to employ Lvt the ratio of the
force V to the flux C being then at once expressible or measurable in
ohms. For v is 30 ohms, and L is a convenient numeric, say from 2 up
to 100, according to circumstances. Z = 20 is a convenient rough
measure in the case of a pair of suspended copper wires. This makes
our critical impedance 600 ohms. It must not be confounded with
resistance, of course, though measurable in ohms. The electric and
magnetic forces are perpendicular. It is the total flux of energy which
is expressed by the product VG, not the dissipativity.
Regarding v, its possible greatest value is the speed of light in wcuo.
AY lien there is distortion also, making the apparent speed variable, it
does not appear that under any circumstances the speed can exceed v.
Now the classical experiments of Wheatstone indicated a speed half as
great again as that of light. Would it not be of scientific interest to
have these important experiments carefully repeated, on a straight
circuit (as well as of other forms), to ascertain whether, on the straight
circuit, the speed is not always less than, rather than greater than, that
of light, and whether there was any difference made by curving the
circuit ]
The following remark may be useful. In treatises on electro-
magnetism by the German methods, a current-element and its properties
of attraction, repulsion, etc., occupy an important place. It is, how-
ever, quite an abstraction, and devoid of physical significance when by
itself. But the current-element in our theory above, ssLy.V=V1 con-
stant through unit distance, C= V^Lv through the same unit distance,
F'and C zero everywhere else, is a physical reality (with limitations to
be mentioned). It is a complete electromagnetic system of itself, with
the electric currents closed. To fix ideas most simply, the two con-
ductors may be a wire with an enveloping tube separated by a dielectric,
and by our current-element we imply a definite electric field, magnetic
field, and dissipation of energy, which can exist apart from all other
current-elements. It is only an abstraction in this quite different
sense, that we could not really terminate the element quite suddenly,
and that in the process of travelling it must be distorted from causes
not considered in our fundamental equations, one cause being the
diffusion of current in the conductors in time, which alone serves
to prevent the propagation of an abrupt wave-front, either in our
distortionless system, or when there is marked distortion. Even
assuming that Maxwell's representation of the electromagnetic field is
not correct, there seems to me to be very marked advantage in assum-
ing its correctness, even as a working hypothesis, from its exceeding
physical explicitness in dynamical interpretation, without specifying a
ON THE SELF-INDUCTION OF WIRES. PART VIII. 31 1
special mechanism to correspond. AVe have also the inimitable advan-
tage of abolishing once for all the speculations about unclosed currents,
and the insoluble problems they present. In Maxwell's scheme currents
always close themselves, and cannot help it.
It will be seen that our waves, in the above, do not in any way differ
from plane waves of light (in Maxwell's theory), save in being attenuated
by dissipation of energy in the dielectric (when it is a tubular conducting
dielectric bounded by a pair of conductors that is in question), and also
in the bounding conductors, and in being practically of quite a different
order of wave-length. The lines of energy-flux are parallel to the wires,
(a wave simply carries its energy with it, less the amount dissipated) ;
these are also the lines of pressure, for the electrostatic attraction equals
and cancels the electromagnetic repulsion. The variation of the pres-
sure constitutes a mechanical force, half derived from the electro-
magnetic force, half from the magneto-electric force. Here, however,
I am bound to say I cannot follow readily. If this mechanical force
exist, there must be corresponding acceleration of momentum ; if it do
not exist, or be balanced, the stress supposed is not the real stress,
though it may be a part of it. Again, if it be the real stress, and there
be the corresponding acceleration of momentum, this is equivalent to
introducing an impressed force (mechanical), and it must be allowed for.
The matter is difficult all round. Yet Maxwell's stresses, assumed to
exist in the fluid dielectric between conductors, account perfectly for
the forces between them, when the electric and magnetic fields are
stationary. But when they vary, then the region of mechanical force
due to stress-variation extends into the dielectric medium. As for
Maxwell's stress in a magnetised medium, there are so many different
arrangements of stress that will serve equally well, that I cannot have
any faith whatever in the special form given by Maxwell
It is also well to remember that we are not exactly representing
Maxwell's scheme, but a working simplification thereof. The lines of
energy-transfer are not quite parallel to the conductors, but converge
upon them at a very acute angle on both sides of the dielectric. Only
by having conductors to bound it of infinite conductivity can we make
truly plane waves. Then they will be greatly distorted, unless we at
the same time remove the leakage by making the dielectric a non-
conductor instead of a feeble conductor ; when we have undissipated
waves without attentuation or distortion.
Properties of the Distortionless Circuit itself, and Effect of Terminal
Reflection and Absorption.
Now to mention some properties of the distortionless circuit. A pair
of equal disturbances, travelling opposite ways, on coincidence, double V
and cancel C. But if the electrifications be opposite, /^is annulled and
C doubled on coincidence.
On arrival of a disturbance at the end of a circuit, what happens
depends upon the connections there. One case is uniquely simple.
Let there be a resistance inserted of amount Lv. It introduces the
312 ELECTRICAL PAPERS.
condition V=LvC if at say B, the positive end of the circuit, and
V— - LvC if at the negative end A, or beginning. These are the
characteristics of a positive and of a negative wave respectively ; it
follows that any disturbance arriving at the resistance is at once
absorbed. Thus, if the circuit be given in any state whatever, without
impressed force, it is wholly cleared of electrification and current in the
time l/v at the most, if I be the length of the circuit, by the complete
absorption of the two waves into which the initial state may be
decomposed.
But let the resistance be of amount 7^ at say B ; and let V-^ and V2
be corresponding elements in the incident and reflected wave. Since
we have
we have the reflected wave given by
• T»<
(15?)
If Ml be greater than the critical resistance of complete absorption, the
current is negatived by reflection, whilst the electrification does not
change sign. If it be less, the electrification is negatived, whilst the
current does not reverse.
Two cases are specially notable. They are those in which there is
no absorption of energy. If 7^ = 0, meaning a short-circuit, the
reflected wave of V is a perverted and inverted copy of the incident.
But if Rl = oo , representing insulation, it is C that is inverted and
perverted.
After reflection, of course, we have the original wave travelling to
the absorber or absorbing reflector, or pure reflector, and the reflected
wave coming from it. Let p0 be the coefficient of attenuation at A,
and p: at B, these being the values of the ratio of the reflected to the
incident waves at A and at B, which may be + or - , due to terminal
resistances (without self-induction or other cause to produce a modified
reflected wave ; some of these will come later) : and let p be the
attenuation from end to end of the circuit (A to B or B to A), viz.,
Then an elementary positive disturbance F0 starting from A becomes
attenuated to pVQ on reaching B; becomes p^V^ by reflection at B;
travels to A, when it becomes pVi^oJ *s reflected, becoming p^p-j^V^}
and so on, over and over again, until it becomes infinitesimal, by the
continuous dissipation of energy in the circuit, and the periodic losses
on reflection. But if the circuit have no resistance and no leakage,
and the terminal resistances be either zero or infinity, there is no
subsidence, and the to-aud-fro passages with the reversals at A and
B continue for ever.
If an impressed force e be inserted anywhere, say at distance zv it
causes a difference of potential of amount e there, which travels both
ways ( + \e, to the right, and - \e to the left) at speed v, with the
ON THE SELF-INDUCTION OF WIRES. PART VIII. 313
proper attenuation as the waves progress. That is, taking for simplicity
the zero of z at the seat of impressed force, we set up a positive wave
F1= J"-^', (170)
and a negative wave V2 = - \e c+*ZILv ; (1&7)
these being true when z is less than vt in the first, and - z is less than
vt in the second. On arrival at A and B these waves are reflected in
the manner before described. It will be understood that the original
waves still keep pouring in, so long as e is kept on. By successive
attenuations we at length arrive at a steady state, which is that cal-
culable by Ohm's law, allowing for leakage.
If the impressed force be at A, and the circuit be short-circuited
there, making /o0= - 1, the two initial waves are converted into one,
thus,
77" _ a f-fo/Lv /I Q~\
ri-et , (iy#7
true when z is not greater than vt. On arrival at B, if the resistance
there be Lv, nothing more happens, i.e., (190) is the complete solution.
This is something quite unique in its way. If e at A vary in any
manner with the time, the current at B varies in the same manner at
a time l/v later. Thus, if e=f(t), the current at B is
But if we short-circuit at B, we superimpose first a negative wave
F2= -ep.€-R(l-t)ILv = -ep^.^ILv, (210)
beginning at time l/v and travelling towards A ; then at time 2l/v add a
positive wave
F3=V.€-^>, : (220)
and so on, ad inf., settling down to the steady state.
The Fourier-series solution in this case (got by the method of
Part IV.) is
Rz Rz
p- p~l " T^V J q2 + vV
This includes the whole process of setting up the final state, but
requires laborious examination to extract its real meaning, which we
have already described, (m goes from TT, 27r, STT, ... , up to <x> .) When
the summation vanishes, we have left the term independent of t, of
which the positive part is the sum of the positive waves Fj, Fg, etc..
and the negative is the sum of the negative waves F"0, etc., above
((190), (210, (220>
The uniquely simple case of complete absorption at B of the first
wave is much more troublesome by Fourier-series than is the really
more complex (230) case. In some other cases in which we can by the
method of waves solve completely, and in a rational manner, the
Fourier-series are difficult to interpret.
Let us construct the complete solution when the terminal resistances
314 ELECTRICAL PAPERS.
have any values ; by (150) we know p0 and plt and by (160) we express
p. First of all we have the positive wave
^ = ^(1-^)6-^, ............................ (240)
true when z is not greater than vt. When t = l/v it is complete, and
remains on. Then begins
travelling towards A, when it is complete and remains on. The third
wave then begins : —
which reaches B at time t = 3//0, and remains on. The fourth wave
then starts : —
reaching A at time il/v ; and so on. We thus follow the whole history
of the establishment of the final state. The resultant positive wave is
the sum of V-^ V^ ... , and the resultant negative wave the sum of V^
V^ ... , which are in geometrical progression ; so that finally we have
In the positive component-waves the current is got by dividing V by
Lv, and in the negative waves by - Lv, so that we get the resultant
final current by dividing Fin (280) by Lv and changing the sign of the
second term, Expressing the negative waves of V.
Should L and S have their values changed in any way, the final state
(280) will be unaltered, but the manner in which it is established will
not be the same, of course. We can, however, form a very fair idea of
the process from the above, when RjL is not greatly different from K/S,
especially if the circuit be sufficiently short to make the attenuation
p be not great.
The case of no resistance is peculiar. There is no steady state if
there be no resistance to make the to-and-fro waves (which may be
regarded as a single wave overlapping itself) attenuate. Thus, if there
be short-circuits at A and B, and also R = 0, K= 0, the first wave due
to e at z = 0 is
^ = 0 from 2 = 0 to z = vt.
Then, when this is completed, we have to add on the reflected wave
F"2 = - e from z = I to z = 21 - vt,
so that when B is reached, there is no electrification left. This is a
period, and the state of electrification repeats itself in the same way.
But the current doubles itself the moment the first wave reaches B, and
the region of doubled current then extends itself to A, where it is at
once increased to a trebled value ; and so on, ad inf., every reflection
adding e/Lv to the current. Thus the current in time mounts up
infinitely, though never becoming permanently steady at any spot.
The least resistance anywhere inserted will cause a settling down to (or
mounting up to) a final steady current.
ON THE SELF-INDUCTION OF WIRES. PART VIII. 315
Effect of Resistances and Conducting Bridges Intermediately Inserted.
Let us now examine the effect of an intermediately inserted
resistance r. (If the circuit be a double wire, then, in accordance
with the Section on Interferences in Part VII., half the resistance
should be put in one wire, and half in the other, just opposite.)
Let a wave be going towards r, and let Vv V^ and VB be corre-
sponding elements in the incident, reflected, and transmitted waves.
As we have
3,
and Fj and Vz are positive waves, whilst V2 is a negative wave, there-
fore
rjr^l+r/ZLv)-*, ....................... (300)
and ^=^+^
From (310) we see that an element of the original wave, on arriving at
the resistance, is divided into two parts, both of the same sign as regards
electrification, of which one goes forward, the other backward, increasing
the electrification behind. The attenuation caused by the resistance
is expressed by (300). If there be n resistances r, such that nr = Rz,
equidistantly arranged, the attenuation produced in the distance z will
be the nth power of the right member of (300), and in the limit, when
the resistances are packed infinitely closely, each being infinitely small,
the attenuation in distance z becomes
(320)
This, it will be observed, is when there is no leakage. R is the resist-
ance per unit length, uniformly distributed.
Now consider the effect of a bridge of conductance kt in the absence
of resistance in the wires, or of uniform leakage. We now have
v + v = y , i
c\ + c2=cl'+kr3, r
if Fj, F2, F3 be corresponding incident, reflected, and transmitted
elements. Consequently
ra/r1-(i+*/2,&)-i, ..................... (340)
and C =
Compare with (300), (310). Observe the changes from voltage to
current, inductance to permittance, and resistance to conductance. It
is the current that now splits without loss, (like the charge before), so
that the reflected electrification is negative, if the incident be positive.
The attenuation in distance z due to uniformly distributed leakage-
conductance K per unit length is therefore
We may infer from this opposite behaviour of a resistance in the
main circuit, and of a bridge across it, that if r/L = k/S, there will be
316 ELECTRICAL PAPERS.
no reflected wave. We must, however, see whether combining the
resistance and bridge does not alter the nature of the result. When
the resistance r and the bridge of conductance k coexist at the same
spot, we shall have
F1+r2=(i+r/i.)r3, \ ,36.
fi -r,-r,+ (F, + ?-,)*/,&,/••
whence r»- «•-(*/&)(- + £•) ,37(.x
T-r + ZLv + ( -
So the reflected wave is annulled when
or by r/L = k/S when r and k are infinitely small. When this happens,
the attenuation is
^^-(l+r/Z*)-!, ........................ (390
and, therefore, when R and K are uniformly distributed,
is the attenuation in distance z. We have thus a complete electrical
explanation of the distortionless system ; reflection due to conductance
in the dielectric itself is annulled by reflection due to the boundary
resistance (of the wires). If there be no leakage, any travelling
isolated disturbance will cast a slender tail behind it, whose electrifica-
tion is similarly signed to that of the nucleus, whilst the current in the
tail points to its tip. On the other hand, if there be leakage, but no
resistance in the wires, the travelling disturbance will cast off a tail of
a different kind, viz., of the opposite electrification to the nucleus, and
of the same current as in the nucleus. And when the resistances in the
wires and in the dielectric are properly balanced, the formation of tails
is prevented altogether.
From this manner of viewing the matter we can get hints as to the
solution of other and more difficult partial differential equations than
the one we are concerned with. Keeping to it, however, we may
somewhat generalise it by making the attenuation-rate a function of
the distance, and also the speed, but managing so that there shall be no
tailing. Thus, it is clear that if L and S be constant, whilst R and K
are functions of z such that their ratio is constant, the speed will be
constant, and there will be no tailing, whilst the attenuation in distance
z — ZQ will be
exp ~
Now if we make the speed also variable, we must inquire how to
prevent tailing due to what is equivalent to a change of medium, as
when light goes from air into glass perpendicularly. The condition
that there be no reflected ray is yu,^ = fj,2v2 in that case, ^ and /*2 being
the inductivities, and v^ and v2 the speeds. In our present case it is
Lft = Lzv2 when the wires and the dielectric have no resistance and no
ON THE SELF-INDUCTION OF WIRES. PART VIII. 317
conductance respectively; Lv vl being the values on one side, L2, v2
those on the other side of the discontinuity. That is, the quantity Lv
must not vary with z, if there is to be no tailing.
We should, however, make sure that this is the condition when we
have simultaneously L, S, R, and K in operation. Let, then, r and k
be the resistance in the main circuit, and the conductance of a bridge
across it, at a place where the main circuit changes in inductance and
permittance from L, S to Z/, Sft the main circuit being supposed to
have itself no resistance or leakage. Let V^, V^ and F"3 be corre-
sponding elements of an incident, reflected and transmitted wave.
We have, by common electrical principles, united with the properties
T- ±LvC,
from which
There is no reflected wave when the numerator on the right of
20) vanishes, or when
r -, k . Lv , rk
and then Fg/Fi^O +r/W)-1 ......... : ..................... (450)
So, if we take Lv = L'vf, we secure the desired result, because the product
rk ultimately vanishes when we distribute resistance and conductance
continuously. That is to say, if Lv does not vary, and ft/L = K/S
always, there will be no tailing, the speed will be a function of z, viz. :
and the attenuation-rate will be a function of z, as indicated by (400).
To verify, observe that our fundamental equations (1) may be
written, if E/L = KjS,
hence, if Lv be constant, we have
which become identical if V= ±LvC, indicating a complete satisfaction
when q and v are functions of z. Then
are the equations of positive or negative waves.
318 ELECTRICAL PAPERS
Approximate Method of following the Growth of Tails, and the
Transmission of Distorted Waves.
The substitution of isolated resistances and conducting bridges for
continuously distributed resistance and leakage leads to a very easy
way of following the course of events when there is distortion by
a want of the balance between the resistance in the main circuit and
the leakage which is required to wholly remove the distortion. As
may be expected, the results are only rough approximations, but the
method is so easy to follow, and gives so much information of a rough
kind, that it is worthy of attention. The subject is quite a large one
in itself, and would need a large number of diagrams to fully illustrate.
I shall therefore only briefly indicate the nature of the process.
Suppose there is no leakage whatever. Then, unless the resistance
in the main circuit be low, there will usually be much distortion due to
tailing, unless the waves be of great frequency, making E/Ln small.
The smaller this quantity is, by either reducing R, or increasing L or
the frequency, the nearer do we approximate to a state of little
distortion, and to attenuation represented by
€-Xz/2Lv
in the distance z. In fact, in long-distance telephony we do not need
any excessive leakage to bring about an approximation to the state of
things which prevails in our distortionless system (where, however,
disturbances of any kind, not merely waves of veiy great frequency, are
propagated without distortion), and the attenuation is of course less
than when there is leakage. As this, however, would require us to
examine the sinusoidal solutions of Parts II. and V., we may now keep
to the question of tailing and its approximate representation.
Let it be required to find how a charge, initially given existent in a
small portion of the circuit, and at rest, divides, when left to itself.
We know that if there were no resistance, it would immediately
separate into equal halves, which would travel with speed v in opposite
directions without attenuation or distortion. And, if there be resist-
ance, but accompanied by proper leakage to match, the same thing will
happen, with attenuation. Now there is to be no leakage ; this keeps
the total charge unchanged. If then there were no tailing there would
be no attenuation. But the charges, on separation, cast out slepder
tails behind them, so that they are joined by a band (the two tails
superimposed). The heads, therefore, or nuclei, are attenuated, besides
being distorted; the loss of charge from them is to be found in the tails.
It is sufficient to consider the progress of one of the two halves of the
initial disturbance, say that which moves to the right, and the tail it
casts behind it.
Localise the resistance at points, between which there is no resist-
ance, and let the attenuation in passing each resistance (equidistantly
placed) be any convenient large proper fraction, say -^ ; though this is
scarcely large enough it is convenient, as all operations will consist in
multiplications by 9 and simple additions. Let the initial charge,
moving to the right, be 10,000, extending uniformly over a complete
ON THE SELF-INDUCTION OF WIRES. PART VIII. 319
section between two resistances, and let a be the time taken to travel
one section. Then first we have
->
10,000 ;
-<- ->
1,000, 9,000 ;
-<- -> ' -«- ->
900, 100, 900, 8,100;
•<- ->-<--> •«- ->
810, 90, 820, 180, 810, 7,290.
The figures in the successive lines show the distribution of the charge
in the consecutive sections to right and left, initially and after intervals
a, 2a, 3a, etc. First of all ~$ of the initial charge passes into the next
section to the right, and the other y1^ is reflected back by the resistance
to where it was at the beginning. Then these two charges similarly
divide, -^ of each going forward, the other y1^ backward. The arrows
indicate the direction of motion of a charge. All subsequent operations
consist in pairing the charges which are moving towards one another in
the proportions T9^ and y1^. After seven operations we have this
result : —
•<- ->
531, 59, 566, 120, 583, 184, 591, 245, 583, 302, 565, 371, 530, 4773;
so that more than half the original charge is in the tail. The directions
of motion are alternately to left and to right, so that it is only necessary
to know this, and not to continue drawing the arrow-heads. The
currents are alternately + and - .
But we should, to approach reality, extend the original charge at
least over two sections, instead of one only. To do this, we have
merely to add each of the numbers to the one following it. After
seven operations, therefore, an initial charge of 20,000 extending over
two sections, and moving to the right, becomes distributed thus : —
531, 590, 625, 686, 703, 767, 775, 836, 828, 885,867, 936,901,5303,4773;
which is really something like its distribution when the resistances are
uniformly spread. The corresponding current is not represented by
these figures, of course, owing to the opposite direction of current in
alternate segments when the original charge extended over only one
segment. Allowing for this fact, the current, after seven operations,
due to 20,000 over two sections initially, is represented by
-4- -<-.-»-.'-*•
531, 472, 507, 446, 463, 399, 407, 346, 338, 281, 263, 194,169,4243,4773.
In the head the current is positive. In the whole of the tail (repre-
sented by the small numbers) the current is negative. We see that
the division of the initial charge over two sections has not been
sufficient to remove the fluctuations wholly, though the reversals have
disappeared.
In course of time, if the circuit be sufficiently long, the nucleus is so
attenuated as to practically make the charge one long tail stretching
320 ELECTRICAL PAPERS.
out both ways, and tending to do so equally, so that the greatest V-
disturbance is at or near the origin to the right of it. The current is
then negative in the hinder part and also in a portion of the forward
part, and positive in the rest. That is, the region of positive current
extends gradually from the nucleus into the tail.
Now pass to the other kind of tail, due to reflection by leakage.
If there be no resistance in the circuit, but uniform leakage instead, we
have tailing and distortion of a distinct kind. It is the current-element
that splits into two parts, one going forward, the other backward on
passing a bridge, whilst the electrification in the reflected wave is the
negative of that in the incident. If, then, the attenuation be ^ as
before (ratio of transmitted to incident wave), at every one of the
isolated conducting bridges which we use to replace uniformly dis-
tributed leakage-conductance, we shall have the same results as above
precisely, except that current takes the place of transverse voltage.
Thus the first row of figures (after seven operations) shows the current
distribution (everywhere positive) due to an initial charge 10,000 (with
corresponding current as before) extending over one section ; the second
row that due to 20,000 over two sections; and the third row the
corresponding distribution of electrification, positive in the head, and
negative in all the rest. Observe that as, when there was no leakage, the
line-integral of V remained constant, so now that there is leakage, the
line integral of C remains constant. In one case it is really conserva-
tion or persistence of the electrification l&Pft*; in the other, of the
momentum \LCdz. In the one case the momentum-integral subsides,
the time-factor being e~Kt!L • in the other the electrification-integral
subsides, the time-factor being c~Xil8. In both cases the energy sub-
sides towards zero, in spite of the persistence of electrification or of
momentum.
When we have both resistance in the conductors and leakage, the
tail is positive or negative (referring to the electrification), according as
RjL is greater or less than K/S. The latter case is quite out of
ordinary practice, which aims at high insulation; the results are con-
sequently very singular, when considered in more detail, which cannot
be done now.
In a somewhat similar manner to that in which we have roughly
followed the growth of tails, we may follow the progress of signals
through a circuit, and obtain the arrival-curves of the current at the
distant end, or rather, we may obtain curves resembling the real ones
somewhat by drawing curves through the zigzags which result. The
method has no recommendation whatever in point of accuracy : its real
recommendation lies in the facility with which a general knowledge of
the whole course of events may be obtained, and I daresay some
people may think that of not insignificant moment.
To make the method intelligible, without going into detail elaborately,
let the circuit be perfectly insulated, and in only seven sections, at each
of the six junctions of which is concentrated one-sixth part of the
ON THE SELF-INDUCTION OF WIRES. PART VIII. 321
resistance of the real circuit. The results will now depend materially
upon the ratio RljLv, whether it be a large number, or small. First,
let it be small, say Rl = ^Lv. The attenuation at each resistance (Rl/Q)
is then T9g- as before. Let us also insert resistances of amount Lv at
both ends, to stop reflections and complications. Then, starting with
10,000 in the first section, we proceed thus : —
->
A. 10,000;
•<- •>
1,000, 9,000 ;
->
0, 900, 8,100;
•<- ->
810, 90, 810, 7,290;
0, 738, 162, 729, 6,561 ;
-<- ->
664, 74, 672, 219, 656, 5,905;
0, 612, 134, 612, 262, 590, 5,314; B.
•+•
551, 61, 564, 181, 557, 295, 0;
0, 514, 112, 520, 219, 29, 266.
If a = time of going one section, this gives the whole history of the
circuit from the moment of putting on a steady impressed force at A up
to 9a, or 2a after commencement of arrival of the current at B. The
calculation is precisely that by which we should calculate (by the
previously described method) the progress of a charge 10,000 initially
in the first section and moving to the right. In time a, 9,000 goes
forward to the second section, 1,000 is reflected back. After another
step the 1,000 is absorbed, whilst T9^ of the 9,000 goes forward, and 1\)-
is reflected back. This brings us to the third line. The first arrival at
B is of 5,314, the second of 266, and so on (not carried further). The
sum total of all the arrivals at B when carried further is 5,999, which
really means 6,000. That is, -^ of the charge would go out at B and
y4^ at A. Now the same figures serve with the impressed force,
which we have to imagine continuously sending into the first section
the 10,000 wave. The real state of electrification of the line at any
stage is to be found by summing up the columns, and the real state of
current by summing up the columns with allowance made for the fact
that all charges moving to the left mean negative currents. Thus the
current at A falls to its final strength, whilst at B it rises to it. Of
course the current would not really arrive at B in a perfectly sudden
manner to |-| of its final strength, though it would arrive far more
suddenly than the current arrives at the end of an Atlantic cable. The
final current is (e/2Lv) x -6. If we increase the number of sections so
greatly that the first arrival at B is insensible, then the arrival-curve
will resemble that at the end of an Atlantic cable (or even much shorter
cables). The value of e~Kl/Lv is exceedingly small in such a case.
H.E.P. — VOL. ii. x
322 ELECTRICAL PAPERS.
Now if we short-circuit at A and B the process is essentially the
same, although we must not absorb all reflected waves arriving at A,
and all transmitted waves arriving at B, but reflect them properly.
This causes there to be a sort of bore running to and fro, in addition to
the regular action, so that the arriving current at B gives a sudden
jump at regular intervals 2l/v apart; these jumps get smaller and
smaller rapidly at each repetition, of course. But should the circuit be
so long that the first increment of current at B is insensible, this jump-
ing cannot occur. It is also to be remarked that the insertion of
terminal resistances stops the oscillatory action.
It was my intention to have given the equations of the tails, positive
or negative, or mixed, but as the investigation would unduly extend
the length of the present communication, I propose to consider the tails
in the next Part IX. At present I may remark that the equation is in
the form of a series of rising powers of (vt + z), true when ±z<vt ; this
gives the results very simply in the early stages of development. But
later on, it is desirable to transform first into powers of z multiplied
into Bessel's functions of the time, and then into other forms, working
down to inertialess solutions.
Conditions Regulating the Improvement of Transmission.
The general lines to be followed to improve the capabilities of
telegraph or telephone circuits (long-distance) for getting signals
through with the least distortion and least attenuation combined are
these. First of all RjL is usually far greater than K/S. We should
therefore reduce M/L and increase K/S. The former may be done by
either reducing the resistance or by increasing the inductance, or by
both together. This will lessen both the attenuation and the distortion.
So remarkable is this effect, that without changing either the resistance
or the permittance of an Atlantic cable, we could, by increasing the
inductance (with sinusoidal currents), make the current-amplitude at B
be nearly twice as great as the full strength of steady current (the
doubling being due to absence of terminal resistance). It is scarcely
necessary to remark that it is wholly impracticable to go anything like
so far as this ; the illustration serves however to show the extraordinary
range of possibilities implied in a single theory. The other way is to
increase K and reduce S, or both together. By increasing the leakage-
conductance we lessen the distortion, but at the same time increase the
attenuation. Thus, if the resistance and the permittance be fixed, we
should increase the inductance as much as possible, and then increase
the leakage-conductance until the attenuation goes as far as is permiss-
ible. We shall then have the least distortion possible with the given
resistance and permittance. (It is, however, assumed that we are only
approximating towards equalizing E/L and K/S, whilst RjL still remains
the larger, as, for instance in the case of a very long cable.)
It seems very probable that the iron-sheathing of a submarine cable
may be beneficial, though it is not at all easy to precisely state its full
effect. But it is naturally suggested to increase the inductance by the
use of an irony insulator. In Part VI. I described the use of non-
ON TELEGRAPH AND TELEPHONE CIRCUITS. 323
conducting iron to demonstrate the strict proportionality of magnetic
force to induction variations when the range is small. This was an
insulator impregnated with iron dust, and it shows, with small range of
magnetic force (with which alone we are concerned in signalling) no
sign of increased resistance, which is to be avoided, >( course, since we
require the lowest possible resistance to reduce attenuation and dis-
tortion. It is possible, therefore, that such an insulator might be of
great service in cables for telephony and telegraphy, especially as its
insulation-resistance could not be so high as is ordinarily the case. The
changed permittance must also be allowed for, though.
As regards open wires, if of copper, and of low resistance, good
telephony is possible to ridiculously great distances, further than any
one wants to speak, without troubling about getting the leakage to be
large.
There is a value of L which gives the least attenuation. For since, in
the distortionless system, the received current is
if short-circuited at A, but with resistance Lv at B ; or one half this
amount, if there be resistance Lv both at A and at B, we see that
fil = Lv, ................................. (51?)
makes CB a maximum. But the attenuation is then so trifling that to
carry this out (by increasing L) would be, if possible, quite unnecessary
in the case of a long circuit.
Again, in the case of no leakage at all, it may be shown by an
examination of the sinusoidal solution in Part V., that if RjLn be small,
we approximate towards the same formula but with the index - Rl/'2Lv,
sothat J8-2Z. ............................... (620)
gives the value of Lv which makes the current received at B a maximum
to suit a given resistance of circuit. It may also be shown by the
same formula that if the receiver have small inductance, the resistance
it should have (when of a given size and shape) to make the magnetic
force a maximum approximates to Lv, which is the critical resistance
that absorbs all arriving disturbances.
May 7, 1887.
XLI. ON TELEGRAPH AND TELEPHONE CIRCUITS.*
[February, 1887 ; but now first published.]
APP. A. On the Measure of the Permittance and Retardation of Closed
Metallic Circuits.
OWING to the fact that most of the circuits of which mention is made in
my brother's paper consist of or contain a considerable amount of
* [This article consists of the three appendices that I wrote to the paper of Mr.
sts of the three appendices that I wrote to the paper o
myself on " The Bridge System of Telephony," which
A. W. Heaviside and myself on " The Bridge System of Telephony," which paper
324 ELECTRICAL PAPERS.
buried wires, and therefore possess considerable permittance, combined
with the fact that these buried wires have very high resistance, as much
as 45 ohms per mile, and with the further fact that the self-induction of
these lines is small, we may, leaving on one side the question of the
apparatus (which is no unimportant one in itself), regard the transmis-
sion of telephonic currents through the lines as being governed mainly
by the three factors— resistance, permittance, and length of line.
Take, therefore, for starting-point the now well-known theory of the
submarine cable promulgated by Sir W. Thomson in 1855, which was
so curiously foreshadowed by Ohm in 1827, in his celebrated memoir on
the galvanic circuit, when guided by an analogy between the flow of
electricity and the flow of heat, which is now known to be entirely
erroneous.
A translation of Ohm's memoir is contained in vol. II. of Taylor's
"Scientific Memoirs," and Sir W: Thomson's writings on the subject of
the submarine cable are collected in vol. n. of his " Mathematical and
Physical Papers."
Electromagnetic induction is wholly ignored. The line is a single
wire, fully defined by the three data — its length, and its resistance and
permittance per unit length. The circuit is completed through the
" earth," supposed to have no resistance, and to extend right up to the
dielectric material which envelops it, whose outer boundary is therefore
taken to be permanently at potential zero. On these suppositions, a
single quantity F", the potential of the wire, when given along it, fully
expresses its state at a given moment, and we may exactly calculate the
effect at the distant end of the line (or at any other part), due to
arbitrarily varying the potential by a battery at the beginning; the
periods of time concerned being, in lines of different lengths, governed
by the important law of the squares. Thus if E be the resistance, and
$ the permittance per mile of a cable of length /, the retardation is pro-
portional to ESI2, a certain interval of time, which, if R be in ohms, and
S in microfarads, is expressed in millionths of a second, owing to the
ohm being 109 and the microfarad 10~15 c.g.s. electromagnetic units.
If there be two cables, with constants fiv Sls lv and R2, $2, 12, and we
operate similarly upon them, the time required to set up a given state
in the first will be to that required to set up the corresponding state in
the second, as R^lf is to R^S^- For instance, if it take 1 second to
bring the current at the distant end to y9^ of its full strength due to a
steady impressed voltage at the beginning of the first cable, and the
was intended for presentation to the Soc. Tel. Eng. and Electricians, but which
never got so far, owing to the objections of the official censor. I have omitted the
portion of Appendix C relating to the distortionless circuit, as the matter is more
fully treated elsewhere in this volume. The portions of the obnoxious paper
contributed by myself (about 20 pages) are also omitted, for a similar reason. I
was given to understand that the official censor ordered it all to be left out,
because he considered that the Society was saturated with self-induction, and
should be given credit for knowing all about it. See, however, Art. xxxvin.,
p. 160, in this volume for evidence to the contrary. The present article may now
usefully serve as appendices to the preceding one "On the Self-induction of
Wires," since it consists mainly of practical applications of the theory contained
therein. ]
ON TELEGRAPH AND TELEPHONE CIRCUITS. 325
retardation Ii^S^ of the second cable be 5 times that of the first, it
will take 5 seconds to bring the current at the distant end of the second
line to T9<j- of its final strength. The final currents will not, of course,
be equal, unless the impressed voltages are in proportion to the resist-
ance of the lines. The way the current rises at the distant end due to
suddenly raising the potential at the beginning to, and keeping it at, a
constant amount, is precisely similar to the way a current of heat
appears at the distant end of a metallic bar when its beginning receives
a sudden accession of temperature, which is maintained constant there,
provided the bar be prevented from losing heat laterally. This reserva-
tion is necessary, because it is usually the case that submarine cables are
well-insulated ; whilst, on the other hand, there is considerable lateral
loss of heat from a bar through which a current of heat is sent. But if
the amounts of loss be properly adjusted in the two cases, there will
still be a perfect similarity, if the loss per unit length be proportional to
temperature-difference in the one case, and to potential-difference in the
other.
The effect of terminal resistances, as of the battery at the beginning
and of the receiving instrument at the distant end of the line, is to
increase the retardation considerably, whilst at the same time somewhat
modifying the manner of rise of the current, so that a strict comparison
of a cable with terminal resistances to one without them is not possible ;
although if both have terminal resistances, and they be properly adjusted
in amount, we may render the systems similar, and allow strict compari-
son. The influence of resistance at either end, or at both ends of a
line, on the nature of the arrival-curve, was given by me in my paper
"On Signalling through Heterogeneous Conductors" [Art. XV., p. 61,
vol. I.], the main object of which was to explain the very singular phe-
nomenon of a marked difference in the speed of working through a sub-
marine cable having land-lines of widely different lengths at its two
ends, which was first observed by myself in October, 1869, when making
trials of the speed of working, both by reversing key and by automatic
transmitter, on the then newly-laid Anglo-Danish cable ; when I also
had the opportunity of being present at both ends of the line (not quite
at the same time, however,) so as to be sure that the anomalous
symptoms did not arise from some easily remediable local cause, but
had their cause deep-seated in the electrical system.
The insertion of a condenser between line and earth at the receiving
end, and more especially the insertion of condensers at both ends of the
line, has, on the other hand, a remarkable accelerating power on the
signalling, more than doubling the speed of working — a performance
that contrasts with the effect of the most ingeniously arranged curbing
keys, especially when the excessive simplicity of the means by which
this result is attained is remembered. This remarkable power seems to
have been found out by pure accident, the practice of signalling through
condensers having arisen out of Mr. Willoughby Smith's system of
testing cables during submersion. It is indeed true that Mr. C. F.
Varley had previously patented the method in what Mr. W. Smith has
called a fishing patent, but it does not appear that Mr. Varley or anyone
326 ELECTRICAL PAPERS.
else had foreseen the extraordinary merits of the condenser-method. The
theory of the influence of terminal condensers I have given in my paper
"On Telegraphic Signalling with Condensers" [Art. xni., p. 47, vol. I.],
and again, more completely, in my paper " On the Theory of Faults in
Cables" [Art. XVL, p. 71, vol. I.], in which the theory of the almost
equally remarkable accelerating effect on the speed of working due to a
leakage-fault in the cable is considered, and it is shown how to take
account of the influence of any terminal arrangements, with the solu-
tions in several simple cases.
Suppose now we take for granted that we know precisely how
signals are propagated through a single submarine cable, with given
terminal arrangements ; and next, take two equal but quite independent
cables, with independent batteries and instruments, and operate upon
them similarly and simultaneously, as is symbolically represented in
Earth
FIG. 1.
fig. 1. If the batteries be both with positive or both with negative
poles to line, the phenomena produced in the two cables will be
identically the same at the same time at corresponding places, owing to
the equality of the cables and of the other circumstances. We could,
therefore, by substituting for the two cables one of double the permit-
tance and half the resistance of either of the old ; and for the two
batteries, one of the same E.M.F. and half the resistance of either ; and
for the two instruments, one of half the resistance and half the induct-
ance ; and, if there be terminal condensers, a single condenser for the
two at either end, but of double the permittance of either ; signal
through the new line in precisely the same manner as through the
former two, the new potential being the same as that in both the old
cables, whilst the new current is the sum of the currents in the former
case.
But if, on the other hand, as in fig. 1, the equal batteries have always
opposite poles to line, the potentials at corresponding points will be
equal and oppositely signed, and the currents will be equal and
oppositely directed in space, or in the same direction in the circuit of
:2R
FIG. 2.
the two cables. We may now remove the earth-connections altogether,
without producing any change in what takes place in the cables,
ON TELEGRAPH AND TELEPHONE CIRCUITS. 327
thus making a closed metallic circuit, as in fig. 2. We see, therefore,
that by the abolition of the earth as a return-conductor, and by the
substitution of a return through an equal and independent cable, we
vary the current in the same manner as before the change, provided
we double the E.M.F. and the resistance of the battery, and double the
resistance and inductance of the receiver, and if there be terminal con-
densers, halve their permittances.
So far, therefore, as signals from end to end are concerned, we may
treat the new circuit as a single wire with earth-return, if instead of R
and S being the constants of either wire, we take them to be "2R and
\S per mile of the new circuit ; and, at the same time, take for V, not
the potential of either wire, but their difference of potential at a given
place ; whilst (7, the current in the single wire, becomes the current in
either wire of the loop-circuit. The new resistance is the resistance
per mile of line, and the new permittance is the effective permittance
per mile of line. The electrostatic retardation of the line is un-
changed. (But if we do not, in passing from single-wire to double,
alter the terminal arrangements in proportion, we naturally accelerate
signalling.)
The halving of the permittance is, in another form, a doubling of
what might be called the electrostatic "resistance," if it were not
desirable to refrain from multiplying applications of the term resistance;
owing to the condensers, first wire to earth, and earth to second wire/
being in sequence, whilst the earth itself counts for nothing except a
perfect conductor, for our present purpose. We may, however, perhaps
appropriately speak of the doubling of the " elastance " of a condenser,
defining the elastance to be the reciprocal of the permittance ; for this
is at once in accord with Maxwell's " electric elasticity," the reciprocal
of the specific inductive capacity, and with the general terminology that
I have proposed, thus : —
T ,. ,N ( Resistance. Resistivity.
Conduction Current | Conductancei Conductivity.
,, ,. T , ,. t Inductance, Inductivity.
Magnetic Induct.on ( [Reluctanc; Reluctivity.]
n, ._* T\: i * f Elastance, Elastivity.
Electric Displacement | jp^tj^ Permittivity.]
Resistance and conductance are reciprocal, as are resistivity and con-
ductivity, which refer to the unit volume. Inductivity and elastivity
also refer to the unit volume; whilst inductivity is to inductance as
conductivity is to conductance ; and elastivity is to elastance as
resistivity is to resistance. In the cases of the fluxes induction and
displacement, it may be observed that appropriate reciprocals are
wanting. This system, I find, works well practically, except in this
respect. Although elastance is supported by Maxwell's elasticity, yet
it does not at all harmonize with displacement, which is, by itself, quite
appropriate, though it does not lend itself to the variations that are
wanted. Again, elasticity might be confounded with mechanical
elasticity, unless we prefix- the adjective electric, which prefixing of
328 ELECTRICAL PAPERS.
adjectives is just one of the things that we should try to avoid in a
convenient terminology. This objection is, however, completely re-
moved by the substitution of elastivity, which has also the advantage
of more perfectly harmonising with conductivity and inductivity. As
for going to the dead languages for more new words, which may be
quite unaccommodative, I must regard that as a barbarous practice.
A good and adaptable substitute for displacement is therefore wanted,
and from it a pair of words which shall stand for the reciprocals of the
above elastance and elastivity, which are convenient. Now capacity, the
present term for the reciprocal of elastance, may mean anything ; it is
too general a term ; we should rather have a word suggestive of elastic
yielding ; capacity seems to suggest the power of holding electricity, a
notion which is thoroughly antagonistic to Maxwell's notion of the
functions of a dielectric. Again, the reciprocals of inductivity and
inductance are wanted. It is quite painful to read of "magnetic resist-
ance" to "lines of force." [I have now inserted the additional words
coined after writing the above, and have substituted permittance for
capacity in the text.]
After this little digression upon a subject which is important to all
who desire the improvement of electrical nomenclature in a systematic
and convenient manner that will harmonize with Maxwell's theory of
^electricity and its later developments, we may return to the looped
cables. The earth between them has, or rather has been assumed to
have, merely the function of a conductor of negligible resistance; which,
though not true, for there would be some small mutual action between
the cables, is perhaps sufficiently true practically when cables are sub-
merged. The above reasoning therefore applies to a pair of buried
wires, provided they be each wholly surrounded by fairly well-conduct-
ing matter, either existent all the way between them, or at least in
good conductive connection, if the matter does not extend from the
outside of the insulator of one wire to that of the other and surround
both. But if this be not the case, it is clear that the effective elastance
will be increased by the substitution of dielectric for conducting matter,
or the effective permittance will be reduced, thus reducing the retarda-
tion. Hence the greatest possible measure of the electrostatic retarda-
tion of a pair of equal buried wires in loop is that of either alone, when
buried in the technical "earth," and it may be considerably less.
Experiment on this point is wanting to see how wires buried in pipes
behave as regards permittance. It is no use at all to measure the per-
mittance of each wire by itself with respect to earth ; the proper way
is (as I have before pointed out) to measure the effective permittance
as it really is, that from one wire to the other, modified in amount to
an unknown extent (in the present case) by the amount of moisture
present, and by the parallel conductors.
If the radius of a wire be ?•, and that of its (homogeneous) insulator
s, its greatest permittance, viz., when earth comes close up to the
outside of the insulator, is
", a)
ON TELEGRAPH AND TELEPHONE CIRCUITS. 329
per unit length, where c is the permittivity of the dielectric, this being
the well-known formula due to Sir W. Thomson. When the covering
consists of concentric layers of different permittivities clt c2, etc., of
outer radii s15 s2, etc., we get the permittance at once by taking the
reciprocal of the sum of the elastances ; thus,
To illustrate the way of getting this formula, let this wire be suspended
in the air, and its permittance with respect to earth be wanted ; we
shall have to add on the elastance between the outside of the solid
covering and the earth, to obtain the total elastance, when, of course,
its reciprocal, the permittance, is greatly reduced.
If c vary continuously with the radius, then
taken between the proper limits, is the elastance. Thus, if c vary
inversely as r, the elastance is simply proportional to the thickness of
the dielectric. If it vary as ?•, the elastance is proportional to the
difference of the reciprocals of the radii, so that the permittance is
finite when the outer radius is infinite, instead of zero, as is the case
when c is constant, or varies inversely as r. The permittance of an
infinitely thick cylindrical dielectric with finite internal radius, is zero
or finite according as, if c = r,0rw, n is negative (including zero) or posi-
tive, the general formula being
2dr _ 2 fl
Vn+1 cQn\an
when the outer and inner radii are b and a.
Similarly, when the dielectric layers are spherical, since the elastance
of a layer of thickness dr is (47r/c)(e?r/47rr2), 4?r/c being the elastivity,
we have
as the expression for the elastance between the proper limits. And
if c = c0r", we have only to change n to n+1 in the cylinder case to
obtain the spherical results ; e.g., permittance inversely as thickness if
n= -2.
The strict application of this method to magnetic induction problems
is not possible on account of the circuital property, except in some
peculiar cases of magnetic circuits. But its partial application is useful
enough.
[It is, I believe, to Mr. F. C. Webb, in his work " Electrical Accum-
ulation and Conduction," 1862, that we must give the credit of first
recognising and employing in electrostatic problems the idea of the
addition of elastances, rather than that of the compounding of per-
mittances. It is, however, unfortunate that the application of the
method is so limited.]
330 ELECTRICAL PAPERS.
In the case of a pair of twin wires in pipes, we only safely know the
greatest possible effective permittance, which is J£, where S is given
by (1) or (2); whilst the effective resistance is double that of either
wire ; and that this measure of the permittance may be considerably
reduced. But using the proper value, whatever it may be, we may
apply the submarine-cable theory, as if a single wire were in question,
but taking V to represent the difference of potential of the two wires.
Let us now pass to the other extreme, by removing all conducting
matter from the neighbourhood of the wires to a very great distance ;
for instance, imagine the twin wires to go from the earth to the moon.
If the wires be at the same distance apart as before, the permittance is
brought to a minimum. (It is, of course, nonsense to talk of the per-
mittance of the wires, strictly speaking, as it is really the permittance
of the dielectric between them that is in question.) Let one be charged
positively, the other equally negatively; the ratio of this charge to the
difference of potential is the permittance required. Its value was given
in my paper " On the electrostatic capacity of suspended wires " [Art.
XII., vol. I., p. 42]. If rx and r2 are the radii, and r12 their distance
apart (between axes or centres),
...(3)
is the permittance per unit length (in electrostatic units), if the
dielectric has the unit permittivity. But if the wires are covered with
solid dielectrics in concentric layers, this formula (3), or rather the
reciprocal, S~l, will only represent the elastance between the external
coverings supposed of radii rt and r2 ; we must then add the elastances
of the various concentric layers, as per equation (2), for each wire, to
obtain the total elastance between the wires ; and, lastly, its reciprocal
is the required permittance.
But, keeping to (3), with a dielectric of unit permittivity all the way
from wire to wire, the resistance to be coupled with S will be the sum
of the resistances of the two wires per unit length. Observe that the
radii of the wires need not be equal, nor their resistances. Quite in-
dependently of equality of the wires, the propagation of signals from
end to end will take place according to the single-wire theory, with R
and S as just defined, and V taken to be the fall of potential across the
dielectric. (As to the permittance of either wire by itself in space, that
is zero, or else meaningless, if it be infinitely long.) But whether
magnetic induction will now be ignorable will depend upon the values
of R, S, and the inductance, which last is not now in question.
If one conductor surround the other concentrically, and be far
removed from other conductors, we of course use formula (1) for the
permittance, whilst the effective resistance is the sum of the resistances
of the wire and sheath, and V is their difference of potential. But if
other conductors be brought close, their presence will necessitate the
consideration of the external permittance of the sheath, and somewhat
modify the propagation of signals according to the single-wire theory.
Returning to the previous case, let the wires be equal, and be not
ON TELEGRAPH AND TELEPHONE CIRCUITS. 331
infinitely removed from other conductors, but still be at a distance from
them which is a large multiple of their distance apart ; for instance, let
them be suspended above the ground in the usual manner. Clearly
they will cancel one another to a great extent as regards their influence
in charging the earth, when they are equally and oppositely charged
by the battery.
Hence the formula (3), with rT = r2, or
(4)
will be approximately true. But this value of S will be rather less
than the true value, which is a little increased by the presence of the
earth. The value of the permittance between two unequal wires of
radii r^ and ?\,, distant r12 between centres, at heights fa and Js2 above
the ground, is, if su be the distance between either wire and the image
of the other (the image being a parallel similar imaginary wire as much
vertically under as the real wire is above the ground), given by
l .......................... (5)
(To get this and other formulae, see the paper last referred to, and
pair wires. ) So, when the wires are of equal radii, and at equal heights,
we shall have
s=
and, since s/s12 is nearly unity, (4) is nearly equivalent. On the other
hand, the permittance between either wire and earth is
(7)
and we see that one-half of this has no necessary equivalence whatever
to the true S of (4) or (6). There may be an accidental equivalence.
But, whilst (4) assumes the earth to be infinitely distant, and (6) allows
for the increase due to the earth's nearness, there is still a further
increase to be practically reckoned on account of the proximity of
parallel wires (i.e.t when there are any, as is usual). The amount of
this increase, which is not at all insignificant, I have calculated in the
paper referred to, when the earth is the return-conductor. To get the
results when wires are looped, we have merely to pair the wires
properly.
It is necessary for the wires to be at the same height above the
ground, and to be equal in other respects, for the looped circuit to
behave strictly as a single wire in the propagation of signals from
end to end. Otherwise, differential effects are produced, due to the
currents not being quite equal in the two wires. The extension of the
meaning of a "line" to include looped wires, generally to be equal, but
sometimes with a complete removal of this restriction, leads to a great
simplicity in the treatment of problems relating to the transmission of
signals from end to end, doing away with a vast quantity of round-
332 ELECTRICAL PAPERS.
about work 'that occurs when each wire is considered independently,
with its own constants and potential and current. I have developed
this in my paper "On the Self-induction of Wires," [Art. XL., vol. n.] ;
a more elementary treatment is contained in "Electromagnetic Induc-
tion and its Propagation," Sections xxxn. to xxxv. [Art. xxxv.,
vol. II., p. 76].
In farther illustration of this matter, go back to fig. 1, in which let
the wires be, not equal, but have the same time-constants of retardation,
or ./ZjiSy2 = R.2Sf. Let the upper wire have N times the resistance of
the lower, and the lower have N times the permittance of the
upper, between wire and earth. The top wire should then have a
battery of N times the resistance of that of the battery on the
lower wire, and also an instrument of N times the resistance and
inductance ; whilst any condensers in the lower terminal arrangements
should have N times the permittance of those in the upper. In short,
the two systems are to be similar ; one to be an enlarged copy of the
other, the ratio being N.
If, now, the earth be kept on for return-conductor, and similar poles
of batteries of equal voltage be to line, the potentials at corresponding
points will be equal, though not the currents, so that the two wires
behave like one, having the same time-constant. And, if the batteries
be with opposite poles to line, with voltages in the ratio R^R^ we
have equal but oppositely signed charges and currents, and the
earth-connections may be removed, leaving a metallic circuit, which, if
J^be taken as the fall of potential from wire to wire, is equivalent to
a single wire with earth-return, of resistance equal to the sum of the
resistances of the two wires, and elastance equal to the sum of the
elastances, so that the electrostatic time-constant is unchanged.
This applies to all wires whose dielectric coverings are externally
joined by matter of negligible resistance. On the other hand, when
there is dielectric everywhere about the wires, we have the case of
equation (3) again, if sufficiently distant from earth and other conductors.
But if not sufficiently distant, we shall have differential effects produced,
and the propagation of signals will not take place strictly according to
the single-wire theory, but will have to be, if the differential effects are
great enough to make it worth while to allow for them, calculated
according to the methods appropriate to self and mutual induction of
wires, electrostatic and magnetic, as developed in my paper "On
Induction between Parallel Wires" [Art. xix., vol. I., p. 116]. As
an extreme case, let one wire be suspended, and the other, of equal
resistance, be buried in the ground. Here the differential effects will
be very large. But this is a mere curiosity, from the practical point of
view. What is important is, that in the practical cases that have
arisen of late years, principally owing to the extension of the use of the
telephone, in which metallic circuits are employed, the wires are
practically equal in all respects, so that the circuit may be treated
as a single wire with very great accuracy in the manner I have
exemplified here in some elementary cases and developed elsewhere,
extended to include self-induction and leakage.
ON TELEGRAPH AND TELEPHONE CIRCUITS. 333
See my paper on "Induction between Parallel Wires" already
referred to. For two parallel wires the equations are [vol. I., p. 140]
where ^ and v2 are the potentials of wires 1 and 2 at distance x;
&! and Kg the resistances ; ^ and i2 the insulation-resistances ; sv s2, S12
the magnetic induction-coefficients ; cp e2, and e]2 the electrostatic
induction-coefficients ; the dot standing for time-differentiation, and the
accent for ^-differentiation.
Now let the wires be equal, and loop them. Let
v\ ~V2 = ^= difference of potential,
C = current,
2k = E = resistance of line per unit length,
•|(c ~ Ci2) =s = permittance „ „ „
2(s - s12) = L = inductance „ „ ,,
(2i) ~ l = K= leakage-conductance „ „
Then we shall have
- <*f= EG + LC, - *j*= KF+ SF;
dx dx
and the potential equation is, by subtracting the equation of v2 from
that of vlt
d^ (K±.Td\ Tf^<Zd\
-j— = (H + L— ) (K + b — )
dx2 \ dtj\ dtj
These are the equations of a single wire with earth-return and constants
R, L, S, arid K, potential Vt and current (7, as in equation (25) of the
same paper [p. 139, vol. I.]. There are several other cases in which a
similar simplification results.
It would appear from the results given in my brother's paper, and
from others of a similar nature, that the greatest value of the time-
constant of a buried circuit with wires of high resistance which it is
possible to work through practically with telephones is about
ES12 = -015 second.
From the results obtained in the early days of the telephone I
concluded that *01 second was something like it. But it is really a
quite indefinite quantity, depending upon so many circumstances,
including not only the instruments, but also the absurdly-called
personal "equation." One man might go on to -015, and another
declare that -0075 was past bearing, a difference of 100 per cent. But
on this point I wish it to be distinctly understood, so far as my own
views are concerned, that, taking this -015 second as expressing the
practical utmost limit of what it claims to represent, it only applies
334 ELECTRICAL PAPERS.
when the line can be treated as a submarine cable. And, to emphasize
this remark, I will add that if any one would pay the cost, which would
be considerable, I would undertake to erect a line of such length and
permittance that its electrostatic time-constant should be several times
this '015 second, and yet work the telephone beautifully through it.
It would not be a submarine cable, that is all. The submarine cable
would have no more to do with it than Mrs. Harris.
Apparatus is a matter of considerable importance. Nearly all the
progress to efficiency described in my brother's paper was in getting rid
of apparatus retardation, and allowing the lines to have the best chance.
When, however, it comes to the complete removal of all intermediate
apparatus (leaving only apparatus in bridge), and then to working
through the longest distance possible, it is clear that, if the terminal
apparatus is fairly good, the substitution of one telephone for another
cannot (unless they are of widely different natures) be accompanied by
any important change in the greatest working distance.
APP. B. On Telephone Lines (Metallic Circuits) considered as
Induction-Balances.
IT is needless to say that a circuit consisting of a single wire with
earth-return is not balanced against the inductive interference of parallel
wires at all. But, as is remarked in my brother's paper, a double-wire
telephone line is an induction-balance. More correctly speaking, it
ought to be made one. The disturbances of balance referred to in the
paper are, from the scientific point of view, of considerable interest.
In the following the theory of these disturbances is illustrated by
investigating some comparatively simple analogous cases.
Take two long wires and thoroughly twist them together ; and join
them up with a telephone so that any current in the circuit must go up
one wire and down the other ; and then try to induce currents in the
circuit by means of intermittences or reversals in an external wire. If
this be done as a laboratory experiment, there will be no sound in the
telephone. It is true that we can easily detect the induction between
the primary and a single loop (or half a complete twist) of the secondary,
especially if we make a loop in the primary of about the same size ; but
there is practically not the least effect when it is not one loop, but
hundreds in the secondary that are in question. In fact, the two wires
of the secondary circuit change places so often that they may, in the
mean, be regarded as identically situated, and have precisely equal
E.M.F.'S induced in them by the primary current. There is, then, no
observable current in the secondary ; nor does it matter whether the
wires have the same resistance or not, (though there might perhaps be
an observable current if the wires were of widely different sizes, especially
if the thicker one be iron), nor whether resistance is inserted in the circuit
or not. It is simply a question of the resistance and inductance of the
secondary circuit ; and since there is no E.M.F. in it on the whole, there
is no current.
But the case becomes different when we stretch out the double wire
ON TELEGRAPH AND TELEPHONE CIRCUITS. 335
to many miles in length ; for then electrostatic permittance comes
sensibly into play, which allows current to leave the wires, and therefore
permits current to exist in them. The difference between the long and
the short line is, however, only one of degree in this respect. In fig. 1,
let the two horizontal lines represent a pair of telephone wires in loop,
which are to be imagined to be twisted (or not, as we please), and let
FIG. 1.
Kv K2 be the terminal apparatus. There is no interference from
parallel wires to be observed at K-^ and K2 in general, but if a resistance
^ be inserted intermediately in one of the wires, there is. It can be
abolished by inserting an equal resistance R2 in the other wire at the
same place. If unequal, there is still interference. If Rl is a coil and
R2 a mere resistance, equal to that of the coil, there is still interference.
We must make R2 an equal coil to get rid of it. These interferences
are weak, and are not observable when it is a telephone-wire that is the
primary; but when the primary is a Wheatstone transmitter wire,
they disturb speech on the telephone circuit, and require removal. The
way in which the Bridge-system absolutely cures the evil is one of the
most interesting things about it, though not the most important, which
is of course the entire removal of the impedance of intermediate
apparatus.
Now, if electromagnetic induction were alone concerned, there could
be no such interference, either at the terminals or anywhere else. The
interference is therefore connected with the permittance of the wires.
Imagine, first, the circuit to be so far removed from other conductors
that the permittance is appreciably the reciprocal of the elastance from
one wire to the other in an infinite dielectric. For illustration in a
simple manner, concentrate the permittance at two places, represented
by the condensers Sl and S2 in fig. 1. Then let the wires be cut by
the lines of magnetic force of a primary current, causing equal and
similarly directed E.M.F.'S in them between K-^ and Slt also between
51 and $2, and between S2 and K2. We shall call these the impressed
forces and ignore the external agency. It is easily seen that those
between K^ and S± can produce no current ; neither can those between
52 and K2 ; as there is no permittance attached to those parts of the
circuit. But between S^ and S2 the wires are not conductively con-
nected. Yet the impressed forces can still produce no current, because
any current there might be is constrained to be of the same strength in
both wires, and to be oppositely directed. This conclusion is wholly
independent of the resistances concerned, as well as of the permittances
of the condensers ; so that there could be, in this case also, no inter-
ference effect.
336 ELECTRICAL PAPERS.
Thus, formally, let the arrows indicate the directions of positive
current and E.M.F. ; let Rl and R2 be the resistances of the upper and
lower middle sections ; L the inductance of the circuit 7t1$27?2$1 ;
gj and e2 the impressed forces in 7^ and R2, and V^ V2 the falls of
potential through the condensers. Then, if G is the current in
-Bj and E2,
el + e^Tl+F'2 + (Ill + E? + Lp)C .................. (1)
is the equation of E.M.F. in the circuit R^S^R^ where p stands for
the timeilifferentiator. Also, the condenser-equations are
C=(Kl + 8,PW^(K^S,p)V2 .................... (2)
if the currents in J^ and K2 in the figure be K^ and K2V2. Here K^
and Kc, may be arbitrary, depending upon the nature of the line, etc.,
to the left of Sl and to the right of S.2, if we take K^ and K2F2 to be
the currents which shunt the condensers. From these data, if el + e2 = 0,
we have C = 0, so far as impressed force in Ml and R2 is concerned.
If e^ + e2 be not zero, P\ and F2 may be found by
same denominator
'
Thus, since the equal and similarly-directed impressed forces in the
two wires between the condensers can produce no current, and since
the same reasoning applies to any number of condensers with any
resistances and inductances between them, we may conclude that there
will be no current induced in any part of a circuit consisting of two
wires twisted together, however unequal they may be, provided the
effective permittance be the permittance in the sense above mentioned.
This is most intimately connected with the fact that under these cir-
cumstances the propagation of signals from end to end of the line takes
place in the same manner as on a single wire with earth-return.
As the interference is not due to the mutual permittance, we must
refer it to the permittances of the wires with respect to external con-
ductors, or rather, to inequalities therein. Let it be the earth that is
the external conductor, and now modify fig. 1 thus, to make fig. 2.
Here the pair of condensers S1 and S2 represent the permittances of the
-* R,
fr ! ^:: - -- im^)
-*- R, —
FIG. 2.
upper and lower wires with respect to earth at one place, and S3 and S4
do the same at another place, the earth being represented by a wire
joining the condensers together as represented, to which wire we may
ON TELEGRAPH AND TELEPHONE CIRCUITS. 337
attribute resistance r, which may be zero if we please. As before, the
arrows indicate the direction of positive current and E.M.F. Let Cv C2,
and c be the currents in Rlt #2, and r ; and let Llt L2, and M be the
inductances, self and mutual, of the circuits RlS3rS1 and rS4R2S2. Then
the equations of E.M.F. in these circuits are
•i - I + a + + lP -rc
e.2=V,+ Vt + (R, + L2p)C2 + rc + JfpCv
where Vlt F2, etc., are the falls of potential through the condensers.
Also, the condenser-equations are
c-, = saP v, + K.( v, + r,) =slf71+ K,( r, + F2),\ . .
"
if K-L and K3 be the conductances (generalised) of the systems to the
left between the upper side of Sl and the lower of S» and to the right
between the upper side of Ss and the lower of $4. Finally, to complete
the relations, we have
C^c^Cs ..................................... (6)
As the current is not now constrained to be of the same strength in
the two wires, on account of the auxiliary conductor r, we shall usually
have differential effects and interferences. Let us then enquire how to
make the currents in K^ and K3 zero when el + e2 = 0. That is,
Fi+F^O, and F3+F4 = 0, when ^ + ^ = 0 .......... (7)
Introduce these into (4), and we get
- rc
.i - « i
-(«i- Vi~ y3) = (^ +
by adding which there results
^^(Rl + Llp + Mp)Cl + (R2 + L2p + Mp}C2 ................ (9)
Also, by (7) in (5), we have
Cl~SlP7l-S^7v 0^-807^ -8#7» ......... (10)
from which we see that C2/Cl = - S%/Sl = - SJSB ; which, used in
(9), give
0 = (Rl-R,S2/S1)Cl+{(L1 + M)-(L, + M)S2/Sl}PCl, ......... (11)
which must be identically satisfied. Hence, finally,
/io\
are the complete conditions of the induction balance. Notice the
independence of the auxiliary wire's resistance. From this we see that
in the previous case (got by making r infinite here), the induction-
balance was merely true because Gl = C2 ; then, as we saw before, Jiv
R2, etc., may have any values. Notice also that M is negative, and
that L^^ + M and Z2 + M are the inductions through the circuits RlSsrSl
and R^StfrSt due to unit current in the circuit R
H.E.P. — VOL. ii. y
338 ELECTRICAL PAPERS.
If, as in the simplest case, the wires are equal, and Rl = R^ etc., we
of course upset the induction-balance by putting a coil in sequence with
one of the wires R^ R^ and restore it by putting an equal coil in
sequence with the other. In this case of equality, undisturbed, we
have, since P^ = Pi2, L^ = L2, Sl = S2, S3 - £4,
Cl=-C2=-^c = SlpF1 = S3pFB = S2pF^S4p^',
and the equation of E.M.F. in the circuit of Pv R2 in parallel, and the
condensers and return, is
Ol ..... (13)
We have now equal and similarly directed currents in Rl and R2,
passing through the condensers and returning combined through the
auxiliary wire. The equal wires may be replaced by one of half the
resistance, and of inductance ^(^-M); the terminal condensers S1
and $2 by one of double the permittance, and similarly for S3 and S4,
when put in sequence with the substituted wire on the one hand and r
on the other. Then 2Cl is the going and return current.
It may, perhaps, be worth while to give the full equations in the
general case of disturbed balance. They are
in which the A's and B's have the expressions
U+j$% + (Rl + ^X*. + ^ + ('^ + MKJP>
-rStp + Mp(K, + Stp),
From these we may deduce (12) by taking
When, instead of two pairs of condensers only, as in fig. 2, we have
a large number of pairs, the earth-wire r must run on and join the
middles of every pair. We see from this that the equal KM.F.'S in
Rl and R2 will cause currents in them similarly directed which will not
return immediately by the wire r in the figure, but only partly there,
the rest going further and getting to the auxiliary wire through other
condensers. Supposing, then, we have the condensers, etc., uniformly
distributed, if the impressed forces be also uniformly distributed along
the two wires, there would be, by their mutual cancelling, little if any
effect produced (not referring to the balance at the terminals, which is
independent of uniformity of distribution of the equal E.M.F.'S). But,
generally, the E.M.F.'S will not be thus uniformly distributed.
The general equations of self- and mutual-induction of parallel wires,
ON TELEGRAPH AND TELEPHONE CIRCUITS. 339
given in "Induction between Parallel Wires" [vol. I., p. 116], show
that if we start with a pair of equal wires looped, and then introduce
some inequality, we cause the induction-balance to be a little upset, and
simultaneously we cause the circuit to behave not quite the same as a
single wire, as described in App. A. Thus, if the wires be equal in all
respects, and be at the same height above the ground, they behave as
one ; and also, if exposed to the interference of a parallel wire equi-
distant from them, the balance will not be upset. But if the paired
wires be in a vertical plane, and therefore at different heights above
the ground, we cause a small departure from behaviour as a single wire,
and also slightly upset the balance, even although the interfering wire
be equidistant from the paired two. Both effects will be small, and it
is questionable whether they would be observable. But I am informed
by my brother that the interference arising from one wire being of iron
and the other of copper has been observed in his district.
When the circuit is completed by a concentric tube, the external
permittance of the tube will give rise to interference, if the circuit be
long enough. This has not yet been observed.
Practical telephonists who keep their eyes open have unusual oppor-
tunities of observing very curious and interesting electrostatic and
magnetic effects. Unfortunately, however, the demands of business, to
say nothing of other reasons, usually prevent their careful examination,
record, and explanation.
APP. C. On the Propagation of Signals along Wires of Low Resistance,
especially in reference to Long-Distance Telephony.
A WHOLLY exaggerated importance has been attached by some writers
to electrostatic retardation. I do not desire to underrate its import-
ance in the least — its influence is sometimes paramount, — but the
application of reasoning based solely upon electrostatic considerations
should certainly be limited to such cases where the application is legiti-
mate. Now some writers, without any justification, take Sir W.
Thomson's theory of the submarine cable to be the theory for universal
(or almost universal) application, supposing that magnetic induction is
merely a disturbing cause, introducing additional retardation, but only
to an extent which is practically negligible in copper circuits. This is
very wide of the truth. What has yet to be distinctly recognised by
practicians, is that the theory of the transmission of signals along wires
is a many-sided one, and that the electrostatic theory shows only one
side — a very important one, but having only a limited application in
some of the more modern developments of commercial electricity,
notably in telephony, especially through wires of low resistance. Some-
times magnetic inertia itself becomes a main controlling factor.
In my paper "On the Extra Current" [Art. xiv., vol. I., p. 53] I
brought the consideration of magnetic induction into the theory of the
propagation of disturbances along a wire, by the introduction of the
E.M.F. of inertia, according to Maxwell's system, in accordance with
which the inductance per unit length of wire is twice the magnetic
340 ELECTRICAL PAPERS.
energy of the unit current in the wire. Calling this L, the momentum
is LC and the E.M.F. due to its variation is - LC per unit length.
In my paper "On Induction between Parallel Wires" [Art. xix.,
vol. I., p. 116] I have further considered the question; and more
recently, 1885-6-7, in the course of my articles "Electromagnetic
Induction and its Propagation," and "The Self-induction of Wires," I
have given a tolerably comprehensive theory of the propagation of dis-
turbances, and have worked out certain important parts of it in detailed
solutions suitable for numerical calculation. In the present place I pro-
pose to give some practical applications of the formulae, in addition to
what I have already given, to be followed by an account of the principal
properties of a distortionless circuit, which casts considerable light on
the subject by reason of the simplicity of treatment it allows.
Roughly speaking, we may divide circuits into five classes : —
(1). Circuits of considerable permittance, to be regarded as submarine
cables in general, according to the electrostatic theory, unless the wave-
frequency be great or the resistance very low. Long overhead wires of
comparatively small permittance may sometimes be included, especially
if the resistance be high.
(2). Short lines which may be treated by disregarding the electro-
static permittance altogether, and considering only the resistance and
inductance, provided the frequency be not too great. Ordinary short
telephone-circuits usually come under this class.
(3). An intermediate class, in which both the electrostatic and
magnetic sides have to be considered simultaneously. This class is
rather troublesome to manage in general.
(4). Yet another class brought into existence by the late extensions
of the telephone in America and on the Continent, and of rapidly
increasing importance, in which wires of small resistance and small
permittance are used combined with high frequencies, and in which the
permittance (though small) must not be ignored, since, in combination
with the inductance it produces an approximation towards the trans-
mission of signals without distortion. The theory is then, even when
the line is thousands of miles long, quite unlike the electrostatic theory.
(5). Distortionless circuits, now to be first described, in which, by
means of a suitable amount of leakage, the distortion of waves is
abolished. Though rather outside practice, except that extreme cases
of the last class resemble it, this class is very important in the compre-
hensive theory, because it supplies a sort of royal road to the more
difficult parts of the subject.
There may also be sub-classes derived from the above. For instance,
a leaky submarine cable, in which resistance, permittance and leakage-
conductance control matters, whilst inertia may be of insensible influence.
The peculiarity that is brought in by magnetic inertia (symbolised
by the inductance) combined with electric displacement, is propagation
by elastic waves (similar to the waves that may be sent along a flexible
cord, or perhaps better, a common clothes-line, though even then there
is not usually enough resistance), as distinguished from the waves of
diffusion (as of heat in metals) which is the main characteristic of the
ON TELEGRAPH AND TELEPHONE CIRCUITS. 341
slow signalling through an Atlantic cable. The two features are always
both present, but sometimes one is paramount, as in class (1), and
sometimes the other, as in classes (4) and (5). [The Americans who
went in for wires of low resistance had, I think, no idea of the import-
ant theoretical significance of the step they took, but did it because
they wanted long-distance telephony, and because wires of high resist-
ance would not go — a characteristically American way of doing things.
Yet their action led the way to a rapid recognition of the sound
practical merits of Maxwell's theory of the dielectric.]
Let E, S, L, K be the resistance, permittance, inductance, and leakage-
conductance respectively, per unit length of circuit, which may be a
single wire with earth-return, or a pair of wires in loop, in which case
the wires should generally be equal, to avoid the interferences which
would remain in spite of the twisting by which the greater part of the
interferences from other circuits may be eliminated. Also, let Fand
C be the potential-difference and current at distance z ; then
-VF=(E + LP)C, -VC=(K+Sp)r, ............. (1)
where V stands for d/dz and p for d/dt, are the fundamental equations.
Now suppose that an oscillatory impressed force acts at the beginning
of the line. Let p denote the ratio of its amplitude to that of the
current. At z = Q, p is plainly the impedance of the circuit to the
impressed force. If the line were perfectly insulated, and had no
permittance, p would be a constant for the whole circuit, at a given
frequency. But the range of the current is not everywhere the same
(besides varying in phase), so that p is a function of z. The term
impedance is strictly applicable only at the place of impressed force,
therefore. But to avoid coining a new word, I shall extend its use, and
term p anywhere the " equivalent impedance." It is with the equivalent
impedance at the far end of the circuit, say z = I, that we are principally
concerned. Call it /, this being the ratio of the amplitude of the
impressed force at z = 0 to that of the current at z = I. Let
LSv*=l, X/Ln=f, . K/Sn = g, ................. (2)
where nftir is the frequency. Also let
P or e = "(l)t{(l+/2)i(l +f}±(fg- 1)}* ............. (3)
On these understandings, the value of / is
provided the line be short-circuited at both ends. Terminal apparatus
will be considered later.
If S — 0, L = 0, K= 0, then I=Rlt the steady resistance of the circuit.
If only S=Q, K= 0, then /= l(E* + L2n2)*, the magnetic impedance. If
£ = 0, K=0, then
I=i(A\ {<?" + e-8"- 2 cos 2^}*, .................. (5)
in which Pl = (\nR3lrf ............................... (6)
342 ELECTRICAL PAPERS.
Now the significance of (4) depends materially upon the values of the
ratios /, g, and on the frequency. First as regards g. A leakage-
resistance of 1 megohm per kiloni. makes K= 10~20, and a permittance
of 1 microf. per kilom. makes S= 10~20 also. Therefore on a land-line
of 1 megohm per kilom. insulation-resistance and '01 microf. per kilom.
permittance, we have g = 100//1. Thus g is important at low frequencies,
and becomes a small fraction at high frequencies, even with this rela-
tively low insulation. Thus, ?i=1000 makes #='1, and n = 20,000
makes g='OQ5. These correspond to frequencies of about 160 and
3200. We see that in telephony, even with poor insulation, g is always
small. By bettering the insulation it is made smaller still. Therefore
we may practically take g = Q in telephony through a fairly well-in-
sulated line. Notice here that the effect of g in attenuating the current
may be considerable when the frequency is low, and yet be small when
the frequency is high.
Now the frequency is low on long submarine cables. Consequently
g, if there is sensible leakage, has an important attenuating effect. But
the above formula does not inform us what other effects leakage has,
except by examination through a large range of frequencies. It has a
remarkable effect in removing the distortion of the signals, by neutralis-
ing the effect of electrostatic retardation. This is marked when the
frequency is low, and becomes less marked when it is high. But in the
latter case, if the frequency be only high enough, there is little distor-
tion even when the insulation is perfect, or g = 0, provided the resistance
be small. Thus g has a large attenuating and also a large rectifying
effect when the frequency is low; when it is high, then it does not
attenuate so much and does not rectify so much, nor is so much rectifi-
cation wanted. But the full nature of this rectifying action will be seen
later in the distortionless circuit.
Now consider /. This depends on the resistance, inductance, and
frequency. Now 1 ohm per kilom. makes -ff=104; consequently, if
r be the resistance in ohms per kilom.,
f=W*r/Ln ................................. (7)
In a long submarine cable r is small, but n is also small, and L is small,
or certainly not great ; therefore / is big. So we may take its reciprocal
to be zero ; or, what will come to the same thing, take L = 0. We have
then the formula (5) for the equivalent impedance (unless leakage is
important) ; and since we can work up to such frequencies that e2^ is
big, we may then write
(8)
or p = I/El = €Pl(8Pl)-\ ...................... (9)
where PI is as in (6). This PI may be as big as 10 on an Atlantic
cable. Equation (8) shows the extent to which the line's resistance
appears to be multiplied, and is according to Sir W. Thomson's theory.
Now consider buried wires of 45 ohms per mile, such as are used in
telephony by the Post Office. Being twin wires, L is small ; so, when
n is even as high as 101, / is made rather large. Consequently we may
ON TELEGRAPH AND TELEPHONE CIRCUITS. 343
still apply the electrostatic theory, even in telephony, so far as the
buried wires mentioned are concerned, although it will somewhat fail
at the higher frequencies : and we see that it is by reason of their
high resistance and low inductance that we can ignore the influence
of inertia in them. But this does not apply to the suspended wires
which are in circuit with the buried wires, as we shall see pre-
sently.
Consider a pair of open or suspended wires. Take 20 ohms per
kilom. as the resistance, or 10 ohms each wire. This will, by (7), make
/=2 if Z=10 and n= 10,000; and /=-2 if £=100. Now the last
value of L is extreme. It could only be got with an iron wire, and its
inductivity would need to be large even then ; besides that, the fre-
quency would need to be low in order to allow the large L to operate,
on account of the increased resistance due to the tendency to skin-
conduction at high frequencies. Such a large value of L may usually
be put on one side, so far as practical work is concerned; but £ = 50
would be more reasonable, remembering that in L is included the part
due to the dielectric surrounding the wire. The data regarding the
inductivity of iron telegraph-wires are not copious ; from my own
observations, I believe that, with the weak magnetic forces concerned in
telephony, /* = 200 is high, and it may be as low as 100. The point is,
however, that /, from being large, may be made small by increasing the
inductance without other changes. Still, however, with the assumed
steady resistance of 20 ohms per kilom., we could not treat /as a small
fraction, especially as the increased resistance due to the imperfect
penetration of the magnetic induction into the wires will increase /, as
will also the reduced inductance due to the same cause. Thus / must
be kept in the formula for the equivalent impedance, though not to
be treated as either very large or very small in general. That is,
we have the form of theory of class (3) mentioned above. Similar
remarks apply to long suspended copper wires if the resistance be
several ohms per kilom., and they be at the usual distance apart ; for
although with high frequencies / will be small, yet it will not be
small enough at the low frequencies to allow of its treatment as a
small quantity. We should therefore use equation (4) with only g = 0
in general.
But now come to a copper wire of only 1 ohm per kilom., in
loop with a similar wire, making R= 204 or r = 2. Now %=104
/.2/i; (10)
from which we see that / may be so small a fraction as to lead to a
simplified form of theory. We now have the fourth class of circuits ;
well-insulated, of low resistance, and of fairly high inductance, making
RjLn small, and a tolerably close approach to distortionless trans-
mission.
To estimate the value of L, go back to equation (2) defining v. Here
v is a speed, always less than that of light, but of the same order of
magnitude. If the wires are of iron, it is considerably less ; but if of
copper it is so little less that we may neglect the difference. Now
344 ELECTRICAL PAPERS.
and 1 microf. = 10~15, so that if SQ is the permittance in microf.
per kilom.,
L=($s0)-\ ................................ (11)
which is useful in giving an immediate notion of the size of L in
terms of the permittance, when that is known. Thus '01 microf.
per kilom. makes L = 11, so that /=T2T when n= 10,000, when the
resistance per kilom. is 2 ohms ; and / is only TXT at the higher
frequency 20,000/27r.
But this estimate (11) will always be too small a one, and sometimes
much too small, if SQ be the measured permittance per kilom. It was
found by Professor Jenkin that the measured permittance was twice as
great as that calculated on the assumption that the wire was solitary.
The explanation (or a part of it) which I have before given [Art. xn.,
vol. L, p. 42, and XXXVIL, vol. IL, p. 159] is that the neighbouring
wires themselves largely increase the permittance. Therefore, if s0 be
the measured permittance in presence of earthed wires, the real L must
be considerably greater than by equation (11). On the other hand,
there is a set-off by reason of L being reduced by the induction of
currents in the neighbouring wires, though not so greatly as to
counteract the preceding effect. Again, the magnetic field pene-
trates the earth, which increases L. But, to avoid these complexities,
which require us to consider the various mutual effects of circuits,
let our circuit be quite solitary. Then, if r = radius of each wire, and
s = distance apart,
L= 1-1-4 log (s/r) ............................ (12)
when yu, = 1, as with copper wires, the 1 standing for J/AJ + J/J2, if /^ and
H2 are the inductivities of the two wires. These terms are important
in the case of iron wires ; but riot with copper, unless the wires are very
close, when they become relatively important on account of the small-
ness of the total inductance. The other part of L is the inductance of
the dielectric, and it is this which, when multiplied by S, gives the
reciprocal of the square of the speed of light, subject to the proper
limitations. Now L = 20 requires s/r = 148 ; or if r be £ inch (which is
about what is wanted to make the resistance 1 ohm per mile), s must
be 18 J inches. We therefore see that L = 20 is quite a reasonable value
with copper loop-circuits. It gives /= 1 when n= 1000, and -^ when
n = 10,000. Thus /is less than unity throughout the whole range of
telephonic frequencies, and becomes a small fraction even at practical
frequencies.
Take, then, g = 0 and / small in (3) and (4). We get
1 n R R n
and the equivalent impedance formula (4) reduces to
(14)
in the fourth class of circuits.
ON TELEGRAPH AND TELEPHONE CIRCUITS. 345
The further significance of this formula will depend materially upon
the value of the ratio ltt/2Lv (that is, the value of PI), the ratio of the
resistance of the circuit to 2Lv, which is, in the present case, 1 200 ohms.
If the length of the circuit be a small fraction of 600 kiloms., the
impedance depends upon the frequency in a fluctuating manner, going
down nearly to Uil and then running up nearly to Lv, as the circular
function goes from - 1 to + 1, on raising the frequency. Thus the
least possible equivalent impedance at z = l is one half the steady
resistance of the line, and the greatest is Lv.
According to (14) this would go on indefinitely, as the frequency was
raised continuously. But another effect would come into play, viz., the
increased resistance due to skin-conduction, with a corresponding small
change in L. As the result of this increased resistance the value of
I£l/2Lv will rise, and the range in the fluctuations of / decrease ; and if
the frequency be pushed high enough the fluctuations will tend to
disappear. But this could not happen in telephony at any reasonable
frequency, say n = 20,000.
The physical cause of the low value \El at certain frequencies is the
timing together of the impressed force at the beginning of the circuit
and the reflected waves. It is akin to resonance. Thus, if the line
had no resistance at all we should have
I=Lv$in(nl/v), ............................ (15)
with the circular function taken always positive. When nl/v = 7r,
1=0. Then 27r/n = 2l/v, or the period of the impressed force coincides
with the time of a double transit (to the end of the circuit and
back again).
In connection with (15) I may mention that an approximate formula
for the impedance, when nl/v is in the first quadrant, and especially in
its early part, is
which shows the beginning of the action of the permittance in reducing
the impedance from its magnetic value as the frequency is raised.
But to use wires of such low resistance for comparatively short lines
would be wastefully extravagant. Such wires admit of very long
circuits being worked. Therefore increase the length of the line in
equation (14) ; as we do this the range in the oscillation in / falls,
until, when fil = 2Lv, I does not depend much upon the circular
function. We may then, and at all higher frequencies, write simply
............................. (17)
--
Compare with (8), the corresponding cable-formula, and note the differ-
ences. The impedance is now nearly independent of the frequency,
and there is nearly distortionless transmission of signals, provided H/Ln
be small, and Bl/Lc = 2 or 3 or more.
346
ELECTRICAL PAPERS.
The following table gives the values of p calculated by (14), which
only assumes that RjLn is small, for a series of values of PdjLv = y.
y-
Min. p.
Mean p.
Max. p.
y>
/>•
y>
P-
\
•505
1-500
2-063
6
1-678
12
16-81
•521
•878
1-128
7
2-°65
14
39-3
2
•587
•686
•771
8
3-378
16
93-2
2-0653
•594
•685
•766
9
5-000
18
225
3
•710
•748
•784
10
7-420
20
550
4
•907
•924
•940
5
1-210
1-218
1-226
Here the "mean," "maximum," and " minimum " values of p mean the
values when the cosine is 0, + 1, and - 1. The fluctuations are very
large when y is small, going from \Rl to Lv ; but they are insensible
when y is bigger. Kemember that the line is short-circuited. The
receiving apparatus, by absorbing energy, reduces the fluctuations, and
we shall see later that they can be nearly abolished.
When RljLv — y is variable, the value of IjRl is made a minimum by
taking 7^ = 2-06 Lv, say 2Lv. This is a little over 1200 ohms in our
example of Z = 20; and makes the length of circuit be 600 kilom.,
when the resistance is 2 ohms per kilom. After y = 3 we may disregard
the fluctuations.
Now this length of only 600 kilom. is still far too short to make it
necessary to employ so expensive a wire. One of much higher
resistance would answer quite well enough for practical telephony, in
which a considerable amount of distortion is permissible, because
transmission would be nearly perfect over 600 kilom. according to the
above data. The question arises, upon what principles can we compare
one circuit with another, and is it possible to lay down the law from
theory as to the limiting distance of telephony ? The answer is plainly
that it is not possible, because the types of telephonic circuits differ.
A cable or other circuit with inertia ignored is radically different from
one in which there is a marked approach to elastic wave-propagation.
Even if we fix the type, and take, say, the above example of low
resistance, 2 ohms per kilom. and L = 20 per centim., and the question
be asked, How far can you telephone ? — the answer is that there is no
fixed limit, as it depends upon so many circumstances, some of which
are unstated, and are hardly susceptible of measurement when stated.
Consider, first, the circuit without terminal influences. We may
distinguish two connected, but yet entirely different, things in opera-
tion. We set up electromagnetic vibrations at A somehow, not regular
vibrations of one frequency, but irregular, and of almost any type.
Now, during transmission along the circuit, the vibrations are attenuated
for one thing, and distorted, or changed in type, for another. With
perfect transmission there would be neither attenuation nor distortion.
This would require perfect conductors, which would not permit the
ON TELEGRAPH AND TELEPHONE CIRCUITS. 347
waves to enter them from the dielectric and be dissipated, but would
let them slip along like greased lightning. Then there is a kind of
circuit which is distortionless, but in which there is considerable attenu-
ation. Here, plainly, any distance can be worked through, provided
the attenuation is not too great. Trial alone could settle how far it
would be practicable with a given type. Coming to more practical
cases, there is the approximately distortionless circuit above described.
Here the attenuation is not nearly so great as in the distortionless
circuit of the same type (that is, only differing in the leakage needed
to remove the remaining distortion), so that the distance to be worked
through is much greater with similarly sensitive instruments, or with
instruments graduated to make the currents received and sounds
produced be about equal in the different cases compared. Here, again,
trial alone can settle how far we may work safely. Supposing, for
instance, we had reached a practical limit with nearly distortionless
transmission, it is clear that we could increase that limit by the simple
expedient of increasing the current sent out or the sensitiveness of the
receiver. So we cannot fix a limit at all on theoretical principles.
But undoubtedly the distortion will increase as the circuit is lengthened
(except in the ideal distortionless circuit) ; this will tend to fix a limit,
though we cannot precisely define it, independently of the attenuation.
Nor should interferences be forgotten, and their distorting effects.
When thousands of miles are in question, many other things may
come in to interfere, all tending to fix a limit. Independently of the
line, too, there are the terminal arrangements to be considered. A
practical limit in a given case might be fixed merely by the inadequate
intensity of the received currents to work the receiver suitably. But
apart from intensity of action, both the transmitter and the receiving
telephone distort the proper "signals" themselves. The distortion
due to the electrical part of the receiver may, however, be minimized
by a suitable choice of its impedance, and especially by making its
inductance the smallest possible consistent with the possession of the
other necessary qualifications. The conditions as regards perfect
silence in reception are also of importance. Finally, there is " personal
equation." It is clear, then, that in such a mixed-up problem as this
is, we cannot safely estimate what amount of distortion is permissible
in transit along the circuit, and how much attenuated and distorted
we may allow the vibrations to become before human speech ceases to
be recognisable as such, and to be intelligibly guessable.
It is, however, surprising what a large amount of distortion is
permissible, not merely on long lines, but on short ones. It is, indeed,
customary, or certainly was on the first introduction of the telephone,
and for long after, for people to enlarge upon the wonderful manner
in which a receiving telephone exactly reproduces, in all details, the
sounds that are communicated to the transmitter, and to be astonished
at the power the disc possesses of doing it, and to explain it by
harmonic analysis, and so forth. Well, the disc does not do it. If it
did, as it would be in quite mechanical obedience to the forces acting
upon it, there would be nothing to wonder at ; or the reason for wonder
348 ELECTRICAL PAPERS.
would be shifted elsewhere. It would be really wonderful if we could
get perfect reproduction of speech. The best telephony is bad to the
critical ear, if a high standard be selected, and not one based upon
mere intelligibility. (As a commentary upon the reports of " perfect
articulation," etc., I may mention that we sometimes see the amusingly
innocent remarks added that even whistling could be heard, and one
voice distinguished from another.) Consider the difficulties in the
way. We cannot even make the diaphragm of the transmitter precisely
follow the vibrations set up by the vocal organs (which vibrations are, by
the way, distorted between the larynx and the diaphragm, though this
is not an important matter), because it is not a dead-beat arrangement,
and responds differently to different tones. Here is one cause of
distortion. A second occurs in trying to make the primary current
variations copy the motion of the diaphragm. A third is in the
transformation to the secondary circuit, though perhaps this and the
last transformation may be taken together with advantage. So to
begin with, we have considerably distorted our signals before getting
them on to the telephone line. Then, there is the distortion in transit,
which may be very little or very great, according to the nature of the line.
Next, the received-current variations ought to be exactly copied by the
magnetic stress between the disc and magnet of the receiver. But the
inductance of the receiver prevents that, even if the resistance be
suitably chosen to nearly stop the reaction of the instrument on the
line. Then we should get the disc of the telephone to exactly copy
the magnetic- force variations, which it cannot do at all well, on account
of the want of dead-beatness, and the augmentation of certain tones
and weakening of others. The remaining transformations, from the
brain to the vocal organs at one end, and from the disc to the brain
via the air and ear at the other end of the circuit, we need not consider.
And yet, after all these transformations and distortions, practical
telephony is possible. The real explanation is, I think, to be found
in the human mind, which has been continuously trained during a
lifetime (assisted by inherited capacity) to interpret the indistinct
indications impressed upon the human ear ; of which some remarkable
examples may be found amongst partially deaf persons, who seem to
hear very well even when all they have to go by (which practice makes
sufficient) is as like articulate speech as a man's shadow is like the man.
In connection with these transformations, I may mention that one
of them, viz., in the telephone receiver itself, was until recently un-
explained. Writers have before now remarked upon the necessity of a
permanent magnetic field, and speculated as to its cause, and recently
Prof. Silvanus Thompson recalled attention to the matter, and candidly
confessed his ignorance of the explanation, beyond what was furnished
by M. Giltay, who had also considered the matter, and found that the
permanent field was needed to eliminate the vibrations of doubled
frequency that would result were there no permanent field. This is
true in a sense ; but it is not the really important part of what is,
I think, the true explanation, because the vibrations of doubled
frequency would be very feeble. What the permanent field does is
ON TELEGRAPH AND TELEPHONE CIRCUITS. 349
to vastly magnify the effect of the weak telephonic currents, and make
them workable. The disc is attracted by the magnet, and the stress
between them varies as the square of the intensity of magnetic force in
the intermediate space. We want the disc to vibrate sensibly by very
weak variations of magnetic force. If the permanent magnet were not
there, we should have insensible vibrations of doubled frequency. But
the permanent field makes the stress-variations vary as the product of
the intensity of the permanent field and that of the weak variation due
to the current-variations ; they are therefore proportional to the received
current-variations, and are also greatly magnified, so that the telephone
becomes efficient. [See Art. xxxvi., vol. n., p. 155.]
Returning to the telephone-circuit itself, the following would appear
to be what should be aimed at (apart from improvements in terminal
transmission and reception) in efficient long-distance telephony. Setting
up an arbitrary train of disturbances at one end, causing the despatch
of a continuously varying train of waves into the circuit, the waves
should travel to the distant end of the line as little distorted as possible,
and with as nearly equal attenuation as possible, which attenuation
should not be too great ; and, finally, on reaching the terminal
telephone, the waves should be absorbed by it, as nearly as possible,
without reflex action. This ideal may be illustrated by a long cord,
along which we can, by forcibly agitating one end, despatch a train
of waves, which travel along it only slightly distorted, and which
should then be absorbed by some mechanical arrangement at the
further end. Theoretically this only needs the further end to have its
motion resisted by a force proportional to its velocity, the coefficient
of resistance depending upon the mass and tension of the cord.
At any intermediate point we may correctly register the disturbances
passing it. It is evident that the reflected wave from the distant end
should be done away with, in order that the disturbances passing (and
reaching the distant end) may be a correct copy of those originally
despatched. This ideal state of things is fairly-well reached in the
fourth class of circuits above mentioned, and perfectly in the fifth
class, whilst the low-resistance long-distance circuits introduced in
America are somewhere between the third and the fourth classes.
In passing from the fourth class to the third, by increasing the
resistance of the line from very low to more common values, the effect
is to introduce a considerable amount of distortion which may be
(somewhat imperfectly) ascribed to electrostatic retardation. The
limiting distance of telephony will therefore now depend more upon
the circuit itself (apart from terminal arrangements) than before. Still
we cannot fix it. Only by passing to the extreme case of such high
resistance of the line acting in conjunction with the permittance that
the effect of inertia is really insensible, do we so magnify the effect of
the distortion in transit as to make the limiting distance be determined
approximately by the value of the electrostatic time-constant JtSl2.
We now come to the first class we began with, and Sir W. Thomson's
law of the squares may be applied in making comparisons. The dis-
tortion in transit is very great, if the line be long, and we therefore to
350
ELECTRICAL PAPERS.
some extent swamp the terminal apparatus as regards the total dis-
tortion.
But there is only a tendency to the electrostatic theory, not a com-
plete fulfilment. In the case of a cable of the Atlantic type, used as a
telephone-circuit (of course not across the Atlantic) the resistance is
rather low, and this is quite sufficient, in conjunction with the induct-
ance, to greatly improve matters from the electrostatic theory, in spite
of the large permittance. In fact, a small amount of inductance is
sufficient to render telephony possible under circumstances which would
preclude possibility were it non-existent. To show this, consider the
following table : —
n.
L=0.
L = 2'5.
L=5.
£ = 10.
1250
1-723
1-567
1-437
1-235
2500
3-431
2-649
2-251
1-510
5000
10-49
5-587
3-176
1-729
10,000
58-87
10-496
4-169
1-825
20,000
778
16-707
4-670
1-854
In the first column we have the frequency-constant n — ITT x frequency,
so that the frequency ranges through four octaves. It is supposed that
the resistance is 4 ohms and the permittance J microf. per kilom., being
somewhat like what obtains in an Atlantic cable. The remaining
columns show the values of the equivalent impedance p at the distant
end according to the already-given formula (4), with the values of L
given at the tops of the columns. (Take # = 0 in (4).)
Thus in the second column we have the figures given by the electro-
static theory, showing such an extremely rapid increase of attenuation
with the frequency that telephony would I think be quite impossible.
But the third column shows that the small inductance of 2-5 per
centim. immensely improves matters, especially with the great fre-
quencies.
The fourth column, with L = 5, shows a far greater improvement,
and I should think good telephony would be possible.
The fifth column, with L = W, is very remarkable, as it shows an
approach to distortionless transmission.
This remarkable result is wholly due to the inductance, in presence
of the rather low resistance. Whereabouts the effective inductance
really lies it is hard to say, but it must surely be greater than 2-5,
though it may not be much more, as the iron sheathing does not make
the effective L run up in the way that might be supposed at first sight.
With Z = 0, n = 10,000 makes /> = 58, or the received current 1/58 of
the steady current. To have the same result in our low-resistance
circuit, we see by the first table that Pd = \5Lv about does it, giving
HI =15 x 600 = 9000 ohms, and Z = 4500 kilom. Now is it possible to
work a telephone fairly well through a mere resistance of 58 x 9000 or
say 50,000 ohms (ignoring complications due to the telephone not
being a mere resistance), remembering that our currents will be fairly
ON TELEGRAPH AND TELEPHONE CIRCUITS. 351
uniformly attenuated ? If so, then this circuit of 4500 kilom. will work
with good articulation, under favourable conditions — freedom from
interferences, etc. But I do not fix this limit, nor any, for reasons
before given.
This difference should be noted. In the case of the cable of no
inductance, the reduction to 1/58 part applies only to %=10,000. If
?i=1250, at the lower limit, the reduction is only to 10/17 of the
steady current ; thus there is plenty of sound, but very inarticulate.
This is the reverse of what occurs in our other case, in which there is
little sound, but with good articulation, and therefore usefully admitting
of magnification.
If, on the other hand, we take the electrostatic time-constant as *02
second, the attenuation at n = 10,000 is, by the second table, to 1/778 of
the steady current ; and this value, by the first table, gives PdjLv = say
20, and HI— 12,000 and £ = 6000 kilom., and the equivalent impedance
= 778 x 12,000 ohms. Of course this is excessively large. If com-
ponent vibrations on a cable really suffer attenuation to 1/778 part,
such vibrations might as well be altogether omitted, leaving only the
lower tones. On the other hand, a sufficient magnification in the
6000 kilom. case would render telephony possible. But the probable
fact is that '01 second with L — Q is not possible, far less '02 second.
When it is said to be done, the reason is that L is not zero. In the
north of England examples there are usually buried wires and overhead
wires in sequence, so that it is still more true that self-induction comes
in to help, although the theory of such composite circuits cannot be
easily brought down to numerical calculation.
But, returning to the 4500 kilom. example, it appears reasonable that
the circuit might be worked under favourable circumstances. Let us
see what its electrostatic time-constant is. We get, by (11), SQ
microf. per kilom. Hence
which is no less than 22 times the supposed maximum of -01 second.
Even if we make a large allowance, and suppose that an attenuation to
^ part only of the steady current, instead of -£% part, is the utmost
allowable, we shall see by the table that this makes Pd = \\Lv (instead
of the previous 15), so that the electrostatic time-constant is still a
large multiple of the value -01 obtained by observation of wires of high
resistance.
Again, to contrast the two theories, let us inquire what length of line
makes '01 sec. the electrostatic time-constant. The result is 300^10
or say 900 kilom., of resistance 1800 ohms, which is only three times Lv ;
so that there is nearly perfect transmission on the line of low resistance,
whilst there is extreme distortion on the circuit having the same electro-
static time-constant if destitute of inductance.
Since there is a minimum value of the attenuation-ratio I/ HI when
the ratio El/Lv is variable, let it be merely L that is variable, without
change of length or resistance. This may be done by simply varying
352 ELECTRICAL PAPERS.
the distance between the two wires in the circuit. The minimum
attenuation at the distant end comes about (by first table) when
Rl El JRlohms
When / = 600 kilom. we have L = 20, as we saw before. If / = 300 kilom.,
then L = 1 0, which change is easily made by bringing the wires closer.
But if I = 1200 kilom., we require L = 40, and a wide separation is neces-
sary, according to equation (12). But there is another thing to be
remembered. The distance between the wires should continue to be a
small fraction of the height above the ground, in order that the property
LSv2 = 1 should remain fairly true. Although the permittance does not
appear explicitly in formula (14), it is implicitly present in v, and in
such a way that a doubling of S and halving of L are equivalent. (But
this does not apply to the table, where L and S may vary independently.)
Now, if we separate wires very widely without raising them any higher,
S tends to become simply the reciprocal of the sum of the elastances
from the first wire to earth and from the earth to the second wire ;
that is, half the permittance of either. It therefore tends to constancy
instead of varying inversely as L, which goes on increasing slowly as
the wires are further separated. Hence the necessity of raising the
wires, as well as of separating them, if the full advantage of L is to be
secured when it is large.
In passing, I may add that if the earth were perfectly conducting, so
as to shut out the magnetic field from itself, the product LSv'2, where L
is the inductance of the dielectric and S its permittance, calculated so
as to suit the propagation of plane-waves, would remain unity always,
however the wires were shifted, provided parallelism were maintained.
It seems at first sight anomalous that when the permittance is so
small that we might expect the common magnetic formula to apply, we
should increase the amplitude of current of any (not too low) frequency
by increasing the inductance. It seems to show how careful we should
be not to extend too widely the application of professedly approximate
formulae. Equation (4) has quite different significations under varied
circumstances ; and, general as it is, it is yet not general enough to
meet extreme cases, even when, as in my original statement of it (The
Electrician, July 23, 1886) [vol. II., p. 61], the increased resistance
and reduced inductance due to the tendency towards skin-conduction
are allowed for. Besides the propagation of disturbances through the
dielectric following the wires, after the manner of plane- waves, there is
an outward propagation from the source of energy, which seems to me,
however, to be quite a secondary matter, and insignificant, especially
when the circuit is a metallic loop, which concentrates the electro-
magnetic field considerably. But when there is an earth-return, there
is a wide extension of the magnetic field, and distances from the line
should be compared with its length, in making estimates of the range of
disturbances of appreciable magnitude, appreciable by cumulative action
on a distant wire. There are also the modifications due to the presence
of neighbouring wires, which may be calculated by the equations of a
ON TELEGEAPH AND TELEPHONE CIRCUITS. 353
system of parallel wires. But perhaps the most important modifying
influence of all is that of the terminal apparatus.
I have considered the effect of any terminal apparatus in my paper,
" On the Self-induction of Wires," Part V., [vol. IL, p. 247]. It is very
complex in general. But so far as relates to a long circuit of low resist-
ance, we do not want the full formulae. Take (17) as the formula
when the wires are short-circuited at the sending and receiving ends.
Then, when we put on terminal apparatus containing no impressed
force except the one sinusoidally varying force at the beginning of the
circuit, (which may be in any part of the main circuit of the terminal
apparatus there), the result is to alter the attenuation-ratio from the
former /> to pv given by
ft-pxejxflf, ............................ (19)
where G$ and G$ are the terminal factors for the sending and receiving
ends, to be calculated in the following manner. Let R^ and L^ be the
" effective " resistance and inductance of the apparatus at the receiving
end, then
(20)
without assumptions regarding the size of / and g. Now take g = 0,
and / a small fraction, and we reduce (20), when the fraction fLfl/Lv
is small, to
G^l+EJLv ............................ (21)
Therefore (19) becomes
P^bLv.e^l+EJLv^l+BJLv) ................ (22)
Note that the full expression for G0 is obtainable from (20) by changing
A\ and L^ to RQ and LQ. But if we only assume / to be small and g
zero, then, instead of (21), we have
£1 = (1 + El/Lv^ + (Lln/Lv)(L1n/Lv-f)+f2(Rl/Lv) ......... (23)
Now let it be merely a telephone that is the receiving apparatus, of
resistance and inductance R1 and Llt or something equivalent to a mere
coil. If it be a mere coil, and also, though less easily, if a telephone,
we may vary L^ independently by changing the form of the coil or by
inserting non-conducting iron. We see, then, that the terminal factor
is made a minimum, with L^ alone variable, when
which, with 72 = 204 and w=104 makes 2Z1 = 606, quite a reasonable
value for a small telephone. But if w = 203, the result is 1507, twenty-
five times as large.
Next let it be, not the current, but the magnetic force of the coil
that is a maximum, on the assumption that L-JRy the time-constant of
the coil, is fixed. This is nearly true when the size of the wire is
varied, if it be a mere coil that is concerned, and is an approach to the
H.E.P.— -VOL. II. Z
354 ELECTRICAL PAPERS.
truth when there is iron. It is now Gl/Rl that has to be a minimum,
subject to RiJL-L = constant. This happens when
)* = Li>, ........................... (24)
or when the impedance of the coil equals the critical Lv.
I showed in my paper " On Electromagnets," etc. [Art. xvn., vol. I.,
p. 99], that in the magnetic theory the condition of maximum magnetic
force of the coil is that its impedance should equal that of the rest of
the circuit, which contains the impressed force. We may easily verify
that Lv is the impedance in the present case (with / small). Now
Lv = 600 ohms when L = 20 ; this is the extreme value of the resistance
of the coil, which should really be less on account of the term L^n.
For instance, if the time-constant be '0002 second, and ?i=104, we
require 2'24:Bl = Lv. We see further that this does make fL-^n/Lv
small, because / is small, and LlnjLv< 1. Therefore, using (23), we
have
nW)-}, ........... (25)
which, with % = 104 and the time-constant a = -0002, becomes G% = 1*7.
This is, of course, a far larger value of the terminal factor than need
be. In fact, the conditions of maximum magnetic force of the coil and
of maximum received current are not usually identical, and may be
quite antagonistic. For instance, if we should make the terminal
factor nearly unity, we should have the biggest current, but with the
least power.
But a remarkable property should be mentioned, which may be
proved by the general formula from which (19) is derived. It is that
if the receiver be a mere resistance, the choice of its resistance to equal
Lv will, when RjLn is small, nearly annihilate the reflected wave, and
so do away with the fluctuations and the distortion due to them,
whether the circuit be a long or a short one. Under these circum-
stances we have practically perfect reception of signals.
The general condition making G^R a minimum on a long circuit,
subject to constancy of a, is by (19) and (20),
The right member expresses the square of the impedance of the circuit to
a S.H. impressed force at its end. When/ and g are small we obtain the
former result. The property of equal impedances is, however, a general
one, so that all we do in verifying it is to see that no glaring error has
crept in. If a coil connect two points of any arrangement in which a
S.H. state is kept up by impressed force, and we vary the size of wire
without varying the size and shape of the coil, we bring the magnetic
force of the coil to a maximum by making its impedance equal to that
external to it, if the thickness of covering vary similarly to that of the
wire.
RESISTANCE AND CONDUCTANCE OPERATORS. 355
XLIL ON RESISTANCE AND CONDUCTANCE OPERATORS,
AND THEIR DERIVATIVES, INDUCTANCE AND PER-
MITTANCE, ESPECIALLY IN CONNECTION WITH
ELECTRIC AND MAGNETIC ENERGY.
[Phil. Mag., December, 1887, p. 479.]
General Nature of the Operators.
1. IF we regard for a moment Ohm's law merely from a mathematical
point of view, we see that the quantity E, which expresses the resist-
ance, in the equation V=RC, when the current is steady, is the
operator that turns the current C into the voltage V. It seems, there-
fore, appropriate that the operator which takes the place of R when
the current varies should be termed the resistance-operator. To
formally define it, let any self-contained electrostatic and magnetic
combination be imagined to be cut anywhere, producing two electrodes
or terminals. Let the current entering at one and leaving at the other
terminal be C, and let the voltage be P] this being the fall of potential
from where the current enters to where it leaves. Then, if V= ZC be
the differential equation (ordinary, linear) connecting V and C, the
resistance-operator is Z.
All that is required to constitute a self-contained system is the
absence of impressed force within it, so that no energy can enter or
leave it (except in the latter case by the irreversible dissipation con-
cerned in Joule's law) until we introduce an impressed force; for
instance, one producing the above voltage J^at a certain place, when
the product VQ expresses the energy-current, or flux of energy into the
system per second.
The resistance-operator Z is a function of the electrical constants of
the combination and of d/dt, the operator of time-differentiation, which
will in the following be denoted by p simply. As I have made ex-
tensive use of resistance-operators and connected quantities in previous
papers,* it will be sufficient here, as regards their origin and manipu-
lation, to say that resistance-operators combine in the same way as if
they represented mere resistances. It is this fact that makes them of
so much importance, especially to practical men, by whom they will be
much employed in the future. I do not refer to practical men in the
very limited sense of anti- or extra-theoretical, but to theoretical men
who desire to make theory practically workable by the ' simplification
and systematisation of methods which the employment of resistance-
operators and their derivatives allows, and the substitution of simple
for more complex ideas. In this paper I propose to give a connected
account of most of their important properties, including some new ones,
especially in connection with energy, and some illustrations of extreme
cases, which are found, on examination, to " prove the rule."
2. If we put p = 0 in the resistance-operator of any system as above
defined, we obtain the steady resistance, which we may write ZQ. If
all the operations concerned in Z involve only differentiations, it is
* Especially Part III. , and after, "On the Self-induction of Wires," [vol. n.,
pp. 201 to 361 generally. Also vol. I., p. 415].
356 ELECTRICAL PAPERS.
clear that when C is given completely, V is known completely. But if
inverse operations (integrations) have to be performed, we cannot find
V immediately from C completely ; but this does not interfere with the
use of the resistance-operator for other purposes.
It is sometimes more convenient to make use of the converse method.
Thus, let Y be the reciprocal of Z, so that C = YV. If we make p
vanish in Y, the result, say YQ) is the conductance of the combination.
Therefore F is the conductance -operator.
The fundamental forms of Y and Z are
................................. (1)
(2)
In the first case, it is a coil of resistance R and inductance L that is in
question, with the momentum LC and magnetic energy ^LC2. In the
second case, it is a condenser of conductance K and permittance S, with
the charge iSFand electric energy ^SF2 ; or its equivalent, a perfectly
nonconducting condenser having a shunt of conductance K.
In a number of magnetic problems (no electric energy) the resistance-
operator of a combination, even a complex one, reduces to the simple
form (1). The system then behaves precisely like a simple coil, so far
as externally impressed force is concerned, and is indistinguishable
from a coil, provided we do not inquire into the internal details. I
have previously given some examples.* Substituting condensers for
coils, permittances for inductances, we see that corresponding reductions
to the simple form (2) occur in electrostatic combinations (no magnetic
energy).
But such cases are exceptional; and, should a combination store
both electric and magnetic energy, it is not possible to effect the above
simplifications except in some very extreme circumstances. There are,
however, two classes of problems which are important practically, in
which we can produce simplicity by a certain sacrifice of generality.
In the first class the state of the whole combination is a sinusoidal or
simple-harmonic function of the time. In the second class we ignore
altogether the manner of variation of the current, and consider only
the integral effects in passing from one steady state to another, which
are due to the storage of electric and magnetic energy.
S.H. Fixations, and the effective K', I/, K', and S'.
3. If the voltage at the terminals be made sinusoidal, the current
will eventually become sinusoidal in every part of the system, unless it
be infinitely extended, when consequences of a singular nature result.
At present we are concerned with a finite combination. Then, if nftir
be the periodic frequency, we have the well-known property p2 = - n2 ;
which substitution, made in Z and F, reduces them to the forms
................................... (3)
.................................. (4)
* "On the Self-induction of Wires," Parts VI. and VII. [vol. n., pp. 268 and
292.]
RESISTANCE AND CONDUCTANCE OPERATORS. 357
where Rf, Z/, Kf, Sf are functions of the electrical constants and of w2,
and are therefore constants at a given frequency.
In the first case we compare the combination to a coil whose resist-
ance is R' and inductance Lf, so that Rf and L' are the effective resist-
ance and inductance of the combination, originally introduced by Lord
Rayleigh* for magnetic combinations. In my papers, however, there is
no limitation to cases of magnetic energy only,f and it would be highly
inconvenient to make a distinction.
In a similar way, in the second case we compare the combination to
a condenser, and we may then call Kf the effective conductance and Sf
the effective permittance at the given frequency. R' reduces to Z^
and Kf to YQ at zero frequency. But it is important to remember that
the two comparisons are of widely different natures : and that the
effective resistance [in the coil-comparison] is not the reciprocal of the
effective conductance [in the condenser-comparison].
Fand Z in (3) and (4) are reciprocal, or YZ= 1, just as the general
Y and Z of (1) and (2) are reciprocal.
If (V) and (C) denote the amplitudes of Fand (7, we have, by (3)
and (4),
= I, say, ..................... (5)
, say ...................... (6)
/ and / are also reciprocal. The former, /, being the ratio of the force
to the flux (amplitudes), is the impedance of the combination. It is
naturally suggested to call / the " admittance " of the combination.
But it is not to be anticipated that this will meet with so favourable a
reception as impedance, which term is now considerably used, because
the methods of representation (1), (3), and (5) are more useful in
practice than (2), (4), and (6) ; although theoretically the two sets are
of equal importance. }
To obtain the relations between R' and Kr, and Lf and /S", we have
.................... (7)
', .................... (8)
from which we derive
i
\ ............
, }
(9)
R'\K' = P = - L'l&,
all of which are useful relations.
* Phil. Mag., May, 1886.
t In Part V. of " On the Self -Induction of Wires " I have given a few examples
of mixed cases of an elementary nature, in connexion with the problem of finding
the effect of an impressed force in a telegraph circuit.
% The necessity of the term impedance (or some equivalent) to take the place of
the various utterly misleading expressions that have been used, has come about
through the wonderful popularisation of electromagnetic knowledge due to the
dynamo, and its adoption to Sir W. Thomson's approval of it and of one or two
other terms.
358 ELECTRICAL PAPERS.
4. By (3) and (4) we have the equations of activity
(10)
....................... (11)
in general. Now, if we take the mean values, the differentiated terms
go out, leaving
VC = R'~& = K'V\ ............................ (12)
the bars denoting mean values. The three expressions in (12) each
represent the mean dissipativity, or heat per second. E' and K' are
therefore necessarily positive. It should be noted that RfC* or K'V^
do not represent the dissipativity at any moment. The dissipativity
fluctuates, of course, because the square of the current fluctuates ; but
besides that, there is usually a fluctuation in the resistance, because the
distribution of current varies, and it is only by taking mean values that
we can have a definite resistance at a given frequency.
If the combination be magnetic, and T denote the magnetic energy,
its mean value is given by
T=$I/C*t ............................... (13)
so that Lf is necessarily positive and Sf negative. But ^I/CZ is not
usually the magnetic energy at any moment.
If the combination be electrostatic, and U denote the electric energy,
its mean value is
Z7=i£'F2, ............................. (14)
so that S' is positive and U negative. The electric energy at any
moment is not usually ±S'V**.
But, in the general case of both energies being stored, we have
T- U=$UC*=-\S'V*. ....................... (15)
If the mean magnetic energy preponderates, the effective inductance
is positive, and the permittance negative ; and conversely if the electric
energy preponderates. If there be no condensers, the comparison
with a coil is obviously most suitable, and if there be no magnetic
energy we should naturally use the comparison with a condenser ; but
when both energies coexist, which method of representation to adopt is
purely a matter of convenience in the special application concerned.
If the mean energies, electric and magnetic, be equal, then
I/ = 0 = 8', R'K'=\, I=R', J = K' ............ (16)
That is, by equalising the mean energies we bring the current and
voltage into the same phase, annihilate the effective inductance (and
also permittance), and make the effective conductance the reciprocal of
the effective resistance, which now equals the impedance itself. It
should be noted that the vanishing of the energy-difference only refers
to the mean value. The two energies are not equal and do not vanish
simultaneously. Sometimes, however, their sum is constant at every
moment, but this is exceptional. (Example, a coil and a condenser in
sequence.)
RESISTANCE AND CONDUCTANCE OPERATORS. 359
Impulsive Inductance and Permittance. General Theorem relating to the
Electric and Magnetic Energies.
5. Passing now to the second class referred to in § 2, imagine, first,
the combination to be magnetic, and that V is steady, producing a
steady (7, dividing in the system in a manner solely settled by the dis-
tribution of conductivity. Although we cannot treat the combination
as a coil as regards the way the current varies when the impressed force
is put on, we may do so as regards the integral effect at the terminals
produced by the magnetic energy. The last is the well-known
quadratic function of the currents in different parts of the system,
T=\L£l + MC& + \L£\ + (17)
Now put every one of these C"s in terms of the C, the total current at
the terminals, which may be done by Ohm's law. This reduces T to
T=$L0C*, (18)
where LQ is a function of the real inductances, self and mutual, of the
parts of the system, and of their resistances. This L0 may be called the
impulsive inductance of the system. For although it is, in a sense, the
effective steady inductance, taking the current C at the terminals as a
basis, being, in fact, the value of the sinusoidal inductance Lr at zero
frequency; yet, as it is only true for impulses that the combination
behaves as a coil of inductance Z0, it is better to signify this fact in the
name, to avoid confusion. This will be specially useful in the more
general case in which both energies are concerned.
Secondly, let the system be electrostatic. Then, in a similar way, we
may write the electric energy in the form
U=iS^, (19)
in terms of the T^at the terminals, where S0 is a function of the real
permittances and of the resistances. $0 is the impulsive permittance of
the combination. It is also the sinusoidal Sr at zero frequency.
In (18) LQ is positive, arid in (19) $0 is positive. The momentum or
electromotive impulse [or the voltaic impulse, if we use the modern
"voltage" to signify the old "electromotive force"] at the terminals in
the former case is L0C, and in the latter case is - S^RV, where R is the
steady resistance. The true analogue of momentum, however, is charge,
or time-integral of current, and this, at the terminals, is - $0 V, corre-
sponding to LQC.
6. Passing to the general case, and connecting with the resistance-
operator, let F be the current at the terminals at time t when varying,
so that
F-&m(fi+'pBi+&*F+..;.W (20)
where the accents denote differentiations to p, and the zero suffixes
indicate that the values when p = 0 are taken. The coefficients of the
powers of p are therefore constants. Integrating to the time,
+ $zi'[t] + (21)
360 ELECTRICAL PAPERS.
If the current be steady at beginning and at end,
^(F-zQr)dt=z>[ri .......................... (22)
and if the initial current be zero, and the final value be C,
^C; ........................... (23)
so that ZQ€ is the voltaic impulse employed in setting up the magnetic
and the electric energy of the steady state due to steady V at the
terminals. Thus
L0 = Z'0 ................................. (24)
finds the impulsive inductance from the resistance-operator. Or,
LQ = (Z-ZQ)p~'i with p = Q .................... (25)
In a similar manner, we may show that
S0 = F{= -Z?Z[ ............................ (26)
finds the impulsive permittance from the conductance-operator. LQC
and -iS0^0Fare equivalent expressions for the voltaic impulse.
If ZQ should be infinite, then use Y. For instance, the insertion of a
nonconducting condenser of permittance Sl in the main circuit of the
current makes Z0 infinite, since the resistance-operator of the condenser
is (Stf)'1. There is no final steady current, and LQ is infinite. We
should then use (26) instead of (24), especially as the energy is wholly
electric in the steady state.
7. To connect with the energy, multiply (23) by (7, the final current,
and, for simplicity, let V be steady ; giving
((7-RT}Cdt=Z^=(F(C-T)dt ................ (27)
It may be anticipated from the preceding that these equated quantities
express twice the excess of the magnetic over the electric energy.
In connexion with this I may quote from Maxwell, vol. ii., art. 580.
A purely electromagnetic system is in question. "If the currents are
maintained constant by a battery during a displacement in which a
quantity of work, W, is done by electromotive force, the electrokinetic
energy of the system will be at the same time increased by W. Hence
the battery will be drawn upon for a double quantity of energy, or 2/F,
in addition to that which is spent in generating neat in the circuit.
This was first pointed out by Sir W. Thomson. Compare this result
with the electrostatic property in art. 93." The electrostatic property
referred to relates to conductors charged by batteries. If " their poten-
tials are maintained constant, they tend to move so that the energy of
the system is increased, and the work done by the electrical forces
during the displacement is equal to the increment of the energy of the
system. The energy spent by the batteries is equal to double of either
of these quantities, and is spent half in mechanical, half in electrical
work."
Although of a somewhat similar nature, these properties are not
RESISTANCE AND CONDUCTANCE OPERATORS. 361
what is at present required, which is contained in the following general
theorem given by me* : — Let any steady impressed electric forces be
suddenly started and continued in a medium permitting linear relations
between the two forces, electric and magnetic, and the three fluxes —
conduction current, electric displacement, and magnetic induction (but
with no rotational property allowed, even for conduction current) ; the
whole work done by the impressed forces during the establishment of
the steady state exceeds what would have been done had this state been
instantly established (but then without any electric or magnetic energy)
by twice the excess of the electric over the magnetic energy. That is,
(28)
where e stands for an element of impressed force, F the current-density
at time t, F0 the final value, and 2 the space-integration to include all
the impressed forces. (Black letters for vectors.) The theorem (28)
seems the most explicit and general representation of what has been
long recognised in a general way, that permitting electric displacement
increases the activity of a battery, whilst permitting magnetisation
decreases it. The one process is equivalent to allowing elastic yielding,
and the other to putting on a load (not to increasing the resistance, as
is sometimes supposed).
Applying (28) to our present case of one impressed voltage V, pro-
ducing the final current C, we obtain
T), ,...(29)
comparing which with (27), we see that
T- U-WP-tLjP- - JS0F* (30)
confirming the generality of our results.
General Theorem of Dependence of Disturbances solely on the Curl of the
Impressed Forcive.
8. It is scarcely necessary to remark that the properties of Z and Zf
previously discussed do not apply merely to combinations consisting of
coils of fine wire and condensers ; the currents may be free to flow in
conducting masses or dielectric masses. Solid cores, for example, may
be inserted in coils within the combination. The only effect is to make
the resultant resistance-operator at a given place more complex.
But a further very remarkable property we do not recognise by
regarding only common combinations of coils and condensers. If we,
in the complex medium above defined, select any unclosed surface, or
surface bounded by a closed line, and make it a shell of impressed
voltage (analogous to a simple magnetic shell), thereby producing a
potential-difference V between its two faces, and C be the current
through the shell in the direction of the impressed voltage, there must
be a definite resistance-operator Z connecting them, depending upon
* Electrician, April 25, 1885, p. 490, [vol. i., p. 464.]
362 ELECTRICAL PAPERS.
the distribution of conductivity, permittivity, and inductivity through
all space, and determinable by a sufficiently exhaustive analysis. The
remarkable property is that the resistance-operator is the same for any
surfaces having the same bounding-edge. For a closed shell of im-
pressed voltage of uniform strength can produce no flux whatever.
This is instructively shown by the equation of activity,
........................... (31)
indicating that the sum of the activities of the impressed forces, or the
energy added to the system per second, equals the total dissipativity Q,
plus the rate of increase of the stored energies, electric and magnetic,
throughout the system. Now here F is circuital; if, therefore, the
distribution of e be polar, or e be the vector space-variation of a single-
valued scalar potential, of which a simple closed shell of impressed
force is an example, the left member of (31) vanishes, so that the dis-
sipation, if any, is derived entirely from the stored energy. Start,
then, with no electric or magnetic energy in the system ; then the
positivity of Q, U, and T ensures that there never can be any, under
the influence of polar impressed force. Hence two shells of impressed
force of equal uniform strength produce the same fluxes if their edges
be the same ; not merely the steady fluxes possible, but the variable
fluxes anywhere at corresponding moments after commencing action.
The only difference made when one shell is substituted for the other is
in the manner of the transfer of energy at the places of impressed force;
for we have to remember that the effective force producing a flux, or
the "force of the flux," equals the sum of the impressed force and the
" force of the field " ; whereas the transfer of energy is determined by
the vector product of the two forces of the field, electric and magnetic
respectively. In (31) no count is taken of energy transferred from one
seat of impressed force to another, reversibly, all such actions being
eliminated by the summation.
It is well to bear in mind, when considering the consequences of this
transferability of impressed force, especially in cases of electrolysis or
the Volta-force, not only that the three physical properties of con-
ductivity, permittivity, and inductivity, though sufficient for the state-
ment of the main facts of electromagnetism, are yet not comprehensive,
but also that they have no reference to molecules and molecular actions;
for the equations of the electromagnetic field are constructed on the
hypothesis of the ultimate homogeneity of matter, or, in another form,
only relate to elements of volume large enough to allow us to get rid of
the heterogeneity.
As the three fluxes are determined solely by the vorticity (to borrow
from liquid motion) of the vector impressed force, we cannot know the
distribution of the latter from that of the former, but have to find
where energy transformations are going on ; for the denial of the law
that eF not only measures the activity of an impressed electric force e
on the current F, but represents energy received by the electromagnetic
system at the very same place, lands us in great difficulties.
Again, as regards the " electric force of induction." We cannot find
RESISTANCE AND CONDUCTANCE OPERATORS. 363
the distribution through space of this vector from the Faraday-law
that its line-integral in a closed circuit equals the rate of decrease of
induction through the circuit. We may add to any distribution
satisfying this law any polar distribution without altering matters,
except that a different potential function arises. In this case we do
not even alter the transfer of energy. The electric force of the field is
always definite • but when we divide it into two distinct distributions,
and call one of them the electric force of induction, and the other the
force derived from electric potential, it is then quite an indeterminate
problem how to effect the division, unless we choose to make the quite
arbitrary assumption that the electric force of induction has nothing of
the polar character about it (or has no divergence anywhere), when of
course it is the other part that possesses the whole of the divergence.
This fact renders a large part of some mathematical work on the
electromagnetic field that I have seen redundant, as we may write
down the final results at the beginning. In the course of some in-
vestigations concerning normal electromagnetic distributions in space
I have been forcibly struck with the utter inutility of dividing the
electric field into two fields, and by the simplicity that arises by not
doing so, but confining oneself to the actual forces and fluxes, which
describe the real state of the medium and have the least amount of
artificiality about them. Similar remarks apply to Maxwell's vector-
potential A. Has it divergence or not ? It does not matter in the
least, on account of the auxiliary polar force. When the electric force
itself is made the subject of investigation, the question of divergence of
the vector-potential does not present itself at all.
The lines of vorticity, or vortex-lines of the vector impressed force,
are of the utmost importance, because they are the originating places
of all disturbances. This is totally at variance with preconceived
notions founded upon the fluid analogy, which is, though so useful in
the investigation of steady states, utterly misleading when variable
states are in question, owing to the momentum and energy belonging
to the magnetic field, not to the electric current. Every solution
involving impressed forces consists of waves emanating from the vortex-
lines of impressed force (electric or magnetic as the case may be, but
only the electric are here considered), together with the various
reflected waves produced by change of media and other causes. At
the first moment of starting an impressed force the only disturbance
is at the vortex-lines, which are the first lines of magnetic induction.
Examples of the Forced Vibrations of Electromagnetic Systems.
(a). Thus a uniform field of impressed force suddenly started over all
space can produce no effect. For, either there are no vortex-lines at
all, or they are at an infinite distance, so that an infinite time must
elapse to produce any effect at a finite distance from the origin.
(b). Copper and zinc put in contact. Whether the Volta-lbrce be at
the contact or over the air-surfaces away from and terminating at the
contact (if perfectly metallic), the vortex-line is the common meeting-
364 ELECTRICAL PAPERS.
place of air, zinc, and copper ; the first line of magnetic force is there,
and from it the disturbance proceeds into the metals and out into the
air, which ends in the steady electric field.*
Since the vortex-lines or tubes are closed, we need only consider one
at present — say, that due to a simple shell of impressed force. If it be
wholly within a conductor, the initial wave emanating from it is so
rapidly attenuated by the conductivity (the process being akin to
repeated internal reflexions, say reflexion of 9 parts and transmission
of 1 part, repeated at short intervals) that the transmission to a distance
through the conductor (if good) becomes a very slow process, that of
diffusion. Consequently, when the impressed force is rapidly alternated,
there is no sensible disturbance except at and near the vortex-line.
But if there be a dielectric outside the conductor, the moment dis-
turbances reach it, and therefore instantly if the vortex-line be on the
boundary, waves travel through the dielectric at the speed of light
unimpeded, and without the attenuating process within the conductor,
which therefore becomes exposed to electric force all over its boundary
in a very short time ; hence diffusion inward from the boundary. The
electric telegraph would be impossible without the dielectric. It would
take ages if the wire itself had to be the seat of transfer of energy.
(c). In the magnetic theory of the rise of current in a wire we have,
at first sight, an exception to the law that at the first moment there
is no disturbance except at the vortex-lines of impressed force. But it
is that theory which is incorrect, in assuming that there is no displace-
ment. This is equivalent to making the speed of propagation through
the dielectric infinitely great ; so that we have results mathematically
equivalent to distributing the impressed force throughout the whole
circuit, and therefore its vortex-lines over the whole boundary.! In
reality, with finite speed, the disturbances come from the real vortex-
lines in time.
There is still a limitation of the disturbances to the neighbourhood
of the vortex-lines when they are on the boundary of the conductor,
and the periodic frequency is sufficiently great, the impressed force being
within the conductor. [The attenuation by resistance is referred to.]
But in a nonconducting dielectric this effect does not occur, at least
in any case I have examined. On the contrary, as the frequency is
raised, there is a tendency to constancy of amplitude of the waves sent
out from the edge of a simple sheet of impressed force, or from a shell
of vortex-lines of the same, in a dielectric. Very remarkable results
follow from the coexistence of the primary and reflected waves. Thus :
(d). If a spherical portion of an infinitely extended dielectric have a
uniform field of alternating impressed force within it, and the radius a,
the wave-frequency n/2ir, and the speed v be so related that
na na
tan — s= — .
v v
*"Some Remarks on the Volta Force," Journal 8. T. E. d; E., 1885 [vol. I.,
p. 425].
t The Electrician, June 25, 1886, p. 129 [vol. n., p. 60],
RESISTANCE AND CONDUCTANCE OPERATORS. 365
there is no disturbance outside the sphere. There are numerous
similar cases ; but this is a striking one, because, from the distribution
of the impressed force, it looks as if there must be external displacement
produced by it. There is not, because the above relation makes the
primary wave outward from the surface of the sphere, which is a shell
of vorticity, be exactly neutralised by the reflexion, from the centre,
of the primary wave inward from the surface.
(e). If, instead of alternating, the uniform field of impressed force in
(d) be steady, the final steady electric field due to it takes the time
(•/• + a)/v to be established at distance r from the centre. The moment
the primary wave inward reaches the centre, the steady state is set up
there; and as the reflected wave travels out, its front marks the
boundary between the steady field (final) and a spherical shell of
depth 2a, within which is the uncancelled first portion of the primary
wave outward from the surface; which carries out to an infinite
distance an amount of energy equal to that of the final steady electric
field. This is the loss by radiation. (The magnetic energy in this
shell equals half the final electric energy on the whole journey ; the
electric energy in the shell is greater, but ultimately becomes the
same.) In practical cases this energy would be mostly, perhaps wholly
dissipated in conductors.
(/). If a uniformly distributed impressed force act alternatingly
longitudinally within an infinitely long circular cylindrical portion of a
dielectric, the axis is the place of reflexion of the primary wave inward,
and the reflected wave cancels the outward primary wave when
so that there is no external disturbance, except at first. Here a = radius
of cylinder.
(g). There is a similar result when the vorticity of impressed force
takes the place of impressed force in (/).
(h). If the alternating impressed force act uniformly and longi-
tudinally in a thin conducting-tube of radius a, with air within and
without, then
destroys the external field and makes the conduction-current depend
upon the impressed force only. And if we put a barrier at distance x
to serve as a perfect reflector, that is, a tube of infinite conductivity,
JQ(nx/v) = Q
makes the electric force of the field in the inner tube be the exact
negative of the impressed force ; so that there is no conduction-current.
The electromagnetic field is in stationary vibration. If the inner tube
be situated at one of the nodal surfaces of electric force, the vibrations
mount up infinitely.
(i). If, in case (h), the impressed force act circularly about the axis
of the inner tube (which may be replaced by a solenoid of small depth),
/1(wa/v) = 0
destroys the external field, and
J^nx/v) = 0
366 ELECTRICAL PAPERS.
makes the electric force of the field the negative of the impressed force,
and so destroys the conduction -current.
(j). We can also destroy the longitudinal force of the field in a con-
ductor without destroying the external field. Let it be a wire of
steady resistance in a dielectric, and the impressed force in it be
e =: eQ cos nix cos nt
per unit length. Then m = n/v makes e be the force of the flux, in the
wire ; so that the current is Ke, if K be the conductance of unit length.
These examples are mostly selected from a paper I am now writing
on the subject of electromagnetic waves, which I hope to be permitted
to publish in this Journal.
If the electric and magnetic energies, and the dissipation of energy,
in a given system be bounded in their distribution, it is clear that the
resistance operator is a rational function of p. But should the field be
boundless, as when conductors are contained in an infinitely extended
dielectric, then just as complete solutions in infinite series of normal
solutions may become definite integrals by the infinite extension, so
may the resistance-operator become irrational. We may also have to
modify the meaning of the sinusoidal R' from representing mean
resistance only, on account of the never-ceasing outward transfer of
energy so long as the impressed force continues.
Induction-Balances — General, Sinusoidal, and Impulsive.
9. Returning to a finite combination represented by V=ZG, there
are at least three kinds of induction-balances possible. First, true
balances of similar systems, where we balance one combination against
another which either copies it identically or upon a reduced scale,
without any reference to the manner of variation of the impressed
force. Along with these we may naturally include all cases in which
the Z of a combination, in virtue of peculiar internal relations, reduces
to a simpler form representing another combination, equivalent so far
as V and 0 are concerned. The telephone may be employed with
great advantage, and is, in fact, the only proper thing to use, especially
for the observation of phenomena.
There are, next, the sinusoidal-current balances. These are also
true, in being independent of the time, so that the telephone may be
used; but are of course of a very special character otherwise. Here
any combination is made equivalent to a mere coil if L' be positive, or
to a condenser if S' be positive (§§ 3 and 4), and so may be balanced by
one or the other. But intermittences of current cannot be safely taken
to represent sinusoidality, and large errors may result from an assumed
equivalence.
In the third kind of balances it is the impulsive inductance that is
balanced against some other impulsive inductance, positive or negative
as the case may be; or perhaps the impulsive inductance of a com-
bination is made to vanish, by equating the electric and magnetic
energies in it when its state is steady. The rule that the impulsive
balance in a Christie arrangement without mutual induction between
RESISTANCE AND CONDUCTANCE OPERATORS. 367
the four sides is given by equating to zero the coefficient of p in
the expansion of Z-^Z^ - Z^Z.^ in powers of p, where Zv etc. are the
resistance operators of the four sides,* is in agreement with the rule
derived from (24) or (25) above, to make the impulsive inductance of
one combination vanish. Impulsive, or "kick" balances, naturally
require a galvanometer. Even then, however, the method is sometimes
unsatisfactory, when the opposing influences which make up the
impulse are not sufficiently simultaneous, as has been pointed out by
Lord Rayleigh.f
There is also the striking method of cumulation of impulses employed
by Ayrton and Perry, J employing false resistance-balances. It seems
complex, and of rather difficult theory ; but, just as a watch is a
complex piece of mechanism, and is yet thoroughly practical, so
perhaps the secohmmeter may have a brilliant career before it.
Several interesting papers relating to the comparison of inductances
and permittances have appeared lately. It is usually impulsive balances
that are in question, probably because it is not the observation of
phenomena that is required, but a direct, even if rough, measurement
of the inductance or permittance concerned, often under circumstances
that do not well admit of the use of the telephone. Only one of these
papers, however, contains anything really novel, scientifically, viz., that
of Mr. W. H. Preece, F.R.S.,§ who concludes, from his latest researches,
that the "coefficient of self-induction" of copper telegraph-circuits is
nearly zero, the results he gives being several hundred times smaller
than the formula derived from electromagnetic principles asserts it to
be. Here is work for the physicist.
10. To equate the expressions for the electric and magnetic energies
of a combination is, I find, in simple cases, the easiest and most direct
way of furnishing the condition that the impulsive inductance shall
vanish. Thus, if there be but one condenser and one coil, SF'2 = LC2 is
the condition, S and L being the permittance and the inductance
respectively, F the voltage of the condenser, and C the current in the
coil. The relation between V and C will be, of course, dependent upon
the resistances concerned. || But in complex cases, and to obtain the
value of the impulsive inductance when it is not zero, equation (24) is
most useful.
The Resistance Operator of a Telegraph Circuit.
The following illustration of the properties of Z and Z$ is a complex
one, but I choose it because of its comprehensive character, and because
it leads to some singular extreme cases, interesting both mathematically
* "On the Self-induction of Wires," Part VI., Phil. Mag., Feb. 1887 [vol. n.,
p. 263].
t Electrical Measurements, p. 65.
£ Journ. Soc. Tel. Engineers and Electricians, 1887.
§B.A. Meeting, 1887: "On the Coefficient of Self-induction of Iron and
Copper Wires."
|| If the condenser shunts the coil, making V=RC, we get the case brought
before the S.T.E. & E. by Mr. Sumpner, with developments.
368 ELECTRICAL PAPERS.
and in the physical interpretation of the apparent anomalies. Let the
combination be a telegraph-circuit, say a pair of parallel copper wires,
of length / ; resistance /£, permittance S, inductance L, and leakage-
conductance K, all per unit length, and here to be considered strictly
constants, or independent of p. Let the two wires be joined through
an arrangement whose resistance-operator is Z± at the distant end B ;
then the resistance-operator at the beginning A of the circuit is given
by*
z_ (R + Lp)l{(ta,n ml) /ml] + Zl /o.2\
1 + K+ fi/tan mlml
if -m? = (R + Lp)(K+Sp) ....................... (33)
Take Z1 = Q for the present, or short-circuit at B. This makes
Z=(E + Lp)l(tenml)lml, ..................... (34)
and the steady resistance at A is therefore
, .......................... (35)
if — 77^ = RK. Also, differentiating (34) to p, and then making p = 0,
we find
„, T 17tanmJ/r RS\ 17 „ ,/,- RS\ /QAx
Z{ = L0 = $1 mlQ(L - -g) + |l sec%0^Z + _ j ....... (36)
represents the impulsive inductance.
If we put $ = 0 in (36) we make the arrangement magnetic, and then
L0 is positive. If we put L = 0, we make it electrostatic, and LQ is nega-
tive, or S0, the impulsive permittance, is positive. It is to be noticed that
there is no confusion when both energies are present; that is, there
are no terms in Z'Q containing products of real permittances and induct-
ances, which is clearly a general property of resistance-operators,
otherwise the two energies would not be independent.
We may make LQ vanish by special relations. Thus, if there be no
leakage, or JT=0, (36) is
L0 = U-kffl.RSP; ..... .................... (37)
so that the magnetic must be one third of the electrostatic time-
constant to make the "extra-current" and the static charge balance.
(The length of the circuit required for this result may be roughly stated
as about 60 kilometres if it be a single copper wire of 6 ohms per
kilometre, 4 metres high, with return through the ground; but it
varies considerably, of course.)
But if leakage be now added, it will increase the relative importance
of the magnetic energy, so that the length of the circuit requires to be
increased to produce a balance. This goes on until K reaches the
value JKS/L, when, as an examination of (36) will show, the length of
the circuit needs to be infinitely great. The same formula also shows
that if K be still greater, L0 cannot be made to vanish at all, being then
always positive.
*"On the Self-induction of Wires," Part IV., Phil. Mag., Nov., 1886
[vol. TI., p. 232 ; also p. 247 and p. 105.]
RESISTANCE AND CONDUCTANCE OPERATORS. 369
11. Now let the circuit be infinitely long. Equation (35) reduces to
the irrational form
..................... (38)
with ambiguity of sign. Of course the positive sign must be taken.
The negative appears to refer to disturbances coming from an infinite
distance, which are out of the question in our problem, as there can be
no reflexion from an infinite distance. But equation (38) may be
obtained directly in a way which is very instructive as regards the
structure of resistance-operators. Since the circuit is infinitely long, Z
cannot be altered by cutting-off from the beginning, or joining on, any
length. Now first add a coil of resistance 7^ and inductance L^ in
sequence, and a condenser of conductance Kl and permittance S19 in
bridge, at A, the beginning of the circuit. The effect is to increase Z
to Z2, where
Z^{Kl + SlP + (Rl + Llp + Z)-^] .............. (39)
i.e., the reciprocal of the new Z2, or the new conductance-operator,
equals the sum of the conductance-operators of the two branches in
parallel, one the conducting condenser, the other the coil and circuit in
sequence. (39) gives the quadratic
S1p)^ ............ (40)
Now choose RVLVKV Slt in exact proportion to fi,L,K, and S, and then
make the former set infinitely small. The result is that we have added
to the original circuit a small piece of the same type, so that Z2 and Z
are identical, and that the coefficient of the first power of ^2 in (40)
vanishes. Therefore (40) becomes
This fully serves to find the sinusoidal solution. Differentiating it, we
find
corroborating the previous result as to the vanishing of LQ when the
circuit is infinitely long by equality of RS and KL, and the positivity
of L0 when KL>RS.
The Distortionless Telegraph Circuit.
1 2. Now, in the singular case of R/L = K/S, we have, by (41) and (42),
Z=Lv, Z0 = 0, ........................... (43)
if v = (LS)-*, the speed of transmission of disturbances along the circuit.
The resistance-operator has reduced to an absolute constant, and the
current and transverse voltage are in the same phase, altogether
independent of the frequency of wave-period, or indeed of the manner
of variation. The quantity Lv, or L x 30 ohms, approximately, if the
dielectric be air, is strictly, and without any reservation, the impedance
of the circuit at A, but it is only exceptionally the resistance,
IJ.E.P. — VOL. ii. 2 A
370 ELECTRICAL PAPERS.
Make V—f(t)t at A, an arbitrary function of the time ; then, if Vx
and Cx are the transverse voltage and the current at distance x from A
at time t, we shall have
Fx=f(t-xlv)e-w, Cx-=Fx/Lv, (44)
or all disturbances originating at A are transmitted undistorted along
the circuit at the speed v, attenuating at a rate indicated by the
exponential function. (I have elsewhere* full} developed the properties
of this distortionless circuit, and only mention such as are necessary to
understand the peculiarities connected with the present subject-matter.)
The electric and magnetic energies are always equal, not only on the
whole, but in any part of the circuit ; this accounts for the disappear-
ance of LQ, and the bringing of Vx and Cx to the same phase, as we
should expect from § 4. But in the present case Z^ or Lv, or E', for
they are all equal, is only the resistance when the steady state due to
the steady V at A is arrived at (asymptotically), or the effective
resistance at a given frequency when Fis sinusoidal, and sufficient time
has elapsed to have allowed Vx and Cx to become sinusoidal to such a
distance from A that we can neglect the remainder of the circuit into
which greatly attenuated disturbances are still being transmitted.
13. Now, since the impedance is unaltered by joining on at A any
length of circuit of the same type, and is a constant, it follows that the
impedance at A of a distortionless circuit as above described, but of
finite length, stopping at B, where x = l, with a resistance of amount Lv
inserted at B, is also a constant, viz. the same Lv. To corroborate, take
RS = KL and Z^ = Lv in the full formula (32). The result is Z = Lv.
The interpretation in this case is that all disturbances sent from A are
absorbed completely by the resistance at B immediately on arrival,
so that the finite circuit behaves as if it were infinitely long. The
permanent state due to a steady V at A is arrived at in the time l/v.
The impedance and the resistance then become identical.
14. If, in the case of § 12, we further specialize by taking R = Q,
K=Q, producing a perfectly insulated circuit of no resistance, the
impedance is, as before, Lv • but no part of it is resistance, or ever can
be, in spite of the identity of phase of V and C. However long we
may keep on a steady Fat A, we keep the impressed force working at
the same rate, the energy being entirely employed in increasing the
electric and magnetic energies at the front of the wave, which is
unattenuated, and cannot return.
But if we cut the circuit at B, at a finite distance /, and there insert
a resistance Lv, the effect is that, as soon as the front of the wave
reaches B, the inserted resistance immediately becomes the resistance
of the whole combination ; or the impedance instantly becomes the
resistance, without change of value.
15. As a last example of singularity, substitute a short-circuit for the
terminal resistance Lv just mentioned. Since there is now no resistance
in any part of the system, if we make the state sinusoidal everywhere,
* "Electromagnetic Induction and its Propagation," Sections XL. to L., Electri-
cian, 1887 [vol. ii., pp. 119 to 155].
RESISTANCE AND CONDUCTANCE OPERATORS. 371
by V sinusoidal at A, Rf musfc vanish, or V and C be in perpendicular
phases, due to the infinite series of to-and-fro reflexions. We now
have, by (32),
Z' = L^^ = Dp^*M, (45)
ph/v nl/v
if n/2ir = frequency, and Rf has disappeared.
If, on the other hand, V be steady at A, the current increases without
limit, every reflexion increasing it by the amount VjLv at A or at B
(according to which end the reflexion takes place at), which increase
then extends itself to B or A at speed v. The magnetic energy mounts
up infinitely. On the other hand, the electric energy does not, fluctu-
ating perpetually between 0 when the circuit is uncharged, and %SIF2
when fully charged. The impedance of the circuit to the impressed
force at A is Lv for the time 2l/v after starting it; then \Lo for a
second period 21 /v ; then \Lv for a third period, and so on.
It will have been observed that I have, in the last four paragraphs,
used the term impedance in a wider sense than in § 3, where it is the
ratio of the amplitude of the impressed force to the amplitude of the flux
produced at the place of impressed force when sufficient time has elapsed
to allow the sinusoidal state to be reached, when that is possible. The
justification for the extension of meaning is that, since in the distortion-
less circuit of infinite length, or of finite length with a terminal resistance
to take the place of the infinite extension, we have nothing to do with
the periodic frequency, or with waiting to allow a special state to be
established, it is quite superfluous to adhere to the definition of the
last sentence ; and we may enlarge it by saying that the impedance of
a combination is simply the ratio of the force to the flux, when it
happens to be a constant, which is very exceptional indeed. I may
add that R, L, K, and S need not be constants, as in the above, to pro-
duce the propagation of waves without tailing. All that is required is
R/L = K/S, and Li) = constant ; so that R and L may be functions of x.
The speed of the current, and the rate of attenuation, now vary from
one part of the circuit to another.
The Use of the Resistance-Operator in Normal Solutions.
16. In conclusion, consider the application of the resistance-operator
to normal solutions. If we leave a combination to itself without
impressed force, it will subside to equilibrium (when there is resistance)
in a manner determined by the normal distributions of electric and
magnetic force, or of charges of condensers and currents in coils ; a
normal system being, in the most extended sense, a system that, in
subsiding, remains similar to itself, the subsidence being represented
by the time-factor ex, where p is a root of the equation Z=0. It is
true that each part of the combination will usually have a distinct
resistance-operator ; but the resistance-operators of all parts involve,
and are contained in, the same characteristic function, which is merely
the Z of any part cleared of fractions. It is sometimes useful to
remember that we should clear of fractions, for the omission to do so
372 ELECTRICAL PAPERS.
may lead to the neglect of a whole series of roots ; but such cases
are exceptional and may be foreseen; whilst the employment of a
resistance-operator rather than the characteristic function is of far
greater general utility, both for ease of manipulation and for physical
interpretation.
Given a combination containing energy and left to itself, it is upon the
distribution of the energy that the manner of subsidence depends, or
upon the distribution of the electric and magnetic forces in those parts
of the system where the permittivity and the inductivity are finite, or
are reckoned finite for the purpose of calculation. Thus conductors,
if they be not also dielectrics, have only to be considered as regards the
magnetic force, whilst in a dielectric we must consider both the electric
and the magnetic force. (The failure of Maxwell's general equations of
propagation arises from the impossibility of expressing the electric
energy in terms of his potential function. " The variables should always
be capable of expressing the energy.) Now the internal connexions of
a system determine what ratios the variables chosen should bear to one
another in passing from place to place in order that the resultant system
should be normal; and a constant multiplier will fix the size of the
normal system. Thus, supposing u and w are the normal functions of
voltage and current, which are in most problems the most practical
variables, the state of the whole system at time t will be represented by
.................. (46)
V being the real voltage at a place where the corresponding normal
voltage is u, and C the real current where the normal current is w, the
summation extending over all the ^>-roots of the characteristic equation.
The size of the systems, settled by the A's (one for each p) are to be
found by the conjugate property of the vanishing of the mutual energy-
difference of any pair of ^-systems, applied to the initial distributions
of Fand C.
17. To find the effect of impressed force is a frequently recurring
problem in practical applications; and here the resistance-operator is
specially useful, giving a general solution of great simplicity. Thus,
suppose we insert a steady impressed force e at a place where the
resistance-operator is Z, producing e = ZC thereafter. Find C in terms
of e and Z. The following demonstration appears quite comprehensive.
Convert the problem into a case of subsidence first, by substituting a
condenser of permittance S, and initial charge Se, for the impressed
force. By making S infinite later we arrive at the effect of the steady e.
In getting the subsidence solution we have only to deal with the energy
of the condenser, so that a knowledge of the internal connexions of the
system is quite superfluous.
The resistance-operator of the condenser being (Sp)~l, that of the
combination, when we use the condenser, is Zlt where
Z1 = (Sp)-^ + Z. ........................... (47)
Let V and C be the voltage and the current respectively, at time t after
insertion of the condenser, and due entirely to its initial charge.
RESISTANCE AND CONDUCTANCE OPERATORS. 373
Equations (46) above express them, if u and w have the special ratio
proper at the condenser, given by
w= -Spu, ................................. (48)
because the current equals the rate of decrease of its charge. Initially,
we have e = 2Au and 2,Aw = Q. So, making use of the conjugate
property,* we have
Seu=2(Up-Tp)A, .......................... (49)
if Up be the electric and Tp the magnetic energy in the normal system.
But the following property of the resistance-operator is also true,*
2(r,-0,) = »; ........................... (50)
that is, dZJdp is the impulsive inductance in the p system at a place
where the resistance-operator is Zlt p being a root of Zl = Q; just as
dZJdp with p = 0 is the impulsive inductance (complete) at the same
place. Using (50) in (49) gives
(5!)
Now use (48) in (51) and insert the resulting A in the second of (46),
and there results
o- .......................... • ...... <52>
where the accent means differentiation to p. This is the complete
subsidence solution. Now increase S infinitely, keeping e constant
Zl ultimately becomes Z ; but, in doing so, one root of Zl = 0 becomes
zero. We have, by (47), and remembering that Zl = 0,
pZ{= -(Sp)-i+pZ' = Z+pZf') ..................... (53)
so, when $=oo and Z = Q, we have pZ{=pZr for all roots except the
one just mentioned, in which case p tends to zero and Zf is finite,
making in the limit pZ{ = Z^ by (53), where ZQ is the^? = 0 value of Z,
or the steady resistance. Therefore, finally,
where the summation extends over the roots of Z--=0, shows the
manner of establishment of the current by the impressed force e. The
use of this equation (54), even in comparatively elementary problems,
leads to a considerable saving of labour, whilst in cases involving partial
differential equations it is invaluable.! To extend it to show the rise
of the current at any other part of the system than where the impressed
* "On the Self-induction of Wires," Phil. Mag., Oct. 1886 [vol. n., pp. 202
to 206].
t In Part III. of " On the Self -Induction of Wires," I employed the Condenser
Method, with application to a special kind of combination ; but, as we have seen
from the above proof, (54) is true for any electrostatic and electromagnetic com-
bination provided it be finite.
374 ELECTRICAL PAPERS.
force is, it is necessary to know the connections, so that we may know
the ratio of the current in a normal system at the new place to that at
the old; inserting this ratio in the summation, and modifying the
external ZQ to suit the new place, furnishes the complete solution there.
Or, use the more general resistance-operator Zxy, such that ex = ZxyCy,
connecting the. impressed force at any place x with the current at
another place y.
18. When the initial current is zero, as happens when there is self-
induction without permittance at the place of et and in other cases, (54)
gives
showing that the normal systems may be imagined to be arranged in
parallel, the resistance of any one being ( -pZf).
To express the impulsive inductance Z'Q in terms of the normal ^s,
multiply (54) by e and take the complete time-integral. We obtain
Uc-«}dt = 2(U-T)= -£-£, (56)
J \ ZJQ/ — p /j
remembering (29). Or, using (26),
(57)
In electrostatic problems the roots of Z=0 are real and negative, as
is also the case in magnetic problems. There are never any oscillatory
results in either case, and the vanishing of Z1 is then accompanied by
vanishing of the corresponding normal functions, to prevent the oscilla-
tions which seem on the verge of occurring by the repetition of a root
which Z' = Q implies.* When both energies are present, the real parts
of the imaginary roots are always compelled to be negative by the
positivity of £7", T, and of Q the dissipativity.
When Z is irrational, it is probable that the complete solution
corresponding to (54) might be immediately derived from Z. In the
case of (41),f however, the application is not obvious, although there is
no difficulty in passing from the (54) solution to the corresponding
definite integrals which arise when the length of the circuit is infinitely
increased.
"* [See p. 529, vol. i. Also Thomson and Tait, Part I. , § 343c and after, relating
to Routh's Theorem, given in his Adam's Prize Essay, "Stability of Motion."]
t [Done in "El. Mag. Waves," 1888. Arts. XLIII. and XLIV. later.]
ON ELECTROMAGNETIC WAVES. PART I. 375
XLIIL ON ELECTROMAGNETIC WAVES, ESPECIALLY IN
RELATION TO THE VORTICITY OF THE IMPRESSED
FORCES ; AND THE FORCED VIBRATIONS OF ELECTRO-
MAGNETIC SYSTEMS.
[Phil. Mag., 1888; Parti., February, p. 130; Part II., March, p. 202; Part III.,
May, p. 379 ; Part IV., October, p. 360; Part V., November, p. 434; Part VL,
December, 1888, p. 488.]
PART I.
Summary of Electromagnetic Connections.
1 . To avoid indistinctness, I start with a short summary of Maxwell's
scheme, so far as its essentials are concerned, in the form given by me
in January, 1885.*
Two forces, electric and magnetic, E and H, connected linearly with
the three fluxes, electric displacement D, conduction-current C, and
magnetic induction B ; thus
B = /zH, C = &E, D = (c/47r)E (1)
Two currents, electric and magnetic, T and G, each of which is
proportional to the curl or vorticity of the other force, not counting
impressed ; thus,
curl (H - h) = 47TF, (2)
curl(e-E) = 47rG; (3)
where e and h are the impressed parts of E and H. These currents
are also directly connected with the corresponding forces through
r = C + D, G = B/47r (4)
An auxiliary equation to exclude unipolar magnets, viz.
divB = 0, (5)
expressing that B has no divergence. The most important feature of
this scheme is the equation (3), as a fundamental equation, the natural
companion to (2).
The derived energy-relations are not necessary, but are infinitely too
useful to be ignored. The electric energy £7, the magnetic energy T7,
and the dissipativity Q, all per unit volume, are given by
Z7=iED, T=JHB/47r, (J = EC (6.)
The transfer of energy W per unit area is expressed by a vector product,
W = V(E-e)(H-h)/47r, (7)
and the equation of activity per unit volume is
er + hG = £+?7+r+divW, (8)
from which W disappears by integration over all space.
The equations of propagation are obtained by eliminating either E or
* See the opening sections of " Electromagnetic Induction and its Propagation,"
Electrician, Jan. 3, 188o, and after [Art. xxx., vol. i., p. 429].
376 ELECTRICAL PAPERS.
H between (2) and (3), and of course take different forms according to
the geometrical coordinates selected.
In a recent paper I gave some examples* illustrating the extreme
importance of the lines of vorticity of the impressed forces, as the
sources of electromagnetic disturbances. Those examples were mostly
selected from the extended developments which follow. Although,
being special investigations, involving special coordinates, vector
methods will not be used, it will still be convenient occasionally to use
the black letters when referring to the actual forces or fluxes, and to
refer to the above equations. The German or Gothic letters employed
by Maxwell I could never tolerate, from inability to distinguish one
from another in certain cases without looking very hard. As regards
the notation EC for the scalar product of E and C (instead of the
quaternionic - SEC) it is the obvious practical extension of EC, the
product of the tensors, what EC reduces to when E and C are parallel, f
Plane Sheets of Impressed Force in a Nonconducting Dielectric.
2. We need only refer to impressed electric force e, as solutions relat-
ing to h are quite similar. Let an infinitely extended nonconducting
dielectric be divided into two regions by an infinitely extended plane
(x, y), on one side of which, say the left, or that of - z, is a field of e of
uniform intensity e, but varying with the time. • If it be perpendicular
to the boundary, it produces no flux. Only the tangential component
can be operative. Hence we may suppose that e is parallel to the
plane, and choose it parallel to x. Then E, the force of the flux, is
parallel to x, of intensity E say, and the magnetic force, of intensity
H, is parallel to y. Let e =f(t) ; the complete solutions due to the
impressed force are then
E-iwH- -i/(*-*/i>) ......................... (9)
on the right side of the plane, where z is + , and
-E = nvH= -$f(t + z/v) ...................... (10)
on the left side of the plane, where z is - . In the latter case we must
deduct the impressed force from E to obtain the force of the field, say
F, which is therefore
* Phil. Mag. Dec. 1887, " On Resistance and Conductance Operators," § 8, p.
487 [Art. XLII., vol. II., p. 363].
t In the early part of my paper " On the Electromagnetic Wave- Surf ace," Phil.
Mag., June, 1885 [Art. xxxi., vol. n., p. 1] I have given a short introduction to
the Algebra of vectors (not quaternions) in a practical manner, i.e., without
metaphysics. The result is a thoroughly practical working system. The matter
is not an insignificant one, because the extensive use of vectors in mathematical
physics is bound to come (the sooner the better), and my method furnishes a way
of bringing them in without any study of Quaternions (which are scarcely wanted
in Electromagnetism, though they may be added on), and allows us to work
without change of notation, especially when the vectors are in special type, as
they should be, being entities of widely different nature from scalars. I denote a
vector by (say) E, its tensor by E, and its x, y, z components, when wanted, by
EI} E%, Ey The perpetually occurring scalar product of two vectors requires no
prefix. The prefix V of a vector product should be a special symbol.
ON ELECTROMAGNETIC WAVES. PART I. 377
The results are most easily followed thus : — At the plane itself, where
the vortex-lines of e are situated, we, by varying e, produce simultaneous
changes in H, thus,
-H=e/2pv, ................................ (12)
at the plane. This disturbance is then propagated both ways undis-
torted at the speed v = (/AC)~*.
On the other hand, the corresponding electric displacements are
oppositely directed on the two sides of the plane.
Since the line-integral of H is electric current, and the line-integral
of e is electromotive force, the ratio of e to H is the resistance-operator
of an infinitely long tube of unit area ; a constant, measurable in ohms,
being 60 ohms in vacuum, or 30 ohms on each side. Why it is a con-
stant is simply because the waves cannot return, as there is no reflecting
barrier in the infinite dielectric.
3. If the impressed force be confined to the region between two
parallel planes distant 2a from one another, there are now two sources
of disturbances, which are of opposite natures, because the vorticity of
e is oppositely directed on the two planes, so that the left plane sends
out both ways disturbances which are the negatives of those simultane-
ously emitted by the right plane. Thus, if the origin of z be midway
between the planes, we shall have
............ (13)
on the right side of the stratum of e, and
............ (H)
on the left side. If therefore e vary periodically in such a way that
f(t)=f(t + 2a/v), ............................ (15)
there is no disturbance outside the stratum, after the initial waves have
gone off, the disturbance being then confined to the stratum of impressed
force.
Decreasing the thickness of the stratum indefinitely leads to the
result that the effect due to e =f(t) in a layer of thickness dz&tz-Q is,
on the right side,
since ^v'2 = 1 ; on the left side the + sign is required.
We can now, by integration, express the effect due to e—f(zt t\ viz.,
In these, however, a certain assumption is involved, viz. that e vanishes
at ~s^ both ways, because we base the formulae upon (16), which concerns
378 ELECTRICAL PAPERS
a layer of e on both sides of which e is zero. Now the disturbances
really depend upon de/dz, for there can be none if this be zero. By
(12) the elementary de/dz through distance dz instantly produces
U=±%d* ............................ (19)
2pv dz
at the place. If, therefore, e =f(z, t), the If-solution at any point con-
sists of the positive waves coming from planes of de/dz on the left, pro-
ducing say, Hlt and of H2, due to the negative waves from the planes
of de/dz on the right side, making the complete solution
H=Hl + H2, £=K#i-tf2); ............... (20)
where
This is the most rational form of solution, and includes the case of
e =f(t) only. The former may be derived from it by effecting the
integrations in (21) and (22) ; remembering in doing so that the
differential coefficient under the sign of integration is not the complete
one with respect to zfy as it occurs twice, but only to the second zr, and
further assuming that e = 0 at infinity.
Waves in a Conducting Dielectric. How to remove the Distortion
due to the Conductivity.
4. Let us introduce a new physical property into the conducting
medium, namely that it cannot support magnetic force without dissipa-
tion of energy at a rate proportional to the square of the force, a
property which is the magnetic analogue of electric conductivity. We
make the equations (2) and (3) become, ifp-d/dt,
......................... (23)
........................ (24)
if there be no impressed force at the spot, where g is the new coefficient
of magnetic conductivity, analogous to k.
Let
47T&/2C = qv ft + q2 = q, E = €'*
,9~
q2 = s, = l."
Substitution in (23), (24) leads to
(26)
(27)
If s = 0, these are the equations of electric and magnetic force in a non-
conducting dielectric. If therefore the new g be of such magnitude as
to make s = 0, we cause disturbances to be propagated in the conducting
dielectric in identically the same manner as if it were nonconducting,
ON ELECTROMAGNETIC WAVES. PART I. 379
but with a uniform attenuation at a rate indicated by the time-
factor €~qt.
Undistorted Plane Waves in a Conducting Dielectric.
5. Taking z perpendicular to the plane of the waves, we now have,
as special forms of (23), (24),
(28)
(29)
E being the tensor of E, parallel to x, and H the tensor of H, parallel
to y, and both being functions of z and t.
Given E — E0 and H=HQ&t time t = 0, functions of z only, decompose
them thus,
(30)
(31)
Here fl makes the positive and /2 the negative wave, and at time t the
solutions are, due to the initial state, when s = 0,
................... (32)
(33)
The only difference from plane waves in a nonconducting dielectric is
in the uniform attenuation that goes on, due to the dissipation of
energy, which is so balanced on the electric and magnetic sides as to
annihilate the distortion the waves would undergo were s finite, whether
positive or negative.
Practical Application. Imitation of this Effect.
6. When I introduced * the new property of matter symbolized by
the coefficient g, it was merely to complete the analogy between the
electric and magnetic sides of electromagnetism. The property is non-
existent, so far as I know. But I have more recently found how to
precisely imitate its effect in another electromagnetic problem, also
relating to plane waves, making use of electric conductivity to effect
the functions of both k and g in §§ 4 and 5. In the case of § 5, first
remove both conductivities, so that we have plane waves unattenuated
and undistorted. Next put a pair of parallel wires of no resistance in
the dielectric, parallel to z, and let the lines of electric force terminate
upon them, whilst those of magnetic force go round the wires. We
shall still have these plane electromagnetic waves with curved lines of
force propagated undistorted and unattenuated, at the same speed v.
If Fbe the line-integral of E across the dielectric from one wire to the
other, and kirC be the line-integral of H round either wire, we shall
have
(34)
(35)
*See first footnote [p. 375].
380 ELECTRICAL PAPERS.
(34) taking the place of (29), and (35) of (28), with k and g both zero.
Here L and S are the inductance and permittance of unit length of the
circuit of the parallel wires, and v = (LS) ~ *.
Next let the wires have constant resistance R per unit length to
current in them, and let the medium between them be conducting (to a
very low degree), making K the conductance per unit length across
from one wire to the other. We then turn the last equations into
(36)
(37)
and have a complete imitation of the previous unreal problem. The
two dissipations of energy are now due to R in the wires, and to K in
the dielectric, it being that in the wires which takes the place of the
unreal magnetic dissipation. The relation RjL = K/S, which does not
require excessive leakage when the wires are of copper of low resist-
ance, removes the distortion otherwise suffered by the waves. I have,
however, found that when the alternations of current are very rapid, as
in telephony, there is very little distortion produced by copper wires,
even without the leakage required to wholly remove it, owing to RjLn
becoming small, n/2ir being the frequency ; an effect which is greatly
assisted by increasing the inductance (see Note A, [p. 392]). Of course
there is little resemblance between this problem and that of the long
and slowly-worked submarine cable, whether looked at from the
physical side or merely from the numerical point of view, the results
being then of different orders of magnitude. A remarkable misconcep-
tion on this point seems to be somewhat generally held. It seems to be
imagined that self-induction is harmful* to long-distance telephony.
The precise contrary is the case. It is the very life and soul of it, as is
proved both by practical experience in America and on the Continent
on very long copper circuits, and by examining the theory of the
matter. I have proved this in considerable detail ; f but they will not
believe it. So far does the misconception extend that it has perhaps
contributed to leading Mr. W. H. Preece to conclude that the coefficient
of self-induction in copper circuits is negligible (several hundred times
smaller than it can possibly be), on the basis of his recent remarkable
experimental researches.
The following formula, derived from my general formulae |, will show
the rdle played by self-induction Let R and L be the resistance and
inductance per unit length of a perfectly insulated circuit of length /,
short-circuited at both ends. Let a rapidly sinusoidal impressed force
of amplitude eQ act at one end, and let C0 be the amplitude of the
*W. H. Preece, F.R.S., "On the Coefficient of Self -Induction of Copper
Wires," B. A. Meeting, 1887.
t"El. Mag. Ind. and its Propagation," Electrician, Sections XL. to L. (1887)
[vol. ii., pp. 119 to 155].
J See the sinusoidal solutions in Part II. and Part. V. of " On the Self -Induction
of Wires," Phil. Mag., Sept. 1886 and Jan. 1887 [vol. n., pp. 194 and 247.
Also p. 62].
ON ELECTROMAGNETIC WAVES. PART I. 381
current at the distant end. Then, if the circuit be very long,
(7 =^o€-w (38)
Li'
where v is the speed (LS)~~ = (/^c)~^, provided E/Ln be small, say J.
It may be considerably greater, and yet allow (38) to be nearly true.
We can include nearly the whole range of telephonic frequencies by
using suspended copper wires of low resistance. *
It is resistance that is so harmful, not self-induction ; as, in combina-
tion with the electrostatic permittance, it causes immense distortion of
waves, unless counteracted by increasing the inductance, which is not
often practicable (see Note B, [p. 393]).
Distorted Plane Waves in a Conducting Dielectric.
7. Owing to the fact that, as above shown, we can fully utilize solu-
tions involving the unreal g, by changing the meaning of the symbols,
whilst still keeping to plane electromagnetic waves, we may preserve g
in our equations (28) and (29), remembering that H has to become G',
E become T7, kirk become K, c become S, kirg become E, and p, become
L, when making the application to the possible problem ; whilst, when
dealing with a real conducting dielectric, g has to be zero.
Required the solutions of (28) and (29) due to any initial states EQ
and H0, when s is not zero. Using the notation and transformations of
(25), (or direct from (26), (27)), we produce
(39)
(40)
from which
^ffiHJd^-tf-VHv (41)
with the same equation for Ev
The complete solution may be thus described. Let, at time £ = 0,
there be H=HQ through the small distance a at the origin. This
immediately splits into two plane waves of half the amplitude, which
travel to right and left respectively at speed v, attenuating as they
progress, so that at time t later, when they are at distances ± vt from
the origin, their amplitudes equal
i#o<-", (42)
with corresponding E's, viz.,
frvHtf-* and -favH0c-«, (43)
on the right and left sides respectively. These extend through the
* The explanation of the \Lv dividing e0 in (38), instead of the Lv we might
expect from the /JLV resistance-operator of a tube of unit section infinitely long one
way only, is that, on arrival at the distant end of the line, the current is immedi-
ately doubled in amplitude by the reflected wave. The second and following
reflected waves are negligible, on account of the length of the line.
382 ELECTRICAL PAPERS.
distance a. Between them is a diffused disturbance, given by
(45)
in which v2t2 > z2.
In a similar manner, suppose initially E = EQ through distance a at
the origin. Then, at time t later, we have two plane strata of depth a
at distance vt to right and left respectively, in which
E = \Ef-«= ±fjivH, ......................... (46)
the + sign to be used in the right-hand stratum, the - in the left.
And, between them, the diffused disturbance given by
............... (47)
Knowing thus the effects due to initial elements of EQ and HQ, we
have only to integrate with respect to z to find the solutions due to
any arbitrary initial distributions. I forbear from giving a detailed
demonstration, leaving the satisfaction of the proper conditions to be
the proof of (42) to (48) ; since, although they were very laboriously
worked out by myself, yet, as mathematical solutions, are more likely
to have been given before in some other physical problem than to
be new.
Another way of viewing the matter is to start with s = 0, and then
examine the effect of introducing s, either + or - . Let an isolated
plane disturbance of small depth be travelling along in the positive
direction undistorted at speed v. We have E = pvH in it. Now
suddenly increase k, making s positive. The disturbance still keeps
moving on at the same speed, but is attenuated with greater rapidity.
At the same time it leaves a tail behind it, the tip of which travels out
the other way at speed vt so that at time t after commencement of the
tailing, the whole disturbance extends through the distance 2vt. In
this tail H is of the same sign as in the head, and its integral amount is
such that it exactly accounts for the extra-attenuation suffered by H in
the head. On the other hand, E in the tail is of the opposite sign to
E in the head ; so that the integral amount of E in head and tail
decreases faster. As a special case, let, in the first place, there be no
conductivity, k = 0 and 0 = 0. Then, keeping g still zero, the effect of
introducing k is to cause the above-described effect, except that as there
was no attenuation at first, the attenuation later is entirely due to k,
whilst the line-integral of H along the tail, or
including H in the head, remains constant. This is the persistence of
momentum.
ON ELECTROMAGNETIC WAVES. PART I. 383
If, on the other hand, we introduce g, the statements made regarding
// are now true as regards E, and conversely. The tail is of a different
nature, E being of same sign in the tail as in the head, and H of the
opposite sign. Hence, of course, when we have both k and g of the
right amounts, there is no tailing. This subject is, however, far better
studied in the telegraphic application, owing to the physical reality
then existent, than in the present problem, and also then by elementary
methods.*
8. Owing to the presence of d/dz in (45) and (47) we are enabled to
give some integral solutions in a finite form. Thus, let H= HQ (constant)
and E = 0 initially on the whole of the negative side of the origin, with
no E or H on the positive side. The E at time t later is got by
integrating (45), giving
which holds between the limits z= ±vt, there being no disturbance
beyond, except the H0 on the left side. When g=0 and z/vt is small,
it reduces to
This is the pure-diffusion solution, suitable for good conductors.
If initially E = E0, constant, on the left side of the origin, and zero on
the right side, then at time t the H due to it is, by (48),
The result of taking c = 0, g = 0, in this formula is zero, as we may
see by observing that c in (49) becomes /* in (51). It is of course
obvious that as the given initial electric field has no energy if c = 0, it
can produce no effect later.
The ^-solution corresponding to (49) cannot be finitely expressed.
which, integrated, gives
H.
where all the J'a operate on st»J - 1 ; thus, e.g. (Bessel's),
* "Electromagnetic Induction and its Propagation, " Electrician, Sections XLIIJ.
to L. (1887) [vol. ii., pp. 132 to 155].
384 ELECTRICAL PAPERS.
But a much better form than (52), suitable for calculating the shape
of the wave speedily, especially at its start, may be got by arranging in
powers of z - vtt thus
true when z < vt, where /lf /2, etc., are functions of t only, of which the
first five are given by
st
At the origin, II is given by
H-lHjf**, .............................. (54)
and is therefore permanently \HQ when g = Q. At the front of the
wave, where z = vt,
#=pro€-*< ................................. (55)
Now, to represent the J^-solution corresponding to (51), we have only
to turn HtoE and HQ to E0 in (53), and change the sign of s throughout,
i.e. explicit, and in the/'s. Similarly in (52). Thus, at the origin,
£=p:0€-2<><, ............................... (56)
and at the front of the wave
E = \E^ ................................. (57)
9. Again, let H=±H0 on the left side, and H= -%HQ on the right
side of the origin, initially. The E that results from each of them is
the same, and is half that of (49); so that (49) still expresses the
^-solution. This case corresponds to an initial electric current of
surface-density HQ/^TT on the z = Q plane, with the full magnetic field
to correspond, and from it immediately follows the ^-solution due to
any initial distribution of electric current in plane layers.
Owing to H being permanently JJT0 at the origin in the case (49),
(54), when # = 0, we may state the problem thus: — An infinite con-
ducting dielectric with a plane boundary is initially free from magnetic
induction, and its boundary suddenly receives the magnetic force %H0 =
constant. At time t later (49) and (52) or (53) give the state of the
conductor at distance z<vt from the boundary. In a good conductor
the attenuation at the front of the wave is so enormous that the
diffusion-solution (50) applies practically. It is only in bad conductors
that the more complete form is required.
Effect of Impressed Force.
10. We can show that the initial effect of impressed force is the
same as if the dielectric were nonconducting. In equations (23), (24),
ON ELECTROMAGNETIC WAVES. PART I. 385
let p = ni, where n/'2ir = periodic frequency, supposing e to alternate
rapidly. By increasing n we can make the second terms on the
right sides be as great multiples of the first terms as we please,
so that in the limit we have results independent of k and g, in this
respect, that as the frequency is raised infinitely, the true solutions
tend to be infinitely nearly represented by simplified forms, in which
k and g play the part of small quantities. An inspection of the sinu-
soidal solution for plane waves shows that E and H get into the same
phase, and that k and g merely present themselves in the exponents of
factors representing attenuation of amplitude as the waves pass away
from the seat of vorticity of impressed force.
Consequently, in the plane problem, the initial effect of an abrupt
discontinuity in <?, say e — constant on the left, and zero on the right
side of the plane through the origin, is to produce
H= -e/2pv (58)
all over the plane of vorticity ; and
E=+& (59)
on its right and left sides respectively. We may regard the plane as
continuously emitting these disturbances to right and left at speed v so
long as the impressed force is in operation, but their subsequent history
can only be fully represented by the tail-formulae already given.
Irrespective of the finite curvature of a surface, any element thereof
may be regarded as plane. Therefore every element of a sheet of
vortex-lines of impressed force acts in the way just described as being
true of the elements of an infinite plane sheet. But it is only in com-
paratively simple cases, of which I shall give examples later, that the
subsequent course of events does not so greatly complicate matters as
to render it impossible to go into details after the first moment. On
first starting the sheet, it becomes a sheet of magnetic induction, whose
lines coincide with the vortex-lines of impressed force. If / be the
measure of the vorticity per unit area, fj^pv is the intensity of the
magnetic force. In the imaginary good conductor of no permittivity,
this is zero, owing to v being then assumed to be infinite.
Notice that whilst the vorticity of e produces magnetic induction,
that of h produces electric displacement, and whilst in the former case
E is made discontinuous at a plane of finite vorticity, in the latter case
it is H that is initially discontinuous.
True Nature of Diffusion in Conductors.
11. The process of diffusion of magnetic induction in conductors
appears to be fundamentally one of repeated internal reflexions with
partial transmission. Thus, let a plane wave El = pvH^ moving in a
nonconducting dielectric strike flush an exceedingly thin sheet of metal.
Let E2 = /J.vH2 be the transmitted wave in the dielectric on the other
side, and E3 = - pvH3 be the reflected wave. At the sheet we have
(60)
(61)
H.E.P.— VOL. II. 2 B
386 ELECTRICAL PAPERS.
if &j be the conductivity of the sheet of thickness s. Therefore
/62)
H is reflected positively and E negatively. A perfectly conducting
barrier is a perfect reflector ; it doubles the magnetic force and destroys
the electric force on the side containing the incident wave, and trans-
mits nothing.
Take ^ = (1600)"1 for copper, and /*# = 3 x 1010 centim. per sec.
Then we see that to attenuate the incident wave H^ to \H^ by trans-
mission through the plate, requires
z = (2ir^) - l = o8 - x 10-8 centim., ......... (63)
O7T
which is a very small fraction of the wave-length of visible light. The
^-disturbance is made %ffv the E reduced to %EV on the transmission
side. There is, however, persistence of H, although there is dissipation
of E. To produce dissipation of H with persistence of E requires the
plate to be a magnetic, not an electric conductor.
Now, imagine an immense number of such plates to be packed closely
together, with dielectric between them, forming a composite dielectric
conductor, and let the outermost sheet be struck flush by a plane wave
as above. The first sheet transmits %H19 the second %HV the third %HV
and so on. This refers to the front of the wave, going into the composite
conductor at speed v. It is only necessary to go a very short distance
to attenuate the front of the wave to nothing ; the immense speed of
propagation does not result in producing any sensible immediate effect
at a distance, which comes on quite slowly as the complex result of all
the internal reflexions and transmissions between and at the sheets.
Observe that there is an initial accumulation of H, so to speak, at the
boundary of the conductor, due to the reflexion. (Example : the current-
density may be greater at the outermost layer * of a round wire when
the current is started in it than the final value, and the total current in
the wire increases faster than if it were constrained to be uniformly
distributed.)
Thus a good conductor may have very considerable permittivity,
much greater than that of air, and yet show no signs of it, on account
of the extraordinary attenuation produced by the conductivity. Now
this is rather important from the theoretical point of view. It is
commonly assumed that good conductors, e.g., metals, are not dielectrics
at all. This makes the speed of propagation of disturbances through
them infinitely great. Such a hypothesis, however, should have no
place in a rational theory, professing to represent transmission in time
by stresses in a medium occupying the space between molecules of gross
matter. But by admitting that not only bad conductors, but all con-
ductors, are also dielectrics, we do away with the absurdity of infinitely
rapid action through infinite distances in no time at all, and make the
method of propagation, although it practically differs so greatly from
* " On the S.I. of Wires," Part I., Phil. Mag., August 1886 [vol. n. p. 181].
ON ELECTROMAGNETIC WAVES. PART I. 387
that in a nonconducting dielectric, be yet fundamentally the same, with
its characteristic features masked by repeated internal reflexions with
loss of energy. WQ need not take any account of the electric displace-
ment in actual reckonings of the magnitude of the effects which can be
observed in the case of good conductors, but it is surely a mistake to
overlook it when it is the nature of the actions involved that is in
question. (See Note C, [p. 153.])
Why conductors act as reflectors is quite another question, which
can only be answered speculatively. If molecules are perfect conduc
tors, they are perfect reflectors, and if they were packed quite closely,
we should nearly have a perfect conductor in bulk, impenetrable by
magnetic induction; and we know that cooling a metal and packing
the molecules closer does increase its conductivity. But as they do not
form a compact mass in any substance, they must always allow a partial
transmission of electromagnetic waves in the intervening dielectric
medium, and this would lead to the diffusion method of propagation.
We do not, however, account in this way for the dissipation of energy,
which requires some special hypothesis.
The diffusion of heat, too, which is, in Fourier's theory, done by
instantaneous action to infinite distances, cannot be physically true,
however insignificant may be the numerical departures from the truth.
What can it be but a process of radiation, profoundly modified by the
molecules of the body, but still only transmissible at a finite speed ?
The very remarkable fact that the more easily penetrable a body is to
magnetic induction the less easily it conducts heat, in general, is at
present a great difficulty in the way, though it may perhaps turn out
to be an illustration of electromagnetic principles eventually.
Infinite Series of Reflected Waves. Remarkable Identities.
Realized Example.
12. When, in a plane-wave problem, we confine ourselves to the
region between two parallel planes, we can express our solutions in
Fourier series, constructed so as to harmonize with the boundary con-
ditions which represent the effect of the whole of the ignored regions
beyond the boundaries in modifying the phenomena occurring within
the limited region. Now the effect of the boundaries is usually to pro-
duce reflected waves. Hence a solution in Fourier series must usually
be decomposable into an infinite series of separate solutions, coming
into existence one after the other in time if the speed v be finite, or all
in operation at once from the first moment if the speed be made infinite
(as in pure diffusion). If the boundary conditions be of a simple
nature, this decomposition can sometimes be easily explicitly repre-
sented, indicating remarkable identities, of which the following investi-
gation leads to one. We may either take the case of plane-waves in a
conducting dielectric bounded by infinitely conductive planes, making
E = 0 the boundary condition ; or, similarly, by perfect magnetically
conductive planes producing #=0. But the most practical way, and the
most easily followed, is to put a pair of parallel wires in the dielectric,
and produce a real problem relating to a telegraph-circuit,
388 ELECTRICAL PAPERS.
Let A and B be its terminations at z = 0 and z = I respectively. Let
them be short-circuited, producing the terminal conditions ^=0 at
A and B in the absence of impressed force at either place. Now, the
circuit being free from charge and current initially, insert a steady
impressed force 60 at A. Kequired the effect, both in Fourier series
and in detail, showing the whole history of the phenomena that
result.
Equations (36) and (37) are the fundamental connections of Fand C
at any distance z from A. Let J?, L, K, S be the resistance, inductance,
leakage-conductance, and permittance per unit length of circuit, and
A = (mV-s0f ............................. (65)
It may be easily shown, by the use of the resistance-operator, or by
testing satisfaction of conditions, that the required solutions are
(66)
where m =jir/l, and j includes all integers from 1 to oo ; whilst V§ and
C0 represent the final steady Fand C, which are
M«"*-£25)' ...................... (68)
(68)
(69)
where ra02 = - RK.
Now if the circuit were infinitely long both ways and were charged
initially to potential-difference 2eQ on the whole of the negative side of
A, with no charge on the positive side, and no current anywhere, the
resulting current at time t later at distance z from A would be
by §§ 7 and 8 ; and if, further, K=Q, Fat A would be permanently ew
which is what it is in (66). Hence the (7-solutiori (67) can be finitely
decomposed into separate solutions of the form (70) in the case of
perfect insulation, when (67) takes the form
(71)
where ^ = s1 = 50, by the vanishing of S2 in (64).
Therefore (70) represents the real meaning of (71) from t = 0 to l/v,
provided vt>z. But on arrival of the wave Cl at B, V becomes zero,
and C doubled by the reflected wave that then commences to travel
from B to A. This wave may be imagined to start when t = 0 from a
ON ELECTROMAGNETIC WAVES. PART I. 389
point distant I beyond B, and be the precise negative of the first wave
as regards V but the same as regards ft Thus
expresses the second wave, starting from B when t = l/v, and reaching
A when t = 2l/v. The sum of Cl and C2 now expresses (71) where the
waves coexist, and Cl alone expresses (71) in the remainder of the
circuit.
The reflected wave arising when this second wave reaches A may be
imagined to start when t = 0 from a point distant 21 from A on its
negative side, and be a precise copy of the first wave. Thus
expresses the third wave; and now (71) means C1 + C2 + CB in those
parts of the circuit reached by (73, and Cl + C2 in the remainder.
The fourth wave is, similarly,
starting from B when t = 3l/v, and reaching A when t - il/v. And so
on, ad inf.*
If we take L = 0 in this problem, we make v = QO , and bring the
whole of the waves into operation immediately. (70) becomes
and similarly for (72, <73, etc. In this simplified form the identity is
that obtained by Sir W. Thomson f in connexion with his theory of
the submarine cable; also discussed by A. Cayley J and J. W. L.
Glaisher. [See also vol. I., p. 88.]
In order to similarly represent the history of the establishment of
F0, we require to use the series for E due to EQ, corresponding to
(53), or some equivalent. In other respects there is no difference.
Whilst it is impossible not to admire the capacity possessed by solu-
tions in Fourier series to compactly sum up the effect of an infinite
series of successive solutions, it is greatly to be regretted that the
Fourier solutions themselves should be of such difficult interpretation.
* It is not to be expected that in a real telegraph -circuit the successive waves
have abrupt fronts, as in the text. There are causes in operation to prevent this,
and round off the abruptness. The equations connecting V and C express the
first approximation to a complete theory. Thus the wires are assumed to be
instantaneously penetrated by the magnetic induction as a wave passes over their
surfaces, as if the conductors were infinitely thin sheets of the same resistance.
It is only a, very partial remedy to divide a wire into several thinner wires, unless
we at the same time widely separate them. If kept quite close it would, with
copper, be no remedy at all.
t Math, and Physical Papers, vol. ii., art. Ixxii. ; with Note by A. Cayley.
SPhil. Mag., June 1874.
390 ELECTRICAL PAPERS.
Perhaps there will be discovered some practical way of analysing them
into easily interpretable forms.
Some special cases of (66), (67) are worthy of notice. Thus V is
established in the same way when fi = Q as when K=0, provided the
value of K/S in the first case be the same as that of E/L in the second.
Calling this value 2q, we have in both cases
F= Jl - f) - S&.-'SELE'fcoB u + q sin AA ......... (76)
\ I / I Tfl \ A /
But the current is established in quite different manners. When it
is K that is zero, (71) is the solution; but if R vanish instead, then
(67) gives
. (77)
C now mounts up infinitely. But the leakage-current, which is KV,
becomes steady, as (76) shows.
In connexion with this subject I should remark that the distortionless
circuit produced by taking RjL = K/S is of immense assistance, as its
properties can be investigated in full detail by elementary methods, and
are most instructive in respect to the distortional circuits in question
above.*
Modifications made by Terminal Apparatus. Certain Cases easily
brought to Full Realization.
13. Suppose that the terminal conditions in the preceding are
V= — Zjb and V—Z-f^ ZQ and Zl being the "resistance-operators " of
terminal apparatus at A and B respectively. In a certain class of cases
the determinantal equation so simplifies as to render full realization
possible in an elementary manner. Thus, the resistance-operator of the
circuit, reckoned at A, ist
pJlZ^ten ml)/mly '
where m2= - (R + Lp)(K + Sp) ........................ (79)
That is, e = $C is the linear differential equation of the current at A.
Now, to illustrate the reductions obviously possible, let ZQ = 0, and
Z^nJtf + Lp) ............................ (80)
This makes the apparatus at B a coil whose time-constant is LfR, and
reduces <f> to
j. /r> T \7/tanwz£ , \f, 2 yatan???^"1
<f>=*(R + Lp)U -- +nl\l 1 -msnjl2 -- — , ....... (81)
so that the roots of $ = 0 are given by
(82)
tan m/ + 7/1^ = 0; .................... '. ...... (83)
*" Electromagnetic Induction and its Propagation," Arts. XL. to L. [vol. II.,
p. 119].
t "On the Self-Induction of Wires," Part IV. [vol. IL, p. 232].
ON ELECTROMAGNETIC WAVES. PART I. 391
i.e., a solitary root p = -E/L, and the roots of (83), which is an
elementary well-known form of determinantal equation.
The complete solution due to the insertion of the steady impressed
force e(} at A will be given by*
...................... (85)
where the summations range over all the p roots of </> = 0, subject to
(79) ; whilst u and w are the V and C functions in a normal system,
expressed by
w = cos mz, u = m sin mz -f (K + Sp) ; ............ (86)
and F0, C0 are the final steady V and C. In the case of the solitary
root (82) we shall find
^), ......................... (87)
but for all the rest
I dm2,..
+V°«> ................ (88)
Realizing (84), (85) by pairing terms belonging to the two j?'s associ-
ated with one m2 through (79), we shall find that (66), (67) express the
solutions, provided we make these simple changes : — Divide the general
term in both the summations by (1 +n1cos%/), and the term following
C0 outside the summation in (67) by (1 4-?^). Of course the m's have
now different values, as per (83), and F"0, 6y0 are different.
14. There are several other cases in which similar reductions are
possible. Thus, we may have
Zl = n^R + Lp) + n((K + Sp)~\
simultaneously, n0, n'0, nv n{ being any lengths. That is, apparatus at
either end consisting of a coil and a condenser in sequence, the time-
constant of the coil being L/R and that of the condenser S/K. Or, the
condenser may be in parallel with the coil. In general we have, as an
alternative form of </> = 0, equation (78),
ml 1 - mWZ^ { (R + Lp)l} ~2 '
from which we see that when
and
. .
(R + Lp}l
are functions of ml, equation (89) finds the value of m2 immediately, i.e.
not indirectly as functions of p. In all such cases, therefore, we may
*lb. Parts III. and IV. Phil. Mag., Oct. and Nov. 1886; or "On Resistance
and Conductance Operators," Phil. Mag., Dec. 1887, § 17, p. 500 [vol. TI., p. 373].
392 ELECTRICAL PAPERS.
advantageously have the general solutions (84), (85) put into the realized
form. They are
mz + tan 6 cos mz)m€~
-
d(ml)
tanw
I same denominator
where q, A, s0, s2 are as in (64), (65). The differentiation shown in the
denominator is to be performed upon the function of ml to which tan ml
is equated in (89), after reduction to the form of such a function in the
way explained ; and 6 depends upon ZQ thus,
tan 6 = - mr\K+ Sp)Z0, sec26> = 1 + m~9Zf(K+ Sp)*, (92)
which are also functions of ml. It should be remarked that the terms
depending upon solitary roots, occurring in the case m2 = 0, are not
represented in (90), (91). They must be carefully attended to when
they occur.
NOTE A. The Electromagnetic Theory of Light.
An electromagnetic theory of light becomes a necessity, the moment one
realizes that it is the same medium that transmits electromagnetic dis-
turbances and those concerned in common radiation. Hence the electro-
magnetic theory of Maxwell, the essential part of which is that the vibra-
tions of light are really electromagnetic vibrations (whatever they may be),
and which is an undulatory theory, seems to possess far greater intrinsic
probability than the undulatory theory, because that is not an electro-
magnetic theory. Adopting, then, Maxwell's notion, we see that the only
difference between the waves in telephony (apart from the distortion and
dissipation due to resistance) and light-waves is in the wave-length ; and the
fact that the speed, as calculated by electromagnetic data, is the same as that
of light, furnishes a powerful argument in favour of the extreme relative
simplicity of constitution of the ether, as compared with common matter in
bulk. There is observational reason to believe that the sun sometimes causes
magnetic disturbances here of the ordinary kind. It is impossible to
attribute this to any amount of increased activity of emission of the
sun so long as we only think of common radiation. But, bearing in mind the
long waves of electromagnetism, and the constant speed, we see that
disturbances from the sun may be hundreds or thousands of miles long
of one kind (i.e. without alternation), and such waves, in passing the earth,
would cause magnetic " storms," by inducing currents in the earth's
crust and in telegraph-wires. Since common radiation is ascribed to
molecules, we must ascribe the great disturbances to movements of large
masses of matter.
There is nothing in the abstract electromagnetic theory to indicate whether
the electric or the magnetic force is in the plane of polarization, or rather,
surface of polarization. But by taking a concrete example, as the reflexion
of light at the boundary of transparent dielectrics, we get Fresnel's formula
for the ratio of reflected to incident wave, on the assumption that his " dis-
placement" coincides with the electric displacement ; and so prove that it is
the magnetic flux that is in the plane of polarization.
ON ELECTROMAGNETIC WAVES. PART I. 393
NOTE B. The Beneficial Effect of Self-Induction.
I give these numerical examples : —
Take a circuit 100 kilom. long, of 4 ohms and | microf. per kilom. and no
inductance in the first place, and also no leakage in any case. Short-circuit
at beginning A and end B. Introduce at A a sinusoidal impressed force,
and calculate the amplitude of the current at B by the electrostatic theory.
Let the ratio of the full steady current to the amplitude of the sinusoidal
current be />, and let the frequency range through 4 octaves, from ft = 1250 to
n = 20,000 ; the frequency being H/ZTT. The values of p are
1-723, 3-431, 10-49, 58'87, 778.
It is barely credible that any kind of speaking would be possible, owing
to the extraordinarily rapid increase of attenuation with the frequency.
Little more than murmuring would be the result.
Now let Z = 2^ (very low indeed), L being inductance per centim.
Calculate by the combined electrostatic and magnetic formula. The
corresponding figures are
1-567, 2-649, 5 '587, 10'496, 16'607.
The change is marvellous. It is only by the preservation of the currents
of great frequency that good articulation is possible, and we see that
even a very little self-induction immensely improves matters. There
is no "dominant" frequency in telephony. What should be aimed at
is to get currents of any frequency reproduced at B in their proper pro-
portions, attenuated to the same extent.
Change L to 5. Results : —
1-437, 2-251, 3-176, 4'169, 4'670.
Good telephony is now possible, though much distortion remains.
Increase L to 10. Results : —
1-235, 1-510, 1-729, 1'825, 1'854.
This is first class, showing approximation towards a distortionless circuit.
Now this is all done by the self-induction carrying forward the waves
undistorted (relatively) and also with much less attenuation.
I should add that I attach no importance to the above figures in point
of exactness. The theory is only a first approximation. In order to
emphasize the part played by self-induction, I have stated that by sufficiently
increasing it (without other change, if this could be possible) we could
make the amplitude of current at the end of an Atlantic cable greater
than the steady current (by the g'wem'-resonance).
NOTE C. The Velocity of Electricity.
In Sir W. Thomson's article on the " Velocity of Electricity " (Nichols's
Cyclopaedia, 2nd edition, 1860, and Art. Ixxxi. of 'Mathematical and Physical
Papers,' vol. ii.) is an account of the chief results published up to that
date relating to the "velocity" of transmission of electricity, and a very
explicit statement, except in some respects as regards inertia, of the
theoretical meaning to be attached to this velocity under different circum-
stances. This article is also strikingly illustrative of the remarkable
contrast between Sir W. Thomson's way of looking at things electrical
(at least at that time) and Maxwell's views ; or perhaps I should say
Maxwell's plainly evident views combined with the views which his followers
have extracted from that mine of wealth ' Maxwell,' but which do not lie on
the surface. (As charity begins at home, I may perhaps illustrate by a
personal example the difference between the patent and the latent, in
394 ELECTRICAL PAPERS.
Maxwell. If I should claim (which I do) to have discovered the true
method of establishment of current in a wire— that is, the current starting
on its boundary, as the result of the initial dielectric wave outside it,
followed by diffusion inwards, — I might be told that it was all "in Max-
well." So it is ; but entirely latent. And there are many more things
in Maxwell which are not yet discovered.) This difference has been the
subject of a most moving appeal from Prof. G. F. Fitzgerald, in Nature,
about three years since. There really seemed to be substance in that
appeal. For it is only a master-mind that can adequately attack the
great constructional problem of the ether, and its true relation to matter ;
and should there be reason to believe that the master is on the wrong track,
the result must be, as Prof. Fitzgerald observed (in effect) disastrous to
progress. Now Maxwell's theory and methods have stood the test of
time, and shown themselves to be eminently rational and developable.
It is not, however, with the general question that we are here concerned,
but with the different kinds of "velocity of electricity." As Sir W.
Thomson points out, his electrostatic theory, by ignoring magnetic in-
duction, leads to infinite speed of electricity through the wire. Inter-
preted in terms of Maxwell's theory, this speed is not that of electricity
through the wire at all, but of the waves through the dielectric, guided by
the wire. It results, then, from the assumption /z = 0, destroying inertia
(not of the electric current, but of the magnetic field), and leaving only
forces of elasticity and resistance.
But he also points out another way of getting an infinite speed, when we,
in the case of a suspended wire, not of great length, ignore the static charge.
This is illustrated by the pushing of incompressible water through an
unyielding pipe, constraining the current to be the same in all parts of the
circuit. This, in Maxwell's theory, amounts to stopping the elastic dis-
placement in the dielectric, and so making the speed of the wave through it
infinite. As, however, the physical actions must be the same, whether
a wire be long or short, the assumption being only warrantable for purposes
of calculation, I have explained the matter thus. The electromagnetic
waves are sent to and fro with such great frequency (owing to the shortness
of the line) that only the mean value of the oscillatory V at any part can be
perceived, and this is the final value ; at the same time, by reason of current
in the negative waves being of the same sign as in the positive, the current
C mounts up by little jumps, which are, however, packed so closely together
as to make a practically continuous rise of current in a smooth curve,
which is that given by the magnetic theory. This curve is of course
practically the same all over the circuit, because of the little jumps being
imperceptible.
But in any case this speed is not the speed of electricity through the wire,
but through the dielectric outside it. Maxwell remarked that we know
nothing of the speed of electricity in a wire supporting current ; it may be
an inch in an hour, or immensely great. This is on the assumption,
apparently, that the electric current in a wire really consists in the transfer
of electricity through the wire. I have been forced, to make Maxwell's
scheme intelligible to myself, to go further, and add that the electricity may
be standing still, which is as much as to say that there is no current, in
a literal sense, inside a conductor. (The slipping of electrification over the
surface of a wire is quite another thing. That is merely the movement
of the wave through the dielectric, guided by the wire. It occurs in a
distortionless circuit, owing to the absence of tailing, in the most plainly
evident manner.) In other words, take Maxwell's definition of electric
current in terms of magnetic force as a basis, and ignore the imaginary
fluid behind it as being a positive hindrance to progress, as soon as one
ON ELECTROMAGNETIC WAVES. PART I. 395
leaves the elementary field of stead)/ currents and has to deal with variable
states.
The remarks in the text on the subject of the speed of waves in conductors
relates to a speed that is not considered in Sir W. Thomson's article, It is
the speed of transmission of magnetic disturbances into the wire, in
cylindrical waves, which begins at any part of a wire as soon as the primary
wave through the dielectric reaches that part. It would be no use trying to
make signals through a wire if we had not the outer dielectric to carry the
magnetizing and electrizing force to its boundary. The slowness of diffusion
in large masses is surprising. Thus a sheet of copper covering the earth,
only 1 centim, in thickness, supporting a current whose external field imitates
that of the earth, has a time-constant of about a fortnight. If the copper
extended to the centre of the earth, the time-constant of the most slowly sub-
siding normal system would be millions of years.
In the article referred to. Sir W. Thomson mentions that Kirch-
hoff's investigation, introducing magnetic induction, led to a velocity
of electricity considerably greater than* that of light, which is so far in
accordance with Wheatstone's observation. Now it seems to me that
we have here a suggestion of a probable explanation of why Sir W.
Thomson did not introduce self-induction into his theory. There were
presumably more ways than one of doing it, as regards the measure of
the electric force of induction. When we follow Maxwell's equations, there
is but one way of doing it, which is quite definite, and leads to a speed which
cannot possibly exceed that of light, since it is the speed (/xc)~£ through
the dielectric, and cannot be sensibly greater than 3 x 1010 centim., though
it may be less. Kirchhoff's result is therefore in conflict with Maxwell's
statement that the German methods lead to the same results as his.
Besides that, Wheatstone's classical result has not been supported by any
later results, which are always less than the speed of light, as is to
be expected (even in a distortionless circuit). But a reference to Wheat-
*(Note by SIR WILLIAM THOMSON.) In this statement I inadvertently did injustice to
Kirchhoff. In the unpublished investigation referred to in the article Electricity,
Velocity of [Nichols's Cyclopaedia, second edition, 1860; or my 'Collected Papers,' vol.
ii. page 135 (3)], I had found that the ultimate velocity of propagation of electricity in a
long insulated wire in air is equal to the number of electrostatic units in the electro-
magnetic unit ; and I had correctly assumed that Kirchhoff's investigation led to
the same result. But, owing to the misunderstanding of two electricities or one,
referred to in §317 of my ' Electrostatics and Magnetism,' I imagined Weber's measure-
ment of the number of electrostatic units in the electromagnetic to be 2x3'lxl010
centimetres per second, which would give for the ultimate velocity of electricity through
a long wire in air twice the velocity of light. In my own investigation, for the sub-
marine cable, I had found the ultimate velocity of electricity to be equal to the number
of electrostatic units in the electromagnetic unit divided by Vk ; k denoting the specific
inductive capacity of the gutta-percha. But at that time no one in Germany (scarcely
any one out of England) believed in Faraday's "specific inductive capacity of a
dielectric."
Kirchhoff himself was perfectly clear on the velocity of electricity in a long insulated
wire in air. In his original paper, "Ueber die Bewegung der Electricitat in Drahten"
(Pogg. Ann. Bd. c. 1857; see pages 146 and 147 of Kirchhoff's Volume of Collected
Papers, Leipzig, 1882), he gives it as c/\/2, which is what I then called the number of
electrostatic units in the electromagnetic unit ; and immediately after this he says,
" ihr Werth ist der von 41950 Meilen in einer Sekunde, also sehr nahe gleich der
Geschwindigkeit des Lichtes im leeren Raume."
Thus clearly to Kirchhoff belongs the priority of the discovery that the velocity of
electricity in a wire insulated in air is very approximately equal to the velocity of light.
[Note by THE AUTHOR. In Maxwell's theory, however, as I understand it, we are not
at all concerned with the velocity of electricity in a wire (except the transverse velocity
of lateral propagation). The velocity is that of the waves in the dielectric outside
the wire.]
396 ELECTRICAL PAPERS.
.stone's paper on the subject will show, first, that there was confessedly
a good deal of guesswork ; and, next, that the repeated doubling of the
wire on itself made the experiment, from a modern point of view, of
too complex a theory to be examined in detail, and unsuitable as a test.
PART II.
NOTE ON PART I. The Function of Self-Induction in the Propagation of
Waves along Wires*
An editorial query, the purport of which I did not at first understand,
has directed my attention to Prof. J. J. Thomson's paper " On Electrical
Oscillations in Cylindrical Conductors" (Proc. Math. Soc., vol. xvii.,
Nos. 272, 273), a copy of which the author has been so good as to send
me. His results, for example, that an iron wire of \ centim. radius,
of inductivity 500, carries a wave of frequency 100 per second about
100,000 miles before attenuating it from 1 to c"1, and similar results,
summed up in his conclusion that the carrying-power of an iron-wire
cable is very much greater than that of a copper one of similar dimen-
sions, are so surprisingly different from my own, deduced from my
developed sinusoidal solutions, in the accuracy of which I have perfect
confidence (having had occasion last winter to make numerous practical
applications of them in connexion with a paper which was to have been
read at the S. T. E. and E.) [see Art. XLL, vol. IL, p. 323], that I felt
sure there must be some serious error of a fundamental nature running
through his investigations. On examination I find this is the case,
being the use of an erroneous boundary condition in the beginning,
which wholly vitiates the subsequent results [relating to the effect of
magnetisation]. It is equivalent to assuming that the tangential com-
ponent of the flux magnetic induction is continuous at the surface of
separation of the wire and dielectric, where the inductivity changes
value, from a large value to unity, when the wire is of iron. The true
conditions are continuity of tangential force and of normal flux.
As regards my own results, and how increasing the inductance is
favourable, the matter really lies almost in a nutshell ; thus. In order to
reduce the full expression of Maxwell's connexions to a practical
working form I make two assumptions. First, that the longitudinal
component of current (parallel to the wires) in the dielectric is negli-
gible, in comparison with the total current in the conductors, which
makes C one of the variables, C being the current in either conductor ;
and next, what is equivalent to supposing that the wave-length of
disturbances transmitted along the wires is a large multiple of their
distance apart. The result is that the equations connecting Fand C
become
- dr/dz = R"C, - dCjdz = KV+ SV\
S being the permittance and K the conductance of the dielectric per
unit length of circuit, whilst R" is a " resistance-operator," depending
* This note may be regarded as a continuation of Note B [p. 393, vol. n.].
ON ELECTROMAGNETIC WAVES. PART II. 397
upon the conductors, and their mutual position, which, in the sinusoidal
state of variation, reduces to
where Rf and L' are the effective resistance and inductance of the
circuit respectively, per unit length, to be calculated entirely upon
magnetic principles. It follows that the fully developed sinusoidal
solution is of precisely the same form as if the resistance and induct-
ance were constants. Disregarding the effect of reflexions, we have
r=ro€-fzsin (nt-Qz),
due to VQ sin nt impressed at z = 0 ; where P and Q are functions of
R', L', S, K, and n.
Now if R'lL'n is large, and leakage is negligible (a well-insulated
slowly-worked submarine cable, and other cases), we have
as in the electrostatic theory of Sir W. Thomson. There is at once
great attenuation in transit, and also great distortion of arbitrary
waves, owing to P and Q varying with n.
But in telephony, n being large, P and Q may have widely different
values, because R'jUn may be quite small, even a fraction. In such
case we have no resemblance to the former results. If R'jL'n is small,
P and Q approximate to
P = R'l^L'vf + K/2S^ Q = »/t/,
where v' = (LfS)-^. This also requires KjSn to be small. But it is
always very small in telephony.
Now take the case of copper wires of low resistance. Lf is practically
Lot the inductance of the dielectric, and vf is practically v, the speed of
undissipated waves, or of all elementary disturbances, through the
dielectric, whilst R' may be taken to be R, the steady resistance, except
in extreme cases. Hence, with perfect insulation,
P = £/2LQv, Q = n/v,
or the speed of the waves is v, and the attenuating coefficient P is practi-
cally independent of the frequency, and is made smaller by reducing
the resistance, and by increasing the inductance of the dielectric.
The corresponding current is
very nearly, or V and C are nearly in the same phase, like undissipated
plane waves. There is very little distortion in transit.
How to increase LQ is to separate the conductors, if twin wires, or
raise the wire higher from the ground, if 'a single wire with earth-
return. It is not, however, to be concluded that L0 could be increased
indefinitely with advantage. If / is the length of the circuit,
Iil = 2LQv
shows the value of LQ which makes the received current greatest. It
is then far greater than is practically wanted, so that the difficulty of
increasing L0 sufficiently is counterbalanced by the non-necessity. The
best value of L0 is, in the case of a long line, out of reach ; so that we
may say, generally, that increasing the inductance is always of advant-
age to reduce the attenuation and the distortion.
398 ELECTRICAL PAPERS.
Now if we introduce leakage, such that E/L0 = K/S, we entirely
remove the distortion, not merely when EjL^n is small, but of any sort
of waves. It is, however, at the expense of increased attenuation. The
condition of greatest received current, L0 being variable, is now
W = LQv.
We have thus two ways of securing good transmission of electromag-
netic waves : one very perfect, for any kind of signals ; the other less
perfect, and limited to the case of fi/L0n small, but quite practical.
The next step is to secure that the receiving-instrument shall not intro-
duce further distortion by the quasi-resonance that occurs. In the truly
distortionless circuit this can be done by making the resistance of the
receiver be L^v (whatever the length of the line) ; this causes complete
absorption of the arriving waves. In the other case, ofE/LQn small, with
good insulation, we require the resistance of the receiver to be also L0e
to secure this result approximately. I have also found that this value
of the receiver's resistance is exactly the one that (when size of wire in
receiver is variable) makes the magnetic force, and therefore the
strength of signal, a maximum. Some correction is required on
account of the self-induction of the receiver ; but in really good tele-
phones of the best kind, with very small time-constants, it is not great.
We see therefore that telephony, so far as the electrical part of the
matter is concerned, can be made as nearly perfect as possible on lines
of thousands of miles in length. But the distortion that is left, due to
imperfect translation of sound waves into electromagnetic waves at the
sending-end, and the reproduction of sound-waves at the receiving-end,
is still very great ; though, practically, any fairly good telephonic
speech is a sufficiently good imitation of the human voice.
There is one other way of increasing the inductance which I have
described, viz., in the case of covered wires to use a dielectric impreg-
nated with iron dust. I have proved experimentally that LQ can be
multiplied several times in this way without any increase in resistance ;
and the figures I have given above (in Note B) prove what a wonderful
difference the self-induction makes, even in a cable, if the frequency is
great. Hence, if this method could be made practical, it would greatly
increase the distance of telephony through cables.
Now, passing to iron wires, the case is entirely different, on account
of the great increase in resistance that the substitution of iron for
copper of the same size causes, which increases P and the attenuation.
Taking for simplicity the very extreme case of such an excessive
frequency as to make the formula
nearly true, R being the steady and Er the actual resistance, we see
that increasing either R or /x, increases R' and therefore P, because ZV
tends to the value L0v. Thus the carrying power of iron is not greatly
above, but greatly below that of copper of the same size.
I have, however, pointed out a possible way of utilizing iron (other
than that above mentioned), viz., to cover a bundle of fine iron wires
with a copper sheath. The sheath is to secure plenty of conductance ;
ON ELECTROMAGNETIC WAVES. PART II.
399
the division of the iron to facilitate the penetration of current, and so
lower the resistance still more, to the greatest extent, whilst at the same
time increasing the inductance. But the theory is difficult, and it is
doubtful whether this method is even theoretically legitimate. First
class results were obtained by Van Rysselberghe on a 1000-mile circuit
in America (2000 miles of wire), using copper-covered steel wire. Here
the resistance was very low, on account of the copper, and the induct-
ance considerable, on account of the dielectric alone ; so that there is no
certain evidence that the iron did any good except by lowering the
resistance. But about the advantage of increasing the inductance of
the dielectric there can, I think, be no question. It imparts momentum
to the waves, and that carries them on.
In Note B to the first part of this paper [p. 393 ante], I gave four sets
of numerical results showing the influence of increasing the inductance,
selecting a cable of large permittance (constant) in order to render the
illustrations more forcible. The formula used was equation (82), Part II.
of my paper "On the Self-induction of Wires" [p. 195 ante], which is
-2 cos 2$)"*;
where
P or =
Here C0 is the amplitude of current at z = l due to impressed force
"
F"0sin nt at z = 0, with terminal short-circuits.
enough to make t~ri small, we obtain
When the circuit is long
as the expression for the ratio /> of the steady current to the amplitude
of the sinusoidal current.
The following table is constructed to show the fluctuating manner of
variation of the amplitude with the frequency. Drop the accents, and
let R/Ln be small. Then, approximately,
where y = Itl/Lv,
under no restriction as regards the length of the circuit. Now give y a
succession of values, and calculate p with the cosine taken as -1,0, and
+ 1. Call the results the maximum, mean, and minimum values of />.
y-
Min. p.
Mean p.
Max. p.
y-
P-
y-
P-
i
•2
•505
1-500
2-063
6
1-678
12
16-81
1
•521
•878
1-128
7
2-365
14
39-3
2
•587
•686
•771
8
3-378
16
93-2
2-065
•594
•685 1 -766
9
5-000
18
225
3
•710
•748
•784
10
7-420
20
550
4
•907
•924
•940
5
1-210
1-218
1-226
400 ELECTRICAL PAPERS.
It will be seen that when the resistance of the circuit varies from a
small fraction to about the same magnitude as Lv (which may be
from 300 to 600 ohms in the case of a suspended copper wire), the
variation in the value of p as the frequency changes through a
sufficiently wide range, is great, merely by reason of the reflexions
causing reinforcement or reduction of the strength of the received
current. The theoretical least value of p is J, when RjLn is vanishingly
small, indicating a doubling of the amplitude of current. But, as y
increases, the range of p gets smaller and smaller. After y = 5 it is
negligible.
It is, however, the mean p that is of most importance, because the
influence of terminal resistances is to lower the range in />, and to a
variable extent. The value y= 2*065, or, practically, El = 2Lv} makes
the mean p a minimum. As I pointed out in the paper before referred
to, these fluctuations can only be prejudicial to telephony. In the
present Note I have described how to almost entirely destroy them.
The principle may be understood thus. Let the circuit be infinitely long
first. Then its impedance to an intermediate impressed force alternat-
ing with sufficient frequency to make R/Ln small will be 2Lv, viz., Lv
each way. The current and transverse voltage produced will be in the
same phase, and in moving away from the source of energy they will be
similarly attenuated according to the time-factor e-^/2^. In order that
the circuit, when of finite length, shall still behave as if of infinite
length, the constancy of the impedance suggests to us that we should
make the terminal apparatus a mere resistance, of amount Lv, by which
the waves will be absorbed without reflexion.
That this is correct we may prove by my formula for the amplitude
of received current when there is terminal apparatus, equation (195),
Part V. "On the Self-Induction of Wires" (Phil. Mag., Jan. 1887). It
is
Here CQ is the amplitude of received current at z = I due to VQ sin nt
impressed force at 0 = 0, R' and L' the effective resistance and induct-
ance per unit length of circuit ; K and S the leakage-conductance and
permittance per unit length,
P or Q = (I
6r0, HQ, are terminal functions depending upon the apparatus at z = 0 ;
Gv Hv upon that at z = I ; the apparatus being of any kind, specified by
resistance-operators, making RfQ, Lf0 the effective resistance and induct-
ance of apparatus at z = 0, and R{, L{, at z = I. G0 is given by
from which H0 is derived by changing the signs of P and Q ; whilst
ON ELECTROMAGNETIC WAVES. PART II. 401
#j and ZTj are the same functions of R{, L( as G0 and H0 are of
RQ, LQ.
Now drop the accents, since we have only copper wires of low resist-
ance (but not very thick) in question, and the terminal apparatus are
to be of the simplest character. K/Sn will be vanishingly small prac-
tically, so take K=0. Next let R/Ln be small, and let the apparatus
at z = l be a mere coil, Rv of negligible inductance first. We shall
now have
P = Jt/2Lv, Q = n/v,
and these make G? = ( 1 + RJLv), H$ = (\- RJLv).
Thus R1 = Lv makes H^ vanish, whatever the length of lin(
terms due to reflexions disappear.
We now have
where 6r~i expresses the effect of the apparatus at z = 0 in reducing the
potential-difference there, F"0 being the impressed force, and the value
of GQ being unity when there is a short-circuit.
Now, to show that Rl = Lv makes the magnetic force of the receiver
the greatest, go back to the general formula, let €~pl be small, and let
the size of the wire vary, whilst the size of the receiving-coil is fixed.
It will be easily found, from the expression for Glt that the magnetic
force of the coil is a maximum when
\l
)'
where we keep in Lv the inductance of the receiver. Or, when R/Ln
and KjSn are both small,
or, as described, Rl = Lv when the receiver has a sufficiently small time-
constant. The rule is, equality of impedances.
We may operate in a similar manner upon the terminal function at
the sending end. Suppose the apparatus to be representable as a
resistance containing an electromotive force, and that by varying the
resistance we cause the electromotive force to vary as its square root.
Then, according to a well-known law, the arrangement producing the
maximum external current is given by RQ = Lv, equality of impedances
again. This brings us to
as if the circuit were infinitely long both ways, with maximum efficiency
secured at both ends.
Lastly, the choice of L such that Rl - 2Lv makes the circuit, of given
resistance, most efficient.
In long-distance telephony using wires of low resistance, the waves
are sent along the circuit in a manner closely resembling the trans-
mission of waves along a stretched elastic cord, subject to a small
amount of friction. In order to similarly imitate the electrostatic
H.E.P. — VOL. ii. 2c
402 ELECTRICAL PAPERS.
theory, we must so reduce the mass of the cord, or else so exaggerate
the friction, that there cannot be free vibrations. We may suppose
that the displacement of the cord represents the transverse voltage in
both cases. But the current will be in the same phase as the transverse
voltage in one case, and proportional to its variation along the circuit
in the other.
We may conveniently divide circuits, so far as their signalling
peculiarities are concerned, into five classes. (1). Circuits of such
short length, or so operated upon, that any effects due to electric
displacement are insensible. The theory is then entirely magnetic, at
least so far as numerical results are concerned. (2). Circuits of such
great length that they can only be worked so slowly as to render
electromagnetic inertia numerically insignificant in its effects. Also
some telephonic circuits in which fi/Ln is large. Then, at least so far
as the reception of signals is concerned, we may apply the electrostatic
theory. (3). The exceedingly large intermediate class in which both
the electrostatic and magnetic sides have to be considered, not separ-
ately, but conjointly. (4). The simplified form of the last to which we
are led when the signals are very rapid and the wires of low resistance.
(5). The distortionless circuit, in which, by a proper amount of uniform
leakage, distortion of signals is abolished, whether fast or slow.
Regarded from the point of view of practical application, this class lies
on one side. But from the theoretical point of view, the distortionless
circuit lies in the very focus of the general theory, reducing it to simple
algebra. I was led to it by an examination of the effect of telephones
bridged across a common circuit (the proper place for intermediate
apparatus, removing their impedance) on waves transmitted along the
circuit. The current is reflected positively, the charge negatively, at a
bridge. This is opposite to what occurs when a resistance is put in
the main circuit, which causes positive reflexion of the charge, and
negative of the current. Unite the two effects and the reflexion of the
wave is destroyed, approximately when the resistance in the main
circuit and the bridge-conductance are finite, perfectly when they are
infinitely small, as in a uniform distortionless circuit.
PART III.
SPHERICAL ELECTROMAGNETIC WAVES.
15. Leaving the subject of plane waves, those next in order of
simplicity are the spherical. Here, at the very beginning, the question
presents itself whether there can be anything resembling condensational
waves ?
Sir W. Thomson (" Baltimore Lectures", as reported by Forbes in
Nature, 1884) suggested that a conductor charged rapidly alternately +
and - would cause condensational waves in the ether. But there is no
other way of charging it than by a current from somewhere else, so he
suggested two conducting spheres to be connected with the poles of an
ON ELECTROMAGNETIC WAVES. PART III. 403
alternating dynamo. The idea seems to be here that electricity would
be forced out of one sphere and into the other to and fro with great
rapidity, and that between the spheres there might be condensational
waves.
But in this case, according to the Faraday law of induction, the
result would be the setting up of alternating electromagnetic disturb-
ances in the dielectric, exposing the bounding surfaces of the two
spheres to rapidly alternating magnetizing and electrizing force, causing .
waves, approximately spherical at least, to be transmitted into the
spheres, in the diffusion manner, greatly attenuating as they progressed
inward.
Perhaps, however, there can be condensational waves if we admit
that a certain quite hypothetical something called electricity is com-
pressible, instead of being incompressible, as it must be if we in
Maxwell's scheme make the unnecessary assumption that an electric
current is the motion through space of the something. In fact, Prof.
J. J. Thomson has calculated* the speed of condensational waves
supposed to arise by allowing the electric current to have convergence.
But a careful examination of his equations will show that the con-
densational waves there investigated do not exist, i.e., the function
determining them has the value zero.f
16. To construct a perfectly general spherical wave we may proceed
thus. The characteristic equation of H, the magnetic force, in a homo-
geneous medium free from impressed force is, by (2) and (3),
V2H = (4w/i^ + /tfjp*)H (93)
Now, let r be the vector distance from the origin, and Q any scalar
function satisfying this equation. Let
H = curl(rQ) (94)
Then this derived vector will satisfy (93), and have no convergence,
and have no radial component, or will be arranged in spherical sheets
From it derive the other electromagnetic quantities. Change H to E
to obtain spherical sheets of electric force.
This method leads to the spherical sheets depending upon any kind
of spherical harmonic. They are, however, too general to be really
useful except as mathematical exercises. For the examination of the
manner of origin and propagation of waves, zonal harmonics are more
useful, besides leading to the solution of more practical problems. It
is then not difficult to generalize results to suit any kind of spherical
harmonics.
The Simplest Spherical Waves.
17. Let the lines of H be circles, centred upon the axis from which 0
is measured, and let r be the distance from the origin. We have no
concern with <£ (longitude) as regards H, so that the simple specification
* B.A. Report on Electrical Theories.
1 1 ought to qualify this by adding that the investigation seems very obscure,
so that, although I cannot make the system work, yet others may.
404 ELECTRICAL PAPERS.
of its intensity H fully defines it. Under these circumstances the
equation (93) becomes
(95)
= q*rH, say,
where the acute accent denotes differentiation to r, and the grave accent
to cos 6 or n, whilst v stands for sin 9. The inductivity will be now /*0,
to avoid confusing with the p of zonal harmonics. Equation (95) also
defines q in the three forms it can assume in a conductor, dielectric, and
conducting dielectric.
Now try to make rH be an undistorted spherical wave, i.e. H varying
inversely as the distance, and travelling inward or outward at speed v.
Let
rH=Af(r-vt), ............................. (96)
where A is independent of r and t. Of course we must have & = 0,
making q =p/v. Now (96) makes
v\rH)" = rfH', .................................. (97)
which, substituted in (95), gives
v(v#)^ = 0; ...................................... (98)
therefore Av = Al^ + Sl .............................. (99)
From these we find the required solutions to be
(100)
(101)
where F0 is any function, Al and Bl constants, E and F the two com-
ponents of the electric force, F being the radial component out, and E
the other component coinciding with a line of longitude, the positive
direction being that of increasing 0, or from the pole. Similarly, if the
lines of E be circular about the axis, we have the solutions
S- -ftpfl.- -^4±±^FI,(r-vt), ............. (102)
Hr-^FJf-^, ........................ (103)
where Hr and He are the radial and tangential components of H.
But both these systems involve infinite values at the axis. We must
therefore exclude the axis somehow to make use of them. Here is one
way. Describe a conical surface of any angle 6V and outside it another
of angle #2, and let the dielectric lie between them. Make the tan-
gential component of E at the conical surfaces vanish, requiring infinite
conductivity there, and we make F vanish in (101), and produce the
solution
(104)
ON ELECTROMAGNETIC WAVES. PART III. 405
exactly resembling plane waves as regards rvE. Here B is the same as
/V-#i» and/ the same as Ff0, in equation (100).*
18. Now bring in zonal harmonics. Split equation (95) into the two
(rHY' = {q*+?«™+VyH, (105)
^ / rr\\> 7/l\Til T 1 ) TT /irk£\
-^(vJti) = — — i — - — '-it V*^"/
The equation (106) has for solution
where A is independent of (9, and is to be found from (105).
The most practical way of getting the r functions is that followed by
Professor Rowland in his paper f wherein he treats of the waves
emitted when the state is sinusoidal with respect to the time. We shall
come across the same waves in some problems.
Let H=Pm-vQ^ ............................. (107)
Then the equation of Pm is, by insertion of (107) in (105),
(108)
* In order to render this arrangement (104) intelligible in terms of more every-
day quantities, let the angles 6l and 6% be small, for simplicity of representation ;
then we have two infinitely conducting tubes of gradually increasing diameter
enclosing between them a non-conducting dielectric. Now change the variables.
Let V be the line-integral of E across the dielectric, following the direction of the
force ; it is the transverse voltage of the conductors. Let 4cirC be the line-integral
of H round the inner tube ; it is the same for a given value of r, independent of 6 ;
C is therefore what is commonly called the current in the conductor. We shall
have
V= LvC, C=SvV, LSv2 = 1 ;
where L is the inductance and 8 the permittance, per unit length of the circuit.
The value of L is
L = 2/t0 log [(tan |02) ± (tan \OJ\ ;
so that the circuit has uniform inductance and permittance. The value of G in
terms of (104) is
When the tubes have constant radii c^ and a2, the value of L reduces to the well
known
of concentric cylinders. The wave may go either way, though only the positive
wave is mentioned.
-\-PhiL Mag., June 1884, " On the Propagation of an Arbitrary Electromagnetic
Disturbance, Spherical Waves of Light, and the Dynamical Theory of Refraction."
Prof. J. J. Thomson has also considered spherical waves in a dielectric in his paper
" On Electrical Oscillations and Effects produced by the Motion of an Electrified
Sphere," Proc. London Math. Soc. vol. xv., April 3, 1884. [See also Stoke's
Mathematical and Physical Papers, and Rayleigh's Sound on the subject of
these functions.!
406 ELECTRICAL PAPERS.
and the solution, for practical purposes with complete harmonics, is
m(m2-l2)(m+2) m(m2-l)(m2-22)(m+3)
2qr
We shall find the first few useful, thus : —
P1==l- (qr)-\ }
, .............. (110)
Now let U= eT, so that U is the r function in Hr. If we change
the sign of q in U, producing, say, W, it is the required second solution
of (105). Thus
_
in the very important case of Qlt when m= 1.
The conjugate property of Z7 and W is
U'tr=-2q, ........................ (112)
which is continually useful.
We have next to combine U and W so as to produce functions suitable
for use inside spheres, right up to the centre, and finite there. Let
u = \(U+W), w = i(U-W), .............. (113)
It will be found that when m is even, w/r is zero and u/r infinite at the
origin ; but that when m is odd, it is u/r that is zero at the origin and
w infinite.
The conjugate property of u and w is
uw' - u'w = q, ............................ (114)
corresponding to (112).
Construction of the Differential Equations connected with a Spherical Sheet of
Vorticity of Impressed Force.
19. Now let there be two media — one extending from r = 0 to r = a, in
which we must therefore use the w-function or ^-function, according as
m is odd or even, and an outer medium, or at least one in which q has a
different form in general. Then, within the sphere of radius a, we have
H=Ar-iu, ............................... (115)
-^ = ^r-V, .............................. (116)
where ^ = 4=7rk + cp, and we suppose m odd. It follows that
E 1 u' (H7)
r=-^¥
In the outer medium use W, if the medium extends to infinity, or both
U and W if there be barriers or change of medium. First, let it be an
infinitely extended medium. Then, in it,
H=Br~\u-w\ ............................ (118)
r-\uf-wr], .......................... (119)
ON ELECTROMAGNETIC WAVES. PART III. 407
where k2 = kirk + cp in the outer medium. From these
B\*-«f ............................ (120)
H k2 u-w
(117) and (120) show the forms of the resistance-operators on the two
sides.*
Now, at the surface of separation, r = a, H is continuous (unless we
choose to make it a sheet of electric current, which we do not) ; so that
the H in (117) and (120) are the same. We only require a relation
between the E's to complete the differential equation.
Let there be vorticity of impressed force on the surface r = a, and
nowhere else (the latter being already assumed). Then
curle = curlE .......................... (121)
is the surface-condition which follows ; or, if / be the measure of the
curl of e,
/-£,-*„ ............................. (122)
E2 meaning the outer and El the inner E. Therefore
(123)
Ha denoting the surface H. So, by (117) and (120), used in (123),
/i 4 1 "L^SW (r=a)) ............. (124)
\& U, kzUz-wJ
the required differential equation. Observe that u^ only differs from
u2 and w1 from w2 in the different values of q inside and outside (when
different), and that r = a in all.
* Some rather important considerations are presented here. On what principles
should we settle which functions to use internally and externally, seeing that these
functions U and W are not quantities, but differential operators ? First, as regards
the space outside the surface of origin of disturbances. The operator e«r turns
J\t) iutojlt + r/v), and can therefore only be possible with a negative wave, coming
to the origin. But there cannot be such a wave without a barrier or change of
medium to produce it. Hence the operator e~9r alone can be involved in the exter-
nal solution when the medium is unbounded, and we must use W. Next, go inside
the sphere r = a. It is clear that both U and W are now needed, because disturb-
ances come to any point from the further as well as from the nearer side of the
surface, thus coming from and going to the centre. Two questions remain : Why
take U and W in equal ratio ; and why their sum or their difference, according as
m is odd or even ? The first is answered by stating the facts that, although it is
convenient to assume the origin to be a place of reflection, yet it is really only a
place where disturbances cross, and that the H produced at any point of the sur-
face is (initially) equal on both sides of it. The second question is answered by
stating the property of the Q}n function, that it is an even function of /j. when m is
odd, and conversely ; so that when m is odd the H disturbances arriving at any
point on a diameter from its two ends are of the same sign, requiring U+ W ', and
when m is even, of opposite sign, requiring U - W.
Similar reasoning applies to the operators concerned in other than spherical
waves. Cases of simple diffusion are brought under the same rules by generalizing
the problem so as to produce wave-propagation with finite speed. On the other
hand, when there are barriers, or changes of media, there is no difficulty, because
the boundary conditions tell us in what ratio U and W must be taken.
408 ELECTRICAL PAPERS.
Equation (124) applies to any odd m. When m is even, exchange u
and w, also u' and w'. In the mth system we may write
the form of <£ being given in (124). The vorticity of the impressed
force is of course restricted to be of the proper kind to suit the mth zonal
harmonic. Thus, any distribution of vorticity whose lines are the lines
of latitude on the spherical surface may be expanded in the form
2/mvCi, .............................. (126)
and it is the mth of these distributions which is involved in the preceding.
20. Both media being supposed to be identical, <£ reduces to
«£ = ! _ 2 _ , ...(127)
*!«.(«.-«>.)
by using (114) in (124). This is with m odd ; if even, we shall get
<£ = !- jJL -- .......................... (128)
^ «*.(«. -w.)
In a non-dielectric conductor, &1 = 47r&, and cf = ^Tr^p; so that,
keeping to m odd,
__ ..................... (129)
Ua(Ua-Wa)
In a non-conducting dielectric, ^ = cp, and q =p/v ; so
<t>= ,*>* . .............................. (130)
«.(«.- «O
In this case the complete differential equation is
-Mo«
when there is any distribution of impressed force in space whose vor-
ticity is represented by (126).
Outside the sphere, consequently,
— a"" r >(132)
(out)
.(133)
understanding that when no letter is affixed to u or w, the value at
distance r is meant. We see at once that ua = 0 makes the external
field vanish, i.e., the field of the particular / concerned. This happens
when / is a sinusoidal function of the time, at definite frequencies.
Also, inside the sphere,
(135)
ON ELECTROMAGNETIC WAVES. PART III. 409
As for the radial component Ft it is not often wanted. It is got thus
from H: —
-cpF=r-\vH)\ .......................... (136)
where for cp write 4?r^ + cp in the general case. Thus, the internal F
corresponding to (135) is
(in) tp*-2fi±l)«K-«OWU .............. (137)
Practical Problem. Uniform Impressed Force, in the Sphere.
21. If there be a uniform field of impressed force in the sphere,
parallel to the axis, of intensity fv its vorticity is represented by /x sin 6
on the surface of the sphere. It is therefore the case m = 1 in the above.
Let this impressed force be suddenly started. Find the effect produced.
We have, by (132),*
(out) H=ua(u-w)^-} ........................... (138)
or, in full, referring to the forms of u and w, equations (110) to (113),
->A - JLYl + IW €-*<Wi + 1 Yi + ^|/r (139)
Effect the integrations indicated by the inverse powers of q or p/v;
thus
if /! be zero before and constant after t = 0. As for the exponentials,
use Taylor's theorem, as only differentiations are involved. We get,
after the process (140) has been applied to (139), and then Taylor's
theorem carried out,
a r ar/ a r
where vi = vt-r + a vt = vt — r-a.
* It will be observed that the operator connecting/! and H is of such a nature that
the process of expansion of H in a series of normal functions fails. I have examined
several cases of this kind. The invariable rule seems to be that when there is a
surface of vorticity of e, leading to an equation of the form f- (f)H, and there is a
change of medium somewhere, or else barriers, causing reflected waves, the form of
0 is such that we can, when / is constant, starting at t = 0, solve thus [p. 373, vol. n. ]
extending over all the (algebraical) p-roots of 0 = 0, which is the determinantal
equation. But should there be no change of medium, the conjugate property of
the functions concerned comes into play. It causes a great simplification in the
form of tf>, and makes the last method fail completely, all trace of the roots having
disappeared. But if we pass continuously from one case to the other, then the last
formula becomes a definite integral. On the other hand, we can immediately
integrate /= (f>H in its simplified form, and obtain an interpretable equivalent for
the definite integral, the latter being more ornamental than useful. In the simpli-
fied form, 0 may be either rational or irrational. The integration of the irrational
forms will be given in some later problems.
410 ELECTRICAL PAPERS.
It is particularly to be noticed that the ^ part of (141) only comes into
operation when ^ reaches zero, and similarly as regards the t2 part.
Thus, the first part expresses the primary wave out from the surface ;
the second, arriving at any point 2a/v later than the first, is the reflected
wave from the centre, arising from the primary wave inward from the
surface.
The primary wave outward may be written
where vt>(r-a), and the second wave by its exact negative, with
vt>(r + a). Now, by comparing (132) with (134), we see that the
internal solution is got from the external by exchanging a and r in the
{}'s in (139) and (141), including also in ^ and t2. The result is that
(142) represents the internal H in the primary inward wave, vt having
to be >(a-r)-, whilst its negative represents the reflected wave,
provided vt>(a + r).
The whole may be summed up thus. First, vt is <a. Then (142)
represents H everywhere between r = a + vt and r = a-vt. But when vt
is >a, H is given by the same formula between the limits r = vt-a and
vt + a. In both cases jETis zero outside the limits named.
The reflected wave, superimposed on the primary, annuls the H
disturbance, which is therefore, after the reflexion, confined to a
spherical shell of depth 2a containing the uncancelled part of the
primary wave outward.
The amplitude of H at the front of the two primary waves, in and
out, before the former reaches the centre, is
After the inward wave has reached the centre, however, the amplitude
of H on the front of the reflected wave is the negative of that of the
primary wave at the same distance, which is itself negative.
The process of reflexion is a very remarkable one, and difficult to
fully understand. At the moment t = a/v that the disturbance reaches
the centre, we have H = (flv) + (4/*00), constant, all the way from r = 0
to 2&, which is just half the initial value of H on leaving the surface of
the sphere. But just before reaching the centre, H runs up infinitely
for an infinitely short time, infinitely near the centre ; and just after
the centre is reached we have H = — GO infinitely near the centre, where
the ^-disturbance is always zero, except in this singular case when it
is seemingly finite for an infinitely short time, though, of course, v is
indeterminate.
With respect to this running-up of the value of H in the inward
primary wave, it is to be observed that whilst H is increasing so fast at
and near its front, it is falling elsewhere, viz., between near the front
and the surface of the sphere ; so that just before the centre is reached
H has only half the initial value, except close to the centre, where it is
enormously great.
After reflexion has commenced, the ^-disturbance is negative in the
hinder part of the shell of depth 2a which goes out to infinity, positive
ON ELECTROMAGNETIC WAVES. PART III. 41 1
of course still in the forward part. At a great distance these portions
become of equal depth a ; at the front of the shell H=(flva)(2pQvr)~l,
at its back H= - ditto ; using of course a different value of r.
22. As regards the electric field, we have, by (133),
(out) E= --L-H. \(u' -*</)/i; .............. (143)
which, expanded, is
comparing which with (139), we see that
qa
We have, therefore, only to develop the second part, which is not in
the same phase with H. It is, in the same manner as before,
,U6)
only operating when vtl = vt — r + a, and vtz = vt — r-a are positive. Or,
1 and 2 referring to the two waves. So, when vt> (r + a), and the two
are coincident, we have the sum
which is the tangential component of the steady electric field left
behind.
The radial component F is, by (137),
(out)
where the unwritten term . . . may be obtained from the preceding by
changing the sign of a. Or
...... "49)
where vt1 = vt + a- r. Or,
-*--*-''#+~* <150>
so that, when both waves coincide, we have their sum,
F 2/ia3cos^
'" — — »
which is the radial component of the steady field left behind by the
part of the primary wave whose magnetic field is wholly cancelled.
412 ELECTRICAL PAPERS.
To verify ; the uniform field of impressed force of intensity flt by
elementary principles, produces the external electric potential
whose derivatives, radial and tangential, taken negatively, are (151)
and (147). The corresponding internal potential is
ft = J// cos 6.
But its slope does not give the force E left behind within the sphere,
because this E is the force of the flux. Any other distribution of
impressed force, with the same vorticity, will lead to the same E. Our
equation (135) and its companion for F, derived from (134) by using
(136), lead to the steady field (residual)
E=-$fl«m6, ^f/icosfl, ............... (152)
the components of the true force of the flux. Add e to the slope of ft
to produce E.*
F is always zero at the front of the primary wave outward, and
E = fJ'QvH. At the front of the primary wave inward F is also zero,
and E = - p^H. After reflection, F at the front of the reflected wave
is still zero, but now E = ^vH.
The electric energy Ul set up is the volume-integral of the scalar
product ^eD. That is,
Di-ttx^x***^ ................... (153)
But the total work done by e is 2 Uv by the general law that the
whole work done by impressed forces suddenly started exceeds the
amount representing the waste by Joule-heating at the final rate (when
there is any), supposed to start at once, by twice the excess of the
electric over the magnetic energy of the steady field set up. It is
clear, then, that when the travelling shell has gone a good way out, and
it has become nearly equivalent to a plane wave, its electric and mag-
netic energies are nearly equal, and each nearly J U^ in value. I did
not, however, anticipate that the magnetic energy in the travelling
shell would turn out to be constant, viz., %Ul during the whole journey,
from t = a/v to t = oo , so that it is the electric energy in the shell which
gradually decreases to J Ur Integrate the square of H according to
(142) to verify.
23. The most convenient way of reckoning the work done, and also
the most appropriate in this class of problems, is by the integral of the
* Sometimes the flux is apparently wrongly directed. For example, a uniform
field of impressed force from left to right in all space except a spherical portion
produces a flux from right to left in that portion. This is matte intelligible by
the above. Let the impressed force act in the space between r=a and r=b, a
being small and b great. In the inner sphere the first effects are those due to the
r=a vorticity, and the flux left behind is against the force. But after a time
comes the wave from the r=b vorticity, which sets matters right. The same
applies in the case of conductors, when, in fact, a long time might have to elapse
before the second and real permanent state conquered the first one.
ON ELECTROMAGNETIC WAVES. PART III. 413
scalar product of the curl of the impressed force and the magnetic force.
Thus, in our problem
> ...... (154)
where dS is an element of the surface r = a. So we have to calculate
the time-integral of the magnetic force at the place of vorticity of e, the
limits being 0 and 2a/v. This can be easily done without solving the
full problem, not only in the case of m= 1, but m = any integer. The
result is, if Um be the electric energy of the steady field due to fm,
and, therefore, by surface-integration according to (154),
(156)
J Um is the magnetic energy in the mth travelling shell. I have entered
into detail in the case of m = 1, because of its relative importance, and
to avoid repetition. In every case the magnetic field of the primary
wave outward is cancelled by that of the reflection of the primary
wave inward, producing a travelling shell of depth 2a, within which is
the final steady field. There, are, however, some differences in other
respects, according as m is even or odd.
Thus, in the case m=- 2, we have, by (110) to (113),
1 + 3 \ _ ^H-a,/! + 1 + 3 \ I x A 3 3 \
qa q2a?J \ go, qWJ) \ qr fl*J
Making this operate upon /2, zero before and constant after t = 0, we
obtain, by (132), (140), and Taylor's theorem,
In the wave represented, vt>(r-a), it being the primary wave out.
The unrepresented part, to be obtained by changing the sign of a
within the {}, is the reflected wave, in which vt>(r + a).
To obtain the internal H exchange a and r within the {} in (158).
The result is that
............ <159>
expresses the IT-solution always, provided that when vt < a the limits
for r are a - vt and a + vt; but when vt > a, they are vt - a and vt + a.
At the surface of the sphere,
from £ = 0 to 2a/v. It vanishes twice, instead of only once, inter-
mediately, finishing at the same value that it commenced at, instead of
at the opposite, as in the m = 1 case.
414 ELECTRICAL PAPERS.
The radial component F of E is always zero at the front of either of
the primary waves or of the reflected wave, and E = ± ^vH, according
as the wave is going out or in. In the travelling shell H changes sign
m times, thus making m + 1 smaller shells of oppositely directed
magnetic force. At its outer boundary
....................... (161)
and at the inner boundary the same formula holds, with ± prefixed
according as m is even or odd.
In case m = 3, the magnetic force at the spherical surface is
-f*v® Sift* 15**** 5
" ~
from t = 0 to 2fl/i> ; after which, zero.
Spherical Sheet of Radial Impressed Force.
24. If the surface r = a be a sheet of radial impressed force, it is clear
that the vorticity is wholly on the surface. Let the intensity be inde-
pendent of <£, so that
e = ?emQm (163)
The steady potential produced is
(in) r1--v^a^Lt4r/ry') (i64)
............. (165)
because, at r = a, these make
Fs-r^e, and dFJdr^dFJdr; ............. (166)
i.e., potential-difference e, and continuity of displacement. The normal
component of displacement is
therefore, integrating over the sphere, the total work done by e is
(168)
which agrees with the estimate (156), because
/._* r*
add a dp
finds the vorticity, /, from the radial impressed force e ; or, taking
e = emQm, •*• ^mvQlfl,-l = vorticity,
so that the old fm = em/a.
Single Circular Vortex Line.
25. There are some advantages connected with transferring the
impressed force to the surface of the sphere, as it makes the force of the
ON ELECTROMAGNETIC WAVES. PART III. 415
flux and the force of the field identical both outside and inside. At
the boundary F is continuous, E discontinuous.
Let the impressed force be a simple circular shell of radius a, and
strength e. Let it be the equatorial plane, so that the equator is the
one line of vorticity. Substitute for this shell a spherical shell of
strength \e on the positive hemisphere, - \e on the negative, the
impressed force acting radially. Expand this distribution in zonal
harmonics. The result is
15-L3-5 mm
..... (170)
so that we are only concerned with the odd ra's. This equation settling
the value of em, the vorticity is
?ema-ivQl = ?fmvQl ........................ (171)
We know therefore, by the preceding, the complete solution due to
sudden starting of the single vortex-line. That is, we know the
individual waves in detail produced by elt ez, etc. The resultant
travelling disturbance is therefore confined between two spherical
surfaces of radii vt-a and vt + a, after the centre has been reached,
or of radii a — vt and a + vt before the centre is reached. But it
cannot occupy the whole of either of the regions mentioned.
The actual shape of the boundaries, however, may be easily found.
It is sufficient to consider a plane section through the axis of the
sphere. Let A and B be the points on this plane cut by the vortex-
line. Describe circles of radius vt with A and B as centres. If vt < a,
the circles do not intersect ; the disturbance is therefore wholly within
them. But when vt is > a, the intersecting part contains no H, and
only the E of the steady field due to the vortex-line, which we know
by § 24.
That within the part common to both circles there is no H we may
prove thus. The vortex-line in question may be imagined to be a line
of latitude on any spherical surface passing through A and B, and
centred upon the axis. Let ax be the radius of any sphere of this kind.
Then, at a time making vt>a, the disturbance must lie between the
surfaces of spheres of radii vt - ax and vt + av whose centre is that of
the sphere a^. Now this excludes a portion of the space between the
vt - a and vt + a circles, referring to the plane section ; and by varying
the radius a^ we can find the whole space excluded. Thus, find the
locus of intersections of circles of radius
with centre at distance z from the origin, upon the axis. The equation
of the circle is
or x* + y*-2xz = vW + az-2vt(a? + z*) ............... (172)
Differentiate with respect to zt giving
x*) =ax, .......................... (173)
416 ELECTRICAL PAPERS.
and eliminate z between (173) and (172). After reductions, the result is
x* + (y±a)* = vW, ........................... (174)
indicating two circles, both of radius vt, whose centres are at A and B.
Within the common space, therefore, the steady electric field has been
established.
If this case be taken literally, then, since it involves an infinite
concentration in a geometrical line of a finite amount of vorticity of e,
the result for the steady field is infinite close up to that line, and the
energy is infinite. But imagine, instead, the vorticity to be spread
over a zone at the equator of the sphere r = a, half on each side of
it, and its surface-density to be /jv, where fl is finite. Consider the
effect produced at a point in the equatorial plane. From time t = 0 to
^ = (r-a)/v (if the point be external) there is no disturbance. But
from time ^ to t2 = b/v, where b is the distance from the point to the
edges of the zone, the disturbance must be identically the same as if the
harmonic distribution f^v were complete, viz. by (142),
*^*\ ...................... (175)
2
After this moment t2, the formula of course fails. Now narrow the
band to width adO at the equator and simultaneously increase fv so as
to make f^uLQ = e^ the strength of the shell of impressed force when
there is but one. The formula (175) will now be true only for a very
short time, and in the limit it will be true only momentarily, at the
front of the wave, viz.,
fla/2pQw = H = e/fy0wdO, .................... (176)
going up infinitely as dO is reduced. To avoid infinities in the electric
and magnetic forces we must seemingly keep either to finite volume
or finite surface-density of vorticity of e, just as in electrostatics with
respect to electrification.
Instead of a simple shell of impressed electric force, it may be one of
magnetic force, with similar results. As a verification, calculate the
displacement through circle v on the sphere r — a due to a vortex-circle
at Vj on the same surface, the latter being of unit strength. It is
,- ,
due to 2 emQm, through the circle v. Take then
m 2m(m+l)
which represents em due to vortex-line of unit strength at vr Use this
in the preceding equation (177), and we obtain
as the displacement through v due to unit vortex-line at vx. Applying
this result to a circular electric current, B = /x0H takes the place of
ON ELECTROMAGNETIC WAVES. PART III. 417
D = (c/4ir)B, as the flux concerned, whilst if h be the strength of the shell
of impressed magnetic force, h/4ir is the equivalent bounding electric
current. The induction through the circle v due to unit electric current
in the circle v^ is therefore obtainable from (179) by turning c to /x0 and
multiplying by (47r)2. The result agrees with Maxwell's formula for
the coefficient of mutual induction of two circles (vol. II., art. 697).
It must be noted that in the magnetic-shell application there must be
no conductivity, if the wave-formulae are to apply.
An Electromotive Impulse, m = 1.
26. Returning to the case of impressed electric force, let in a spherical
portion of an infinite dielectric a uniform field of impressed force act
momentarily. We know the result of the continued application of the
force. We have, then, to imagine it cancelled by an oppositely directed
force, starting a little later. Let ^ be the time of application of the
real force, and let it be a small fraction of 2a/v, the time the travelling
shell takes to traverse any point. The result is evidently a shell of
depth ^ at r = vt + a, in which the electromagnetic field is the same as in
the case of continued application of the force, and a similar shell situated
at r = vt- a, in which H is negative. Within this inner shell there is
no E or H. But between the two thin shells just mentioned there is a
diffused disturbance, of weak intensity, which is due to the sphericity of
the waves, and would be non-existent were they plane waves. In fact,
at time t = tv when the initial disturbance H—f^yft^ has extended itself
a small distance v^ on each side of the surface of the sphere, there is a
radial component F &t the surface itself, since, by (150),
(180)
so that the sudden removal of /j leaves two waves which do not satisfy
the condition E = p^H at their common surface of contact. On separa-
tion, therefore, there must be a residual disturbance between them.
The discontinuity in E at the moment of removing yj is abolished by
instantaneous assumption of the mean value, but it is impossible to
destroy the radial displacement which joins the two shells at the
moment they separate. Put on/j when £ = 0, then — /j at time tt later.
The H at time t due to both is, by (142),
W-2^); (181)
which, when ^ is infinitely small, becomes
H=-t^. ........................... (182)
2/ytf-2
First of all, at a point distant r from the centre, comes the primary
disturbance or head,
.............................. (183)
when vt = r- a, lasting for the time tr It is followed by the diffused
negative disturbance, or tail, represented by (182), lasting for the time
H.E.P. — VOL. ii. 2o
418 ELECTRICAL PAPERS.
2a/v. At its end comes the companion to (183), its negative, when
vt = r + a, lasting for time tv after which it is all over. This description
applies when r > a. If r < a, the interval between the beginning and
end of the JJ-disturbance is only 2r/v. From the above follows the
integral solution expressing the effect of ^ varying in any manner with
the time.
Alternating Impressed Forces.
27. If the impressed force in the sphere, or wherever it may be, be a
sinusoidal function of the time, making p2 = — n2, if n = 2?r x frequency,
the complete solutions arise from (132) to (135) so immediately that we
can almost call them the complete solutions. Of course in any case in
which we have developed the connection between the impressed force
and the flux, say e = ZC, or C = Z~1e) where Z is the resistance-operator,
we may call this equation the solution in the sinusoidal case, if we state
that p2 is to mean - n2. But there is usually a lot of work needed to
bring the solution to a practical form. In the present instance, how-
ever, there is scarcely any required, because u and w are simple functions
of qr, and q2 is real. The substitution p2 = - n2 in u results in a real
function of nr/v, and in w in a real function x ( - 1 )*. Thus : —
nr
(184)
3v2\ nr 3v . nr
--- sm— i
nr v (185)
nr
— + _cos
nzr2 v nr
nr)
— I.
v j
In the case m = 1, if (f^cosnt is the form of /lf so that (fj represents
the amplitude, we find, writing this case fully because it is the most
important : —
- ±sin^. (cos - -IsinY^ -
no, )v \ nr J\v
*a
- JLrin^"* . fsin + LcosV^ - *t\
)v \ nr
- 1 rin^. (sin + ±cosV^ - nt
nr J v \ na A • /
(in) B—
nr v na
ON ELECTROMAGNETIC WAVES. PART III. 419
It is very remarkable, on first acquaintance, that the impressed force
produces no external effect at all when
K.-0, or tan™-™.
V V
For the impressed force may be most simply taken to be a uniform field
of intensity (f})cosnt in the sphere of radius a acting parallel to the
axis, and it looks as if external displacement must be produced. Of
course, on acquaintance with the reason, the fact that the solution is
made up of two sets of waves, those outward from the lines of vorticity
and those going inward, and then reflected out, the mystery disappears.
To show the positive and negative waves explicitly, we may write
the first of (185a) in the form
(18M)
(ant) J-
na nr
.
n2arj \nr na
the second line showing the primary wave out, the first the reflected
wave.* Exchange a and r within the [ ] to obtain the internal H. The
disturbance, at the surface, of the primary wave going both ways is,
from t = 0 to 2a/v,
-
n2ar
The amplitude due to both waves is
The time-rate of outward transfer of energy per unit area at any
distance r is EHj^Tr. In the mth system this is
(-^)sm}^ (186)
where m is supposed odd, whilst u and - iw are the real functions of
* In reference to this formula (185rf), and the corresponding ones for other
values of m, it is not without importance to know that a very slight change
'suffices to make (lS5d) represent the solution from the first moment of starting
the impressed force. Thus, let it start when t = 0, and let the/x in equation (139)
be (fjcosnt. Effect the two integrations thus,
•6 = (/^sin nt, 4 = (/i)^1 ~ cos nt^
vanishing when t = 0, and then operate with the exponentials, and we shall obtain
(185rf) thus modified:— To the first line must be added
Lfife? *
2/jt.Qvr n2ar
and to the second line its negative. Thus modified, (185rf) is true from < = 0,
understanding that the second line begins when t = (r - a)/v, and the first when
t = (r + a)lv. The first of (185a) is therefore true up to distance r = rt-a, when
this is positive. In the shell of depth 2a beyond, it fails,
420 ELECTRICAL PAPERS.
nr/v obtained in the same way as (184). The mean value of the t
function is, by the conjugate property of u and u-, equation (114),
= -n/2v.
Using this, and integrating (186) over the complete surface of radius r,
giving
.(187)
JJ<
we find the mean transfer of energy outward per second through any
surface enclosing the sphere to be
• (/J2M>2, -..(188)
if (/m)v$mcos?i£ is the vorticity of the impressed force. [When in is
even substitute - w*.]
In the case m = 1 , the waste of energy per second is
due to the uniform alternating field of impressed force of intensity
(/j) cos nt within the sphere.
In reality, the impressed force must have been an infinitely long time
in operation to make the above solutions true to an infinite distance,
and have therefore already wasted an infinite amount of energy. If
the impressed force has been in operation any finite time t, however
great, the disturbance has only reached the distance r = vt + a. Of
course the solutions are true, provided we do not go further than
r = vt — a. We see, therefore, that the real function of the never-ceasing
waste of energy is to set up the sinusoidal state of E and H in the
boundless regions of space which the disturbances have not yet
reached. The above outward waves are the same as in Rowland's
solutions.* Here, however, they are explicitly expressed in terms of
the impressed forces causing them.
ua — 0 makes the external field vanish when m is odd ; and wa = 0
when m is even ; that is, when the sinusoidal state has been assumed.
It takes only the time 2a/v to do this, as regards the sphere r = a; the
initial external disturbance goes out to infinity and is lost. This
vanishing of the external field happens whatever may be the nature of
the external medium away from the sphere, except that the initial
external disturbance will behave differently, being variously reflected
or absorbed according to circumstances.
Conducting Medium. m= 1.
28. Now consider the same problem in an infinitely extended con-
ductor of conductivity k. We may remark at once that, unless the
conductivity is low, the solution is but little different from what it
would be were the conductor not greatly larger than the spherical
*In paper referred to in § 18.
ON ELECTROMAGNETIC WAVES. PART III. 421
portion within it on whose surface lie the vortex-lines of the impressed
force, owing to the great attenuation suffered by the disturbances as
they progress from the surface. In a similar manner, if the sphere be
large, or the periodic frequency great, or both, we may remove the
greater part of the interior of the sphere without much altering matters.
We have now
(190)
The realization is a little troublesome on account of this pt. The result
is that the uniform alternating field of impressed force of intensity
(/x) cos nt, gives rise to the internal solution
*?*}*uJr. ; see (129), § 20 fl
popj 'J
(in) H={(A+£)coBnt + (A-S)*mnt}, ..... (191)
where A and B are the functions of r expressed by
VOS + (_L - L + 2
rJ \2xr 2xa 2xr.2xa
i \cos_/ i + i + 2\8iu-i (a+r) (192)
xrJ \2xa 2xr 2xr.2xaJ J
A = c*-'f ( i + _L - J_VOS + (_L - L + 2 n~L(a _ r)
\__\ 2xa 2xrJ \2xr 2xa 2xr.2xaJ x
2xr
B
5-r- o- -
2xr 2xa 2xr.2xaJ \ 2xr 2xa
1 +^_+ 2 ; \ A 1 1 \ i
2xr 2xa 2xr.2xaJ \ 2xr 2xaJ
Equation (191) showing the internal H, the external is got by exchang-
ing a and r in the functions A and B.
Now xa is easily made large, in a good conductor ; then, anywhere
near the boundary, (r = a), we have
A = e-*(a-r> cos x(a -r), -B = €-*<«-»•> sin x(a - r), ..... (194)
and (191) becomes
(in) ff=*->.cos«i-z(«-r)- ........ (195)
The wave-length A is
Thus, in copper, a frequency of 1600 to 1700 makes A = l centim.
Both A and the attenuation-rate depend inversely on the square roots
of the inductivity, conductivity, and frequency, whereas the amplitude
varies directly as the square root of the conductivity, and inversely as
the square roots of the others.
[The attenuation in distance X is €-*X = €~27r; therefore we may say
it is nearly insensible further on. If we introduce an auxiliary
422 ELECTRICAL PAPERS.
impressed force to keep the current straight, we shall, when xa is
large, just double the external H and the activity.]
To verify that very great frequency ultimately limits the disturbance
to the vortex-line of e when there is but one, we may use the last solu-
tion to construct that due to a sheet of impressed force
acting radially on the surface of the sphere. Thus,
(in) H= f^fy. e^t-««-^(nt - x(a -r)- , (197)
when xa is very great. When the vorticity is confined to one line of
latitude, H in (197) vanishes everywhere except at the vortex-line.
But a further approximation is required, or a different form of solution,
to show the disturbance round the vortex-line explicitly, i.e., when n is
great, though not infinitely great.
A Conducting Dielectric. m = l.
29. Here, if k is the conductivity, c the permittivity, and /*0 the
inductivity, let
q = (4ir^ + fi0cp2)* = w1 + »2t> ................... (198)
when p = ni. Then n^ and nz will be given by
Using this q in the general external jET-solution, but ignoring the explicit
connexion with the impressed force, we shall arrive at
(out) H = *-'vl+ ,i caa- * Sm(n2r - nt), (2
where C0 is an undetermined constant, depending upon the magnitude
of the disturbance at r-a. So far as the external solution goes, how-
ever, the internal connexions are quite arbitrary save in the periodicity
and confinement to producing magnetic force proportional in intensity
to the cosine of the latitude. The solution (200) may be continued
unchanged as near to the centre as we please. Stopping it anywhere,
there are various ways of constructing complementary distributions in
the rest of space, from which (200) is excluded.
Wj is zero when k = 0. We then have the dielectric solution, with
% = n/v. On the other hand, c = 0 makes
as in § 28. The value of
Enormously great frequency brings us to the formulae of the non-
conducting dielectric, with a difference, thus : n1 and n2 become
n2 — n/Vj ..................... (202)
ON ELECTROMAGNETIC WAVES. PART III. 423
when 4:7rkfcn is a small fraction. The attenuation due to conductivity
still exists, but is independent of the frequency. We have now
(out) ff-^Vvfcos-- sinY— -tA (203)
r \ nr J\v J
differing from the case of no conductivity only in the presence of the
exponential factor.
It is, however, easily seen by the form of n^ in (202) that in a good
conductor the attenuation in a short distance is very great, so that the.
disturbances are practically confined to the vortex-lines of the impressed
force, where the /^-disturbance is nearly the same as if the conductivity
were zero, as before concluded. It follows that the initial effect of the
sudden introduction of a steady impressed force in the conducting
dielectric is the emission from the seat of its vorticity of waves in the
same manner as if there were no conductivity, but attenuated at their
front to an extent represented by the factor e~wir, with the (202) value
of nlt in addition to the attenuation by spreading which would occur
were the medium nonconducting. This estimate of the attenuation
applies at the front only.
Current in Sphere constrained to be uniform.
30. Let us complete the solution (200) of § 29 by means of a current
of uniform density parallel to the axis within the sphere of radius a,
beyond which (200) is to be the solution. This will require a special
distribution of impressed force, which we shall find. Equation (200)
gives us the normal component of electric current at r = a, by differenti-
ation. Let this be F cos 6. Then F is the density of the internal
current. The corresponding magnetic field must have the boundary-
value according to (200), and vary in intensity as the distance from the
axis, its lines being circles centred upon it, and in planes perpendicular
to it. Thus the internal H is also known. The internal E is fully
known too, being k"lT in intensity and parallel to the axis. It only
remains to find e to satisfy
curl(e-E) = /xH, (3) bis
within the sphere, and at its boundary (with the suitable surface inter-
pretation), as it is already satisfied outside the sphere. The simplest
way appears to be to first introduce a uniform field of e parallel to the
axis, of such intensity ^ as to neutralize the difference between the
tangential components of the internal and external E at the boundary,
and so make continuity there in the force of the field ; and next, to
find an auxiliary distribution e2, such that
curl e2 = /zH,
and having no tangential component on the boundary. This may be
done by having e2 parallel to the axis, of intensity proportional to
(a2 - r2) sin 6.
The result is that the internal H is got from the external by putting
r = a in (200) and then multiplying by r/a ; F from the internal H by
424 ELECTRICAL PAPERS.
multiplying by (27rrsin 0)~l ; e1 from the difference of the tangential
components E outside and inside is given by
(204)
Finally, the auxiliary force has its intensity given by
(205)
A remarkable property of this auxiliary force, which (or an equivalent)
is absolutely required to keep the current straight, is that it does no
work on the current, on the average ; the mean activity and waste of
energy being therefore settled by er
Nov. 27, 1887.
PART IV.
Spherical Waves (with Diffusion) in a Conducting Dielectric.
31. In an infinitely extended homogeneous isotropic conducting
dielectric, let the surface r = a be a sheet of vorticity of impressed
electric force ; for simplicity, let it be of the first order, so that the
surface-density is represented by fv. By (127), § 20, the differential
equation of H, the intensity of magnetic force is, at distance r from the
origin, outside the surface of/, (v meaning sin 6),
(206)
where / may be any function of the time. Here, in the general case,
including the unreal " magnetic conductivity " g* we have
..... (2Q7)
:ir + cp ;
if, for subsequent convenience,
......
The speed is v, and pv p2 are the coefficients of attenuation of the parts
transmitted of elementary disturbances due to the real electric con-
ductivity k and the unreal g ; that is, e~<* is the factor of attenuation
due to conductivity. On the other hand, the distortion produced by
conductivity depends on <r, and vanishes with it. There is some utility
* Owing to the lapse of time, I should mention that the physical and other
meanings of the coefficient g are explained in Part I. of this paper. Also k = electric
conductivity ; /* = magnetic inductivity ; and c/4?r = electric permittivity. All the
problems in this paper, except in § 43, relate to spherical waves ; the geometrical
coordinates are r and 6. Unless otherwise mentioned, p always signifies the
operator d/dt, t being the time.
ON ELECTROMAGNETIC WAVES. PART IV. 425
in keeping in g, because it sometimes happens that the vanishing of &,
making p = - o-, leads to a solvable case. We can then produce a real
problem by changing the meaning of the symbols, turning the magnetic
into an electric field, with other changes to correspond.
The Steady Magnetic Field due to f Constant.
32. Let/ be zero before, and constant after / = 0, the whole medium
having been previously free from electric and magnetic force. All
subsequent disturbances are entirely due to /. The steady field which
finally results is expressed by (206), by taking p = 0 ; that is, ^ has to
mean 4?r&, and q = ^ir(kg)^, by (207). To obtain the corresponding
internal field, exchange a and r in (206), except in the first a/r. The
same values of kt and q used in the corresponding equations of E and F
give the final electric field. The steady magnetic field here considered
depends upon g, and vanishes with it.
Variable State when /o1 = /o2- First Case. Subsiding f.
33. There are cases in which we already know how the final state
is reached, viz., the already given case of a nonconducting dielectric
(§§ 21, 22), and the case o- = 0 in (208), which is an example of the
theory of § 4. In the latter case the impressed force must subside at
the same rate as do the disturbances it sends out from the surface of/.
Thus, given/=/0e-^, starting when £ = 0, with/0 constant, the resulting
electric and magnetic fields are represented by those in the correspond-
ing case in a nonconducting dielectric, when multiplied by e-?1. The
final state is zero because / subsides to zero ; the travelling shell also
loses all its energy. But there are, in a sense, two final states; the
first commencing at any place as soon as the rear of the travelling shell
reaches it, and which is entirely an electric field ; the second is zero,
produced by the subsidence of this electric field. There is no magnetic
force to correspond, and therefore no "true" electric current, in Max-
well's sense of the term, except in the shell.
Second Case, f Constant.
34. But let the impressed / be constant. Then, by effecting the
integrations in (206), we are immediately led to the full solution
pr\ pa
+ same function of
-a , ...(209)
where the fully-represented part expresses the primary wave out from
the surface of /, reaching r at time (r - a)/v ; whilst the rest expresses
the second wave, reaching r when t = (r + a)/v. After that, the actual H
is their sum, viz.,
cosh -sinh, ........ .(210)
prj {_ pa
426 ELECTRICAL PAPERS.
agreeing with (206), when we give q therein the special value p/v at
present concerned, and ^ = 4-n-L
At the front of the first wave we have
.......................... (211)
so that the energy in the travelling shell still subsides to zero.
Equation (211) also expresses H at the front of the inward wave,
both before and after reaching the centre of the sphere. The exchange of
a and r in the [] in (209) produces the corresponding internal solution.
Unequal pl and p2. General Case.
35. If we put d/dr = V, we may write (206) thus,
It is, therefore, sufficient to find
e-«"-V/, .............................. (213)
to obtain the complete solution of (212); namely, by performing upon
the solution of (213) the differentiations V and the operation &1; This
refers to the first half of (212); the second half only requires the
changed sign of a in the [] to be attended to.
Now (213) is the same as
(214)
Expand the two functions of p in descending powers of p, thus,
9X 8 [-, 3 o-2 3.5 o-4 3.5.7 o-6
-*
........ <216>
where the h's are functions of r, but not of p. Multiplying these
together, we convert (213) or (214) to
where the i's are functions of r, but not of p. The integrations can
now be effected. Let/ be constant, first. Then, / starting when t = 0,
we have
^-3(/^)=/p"3(^-i-^-i^2) = p~3/(€/)03 say; ..... (218)
etc., etc. Next, operating with the exponential containing p in (217)
turns ttot-(r- a)/v, and gives the required solution in the form
same function of
-a , ........... (219)
ON ELECTROMAGNETIC WAVES. PART IV. 427
where ^ = t - (r - a)/v ; the represented part beginning when ^ reaches
zero, and the rest when t - (r + a)/v reaches zero.
Fuller Development in a Special Case. Theorems involving Irrational
Operators.
36. As this process is very complex, and (219) does not admit of
being brought to a readily interpretable form, we should seek for
special cases which are, when fully developed, of a comparatively
simple nature. Write the first half of (212) thus,
(220)
Now the part in the square brackets can be finitely integrated when
ft?1 subsides in a certain way. We can show that
....... (221)
in which, observe, the sign of a- may be changed, making no difference
on the right side (the result), but a great deal on the left side.
The simplest proof of (221) is perhaps this. First let r = a. Then
by getting the exponential to the left side, so as to operate on unity.
Next, by the binomial theorem,
^V}" ............. (223)
Now integrate, and we have (/ commencing when t = 0),
(224)
so that, finally,
(225)
It is also worth notice that, integrating in a similar manner,
<226>
These theorems present themselves naturally in problems relating to a
telegraph-circuit, when treated by the method of resistance-operators.
A special case of (225) is
(*Q-* ............................ (227)
428 ELECTRICAL PAPERS.
which presents itself in the electrostatic theory of a submarine
cable. *
We have now to generalize (225) to meet the case (221). The left
member of (221) satisfies the partial differential equation
t;2y2=^2_0-2) . ........................ (228)
so we have to find the solution of (228) which becomes J0(vti) when
r = a. Physical considerations show that it must be an even function
of (r - a), so that it is suggested that the t in JG(o-ti) has to become, not
t-(r — a)/v or t + (r - a)/v, but that t'2 has to become their product. In
any case, the right member of (221) does satisfy (228) and the further
prescribed condition, so that (221) is correct.
If a direct proof be required, expand the exponential operator in
(221) containing r in the way indicated in .(216), and let the result
operate upon JQ(a-ti). The integrated result can be simplified down to
(221).
37. Now use (221) in (220). Let fept=f0€~ftt where /0 is constant ;
and the square bracket in (220) becomes known, being in fact the right
member of (221) multiplied by /0. So, making use also of (228), we
bring (220) to
(229)
dr "
to which must be added the other part, beginning 2a/v later, got by
negativing a, except the first one. The operation (^-o-2)"1 may be
replaced by two integrations with respect to r.
Let r and a be infinitely great, thus abolishing the curvature. Let
r-a = zt and/0^a/r, which is now constant, be called eQ. Then we have
simply
(230)
showing the H produced in an infinite homogeneous conducting
dielectric medium at time t after the introduction of a plane sheet (at
2 = 0), of vorticity of impressed electric force, the surface-density of
* Thus, let an infinitely long circuit, with constants R, S, K, L, be operated
upon by impressed force at the place z = 0, producing the potential- difference V0
there, which may be any function of the time. Let G be the current and V the
potential- difference at time t at distance z. Then
where q = (R + Lp)*(K + 8p)*. Take K=Q, and L=Q; then, if F0 be zero before
and constant after t = 0, the current at z=0 is given by
and (227) gives the solution. Prove thus : let 6 be any constant, to be finally
made infinite ; then
p\(\ ) =
by the investigation in the text. Now put 6 = 00, and (227) results.
In the similar treatment of cylindrical waves in a conductor, pi, pi, etc., occur.
We may express the results in terms of Gamma-functions.
ON ELECTROMAGNETIC WAVES. PART IV. 429
vorticity being e0€"W. This corroborates the solution in § 8, equation
(51) [Part L, p. 383], whilst somewhat extending its meaning.
The condition to which/ is subject may be written, by (208),
f=f^, ............................... (231)
where /0 is constant. If, then, we desire / to be constant, pl must
vanish, which, by (208), requires k = 0, whilst g may be finite.
But we can make the problem real thus. In (229) change H to E
and pv to cv ; we have now the solution of the problem of finding the
electric field produced by suddenly magnetizing uniformly a spherical
portion of a conducting dielectric ; i.e., the vorticity of the impressed
magnetic force is to be on the surface of the sphere r = a, parallel to its
lines of latitude, and of surface-density fv, such that fve-fo1 is constant
This makes / constant when g = 0 and k finite, representing a real
conducting dielectric.
The Electric Force at the Origin dm to fv at r = a.
38. Eeturning to the case of impressed electric force, the differential
equation of F, the radial component of electric force inside the sphere
on whose surface r = a the vorticity of e is situated, is, by § 20,
equations (136), (137),
h
qr2 \ qaj \ qr J
At the centre, therefore, the intensity of the full force, which call
whose direction is parallel to the axis, is
= § l -««-/• .............. (233)
Unless otherwise specified, I may repeat that the forces referred to are
always those of the fluxes, thus doing away with any consideration of
the distribution of the impressed force, and of scalar potential, of vary-
ing form, which it involves. (233) is equivalent to
(234)
Let / be constant, and p = <r, or g = 0. Then (234) becomes
), ...... (235)
of which the complete solution is, by (221),
^o = (f /) (e-ftav-\p + ar)J0{crv-l(a2 - v*trf} + X\ (236)
where, subject to g = 0, €-qa(\) = Xa; (236a)
or, solved,
(237)
430 ELECTRICAL PAPERS.
in which £ = (-!)*, and all the J's operate upon <rti. This solution
(236) begins when t = a/v. The value of a- is 47r£/2e.
In a good conductor or is immense. Then assume c — 0, or do away
with the elastic displacement, and reduce (236) to the pure-diffusion
formula, which is
where y = (4:r/>d-a2/2/)i The relation of Xa in (236) to the preceding
terms is explained by equations (233) or (235).
Effect of uniformly magnetizing a Conducting Sphere surrounded by a
Nonconducting Dielectric.
39. Here, of course, it is the lines of E that are circles centred upon
the axis, both inside and outside. Let h be the impressed magnetic
force, and hv the surface-density of its vorticity, at r = o> outside which
the medium is nonconducting, and inside a conducting dielectric. The
differential equation of EM the surf ace- value of the tensor of E at r = a,
is (compare (124), § 19)
(239)
in which r = a, and p and q are to have the proper values on the two
sides of the surface.
Now, by (111),
W'\W= -q{l+(qr)-i(l+qr)-1} ............... (240)
in the case of m=l, (first order), here considered. This refers to the
external dielectric, in which q =p/v. Let v = oc , making
W\W= -ft"1 ............................. (241)
This assumption is justifiable when the sphere has sensible conductivity,
on account of the slowness of action it creates in comparison with the
rapidity of propagation in the dielectric outside. Then (239) becomes
hv 1 flsinhq 1/1_1\ /242)
cosn <lia ~ feoO
if ft0 is the external and /Xj the internal inductivity, and ql the internal
. When the inductivities are equal, there is a material simplification, .
ing to
lfl " ( "lBinh Whv, ............... (243)
q^a smh q^a
where ql = {(4ir^ + c^pj^p}^. First let cl = 0-, in the conductor, making
j12 = 4ir/*1^= -s2, say. Then
(sa)~lsmsa
(244)
ON ELECTROMAGNETIC WAVES. PART IV. 431
From this we see that sin sa = 0 is the determinantal equation of normal
systems. The slowest is
sa = 7T, or -p-l = 4fi1k1a?/ir ................. (245)
This time-constant is about (1250)"1 second if the sphere be of copper
of 1 centim. radius; about 8 seconds if of 1 metre radius, and about 10
million years if of the size of the earth.
At distance r from the centre of the sphere, within it, at time / after
starting A, we have
F= hv cossr-(sr)-lsmsr
subject to the determinantal equation, over whose roots the summation
extends, p being now algebraic. Effecting the differentiation indicated,
we obtain
" ...(247)
cos sa
The corresponding solution for the radial component of the magnetic
force, say H^ is
Hr = (» cos 6) - 4h cos 0 % cos Sr~
At the centre of the sphere, let HQ be the intensity of the actual
magnetic force. It is, by (248),
jyo = ^(l + 22(cosm)-V^ ..................... (249)
Thus the magnetic force arrives at the centre of the sphere in identi-
cally the same manner as current arrives at the distant end of an
Atlantic cable according to the electrostatic theory, when a steady
impressed force is applied at the beginning, with terminal short-circuits.
In the case of the cable the first time-constant is
where El is the total resistance and SI the total permittance. It is not
greatly different from 1 second, so that, by (245), the sphere should be
about a foot in radius to imitate, at its centre, the arrival-curve of the
cable.
To be precise we should not speak of magnetizing the sphere, because
(ignoring the minute diamagnetism) it does not become magnetized.
The principle, however, is the same. We set up the flux magnetic
induction. But the magnetic terminology is defective. Perhaps it
would be not objected to if we say we inductize* the sphere, whether
we magnetize it or not. This is, at any rate, better than extending the
meaning of the word magnetize, which is already precise in the mathe-
matical theory, though of uncertain application in practice, from the
variable behaviour of iron.
* Accent the first syllable, like magnetize. Practical men sometimes speak of
energizing a core, etc. But energize is too general ; by using inductize we specify
what flux is set up.
432 ELECTRICAL PAPERS.
40. The following is the alternative form of solution showing the
waves, when cl is finite. With the same assumption as before that
v = oo outside the sphere, the equation of Hr, the radial component of
H, is
Tj_2cosO cosh qr — (qr)~lsinhqr i
U'—fjr (qa)-i sinh qa
which, at r = 0, becomes
HQ = 2qa(sinhqa)-lh ......................... (251)
Expand the circular function, giving
HQ = ±qat-'ia(l+t-^ + 6-*9a+...}h; .............. (252)
or, since here q = v~l{(p + <r)2 -o-2}*, where a- = 4jr&/2e,
(253)
so, using (221), we get finally
H° = '"<* + <r)<7»fl' " ** + J9a" - "2'2) + • • •• (254)
The J0 functions commence when vt='a, 3a, 5a, <3tc., in succession,
and the successive terms express the arrival of the fi it wave and of the
reflexions from the surface which follow. In the cas of pure diffusion,
this reduces to
#0 = (1^)20(47^^ ..... (255)
which is the alternative form of (249), involving instantaneous action
at a distance. The theorem (in diffusion)
€-aspl._p*(l) = (irQ-*6-«8/« ..................... (256)
becomes generalized to
c-'«q(l)~V-*€-ff<(p+<r)JQ{<nrl(y?-iPP) }, .......... (257)
if = t
On the right side of (257), the p means, as usual, differentiation to t.
The two quantities a- and v may have any positive values ; to reduce to
(256), make v infinite whilst keeping or/v2 finite.
Diffusion of Waves from a Centre of Impressed Force in a
Conducting Medium.
41. In equation (206) let a be infinitely small. It then becomes
H=^a3vr-2(±7rk + cp)(l+qr)€-'irf) ............... (258)
the equation of H at distance r from an element of impressed electric
force at the origin. Comparing with (233), we see that the solution of
(258) may be derived, when / is constant, starting when t = 0. Take
g = 0, making p = <r = 4?r^/2c. Then
(259)
ON ELECTROMAGNETIC WAVES. PART IV. 433
where Xr is what the Xa of (237) becomes on changing a to r ; and
jgro = i/&r-2Xvol. integral of/, .................. (260)
supposing the impressed force to be confined to the infinitely small
sphere, so that its volume-integral is the " electric moment," by analogy
with magnetism. The solution (259) begins at r as soon as t = r/v. It
is true from infinitely near the origin to infinitely near the front ; but
no account is given of the state of things at the front itself. HQ is the
final value of H. We may also write Xr thus,
........... (261)
and (259) may also be written
tt~&M+*>(l-r*F* .................. (262)
When c = 0, (259) or (262) reduce to
where
Conducting Sphere in a Nonconducting Dielectric. Circular Vorticity
of e. Complex Reflexion. Special very Simple Case.
42. At distance r from the origin, outside the sphere of radius a,
which is the seat of vorticity of e, represented by fv, we have
r ........................ (264)
The operator <£ will vary according to the nature of things on both
sides of r = a. When it is a uniform conducting medium inside, and
nonconducting outside, to infinity, we shall have
when <£lf depending upon the inner medium, is given by
1
47T&J + c^p cosh q-^ - (q-^a) ^sinh q:a
and <£2, depending upon the outer medium, is given by
The solution arising from the sudden starting of/ constant is therefore
Pdp
where p is now algebraical, and the summation ranges over the roots of
<£ = 0. There is no final H in this case, if we assume # = 0 all over.
H.E.P. — VOL. II. 2 E
434 ELECTRICAL PAPERS.
But the determinantal equation is very complex, so that this (267)
solution is not capable of easy interpretation. The wave-method is
also impracticable, for a similar reason.
In accordance, however, with Maxwell's theory of the impermeability
of a " perfect " conductor to magnetic induction from external causes,
the assumption ^ = 00 makes the solution depend only upon the
dielectric, modified by the action of the boundary, and an extraordinary
simplification results. (j>i vanishes, and the determinantal equation
becomes </>2 = 0, which has just two roots,
qa=pafi-= - J±t(j)*; ...................... (268)
and these, used in (267), give us the solution
--*3 cos - 3*(1 - 2a/r)sinsN/3, ...... (269)
where z = (vt - (r - a)}/2a.
Correspondingly, the tangential and radial components of E are
............ (270)
*- / cos *l - -* cos - V32 - sinV3 (271)
This remarkably simple solution, considering that there is reflexion,
corroborates Prof. J. J. Thomson's investigation * of the oscillatory
discharge of an infinitely conducting spherical shell initially charged
to surface-density proportional to the sine of the latitude, for, of
course, it does not matter how thin or thick the shell may be when
infinitely conducting, so that it may be a solid sphere. (269) to (271)
show the establishment of the permanent state. Take off the im-
pressed force, and the oscillatory discharge follows. But the impressed
force keeping up the charge on the sphere need not be an external
cause, as supposed in the paper referred to. There seems no other
way of doing it than by having impressed force with vorticity fv on
the surface, but in other respects it is immaterial whether it is internal
or external, or superficial.
It may perhaps be questioned whether the sphere does reflect,
seeing that its surface is the seat of /. But we have only to shift
the seat of / to an outer spherical surface in the dielectric, to see at
once that the surface of the conductor is the place of continuous
reflexion of the wave incident upon it coming from the surface of /.
The reflexion is not, however, of the same simple character that occurs
when a plane wave strikes a plane boundary (k = oc ) flush, which
consists merely in sending back again every element of H unchanged,
but with its E reversed ; the curvature makes it much more complex.
When we bring the surface of / right up to the conducting sphere, we
make the reflexion instantaneous. At the front of the wave we have
* " On Electrical Oscillations and the Effects produced by the Motion of an
Electrified Sphere," Proc. Math. Soc., vol. xv., p. 210.
ON ELECTROMAGNETIC WAVES. PART IV. 435
by (269) and (270). This is exactly double what it would be were
the conductor replaced by dielectric of the same kind as outside, the
doubling being due to the instantaneous reflexion of the inward-going
wave by the conductor.
The other method of solution may also be applied, but is rather more
difficult. We have
H-™.-«>-«(l +1) (l -1) (l - 4-3) "/. ....... (272)
pvr \ grj \ qa/ \ (fa6/
Expand the last factor in descending powers of (qa)s, and integrate.
The result may be written
rr_a
-
where x = a~l(vt-r + a). Conversion to circular functions reproduces
(269).
Same Case with Finite Conductivity. Sinusoidal Solution.
4 2 A. It is to be expected that with finite conductivity, even with the
greatest at command, or ^ = (1600)~1, the solution will be considerably
altered, being controlled by what now happens in the conducting sphere.
To examine this point, consider only the value of H at the boundary.
We have, by (264),
ff.-*-yv-(^+*,)-yv ..................... (274)
Let / vary sinusoidally with the time, and observe the behaviour of </>x
and <f>2 as the frequency changes. The full development which I have
worked out is very complex. But it is sufficient to consider the case
in which k is big enough, in concert with the radius a and frequency
n/2-Tr, to make the disturbances in the sphere be practically confined to
a spherical shell whose depth is a small part of the radius. Let
s — (^Tr/Xj&jtta2) ; then our assumption requires e - * to be small. This
makes
............... <275>
and, if further, s itself be a large number, this reduces to
8^)* ............................ <276)
Adding on the other part of <£, similarly transformed by p2 = - n~, we
obtain
tf w*)2 ,/wn?f _ e* __ (J&f\, (277)
1 + (na/v)* + WV J L(*a/«) + (na/v)* WV J
where the terms containing ^ show the difference made by its not being
infinite. The real part is very materially affected. Thus, copper, let
^ = (1600)-!, ^ = 1, 27T7i=1600, a = 10, .-. s = 10.
These make s large enough. Now najv is very small, but, on the
other hand,
436 ELECTRICAL PAPERS.
so that the real part of <f> depends almost entirely on the sphere, whilst
the other part is little affected.
Now make n extremely great, say na/v = 1 ; else the same. Then
<£ = (| x 1010 + 44 x 104) - 1(| x 1010 - 44 x 104),
from which we see that the dissipation in space has become relatively
important. The ultimate form, at infinite frequency, is
t^HV + dijnl&rktfp+i)', (278)
so that we come to a third state, in which the conductor puts a stop to
all disturbance. This is, however, because it has been assumed not to
be a dielectric also, so that inertia ultimately controls matters. But if,
as is infinitely more probable, it is a dielectric, the case is quite changed.
We shall have
^ = (4^ + ^(4^ + ^)^, (279)
when the frequency is great enough, and this tends to fj^vv /^ being the
inductivity and ^ the speed in the conductor, whatever g and k may be,
provided they are finite. Thus, finally,
<J> = HlVl+nv (280)
represents the impedance, or ratio of fv to Ha, which are now in the
same phase.
At any distance outside we know the result by the dielectric-solution
for an outward wave. But there is only superficial disturbance in the
conducting sphere.
Resistance at the front of a Wave sent along a Wire.
43. In its entirety this question is one of considerable difficulty, for
two reasons, if not three. First, although we may, for practical pur-
poses, when we send a wave along a telegraph-circuit, regard it as a
plane wave, in the dielectric, on account of the great length of even the
short waves of telephony, and the great speed, causing the lateral
distribution (out from the circuit) of the electric and magnetic fields
to be, to a great distance, almost rigidly connected with the current in
the wires and the charges upon them ; yet this method of representation
must to some extent fail at the very front of the wave. Secondly, we
have the fact that the penetration of the electromagnetic field into the
wires is not instantaneous ; this becomes of importance at the front of
the wave, even in the case of a thin wire, on account of the great speed
with which it travels over the wire.* The resistance per unit length
must vary rapidly at the front, being much greater there than in the
body of the wave ; thus causing a throwing back, equivalent to electro-
static or "jar " retardation.
* The distance within which, reckoned from the front of the wave backward,
there is materially increased resistance, we may get a rough idea of by the distance
travelled by the wave in the time reckoned to bring the current-density at the
axis of the wire to, say, nine-tenths of the final value. It has all sorts of values.
It may be 1 or 1000 kilometres, according to the size of wire and material. At the
front, on the assumption of constant resistance, the attenuation is according to
6-Rt;zL^ ft being the resistance, and L the inductance of the circuit per unit length.
Hence the importance of the increased resistance in the present question.
ON ELECTROMAGNETIC WAVES. PART IV. 437
Now, according to the magnetic theory, the resistance must be
infinitely great at the front. Thus, alternate the current sufficiently
slowly, and the resistance is practically the steady resistance. Do it
more rapidly, and produce appreciable departure from uniformity of
distribution of current in the wire, and we increase the resistance to an
amount calculable by a rather complex formula. But do it very rapidly,
and cause the current to be practically confined to near the boundary,
and we have a simplified state of things in which the resistance varies
inversely as the area of the boundary, which may, in fact, be regarded as
plane. The resistance now increases as the square root of the frequency,
and must therefore, as said, be infinitely great at the front of a wave,
which is also clear from the fact that penetration is only just
commencing.
But for many reasons, some already mentioned, it is far more probable
that the wire is a dielectric. If, as all physicists believe, the ether
permeates all solids, it is certain that it is a dielectric. Now this
becomes of importance in the very case now in question, though of
scarcely any moment otherwise. Instead of running up infinitely, the
resistance per unit area of surface of a wire tends to the finite value
4737^, This is great, but far from infinity, so that the attenuation and
change of shape of wave at its front produced by the throwing back
cannot be so great as might otherwise be expected.
Thus, in general, at such a great frequency that conduction is nearly
superficial, we have, if /A, c, k, and g belong to the wire,
BIH*(4ty+jgftM+qfF*i (281)
if E is the tangential electric force and H the magnetic force, also
tangential, at the boundary of a wire. Now let R' and L' be the
resistance and inductance of the wire per unit of its length. We must
divide H by 4?r to get the corresponding current in the wire, as ordi-
narily reckoned. So ^irA~l times the right member of (281) is the
resistance-operator of unit length, if A is the surface per unit length ;
so, expanding (281), we get
R' or |*.3J-J(«ff^Y±!MgFF> (282)
where pv p2 are as before, in (208). Here n/2«r = frequency.
Disregarding <?, and therefore />2, we have
R' or Un = (^±TrnvA^{B±Bs>} ............. (283)
where
When c is zero, Rf and Lfn tend to equality, as shown by Lord Rayleigh.
But when c is finite, L'n tends to zero, and Rf to ±vpioA~\ as indeed we
can see from (281) at once, by the relative evanescence of k and g,
when finite.
But the frequency needed to bring about an approximation towards
the constant resistance is excessive ; in copper we require trillions per
second. This brings us to the third reason mentioned ; we have no
438 ELECTRICAL PAPERS.
knowledge of the properties of matter under such circumstances, or of
ether either. The net result is that although it is infinitely more
probable that the resistance should tend to constancy than to infinity,
yet the real value is quite speculative.* Similar remarks apply to
sudden discharges, as of lightning along a conductor. The above R', it
should be remarked, is real resistance, in spite of its ultimate form,
suggestive of impedance without resistance.! The present results are
corroborative of those in Part I., and, in fact, only amount to a special
application of the same.
Reflecting Barriers.
44. Let the medium be homogeneous between r = a0 and r = av where
there is a change of some kind, yet unstated. Let between them the
surface r = a be a sheet of vorticity of e of the first order. We already
know what will happen when fv is started, for a certain time, until in
fact the inward wave reaches the inner boundary, and, on the other
side, until the outward wave reaches the outward boundary ; though,
when the surface of /is not midway between the boundaries, the reflected
wave from the nearest barrier may reach into a portion of the region
beyond /, by the time the further barrier is reached by the primary
wave. The subsequent history depends upon the constitution of the
media beyond the boundaries, which can be summarized in two boundary
conditions. The expression for EjH is, in general,
by (120), extended, the extension being the introduction of y, which is
a differential operator of unstated form, depending upon the boundary
* The above was written before the publication of Professor Lodge's highly
interesting lectures before the Society of Arts. Some of the experiments
described in his second lecture are seemingly quite at variance with the magnetic
theory. I refer to the smaller impedance of a short circuit of fine iron wire than
of thick copper, as reckoned by the potential-difference at its beginning needed to
spark across the circuit between knobs. Should this be thoroughly verified, it has
occurred to me as a possible explanation that things may be sometimes so nicely
balanced that the occurrence of a discharge may be determined by the state of the
skin of the wire. A wire cannot be homogeneous right up to its boundary, with
then a perfectly abrupt transition to air ; and the electrical properties of the
transition-layer are unknown. In particular, the skin of an iron wire may be
nearly unmagnetisable, p. varying from 1 to its full value, in the transition-layer.
Consequently, in the above formula, resistance 4irfjt.v per unit surface, we may
have to take fj.= l in the extreme, in the case of an iron wire. But even then, the
explanation of Professor Lodge's results is capable of considerable elucidation.
Perhaps resonance will do it. [Professor Lodge has since examined the theory of
the apparently anomalous behaviour ; and concludes that it was due to the great
effective resistance of iron producing very rapid attenuation of the oscillations.]
*t* There is a tendency at present amongst some writers to greatly extend the
meaning of resistance in electromagnetism ; to make it signify cause/effect. This
seems a pity, owing to the meaning of resistance having been thoroughly specialized
in electromagnetism already, in strict relationship to "frictional" dissipation of
energy. What the popular meaning of " resistance" may be is beside the point.
I would suggest that what is now called the magnetic resistance be called the
magnetic reluctance ; and per unit volume, the reluctancy [or reluctivity].
ON ELECTROMAGNETIC WAVES. PART IV. 439
conditions. Let yQ and yl be the y's on the inner and outer side of the
surface of /. The differential equation of Hn, the magnetic force there,
is then
fv-{(EIH)^-(EIH)^)}Ht ................... (285)
as in §19. Applying (284) and the conjugate property (114) of the
functions u and w (since there is no change of medium at the surface of
f), this becomes
H _ 4vk + cp (ua - y0wa)(ua - y^)^ . ...(286)
</ y\ - 2/0
from which the differential equation of // at any point between a0 and
a is obtained by changing ua - y0wa to («/V)(w - yQw) ; and at any point
between a and al by changing ua-ylwa to (a/r)(u-yliv).
Unless, therefore, there are singularities causing failure, the deter-
minantal equation is
2/i-2/o = °> .............................. (287)
and the complete solution between a0 and ax due to / constant may be
written down at once. Thus, at a point outside the surface of/ we have
(out) H=n--fv = ^f. (288)
9. r 2/i-2/o
and therefore, if / starts when i = 0,
ZT- / Jav
~ +
p being now algebraic, given by (287) ; <£0 the steady <j>, from (288) ;
and y the common value of the (now) equal y's • which identity makes
(289) applicable on both sides of the surface of/.
Construction of the Operators yx and y0.
45. In order that yl and yQ should be determinable in such a way as
to render (286) true, the media beyond the boundaries must be made
up of any number of concentric shells, each being homogeneous, and
having special values of c, k, p, and g. For the spherical functions
would not be suitable otherwise, except during the passage of the
primary waves to the boundaries, or until they reached places where
the departure from the assumed constitution commenced. Assuming
the constitution in homogeneous spherical layers, there is no difficulty
in building up the forms of yQ and yl in a very simple and systematic
manner, wholly free from obscurities and redundancies. In any layer
the form of E/H is as in (284), containing one y. Now at the boundary
of two layers E is continuous, and also H (provided the physical con-
stants are not infinite), so E/H is continuous. Equating, therefore, the
expressions for EjH in two contiguous media expresses the y of one in
terms of the y of the other. Carrying out this process from the origin
up to the medium between a0 and a, expresses yQ in terms of the y of
the medium containing the origin ; this is zero, so that yQ is found as
an explicit function of the values of u, w, uf, w' at all the boundaries
440 ELECTRICAL PAPERS.
between the origin and «0. In a similar manner, since the y of the
outermost region, extending to infinity, is 1, we express yv belonging
to the region between a and av in terms of the values of u, etc., at all
the boundaries between a and oo . Each of these four functions will
occur twice for each boundary, having different values of the physical
constants with the same value of r. I mention this method of equation
of E/H operators because it is a far simpler process than what we are
led to if we use the vector and scalar potentials ; for then the force of
the flux has three component vectors — the impressed force, the slope of
the scalar potential, and the time-rate of decrease of the vector potential.
The work is then so complex that a most accomplished mathematician
may easily go wrong over the boundary conditions. These remarks
are not confined in application to spherical waves.
If an infinite value be given to a physical constant, special forms of
boundary condition arise, usually greatly simplified ; e.g., infinite con-
ductivity in one of the layers prevents electromagnetic disturbances
from penetrating into it from without ; so that they are reflected with-
out loss of energy.
Knowing yl and yQ in (288), we virtually possess the sinusoidal solu-
tion for forced vibrations, though the initial effects, which may or may
not subside or be dissipated, will require further investigation for their
determination ; also the solution in the form of an infinite series showing
the effect of suddenly starting / constant ; also the solution arising from
any initial distribution of E and H of the kind appropriate to the
functions, viz., such as may be produced by vorticity of e in spherical
layers, proportional to v (or vQ^ in general). But it is scarcely neces-
sary to say that these solutions in infinite series, of so very general a
character, are more ornamental than useful. On the other hand, the
immediate integration of the differential equations to show the develop-
ment of waves becomes excessively difficult, from the great complexity,
when there is a change of medium to produce reflexion.
Thin Metal Screens.
46. This case is sufficiently simple to be useful. Let there be at
r = a1a, thin metal sheet interposed between the inner and outer non-
conducting dielectrics, the latter extending to infinity. If made in-
finitely thin, E is continuous, and H discontinuous to an amount equal
to 47r times the conduction-current (tangential) in the sheet. Let Kl
be the conductance of the sheet (tangential) per unit area ; then
at r = av
Therefore by (284), when the dielectric is the same on both sides,
^u{ - w{ u{
where the functions uv etc., have the r = a1 values. From this,
4? (290)
ON ELECTROMAGNETIC WAVES. PART IV. 441
expresses yl for an outer thin conducting metal screen, to be used in
(286). If of no conductivity, it has no effect at all, passing disturbances
freely, and y^ = 1. At the other extreme we have infinite conductivity,
making yl = u'1/w{, with complete stoppage of outward -going waves,
and reflexion without absorption, destroying the tangential electric
disturbance.
When the screen, on the other hand, is within the surface of /, say
at r = «0, of conductance K0 per unit area, we shall find
2/o =
where «0, etc., have the r = aQ values. The difference of form from •yl
arises from the different nature of the r functions in the region includ-
ing the origin. As before, no conductivity gives transparency (y0 = 0),
and infinite conductivity total reflexion (;y0 = w£/w£). When the inner
screen is shifted up to the origin, we make y0 = 0, and so remove it.
Solution with Outer Screen ; Kx = oo ; f constant.
47. Let there be no inner screen, and let the outer be perfectly con-
ducting. As J. J. Thomson has considered these screens,* I will be
very brief, regarding them here only in relation to the sheet of/ and
to former solutions. The determinarital equation is
w( = 0, or tar\x = x(l-x2)~l, (292)
if x = ipajv. Roots nearly TT, 27r, STT, etc. ; except the first, which is
considerably less. The solution due to starting / constant, by (289), is
therefore
H= — 2 ~ a riltpt ) (293)
which, developed by pairing terms, leads to
^=S.s-;f,Sy2-^cos-^sin)?(cos--
which of course includes the effects of the infinite series of reflexions at
the barrier. By making ^ = oo , however, the result should be the same
as if the screen were non-existent, because an infinite time must elapse
before the first reflexion can begin, and we are concerned only with
finite intervals. The result is
H=^ . ?f ^^iLYcos - JL sin Wcos - -1 sinW (295)
nvr 7rJ0 ^ \ Xjr J l\ Xja J l
which must be the equivalent of the simple solution (142) of §21,
showing the origin and progress of the wave.
Now reduce it to a plane wave. We must make a infinite, and
r - a = z finite. Also take fv = e, constant. We then have
* In the paper before referred to.
442 ELECTRICAL PAPERS.
showing the H at s due to a plane sheet of vorticity of e situated at
z = Q. This is the equivalent of the solution (12) of §2, indicating the
continuous uniform emission of H=e/2fj-v both ways from the plane
z = 0. [But the sign of e is changed from that of § 2.]
Returning to (294), it is clear that from t = 0 to t = (al-a)lv, the
solution is the same as if there were no screen. Also if a is a very
small fraction of av the electromagnetic wave of depth 2a will, when it
strikes the screen, be reflected nearly as from a plane boundary. It
would therefore seem that this wave would run to-and-fro between
the origin and boundary unceasingly. This is to a great extent true ;
and therefore there is no truly permanent state (the electric flux,
namely, alone) ; but examination shows that the reflexion is not clean,
on account of the electrification of the boundary, so that there is a
spreading of the magnetic field all over the region within the screen.
Alternating f with Reflecting Barriers. Forced Vibrations.
48. Let the medium be nonconducting between the boundaries «0
and av Equation (288) then becomes
Hss va (u.-yoWa)(u-y1w), ,997)
/*w 2/i-2/o
giving H outside the surface of /. We see that y0 = 0 and un = 0 make
H=Q. That is, the forced vibrations are confined to the inside of the
surface of/ only, at the frequencies given by ua = 0, provided there is no
internal screen to disturb, but independently of the structure of the
external medium (since yl is undetermined so far), with possible
exceptions due to the vanishing of y^ simultaneously. But (297),
sinusoidally realized by p2 = - n2, does not represent the full final
solution, unless the nature of y0 and yl is such as to allow the initial
departure from this solution to be dissipated in space or killed by
resistance. Ignoring the free vibrations, let y0 = 0, and yl=u^/w/l,
meaning no internal, and an infinitely conducting external screen.
Then
(out) H=(valpvr)ua{uwyui-w}f, }
- wa}f.)
(in) H= (va/pw)u {
If wtf = 0, or in full,
(v/na^t&n^iajv) = 1 - (vjna-^f^
we obtain a simplification, viz.
tf(inorout)=-(va/j*ty)(tif0a or uaw)f; ............... (299)
and the corresponding tangential components of electric force are
^(inorout) = (va//xiT)(wX or uaw')(cp)~lf. ........... (300)
But if u{ = 0, the result is infinite. This condition indicates that the
frequency coincides with that of one of the free vibrations possible within
the sphere r = al without impressed force. But, considering that we may
confine our impressed force to as small a space as we please round the
origin, the infinite result is not easily understood, as regards its
development.
ON ELECTROMAGNETIC WAVES. PART V. 443
But the development of infinitely great magnetic force by a plane
sheet of/ is very easily followed in full detail, not merely with sinu-
soidal /, but with / constant. Considering the latter case, the emission
of H is continuous, as before described, from the surface of /. Now
place a plane infinitely-conducting barrier parallel to /, say on the left
side. We at once stop the disturbances going to the left and send them
back again, unchanged as regards H, reversed as regards E. The
H-disturbance on the left side of /therefore commences to be doubled
after the time a/v has elapsed, a being the distance of the reflecting
barrier from the plane of/, and on the right side after the interval 2a/v.
Next, put a second infinitely-conducting barrier on the right side of /.
It also doubles the H-disturbances as they arrive ; so that, by the
inclusion of the plane of/ between impermeable barriers, combined with
the continuous emission of H, the magnetic disturbance mounts up
infinitely, in a manner which may be graphically followed with ease.
Similarly with / alternating, at particular frequencies depending upon
the distances of the two barriers from /.
Returning to the spherical case, an infinitely-conducting internal
screen, with no external, produces
H _ KX - ^X)K - wa)fr /301v
/«?W-wJ)
We cannot produce infinite H in this case, because the absence of an
external barrier will not let it accumulate. Shifting the surface of/
right up to the screen, or conversely, simplifies matters greatly, reducing
to the case of § 42.
May 8, 1888.
PART V.
CYLINDRICAL ELECTROMAGNETIC WAVES.
49. In concluding this paper I propose to give some cases of
cylindrical waves. They are selected with a view to the avoidance
of mere mathematical developments and unintelligible solutions, which
may be multiplied to any extent ; and for the illustration of peculiarities
of a striking character. The case of vibratory impressed E.M.F. in a
thin tube is very rich in this respect, as will be seen later. At present
I may remark that the results of this paper have little application in
telegraphy or telephony, when we are only concerned with long waves.
Short waves are, or may be, now in question, demanding a somewhat
different treatment.* We do, however, have very short waves in the
* The waves here to be considered are essentially of the same nature as those
considered by J. J. Thomson, "On Electrical Oscillations in a Cylindrical Con-
ductor," Pruc. Math. Soc. vol. xvn., and in Parts I. and II. of my paper, " On the
Self-induction of Wires," Phil. Mar/., August and September, 1886 ; viz. a mixture
of the plane and cylindrical. But the peculiarities of the telegraphic problem
make it practically a case of plane waves as regards the dielectric, and cylindrical
in the wires. The " resonance " effects described in my just-mentioned paper arise
from the to-aud-fro reflexion of the plane waves in the dielectric, moving parallel
444 ELECTRICAL PAPERS.
discharge of condensers, and in vacuum-tube experiments, so that we
are not so wholly removed from practice as at first appears. But
independently of considerations of practical realization, I am strongly
of opinion that the study of very unrealizable problems may be of use
in forwarding the supply of one of the pressing wants of the present
time or near future, a practicable ether — mechanically, electromagneti-
cally, and perhaps also gravitationally comprehensive.
Mathematical Preliminary.
50. On account of some peculiarities in Bessel's functions, which
require us to change the form of our equations to suit circumstances, it
is desirable to exhibit separately the purely mathematical part. This
will also considerably shorten and clarify what follows it.
Let the axis of z be the axis of symmetry, and let r be the distance of
any point from it. Either the lines of E, electric force, or of H, magnetic
force, may be circular, centred on the axis. For definiteness, choose H
here. Then the lines of E are either longitudinal, or parallel to the
axis ; or there is, in addition, a radial component of E, parallel to r.
Thus the tensor H of H, and the two components of E, say E longi-
tudinal and F radial, fully specify the field. Their connexions are these
special forms of equations (2) and (3) : —
(302)
where (and always later) p stands for d/dt. This is in space where neither
the impressed electric nor the impressed magnetic force has curl, it being
understood that E and H are the forces of the fluxes, so as to include
impressed. From (302) we obtain
1 d dE
r*r*7*-'
d 1 d rr^&H
TrrdrrH+V
the characteristics of E and H. Let now
<f= -s* = (47rk + ci))w-d-2/dzi; ................. (304)
then the first of (303) becomes the equation of J0(sr) and its companion,
whilst the second becomes that of J^sr) and its companion. Thus E
is associated with /0 and H with Jv when H is circular ; conversely
when E is circular.
to the wire. This is also practically true in Prof. Lodge's recent experiments,
discharging a Leyden jar into a miniature telegraph -circuit. On the other hand,
most of such effects in the present paper depend upon the cylindrical waves in the
dielectric ; and in order to allow the dielectric fair play for their development, the
contaminating influence of diffusion is done away with by using tubes only, when
there are conductors. In Hertz's recent experiments the waves are of a very
mixed character indeed.
ON ELECTROMAGNETIC WAVES. PART V. 445
We have first Fourier's cylinder function
/0r = /o(s,) = l_(^! + W_.... .................. (305)
and its companion,"* which call 6r0, is
G0r = GQ(sr) = (2/7r)[/0r (log sr -
r n ^i\^n ^i^i\ ......... (306)
where -
The coefficient 2/?r is introduced to simplify the solutions. The func-
tion J^sr) or /lr is the negative of the first derivative of J^ with respect
to sr. Let G^sr) or 6rlr be the function similarly derived from 6r0r. The
conjugate property, to be repeatedly used, is
(/00i-^0o)r= -2/»*r. ........................ (307)
We have also Stokes's formula for J^., useful when sr is real and not
too small, viz.
J^ = (JLWj2(co(i + sin)sr + Si(sin - cos)sA ......... (308)
where R and Si are functions of sr to be presently given. The corre-
sponding formula for G& is obtained by changing cos to sin and sin
to - cos in (308).
Besides these two sets of solutions, we sometimes require to use a
third set. A pair of solutions of the /0 equation is
1 1232 123252 .......... (309)
where
The last also defines the R and Si in (308). R is real whether <? be +
* [In investigations where we are concerned with the complementary function
to J0(sr) between boundaries, the constant /3 (which I now introduce) may be
omitted ab initio, being superfluous. If retained, it will go out later, by the /3's of
one boundary cancelling those of the other. This is true in the resultant differ-
ential equations as well as in solutions. For this reason /3 has been omitted in the
previous investigations in this work. But in the following investigations we are
often concerned with the G0 function when the outer boundary is removed to
infinity, that is, when there is no outer boundary. We should then standardize O0
so as to vanish at infinity. This requirement is satisfied by the form
G0(sr) = (7rsr)~}( #(sin - cos)«r - £t'(cos + sin).sr) , ............... (308a)
derived from (308) in the manner described above. But the form (306) requires p
to be retained, for evanescence at infinity. Its value is
/3 = log2-7 = log2- -5772= -11593, ........................ (3086)
where 7 is Euler's constant
(308c)
An evaluation of this £ will be found in Lord Rayleigh's Sound, vol. n. The
process is not free from difficulty, and a different estimate has been given, but I
have corroborated the above estimate by two other independent methods. Note
that (306) with /3 and (308a) are equivalent.]
446 ELECTRICAL PAPERS.
or - , whilst S is unreal when cf is - , or Si is then real, s2 being + .
[Take q = si in (309), then we have
12325272 _ g._ I 123252 1232527292 _
(4(8sr)4 8sr [3(8sr)8+ [5(8sr)5
to be used in (308).]
When qr is a + numeric, the solution U is meaningless, as its value
is infinity. But in our investigations q2 is a differential operator, so
that the objection to U on that score is groundless. We shall use it to
calculate the shape of an inward progressing wave, whilst /Fgoes to
find an outward wave. The results are fully convergent within certain
limits of r and t. From this alone we see that a comprehensive theory
of ordinary linear differential equations [by themselves] is sometimes
impossible. They must be generalized into partial differential equations
before they can be understood.*
The conjugate property of U and W is
UW-U'W= -20/r, ....................... (310)
if the ' = d/dr. An important transformation sometimes required is
Jor-iG^ZiJTVirq)-*; ...................... (311)
or, which means the same,
* [We may, however, use U to calculate the numerical value of J0(sri) or I0(qr)
when qr is not too small, namely, by wholly rejecting the infinite divergent part
of the series. Thus
expresses the equivalence, the convergent series being suitable for small, and the
divergent for large values of the argument. But the convergent series admits of
exact calculation, whilst the divergent series does not, though by stopping at the
smallest term we obtain the nearest approach to the true value of I0(qr). This
contrasts with the behaviour of U as a complex differentiator, when the whole
series is operative.
It is difficult to imagine a direct transformation from the convergent to the
divergent series by ordinary mathematics, for, owing to the terms in the latter
being all positive, it makes nonsense. The following transformation is the only
one I have been able to make up. Let t be the variable, and p the differentiator
d/dt. Then, q being a constant,
i+^-'*- ............ (3096)
by applying p~n = tn/\n, understanding here and later that when no operand is
expressed, the operand is 1, that is, zero before and 1 after 2 = 0. Therefore, by
the binomial theorem,
.(309c)
Now we also have eit = JP—, or p = (p-q)eit (309(2)
p-q
Substituting this for the numerator in the last form we get
'*(& = . P~*J«=(^9y«'' ...(309e)
ON ELECTROMAGNETIC WAVES. PART V. 447
When we have obtained the differential equation in any problem, the
assumption s2 = a constant* converts it into the solution due to impressed
force sinusoidal with respect to i and z ; this requires d^/dz2 = - in2, and
d'2/dfi = - n2, where m and n are positive constants, being 2?r times the
wave shortness along z and 2?r times the frequency of vibration respec-
tively.
After (309) we became less exclusively mathematical. To go further
in this direction, and come to electromagnetic waves, observe that we
need not concern ourselves at all with F the radial component, in seek-
ing for the proper differential equation connected with a surface of curl
of impressed force ; it is E and H only that we need consider, as the
boundary conditions concern them. The second of (302) derives F
from H.
When H is circular, the operator EjH is given by
where y is undetermined. When E is circular, the operator E/H is
given by
:?=_L_. J*-y^r (314)
H '
The use of these operators greatly facilitates and systematizes investi-
gation. The meaning is that (313) or (314) is the characteristic equa-
tion connecting E and H.
Longitudinal Impressed E.M.F. in a Thin Conducting Tube.
51. Let an infinitely long thin conducting tube of radius a have con-
ductance K per unit of its surface to longitudinal current, and be
bounded by a dielectric on both sides. Strictly speaking, the tube
should be infinitely thin, in order to obtain instantaneous magnetic
penetration, and yet be of finite conductance without possessing infinite
Now shift the new operand e^ to the left (or make 1 the operand again) and we
change p to p + q, giving
So far is equivalent to the work on p. 427, vol. II. But now use the result
pl = (irt)-l, make it the operand, and expand the radical denominator in rising
powers of p. Then (309/) gives
Lastly, perform the differentiations, and we get
which is the required result.]
*[When k = Q, then p-ni and d2/dz2 = - wi2 makes s2 constant, either + or
In a conducting dielectric s2 is complex. We have p = ni, q = si, in the rest.]
448 ELECTRICAL PAPERS.
conductivity, because that would produce opacity. In this tube let
impressed electric force, of intensity e per unit length, act longitudinally,
e being any function of t and z. We have to connect e with E and H
internally and externally.
The magnetic force being circular, (313) is the resistance-operator
required. Within the tube take y — 0 if the axis is to be included ; else
find y by some internal boundary-condition. Outside the tube take
y - i when the medium is homogeneous and boundless, because that is
the only way to prevent waves from coming from infinity ; else find y
by some outer boundary-condition. There is no difficulty in forming
the y to suit any number of coaxial cylinders possessing different
electrical constants, by the continuity of E and H at each boundary,
which equalizes the E/H's of its two sides, and so expresses the y on one
side in terms of that on the other ; but this is useless for our purpose.
For the present take y = 0 inside, and leave it unstated outside.
At r = a, Ea has the same value on both sides of the tube, on account
of its thinness. In the substance of the tube e + Ea is the force of the
flux. On the other hand H is discontinuous at the tube, thus
. ....... (315)
In this use (313), and the conjugate property (307), and we at once
obtain
' ..... <S16>
from which all the rest follows. Merely remarking concerning k that
the realization of (316) when k is finite requires the splitting up of the
Bessel functions into real and imaginary parts, that the results are com-
plex, and that there are no striking peculiarities readily deducible ; let
us take k = 0 at once, and keep to nonconducting dielectrics. Then,
from (316), follow the equations of E and JT, in and out ; thus
or (out) = ^(^-yg») or J^-yG^ ...... (317)
TT or _cp
-"(in) OI (out) -- • — - i -- : -
s same denominator
which we can now examine in detail.
Vanishing of External Field. J0a = 0.
52. The very first thing to be observed is that J0a = 0 makes E and H
and therefore also F vanish outside the tube, and that this property is
independent of y, or of the nature of the external medium. We require
the impressed force to be sinusoidal or simply periodic with respect to
z and t, thus
e = e0 sin (mz + a) sin (nt + /?), .................... (319)
so that, ultimately, s2 = n2/v2 - m* ; ........................... ,..(320)
ON ELECTROMAGNETIC WAVES. PART V. 449
and any one of the values of s given by /0(? = 0 causes the evanescence
of the external field. The solutions just given reduce to
(in) E^(sjcn)^irK(JJiJla)ie,
(321)
which are fully realized, because i signifies p/n, or involves merely a
time-differentiation performed on the e of (319).
The electrification is solely upon the inner surface of the tube. In
its substance H falls from - 4irKe inside to zero outside, and Ea being
zero, the current in the tube is Ke per unit surface.
The independence of y raises suspicion at first that (321) may not
represent the state which is tended to after e is started. But since the
resistance of the tube itself is sufficient to cause initial irregularities to
subside to zero, even were there a perfectly reflecting barrier outside the
tube to prevent dissipation of these irregularities in space, there seems
no reason to doubt that (321) do represent the state asymptotically
tended to. Changing the form of y will only change the manner of the
settling down. We may commence to change the nature of the medium
immediately at the outer boundary of the tube. We cannot, however,
have those abrupt assumptions of the steady or simply periodic state
which characterize spherical waves, owing to the geometrical conditions
of a cylinder.
Case of Two Coaxial Tubes.
53. If there be a conducting tube anywhere outside the first tube,
there is no current in it, except initially. From this we may conclude
that if we transfer the impressed force to the outer tube, there will be no
current in the inner. Thus, let there be an outer tube at r = #, of con-
ductance K± per unit area, containing the impressed force er We have
....................... (322)
where 73 and Y2 are the H/E operators just outside and inside the
tube, whilst Ex is the E at x, on either side of the tube, resulting
from er We have
y _cp /to-ftflk Y _cpJlx-yGlx
~~ ~
where yl is settled by some external and y by some internal condition.
In the present case the inner tube at r = «, if it contains no impressed
force, produces the condition
Yt-Yi = l*K at r = a, .................. (324)
where Yl is the internal H/E operator. Or
• • ^7rJ\.t/(\ft /OOK\
giving ^ = -— ~ (325)
H.E.P. — VOL. II.
450 ELECTRICAL PAPERS.
Now, using (323) in (322) brings it to
E oz-teox-ioxi-i ...(326)
2(yi - y)— - 4- W* - y0«,)(/«, - W
S TTSiC
in which y is given by (325), and from (326) the whole state due to e1
follows, as modified by the inner tube.
Now J0a = 0 makes y = 0j this reduces (326) to
(327)
and, by comparison with (317), we see that it is now the same as if the
inner tube were non-existent. That is, when it is situated at a nodal
surface of E due to impressed force in the outer tube, and there is
therefore no current in it (except transversely, to which the dissipation
of energy is infinitely small), its presence does nothing, or it is perfectly
transparent.
It is clearly unnecessary that the external impressed force should be
in a tube. Let it only be in tubular layers, without specification of
actual distribution or of the nature of the medium, except that it is
in layers so that c, k, and p are functions of r only ; then if the axial
portion be nonconducting dielectric, the J0r function specifies E and
allows there to be nodal surfaces, for instance J0a = Q, where a con-
ducting tube may be placed without disturbing the field. Admitting
this property gb initio, we can conversely conclude that e in the
tube at r = a will, when /Oa = 0, make every external cylindrical
surface a nodal surface, and therefore produce no external disturb-
ance at all.
54. Now go back to § 51, equations (317), (318). There are no
external nodal surfaces of E in general (exception later). We cannot
therefore find a place to put a tube so as not to disturb the existing
field due to e in the tube at r = ft. But we may now make use of a
more general property. To illustrate simply, consider first the mag-
netic theory of induction between linear circuits. Let there be any
number of circuits, all containing impressed forces, producing a deter-
minate varying electromagnetic field. In this field put an additional
circuit of infinite resistance. The E.M.F. in it, due to the other circuits,
will cause no current in it of course, so that no change in the field
takes place. Now, lastly, close the circuit or make its resistance finite,
and simultaneously put in it impressed force which is at every moment
the negative of the E.M.F. due to the other circuits. Since no current
is produced there will still be no change, or everything will go on as
if the additional circuit were non-existent.
Applying this to our tubes, we may easily verify by the previous
equations that when there are two coaxial tubes, both containing
impressed forces, we can reduce the resultant electromagnetic field
everywhere to that due to the impressed force in one tube, provided
we suitably choose the impressed force in the second to be the negative
ON ELECTROMAGNETIC WAVES. PART V. 451
of the electric force of field due to e in the first tube when the second
is non-existent. That is, we virtually abolish the conductance of the
second tube and make it perfectly transparent.
Perfectly Reflecting Barrier. Its Effects. Vanishing of Conduction
Current.
55. To produce nodal surfaces of E outside the tube containing the
vibrating impressed force, we require an external barrier, which shall
prevent the passage of energy or its absorption, by wholly reflecting all
disturbances which reach it. Thus, let there be a perfect conductor at
r = x. This makes E = 0 there. This requires that the y in (317),
(318) shall have the value Jox/'Gr0n whereas without any bound to the
dielectric it would be i. We can now choose m and n so as to make
JQx = 0. This reduces those equations to
E=-»rt
(in and out)
*—"&•
,(328)
This solution is now the same inside and outside the tube containing
the impressed force, and there is no current in the tube, that is, no
longitudinal current.
To understand this case, take away the impressed force and the tube.
Then (328) represents a conservative system in stationary vibration.
Now, by the preceding, we may introduce the tube at a nodal surface
of E without disturbing matters, provided there be no impressed force
in the tube. But if we introduce the tube anywhere else, where E is
not zero, we require, by the preceding, an impressed force which is at
every moment the negative of the undisturbed force of the field, in
order that no change shall occur. Now this is precisely what the
solution (328) represents, e in the tube being cancelled by the force of
the field, so that there is no conduction-current. The remarkable
thing is that it is the impressed force in the tube itself that sets up the
vibrating field, and gradually ceases to work, so that in the end it and
the tube may be removed without altering the field. That a perfect
conductor as reflector is required is a detail of no moment in its
theoretical aspect.
Shifting the tube, with a finite impressed force in it, towards a nodal
surface of E, sends up the amplitude of the vibrations to any extent.
K = 0 and K = <x> .
56. If the tube have no conductance, e produces no effect. This is
because the two surfaces of curl of e are infinitely close together, and
therefore cancel, not having any conductance between them to produce
a discontinuity in the magnetic force.
But if the tube have infinite conductance, we produce complete
mutual independence of the internal and external fields, except in the
452 ELECTRICAL PAPERS.
quite unessential particular that the two surfaces of curie are of
opposite kind and time together. Equations (317), (318) reduce to
(in) E=-^e, F=+lJ>r^ H= -l^cpe (329)
i/Oa S J0a dZ S J0a
(out)
J0a - yG^ dz
(330)
Observe that (329) is the same as (328). The external solution (330)
requires y to be stated. When y = i, for a boundless dielectric, the
realization is immediate.
s = 0. Vanishing of E all over, and of F and H also internally.
57. This is a singularity of quite a different kind. When n = mv, we
make ,s- = 0. Of course there is just one solution with a given wave-
length along z; a great frequency with small wave-length, and con-
versely.
E vanishes all over, that is, both inside and outside the tube contain-
ing e, provided s/y is zero. The internal J^and therefore also Evanish.
Thus within the tube is no disturbance, and outside, (317) (318)
reduce to
(out) H=4irKe, F~--4arK ...(331)
r en r dz
Observe that H and F do not fluctuate or alternate along r, but that
H has the same distribution (out from the tube) as if e were steady and
did not vary along z.
A special case is in = 0. Then also n = 0, or e is steady and indepen-
dent of z. F vanishes, and the first of (331) expresses the steady state.
Without this restriction, the current in the tube is Ke per unit
surface, owing to the vanishing of the opposing longitudinal E of the
field. This property was, by inadvertence, attributed by me in a
former paper * to a wire instead of a tube. The wave-length must be
great in order to render it applicable to a wire, because instantaneous
penetration is assumed.
I mentioned that s/y must vanish. This occurs when y — it or the
external dielectric is boundless. But it also occurs when E = 0 at r = x,
produced by a perfectly conductive screen. This is plainly allowable
because it does not interfere with the E =-0 all-over property. What
the screen does is simply to terminate the field abruptly. Of course it
is electrified.
s = 0 and Hx = 0.
58. But with other boundary conditions, we do not have the solutions
(331). Thus, let HX = Q, instead of Ex = 0. This makes y = Jlx/Glx in
* "On Resistance and Conductance Operators," Phil. Mag., Dec. 1887, p. 492,
Ex. . [vol. n. t p. 366].
ON ELECTROMAGNETIC WAVES. PART V. 453
(317), (318). There are at least two ways (theoretical) of producing
this boundary condition. First, there may be at r = v a screen made of
a perfect magnetic conductor (g = ao). Or, secondly, the whole medium
beyond r = x may be infinitely elastive and resistive (c = 0, k = 0) to an
infinite distance.
Now choose 5 = 0 in addition, and reduce (317), (318). The results
are
Ess _e_ F= 1 dH
l+frfyf&Za' cpdz*
.
(in)or<out> *—
which are at once realized by removing p from the denominator to the
numerator.
Although E is not now zero, it is independent of ?', only varying
with t and z.
When s2 is negative, or n < m/v, the solutions (317), (318) require
transforming in part because some of the Bessel functions are unreal.
Use (312), because (^ is now real. There are no alternations in E or H
along r. They only commence when n > mv.
Separate A dims of the Two Surfaces of curl e.
59. Since all the fluxes depend solely upon the curl of e, and not
upon its distribution, and there are two surfaces of curl e in the tube
problem, their actions, which are independent, may be separately
calculated. The inner surface may arise from e in the - direction in
the inner dielectric, or by the same in the + direction in the tube and
beyond it. The outer may be due to e in the - direction beyond the
tube, or in the + direction in the tube and inner dielectric.
We shall easily find that the inner surface of curl of e, say of surface-
density /15 produces
(333)
(OUt) E= "la^Or-^Or/ /
same denominator
from which H may be got by the E/H operator.
The external sheet, say /2, produces
(in) E = ^Or^la ~ y®l*)f
(334)
(out)
where the unwritten denominators are as in the first of (333). Observe
that when Jla = 0, /x produces no external field (in tube or beyond it).
It is then only /2 that operates in the tube and beyond.
454 ELECTRICAL PAPERS.
Now take f2 = e and /j = - e in (333) and (334) and add the
results. We then obtain (317), (318); and it is now J0a = 0 that
makes the external field vanish, instead of Jla = 0 when /x alone is
operative.
Having treated this problem of a tube in some detail, the other
examples may be very briefly considered, although they too admit of
numerous singularities.
Circular Impressed Force in Conducting-Tube.
60. The tube being as before, let the impressed force e (per unit
length) act circularly in it instead of longitudinally, and let e be a
function of t only, so that we have an inner and an outer cylindrical
surface of longitudinally directed curl of e. H is evidently longitudinal
and E circular, so that we now require to use the (314) operator.
At the tube Ea is continuous, this being the tensor of the force of the
flux on either side, and H is discontinuous thus,
............ (335)
Substituting the (314) operator, with y = 0 inside, and y undetermined
outside, and using the conjugate property (307), we obtain
Hm or ,out,= -j(4.-yguV» °r W»-»\ ...... (336)
or l = ,-» - or
_.
same denominator
When e is simply periodic, Jla = 0 makes the external E and H vanish
independent of the nature of y. The complete solution is then
(338)
The conduction-current in the tube is Ke per unit area of surface.
To make the conduction-current vanish by balancing the impressed
force against the electric force of the field that it sets up, put an
infinitely-conducting screen at r-x outside the tube, and choose the
frequency to make Jlx = 0, since we now have y = J-^JG^ We shall
then have the same solution inside and outside, viz.
H= --^ie, E=-J*e-,. ...(339)
so that at the tube itself, E = - e. This case may be interpreted as in
§ 55, the tube being at a nodal surface of E.
A special case of (338) is when n = 0, or e is steady. Then there is
merely the longitudinal H inside the tube, given by H=4=irKe.
ON ELECTROMAGNETIC WAVES. PART V. 455
Cylinder of Longitudinal cwrl of e in a Dielectric.
61. In a nonconductive dielectric let the impressed electric force be
such that its curl is confined to a cylinder of radius a, in which it is
uniformly distributed, and is longitudinal. Let / be the tensor of curl e,
and let it be a function of t only. Since E is circular and H longi-
tudinal, we have (314) as operator, in which k is to be zero. This is
outside the cylinder. Inside, on the other hand, on account of the
existence of curie, the equation corresponding to (314) is
J ........................... (340)
At the boundary r = a both E and H are continuous ; so, by taking
r = a in (340) and in the corresponding (314) with k = 0, and eliminating
Ea or Ha between them, we obtain the equation of the other. We
obtain
(out) = ulr-lr, .. ..(341)
--
in which y, as usual, is to be fixed by an external boundary condition,
or, if the medium be boundless, y = i.
We see at once that Jla = 0, with / simply-periodic, makes the exter-
nal fluxes vanish. We should not now say that it makes the external
field vanish, though the statement is true as regards H, because the
electric force of the field does not vanish ; it cancels the impressed
force, so that there is no flux. This property is apparently independent
of y. But, since there is no resistance concerned, except such as may
be expressed in y, it is clear that (341), sinusoidally realized, cannot
represent the state which is tended to after starting/, unless there be
either no barrier, so that initial disturbances can escape, or else there
be resistance somewhere, to be embodied in y, so that they can be
absorbed, though only through an infinite series of passages between
the boundary and the axis of the initial wave and its consequences.
Thus, with a conservative barrier producing E = 0 at r~x, and
y -Jix/@ixi there is no escape for the initial effects, which remain in the
form of free vibrations, whilst only the forced vibrations are got by
taking s'2= + constant in (341). The other part of the solution must
be separately calculated. If t/liB = 0, E and H run up infinitely. If
Jla = 0 also, the result is ambiguous.
With no barrier at all, or y = i,vre have
(out) / E= H2a)-VU0ir + ^)/»l ...(342)
\ JET=(2^)-i/la(/0r-^0r)/0,J
which are fully realized. Here /0=/7ra2, which may be called the
strength of the filament. We may most simply take the impressed
force to be circular, its intensity varying as r within, and inversely as r
outside the cylinder. Then/= 2eja, if ea is the intensity at r = a.
When nr/v is large, (342) becomes, by (308), writing /0 sin nt for/0,
(out) E = f*vH=^(sm(nt-™ + ?\ ........... (343)
4# \irnrj \ v 4/
456 ELECTRICAL PAPERS
approximately. 2?rr should be a large multiple, and 2ira a small frac-
tion of the wave-length along r.
Filament of curl e. Calculation of Wave.
62. In the last, let /0 be constant, whilst a is made infinitely small.
It is then a mere filament of curl of e at the axis that is in operation.
We now have, bythe second of (342), with Jla = ^na/v,
|-(/fr-iffJ/0 = If= -(<p/4)(W» + fiW/o. ............ (344>
which may be regarded as the simply-periodic solution or- as the
differential equation of H. In the latter case, put in terms of W by
(311), then
^=(2^)-%/27r)-i/F/0; ......................... (345)
or, expanding by (309),
........ (346)
in which /0 may be any function of the time. Let it be zero before, and
constant after t = 0. Then, first,
Next effect the integrations of this function indicated by the inverse
powers of q or p/v, thus
2r)]- .......... (348)
Lastly, operating on this by t~9r turns vt to vt — r, and brings (346) to
H=(f0/2irpv)(W -**)-*, .................... (349)
which is ridiculously simple. Let Z be the time-integral of H, then
?-1)*] .................. (350)
from which we may derive E ; thus
curl Z = cE, or E=-ldZ=- ___ *#* (351)
c dr 27rr^2-r2*
The other vector-potential A, such that E= -^>A, is obviously
...................... (352)
All these formulae of course only commence when vt reaches r. The
infinite values of E and H at the wave-front arise from the infinite con-
centration of the curl of e at the axis.
Notice that E = .............................. (353)
ON ELECTROMAGNETIC WAVES. PART VI. 457
everywhere. It follows from this connexion between E and H (or from
their full expressions) that
= ce* = c(/0/27ir)2 ; .................. (354)
where e denotes the intensity of impressed force at distance r, when it
is of the simplest type, above described. That is, the excess of the
electric over the magnetic energy at any point is independent of the
time. Both decrease at an equal rate ; the magnetic energy to zero,
the electric energy to that of the final steady displacement ce/4?r.
6 2 A. The above E and H solutions are fundamental, because all
electromagnetic disturbances due to impressed force depend solely upon,
and come from, the lines of curl of the impressed force. From them, by-
integration, we can find the disturbances due to any collection of recti-
linear filaments of f. Thus, to find the H due to a plane sheet of parallel
uniformly distributed filaments, of surface-density /, we have, by (349),
at distance a from the plane, on either side,
H- f
J
y
where the limits are ± (vW - a2)*. Therefore
after the time t = a/v ; before then, H is zero. [Compare with § 2,
equation (12).]
62 B. Similarly, a cylindrical sheet of longitudinal f produces
H_ fa f dO .
where b is the distance of the point where H is reckoned from the
element adO of the circular section of the sheet, a being its radius. The
limits have to be so chosen as to include all elements of / which have
had time to produce any effect at the point in question. When the
point is external and vt exceeds a + r the limits are complete, viz. to
include the whole circle. The result is then, at distance r from the axis
of the cylinder,
n fal^v f^l-3 x 1-3.5.7 .r2 4.3 1.3.6.7.9.11 a* 6.5.4 1 ,»„.
r= ' ''' " " ' (
where x = (2ar)2(i^2 - a2 - r2)~2.
This formula begins to operate when x= 1, or vt = a + r. As time goes
on, x falls to zero, leaving only the first term.
PART VI.
Cylindrical Surface of Circular curl e in a Dielectric.
63. Let the curl of the impressed electric force be wholly situated on
the surface of a cylinder, of radius a, in a nonconducting dielectric. The
458 ELECTRICAL PAPERS.
impressed force e to correspond may then be most conveniently imagined
to be either longitudinal, within or without the cylinder, uniformly dis-
tributed in either case (though oppositely directed), and the density of
curie will be e; or, the impressed force may be transferred to the sur-
face of the cylinder, by making e radial, but confined to an infinitely
thin layer. The measure of the surface-density of curl e will now be
/==£M-£(OTItl ...................... -(356)
where e is the total impressed force (its line-integral through the layer).
The second form of this equation shows the effect produced on the
electric force E of the flux, outside and inside the surface. This E is,
as it happens, also the force of the field ; but in the other case, when e
is uniformly distributed within the cylinder, producing f=e, we have
the same discontinuity produced by /.
H being circular, we use the operator (313). Applying it to (356),
we obtain
n. ................... (357)
from which, by the conjugate property (307), and the operator (313),
we derive
or J^-yGf, (358)
or Jla(Jir-yGlr)f, (359)
in which / is a function of t, and it may be also of z. If so, then we
have the radial component F of electric force given by
Fw or (out) = - /i,W. - yG^ or /la(/lr - *A,) • (360)
From these, by the use of Fourier's theorem, we can build up the
complete solutions for any distribution of / with respect to z; for
instance, the case of a single circular line of curl e.
Jja = 0. Vanishing of External Field.
64. Let/ be simply-periodic with respect to t and z ; then Jla — 0, or
v2-m2}=0, ........................ (361)
produces evanescence of E and H outside the cylinder. The indepen-
dence of this property of y really requires an unbounded external
medium, or else boundary-resistance, to let the initial effects escape or
be dissipated, because no resistance appears in our equations except in
y. The case s = 0 or n = mv is to be excepted from (361) ; it is treated
later.
ON ELECTROMAGNETIC WAVES. PART VI. 459
y = i. Unbounded Medium.
65. When n/v > m, s is real, and our equations give at once the fully
realized solutions in the case of no boundary, by taking y = i,
,i or (out) =
or =
ir(Jia - iGla) or Jla(Jlr - iGlr)jf,
J^(Gla + iJla) or J^G^ + i/») V,
n, or (out) = 4™ (jlr(Gla + i/la) or Jla(Glr + i/lr))
(362)
in which i means pjn.
The instantaneous outward transfer of energy per unit length of
cylinder is (by Poynting's formula)
and the mean value with respect to the time comes to
....................... (363)
if /0 is the maximum value of /, [thus, f=f0 cos mz sin nt]. This may of
course be again averaged to get rid of the cosine.
s = 0. Vanishing of External E.
66. When n = mv, we make s = 0, and then (362) reduce to the singular
solution
a f v n P i a2 df "
— ' Cp/, £(out) = 0, ^ (out) = - i - - • .
Observe that the internal longitudinal displacement is produced entirely
by the impressed force (if it be internal), though there is radial displace-
ment also, on account of the divergence of e (if internal). Outside the
cylinder, the displacement is entirely perpendicular to it.
H and F do not alternate along r. This is also true when s2 is nega-
tive, or n lies between 0 and mv. Then, q2 being positive, we have
(365)
as the rational form of the equation of the external E when the fre-
quency is too low to produce fluctuations along r.
The system (364) may be obtained directly from (358) to (360) on
the assumption that s/y is zero when s is zero. But (364) appears to
require an unbounded medium. Even in the case of the boundary
condition E = 0 at r = z, which harmonizes with the vanishing ' of E
externally in (364), there will be the undissipated initial effects con-
tinuing.
If, on the other hand, HX=Q, making y = Jlx/Glx) we shall not only
have the undissipated initial effects, but a different form of solution for
460 ELECTRICAL PAPERS.
the forced vibrations. Thus, using this expression for ?/, and also s = 0,
in (358) to (360), we obtain
(366)
representing the forced vibrations.
Effect of suddenly Starting a Filament of e.
67. The vibratory effects due to a vibrating filament we find by taking
a infinitely small in (362), that is Jla = ^sa. To find the wave produced
by suddenly starting such a filament, transform equations (358), (359)
by means of (311). We get [e being intensity of longitudinal e]
(367)
where W is given by (309) ; the accent means differentiation to r, and
the suffix a means the value at r - a.
In these, let e0 = ira2e, which we may call the strength of the filament,
and let a be infinitely small. We then obtain
Now if e0 is a function of t only, it is clear that there is no scalar electric
potential involved. We may therefore advantageously employ (and for
a reason to be presently seen) the vector-potential A, such that
E=-pA, or A=-p~lE; and /x#= -^. (369)
The equation of A is obviously, by the first of (369) applied to second
of (368),
A = \(pl%mP)*W% (370)
Comparing this equation with that of H in (345) (problem of a filament
of curl of e), we see that /0 there becomes e0 here, and pH there becomes
A here. The solution of (370) may therefore be got at once from the
solution of (345), viz. (349). Thus
A = % — ; (371)
from which, by (369),
E = W* ?> #=-- — W _, (372)
the complete solution. It will be seen that
(373)
ON ELECTROMAGNETIC WAVES. PART VI. 461
whilst the curious relation (353) in the problem, of a filament of curie
is now replaced by A=rpZ/t, (374)
where Z is the time-integral of the magnetic force ; so that
H=pZ, and curlZ = cE, (375)
Z being merely the vectorised Z. It is the vector-potential of the
magnetic current.
The following reciprocal relation is easily seen by comparing the
differential equations of an infinitely fine filament e0 and a finite fila-
ment. The electric current-density at the axis due to a longitudinal
cylinder of e (uniform) of radius a is numerically identical with the
total current through the circle of radius a due to the same total
impressed force (that is, rfe) concentrated in a filament at the axis, at
corresponding moments.
68. "Having got the solutions (372) for a filament e^ it might appear
that we could employ them to build up the solutions in the case of, for
instance, a cylinder of longitudinal impressed force of finite radius a.
But, according to (372), E would be positive and H negative every-
where and at every moment, in the case of the cylinder, because the
elementary parts are all positive or all negative. This is clearly a
wrong result. For it is certain that, at the first moment of starting
the longitudinal impressed force of intensity e in the cylinder, E just
outside it is negative ; thus
E— ±^e, in or out, at r = a, t = 0 ;
and that H is positive ; viz.
H=e/2fMV at r = a, t = 0.
We know further that, as E starts negatively just outside the cylinder,
E will be always negative at the front of the outward wave, and H
positive; thus _E.faH^ x (a/r)» (376)
the variation in intensity inversely as the square root of the distance
from the axis being necessitated in order to keep the energy constant
at the wave-front. The same formula with + E instead of - E will
express the state at the front of the wave running in to the axis.
There is thus a momentary infinity of E at the axis, viz., when t = a/v.
So far we can certainly go. Less securely, we may conclude that
during the recoil, E will be settling down to its steady value e within
the cylinder, and therefore the force of the field there will be positive,
and, by continuity, also positive outside the cylinder. Similarly, H
must be negative at any distance within which E is decreasing. We
conclude, therefore, that the filament-solutions (372) only express the
settling down to the final state, and are not comprehensive enough to
be employed as fundamental solutions.
Sudden Starting of e longitudinal in a Cylinder.
69. In order to fully clear up what is left doubtful in the last para-
graph, I have investigated the case of a cylinder of e comprehensively.
462 ELECTRICAL PAPERS.
The following contains the leading points. We have to make four inde
pendent investigations: viz., to find (1), the initial inward wave; (2),
the initial outward wave ; (3), the inside solution after the recoil ; (4),
the outside solution ditto. We may indeed express the whole by a
definite integral, but there does not seem to be much use in doing so,
as there will be all the labour of finding out its solutions, and they are
what we now obtain from the differential equations.
Let El and E2 be the E's of the inward and outward waves. Their
equations are
et ....................... (377)
- ....................... (378)
where U and W are given by (309), the accent means differentiation to
r, and the suffix indicates the value at r = a. To prove these, it is
sufficient to observe that U and W involve €qr and e~qr respectively, so
that (377) expresses an inward and (378) an outward wave; and
further that, by (310), we have
El-Ez = e at r = a, always; ............... (379)
which is the sole boundary condition at the surface of curl of e.
Expanding (377), we get
3-- + - + ...e> (380)
where B + S is given by (309), and y = Sqa. Now, e being zero before
and constant after t = 0, effect the integrations indicated by the inverse
powers of p, and then turn t to tv where
The result is
» .... 4
"~
. _.
"T^ a+1
....... (3
the structure of which is sufficiently clear. Here z: = vt-JSa.
This formula, when vt < a, holds between r = a and r = a - vt. But
when vt > a though < 2a, it holds between r = a and vt - a. Except
within the limits named, it is only a partial solution.
70. As regards E% it may be obtained from (381) by the following
changes. Change E: to - E2 on the left, and on the right change zl
to - z2l where
It is therefore unnecessary to write out E2. This E2 formula will
hold from r = a to r = vt + a, when vt<2a; but after that, when the
front of the return wave has passed r = a, it will only hold between
r = vt-a and vt + «.
ON ELECTROMAGNETIC WAVES. PART VI. 463
71. Next to find E3, the E in the cylinder when vt> a and the solu-
tion is made up of two oppositely going waves, and E± the external E
after vt = 2a, when it is made up of two outward going waves. I have
utterly failed to obtain intelligible results by uniting the primary waves
with a reflected wave. But there is another method which is easier,
and free from the obscurity which attends the simultaneous use of U
and W. Thus, the equations of EB and E± are
(382)
............. (383)
by (367) ; and a necessity of their validity is the presence of two waves
inside the cylinder, because of the use of /0 and J^ ; it is quite inad-
missible to use J0 when only one wave is in question, because J^ = 1
when r = 0, and being a differential operator in rising powers of p, the
meaning of (382) is that we find E^ at r by differentiations from EB at
r = 0; thus (382) only begins to be valid when vt = a.
To integrate (382), (383), it saves a little trouble to calculate the
time-integrals of E3 and E4, say
A3=-p-*E3, A,= -p-^E, ........ . ....... (384)
The results are - As = /<». e-(vW-arf, ........................ (385)
^'1 ................ (386)
From these derive E3 and E± by time-differentiation, and H3, H4 by
space-differentiation, according to
pK, or H=---^ (387)
We see that the value of E3 at the axis, say E0, is
EQ = evt(v*P-a2)~*; (388)
and by performing the operation J0r in (385) we produce, if u = (v*t2 - a2)*,
-Ao = -\ u + ~(- -
•-•(3
from which we derive
(390)
These formulae commence to operate when vt = a at the axis, and when
i)t = a + r at any point r < a, and continue in operation for ever after.
464 ELECTRICAL PAPERS.
72. Lastly, perform the operation (2/sa)Jla in (386), and we obtain
A = a2*ri -( - l ^-\ !*(*. 3(W 35*;4*4\
4 2v [_u + 8 V u3 + u* ) + 64\M5 u7 ~~«?~/
45a6 / 5 135v2/2 315^ 231 tW\ ~1
+ 4. 36.64V' ^ + ^9~ "~^~ P / + •"__]'
from which we derive
15?4)
. (392)
1
These begin to operate at r = a when vt = 2a ; and later, the range is
from r = a to r = vt - a.
This completes the mathematical work. As a check upon the
accuracy, we may test satisfaction of differential equations, and of
the initial condition, and that the four solutions join together with
the proper discontinuities.
73. The following is a general description of the manner of establish-
ing the steady flux. We put on e in the cylinder when t = 0. The
first effect inside is E1 = \e, at the surface, and H^ = EJpv. This
primary disturbance runs in to the axis at speed v, varying at its
front inversely as the square root of the distance from the axis, thus
producing a momentary infinity there. At this moment t = a/v, El is
also very great near the axis. In the meantime, El ,has been increasing
generally all over the cylinder, so that, from being \& initially at the
boundary, it has risen to '77 e, whilst the simultaneous value at r - ^a
is about *95 e.
Now consider E3 within the cylinder, it being the natural con-
tinuation of Ey The large values of E1 near the axis subside with
immense rapidity. But near the boundary El still goes on increasing.
The result is that when vt = 2a, and the front of the return-wave reaches
the boundary, Ez has fallen from oo to l'154e at the axis; at r = Jo.
the value is 1-183 e; at r = fa it is 1-237 e; and at the boundary the
value has risen to 1-71 e, which is made up thus, 1-21 e + ^e; the first
of these being the value just before the front of the return-wave arrives,
the second part the sudden increase due to the wave-front. Es is now
a minimum at the axis and rises towards the wave-front, the greater
part of the rise being near the wave-front.
Thirdly, go back to £ = 0 and consider the outward wave. First,
-^2 - ~~ %e at r = a- This runs out at speed v, varying at the front
inversely as ri As it does so, the E2 that succeeds rises, that is, is
less negative. Thus when vt = a, and the front has got to r = 2«, the
values of E.2 are - '232 e at r = a and - -353 e at r = 2a. Still later, as
this wave forms fully, its hinder part becomes positive. Thus, when
fully formed, with front at r = 3a, we have Ez = - -288 e at r = 3a ;
- '14:5 e at r = 2a; and '21 e at r = a. This is at the moment when
the return-wave reaches the boundary, as already described.
ON ELECTROMAGNETIC WAVES. PART VI. 465
The subsequent history is that the wave E2 moves out to infinity,
being negative at its front and positive at its back, where there is
a sudden rise due to the return-wave E^ behind which there is a rapid
fall in E^ not a discontinuity, but the continuation of the before-
mentioned rapid fall in E3 near its front. The subsidence to the
steady state in the cylinder and outside is very rapid when the front
of E4 has moved well out. Thus, when vt = 5a, we have E3 = 1-022 e
at r = a, and of course, just outside, we have E4 = '022e; and when
vt = l(k, we have E3 = 1 -005 e, E4 = -005 e, at r = a.
As regards H, starting when t = 0 with the value e/2pv at r = a only,
at the front of the inward or outward wave it is E = ± pvH, as usual.
It is positive in the cylinder at first, and then changes to negative.
Outside, it is first positive for a short time, and then negative for ever
after.
74. We can now see fully why the solution for a filament eQ of e can
not be employed to build up more complex solutions in general, whilst
that for a filament /0 of curl e can be so employed. For, in the latter
case, the disturbances come, ab initio, from the axis, because the lines
of curl e are the sources of disturbance, and they become a single line
at the axis. But in the former case it is not the body of the filament,
but its surface only, that is the real source, however small the filament
may be, producing first E negative (or against e) just outside the
filament, and, immediately after, E positive. Now when the diameter
of the filament is indefinitely reduced, we lose sight altogether of the
preliminary negative electric and positive magnetic force, because their
duration becomes infinitely small, and our solutions (372) show only
the subsequent state of positive electric and negative magnetic force
during the settling down to the final state, but not its real commence-
ment, viz., at the front of the wave.
75. The occurrence of momentary infinite values of E or of H, in
problems concerning spherical and cylindrical electromagnetic waves,
is physically suggestive. By means of a proper convergence to a point
or an axis, we should be able to disrupt the strongest dielectric, starting
with a weak field, and then discharging it. Although it is impossible
to realize the particular arrangements of our solutions, yet it might be
practicable to obtain similar results in other ways.*
It may be remarked that the solution worked out for an infinitely
* If we wish the solution for an infinitely long cylinder to be quite unaltered,
when of finite length I, let at z = Q and z = l infinitely conducting barriers be
placed. Owing to the displacement terminating upon them perpendicularly, and
the magnetic force being tangential, no alteration is required. Then, on taking
off the impressed force, we obtain the result of the discharge of a condenser
consisting of two parallel plates of no resistance, charged in a certain portion
only ; or, by integration, charged in ?ny manner.
To abolish the momentary infinity at the axis, in the text, substitute for the
surface distribution of curl of e a distribution in a thin layer. The infinity will
be replaced by a large finite value, without other material change. Of course the
theory above assumes that the dielectric does not break down. If it does, we
change the problem, and have a conducting (or resisting) path, possibly with
oscillations of great frequency if the resistance be not too great, as Prof. Lodge
believes to be the case in a lightning discharge.
H.E.P. — VOL. II. 2o
466 ELECTRICAL PAPERS.
long cylinder of longitudinal e is also, to a certain extent, the solution
for a cylinder of finite length. If, for instance, the length is 21, and
the radius ft, disturbances from the extreme terminal lines of f (or curie)
only reach the centre of the axis after the time (a2 + l2)*/v, whilst from
the equatorial line of f the time taken is a/v, which may be only a little
less, or very greatly less, according as I/a is small or large. If large, it
is clear that the solutions for E and H in the central parts of the
cylinder are not only identical with those for an infinitely long cylinder
until disturbances arrive from its ends, but are not much different
afterwards.
Cylindrical Surface of Longitudinal f, a Function of 0 and t.
76. When there is no variation with 0, the only Bessel functions con-
cerned are JQ and Jr The extension of the vibratory solutions to
include variation of the impressed force or its curl as cos 6, cos 20, etc.,
is so easily made that it would be inexcusable to overlook it. Two
leading cases will be very briefly considered. Let the curl of the
impressed force be wholly upon the surface of a cylinder of radius a,
longitudinally directed, and be a function of t and 6, its tensor being/,
the measure of the surface-densitj'. H is also longitudinal, of course,
whilst E has two components, circular E and radial F. The connections
are
from which the characteristic of H is
1 d dH
-0 ..................... (394)
r \ r /
if s2 = -^2/v2 and w2 = - d2/d02. Consequently
H= (Jmr-yGmr) cos mB x function of t ............ (395)
when m? is constant, and the E/H operator is
* IJLrlgk ...(396)
H cpJmr-yGj
if Jmr or Jm(sr) is the mth Bessel-function, and Gmr its companion,
whilst the ' means d/dr.
The boundary condition is
Ei = E*-f at r = a, .................... (397)
E-i being the inside, E2 the outside value of the force of the flux.
Therefore, using (396) with ?/ = 0 inside, we obtain
where x is a constant, being ?r/2 when m = 0, according to (307), and
always ?r/2 if G^ has the proper numerical factor to fix its size.
We see that if
ON ELECTROMAGNETIC WAVES. PART VI. 467
where /0 is constant, the boundary H, and with it the whole external
field, electric and magnetic, vanishes when
/..-o.
If 77i = 0, or there is no variation with 0, the impressed force may be
circular, outside the cylinder, and varying as r~l.
If m= 1, the impressed force may be transverse, within the cylinder,
and of uniform intensity.
Conducting Tube, e Circular, a Function of 6 and t.
77. This is merely chosen as the easiest extension of the last case.
In it let there be two cylindrical surfaces of f, infinitely close together.
They will cancel one another if equal and opposite, but if we fill up the
space between them with a tube of conductance K per unit area, we get
the case of e circular in the tube, e varying with 6 and t, and produce a
discontinuity in H (which is still longitudinal, of course). Let Ea be
the common value of E just outside and inside the tube ; e + Ea is then
the force of the flux in the substance of the tube, and
........................ (399)
the discontinuity equation, leads, by the use of (396) and the conjugate
property of Jm and G-m as standardized* in the last paragraph, through
to the equation of EM viz.,
...(400)
ira Lt/maVt/tna #ww_
from which we see that it is J^ = 0 that now makes the external field
vanish.
78. This concludes my treatment of electromagnetic waves in relation
to their sources, so far as a systematic arrangement and uniform method
is concerned. Some cases of a more mixed character must be reserved.
It is scarcely necessary to remark that all the dielectric solutions may
be turned into others, by employing impressed magnetic instead of
electric force. The hypothetical magnetic conductor is required to
obtain full analogues of problems in which electric conductors occur.
August 10, 1888.
* [If we take Stokes's formula for Jmt thus
then the substitution of sin for cos and - cos for sin will give the Om function
standardized as in the text. Also note that the infiniteness of G0 when /3 is
omitted, referred to in footnote p. 445, arises when q* is + ].
468 ELECTRICAL PAPERS.
XLIV. THE GENERAL SOLUTION OF MAXWELL'S ELECTRO-
MAGNETIC EQUATIONS IN A HOMOGENEOUS ISO-
TROPIC MEDIUM, ESPECIALLY IN REGARD TO THE
DERIVATION OF SPECIAL SOLUTIONS, AND THE
FORMULAE FOR PLANE WAVES.
[Phil. Mag., Jan. 1889, p. 30.]
Equations of the Field.
1. ALTHOUGH, from the difficulty of applying them to practical problems,
general solutions frequently possess little practical value, yet they may
be of sufficient importance to render their investigation desirable, and
to let their applications be examined as far as may be practicable. The
first question here to be answered is this. Given the state of the whole
electromagnetic field at a certain moment, in a homogeneous isotropic
conducting dielectric medium, to deduce the state at any later time,
arising from the initial state alone, without impressed forces.
The equations of the field are, if p stand for d/dt,
(1)
......................... (2)
the first being Maxwell's well-known equation defining electric current
in terms of the magnetic force H, k being the electric conductivity and
c/4?r the electric permittivity (or permittance of a unit cube condenser),
and E the electric force ; whilst the second is the equation introduced
by me* as the proper companion to the former to make a complete
system suitable for practical working, g being the magnetic conductivity
and //, the magnetic inductivity. This second equation takes the place
of the two equations
E=-A-W, curlA = /xH, .................. (3)
of Maxwell, where A is the electromagnetic momentum at a point, and
Mf the scalar electric potential. Thus ^ and A are murdered, so to
speak, with a great gain in definiteness and conciseness. As regards g,
however, standing for a physically non-existent quality, such that the
medium cannot support magnetic force without a dissipation of energy
at the rate </H2 per unit volume, it is only retained for the sake of
mathematical completeness, and on account of the singular telegraphic
application in which electric conductivity is made to perform the
functions of both the real k and the unreal g.
Let
v = (i*c)-*.\ ........... (4)
The speed of propagation of all disturbances is V, and the attenuating
effects due to the two conductivities depend upon ft and p2, whilst or
determines the distortion due to conductivity.
* " Electromagnetic Induction and its Propagation," The Electrician, January
3, 1885, and later [vol. i., p. 449.]
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 469
General Solutions.
2. Let <f denote the operator
?2 = -(fl curl)2 + o-2; ........................... (5)
or, in full, when operating upon E for example,
E. .. ................... (6)
Now it may be easily found by ordinary " symbolical " work which
it is not necessary to give, that, given B0, H0, the values of E and H
when rf = 0, and satisfying (1) and (2), those at time t later are given by
E = .-/"[(cosh gt-* sinh gffi + ^* . ^ H»], ]
H - .-.'[(cosh qt + "- sinh 2/)H0 - 22*1' . ^41. J ' '
A sufficient proof is the satisfaction of the equations (1), (2), and of
the two initial conditions.
An alternative form of (7) is
E = e-
showing the derivation of E from E0 and ^?E0 in precisely the same way
as H from H0 and ^H0. In this form of solution the initial values of
^E0 and pEQ occur. But they are not arbitrary, being connected by
equations (1), (2). The form (7) is much more convenient, involving
only E0 and H0 as functions of position, although (la) looks simpler.
The form (7) is also the more useful for interpretations and derivations.
If, then, E0 and H0 be given as continuous functions admitting of
the performance of the differentiations involved in the functions of g2,
(7) will give the required solutions. The original field should there-
fore be a real one, not involving discontinuities. We shall now con-
sider special cases.
Persistence or Subsidence of Polar Fields.
3. We see immediately by (7) that the E resulting from H0 depends
solely upon its curl, or on the initial electric current, and, similarly,
that the H due to E0 depends solely upon its curl, or on the magnetic
current. Notice also that the displacement due to H0 is related to H0
in the same way as the induction -f - 4?r due to E0 is related to E0.
Or, if it be the electric and magnetic currents that are considered, the
displacement due to electric current is related to it in the same way as
the induction -f 4?r due to magnetic current is related to it.
Observe, also, that in passing from the E due to E0 to the H due to
H0, the sign of o- is changed.
By (7), a distribution of H0 which has no curl, or a polar magnetic
field, does not, in subsiding, generate electric force ; and, similarly, a
470 ELECTRICAL PAPERS.
polar electric field does not, in subsiding, generate magnetic force. Let
theu E0 and H0 be polar fields, in the first place. Then, by (5),
ji^o*
that is, a constant; and, using this in (7), we reduce the general
solutions to
E = E06-2/tf, H = H0€-2/v ..................... (8)
The subsidence of the electric field requires electric conductivity,
that of the magnetic field requires magnetic conductivity ; but the two
phenomena are wholly independent. The first of (8) is equivalent to
Maxwell's solution.* The second is its magnetic analogue.
As, in the first case, there must be initial electrification, so in the
second, there should be " magnetification," its volume-density to be
measured by the divergence of the induction -f 4:r. Now the induction
can have no divergence. But it might have, if g existed.
There is no true electric current during the subsidence of E0, and
there would be no true magnetic current during the subsidence of H0.
In both cases the energy is frictionally dissipated on the spot, or there
is no transfer of energy, f The application of (8) will be extended
later.
Circuital Distributions.
4. By a circuital | distribution, I mean one which has no divergence
anywhere. Any field of force vanishing at infinity may be uniquely
divided into two fields, one of which is polar, the other circuital ; the
proof thereof resting upon Sir W. Thomson's well-known theorem of
Determinancy. Now we know exactly what happens to the polar fields.
Therefore dismiss them, and let E0 and H0 be circuital. Then
.............................. (9)
where V2 is the usual Laplacean operator. Of course coshqt and
q~l sinh qt are rational functions of q2, so that if the differentiations are
possible we shall obtain the solutions out of (7).
Distortionless Cases.
5. Let the subsidence-rates of the polar electric and magnetic fields
be equal. We then have
o- = 0, £2 = -(flcurl)2, p = 4:7r]c/c = 4:irg/fJL, ..... (10)
in the solutions (7). The fields change in precisely the same manner
as if the medium were nonconducting, as regards the relative values at
different places ; that is, there is no distortion due to the conductivities;
* Vol. i. chap, x., art. 325, equation (4).
t This is of course obvious without any reference to Poynting's formula. The
only other simple case of no transfer of energy, which had been noticed before that
formula, is that of conduction-current kept up by impressed force so distributed as
to require no polar force to supplement it.
t [Lord Kelvin's word "circuital" is here substituted for "purely solenoidal."]
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 471
but there is a uniform subsidence all over brought in by them, * ex-
pressed by the factor e~^e. This property I have explained by showing
the opposite nature of the tails left behind by a travelling plane-wave
according as a- is + or - .
The above applies to a homogeneous medium. But if, in
curl(H-h) = (47r& + cp)E, ........................ (la)
curl(e-E) = (4arg + pp)R, ................. ....... (2a)
differing from (1), (2) only in the introduction of impressed forces e and
h, we write
(H,h, E, e) = (H15 hlf Blf eje-/*,
we reduce them to
and these, if o- = 0, are the equations of a nonconducting dielectric.
That is,
p = 47T&/C = 47r<7//z = constant
is the required condition. Therefore c and //. may vary anyhow, inde-
pendently, provided k and g vary similarly.! The impressed forces
should subside according to e-'", in order to preserve similarity to the
phenomena in a nonconducting dielectric.
Observe that there will be tailing now, on account of the variability
of (fi/c)* or [j.v. That is, there are reflexions and refractions due to
change of medium. The peculiarity is that they are of the same nature
with as without conductivity.
First Special Case.
6. A special case of (11) is given by taking fi = 0 and g = Q ', that is,
a real conducting dielectric possessing no magnetic inductivity, in which
k/c is constant. If the initial field be polar, then
E = EoC-^, H = 0. ........................ (12)
This extension of Maxwell's before-mentioned solution I have given
before, and also the extension to any initial field, and the inclusion of
impressed forces. J The theory of the result has considerable light now
thrown upon it.
If the initial field be arbitrary, the circuital part of the flux displace-
ment disappears instantly, therefore (12) is the solution, provided E0
means the polar part of the initial field ; that is, E0 must have no curl,
and the flux cE0/47r must have the same divergence as the arbitrarily
given displacement.
Now an impressed force e produces a circuital flux only. Therefore
it produces its full effect and sets up the appropriate steady flux in-
stantaneously ; and all variations of e in time and in space are kept
* "Electromagnetic Waves," Part I., §7 [p. 381, vol. IT.].
t In § 4 of the article referred to in the last footnote the property was described
only in reference to a homogeneous medium.
J " Electromagnetic Induction " [vol. T., p. 534].
472 ELECTRICAL PAPERS.
time to without lag by the conduction-current in spite of the electric
displacement.
This property is seemingly completely at variance with ideas founded
upon the retardation usually associated with combinations of resistances
and condensers. But, being a special case of the distortionless theory,
we can now understand it. For suppose we start with a nonconducting
dielectric, and put on e uniform within a spherical portion thereof, and
send out an electromagnetic wave to infinity and set up the steady flux.
On now removing e, we send out another wave to infinity, and the flux
vanishes. Now make the medium conducting, with both conductivities
balanced, as in (10). Starting with the same steady flux, its vanishing
will take place in the same manner precisely, but with an attenuation-
factor €-P*. Now gradually reduce g and //, at the same time, in the
same ratio. The vanishing of the flux will take place faster and faster,
and in the limit, when both //. and g are zero, will take place instantly,
not by subsidence, but by instantaneous transference to an infinite
distance when the impressed force is removed, owing to v being made
infinite.
Second Special Case.
7. There is clearly a similar property when k = 0 and c = 0 ; that is,
in a medium possessing magnetic inductivity and conductivity, but
deprived of the electric correspondences. Thus, when #//x is constant,
the solution due to any polar field H0 is
H = H0€-*, E = 0; (13)
wherein /> = 4irg/p. But a circuital state of /xH disappears at once, by
instantaneous transference to infinity. Thus any varying impressed
force h is accompanied without delay by the corresponding steady flux,
the magnetic induction.
When the inertia associated with //, is considered, the result is rather
striking and difficult to understand. It appears, however, to belong to
the same class of (theoretical) phenomena as the following. If a coil in
which there is an electric current be instantaneously shunted on to a
second coil in which there is no current, then, according to Maxwell,
the first coil instantly loses current and the second gains it, in such a
way as to keep the momentum unchanged. Now we cannot set up a
current in a coil instantly, so that we have a contradiction. But the
disagreement admits of easy reconciliation. We cannot set up current
instantly with a finite impressed force, but if it be infinite we can. In
the case of the coils there is an electromotive impulse, or infinite electro-
motive force acting for an infinitely short time, when the coils are con-
nected, with corresponding instantaneous changes in their momenta.
A loss of energy is involved.
It is scarcely necessary to remark that the true physical theory
involves other considerations, on account of the dielectric not being
infinitely elastive, and on account of diffusion in the wires ; so that
we have sparking and very rapid vibrations in the dielectric. The
energy which is not wasted in the spark, and which would go out to
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 473
infinity were there no conducting obstacles, is probably all wasted
practically in the heat of conduction-currents in them.
Impressed Forces.
8. Given initially E0 and H0, we know that the diverging parts
must either remain constant or subside, and are, in a manner, self-
contained; but the circuital parts, which would give rise to waves,
may be kept from changing by means of impressed forces e0 and h0.
Thus, let E0 and H0 be circuital. To keep them steady we have, in
equations (1), (2), to get rid of^E and^?H. Thus
curl (H0 - h0) = 47r£E0, \
curl(e0-E0) -fcftyj"
are the equations of steady fields E0 and H0, these being the forces of
the fluxes. Or
curl h0 = curl H0 - 47r£E0, 1
curl e0 = curl EO + ^H,,,/''
give the curls of the required impressed forces in terms of the given
fluxes, and any impressed forces having these curls will suffice.
Now, on the sudden removal of e0, h0, the forces E0, H0, which had
hitherto been the forces of the fluxes, become, instantaneously, the
forces of the field as well. That is, the fluxes themselves do not change
suddenly, except in such a case as a tangential discontinuity in a flux
produced at a surface of curl of impressed force, when, at the surface
itself, the mean value will be immediately assumed on removal of
the impressed force. We know, therefore, the effects due to certain
distributions of impressed force when we know the result of leaving
the corresponding fluxes to themselves without impressed force. It is,
however, the converse of this that is practically useful, viz., to find the
result of leaving the fluxes without impressed force by solving the
problem of the establishment of the steady fluxes when the impressed
forces are suddenly started ; because this problem can often be attacked
in a comparatively simple manner, requiring only investigation of the
appropriate functions to suit the surfaces of curl of the impressed
forces. The remarks in this paragraph are not limited to homogeneity
and isotropy.
s Primitive Solutions for Plane Waves.
9. If we take z normal to the plane of the waves, we may suppose
that both E and H have x and y components. This is, however, a
wholly unnecessary mathematical complication, and it is sufficient to
suppose that E is everywhere parallel to the «-axis, and H to the y-axis.
The specification of an initial state is therefore EQ, jET0, the tensors
of E and H, given as functions of z; and the circuital equations (1), (2)
become
-dH/dz = (±7rk + cp)E, -dE/dz=(47rg + w)H. (15)
Now the operator q2 in (5) becomes
474 ELECTRICAL PAPERS.
where by V we may now understand d/dz simply. Therefore, by (7),
the solutions of (15) are
When the initial states are such as aete, or acosbz, the realization is
immediate, requiring only a special meaning to be given to q in (17).
But with more useful functions-, as ae~62'2, etc., etc., there is much work
to be performed in effecting the differentiations, whilst the method
fails altogether if the initial distribution is discontinuous.
But we may notice usefully that when E0 and HQ are constants the
solutions are
E = c-WEQ, tf=«-WJEroi ................. (18)
which are quite independent of one another. Further, since disturb-
ances travel at speed v, (IS) represents the solutions in any region in
which EQ and H0 are constant, from i = 0 up to the later time when a
disturbance arrives from the nearest plane at which E0 or HQ varies.
Fourier-Integrals.
10. Now transform (17) to Fourier-integrals. We have Fourier's
theorem,
f(a)cosm(z-a)dmda, ............. (19)
and therefore <{>(V2)f(z) = - [ f f(a)<j>( - m2) cos m(z - a) dm da ; (20)
^J o J -*
applying which to (17) we obtain
E = — I dm da\ EQcos m(z - a)( cosh - -sinhW
"" JoJ-« L 2
=— I dm da\ H0cos m(z - ft)^cosh + -sinh \g
(21)
in which, by (16), f = <r*-m*v*, .............................. (22)
and E0, HQ are to be expressed as functions of a, whilst E and H belong
to z. Discontinuities are now attackable.
The integrations with respect to m may be effected. In fact, I have
done it in three different ways. First by finding the effect produced by
impressed force. Secondly, by an analogous method applied to (17),
transforming the differentiations to integrations. Thirdly, by direct
integration of (21) ; this is the most difficult of all. The first method
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 475
was given in a recent paper* ; a short statement of the other two
methods follows.
Transformation of the Primitive Solutions (17).
11. In (17) we naturally consider the functions of qt to be expanded
in rising powers of q2, and therefore of V2, leading to differentiations to
be performed upon the initial states. But if we expand them in
descending powers of V, we substitute integrations, and can apply them
to a discontinuous initial distribution.
The following are the expansions required : —
i, ,«-rx- ,, /^x- , -(23)
€«' =
where the £/'s are functions of (vVt)~l given by
TJ = v^Tl _*fr+l) , r(rM2)(r+2) r(^-18)(r^2')(r+3) 1
2vtV 2A.(vtV)* 2.4.6(^V)3 ~J
being in fact identically the same functions of vrfV as those of r which
occur in the investigation of spherical waves. [See p. 406, vol. II.]
Arranged in powers of s = o-/vV, we have
(25)
€« = ^V(1+s/ii + s2^+<<>)
where
"2T"1" 2.4.6.8' 82 42. 4.6 ^2.4.6.8.10
^6= --T* + T<r^-2-2.4.6.8 + 274777T2;
~1^~ • 2*.5.6
* "Electromagnetic Waves," Part IV. [p. 428, vol. II.].
476
ELECTRICAL PAPERS.
The following properties of the g's and ^'s are useful. Understanding
that g0 and h0 are unity, we have
gr + <rtgr+1 + ±^f-gr+t + . . . = 0. when r is odd,
I?
and when r is even,
except r = 0, when
/
[Also, hr
= 1.3.5. ..(?•-!)( -l)ir-
= /0(o^).
...(28)
when r is odd, but is zero when r is even (except r = 0, which case is
not wanted), and = - iJ^a-ti) when r = 1.] Now if
€*(l+oV?) = e^(l+S/1 + sy2+...), ................ (30)
the/'s* will be given by (25), viz.,
/o = 1> /i = 00 + ^1* /2 = #i + ^2> etc-; ......... (31)
and the properties of the/'s corresponding to (28), (29) are
* + (^£fr+,+ ...-«" when r-0,
= 0 when r is even, except 0 ;
and
= ± 1 . 3. 5 . . . (r -
\ /
when r is odd, with the + sign for r=l, 5, 9, ..., and the - sign for
the rest. The first case in (32), of r = 0, is very important. But in
case r= 1, the coefficient in (33) is + 1 ; thus,
Special Initial States.
1 2. Now let there be an initial distribution of H0 only, so that, by (17),
(34)
by (17). Let HQ be zero on the right side and constant on the left
side of the origin, and let us find H and E at a point on the right side.
The operator evfv is inoperative, so that, by (30),
- Sf1+ s2/2-s3/3+ ...)#<» 1 /35)
'
* These fs are the same as in my paper "On Electromagnetic Waves," §8
[vol. ii., p. 384] ; but s there is a here.
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 477
the immediate integration of which gives
K-/i( 1 ~ -J •*•••• f»
...(36)
To obtain the E due to E0 constant from z = - co to 0, use the first
of (36) ; change H to E, H0 to E^ and change the sign of o-, not
forgetting it in the f's. To obtain the corresponding H due to E0, use
the second of (36) ; change E to H, HQ to E0, and /* to c. So
where the accent means that the sign of a- is changed in the f's.
From these, without going any further, we can obtain a general idea
of the growth of the waves to the right and left of the origin, because
the series are suitable for small values of vt. But, reserving a descrip-
tion till later, notice that E in (36) and H in (37) must be true on
both sides of the origin ; on expanding them in powers of z we con-
sequently find that the coefficients of the odd powers of z vanish, by
the first of (28), and what is left may be seen to be the expansion of
.................. (38)
the complete solution for E due to H0. Similarly,
.................. (39)
is the complete solution for H due to E0. In both cases the initial
distribution was on the left side of the origin; but, if its sign be
reversed, it may be put on the right side, without altering these
solutions.
Similarly, by expanding the first of (36) and first of (37) in powers
of z we get rid of the even powers of z, and produce the solutions
given by me in a previous paper,* which, however, it is needless to
write out here, owing to the complexity.
Arbitrary Initial States.
13. Knowing the solutions due to the above distributions, we find
those due to initial E0da at the origin, or HQda, by differentiation to z:
* " Electromagnetic Waves," § 8 [vol. n., p. 383],
478 ELECTRICAL PAPERS.
and for this we do not need the firsts of (36) and (37), but only the
seconds. The results bring the Fourier-integrals (21) to
E . f-
H=
where p = d/dt, V = d/dz,
z+vt
(40)
Another interesting form is got by the changes of variables
These lead to
T P* ( TT ^ °" W \ T J°Y V \*\t? \
w>0 ~ I I ^fJin tytl ^/^l')) I 'I
...(42)
The connexions and partial characteristic ofUorW are
dW a- dU a- r
r
(43)
and this characteristic has a solution
(44)
where m is any + integer, and in which the sign of the exponent may
be reversed. We have utilized the case m = 0 only.
Evaluation of "Fourier-Integrals.
14. The effectuation of the integration (direct) of the original Fourier-
integrals will be found to ultimately depend upon
q v
provided vt > z, where, as before,
(f- = o-2 - m2v2.
By equating coefficients of powers of z2 in (45) we get
(45)
2 fsinh gt^fa _ ^1 .3.5.(2r - 1) J>^ .............. (46)
except with r = 0 ; then =v~lJQ(a-fi).
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 479
To prove (45), expand the ^-function in powers of o-2. Thus,
symbolically written,
sin mvi (47)
q \ mv
the operand being in the brackets, and p~l meaning integration from 0
to t with respect to t. Thus, in full,
"sin mvt er2(\ sinm^
2j,'-
mv
~. ...(48)
2 4o
Now the value of the first term on the right is
v~l, or 0, when z is <, or >vt.
Thus, in (48), if z>vt, since the first term vanishes, so do all the rest,
because their values are deduced from that of the first by integrations
to t, which during the integrations is always <z/v. Therefore the value
of the left member of (45) is zero when z>vt. In another form,
disturbances cannot travel faster than at speed v.
But when z < vt in (48), it is clear that whilst if goes from 0 to t or
from 0 to z/v, and then from z/v to t, the first integral is zero from 0 to
z/vt so that the part z/v to t only counts. Therefore the second term is
ma «• mv
The third is, similarly,
and so on, in a uniform manner, thus proving that the successive terms
of (48) are the successive terms of the expansion of (45) (right member)
in powers of o-2 ; and therefore proving (45).
The following formulse occur when the front of the wave is in
question, where caution is needed in evaluations : —
, A*\
(49)
m
sinh a-t _ 2 rsinmvt sinh qt^
o- 7rJ0 m q
Interpretation of Results.
15. Having now given a condensation of the mathematical work, we
may consider, in conclusion, the meaning and application of the formulae.
480 ELECTRICAL PAPERS.
In doing so, we shall be greatly assisted by the elementary theory of a
telegraph circuit. It is not merely a mathematically analogous theory,
but is, in all respects save one, essentially the same theory, physically,
and the one exception is of a remarkable character. Let the circuit
consist of a pair of equal parallel wires, or of a wire with a coaxial tube
for the return, and let the medium between the wires be slightly
conducting. Then, if the wires had no resistance, the problem of the
transmission of waves would be the above problem of plane waves in a
real dielectric, that is, with constants //., c, and k, but without the
magnetic conductivity; i.e. g = Q in the above.
The fact that the lines of magnetic and electric force are no longer
straight is an unessential point. But it is, for convenience, best to take
as variables, not the forces, but their line-integrals. Thus, if V be the
line-integral of E across the dielectric between the wires, V takes the
place of E. Then JcE, the density of the conduction-current, is replaced
by KVj where K is the conductance of the dielectric per unit length of
circuit ; and cE/4:7r, the displacement, becomes SV, where S is the per-
mittance per unit length of circuit. The density of electric current
cpE/^Tr is then replaced by SpV. Also SV\& the charge per unit length
of circuit.
Next, take the line-integral of H/4ir round either conductor for
magnetic variable. It is (7, usually called the current in the wires.
Then /*//", the induction, becomes LC ; where LC is the momentum
er unit length of circuit, L being the inductance, such that
A more convenient transformation (to minimize the trouble with
47r's) is
E to V, E to C, p to L, c to S, hrk to K.
Now, lastly, the wires have resistance, and this is without any repre-
sentation whatever in a real dielectric. But, as I have before shown,
the effect of the resistance of the wires in attenuating and distorting
waves is, to a first approximation (ignoring the effects of imperfect
penetration of the magnetic field into the wires), representable in the
same manner exactly as the corresponding effects due to #, the
hypothetical magnetic conductivity of a dielectric.* Thus, in addition
to the above,
becomes R,
R being the resistance of the circuit per unit length.
16. In the circuit, if infinitely long and perfectly insulated, the total
charge is constant. This property is independent of the resistance of
the wires. If there be leakage, the charge Q at time t is expressed in
terms of the initial charge Q0 b}7
independently of the way the charge redistributes itself.
In the general medium, the corresponding property is persistence of
* " Electromagnetic Waves," § 6 [p. 379, vol. n.].
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 481
displacement, no matter how it redistributes itself, provided k be zero,
whatever g may be. And, if there be electric conductivity,
E/f°°
D<fe-(
00 \J-0
where D0 is the initial displacement, and D that at time t, functions of z.
In the circuit, if the wires have no resistance, the total momentum
remains constant, however it may redistribute itself. This is an exten-
sion of Maxwell's well-known theory of a linear circuit of no resistance.
The conductivity of the dielectric makes no difference in this property,
though it causes a loss of energy. When the wires have resistance,
then
f
J-o
expresses the subsidence of total momentum ; and this is independent
of the manner of redistribution of the magnetic force, and of the leakage.
In the general medium, when real, the corresponding property is per-
sistence of the induction (or momentum) ; and when g is finite,
f
J -
In passing, I may remark that, in my interpretation of Maxwell's
views, it is not his vector-potential A, the so-called electrokinetic
momentum, that should have the physical idea of momentum associated
with it, but the magnetic induction B. To illustrate, consider Maxwell's
theory of a linear circuit of no resistance, the simplest case of persist-
ence of momentum. We may express the fact by saying that the
induction through the circuit remains constant, or that the line-integral
of A along or in the circuit remains constant. These are perfectly
equivalent. Now, if we pass to an infinitely small closed circuit, the
line-integral of A becomes B itself (per unit area). But if we consider
an element of length only, we get lost at once.
Again, the magnetic energy being associated with B, (and H), so
should be the momentum.
Suppose also we take the property that the line-integral of - A is
the E.M.F. in a circuit, and then consider - A as the electric force of
induction at a point. Its time-integral is A. But this is an electro-
motive impulse, not momentum.
Lastly, whilst B (or H) defines a physical property at a point, A does
not, but depends upon the state of the whole field, to an infinite
distance. In fact, it sums up, in a certain way, the effect which would
arise at a point from disturbances coming to it from all parts of the
field. It is therefore, like the scalar electric potential, a mathematical
concept merely, not indicative in any way of the actual state of the
medium anywhere.
The time-integral of H, whose curl is proportional to the displace-
ment, has equal claims to notice as a mathematical function which is of
occasional use for facilitating calculations, but which should not, in my
H.E.P. — VOL. ii. 2n
482
ELECTRICAL PAPERS.
opinion, be elevated to the rank of a fundamental quantity, as was done
by Maxwell with respect to A.
Independently of these considerations, the fact that A has often a
scalar potential parasite (and also the other function), sometimes causes
great mathematical complexity and indistinctness; and it is, for
practical reasons, best to murder the whole lot, or, at any rate, merely
employ them as subsidiary functions.
1 7. Returning to the telegraph-circuit, let the initial state be one of
uniform V on the whole of the left side of the origin, V= 0 on the
right side, and (7=0 everywhere. The diagram will serve to show
roughly what happens in the three principal cases.
First of all we have ABCD to represent the curve of F0, the origin
being at C. When the disturbance has reached Z, that is when t = CZ/v,
the curve is A 1 1 1 1 Z, if there be no leakage, when R and L are such
that €-*"M = \m At the origin, V= \V^\ at the front, V= \V^\ and at
the back, F=jF0.
A —
n
X
>~. —
rVo . --v.
i
2
2
^^^_l
3 —
-±* ,3 _^
3 1_^^|
Now introduce leakage to make RjL = K/S. Then 2 2 2 2 1 Z shows
the curve of F, provided e~«/s = J. We have F=iF0 on the left, and
P^JFlintherest.
Thirdly, let the leakage be in excess. Then, when F0 has fallen, by
leakage only, to JF0 on the left, the curve 3 3 3 3 1 Z shows F; it is
^Fo at the origin, - ^F0 at the back, and ^F0 at the front.
[The third case is numerically wrong. Thus, at the front we have
j7/F0 = j€-(/5l+^, at origin Je~2/)1', and behind e-2"'. Now take p2 = 0.
Then, when e~flit = J, we have F/F0 = J at front, \ at origin, 0 at back,
and j behind. It is later on that V becomes negative at the back.
Thus, when c~pit = J, we have F/F0 = -| at front, ^V at origin, -^ at
back, and y1^ behind. And when e~Pit = ^, we have F/F0 = T1g- at front,
T|-¥ at origin, - /T at back, and -^ behind.]
Of course there has to be an adjustment of constants to make
€-(Riu+s/is)t j^ the game | jn a]| casegj vjz ? the attenuation at the front.
18. Precisely the same applies when it is C0 that is initially given
instead of FQ, provided we change the sign of a-. That is, we have the
curve 1 when the leakage is in excess, and the curve 3 when the leakage
is smaller than that required to produce distortionless transmission.
19. Now transferring attention to the general medium, if we make
the substitution of magnetic conductivity for the resistance of the wires,
the curve 1 would apply when it is E0 that is the initial state and g in
excess, and 3 when it is deficient ; whilst if H0 is the initial state, 1
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 483
applies when g is deficient, and 3 when in excess. But g is really zero,
so we have the curve 1 for that of H and 3 for that of E.
This forcibly illustrates the fact that the diffusion of charge in a sub-
marine cable and the diffusion of magnetic disturbances in a good con-
ductor, though mathematically analogous, are physically quite different.
They are both extreme cases of the same theory ; but they arise by
going to opposite extremities; with the peculiar result that, whereas
the time-constant of retardation in a submarine cable is proportional to
the resistance of the wire, that in the wire itself is proportional to its
conductivity.
20. Going back to the diagram, if we shift the curves bodily through
unit distance to the left, and then take the difference between the new
and the old curves, we shall obtain the curves showing how an initial
distribution of V or C through unit-distance at the origin divides and
spreads. In the case of curve 2, we have clean splitting without a
trace of diffusion. In the other cases there is a diffused disturbance
left behind between the terminal waves, positive in case 1, negative in
case 3. But I have sufficiently described this matter in a former
paper. *
October 18, 1888.
POSTSCRIPT.
On the Metaphysical Nature of the Propagation of the Potentials.
At the recent Bath Meeting of the British Association there was con-
siderable discussionf in Section A on the question of the propagation of
electric potential. I venture therefore to think that the following
remarks upon this subject may be of interest.
According to the way of regarding the electromagnetic quantities I
have consistently carried out since January 1885, the question of the
propagation of, not merely the electric potential ^, but the vector
potential A, does not present itself as one for discussion ; and, when
brought forward, proves to be one of a metaphysical nature.
We make acquaintance, experimentally, not with potentials, but with
forces, and we formulate observed facts with the least amount of
hypothesis, in terms of the electric force E and magnetic force H. In
Maxwell's development of Faraday's views, E and H actually represent
the state of the medium anywhere. (It comes to the same thing if we
consider the fluxes, but less conveniently in general.) Granting this,
it is perfectly obvious that in any case of propagation, since it is a
physical state that is propagated, it is E and H that are propagated.
Now, in a limited class of cases, E is expressible as -V*". Con
siderations of mathematical simplicity alone then direct the mathe-
matician's attention to "¥ and its investigation, rather than to that of
E directly. But when this is possible the field is steady, and no
question of propagation presents itself (except in the very artificial form
* "Electromagnetic Waves," §7 [vol. n., p. 382].
tSee Prof. Lodge's "Sketch of the Electrical Papers read in Section A," The
Electrician, September 21 and 28, 1888.
484 ELECTRICAL PAPERS.
of balanced exchanges). When there is propagation, and H is involved,
we have
Now this is not an electromagnetic law specially, but strictly a truism,
or mathematical identity. It becomes electromagnetic by the definition
ofA'
leaving A indeterminate as regards a diverging part, which, however,
we may merge in - V*". Supposing, then, A and ¥ to become fixed in
this or some other way, the next question in connection with propaga-
tion is, Can we, instead of the propagation of E and H, substitute that
of >F and A, and obtain the same knowledge, irrespective of the
artificiality of W and A ? The answer is perfectly plain — we cannot do
so. We could only do it if ^ A, given everywhere, found E and H.
But they cannot. A finds H, irrespective of *P, but both together will
not find E. We require to know a third vector, A. Thus we have M*,
A, and A, required, involving seven scalar specifications to find the six
in E and H. Of these three quantities, the utility of A is simply to
find H, so that we are brought to a highly complex way of representing
the propagation of E in terms of ¥ and A, giving no information about
H, which is, it seems to me, as complex and artificial as it is useless and
indefinite.
Again, merely to emphasize the preceding, the variables chosen should
be capable of representing the energy stored. Now the magnetic
energy may be expressed in terms of A, though with entirely erroneous
localization ; but the electric energy cannot be expressed in terms of "SK
Maxwell (chap. XI. vol. II.) did it, but the application is strictly limited
to electrostatics ; in fact, Maxwell did not consider electric energy
comprehensively. The full representation in terms of potentials
requires M* and Z, the vector-potential of the magnetic current. (This
is developed in my work " On Electromagnetic Induction and its
Propagation " [vol. L, p. 507].) This inadequacy alone is sufficient to
murder ^ and A, considered as subjects of propagation.
Now take a concrete example, leaving the abstract mathematical
reasoning. Let there be first no E or H anywhere. To produce any,
impressed force is absolutely needed. Let it be impressed e, and of the
simplest type, viz , an infinitely extended plane sheet of e of uniform
intensity, acting normally to the plane. What happens ? Nothing at
all. Yet the potential on one side of the plane is made greater by the
amount e (tensor of e) than on the other side. Say ^f = \e and - \e.
Thus we have instantaneous propagation of ^ to infinity. I prefer,
however, to say that this is only a mathematical fiction, that nothing is
propagated at all, that the electromagnetic mechanism is of such a
nature that the applied forces are balanced on the spot, that is, in the
sheet, by the reactions.
To emphasize this again, let the sheet be not infinite, but have a
circular boundary. Let the medium be of uniform inductivity p, and
permittivity c. Then, irrespective of its conductivity, disturbances are
GENERAL SOLUTION OF ELECTROMAGNETIC EQUATIONS. 485
propagated at speed fl = (/xc)"i, and their source is the vortex-line of e,
on the edge of the disk. At any time t less than a/v, where a is the
radius of the disk, the disturbance is confined within a ring whose axis
is the vortex-line. Everywhere else, E = 0 and H = 0. On the surface
of the ring, E = pvH, and E and H are perpendicular ; there can be no
normal component of either.
Now, we can naturally explain the absence of any flux in the central
portion of the disk, by the applied forces being balanced by the
reactions on the spot, until the wave arrives from the vortex-line.
But how can we explain it in terms of *P, seeing that *P has now to
change by the amount e at the disk, and yet be continuous everywhere
else outside the ring ? We cannot do it, so the propagation of ¥ fails
altogether. Yet the actions involved must be the same whether the
disk be small or infinitely great. We must therefore give up the idea
altogether of the propagation of a *F to balance impressed force. In
the ring itself, however, we may regard the propagation of "*" (a different
one), A, and A ; or, more simply, of E and H.
If there be no conductivity, the steady electric field is assumed any-
where the moment the two waves from opposite ends of a diameter of
the disk coexist ; that is, as soon as the wave arrives from the more
distant end.* But this simplicity is quite exceptional, and seems to be
confined to plane and spherical waves. In general there is a subsidence
to the steady state after the initial phenomena.
If it be remarked that incompressibility (or something equivalent or
resembling it) is needed in order that the medium may behave as described
(i.e., no flux except at the vortex-line initially), and that if the medium
be compressible we shall have other results (a pressural wave, for
example, from the disk generally), the answer is that this is a wholly
independent matter, not involved in Maxwell's dielectric theory, though
perhaps needing consideration in some other theory. But the moment
we let the electric current have divergence (the absence of which makes
the vortex-lines of e to be the sources of disturbances), we at once (in
my experience) get lost in an almost impenetrable fog of potentials.
Maxwell's theory unamended, on the other hand, works perfectly and
without a trace of indefiniteness, provided we regard E and H as the
variables, and discard his " equations of propagation " containing the
two potentials.!
October 22, 1888.
* "Electromagnetic Waves," §25 [p. 415, vol. n.].
t [March 20, 1889. — Referring to the example given above of a circular disk, I
strangely overlooked the fact that the absence of flux initially can be expressed by
infinitely rapid propagation of both a ^ and an A. In the disk itself we must have
- V^ - A= - impressed force, so that there is no flux there, and outside we must
have - V* - A = 0. This makes it go. But as regards propagation, it only makes
matters worse. It is a reductio ad absurdum to have an electrostatic field pro-
pagated infinitely rapidly, and, simultaneously, the electric force of induction,
its exact negative, merely to cancel the former, itself quite hypothetical.
In my paper "On the Electromagnetic Effects due to Moving Electrification,"
Phil. May., April, 1889 (vol. IL, Art. L.), is an explicit example showing the
absurdity of the thing.]
486 ELECTRICAL PAPERS.
XLV. LIGHTNING DISCHARGES, ETC.
[The Electrician, Aug. 17, 1888, p. 479.]
THE gap between the electrical phenomena of common practice and
those concerned in the transmission of light and heat, a gap that it
once seemed almost impossible to bridge, is being gradually filled up,
both from the theoretical and the experimental side ; both from above,
by the observation of dark heat and in other ways ; and from below,
by electrical means, as condenser-discharges, vacuum-tube experiments,
etc. Dr. Lodge's recent work on lightning discharges, especially the
experiments described in his second lecture, deserves the most careful
attention, as a substantial addition to our knowledge of the subject, and
also because it is, so far as I know, the first serious attempt to treat the
subject electromagnetically.
The fluids are played out ; they are fast evaporating into nothingness.
The whole field of electrostatics must be studied from the electro-
magnetic point of view to obtain an adequately comprehensive notion
of the facts of the case ; and it is here that Dr. Lodge's experiments are
also useful.
Independently of this, I should not be surprised to find that a new
fact is contained in some of the experiments. Now a new fact is a
serious matter, and its existence can only be granted upon the most
conclusive evidence, of varied nature. There is already some inde-
pendent evidence, viz., in Kundt's. recent paper on the speed of light in
metals. But it is scarcely sufficient.
There is the plainest possible evidence that with waves of telephonic
frequency the magnetic force and the flux induction are proportionate,
and that their ratio is a large number in iron. I have observed, and I
read that Ayrton and Perry have also observed, decrease of the
inductivity with increased wave-frequency. But, at least with me, it
went only a little way, and I had not the opportunity to extend the
experiments.
Now a conducting wire at the first moment of receiving a wave (in
the dielectric, of course) performs the important function of guiding it
and preventing its dissipation in space ; and besides that, the nature of
the conductor partly determines what impedance the wave suffers,
causing a reflection back, with heaping up behind, so to speak, of the
electric disturbance. But at first the conduction-current is purely super-
ficial. It is clear then that at the very front of a wave, where con-
duction is just commencing on the surface, the conductor cannot be
treated as if it had the same properties (conductivity, inductivity,
permittivity) as if it were material in bulk, for only a thin layer of
molecules is concerned. We therefore do not know what the true
boundary condition is when pushed to the extreme. And yet it may
be that this unknown condition may sometimes serve to determine a
choice of paths.
Thus, iron may behave, superficially, as if it were non-magnetic.
(This does not mean that the inductivity of an iron wire is unity.) In
LIGHTNING DISCHARGES, ETC. 487
Kundt's experiments, electromagnetically interpreted, the inductivity
of iron is nowhere ; the conductivity, too, must, in other cases as well,
be less than the steady value. This corroborates Maxwell's remarks
concerning gold-leaf. Of course the application of electromagnetic
principles to the passage of light through material substances is at
present in a very tentative state ; so that too much importance should
not be attached to the speculations one may be led to make in these
matters.
(If a conductor could be treated as homogeneous right up to its
surface, the initial resistance of unit of surface I calculate to be kirpv,
where //, is the inductivity and v the speed of transmission in the con-
ductor. But neither p nor r can be considered to be known in the case
of iron.) [See p. 437, vol. IL]
Another matter I wish to direct attention to is this. Dr. Lodge has
described some experiments relating to the reflection of waves sent
along a circuit. It will also be in the knowledge of some readers that
Sections XL. to XLVI. of my " Electromagnetic Induction and its
Propagation," Electrician, June to September, 1887 (and a straggler,
XLVII., December 31, 1887), deal with the subject of the transmission
of waves along wires, their reflection, absorption, etc., by a new method.
Now I find that there is an idea prevalent that it is only possible for
very advanced mathematicians to understand this subject. It is true
that when it is comprehensively considered it is by no means easy.
But I desire to call attention to the fact (as I did in one or more of the
articles referred to) that all the main features of the transmission,
reflection, absorption, etc., of waves can be worked out (as done there
by me) by elementary algebra.
I was informed (substantially) that no one read my articles. Possibly
some few may do so now, with Dr. Lodge's experiments in practical
illustration of some of the matters considered.
My next communication, I may add (written in September, 1887), is
on the important subject of the measure of the inductance of circuits,
and its true effects, in amplification of preceding matter. It has also
special reference to some experimental observations. It has also some
valuable annotations by an eminent authority. [Art. xxxviu., vol. II.,
p. 160.]
P.S. — In connection with lightning discharges, I may remark that it
is usual, and seems very natural, to assume that the discharge is
initiated' at the place of the visible spark — the crack, so to speak. But
my recent investigations lead me to conclude that this is by no means
necessary, and that the strongest dielectric can be disrupted by a suit-
able convergence of a wave to a centre or an axis, starting with any
steady field.
For instance, if in a cylindrical portion of a dielectric the displacement
be uniform, and parallel to the axis, and it be allowed to discharge, the
convergence of the resulting wave to the axis causes the electric force
to mount up infinitely there, momentarily ; hence disruption.
But I do not pretend to give a complete theory of the thundercloud.
It is only a detail.
488 ELECTRICAL PAPERS.
P.P.S. — In Dr. Fleming's recent articles on the theory of alter-
nating currents, I observe that he calls the component Ln of the imped-
ance (E2 + L2n'2)* the "inductive resistance."
I should myself have scarcely thought that it deserved a name, for of
course we must draw the line somewhere. But the fact that Dr.
Fleming has given it a name is evidence that he found it convenient to
do so. Taking it, then, for granted that it should have a special name,
I can only object to the one chosen that it creates two kinds of resist-
ance. I desire to recognise but one — the resistance. I might, for
instance, call Ln the hindrance. Thus, in the case of a coil, R is the
electric resistance, Ln the magnetic hindrance, and their resultant the
impedance. But in any case it would not be a term for popular use,
August 13, 1888.
XL VI. PRACTICE VERSUS THEORY.— ELECTROMAGNETIC
WAVES.
[The Electrician, Oct. 19, 1888, p. 772.]
THE remarkable leader in The Electrician for Oct. 12, 1888, states very
lucidly some of the ways in which theory and practice seem to become
antagonistic. There is, however, one point which does not, I think,
receive the attention it deserves, which is, that it is the duty of the
theorist to try to keep the engineer who has to make the practical
applications straight, if the engineer should plainly show that he is
behind the age, and has got shunted on to a siding. The engineer
should be amenable to criticism.
Another point is this. It might appear from the concluding para-
graph of the article to which I have referred that the points at issue
between Mr. Preece's views and my own were mere matters of com-
plicated corrections, not affecting the main argument much. But the
case is far different. A complete change of type is involved.
Now, I shall have great pleasure, when opportunity offers, in en-
deavouring to demonstrate that such is the case, and that the despised
self-induction is the great moving agent ; that although Mr. Preece, in
the presence of some distinguished mathematicians, recently boasted *
that he made mathematics his slave, yet it is not wholly improbable
that he is a very striking and remarkable example of the opposite pro-
cedure ; that although Mr. Preece, who, as a practical engineer, knows
all about electromagnetic inertia and throttling, does not see the
use of inductance, impedance, and all that sort of thing, yet there is
not wanting evidence to make it not wholly unbelievable that Mr.
Preece is not quite fully acquainted with the subject as generally
* [The Discussion on Lightning Conductors at the Bath meeting of the B.A.,
reported at length in The Electrician, Sept. 21 and 28, 1888, is interesting reading,
and is made quite amusing by Mr. Preece's attack upon mathematicians to his own
exaltation, and the rejoinders thereto.]
PRACTICE VERSUS THEORY.— ELECTROMAGNETIC WAVES. 489
understood; that, for example, his coefficient of self-induction is of
very different size, and has very different properties, from the theo-
retical one ; and that Mr. Preece's knowledge of the manner of trans-
mission of signals, though it may not be "extensive," is certainly
" peculiar."
I may take the opportunity of adding that on account of a certain
peculiar concurrence and concatenation of circumstances last year
rendering it impossible for me to communicate the practical applications
of my theory (based upon Maxwell's views, so far as the higher de-
velopments are concerned), either vid the S. T.-E. and E. or four other
channels, the resultant effect of which was to screen Mr. Preece from
criticism, combined with the fact that Mr. Preece, in his papers to the
Royal Society, British Association, and S. T.-E. and E. has taken his
stand upon Sir W. Thomson's celebrated theory of the submarine cable,
I have been forced, with great reluctance, to assume what may have
appeared to be, superficially, an apparently unnecessarily aggressive
attitude towards the said theory. But those who are acquainted with
the subject will know that there is no antagonism whatever between
the electrostatic theory and the wider theory ; and those, further, who
may be acquainted with the peculiar concurrence I have mentioned
will understand the meaning of the apparent aggressiveness.
In addition, it seems to me to be almost mathematically certain that
Sir W. Thomson would emphatically repudiate the very notion of apply-
ing his theory of the diffusion of potential to cases to which it does not
apply, and to which it was never meant to apply ; and I cannot find
any evidence in his writings that he ever would have made such a
misapplication.
p.S. — Is self-induction played out? I think not. What is played
out is what we may call (uniting the expressions of Ayrton, Preece,
Thomson, and Lodge) the British engineer's self-induction, which stands
still, and won't go. But the other self-induction, in spite of strenuous
efforts to stop it, goes on moving; nay, more, it is accumulating
momentum rapidly, and will, I imagine, never be stopped again. It is,
as Sir W. Thomson is reported to have remarked, with a happy union
of epigrammatic force and scientific precision, " in the air." Then
there are the electromagnetic waves. Not so long ago they were
nowhere ; now they are everywhere, even in the Post Office. Mr.
Preece has been advising Prof. Lodge to read Prof. Poynting's paper
on the transfer of energy. This is progress, indeed ! Now these waves
are also in the air, and it is the " great bug " self-induction that keeps
them going.
On this question of waves I take the opportunity of referring to a
point mentioned at the Bath meeting by Prof. Fitzgerald. That phy-
sicist, in directing attention to Hertz's recent experiments, considered
that they demonstrated the truth of the propagation of waves in time
through the ether ; but that, on the other hand, the waves sent along
a circuit did not do so, because they might be explained by action at a
distance.
It seems to me, however, that the more closely we look at the matter
490 ELECTRICAL PAPERS.
the less distinction there is between the two cases, and that to an
unbiassed mind the experiments of Prof. Lodge, sending waves of short
length into a miniature telegraph circuit, with consequent "resonance"
effects, are equally conclusive to those of Hertz on the point named ; in
one respect, perhaps, more so, because their theory is simpler, and can
be more closely followed.
But, after all, has it been demonstrated that we cannot explain the
propagation of electromagnetic waves in time by action at a distance,
pure and simple ? I suggest the following as evidence to the contrary.
Take the case of Maxwell's non-conducting dielectric. Let the electric-
current element cause magnetic force at a distance according to Ampere's
law, and let the magnetic current element cause electric force at a
distance according to the same law with sign reversed. Then
curl H = cE, and - curl E = /xH
follow, and propagation of waves in time follows. That is, by instant-
aneous mutual action at a distance between electric-current elements,
and also between magnetic-current elements, we get propagation in
time. Of course the currents may be oppositely moving electric or
magnetic fluids or particles.
Whether there is any flaw here or not, it is scarcely necessary for me
to remark that I do not believe in action at a distance. Not even
gravitational.
XLVII. ELECTROMAGNETIC WAVES, THE PROPAGATION
OF POTENTIAL, AND THE ELECTROMAGNETIC EFFECTS
OF A MOVING CHARGE.
[The Electrician-, Part L, Nov. 9, 1888, p. 23 ; Part II., Nov. 23, 1888, p. 83 ;
Part. III., Dec. 7, 1888, p. 147 ; Part IV., Sept. 6, 1889, p. 458.]
PART I.
IN connection with the letters of Profs. Poynting and Lodge in The
Electrician, Nov. 2, 1888, I believe that the following extract from a
letter from Sir William Thomson (which I have permission to publish)
will be of interest [see Postscript, p. 483, vol. IL, to elucidate] :—
" I don't agree that velocity of propagation of electric potential is a
merely metaphysical question. Consider an electrified globe, A, moved
to and fro, with simple harmonic motion, if you please, to fix the ideas.
Consider very quickly-acting electroscopes B, B', at different distances
from A. If the indications of B, B' were exactly in the same phase,
however their places are changed, the velocity of propagation of electric
potential would be infinite ; but if they showed differences of phase,
they would demonstrate a velocity of propagation of electric potential.
" Neither is velocity of propagation of ' vector-potential ' meta-
physical. It is simply the velocity of propagation of electromagnetic
force — the velocity of * electromagnetic waves/ in fact."
ELECTROMAGNETIC WAVES, ETC. 491
Taking the second point first, it is, I think, clear that if by the pro-
pagation of vector-potential is to be understood that of electric and
magnetic disturbances, it is merely the mode of expression that is in
question. I am myself accustomed to mentally picture the electric and
magnetic forces or fluxes, arid their propagation, which takes place at
the speed of light or thereabouts, because they give the most direct
representation of the state of the medium, which, I think, must be
agreed is the real physical subject of propagation. But if we regard
the vector-potential directly, then we can only get at the state of the
medium by complex operations, and we really require to know the
vector-potential both as a function of position and of time, for its space-
variation has to furnish the magnetic force, and its time-variation the
electric force ; besides which, there is sometimes the space-variation of a
scalar potential in addition to be regarded, before we can tell what the
electric force is. Besides this roundaboutness, it implies a knowledge
of the full solution, and if we do not possess it, it is much simpler to
think of the propagation of the electric and magnetic disturbances, and
I find that this method works out much more easily in the solution of
problems.
The other question will, I believe, be found to be ultimately of pre-
cisely the same nature. Start with the sphere A at rest, and the field
steady, and consider two external points, P and P', at different distances.
The electric force at them has different values, and the whole field has
a potential. But now give the sphere a displacement, and bring it to
rest again in a new position. Is the readjustment of potential instan-
taneous 1 I should say, Certainly not, and describe what happens thus.
When the sphere is moved, magnetic force is generated at its boundary
(lines circles of latitude, if the axis be the line of motion), and with it
there is necessarily disturbance of electric force. The two together
make an electromagnetic wave, which goes out from the sphere at the
speed of light, and at the front of the wave we have E = f^vH, where E
is the electric and H the magnetic force intensity. Before the front
reaches P or P' we have the electric field represented by the potential
function, but after that it cannot be so represented until the magnetic
force has wholly disappeared, when again we have a steady field repre-
sentable by a potential function. It is difficult to see how to plainly
differentiate any propagation of potential per se.
If the motion is simple-harmonic, there is a train of outward waves
and no potential. I imagine that an electroscope, if infinitely sensitive
and without reactions, would register the actual state of the electric
field, irrespective of its steadiness. By an electroscope, as this is a
purely theoretical question, I understand the very simplest one, a very
small charge at a point ; or, say, the unit charge, the force on which is
the electric force of the field.
When these things are closely examined into, if the facts as regards
the propagation of disturbances (electric and magnetic) are agreed on,
the only subject of question is the best mode of expressing them, which
I believe to be in terms of the forces, not potentials.
But there really is infinite speed of propagation of potential sometimes ;
492 ELECTRICAL PAPERS.
on examination, however, it is found to be nothing more than a mathe-
matical fiction, nothing else being propagated at the infinite speed.
It will be understood that I preach the gospel according to my inter-
pretation of Maxwell, and that any modification his theory of the
dielectric may receive may involve a fresh kind of propagation at pre-
sent not in question.
Nov. 5, 1888.
PART II.
The question raised by Prof. S. P. Thompson (in The Electrician,
Nov. 16, 1888, p. 54) as to whether the motion of an uncharged
dielectric through a field of electric force produces magnetic effects
must, I think, be undoubtedly answered in the affirmative. As the
distribution of displacement varies, its time-variation is the electric
current, with determinable magnetic force to match. When the speed
of motion is a small fraction of that of light, we may regard the
displacement as having at every moment its proper steady distribution,
so that there is no difficulty in estimating the magnetic effects, except,
it may be, of a merely mathematical character. For instance, the case
of a sphere moving in a field which would be uniform were the sphere
absent, may be readily attacked, and does perfectly well to illustrate
the general nature of the action.
But if the moved dielectric have the same electric permittivity as
the surrounding medium, so that there is no difference made in the
steady distribution, the question which may be now raised as to the
possible production of transient disturbances is one to which the above
theory does not present any immediate answer. I believe that the
body will be magnetized transversely to the electric displacement and
the velocity. [The motional magnetic force is referred to.]
Another question, somewhat connected, is contained in Prof. Poynt-
ing's suggestion (in letter to Prof. Lodge, The Electrician, p. 829, vol.
xxi.) that electric displacement may possibly be produced without
magnetic force by the agency of pyroelectricity. But, whatever the
agency, it would, I conceive, be a new fact — quite outside Maxwell's
theory legitimately developed. We may have subsidence of electric
displacement without magnetic force; but I cannot see any way to
produce it.
But the main subject of this communication is the electromagnetic
effect of a moving charge. That a moving charge is equivalent to an
electric current-element is undoubted, and to call it a convection-
current. as Prof. S. P. Thompson does, seems reasonable. The true
current has three components, thus,
where H is the magnetic force, C the conduction-current, D the dis-
placement, and p the volume-density of electrification moving with
velocity u. The addition of the term pu is, I presume, the extension
made by Prof. Fitzgerald to which Prof. S. P. Thompson refers. At
any rate, I can at present see no other.
ELECTROMAGNETIC WAVES, ETC. 493
There are several ways of arriving at the conclusion that a moving
charge must be regarded as an electric current; but, when that is
admitted, we are very far from knowing what its magnetic effect is. No
cut-and-dried statement of it can be made, because it varies according to
circumstances. The magnetic field, whatever it be in a given case, is
not that of a current-element (supposing the charge to be at a point),
for that is anti-Maxwellian, but is that of the actual system of electric
current, which is variable.
Thus, in the case of motion at a speed which is a small fraction of
that of light, the magnetic field (as found by Prof. J. J. Thomson) is
the same as that of Ampere's current-element represented by pn ; that
is, a current-element whose direction is that of u and whose moment is
pu, if u is the tensor of u (understanding by "moment," current-density
x volume) ; but the true current to correspond bears the same relation
to the current-element as the induction of an elementary magnet bears
to its magnetic moment. The magnetic energy due to the motion of
a charge q upon a sphere of radius a in a medium of inductivity /*,
at a speed u which is only a very small fraction of that of light, is
expressed by J/^2w'2/a. But if the speed be not a small fraction of
that of light, the result is very different. Increasing the speed of
the charge causes not merely greater magnetic force but changes its
distribution altogether, and with it that of the electric field. It is no
use discussing the potential. There is not one. The magnetic field
tends to concentrate itself towards the equatorial plane, or plane
through the charge perpendicular to the line of motion. When the
speed equals that of light itself this process is complete, and the
is simply a plane wave (electromagnetic).
Since a charge at a point gives infinite values,
it is more convenient to distribute it. Let it be,
first, of linear density q along a straight line AB,
moving in its own line at the speed of light. Then
the field is contained between the parallel planes
through A and B perpendicular to AB, and is
completely given by
where E and H are the intensities of the electric
and magnetic forces at distance r from AB. The
lines of E radiate uniformly from AB in all direc-
tions parallel to the planes ; those of H are every-
where perpendicular to those of E, or are circles
centred upon AB. Outside this electromagnetic
wave there is no disturbance. I should remark that the above is a
description of the exact solution. It is, of course, nothing like the
supposed field of a current-element AB.
To still further realize, we may substitute a cylindrical distribution
for the linear, and then, again, terminate the lines of E on another
cylindrical surface between the bounding planes. To find the resulting
distributions of E and H (always perpendicular) may be done by super-
494 ELECTRICAL PAPERS.
imposition of the elementary solutions, or by solving a bidimensional
problem in a well-known manner.
Those who are acquainted with my papers in this journal will
recognise that what we have arrived at is simply the elementary
plane wave travelling along a distortionless circuit. All roads lead
to Rome !
Returning to the case of a charge q at a point moving through a
dielectric, if the speed of motion exceeds that of light, the disturbances
are wholly left behind the charge,
and are confined within a cone,
A<?B. The charge is at the apex,
moving from left to right along C^.
The semi-angle, 6, of the cone, or
the angle A$C, is given by
sin 6 = vlu,
where v is the speed of light, and u
that of the charge. The magnetic
lines are circles round the axis, or line of motion. The displacement
is away from q, of course, and of total amount q, but not uniformly
distributed within the cone. The electric current is towards q in the
inner part of the cone, and away from q in the outer.
It will be seen that the electric stress tends to pull the charge back.
Therefore, applied force on q in direction Cq is required to keep up the
motion. Its activity is accounted for by the continuous addition at
a uniform rate which is being made to the electric and magnetic
energies at q. For the motion at the wave-front, at any point on
A.q or B<?, is perpendicularly outward, not towards q. Whilst the cone
is thus expanding all over, the forward motion of q continually renews
the apex, and keeps the shape unchanged.
Steady motion alone is assumed.
To avoid misconception I should remark that this is not in any way
an account of what would happen if a charge were impelled to move
through the ether at a speed several times that of light, about which
I know nothing ; but an account of what would happen if Maxwell's
theory of the dielectric kept true under the circumstances, and if I have
not misinterpreted it. [See footnote on p. 516, later.]
Nov. 18, 1888.
PART III.
All disturbances being propagated through the dielectric ether at the
speed of light, when, therefore, a charge is in motion through the
medium, the discussion of the effects produced naturally involves the
consideration of three cases, those in which the speed u of the charge is
less than, or equal to, or greater than v, that of light.
In a previous communication [Part II. above], I gave the complete
and very simple solution of the intermediate case of equality of speeds.
A formal demonstration is unnecessary, as the satisfaction of the
necessary conditions may be immediately tested.
ELECTROMAGNETIC WAVES, ETC. 495
But I was not then aware that the case u < v admitted of being pre-
sented in a nearly equally-simple form. That such is the fact is rather
surprising, for it is very exceptional to arrive at simple results, and
these now in question are sufficiently free from complexity to take a
place in text-books of electricity.
Let the axis of z be the line of motion of the charge q at speed u.
Everything is symmetrical with respect to this axis. The lines of
electric force are radial out from the charge. Those of magnetic force
are circles about the axis. The two forces are perpendicular. Having
thus settled the directions, it only remains to specify their intensities
at any point P distant r from the charge, the line r making an angle 6
with the axis. Let E be the intensity of the electric, and H of the
magnetic force. Then, if c is the permittivity and ^ the inductivity,
such that /Jicv2— 1, we have
cE =
-S-
H=cEusiu 0.
That (A), (B) represent the complete solution may be proved by
subjecting them to the proper tests. Premising that the whole system
is in steady motion at speed u, we have to satisfy the two fundamental
laws of electromagnetism : —
(1). (Faraday's law). The electromotive force of the field [or voltage]
in any circuit equals the rate of decrease of the induction through the
circuit (or the magnetic current x - 47r).
(2). (Maxwell's law). The magnetomotive force of the field [or
gaussage] in any circuit equals the electric current x 4?r through the
circuit.
Besides these, there is continuity of the displacement to be attended
to. Thus :—
(3). (Maxwell). The displacement outward through any surface
equals the enclosed charge.
Since (A) and (B) satisfy these tests, they are correct. And since no
unrealities are involved, there is no room for misinterpretation.
When u/v is very small, we have, approximately,
representing Prof. J. J. Thomson's solution — that is, the lines of dis-
placement radiate uniformly from the charge, and the magnetic force is
that of the corresponding displacement-currents together with the
moving charge regarded as a current-element of moment qu. Instant-
aneous action through the medium is involved — that is, to make the
solution quite correct.
That the lines of electric force should remain straight as the speed of
the charge is increased is itself a rather remarkable result. Examining
496 ELECTRICAL PAPERS.
(A), we see that the effect of increasing u is to concentrate the displace-
ment about the equatorial plane 0 = j7r. Self-induction does it. In
the limit, when u = v, the numerator vanishes, making E = Q, H=0
everywhere except at the plane mentioned, where, by reason of the
denominator becoming infinitely small in comparison with the numer-
ator, the displacement is all concentrated in a sheet, and with it the
induction, forming a plane electromagnetic wave, as described (and
realized) in my previous communication.
If we terminate the field described in (A) and (B) on a spherical
surface of radius a, instead of continuing it up to the charge q at the
origin, we have the case of a perfectly conducting sphere of radius a
possessing a total charge <?, moving steadily at speed u through the
dielectric ether. As the speed is increased to v, the charge all accumu-
lates at the equator of the sphere. [See footnote on p. 514, later.]
But after that 1 This brings us to the third case of u > v, and here
I have so-far failed to find any solution which will satisfy all the neces-
sary conditions without unreality. The description at the close of
Part II. must therefore be received as a suggestion, at present uncon-
firmed. I hope to consider the matter in a future communication.
P.S. — In a recent number Mr. W. P. Granville raised the question of
action through a medium being only action at a short distance instead
of a long one, and asked for instruction. His inquiry has elicited no
response. This is not, however, because there is nothing to be said
about it. The matter did not escape the notice of the " anti-distance-
action sage." My own opinion is that the question involved is, if not
metaphysical, dangerously near to being so ; consequently, whole books
might be devoted to it. At present, however, I think it is more useful
to try to find out what happens, and to construct a medium to make it
happen ; after that, perhaps, the matter referred to may be more
advantageously discussed. The well of truth is bottomless.
PART IV.
In previous communications [above] I have discussed this matter.
Referring to the case of steady rectilinear motion, I gave a description
of the result when the speed of the charge exceeds that of light, obtained
mainly by general reasoning, and stated my inability to find a solution
to represent it. The displacement cannot be outside a certain cone of
semi-vertical angle whose sine equals the ratio v/u of the speed of light
to that of the charge, which is at the apex.
In the Phil. Mag. for July, 1889, Prof. J. J. Thomson has examined
this question. Like myself, he fails to find a solution within the cone ;
but concludes that the displacement is confined to its surface. If so, it
must form, along with the magnetic induction, an electromagnetic wave.
But it may be readily seen that such a wave is impossible, having no
stability.
For as the charge moves from A to B, a given surface-element, C,
would move to D. In doing so its area would vary directly as its
distance from the apex, and the energy in the element would therefore
ELECTROMAGNETIC WAVES, ETC. 497
vary inversely as its distance from the apex, and the forces, electric
and magnetic, would therefore vary inversely as the square root of the
distance from the apex, instead of inversely as the distance, which is
obviously necessary in order that the
displacement may be confined to the
surface. This conflict of conditions
constitutes instability. In the Phil.
Mag. for April, 1889, I suggested
that whilst there must be a solution
of some kind, one representing a
stead)/ state was impossible. This
conclusion is confirmed by the failure of Prof. Thomson's proposed
surface- wave to keep itself going.
Prof. Thomson, who otherwise confirms my results, has also extended
the matter by supposing that the medium itself is set in motion, as well
as the electrification. This is somewhat beyond me. I do not yet
know certainly that the ether can move, or its laws of motion if it can.
Fresnel thought the earth could move through the ether without dis-
turbing it ; Stokes, that it carried the ether along with it, by giving
irrotational motion to it. Perhaps the truth is between the two. Then
there is the possibility of holes in the ether, as suggested by a German
philosopher. When we get into one of these holes, we go out of
existence. It is a splendid idea, but experimental evidence is much
wanting.
But if we consider that the medium supporting the electric and
magnetic fluxes is really set moving when a body moves, and assume a
particular kind of motion, it is certainly an interesting scientific ques-
tion to ask what influence the motion exerts on the electromagnetic
phenomena. I do not, however, think that any new principles are
involved.
The general connections of E and H, referred to fixed space without
conductivity, being
curl(e-E) = /^H, .............................. (1)
curl(H-h)=cpE, .............................. (2)
where p stands for d/dt and e and h are the impressed parts of E and H ;
if there is also motion of electrification, we have to consider it to con-
stitute a convection-current, a part of the true current, and so make (2)
become
........................ (3)
where p is the density of electrification, whose velocity is u. [See Part
II.] It now remains to specify e and h. They are zero when the
medium supporting the fluxes is at rest. But if it moves, and its
velocity is w, there is, first, the electric force due to motion in a
e-fVwH, ................................ (4)
which is well known : and next the magnetic force due to motion in an
electric field, h = oVEw, ............................... (5)
H.E.P.— VOL. II. 2 I
498 ELECTRICAL PAPERS.
which is not so well known. (First, I believe, given by me in the third
Section of "Electromagnetic Induction and its Propagation," The
Electrician, January 24, 1885 [vol. I., p. 446] ; again, obtained in a
different way in Section XXIL, January 15, 1886 [vol. I., p. 546]; see
also Phil. Mag., August, 1886 [vol. II., Art. L.], and an example of the
use of (4) and (5) in The Electrician, April 12, 1889, p. 683 [vol. II.,
Art. LI.].)
The mechanical force called by Maxwell the "electromagnetic force"
is VCB, where C is the true current and B the induction. It is the
force on the matter supporting electric current. Let it move. If w is
its velocity, the activity of the force is
wVCB = CVBw= -eC (6)
Similarly, as I obtained in Section xxn. above referred to, there is a
mechanical force (the magneto-electric) on matter supporting magnetic
current G = /xpH/47r, expressed by 4?rVDG, and its activity is
47TWVDG = 47rGVwD = -hG (7)
Of course e and h. are reckoned as impressed forces, which is the reason
of the change of sign. Their activities are eC and hG.
It should be remarked further, that the above expressions for e
and h are not certain. For I have shown that the sources of all
disturbances are the lines of curl of the impressed forces (Phil. Mag.,
Dec., 1887) [vol. n., p. 362], and that the fluxes produced depend
solely upon the curls of e and h, both as regards the steady fluxes
and the variable ones leading to them. We may, therefore, use any
other expressions for e and h which have the same curls as the
above. And, in fact, we see that equations (1) and (2) only contain
their curls.
Equations (1) and (3), with e and h defined by (4) and (5), therefore
enable us to determine the effect of the moving medium. Prof.
Thomson also arrives at (4) and (5), and at the " magneto-electric
force," in his paper to which I have referred, by an entirely different
method. And to show how well things fit together, he concludes, from
the consideration of the moving medium, that a moving electrified
surface is a current-sheet, which is another way of saying that a convec-
tion current is a part of the true current, as expressed in (3). I must,
however, disagree with Prof. Thomson's assumption that the motion
must be irrotational. It would appear, by the above, that this limita-
tion is unnecessary.
As an example, and to introduce a new point, take the case of a charge
q moving at speed u along the axis of z. It will come to the same thing
if we keep the charge at rest, and move the medium the other way.
We then use the equations (1) and (2), and in them use (4) and (5)
with w = - u. Now when the steady state is arrived at, we have p = 0,
so (1) and (2) become
curl(/>iVHu-E) = 0, (8)
curl(H-cVuE) = 0 (9)
ELECTROMAGNETIC WAVES, ETC. 499
In addition, the divergence of D must be q at the origin, and the
divergence of B must be zero. The latter gives, applied to (9),
H = cVuE, (10)
which gives H fully in terms of E. Eliminate H from (8) by means of
(10), and we get
curl(/xcVuVEu-E) = 0, (11)
or curl nC(E-£sk>)-En=0, (12)
where E$ is the ^-component of E and k a unit vector along z ; or, inte-
grating, and writing the three components,
„ dP dP /, u*\dP
where P is a scalar potential. Here is the new point. There is a
potential, of a peculiar kind. The displacement due to the moving
charge is distributed in precisely the same way as if it were at rest in an
eolotropic medium, whose permittivity is c in all directions transverse to
the line of motion, but is smaller, viz., c(l -v?/v2), along that line and
parallel to it. The potential P is given by
(H)
It is a particular case of eolotropy. In general, clt c2, c3, the prin-
cipal permittivities, are all unequal. Then, with q at the origin, the
potential is
..... (15)
Observe that although the electric force in the substituted problem
of a charge at rest in an eolotropic medium is the slope of a potential ;
yet it is not so when the medium is isotropic, and moves past the fixed
charge, or vice versa, although the distributions of displacement are the
same.
When u = v, we abolish the permittivity along the 2-axis in the
substituted case, so that the displacement must be wholly transverse.
We then have the plane electromagnetic wave. When u is greater than
v it makes the permittivity negative along z ; this is an impossible
electrical problem, and furnishes another reason for supposing that
there can be no steady state in the corresponding electromagnetic
problem.
It now remains to find what would happen if electrification were con-
veyed through a medium faster than the natural speed of propagation
of disturbances. There is the cone ; but what takes place within it ?
Aug. 25, 1889.
500 ELECTRICAL PAPERS.
XLVIII. THE MUTUAL ACTION OF A PAIR OF RATIONAL
CURRENT-ELEMENTS.
[The Electrician, Dec. 28, 1888, p. 229.]
STRICTLY speaking, there is no such thing, from the Maxwellian point
of view, as mutual action between current elements. Suppose, however,
we have the well-known Amperian field of magnetic force usually
ascribed to a current-element at one place, and a similar one centred at
another place, it is clear that the forces concerned are quite definite,
according to Maxwell's theory. The electric current of such an arrange-
ment is closed. It is related to the nominal current, viz., in the
element, in the same way as the induction of an elementary magnet is
related to its magnetic moment, as regards the space-distribution. We
may term the arrangement a rational current-element. If we take any
number of equal rational current-elements and put them in line, with
opposite poles in contact, only the terminal poles are left free, so that
the current consists of a straight or curved line or tube of current,
joining two points, A and B, with external continuity produced by
means of an equal current diverging
from the positive pole B in all directions
uniformly, and converging to the nega-
tive pole A in a similar manner. Of
course the tubes of current from B join
on to those at A, and are curved ; but
it would only confuse matters to super-
impose the two systems of polar current,
which are much better kept separate.
The rational current-element itself is
to be regarded as an infinitely small
volume with a uniform current distributed in it, and of the com-
plementary currents from and to the poles. The moment is current-
density multiplied by volume, ignoring the complementary currents
altogether for the moment. What the actual current in the element
may be does not matter much. It depends on the shape of the element.
Thus, if spherical, the nominal strength of current, reckoned by its
moment, is half as great again as the real, owing to the back action of
the polar current. We need only consider the moment, which is fully
representative of the external magnetic field, which, it should be
remembered, is that due to the moment, according to Ampere's rule.
To further illustrate, take the case of a charge, q, moving at speed u,
small compared with that of light [p. 495, vol. II.], through a dielectric.
The moment is qu ; the magnetic force is qu/r2 at distance r in the
equatorial plane, and elsewhere proportional to the cosine of the
latitude. The actual state of things in the element may require very
complex calculations to discover, but is of little importance.
The mutual action of two German or irrational current-elements is
indeterminate, and so we get a large number of so-called theories of
electrodynamics. But the mutual action of a pair of rational current-
THE MUTUAL ACTION OF CURRENT-ELEMENTS. 501
elements is a legitimate subject of inquiry, is determinate, and does not
involve any action at a distance. The quantity from which, by
dynamical methods, we derive the forces (mechanical) on the elements,
is the mutual magnetic energy (leaving out of consideration the electro-
static force, if any), that part of the magnetic energy due to both rational
current-elements. If I have correctly calculated it, the mutual energy
M of elements whose distance apart is r, in the medium of inductivity
/*, is expressed by
where u^ u2, u3 are the components of Gv the moment of the first
element, and vv v2, v3 those of the second, C2, on the understanding
that the axis of x is the line
joining the elements, whilst
the y and z axes are, as usual,
perpendicular to it and to each
other. In another form,
KT— /COS€ i i cPr
\ r 2dslds^
where e is the inclination of
the elements Cj and C2, parallel
to 8l and S2.
If we substitute for r, in the
differential coefficient, an arbitrary function R, we obtain the most
general formula which will lead to Neumann's result for closed circuits.
It is this R that is, by German methods, indeterminate, nationalize
the elements, and we fix it to be r. Clausius took R = 0, I believe. It
does not matter at all, so far as closed circuits are concerned, what
formula we use, provided Neumann's result is complied with ; but it is
interesting to observe that the problem as stated by me has no un-
certainty about it (except any possible working errors) and makes M
definite, whilst it is not a mere mathematical abstraction (i.e., the
problem), but representative of (under certain circumstances) a reality.
It is for these reasons that I mention the matter. For, as a matter of
fact, I believe the whole method is fundamentally wrong, and of little
practical service in the investigation of electromagnetism from the
physical side, i.e., with propagation in time through a medium. What
does it matter about the current-elements ? They are not in it. Still,
such formulas are sometimes of service, as, for instance, in the calcula-
tion of inductances.
It has been stated, on no less authority than that of the great
Maxwell, that Ampere's law of force between a pair of current-elements
is the cardinal formula of electrodynamics. If so, should we not be
always using it ? Do we ever use it ? Did Maxwell, in his treatise ?
Surely there is some mistake. I do not in the least mean to rob
Ampere of the credit of being the father of electrodynamics ; I would
only transfer the nameTof cardinal formula to another due to him,
502 ELECTRICAL PAPERS.
expressing the mechanical force on an element of a conductor support-
ing current in any magnetic field ; the vector product of current and
induction. There is something real about it ; it is not like his force
between a pair of unclosed elements ; it is fundamental ; and, as every-
body knows, it is in continual use, either actually or virtually (through
electromotive force) both by theorists and practicians.
Nov. 25, 1888.
XLIX. THE INDUCTANCE OF UNCLOSED CONDUCTIVE
CIRCUITS.
IN my communication on "The Mutual Action of Rational Current-
Elements" [the last Art. XLVIIL] I described 'the meaning of, and gave
the formula for, the mutual energy M of a pair of rational current-
elements.
Thus, let G^ and C2 be their moments, r their distance apart, e the
angle between their directions Sj and S2, ^ the magnetic inductivity of
the medium (uniform), and M the mutual energy. Then,
(1)
It follows immediately from this that the mutual inductance of any
two linear circuits is
M being now the mutual inductance. If the circuits are closed the
second part contributes nothing, and we have
(3)
the common form of Neumann's equation, with the /x prefixed to adapt
it to Maxwell's theory.
But if the lines are unclosed, then, according to my description of the
nature of a rational current-element, the linear currents become closed
by means of currents uniformly diverging from their positive ends, and
uniformly converging to their negative ends. The second part of (2) is
now finite. Let Pt and P2 be the positive poles, Nj and N2 the negative
poles of the linear currents, and let the value of the second part of (2)
be Mv It is given by
P^VN^), ................. (4)
where PXN2 means the length of the straight line joining PT to N2, and
similarly for the rest. We may, therefore, calculate M by Neumann's
formula, applied to the linear circuits, and then add the correction (4)
to obtain the complete expression.
INDUCTANCE OF UNCLOSED CONDUCTIVE CIRCUITS. 503
A practical application is to the theory of a Hertzian oscillator, at
least of a certain kind. Let a straight wire join two conducting spheres,
or discs, etc. Imagine an impressed force to act in the wire, and to
vary in any not too rapid manner. The current will leak out (or in)
from (or to) the wire as well as the terminal conductors, but if they are
relatively large nearly all the current will go across the air from one
terminal conductor to the other, and we may ignore the wire-leakage.
The permittance S is then that of the dielectric between the two spheres
(say), and is quite definite. Also, if the changes of current are not too
rapid, as mentioned, the current in the air will follow the lines or tubes
of displacement. The inductance L is therefore also quite definite, in
accordance with Maxwellian principles, so that the natural frequency of
oscillation of the condenser-conductor circuit can be calculated with
considerable precision from the dimensions.
If, as an illustrative approximation, we suppose the current to come
from the centre of one sphere and go to that of the other, and then
diverge or converge uniformly, we have to find the inductance L of &
straight wire or tube of length / and radius a, with terminal continua-
tions as before specified. In the Phil. Mag., July, 1888, Prof. Lodge
calculates L without any allowance for the current in the dielectric, viz.,
by Neumann's formula (3). We have therefore only to examine what
the correction (4) amounts to.
In the case of two very close parallel lines, we may put
PjPa^ 0 = ]^, and P^, = P^ = /,
so that the correction is simply - //A. That is, if the dielectric current
is ignored, (3) overestimates M by the amount pi. The same applies
when it is the inductance of a straight tube or solid wire that is in
question. Deduct its length in centimetres from the uncorrected to
obtain the true value, in c.g.s. electromagnetic units, i.e., centimetres.
Prof. Lodge (loc. cit.) also gives the formula which Hertz says Max-
well's theory gives. On making the comparison, I find it is equivalent
to adding, instead of deducting I, from the result of Neumann's formula.
It should be remarked, as an essential condition of the validity of the
process described above, when practically applied, that the changes of
current must not be too rapid. When the changes are slow the im-
mense speed of propagation of disturbances through the air causes the
electric displacement at any moment in the neighbourhood of the
vibrator to be very nearly that which would obtain according to electro-
static principles, and the current to follow the tubes of displacement.
But go to the other extreme, and imagine the changes to be so rapid
that waves, whose length is a fractional part of the length of the
vibrator, are produced. It is then clear that the theory would not
apply at all, either as regards the inductance or the permittance. Now
Hertz, in that series of brilliant experiments which have gone far
towards practically establishing the truth of Maxwell's inimitable
theory of the ether considered as a dielectric, sometimes employs waves
which are not very much longer than the vibrator itself. Only close to
the vibrator, therefore, do we have the electrostatic field (approximately)
504 ELECTRICAL PAPERS.
predominant, and we may expect a sensible error in applying the electro-
static theory. It is, however, quite easy — in fact, easier — to use longer
waves. But in any case, the exact calculation of the permittance and
inductance of a vibrator involves a good deal of mathematics to find
relatively small corrections.
July 21, 1889.
L. ON THE ELECTROMAGNETIC EFFECTS DUE TO THE
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC.
[Phil. Mag., April, 1889, p. 324.]
Theory of the Slow Motion of a Charge.
1. THE following paper consists of, First, a short discussion of the
theory of the slow motion of an electric charge through a dielectric,
having for object the possible correction of previously published results.
Secondly, a discussion of the theory of the electromagnetic effects due
to motion of a charge at any speed, with the development of the com-
plete solution in finite form when the motion is steady and rectilinear.
Thirdly, a few simple illustrations of the last when the charge is
distributed.
Given a steady electric field in a dielectric, due to electrification. It
is sufficient to consider a charge q at a point, as we may readily extend
results later. If this charge be shifted from one position to another,
the displacement varies. In accordance, therefore, with Maxwell's
inimitable theory of a dielectric, there is electric current produced. Its
time-integral, which is the total change in the displacement, admits of
no question ; but it is by no means an elementary matter to settle its
rate of change in general, or the electric current. But should the speed
of the moving charge be only a very small fraction of that of the pro-
pagation of disturbances, or that of light, it is clear that the accommo-
dation of the displacement to the new positions which are assumed by
the charge during its motion is practically instantaneous in its neighbour-
hood, so that we may imagine the charge to carry about its stationary
field of force rigidly attached to it. This fixation of the displacement
at any moment definitely fixes the displacement-current. We at once
find, however, that to close the current requires us to regard the moving
charge itself as a current-element, of moment equal to the charge
multiplied by its velocity ; understanding by moment, in the case of a
distributed current, the product of current-density and volume. The
necessity of regarding the moving charge as an element of the "true
current" may be also concluded by simply considering that when a
charge q is conveyed into any region, an equal displacement simul-
taneously leaves it through its boundary.
Knowing the electric current, the magnetic force to correspond
becomes definitely known if the distribution of inductivity be given ;
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 505
and when this is constant everywhere, as we shall suppose now and
later, the magnetic force is simply the circuital vector whose curl
is 4 TT times the electric current; or the vector-potential of the curl of
the current; or the curl of the vector-potential of the current, etc., etc.
Thus, as found by J. J. Thomson,* the magnetic field of a charge
moving at a speed which is a small fraction of that of light is that
which is commonly ascribed to a current-element itself. I think it,
however, preferable to regard the magnetic field as the primary object
of attention ; or else to regard the complete system of closed current
derived from it by taking its curl as the unit, forming what we may
term a rational current-element, inasmuch as it is not a mere mathe-
matical abstraction, but is a complete dynamical system involving
definite forces and energy.
2. Let the axis of z be the line of motion of the charge q at the speed
u ; then the lines of magnetic force H are circles centred upon the axis,
in planes perpendicular to it, and its tensor H at distance r from the
charge, the line r making an angle 6 with the axis, is given by
........................... (1)
where v = sin 0, E the intensity of the radial electric force, c the per-
mittivity such that /x0cv2 = l, if /x0 is the other specific quality of the
medium, its inductivity, and v is the speed of propagation.
Since, under the circumstance supposed of u/v being very small, the
alteration in the electric field is insensible, and the lines of E are radial,
we may terminate the fields represented by (1) at any distance r = a
from the origin. We then obtain the solution in the case of a charge q
upon the surface of a conducting sphere of radius a, moving at speed u.
This realization of the problem makes the electric and magnetic energies
finite. Whilst, however, agreeing with J. J. Thomson in the funda-
mentals, I have been unable to corroborate some of his details; and
since some of his results have been recently repeated by him in another
place,! it may be desirable to state the changes I propose, before pro-
ceeding to the case of a charge moving at any speed.
The Energy and Forces in the Case of Slow Motion.
3. First, as regards the magnetic energy, say T. This is the space-
summation 2/x0JT2/87r; or, by
The limits are such as include all space outside the sphere r = a. The
coefficient | replaces T2¥.
4. Next, as regards the mutual magnetic energy M of the moving
charge and any external magnetic field. This is the space-summation
* Phil. Mag., April, 1881.
t " Applications of Dynamics to Physics and Chemistry," chap, iv., pp. 31 to 37.
J The Electrician, Jan. 24, 1885, p. 220 [vol. i., p. 446].
506 ELECTRICAL PAPERS.
2 /A0H0H/47r, if H0 is the external field ; and, by a well-known trans-
formation, it is equivalent to 2A0F, if A0 is any vector whose curl is
^0H0, whilst F is the current-density of the moving system. Further,
if we choose A0 to be circuital, the polar part of T will contribute
nothing to the summation, so that we are reduced to the volume-
integral of the scalar product of the circuital A0 of the one system
and the density of the convection- current in the other. Or, in the
present case, with a single moving charge at a point, we have simply
the scalar product A0u<? to represent the mutual magnetic energy ; or
^~=A0u?, ................................. (3)
which is double J. J. Thomson's result.
5. When, therefore, we derive from (3) the mechanical force on the
moving charge due to the external magnetic field, we obtain simply
Maxwell's "electromagnetic force" on a current-element, the vector
product of the moment of the current and the induction of the external
field ; or if F is this mechanical force,
F = MVuH0, .............................. (4)
which is also double J. J. Thomson's result. Notice that in the appli-
cation of the "electromagnetic force" formula, it is the moment of the
convection-current that occurs. This is not the same as the moment of
the true current, which varies according to circumstances ; for instance,
in the case of a small dielectric sphere uniformly electrified throughout
its volume, the moment of the true current would be only f of that of
the convection-current.
The application of Lagrange's equation of motion to (3) also gives
the force on q due to the electric field so far as it can depend on M ;
that is, a force _ ^
where the time-variation due to all causes must be reckoned, except
that due to the motion of q itself, which is allowed for in (4). And
besides this, there may be electric force not derivable from A0, viz.
where ^ is the scalar potential companion to A0.
6. Now if the external field be that of another moving charge, we
shall obtain the mutual magnetic energy from (3) by letting A0 be the
vector-potential of the current in the second moving system, constructed
so as to be circuital. Now the vector-potential of the convection-
current qu is simply qu/r ; this is sufficient to obtain the magnetic force
by curling; but if used to calculate the mutual energy, the space-
summation would have to include every element of current in the other
system. To make the vector-potential circuital, and so be able to
abolish this work, we must add on to qu/r the vector-potential of the
displacement current to correspond. Now the complete current may be
considered to consist of a linear element qu having two poles ; a radial
current outward from the + pole in which the current-density is qu/4:irr?;
and a radial current inward to the - pole, in which the current-density
is - qu/^Trrj ; where rl and rz are the distances of any point from the
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 507
poles. The vector-potentials of these currents are also radial, and their
tensors are \qu and - \qu. We have now merely to find their resultant
when the linear element is indefinitely shortened, add on to the former
<?u/r, and multiply by /x0, to obtain the complete circuital vector-
potential of qu, viz. : —
........................... (5)
where r is the distance from q to the point P when A is reckoned, and
the differentiation is to s, the axis of the convection-current. Both it
and the space-variation are taken at P. The tensor of u is u. Though
different and simpler in form (apart from the use of vectors) this vector-
potential is, I believe, really the same as the one used by J. J. Thomson.
From it we at once find, by the method described in § 4, the mutual
energy of a pair of point-charges ql and <?2, moving at velocities Uj and U2,
to be
(«)
when at distance r apart. Both axial differentiations are to be effected
at one end of the line r.
As an alternative form, let e be the angle between Uj and U2, and let
the differentiation to sl be at dsv that to s2 at ds2, as in the German
investigations relating to current-elements ; then *
Another form, to render its meaning plainer. Let Ap fj,v v1 and
A2, /A2, v2 be the direction-cosines of the elements referred to rectangular
axes, with the z-axis, to which Ax and A2 refer, chosen as the line
joining the elements. Thenf
2 2 ) ................ (8)
J. J. Thomson's estimate is \
K-lHMW*^ ................................ (9)
Comparing this with (8), we see that there is a notable difference.
7. The mutual energy being different, the forces on the charges, as
derived by J. J. Thomson by the use of Lagrange's equations, will be
different. When the speeds are constant, we shall have simply the
before-described vector product (4) for the "electromagnetic force"; or
.............. (10)
if Fj is the electromagnetic force on the first, and F2 that on the second
element, whilst Hj and H2 are the magnetic forces. Similar changes are
needed in the other parts of the complete mechanical forces.
* The Electrician, Dec. 28, 1888, p. 230 [p. 501, vol. u.].
f The Electrician, Jan. 24, 1885, p. 221 [vol. I., p. 446].
£ "Applications of Dynamics to Physics and Chemistry," chap. iv. ; and Phil.
Mag., April, 1881.
508 ELECTRICAL PAPERS.
It may be remarked that (if my calculations are correct) equation (7)
or its equivalents expresses the mutual energy of any two rational
current-elements (see § 1) in a medium of uniform inductivity, of
moments q^ and q2u2, whether the currents be of displacement, or
conduction, or convection, or all mixed, it being in fact the mutual
energy of a pair of definite magnetic fields. But, since the hypothesis
of instantaneous action is expressly involved in the above, the application
of (7) is of a limited nature.
General Theory of Convection Currents.
8. Now leaving behind altogether the subject of current-elements, in
the investigation of which one is liable to be led away from physical
considerations and become involved in mere exercises in differential
coefficients, and coming to the question of the electromagnetic effects of
a charge moving in any way, I have been agreeably surprised to find
that my solution in the case of steady rectilinear motion, originally an
infinite series of corrections, easily reduces to a very simple and interest-
ing finite form, provided u be not greater than v. Only when u > v is
there any difficulty. We must first settle upon what basis to work.
First the Faraday-law (p standing for d/dt),
-curlE = /v?H, (11)
requires no , change when there is moving electrification. But the
analogous law of Maxwell, which I understand to be really a definition
of electric current in terms of magnetic force, (or a doctrine), requires
modification if the true current is to be
C+pD + /ou; (12)
viz., the sum of conduction-current, displacement-current, and convec-
tion-current pu, where p is the volume-density of electrification. The
addition of the term />u was, I believe, proposed by G. F. Fitzgerald.*
(This was not meant exactly for a new proposal, being in fact after
Rowland's experiments; besides which, Maxwell was well acquainted
with the idea of a convection-current. But what is very strange is that
Maxwell, who insisted so strongly upon his doctrine of the quasi-
incompressibility of electricity, never formulated the convection-current
in his treatise. Now Prof. Fitzgerald pointed out that if Maxwell, in
his equation of mechanical force,
F = VCB - eW - raVft,
had written E for - V*P, as it is obvious he should have done, then the
inclusion of convection-current in the true current would have followed
naturally. (Here C is the true current, B the induction, e the density
of electrification, m that of imaginary magnetic matter, "*" the electro-
static and ft the magnetic potential, and E the real electric force.)
Now to this remark I have to add that it is as unjustifiable to derive
H from ft as E from *¥ ; that is, in general, the magnetic force is not
the slope of a scalar potential ; so, for - Vft we should write H, the real
magnetic force.
* Brit. Assoc., Southport, 1883.
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 509
But this is not all. There is possibly a fourth term in F, expressed
by 47rVDG, where D is the displacement and G the magnetic current ;
I have termed this force the " magneto-electric force," because it is the
analogue of Maxwell's "electromagnetic force," VCB. Perhaps the
simplest way of deriving it is from Maxwell's electric stress, which was
the method I followed.*
Thus, in a homogeneous nonconducting dielectric free from electri-
fication and magnetization, the mechanical force is the sum of the
"electromagnetic" and the "magnetoelectric," and is given by
F_ 1 dW
?~3P
where W = VEH/4?r is the transfer-of-energy vector.
It must, however, be confessed that the real distribution of the
stresses, and therefore of the forces, is open to question. And when
ether is the medium, the mechanical force in it, as for instance in a
light-wave, or in a wave sent along a telegraph-circuit, is not easily to
be interpreted.)
The companion to (11) in a nonconducting dielectric is now
curlH = cpE + 47rpu ................... . ........ (13)
Eliminate E between (11) and (13), remembering that H is circuital,
because /x0 is constant, and we get
Q?>2-V2)H = curl4izy>u, ........................ (14)
the characteristic of H. Here V2 = d2/dx2 + ..., as usual.
Comparing (14) with the characteristic of H when there is impressed
force e instead of electrification />, which is
we see that />u becomes cpe/47r. We may therefore regard convection-
current as impressed electric current. From this comparison also, we
may see that an infinite plane sheet of electrification of uniform density
cannot produce magnetic force by motion perpendicular to its plane.
Also, we see that the sources of disturbances when p is moved are the
places where /ou has curl ; for example, a dielectric sphere uniformly
filled with electrification (which is imaginable), when moved, starts the
magnetic force solely upon its boundary.
The presence of "curl" on the right side tells us, as a matter of
mathematical simplicity, to make H/curl the variable. Let
H = curlA, ................................. (15)
and calculate A, which may be any vector satisfying (15). Its
characteristic is
Q?2/*>2-V2)A = 47r/>u ............................ (16)
The divergence of A is of no moment, and it is only vexatious compli-
cation to introduce ^F. The time-rate of decrease of A is not the real
*"E1. Mag. Ind. and its Prop." xxn. The Electrician, Jan. 15, 1886, p. 187
[vol. i., p. 545].
510 ELECTRICAL PAPERS.
distribution of electric force, which has to be found by the additional
datum
divcE = 47i7>, ............................... (17)
where E is the real force.
9. " Symbolically " expressed, the solution of (16) is
47TPU _-47T/)U/V2
Here the numerator of the fraction to the right is the vector-potential of
the convection-current. Calling it A0, we have
Inserting in (18) and expanding, we have
.................. (20)
Given then /ou as a function of position and time, A0 is known by (19),
and (20) finds A, whilst (15) finds H.
Complete Solution in the Case of Steady Rectilinear Motion. Physical
Inanity of "*&.
10. When the motion of the electrification is all in one direction, say
parallel to the s-axis, u, A0, and A are all parallel to this axis, so that
we need only consider their tensors. When there is simply one charge
q at a point, we have
A = ur
and (20) becomes
(21)
at distance r from q. When the motion is steady, and the whole electro-
magnetic field is ultimately steady with respect to the moving charge,
we shall have, taking it as origin,
p = -u(d/dz) = -uD,
for brevity ; so that
(22)
Now the property W+a = (n + 2)(w + 3)r" ........................ (23)
brings (22) to ^ = ^i + g^ + ^+...}; ................. (24)
and the property DZnr2n~l = l*.32.5*...(2w- l)V/r, ............... (25)
where v = sin 6, 0 being the angle between r and the axis, brings (24) to
' ....... <26>
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 51 1
which, by the Binomial Theorem, is the same as
A = (qulr){l-u*v*l<#Y\ ....................... (27)
the required solution.
11. To derive //, the tensor of the circular H, let rv = h, the distance
from the axis. Then, by (15),
.-T (28)
dh dr r dp r2 \ rdp) V v2 )
by (27), if /z = cos#. Performing the differentiation, and also getting
out E, the tensor of the electric force, we have the final result that the
electromagnetic field is fully given by *
cE=*. l-*/**t> H=cEuv, ............... (29)
r'2 (1 -«**/«*)*
with the additional information that E is radial and H circular.
Now, as regards ^, if we bring it in, we have only got to take it out
again. When the speed is very slow we may regard the electric field as
given by - VM* plus a small correcting vector, which we may call the
electric force of inertia. But to show the physical inanity of "*P, go to
the other extreme, and let u nearly equal v. It is now the electric force
of inertia (supposed) that equals + V^ nearly (except about the equa-
torial plane), and its sole utility or function is to cancel the other - V^
of the (supposed) electrostatic field. It is surely impossible to attach
any physical meaning to ¥ and to propagate it, for we require two TF's,
one to cancel the other, and both propagated infinitely rapidly.
As the speed increases, the electromagnetic field concentrates itself
more and more about the equatorial plane, 6 = \TC. To give an idea of
the accumulation, let tt2/02 = -99. Then cE is -01 of the normal value
q/r2 at the pole, and 10 times the normal value at the equator. The
latitude where the value is normal is given by
~ (30)
Limiting Case of Motion at the Speed of Light. Application to a
Telegraph Circuit.
12. Whentt = fl, the solution (29) becomes a plane electromagnetic
wave, E and H being zero everywhere except in the equatorial plane.
As, however, the values of E and H are infinite, distribute the charge
along a straight line moving in its own line, and let the linear-density
be q. The solution is then f
H=Ecv = 2qv/r ............................. (31)
at distance r from the line, between the two planes through the ends of
the line perpendicular to it, and zero elsewhere.
To further realize, let the field terminate internally at r = a, giving a
cylindrical-surface distribution of electrification, and terminate the tubes
* The Electrician, Dec. 7, 1888, p. 148 [p. 495, vol. n.].
tlbid., Nov. 23, 1888, p. 84 [p. 493, vol. 11.].
512 ELECTRICAL PAPERS.
of displacement externally upon a coaxial cylindrical surface ; we then
produce a real electromagnetic plane wave with electrification, and of
finite energy. We have supposed the electrification to be carried through
the dielectric at speed v, to keep up with the wave, which would of course
break up if the charge were stopped. But if perfectly-conducting
surfaces be given on which to terminate the displacement, the natural
motion of the wave will itself carry the electrification along them. In
fact, we now have the rudimentary telegraph-circuit, with no allowance
made for absorption of energy in the wires, and the consequent
distortion. If the conductors be not coaxial, we only alter the distri-
bution of the displacement and induction, without affecting the
propagation without distortion.*
If we now make the medium conduct electrically, and likewise
magnetically, with equal rates of subsidence, we shall have the same
solutions, with a time-factor e~^ producing ultimate subsidence to zero ;
and, with only the real electric conductivity in the medium the wave is
running through, it will approximately cancel the distortion produced
by the resistance of the wires the wave is passing over when this resist-
ance has a certain value. f We should notice, however, that it could
not do so perfectly, even if the magnetic retardation in the wires due to
diffusion were zero ; because in the case of the unreal magnetic con-
ductivity its correcting influence is where it is wanted to be, in the
body of the wave ; whereas in the case of the wires, their resistance,
correcting the distortion due to the external conductivity, is outside the
wave ; so that we virtually assume instantaneous propagation laterally
from the wires of their correcting influence, in the elementary theory of
propagation along a telegraph-circuit which is symbolized by the
equations
(32)
where R, L, K, and S are the resistance, inductance, leakage-conduct-
ance, and permittance per unit length of circuit, C the current, and V
what I, for convenience, term the potential-difference, but which I have
expressly disclaimed^: to represent the electrostatic difference of
potential, and have shown to represent the transverse voltage or line-
integral of the electric force across the circuit from wire to wire,
including the electric force of inertia. Now in case of great distortion,
as in a long submarine cable, this /^approximates towards the electro-
static potential-difference, which it is in Sir W. Thomson's diffusion
theory ; but in case of little distortion, as in telephony through circuits
of low resistance and large inductance, there may be a wide difference
between my V and that of the electrostatic force. Consider, for
instance, the extreme case of an isolated plane-wave disturbance with no
spreading-out of the tubes of displacement. At the boundaries of the
* The Electrician, Jan. 10, 1885 [p. 440, vol. i.]. Also "Self-Induction of
Wires," Part IV. Phil. Mag., Nov. 1886 [p. 221, vol. n.].
t " Electromagnetic Waves," § 6, Phil. Mag., Feb. 1888 [p. 379, vol. n.]. The
Electrician, June, 1887 [p. 123, vol. n.].
t " Self-induction of Wires," Part. II., Phil. Mag., Sept. 1886 [vol. n., p. 189].
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 513
disturbance the difference between V and the electrostatic difference of
potential is great.
But it is worth noticing, as a rather remarkable circumstance, that
when we derive the system (32) by elementary considerations, viz., by
extending the diffusion-system by the addition of the E.M.F. of inertia
and leakage-current, we apparently as a matter of course take V to
mean the same as in the' diffusion-system. The resulting equations are
correct, and yet the assumption is certainly wrong. The true way
appears to be that given by me in the paper last referred to, by con-
sidering the line-integral of electric force in a closed curve [vol. II.,
p. 187. Also p. 87]. We cannot, indeed, make a separation of the
electric force of inertia from - VP" without some assumption, though
the former is quite definite when the latter is suitably defined, But,
and this is the really important matter, it would be in the highest
degree inconvenient, and lead to much complication and some confusion,
to split V into two components, in other words, to bring in "^f and A.
In thus running down Mf, I am by no means forgetful of its utility in
other cases. But it has perhaps been greatly misused. The clearest
course to pursue appears to me to invariably make E and H the primary
objects of attention, and only use potentials when they naturally suggest
themselves as labour-saving appliances.
Special Tests. The Connecting Equations.
13. Returning to the solutions (29), the following are the special tests
of their accuracy. Let El and JE2 be the z and h components of E.
Then, by (11) and (13), with the special meaning assumed by^?, we have
7,77 «/
r -==- tin. — - CU
hdh
_^L-cA or
dz az
dEl dE« dH
---
- °r -=-
,(33)
In addition to satisfying these equations, the displacement outward
through any spherical surface centred at the charge may be verified to
be q ; this completes the test of the accuracy of (29).
But (33) are not limited to the case of a single point-charge, being
true outside the electrification when there is symmetry with respect to
the z-axis, and the electrification is all moving parallel to it at speed u.
When u = «, E1 = Q, and E2 = E = [j.vH, so that we reduce to
Aff=°' ........................... -(34)
outside the electrification. Thus, if the electrification is on the axis of z,
we have
E/nv = H=2qv/r, ........................... (35)
differing from (31) only in that q, the linear density, may be any
function of z.
H.E.P.— VOL. II. 2K
514 ELECTRICAL PAPERS.
The Motion of a Charged Sphere. The Condition at a Surface of
Equilibrium (Footnote).
14. If, in the solutions (29), we terminate the fields internally at
r = a, the perpendicularity of E and the tangentiality of H to the surface
show that (29) represents the solutions in the case of a perfectly con-
ducting sphere of radius a, moving steadily along the 2-axis at the speed
u, and possessing a total charge q. The energy is now finite. Let U
be the total electric and T the total magnetic energy. By space-
integration of the squares of E and H we find that they are given by
Z7=JL.
2ca
2ca
(36)
in which %<#. When ii = v, with accumulation of the charge at the
equator of the sphere, we have infinite values, and it appears to be
only possible to have finite values by making a zone at the equator
cylindrical instead of spherical. The expression for T in (37) looks
quite wrong ; but it correctly reduces to that of equation (2) when u/v
is infinitely small.*
* [I am indebted to Mr. G. F. C. Searle, of Cambridge, for the opportunity of
making a somewhat important correction before going to press. In a private
communication (August 19, 1892) he informed me that he had verified the accuracy
of the solution for a point-charge, which he had also obtained in another way,
from equations equivalent to (33), without the use of the function A of §§ 8 to 10 ;
but he cast doubt upon the validity of the extension made in § 14, from a point-
charge to a charged conducting sphere, and asked the plain question (in effect),
What justification is there for terminating the displacement perpendicularly, to
make a surface of equilibrium ?
On examination, I find that there is no justification whatever, exceptions
excepted. The true boundary condition may, however, be found without a fresh
investigation. On p. 499 the problem of uniform motion of electrification through
a dielectric medium, or conversely, of the uniform motion of. the whole medium
past stationary electrification, is reduced to a case of eolotropy in electrostatics.
The eS'ect of the motion of the isotropic medium on the displacement emanating
from stationary electrification is there shown to be identical with the effect of
keeping the medium stationary and reducing its permittivity in lines parallel to
the (abolished) motion from c to c(l -w2/^2), whilst keeping the transverse permit-
tivity the same. The transverse concentration of the displacement is obvious.
Now the function P (equation (14), p. 499) is the electrostatic potential in the
stationary eolotropic problem, so that its slope - VP, which call F, is the electric
force, and the displacement D is a linear function thereof, say D = XF, where X is
the permittivity operator. The condition of equilibrium is that F is perpendicular
to the surface where it terminates, this being required to make curl F = 0, or the
voltage zero in every circuit. Now, in the corresponding problem of the same
electrification in a moving isotropic medium, we have the same function P (no
longer the electrostatic potential) and the same derived vector F, whilst the
displacement D is also derived from F in the same way. But whilst the meaning
of D is the same in both cases, that of F is not. In the eolotropic case, F is the
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 515
The State when the Speed of Light is exceeded.
15. The question now suggests itself, What is the state of things
when u>v1 It is clear, in the first place, that there can be no dis-
turbance at all in front of the moving charge (at a point, for simplicity).
Next, considering that the spherical waves emitted by the charge in its
motion along the £-axis travel at speed v, the locus of their fronts is a
conical surface whose apex is at the charge itself, whose axis is that of
z, and whose semiangle 0 is given by
smO = v/u (38)
The whole displacement, of amount q, should therefore lie within this
cone. And since the moving charge is a convection-current qu, the
displacement-current should be towards the apex in the axial portion of
the cone, and change sign at some unknown distance, so as to be away
from the apex either in the outer part of the cone or else upon its
boundary. The pulling back of the charge by the electric stress would
require the continued application of impressed force to keep up the
motion, and its activity would be accounted for by the continuous addi-
tion made to the energy in the cone ; for the transfer of energy on its
boundary is perpendicularly outward, and the field at the apex is being
continuously renewed.
The above general reasoning seems plausible enough, but I cannot
find any solution to correspond that will satisfy all the necessary condi-
tions. It is clear that (29) will not do when u > v. Nor is it of any
use to change the sign of the quantity under the radical, when needed,
to make real. It is suggested that whilst there should be a definite
solution, there cannot be one representing a steady condition of E
and H with respect to the moving charge. As regards physical
electric force, and is not parallel to D. In the moving isotropic medium, on the
other hand, F is not the electric force, which is E, parallel to D. Nevertheless,
the same condition formally obtains, for we have curlF = 0 in the moving medium,
requiring that F shall be perpendicular to a surface of equilibrium, not the
electric force or displacement. P = constant is therefore the equation to a
surface of equilibrium. That is, in the case of a point-charge, the surfaces of
equilibrium are not spheres, but are concentric oblate spheroids, whose principal
axes are proportional to the square roots of c, c, and c(l-w2/v2), the principal
permittivities in the eolotropic problem. In the extreme case of u = v, the
spheroid reduces to a flat circular disc, with a single circular line of electrification
on its edge. It would seem, however, to be a matter of indifference, in this
extreme case, whether the conductor be a disc or a solid sphere.. Bearing in
mind the conditions assumed to prevail in the problem of motion of sources of
displacement in a uniform medium, we see that if we introduce conductors, say by
filling up spaces void of electric force with conducting matter, this should not
interfere with the assumed motions. (See also " Electromagnetic Theory," § 164.)
Equations (36), (37) express the electric and magnetic energy outside a sphere
of radius a, within which is either a point-source at the origin, or any equivalent
spheroidal electrified surface.
In the corresponding bidimensional problem of § 17 in the text, with the
solution (43), it is clear from the above that the surface of equilibrium is an
elliptic cylinder, the shorter axis being in the direction of motion, and the axes
themselves in the ratio 1 to ( 1 - M2/^2)*. This surface degenerates to a flat strip
when u = v. ]
516 ELECTRICAL PAPERS.
possibility, in connexion with the structure of the ether, that is not
in question.*
A Charged Straight Line moving in its own Line.
16. Let us now derive from (29), or from (27), the results in some
cases of distributed electrification, in steady rectilinear motion. The
integrations to be effected being all of an elementary character, it is
not necessary to give the working.
First, let a straight line AB be
charged to linear density q, and be in
motion at speed u in its own line
from left to right. Then a-t P we
shall have
...(39)
2 /x2 + -v2)
from which H= - dAjdh gives
H^gufl - ^f Vl —_ T-same fn of r2, /*2, v2"l, (40
where /x = cos 0, v = sin 0.
When P is vertically over B, and A is at an infinite distance, we shall
................................ (41)
which is one half the value due to an infinitely long (both ways) straight
current of strength qu. The notable thing is the independence of the
ratio u/v.
* [The difficulty about the above method and solution (29) is that it is not
explicit enough when u > v, and does not indicate the limits of application. It
gives a real solution for the hinder cone, a real solution for the forward cone, and
an unreal solution in the rest of space, but we have no instruction to reject the
part for the forward cone and the unreal part, nor have we any means of testing
that the remainder, confined to the hinder cone, is the proper solution, viz., by
the test of divergence, to give the right amount of electrification. The integral
displacement comes to - GO . Now this may require to be supplemented by
+ oo + q on the boundary of the cone, but we have no way of testing it.
But certain considerations led me to the conclusion that the problem of u>v
was really quite as definite a one as that of u < v, and that a correct method of
a general character (independent of the magnitude of u) would show this explicitly.
I therefore (in 1890) attacked the problem from a different point of view, employ-
ing the method of resistance-operators (or an equivalent method). Form the
complete differential equation D = 0u, connecting the displacement D associated
with a moving point-charge with its velocity u, which is any function of the
time t. Here <f> is a differential operator, a function of p or djdt. The solution of
this equation gives D explicitly in terms of u, whether steady or variable, and its
structure indicates the limits of application.
Taking u = constant, we obtain the result (29) when u < v. But when u > v, the
formula tells us to exclude all space except the hinder cone, and that in it, the
solution is not (29), but double as much. That is, double the right member of the
first of (29) when u > v. The boundary of the cone is also a displacement sheet.
The displacement is to the charge in the cone, and from the charge on its surface.
Being so near the end of the second volume, I regret that there is no space
here for the mathematical investigation, which cannot be given in a few words,
and must be reserved.]
MOTION OF ELECTRIFICATION THROUGH A DIELECTRIC. 517
But if u = v in (40), the result is zero, unless ^ = 1, when we have
the result (41). But if P be still further to the left, we shall have to
add to (41) the solution due to the electrification which is ahead of P.
So when the line is infinitely long both ways, we have double the result
in (41), with independence of u/v again.
But should q be a function of z, we do not have independence of u/v
except in the already-considered case of u = v, with plane waves, and no
component of electric force parallel to the line of motion.
A Charged Straight Line moving Transversely.
17. Next, let the electrified line be in
steady motion perpendicularly to its length.
Let q be the linear density (constant), the
2-axis that of the motion, the z-axis coin-
cident with the electrified line, and that of
y upward on the paper. Then the A at
P will be
. (42)
(1 - U*lv*) X2 + {Xl + yS + 38(1 - tf/rlp '
where y and z belong to P, and xv x2 are the limiting values of x in the
charged line. From this derive the solution in the case of an infinitely
long line. It is
where v = sin 9 ; understanding that E is radial, or along qP in the
figure, and H rectilinear, parallel to the charged line.
Terminating the fields internally at r = a, we have the case of a per-
fectly conducting cylinder of radius a, charged with q per unit of length,
moving transversely. When u = v there is disappearance of E and H
everywhere except in the plane 6 = JTT, as in the case of the sphere, with
consequent infinite values. It is the curvature that permits this to
occur, i.e. producing infinite values ; of course it is the self-induction
that is the cause of the conversion to a plane wave, here and in the
other cases. There is some similarity be-
tween (43) and (29). In fact, (43) is the
bidimensional equivalent of (29).
A Charged Plane moving Transversely.
18. Coming next to a plane distribution
-y*
of electrification, let q be the surface-density,
and the plane be moving perpendicularly
to itself. Let it be of finite breadth and
of infinite length, so that we may calculate H from (43).
at Pis
The result
H
a1**;
,(44)
518 ELECTRICAL PAPERS.
When P is equidistant from the edges, H is zero. There is therefore
no H anywhere due to the motion of an infinitely large uniformly
charged plane perpendicularly to itself. The displacement-current is
the negative of the convection-current and at the same place, viz. the
moving plane, so there is no true current.
Calculating Ev the ^-component of E, z being measured from left to
right, we find
(45)
The component parallel to the plane is H/cu. Thus, when the plane is
infinite, this component vanishes with H, and we are left with
cE1 = cE = 2Trq, ............................. (46)
the same as if the plane were at rest.
A Charged Plane moving in its own Plane.
19. Lastly, let the charged plane be moving in its own plane. Refer
to the first figure, in which let AB now be the trace of the plane when
of finite breadth. We shall find that
(47)
zl and z2 being the extreme values of z, which is measured parallel to
the breadth of the plane.
Therefore, when the plane extends infinitely both ways, we have
H=2Trqu . ................................ (48)
above the plane, and its negative below it. This differs from the previous
case of vanishing displacement-current. There is H, and the convection-
current is not now cancelled by coexistent displacement-current.
The existence of displacement-current, or changing displacement, was
the basis of the conclusion that moving electrification constitutes a part
of the true current. Now in the problem (48) the displacement-current
has gone, so that the existence of H appears to rest merely upon the
assumption that moving electrification is true current. But if the plane
be not infinite, though large, we shall have (48) nearly true near it, and
away from the edges ; whilst the displacement-current will be strong
near the edges, and almost nil where (48) is nearly true.
But in some cases of rotating electrification, there need be no dis-
placement anywhere, except during the setting up of the final state.
This brings us to the rather curious question whether there is any
difference between the magnetic field of a convection-current produced
by the rotation of electrification upon a good nonconductor and upon a
good conductor respectively, other than that due to diffusion in the
conductor. For in the case of a perfect conductor, it is easy to imagine
that the electrification could be at rest, and the moved conductor merely
slip past it. Perhaps Professor Rowland's forthcoming experiments on
convection-currents may cast -some light upon this matter.
December 27, 1888.
DEFLECTION OF AN ELECTROMAGNETIC WAVE. 519
LI. DEFLECTION OF AN ELECTROMAGNETIC WAVE BY
MOTION OF THE MEDIUM.
[The Electrician, April 12, 1889, p. 663.]
THIS subject is of interest in connection with theories of Aberration,
which requires to be explained electromagnetically. A plane wave in
a nonconducting dielectric is carried on at speed v = (/*c)~*, where p is
the inductivity and c the permittivity, and is not altered in any way,
according to the rudimentary theory, that is to say, which overlooks
dispersion. But if the medium be moving through the ether, it is
altered in a manner depending upon the speed of motion and the angle
it makes with the undisturbed direction of propagation.
Thus, let EQ = ^vH^ specify a plane wave in a medium at rest,
E0 being the tensor of the electric and HQ of the magnetic force.
Next set the medium in motion with velocity u, changing E0 to E and
H0 to H, thus
E = e + E0, H = h + H0, (A)
where e and h are the auxiliary electric and magnetic forces due to the
motion. To find them, we have, first, the electric force due to motion
of matter in a magnetic field, or
e = /*VuH, (B)
which formula is well known, and is included in Maxwell's treatise.
Next, the magnetic force due to motion in an electric field, or
h = cVEu (C)
This equation, which is as necessary as (B), was, so far as I am at
present aware, first given by me in Section III. of " Electromagnetic In-
duction and its Propagation," January 24, 1885 [vol. I., p. 446], and was
again considered later on in connection with the " magneto-electric
force," which is as necessary as Maxwell's " electromagnetic force."
We require one more relation, viz., between E0 and H0, viz.,
H0 = cVvE0, (D)
the property of a plane wave, due to Maxwell ; and we can now fully
find the auxiliaries e and h in terms of the originals E0 and H0. Here
v is the vectorized v of the wave when undisturbed.
In the above V is the symbol of vector product. Thus VuH is the
vector perpendicular to u and to H, whose tensor equals the product of
their tensors, u and H, into the sine of the angle between their directions.
But this is merely used to state the general relations in a compact and
intelligible form, instead of with Cartesian circumlocutions.
Instead of taking the general case, it is convenient to divide into
three, viz., (1), u parallel to v ; (2), u parallel to E0 ; (3), u parallel to
H0. By putting the results together we shall obtain the mixed-up
general case.
(1). u parallel to v. Here the medium is moving in the same direc-
tion as that of undisturbed propagation, and there is no alteration of
520 ELECTRICAL PAPERS.
direction of either E0 or H0, so that it is only necessary to specify the
tensors of the auxiliaries e and h. Thus : —
e=- — En fc=-_^ ' HQ ................... (1)
u+v c u+v (
If, for example, the medium be moving at half the speed v, and with
it, the displacement and induction in a given length are spread over a
space half as great again as
if the medium were at rest,
so that their intensities are
reduced to two-thirds of the
undisturbed values. There
is no discontinuity when u is
equal to or greater than v.
But if the medium move
the other way there is com-
pression into half the space,
so that the intensities are
doubled. As it is increased
up to i\ the compression in-
creases infinitely. After that, with u>v, there is reversal of sign of E
and H as compared with E0 and H0.
(2). u and E0 parallel. Here h0 is parallel to H0, but e0 is parallel to
V. Their tensors are given by .
(3). Lastly, u and H0 parallel. Now e is parallel to E0, whilst h is
parallel to v. Their tensors are
In either case, (2) or (3), the angle of deflection 6 is given by
n UV
consequently the deflection is wholly independent of the plane of
polarization.
Thus, let a slab of (say) glass move in its own plane at speed u, and
a plane-wave from the upper medium strike the glass flush. The trans-
mitted rays are deflected as shown in Fig. 1, the deflection being given
by the above formula, where, observe, v is the speed in the glass when
at rest, and u the speed of the glass with respect to the external medium.
The above working out of the effect of moving matter on a plane
electromagnetic wave is (if done properly) strictly in accordance with
electromagnetic principles. But it will be observed that Fresnel's result,
relating to the alteration in the speed of light produced by moving a
transparent medium through which it is passing, is not accounted for.
It is said to have been thoroughly confirmed by Michelson. I should
like to direct the attention of electromagneticians to this question, with
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 521
a view to the discovery of a modification of the above data, or correction
of the working, in order to explain Fresnel arid Michelson, which must
be done electromagnetically. Mr. Glazebrook has made Sir W. Thom-
son's extraordinary contractile ether do it by an auxiliary hypothesis ;
surely, then, Maxwell's ether equations could be appropriately modified.
LII. ON THE FORCES, STRESSES, AND FLUXES OF ENERGY
IN THE ELECTROMAGNETIC FIELD.
[Royal Society. Received June 9, Read June 18, 1891.* Abstract in
Proceedings, vol. 50, 1891 ; Paper in Transactions, A. 1892.]
(ABSTRACT.)
THE abstract nature of this paper renders its adequate abstraction
difficult. The principle of conservation of energy, when applied to a
theory such as Maxwell's, which postulates the definite localization of
energy, takes a more special form, viz., that of the continuity of energy.
Its general nature is discussed. The relativity of motion forbids us to
go so far as to assume the objectivity of energy, and to identify energy,
like matter ; hence the expression of the principle is less precise than
that of the continuity of matter (as in hydrodynamics), for all we can
say in general is that the convergence of the flux of energy equals the
rate of increase of the density of the energy ; the flux of the energy
being made up partly of the mere convection of energy by motion of
the matter (or other medium) with which it is associated localizably, and
partly of energy which is transferred through the medium in other
ways, as by the activity of a stress, for example, not obviously (if at
all) representable as the convection of energy. Gravitational energy is
the chief difficulty in the way of the carrying out of the principle. It
must come from the ether (for where else can it come from ?), when it
goes to matter ; but we are entirely ignorant of the manner of its dis-
tribution and transference. But, whenever energy can be localized, the
principle of continuity of energy is (in spite of certain drawbacks con-
nected with the circuital flux of energy) a valuable principle which
should be utilized to the uttermost. Practical forms are considered.
In the electromagnetic application the flux of energy has a four-fold
make-up, viz., the Poynting flux of energy, which occurs whether the
medium be stationary or moving; the flux of energy due to the
activity of the electromagnetic stress when the medium is moving ; the
convection of electric and magnetic energy ; and the convection of other
energy associated with the working of the translational force due to the
stress.
As Electromagnetism swarms with vectors, the proper language for
its expression and investigation is the Algebra of Vectors. An account
* Typographical troubles have delayed the publication of this paper. The foot-
notes are of date May 11, 1892.
522 ELECTRICAL PAPERS.
is therefore given of the method employed by the author for some
years past. The quaternionic basis is rejected, and the algebra is based
upon a few definitions of notation merely. It may be regarded "as
Quaternions without quaternions, and simplified to the uttermost ; or
else as being merely a conveniently condensed expression of the Cartesian
mathematics, understandable by all who are acquainted with Cartesian
methods, and with which the vectorial algebra is made to harmonize.
It is confidently recommended as a practical working system.
In continuation thereof, and preliminary to the examination of
electromagnetic stresses, the theory of stresses of the general type, that
is, rotational, is considered ; and also the stress activity, and flux of
energy, and its convergence and division into translational, rotational,
and distortional parts; all of which, it is pointed out, maybe associated
with stored potential, kinetic, and wasted energy, at least so far as the
mathematics is concerned.
The electromagnetic equations are then introduced, using them in
the author's general forms, i.e., an extended form of Maxwell's circuital
law, defining electric current in terms of magnetic force, and a com-
panion equation expressing the second circuital law ; this method
replacing Maxwell's in terms of the vector-potential and the electro-
static potential, Maxwell's equations of propagation being found im-
possible to work and not sufficiently general. The equation of activity
is then derived in as general a form as possible, including the effects of
impressed forces and intrinsic magnetization, for a stationary medium
which may be eolotropic or not. Application of the principle of con-
tinuity of energy then immediately indicates that the flux of energy in
the field is represented by the formula first discovered by Poynting.
Next, the equation of activity for a moving medium is considered. It
does not immediately indicate the flux of energy, and, in fact, several
transformations are required before it is brought to a fully significant
form, indicating (1), the Poynting flux, the form of which is settled ;
(2), the convection of electric and magnetic energy; (3), a flux of energy
which, from the form in which the velocity of the medium enters,
represents the flux of energy due to a working stress. Like the
Poynting flux, it contains vector products. From this flux the stress
itself is derived, and the form of translational force, previously tentatively
developed, is verified. It is assumed that the medium in its motion
carries its properties with it unchanged.
A side matter which is discussed is the proper measure of "true"
electric current, in accordance with the continuity of energy. It has a
four-fold make-up, viz., the conduction-current, displacement-current,
convection-current (or moving electrification), and the curl of the
motional magnetic force.
The stress is divisible into an electric and a magnetic stress. These
are of the rotational type in eolotropic media. They do not agree with
Maxwell's general stresses, though they work down to them in an
isotropic homogeneous stationary medium not intrinsically magnetized
or electrized, being then the well-known tensions in certain lines with
equal lateral pressures.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 523
Another and shorter derivation of the stress is then given, guided by
the previous, without developing the expression for the flux of energy.
Variations of the properties permittivity and inductivity with the strain
can be allowed for. An investigation by Professor H. Hertz is referred
to. His stress is not agreed with, and it is pointed out that the
assumption by which it is obtained is equivalent to the existence of
isotropy, so that its generality is destroyed. The obvious validity of
the assumption on which the distortional activity of the stress is
calculated is also questioned.
Another form of the stress-vector is examined, showing its relation
to the fictitious electrification and magnetic current, magnetification
and electric current, produced on the boundary of a region by termi-
nating the stress thereupon ; and its relation to the theory of action at
a distance between the respective matters and currents.
The stress-subject is then considered statically. The problem is now
perfectly indeterminate, in the absence of a complete experimental
knowledge of the strains set up in bodies under electric and magnetic
influence. Only the stress in the air outside magnets and conductors
can be considered known. Any stress within them may be superadded,
without any difference being made in the resultant forces and torques.
Several stress-formulae are given, showing a transition from one extreme
form to another. A simple example is worked out to illustrate the
different ways in which Maxwell's stress and others explain the
mechanical actions. Maxwell's stress, which involves a translational
force on magnetized niatter (even when only inductively magnetized),
merely because it is magnetized, leads to a very complicated and un-
natural way of explanation. It is argued, independently, that no stress-
formula should be allowed which indicates a translational force of the
kind just mentioned.
Still the matter is left indeterminate from the statical standpoint.
From the dynamical standpoint, however, we are led to a certain
definite stress-distribution, which is also, fortunately, free from the
above objection, and is harmonized with the flux of energy. A pecu-
liarity is the way the force on an intrinsic magnet is represented. It
is not by force on its poles, nor on its interior, but on its sides, referring
to a simple case of uniform longitudinal magnetization ; i.e., it is done
by a ^wasi-electromagnetic force on the fictitious electric current which
would produce the same distribution of induction as the magnet does.
There is also a force where the inductivity varies. This force on
fictitious current harmonizes with the conclusion previously arrived at
by the author, that when impressed forces set up disturbances, such
disturbances are determined by the curl of the impressed forces, and
proceed from their localities.
In conclusion it is pointed out that the determinateness of the stress
rests upon the assumed localization of the energy and the two laws of
circuitation, so that with other distributions of the energy (of the same
proper total amounts) other results would follow ; but the author has
been unable to produce full harmony in any other way than that
followed.
524 ELECTRICAL PAPERS.
General Remarks, especially on the Flux of Energy.
§ 1. The remarkable experimental work of late years has inaugurated
a new era in the development of the Faraday-Maxwellian theory of the
ether, considered as the primary medium concerned in electrical pheno-
mena— electric, magnetic, and electromagnetic. Maxwell's theory is no
longer entirely a paper theory, bristling with unproved possibilities.
The reality of electromagnetic waves has been thoroughly demonstrated
by the experiments of Hertz and Lodge, Fitzgerald and Trouton, J. J.
Thomson, and others ; and it appears to follow that, although Maxwell's
theory may not be fully correct, even as regards the ether (as it is
certainly not fully comprehensive as regards material bodies), yet the
true theory must be one of the same type, and may probably be merely
an extended form of Maxwell's.
No excuse is therefore now needed for investigations tending to
exhibit and elucidate this theory, or to extend it, even though they be
of a very abstract nature. Every part of so important a theory deserves
to be thoroughly examined, if only to see what is in it, and to take note
of its unintelligible parts, with a view to their future explanation or
elimination.
§ 2. Perhaps the simplest view to take of the medium which plays
such a necessary part, as the recipient of energy, in this theory, is to
regard it as continuously filling all space, and possessing the mobility
of a fluid rather than the rigidity of a solid. If whatever possess the
property of inertia be matter, then the medium is a form of matter.
But away from ordinary matter it is, for obvious reasons, best to call
it as usual by a separate name, the ether. Now, a really difficult and
highly speculative question, at present, is the connection between
matter (in the ordinary sense) and ether. When the medium trans-
mitting the electrical disturbances consists of ether and matter, do they
move together, or does the matter only partially carry forward the ether
which immediately surrounds it 1 Optical reasons may lead us to con-
clude, though only tentatively, that the latter may be the case ; but at
present, for the purpose of fixing the data, and in the pursuit of investi-
gations not having specially optical bearing, it is convenient to assume
that the matter and the ether in contact with it move together. This
is the working hypothesis made by H. Hertz in his recent treatment of
the electrodynamics of moving bodies; it is, in fact, what we tacitly
assume in a straightforward and consistent working out of Maxwell's
principles without any plainly-expressed statement on the question of
the relative motion of matter and ether ; for the part played in Maxwell's
theory by matter is merely (and, of course, roughly) formularized by
supposing that it causes the etherial constants to take different values,
whilst introducing new properties, that of dissipating energy being the
most prominent and important. We may, therefore, think of merely
one medium, the most of which is uniform (the ether), whilst certain
portions (matter as well) have different powers of supporting electric
displacement and magnetic induction from the rest, as well as a host
of additional properties; and of these we can include the power of
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 525
supporting conduction-current with dissipation of energy according to
Joule's law, the change from isotropy to eolotropy in respect to the
distribution of the several fluxes, the presence of intrinsic sources of
energy, etc.*
§ 3. We do not in any way form the equations of motion of such a
medium, even as regards the uniform simple ether, away from gross
matter ; we have only to discuss it as regards the electric and magnetic
fluxes it supports, and the stresses and fluxes of energy thereby necessi-
tated. First, we suppose the medium to be stationary, and examine
the flux of electromagnetic energy. This is the Poynting flux of
energy. Next we set the medium into motion of an unrestricted kind.
We have now necessarily a convection of the electric and magnetic
energy, as well as the Poynting flux. Thirdly, there must be a similar
convection of the kinetic energy, etc., of the translation al motion ; and
fourthly, since the motion of the medium involves the working of
ordinary (Newtonian) force, there is associated with the previous a flux
of energy due to the activity of the corresponding stress. The question
is therefore a complex one, for we have to properly fit together these
various fluxes of energy in harmony with the electromagnetic equations.
A side issue is the determination of the proper measure of the activity
of intrinsic forces, when the medium moves ; in another form, it is the
determination of the proper meaning of "true current" in Maxwell's
sense.
§ 4. The only general principle that we can bring to our assistance in
interpreting electromagnetic results relating to activity and flux of
energy, is that of the persistence of energy. But it would be quite
inadequate in its older sense referring to integral amounts ; the definite
localization by Maxwell, of electric and magnetic energy, and of its
waste, necessitates the similar localization of sources of energy ; and in
the consideration of the supply of energy at certain places, combined
with the continuous transmission of electrical disturbances, and there-
fore of the associated energy, the idea of a flux of energy through space,
and therefore of the continuity of energy in space and in time, becomes
forced upon us as a simple, useful, and necessary principle, which
cannot be avoided.
When energy goes from place to place, it traverses the intermediate
space. Only by the use of this principle can we safely derive the
electromagnetic stress from the equations of the field expressing the
two laws of circuitation of the electric and magnetic forces ; and this
* Perhaps it is best to say as little as possible at present about the connection
between matter and ether, but to take the electromagnetic equations in an abstract
manner. This will leave us greater freedom for future modifications without con-
tradiction. There are, also, cases in which it is obviously impossible to suppose
that matter in bulk carries on with it the ether in bulk which permeates it.
Either, then, the mathematical machinery must work between the molecules ; or
else, we must make such alterations in the equations referring to bulk as will be
practically equivalent in effect. For example, the motional magnetic force VDq
of equations (88), (92), (93) may be modified either in q or in D, by use of a smaller
effective velocity q, or by the substitution in D or cE of a modified reckoning
of c for the effective permittivity.
526 ELECTRICAL PAPERS.
again becomes permissible only by the postulation of the definite
localization of the electric and magnetic energies. But we need not go
so far as to assume the objectivity of energy. This is an exceedingly
difficult notion, and seems to be rendered inadmissible by the mere
fact of the relativity of motion, on which kinetic energy depends. We
cannot, therefore, definitely individualize energy in the same way as is
done with matter.
If p be the density of a quantity whose total amount is invariable,
and which can change its distribution continuously, by actual motion
from place to place, its equation of continuity is
convq/D = /3, (1)
where q is its velocity, and q/> the flux of />. That is, the convergence
of the flux of p equals the rate of increase of its density. Here p may
be the density of matter. But it does not appear that we can apply
the same method of representation to the flux of energy. We may,
indeed, write
convX = J, (2)
if X be the flux of energy from all causes, and T the density of localiz-
able energy. But the assumption X = Tq would involve the assumption
that T moved about like matter, with a definite velocity. A part of T
may, indeed, do this, viz., when it is confined to, and is carried by
matter (or ether) ; thus we may write
conv(qr+X) = r, (3)
where T is energy which is simply carried, whilst X is the total flux of
energy from other sources, and which we cannot symbolize in the form
Tq ; the energy which comes to us from the Sun, for example, or
radiated energy. It is, again, often impossible to carry out the principle
in this form, from a want of knowledge of how energy gets to a certain
place. This is, for example, particularly evident in the case of gravita-
tional energy, the distribution of which, before it is communicated to
matter, increasing its kinetic energy, is highly speculative. If it come
from the ether (and where else can it come from ?), it should be possible
to symbolize this in X, if not in <\T ; but in default of a knowledge of
its distribution in the ether, we cannot do so, and must therefore turn
the equation of continuity into
S + conv(qr+X) = T, (4)
where S indicates the rate of supply of energy per unit volume from
the gravitational source, whatever that may be. A similar form is
convenient in the case of intrinsic stores of energy, which we have
reason to believe are positioned within the element of volume concerned,
as when heat gives rise to thermoelectric force. Then S is the activity
of the intrinsic sources. Then again, in special applications, T is con-
veniently divisible into different kinds of energy, potential and kinetic.
Energy which is dissipated or wasted comes under the same category,
because it may either be regarded as stored, though irrecoverably, or
passed out of existence, so far as any immediate useful purpose is
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 527
concerned. Thus we have as a standard practical form of the equation
of continuity of energy referred to the unit volume,
S + conv{X + C((U + T)} = Q+U+f, (5)
where S is the energy supply from intrinsic sources, U potential energy
and T kinetic energy of localizable kinds, (\[U-\-T) its convective flux,
Q the rate of waste of energy, and X the flux of energy other than
convective, e.g., that due to stresses in the medium and representing
their activity. In the electromagnetic application we shall see that
U and T must split into two kinds, and so must X, because there is
a flux of energy even when the medium is at rest.
§5. Sometimes we meet with cases in which the flux of energy is
either wholly or partly of a circuital character. There is nothing
essentially peculiar to electromagnetic problems in this strange and
apparently useless result. The electromagnetic instances are paralleled
by similar instances in ordinary mechanical science, when a body is in
motion and is also strained, especially if it be in rotation. This result
is a necessary consequence of our ways of reckoning the activity of
forces and of stresses, and serves to still further cast doubt upon the
" thinginess " of energy. At the same time, the flux of energy is going
on all around us, just as certainly as the flux of matter, and it is
impossible to avoid the idea ; we should, therefore, make use of it and
formnlarize it whenever and as long as it is found to be useful, in spite
of the occasional failure to obtain readily understandable results.
The idea of the flux of energy, apart from the conservation of energy,
is by no means a new one. Had gravitational energy been less obscure
than it is, it might have found explicit statement long ago. Professor
Poynting* brought the principle into prominence in 1884, by making
use of it to determine the electromagnetic flux of energy. Professor
Lodgef gave very distinct and emphatic expression of the principle
generally, apart from its electromagnetic aspect, in 1885, and pointed
out how much more simple and satisfactory it makes the principle
of the conservation of energy become. So it would, indeed, could we
only understand gravitational energy ; but in that, and similar respects,
it is a matter of faith only. But Professor Lodge attached, I think,
too much importance to the identity of energy, as well as to another
principle he enunciated, that energy cannot be transferred without being
transformed, and conversely; the transformation being from potential
to kinetic energy or conversely. This obviously cannot apply to the
convection of energy, which is a true flux of energy ; nor does it seem
to apply to cases of wave-motion in which the energy, potential and
kinetic, of the disturbance, is transferred through a medium unchanged
in relative distribution, simply because the disturbance itself travels
without change of type ; though it may be that in the unexpressed
internal actions associated with the wave-propagation there might be
found a better application.
* Poynting, Phil. Trans., 1884.
t Lodge, Phil. Mag., June, 1885, " On the Identity of Energy."
528 ELECTRICAL PAPERS.
It is impossible that the ether can be fully represented, even merely
in its transmissive functions, by the electromagnetic equations. Gravity
is left out in the cold; and although it is convenient to ignore this
fact, it may be sometimes usefully remembered, even in special electro-
magnetic work ; for, if a medium have to contain and transmit gravita-
tional energy as well as electromagnetic, the proper system of equations
should show this, and, therefore, include the electromagnetic. It seems,
therefore, not unlikely that in discussing purely electromagnetic specu-
lations, one may be within a stone's throw of the explanation of gravita-
tion all the time. The consummation would be a really substantial
advance in scientific knowledge.
On the Algebra and Analysis of Vectoi's without Quaternions. Outline of
Author's System.
§6. The proper language of vectors is the algebra of vectors. It is,
therefore, quite certain that an extensive use of vector-analysis in
mathematical physics generally, and in electromagnetism, which is
swarming with vectors, in particular, is coming and may be near at
hand. It has, in my opinion, been retarded by the want of special
treatises on vector-analysis adapted for use in mathematical physics,
Professor Tait's well-known profound treatise being, as its name
indicates, a treatise on Quaternions. I have not found the Hamilton-
Tait notation of vector-operations convenient, and have employed, for
some years past, a simpler system. It is not, however, entirely a
question of notation that is concerned. I reject the quaternionic basis
of vector-analysis. The anti-quaternionic argument has been recently
ably stated by Professor Willard Gibbs.* He distinctly separates
this from the question of notation, and this may be considered fortunate,
for whilst I can fully appreciate and (from practical experience) endorse
the anti-quaternionic argument, I am unable to appreciate his notation,
and think that of Hamilton and Tait is, in some respects, preferable,
though very inconvenient in others.
In Hamilton's system the quaternion is the fundamental idea, and
everything revolves round it. This is exceedingly unfortunate, as it
renders the establishment of the algebra of vectors without metaphysics
a very difficult matter, and in its application to mathematical analysis
there is a tendency for the algebra to get more and more complex
as the ideas concerned get simpler, and the quaternionic basis forms
a real difficulty of a substantial kind in attempting to work in harmony
with ordinary Cartesian methods.
Now, I can confidently recommend, as a really practical working
system, the modification I have made. It has many advantages, and
not the least amongst them is the fact that the quaternion does not
appear in it at all (though it may, without much advantage, be brought
* Professor Gibbs's letters will be found in Nature, vol. 43, p. 511, and vol. 44,
p. 79 ; and Professor Tait's in vol. 43, pp. 535, 608. This rather one-sided dis-
cussion arose out of Professor Tait stigmatizing Professor Gibbs as ' ' a retarder of
quaternionic progress." This may be very true ; but Professor Gibbs is anything
but a retarder of progress in vector analysis and its application to physics.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 529
in sometimes), and also that the notation is arranged so as to harmonize
with Cartesian mathematics. It rests entirely upon a few definitions,
and may be regarded (from one point of view) as a systematically
abbreviated Cartesian method of investigation, and be understood and
practically used by any one accustomed to Cartesians, without any
study of the difficult science of Quaternions. It is simply the elements
of Quaternions without the quaternions, with the notation simplified to
the uttermost, and with the very inconvenient minus sign before scalar
products done away with.*
§ 7. Quantities being divided into scalars and vectors, I denote the
scalars, as usual, by ordinary letters, and put the vectors in the plain
black type, known, I believe, as Clarendon type, rejecting Maxwell's
German letters on account of their being hard to read. A special type
is certainly not essential, but it facilitates the reading of printed com-
plex vector investigations to be able to see at a glance which quantities
are scalars and which are vectors, and eases the strain on the memory.
But in MS. work there is no occasion for specially formed letters.
Thus A stands for a vector. The tensor of a vector may be denoted
by the same letter plain ; thus A is the tensor of A. (In MS. the
tensor is AQ.) Its rectangular scalar components are Alt A2, A3. A
unit vector parallel to A may be denoted by A1? so that A = AAl. But
little things of this sort are very much matters of taste. What is
important is to avoid as far as possible the use of letter prefixes, which,
when they come two (or even three) together, as in Quaternions, are
very confusing.
The scalar product of a pair of vectors A and B is denoted by AB,
and is defined to be A
AE = AlB1 + A2B2 + A3BB = ABcosA3 = EA (6)
* §§ 7, 8, 9 contain an introduction to vector-analysis (without the quaternion),
which is sufficient for the purposes of the present paper, and, I may add, for
general use in mathematical physics. It is an expansion of that given in my
paper "On the Electromagnetic Wave Surface," Phil. Mag., June, 1885, (vol. n.,
pp. 4 to 8). The algebra and notation are substantially those employed in all my
papers, especially in " Electromagnetic Induction and its Propagation," The
Electrician, 1885.
Professor Gibbs's vectorial work is scarcely known, and deserves to be well
known. In June, 1888, 1 received from him a little book of 85 pages, bearing the
singular imprint NOT PUBLISHED, Newhaven, 1881-4. It is indeed odd that the
author should not have published what he had been at the trouble of having
of
say
the
subject.
In The Electrician for Nov. 13, 1891, p. 27, I commenced a few articles on
elementary vector-algebra and analysis, specially meant to explain to readers of
my papers how to work vectors. I am given to understand that the earlier ones,
on the algebra, were much appreciated ; the later ones, however, are found diffi-
cult. But the vector-algebra is identically the same in both, and is of quite a
rudimentary kind. The difference is, that the later ones are concerned with
analysis, with varying vectors ; it is the same as the difference between common
algebra and differential calculus. The difficulty, whether real or not, does not
indicate any difficulty in the vector-algebra. I mention this on account of the
great prejudice which exists against vector-algebra.
H.E.P. — VOL. II. 2L
530 ELECTRICAL PAPERS.
The addition of vectors being as in the polygon of displacements, or
velocities, or forces; i.e., such that the vector length of any closed
circuit is zero ; either of the vectors A and B may be split into the sum
of any number of others, and the multiplication of the two sums to
form AB is done as in common algebra ; thus
(a + b)(c + d) = ac + ad + be + bd = ca + da + cb + db ....... (7)
If N be a unit vector, NN or N2 = 1 ; similarly, A? = A2 for any vector.
The reciprocal of a vector A has the same direction ; its tensor is the
reciprocal of the tensor of A. Thus
AA-^^1; and AB-1 = B-1A = 4 = 4COS ^ ...... (8)
A 15 x)
The vector product of a pair of vectors is denoted by VAB, and is
A
defined to be the vector whose tensor is ABsin AB, and whose direc-
tion is perpendicular to the plane of A and B, thus
VAB = i(A2B3 - A3B2) + j(A3Bl - A&) + k(^^ - A2B,) = - VBA, (9)
where i, j, k, are any three mutually rectangular unit vectors. The
tensor of VAB is V0AB ; or
V0AB = ^BsinAB ......................... (10)
Its components are iVAB, JVAB, kVAB.
In accordance with the definitions of the scalar and vector products,
we have
i'=l, J2=l, k* = l; |
ij = 0, jk = 0, ki = 0; ................... (11)
Vij=k, Vjk = i, Vki=:j;l
and from these we prove at once that
V(a + b)(o + d) = Vac + Vad + Vbc + Vbd,
and so on, for any number of component vectors. The order of the
letters in each product has to be preserved, since Vab= - Vba.
Two very useful formulae of transformation are
1C2 -£&); ....(12)
and VAVBC = B.CA-C.AB, or =B(CA)-C(AB) ....... (13)
Here the dots, or the brackets in the alternative notation, merely
act as separators, separating the scalar products CA and AB from the
vectors they multiply. A space would be equivalent, but would be
obviously unpractical.
A
As — is a scalar product, so in harmony therewith, there is the
B A
vector product V—. Since VAB = - VBA, it is now necessary to make
B
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 531
a convention as to whether the denominator comes first or last in
V=. Say therefore, VAB"1. Its tensor is
D
(U)
§ 8. Differentiation of vectors, and of scalar and vector functions of
vectors with respect to scalar variables is done as usual. Thus,
.(15)
= AVBC + AVBC + AVBC.
The same applies with complex scalar differentiators, e.g., with the
differentiator
used when a moving particle is followed, q being its velocity. Thus,
?AB = A?? + B~ = AB + BA + A
ct Ct ot
Here qV is a scalar differentiator given by
?AB = A?? + B~ = AB + BA + A.qV.B + B.qV.A .......... (16)
ct Ct ot
so that A.qV.B is the scalar product of A and the vector qV.B; the
dots here again act essentially as separators. Otherwise, we may write
it A(qV)B.
The fictitious vector V given by
k ................... (18)
is very important. Physical mathematics is very largely the mathe-
matics of V. The name Nabla seems, therefore, ludicrously inefficient.
In virtue of i, j, k, the operator V behaves as a vector. It also, of
course, differentiates what follows it.
Acting on a scalar P, the result is the vector
VP = iV1P+jV2P + kV3P, ........................ (19)
the vector rate of increase of P with length.
If it act on a vector A, there is first the scalar product
VA = V1^1 + V2^2 + V3^3 = divA, .................. (20)
or the divergence of A. Regarding a vector as a flux, the divergence
of a vector is the amount leaving the unit volume.
The vector product WA is
VVA = i(V2^3 - V3^2) + j(V3^! - V^3) + k(V^2 - V^) = curl A. (21)
532 ELECTRICAL PAPERS.
The line-integral of A round a unit area equals the component of the
curl of A perpendicular to the area.
We may also have the scalar and vector products NV and VNV,
where the vector N is not differentiated. These operators, of course,
require a function to follow them on which to operate; the previous
qV. A of (16) illustrates.
The Laplacean operator is the scalar product V2 or VV ; or
(22)
and an example of (13) is
WWA = V. VA - V2A, or curPA = V div A - V2A, ..... (23)
which is an important formula.
Other important formulae are the next three.
divPA = PdivA + AV.P, ........................ (24)
P being scalar. Here note that AV.P and AVP (the latter being the
scalar product of A and VP) are identical. This is not true when for P
we substitute a vector. Also
divVAB = BcurlA-AcurlB; .................... (25)
which is an example of (12), noting that both A and B have to be
differentiated. And
curlVAB = BV.A + AdivB-AV.B-BdivA ............ (26)
This is an example of (13).
§ 9. When one vector D is a linear function of another vector E, that
is, connected by equations of the form
A =
(27)
in terms of the rectangular components, we denote this simply by
D = cE, ................................... (28)
where c is the linear operator. The conjugate function is given by
D' = c'E, ................................. (29)
where D' is got from D by exchanging c12 and c21, etc. Should the nine
coefficients reduce to six by C12 = c21, etc., D and D' are identical, or D
is a self-conjugate or symmetrical linear function of E.
But, in general, it is the sum of D and D' which is a symmetrical
function of E, and the difference is a simple vector-product. Thus
where c0 is a self-conjugate operator, and e is the vector given by
(31)
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 533
The important characteristic of a self-conjugate operator is
B^EA, or ElC()E2 = E2c0El5 ............. (32)
where Ex and E2 are any two E's, and DI} D2, the corresponding D's.
But when there is not symmetry, the corresponding property is
E1D2 = E2D(, or B1cB2 - BjC^ ............... (33)
Of these operators we have three or four in electromagnetism con-
necting forces and fluxes, and three more connected with the stresses
and strains concerned. As it seems impossible to avoid the considera-
tion of rotational stresses in electromagnetism, and these are not usually
considered in works on elasticity, it will be desirable to briefly note
their peculiarities here, rather than later on.
On Stresses, irrotational and rotational, and their Activities.
£ 10. Let P^v be the vector stress on the N-plane, or the plane whose
unit normal is N. It is a linear function of N. This will fully specify
the stress on any plane. Thus, if Pv P2, P3 are the stresses on the
i, j, k planes, we shall have
[ (34)
Let, also, Q v be the conjugate stress ; then, similarly,
\ (35)
Q3 = iP13+jP23
Half the sum of the stresses P^ and Q,v is an ordinary irrotational
stress ; so that
P.V = 4>0N + V€N, Q^=<£0N-VeN, ............ (36)
where <£0 is self-conjugate, and
2e = i(P23-P32)+j(P31-P13) + k(P12-P21) ........... (37)
Here 2« is the torque per unit volume arising from the stress P.
The translational force, F, per unit volume is (by inspection of a
unit cube)
F = V1P1 + V2P2 + V3P3 ........................ (38)
= idivQ1+jdivQ2 + kdivQ3; ............ (39)
or, in terms of the self-conjugate stress and the torque,
F = (i div <£0i + j div $<$ +k div <£0k) - curl e, .......... (40)
where -curie is the translational force due to the rotational stress
alone, as in Sir W. Thomson's latest theory of the mechanics of an
"ether."*
* Mathematical and Physical Papers, vol. 3, Art. 99, p. 436.
534 ELECTRICAL PAPERS.
Next, let N be the unit-normal drawn outward from any closed
surface. Then
SP^SF, (41)
where the left summation extends over the surface and the right sum-
mation throughout the enclosed region. For
PJ, = ^1P1 + JV2P2 + JV3P3 = i.NQ1+j.NQ2 + k.NQ3; (42)
so the well-known theorem of divergence gives immediately, by (39),
2PJ = 2(idivQ1+jdivQ, + kdivQs)=s2F (43)
Next, as regards the equivalence of rotational effect of the surface-
stress to that of the internal forces and torques. Let r be the vector
distance from any fixed origin. Then VrF is the vector moment of a
force, F, at the end of the arm r. Another (not so immediate) appli-
cation of the divergence theorem gives
2VrP.v = 2VrF + 22e (44)
Thus, any distribution of stress, whether rotational or irrotational, may
be regarded as in equilibrium. Given any stress in a body, terminating
at its boundary, the body will be in equilibrium both as regards trans-
lation and rotation. Of course, the boundary discontinuity in the stress
has to be reckoned as the equivalent of internal divergence in the
appropriate manner. Or, more simply, let the stress fall off continuously
from the finite internal stress to zero through a thin surface-layer. We
then have a distribution of forces and torques in the surface-layer which
equilibrate the internal forces and torques.
To illustrate; we know that Maxwell arrived at a peculiar stress,
compounded of a tension parallel to a certain direction, and an equal
lateral pressure, which would account for the mechanical actions apparent
between electrified bodies ; and endeavoured similarly to determine the
stress in the interior of a magnetized body to harmonize with the similar
external magnetic stress of the simple type mentioned. This stress in
a magnetized body I believe to be thoroughly erroneous ; nevertheless,
so far as accounting for the forcive on a magnetized body is concerned,
it will, when properly carried out with due attention to surface-discon-
tinuity, answer perfectly well, not because it is the stress, but because
any stress would do the same, the only essential feature concerned being
the external stress in the air.
Here we may also note the very powerful nature of the stress-function,
considered merely as a mathematical engine, apart from physical reality.
For example, we may account for the forcive on a magnet in many
ways, of which the two most prominent are by means of forces on
imaginary magnetic matter, and by forces on imaginary electric currents,
in the magnet and on its surface. To prove the equivalence of these
two methods (and the many others) involves very complex surface-
and volume-integrations and transformations in the general case,
which may be all avoided by the use of the stress-function instead
of the forces.
§ 11. Next as regards the activity of the stress PA and the equivalent
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 535
translational, distortional, and rotational activities. The activity of P^
is P vq per unit area, if q be the velocity. Here
P.vq = ft.NQ1 + ?2.NQ2 + ?3.NQ3) .................. (45)
by (42) ; or, re- arranging,
P.vq = N(?1Q1-f?2Q2 + (?3Q3) = N2?Q = N?Q9, ............. (46)
where Q7 is the conjugate stress on the q-plane. That is, qtyq or 2 Qg
is the negative of the vector flux of energy expressing the stress-activity.
For we choose Pyx. so as to mean a pull when it is positive, and when
the stress P v works in the same sense with q, energy is transferred
against the motion, to the matter which is pulled.
The convergence of the energy-flux, or the divergence of <?Q}, is there-
fore the activity per unit volume. Thus
= q(i div Qx + j div Q2 + k div Q3) + (Q.Vfc + Q2V<?2 + Q3V?3) (47)
= q(V1P1 + V2P2 + V3P3) + P1V1q + P2V2q + P3V3q, ............ (48)
where the first form (47) is generally most useful. Or
........................ (49)
where the first term on the right is the translational activity, and the
rest is the sum of the distortional and rotational activities. To separate
the latter introduce the strain-velocity vectors (analogous to Pv P2, P3)
Pi = 4(V?i + V1q), P2 = KV<?2 + V2q), P3 = i(V<?3 + V3q); (50)
and generally pA = £(V.qN + NV.q) ............................ (51)
Using these we obtain
= 2 Qp + JQiVi curl q + |Q2Vj curl q + JQ3Vk curl q
= 2Qp + ecurlq .................................................... (52)
Thus 2 Qp is the distortional activity and e curl q the rotational
activity. But since the distortion and the rotation are quite inde-
pendent, we may put 2 Pp for the distortional activity ; or else use the
self-conjugate stress, and write it J2 (P + Q)p.
§ 12. In an ordinary "elastic solid." when isotropic, there is elastic
resistance to compression and to distortion. We may also imaginably
have elastic resistance to translation and to rotation ; nor is there,
so far as the mathematics is concerned, any reason for excluding
dissipative resistance to translation, distortion, and rotation ; and
kinetic energy may be associated with all three as well, instead of with
the translation alone, as in the ordinary elastic solid.
Considering only three elastic moduli, we have the old k and n of
Thomson and Tait (resistance to compression and rigidity), and a new
coefficient, say n^ such that
e-^curlD, ............................... (53)
if D be the displacement and 2e the torque, as before.
536 ELECTEICAL PAPERS.
The stress on the i-plane (any plane) is
P! = n(VD1 + VjD) + i(k - |w) div D + 14 V curl D . i
= (n + n1)VlV + (n-nl)VDl + (k-*n)idiv'D', .......... (54)
and its conjugate is
Q! = n(VDl + VjD) + i(k - §n) div D - ^(VjD - V^)
= (n-nl)V1D + (n + nl)VD1 + i(1c-%n)di\'D; ........... (55)
from which
2JD1 ...... (56)
is the i-component of the translational force ; the complete force P is
therefore
............... (57)
or, in another form, if P = - k div D,
P being the isotropic pressure,
F= - VP + n( V2D + JV div D)-^ curl2 D, ........... (58)
remembering (23) and (53).
We see that in (57) the term involving divD may vanish in a com-
pressible solid by the relation nl = k + ^n'} this makes
n + nl = k + ^n, nl-n = k-^n, ............... (59)
which are the moduli, longitudinal and lateral, of a simple longitudinal
strain ; that is, multiplied by the extension, they give the longitudinal
traction, and the lateral traction required to prevent lateral contraction.
The activity per unit volume, other than translational, is
2 QV? = (7i - nOfaD. Vft + V2D. Vq2 + V3D. V&)
+ (n + ThXVA-V?! + V£2. V
+ (&-§?i)divDdivq
= ^(VjD . Vfr + V2D . V?2 + V3D .
+ (k - f/i)div D div q + Wj curl D curl q; ........................... (60)
or, which is the same,
iv D)2 + ^(curl D)2 - Jw(div D)2
+ VDr V^ + VD2. V2D + V£3. V3D (61)
where the quantity in square brackets is the potential energy of an
infinitesimal distortion and rotation. The italicized reservation appears
to be necessary, as we shall see from the equation of activity later, that
the convection of the potential energy destroys the completeness of the
statement
if U be the potential energy.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 537
In an elastic solid of the ordinary kind, with n^ = 0, we have
P v = n(2 curl VDN + VN curl D), )
F . -ncurl'D. /*
In the case of a medium in which n is zero but ?^ finite (Sir W.
Thomson's rotational ether),
F . -nlCurl«D. "
Thirdly, if we have both k = - ^n and n = nv then
P,v = 2» curl VDN,
f64^
F =-2WcurPD,/
i.e.) the sums of the previous two stresses and forces.
§ 13. As already observed, the vector flux of energy due to the stress
is -2Q<z = -Q3£= -(Qifc + Qsfc + Qsfe) (65)
Besides this, there is the flux of energy
*L(U+T)
by convection, where U is potential and T kinetic energy. Therefore,
represents the complete energy-flux, so far as the stress and motion are
concerned. Its convergence increases the potential energy, the kinetic
energy, or is dissipated. But if there be an impressed translational
force f, its activity is fq. This supply of energy is independent of the
convergence of W. Hence
fq = $+Z7+ j+div[q(^7+T)-2Q^] (67)
is the equation of activity.
But this splits into two parts at least. For (67) is the same as
(f+F)q + 2Qv<?=$ + U + T + div q(£7 + T), . (68)
and the translational portion may be removed altogether. That is,
if the quantities with the zero suffix are only translationally involved.
For example, if
•a«
.(70)
as in fluid motion, without friction al or elastic forces associated with
the translation, then
qr, ..................... (71)
if T=^pq2, the kinetic energy per unit volume. The complete form
(69) comes in by the addition of elastic and frictional resisting forces.
So, deducting (69) from (68), there is left
Z1!), ................ (72)
538 ELECTRICAL PAPERS.
where the quantities with suffix unity are connected with the distortion
and the rotation, and there may plainly be two sets of dissipative terms,
and of energy (stored) terms. Thus the relation
+n+n* curlD (73)
will bring in dissipation and kinetic energy, as well as the former
potential energy of rotation associated with nr
That there can be dissipative terms associated with the distortion is
also clear enough, remembering Stokes's theory of a viscous fluid.
Thus, for simplicity, do away with the rotating stress, by putting e = 0,
making P^ and Q v identical. Then take the stress on the i-plane to be
given by
P = (n + /4 + v£] ( VA + viD) - i(P + 1 (n + /4 + v^\ div D), (74)
\ rdt dt2/ { d\ dt dt2/ }
and similarly for any other plane ; where P = - k div D.
When ft = 0, v = 0, we have the elastic solid with rigidity and com-
pressibility. When 7i = 0, v = 0, we have the viscous fluid of Stokes.
When v — 0 only, we have a viscous elastic solid, the viscous resistance
being purely distortional, and proportional to the speed of distortion.
But with 7i, //,, v, all finite, we still further associate kinetic energy with
the potential energy and dissipation introduced by n and /*.
We have
for infinitesimal strains, omitting the effect of convection of energy;
where
+ V2q) + Vfc(Vft + V3q)], .......... ('
- t(div q)2 + Vft(Vft + Vtf) + V32(V<fe + V2q) + V?s(Vft + V8q)], ....... ('
^ 0
Observe that T2 and Q2 only differ in the exchange of /x to Jv ; but Z72,
the potential energy, is not the same function of n and D that T2 is of v
and q. But if we take k = 0, we produce similarity. An elastic solid
having no resistance to compression is also one of Sir W. Thomson's
ethers.
When n = 0, /* = 0, v = 0, we come down to the frictionless fluid, in
which
f-vp=/°' .............................. (78)
and 2PV?= -Pdivq, ........................... (79)
with the equation of activity
fq=r/+r+div(C7+r+P)q, ................... (80)
the only parts of which are not always easy to interpret are the Pq term,
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 539
and the proper measure of U. By analogy, and conformably with more
general cases, we should take
P = - k div D, and U= J&(div D)2,
reckoning the expansion or compression from some mean con
The Electromagnetic Equations in a Moving Medium.
§ 14. The study of the forms of the equation of activity in purely
mechanical cases, and of their interpretation, is useful, because in
the electromagnetic problem of a moving medium we have still
greater generality, and difficulty of safe and sure interpretation. To
bring it as near to abstract' dynamics as possible, all we need say
regarding the two fluxes, electric displacement D and magnetic induc-
tion B, is that they are linear functions of the electric force E and
magnetic force H, say
B = /*H, D = cE, ........................ (81)
where c and //, are linear operators of the symmetrical kind, and that
associated with them are the stored energies U and T, electric and
magnetic respectively (per unit volume), given by
Z7=|ED, r=JHB ........................ (82)
In isotropic media c is the permittivity, /* the inductivity. It is
unnecessary to say more regarding the well-known variability of p. and
hysteresis than that a magnet is here an ideal magnet of constant
inductivity.
As there may be impressed forces, E is divisible into the force of the
field and an impressed part ; for distinctness, then, the complete E may
be called the " force of the flux " D. Similarly as regards H and B.
There is also waste of energy (in conductors, namely) at the rates
C^EC, £2 = HK ....................... (83)
where the fluxes C and K are also linear functions of E and H respec-
tively; thus
C = &E, K = ^H, ........................ (84)
where, when the force is parallel to the flux, and k is scalar, it is the
electric conductivity. Its magnetic analogue is g, the magnetic con-
ductivity. That is, a magnetic conductor is a (fictitious) body which
cannot support magnetic force without continuously dissipating energy.
Electrification is the divergence of the displacement, and its analogue,
magnetification, is the divergence of the induction ; thus
/o = divD, o- = divB, .................... (85)
are their volume-densities. The quantity o- is probably quite fictitious,
like K.
According to Maxwell's doctrine, the true electric current is always
circuital, and is the sum of the conduction-current and the current of
displacement, which is the time-rate of increase of the displacement.
540 ELECTRICAL PAPERS.
But, to preserve circuitality, we must add the convection-current when
electrification is moving, so that the true current becomes
............................. (86)
where q is the velocity of the electrification p. Similarly
G = £ + B + qo- ............................. (87)
should be the corresponding magnetic current.
§ 15. Maxwell's equation of electric current in terms of magnetic
force in a medium at rest, say,
curl HT = C + D,
where E1 is the force of the field, should be made, using H instead,
curl(H-h0) = C + I) + q/>,
and here h0 will be the intrinsic force of magnetization, such that /xh0
is the intensity of intrinsic magnetization. But I have shown that
when there is motion, another impressed term is required, viz., the
motional magnetic force
h = VDq, .................................. (88)
making the first circuital law become
curl(H-h0-h) = J = C + D + q/> .................. (89)
Maxwell's other connection to form the equations of propagation is
made through his vector-potential A and scalar potential Mf. Finding
this method not practically workable, and also not sufficiently general,
I have introduced instead a companion equation to (89) in the form
-curl(E-e0-e) = G = K + B + qo-, ............... (90)
where e0 expresses intrinsic force, and e is the motional electric force
given by
e = VqB, ................................ (91)
which is one of the terms in Maxwell's equation of electromotive force.
As for e0, it includes not merely the force of intrinsic electrization,
the analogue of intrinsic magnetization, but also the sources of energy,
voltaic force, thermoelectric force, etc.
(89) and (90) are thus the working equations, with (88) and (91) in
case the medium moves; along with the linear relations before
mentioned, and the definitions of energy and waste of energy per unit
volume. The fictitious K and o- are useful in symmetrizing the equa-
tions, if for no other purpose.
Another way of writing the two equations of curl is by removing the
e and h terms to the right side. Let
curlh=j,
-curie =g, G + g = G0.
Then (89) and (90) may be written
curl(H-h0)= J0 = C
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 541
So far as circuitality of the current goes, the change is needless, and
still further complicates the make-up of the true current, supposed now
to be J0. On the other hand, it is a simplification on the left side,
deriving the current from the force of the flux or of the field more
simply.
A question to be settled is whether J or J0 should be the true
current. There seems only one crucial test, viz., to find whether e0J
or e0J0 is the rate of supply of energy to the electromagnetic system by
an intrinsic force e0. This requires, however, a full and rigorous
examination of all the fluxes of energy concerned.
The Electromagnetic Flux of Energy in a stationary Medium.
§ 1 6. First let the medium be at rest, giving us the equations
curl(H-h0) = J = C + D, (94)
-curl(E-eo)=G = K + B (95)
Multiply (94) by (E - e0), and (95) by (H - h0), and add the results.
Thus,
(E - e0) J + (H - hc)G = (E - e0) curl (H - h0) - (H - h0) curl (E - e0),
which, by the formula (25), becomes
e0J + h0G = EJ + HG + div V(E - e0)(H - h0) ;
or, by the use of (82), (83),
e0J-fh0G = £+£7+ J+divW, (96)
where the new vector W is given by
W=V(E-e0)(H-h0) (97)
The form of (96) is quite explicit, and the interpretation sufficiently
clear. The left side indicates the rate of supply of energy from
intrinsic sources. Thus, (Q+ U+f) shows the rate of waste and of
storage of energy in the unit volume. The remainder, therefore,
indicates the rate at which energy is passed out from the unit volume ;
and the flux W represents the flux of energy necessitated by the
postulated localization of energy and its waste, when E and H are
connected in the manner shown by (94) and (95).
There might also be an independent circuital flux of energy, but,
being useless, it would be superfluous to bring it in.
The very important formula (97) was first discovered and interpreted
by Professor Poynting, and independently discovered and interpreted
a little later by myself in an extended form. It will be observed that
in my mode of proof above there is no limitation as to homogeneity or
isotropy as regards the permittivity, inductivity, and conductivity.
But c and //. should be symmetrical. On the other hand, k and g do
not require this limitation in deducing (97).*
* The method of treating Maxwell's electromagnetic scheme employed in the
text (first introduced in " Electromagnetic Induction and its Propagation," The.
Electrician, January 3, 1885, and later) may, perhaps, be appropriately termed the
542 ELECTRICAL PAPERS.
It is important to recognize that this flux of energy is not dependent
upon the translational motion of the medium, for it is assumed explicitly
to be at rest. The vector W cannot, therefore, be a flux of the kind
Q9<? before discussed, unless possibly it be merely a rotating stress that
is concerned.
The only dynamical analogy with which I am acquainted which
seems at all satisfactory is that furnished by Sir W. Thomson's theory
of a rotational ether. Take the case of e0 = 0, h0 = 0, k = 0, g = 0, and
c and //. constants, that is, pure ether uncontaminated by ordinary
matter. Then
curlH = cE, ................................ (98)
-curlE = yaH ................................. (99)
Now, let H be velocity, /A density; then, by (99), -curlE is the
translational force due to the stress, which is, therefore, a rotating
stress; thus,
P^ = VEN, Q^V = VNE; .................. (100)
and 2E is the torque. The coefficient c represents the compliancy or
reciprocal of the quasi-rigidity. The kinetic energy |/*H2 represents
the magnetic energy, and the potential energy of the rotation represents
the electric energy ; whilst the flux of energy is VEH. For the activity
of the torque is
and the translational activity is
-HcurlE.
Their sum is - div VEH,
making VEH the flux of energy.*
All attempts to construct an elastic-solid analogy with a distortional
stress fail to give satisfactory results, because the energy is wrongly
localized, and the flux of energy incorrect. Bearing this in mind, the
above analogy is at first sight very enticing. But when we come to
Duplex method, since its characteristics are the exhibition of the electric,
magnetic, and electromagnetic relations in a duplex form, symmetrical with
respect to the electric and magnetic sides. But it is not merely a method of
exhibiting the relations in a manner suitable to the subject, bringing to light
useful relations which were formerly hidden from view by the intervention of the
vector-potential and its parasites, but constitutes a method of working as well.
There are considerable difficulties in the way of the practical employment of
Maxwell's equations of propagation, even as they stand in his treatise. These
difficulties are greatly magnified when we proceed to more general cases, involving
heterogeneity and eolotropy and motion of the medium supporting the fluxes.
The duplex method supplies what is wanted. Potentials do not appear, at least
initially. They are regarded strictly as auxiliary functions which do not represent
any physical state of the medium. In special problems they may be of great
service for calculating purposes ; but in general investigations their avoidance
simplifies matters greatly. The state of the field is settled by £ and H, and these
are the primary objects of attention in the duplex system.
*This form of application of the rotating ether I gave in The Electrician,
January 23, 1891, p. 360.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 543
remember that the d/dt in (98) and (99) should be d/cfy and find extra-
ordinary difficulty in extending the analogy to include the conduction
current, and also remember that the electromagnetic stress has to be
accounted for (in other words, the known mechanical forces), the per-
fection of the analogy, as far as it goes, becomes disheartening. It
would further seem, from the explicit assumption that q = 0 in obtaining
W above, that no analogy of this kind can be sufficiently comprehensive
to form the basis of a physical theory. We must go altogether beyond
the elastic solid with the additional property of rotational elasticity. I
should mention, to avoid misconception, that Sir W. Thomson does not
push the analogy even so far as is done above, or give to //, and c the
same interpretation. The particular meaning here given to /A is that
assumed by Professor Lodge in his " Modern Views of Electricity," on
the ordinary elastic-solid theory, however. I have found it very con-
venient from its making the curl of the electric force be a Newtonian
force (per unit volume). When impressed electric force e0 produces
disturbances, their real source is, as I have shown, not the seat of e0,
but of curl e0. So we may with facility translate problems in electro-
magnetic waves into elastic-solid problems by taking the electromagnetic
source to represent the mechanical source of motion, impressed New-
tonian force.
Examination of the Flux of Energy in a Moving Medium*, and Establishment
of the Measure of " True " Current.
§ 17. Now pass to the more general case of a moving medium with
the equations
curlH^ curl(H-h0-h) = J = C + D + q/3, (101)
- curlE1= -curl(E-e0-e) = G = K + B + qo-, (102)
where Ej is, for brevity, what the force E of the flux becomes after
deducting the intrinsic and motional forces ; and similarly for Hr
From these, in the same way as before, we deduce
(e0 + e)J + (h0 + h)G = EJ + HG + divVE1H1; (103)
and it would seem at first sight to be the same case again, but with
impressed forces (e + e0) and (h + h0) instead of e0 and h0, whilst the
Poyntirig flux requires us to reckon only Ej and Hj as the effective
electric and magnetic forces concerned in it.*
*It will be observed that the constant 4?r, which usually appears in the
electrical equations, is absent from the above investigations. This demands a
few words of explanation. The units employed in the text are rational units,
founded upon the principle of continuity in space of vector functions, and the
corresponding appropriate measure of discontinuity, viz. , by the amount of diver-
gence. In popular language, the unit pole sends out one line of force, in the
rational system, instead of 4?r lines, as in the irrational system. The effect of the
rationalization is to introduce 4?r into the formulae of central forces and potentials,
and to abolish the swarm of 47r's that appears in the practical formulas of the
practice of theory on Faraday- Max well lines, which receives its fullest and most
appropriate expression in the rational method. The rational system was explained
by me in The Electrician in 1882, and applied to the general theory of potentials
544 ELECTRICAL PAPERS.
But we must develop (Q+ U+f) plainly first. We have, by (86),
(87), used in (103),
e0J + h0G = E(C + D + q/)) + H(K + B + qo-)-(eJ + hG)+divVE1H1. (104)
Now here we have
(IDo)
Comparison of the third with the second form of (105) defines the
generalized meaning of c when c is not a mere scalar. Or thus,
= JM? + JcJStf + faJE* + 6.AE, + c,sE,Es + CaEiE* ...... ( 1 06)
representing the time-variation of U due to variation in the c's only.
Similarly f = HB - JH/iH = HB - f^ ................... (107)
with the equivalent meaning for p. generalized.
Using these in (104), we have the result
e0J + h0G = (Q + U+ T} + q(E/) + Ho-) + (JBcB + JH/1H)
-(eJ + hGJ + divVEjHj. (108)
Here we have, besides (Q+ U+T\ terms indicating the activity of a
and connected functions in 1883. (Reprint, vol. 1, p. 199, and later, especially
p. 262. ) I then returned to irrational formulas because I did not think, then, that
a reform of the units was practicable, partly on account of the labours of the B. A.
Committee on Electrical Units, and partly on account of the ignorance of, and
indifference to, theoretical matters which prevailed at that time. But the circum-
stances have greatly changed, and I do think a change is now practicable. There
has been great advance in the knowledge of the meaning of Maxwell's theory, and
a diffusion of this knowledge, not merely amongst scientific men, but amongst a
large body of practicians called into existence by the extension of the practical
applications of electricity. Electricity is becoming, not only a master science, but
also a very practical one. It is fitting, therefore, that learned traditions should
not be allowed to control matters too greatly, and that the units should be ration-
alized. To make a beginning. I am employing rational units throughout in my
work on " Electromagnetic Theory," commenced in The Electrician in January,
1891, and continued as fast as circumstances will permit; to be republished in
book form. In Section XVII. (October 16, 1891, p. 655) will be found stated
more fully the nature of the change proposed, and the reasons for it. I point out,
in conclusion, that as regards theoretical treatises and investigations, there is no
difficulty in the way, since the connection of the rational and irrational units may
be explained separately ; and I express the belief that when the merits of the
rational system are fully recognised, there will arise a demand for the rationaliza-
tion of the practical units. We are, in the opinion of men qualified to judge,
within a measurable distance of adopting the metric system in England. Surely
the smaller reform I advocate should precede this. To put the matter plainly, the
present system of units contains an absurdity running all through it of the same
nature as would exist in the metric system of common units were we to define the
unit area to be the area of a circle of unit diameter. The absurdity is only
different in being less obvious in the electrical case. It would not matter much if
it were not that electricity is a practical science.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 545
translational force. Thus, E/> is the force on electrification p, and Eqp
its activity. Again,
so that we have c = -^ - qV . c,
ot
.(109)
and, similarly, (L = J- - qV . /*,
the generalized meaning of which is indicated by
^2 + JEcE = -iE(qV.c)E= -qVZ7c; (110)
where, in terms of scalar products involving E and D,
-qV£/"c= - J(E.qV.D-D.qV.E) (Ill)
This is also the activity of a translational force. Similarly,
'dT
— (112)
is the activity of a translational force. Then again,
-(eJ + hG) = - JVqB-GVDq = q(VJB + VDG) ....... (113)
expresses a translational activity. Using them all in (108), it becomes
. (114)
It is clear that we should make the factor of q be the complete trans-
lational force. But that has to be found ; and it is equally clear that,
although we appear to have exhausted all the terms at disposal, the
factor of q in (114) is not the complete force, because there is no term
by which the force on intrinsically magnetized or electrized matter
could be exhibited. These involve e0 and h0. But as we have
.................. (115)
a possible way of bringing them in is to add the left member and
subtract the right member of (115) from the right member of (114);
bringing the translational force to f, say, where
f=E/> + Ho--VZ7c-V^ + V(J+j0)B + VD(G + g0) ...... (116)
But there is still the right number of (115) to be accounted for. We
have
-div(Veh0 + Ve0h) = ej0 + hg0 + e0j+h0g, .......... (117)
and, by using this in (114), through (115), (116), (117), we bring it to
e0J + h0G = (Q + U+ T) + fq - (e0j + h0g) + div (VE^ - Veh0 - Ve0h)
+ |(^c + ^); (US)
H.E.P. — VOL. II. 2M
546 ELECTRICAL PAPERS.
or, transferring the e0, h0 terms from the right to the left side,
= Q+i/r+r+fq+div(VE1H1-Veh0-Ve0h)+^(C7c+r,). (119)
Here we see that we have a correct form of activity equation, though it
may not be the correct form. Another form, equally probable, is to be
obtained by bringing in Yeh ; thus
div Veh = h curl e - e curl h = - (ej + hg) = q( VjB + VDg), (120)
which converts (119) to
e0Jo+h A = Q+ ^7+r+Fq+div(VE1Hl -Veh-Veh0-Ve0li)+|( Ue+Tfl\ (121)
where F is the translational force
P = B/) + H<r-VK-Vr/t + VcurlH.B + VcurlB.D, ...... (122)
which is perfectly symmetrical as regards E and H, and in the vector
products utilizes the fluxes and their complete forces, whereas former
forms did this only partially. Observe, too, that we have only been
able to bring the activity equation to a correct form (either (119) or
(122)) by making e0J0 be the activity of intrinsic force e0, which requires
that J0 should be the true electric current, according to the energy
criterion, not J.
§18. Now, to test (119) and (121), we must interpret the flux in
(121), or say
Y = VE1H1-Veh-Veh0-Ve0h, ................ (123)
which has replaced the Poynting flux VEjHj when q = 0, along with
the other changes. Since Y reduces to VEjHj when q = 0, there must
still be a Poynting flux when q is finite, though we do not know its
precise form of expression. There is also the stress flux of energy and
the flux of energy by convection, making a total flux
ro)f ............ (124)
where W is the Poynting flux, and - 2 Qj that of the stress, whilst
q(tr0 + 7T0) means convection of energy connected with the translational
force. We should therefore have
e0J0 + h0G0 = (£+ U+f) + (Q0+ tf0 + T0) + divX ...... (125)
to express the continuity of energy. More explicitly
e0J0 + hoGo = Q + U + f + div [W + q([7+ T)]
But here we may simplify by using the result (69) (with, however,
f put = 0), making (126) become
where S is the torque, and a the spin.
Comparing this with (121), we see that we require
W + q(CT+r)-2Q0=VB1H1-Veh-Ve0li--Veho ...... (128)
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 547
with a similar equation when (119) is used instead; and we have now
to separate the right member into two parts, one for the Poynting flux,
the other for the stress flux, in such a way that the force due to the
stress is the force F in (121), (122), or the force fin (119), (116); or
similarly in other cases. It is unnecessary to give the failures; the
only one that stands the test is (121), which satisfies it completely.
I argued that
W = V(E-e0)(H-h0) ...................... (129)
was the probable form of the Poynting flux in the case of a moving
medium, not VE^Hp because when a medium is endowed with a uniform
translational motion, the transmission of disturbances through it takes
place just as if it were at rest. With this expression (129) for W, we
have, identically,
VEjHj-Veh-Veoh-Veho^W-VeH-VEh ........ (130)
Therefore, by (128) and (130), we get
2Q^ = VeH + VEh + q(Z7+77), ................. (131)
to represent the negative of the stress flux of energy, so that, finally,
the fully significant equation of activity is
(132)
This is, of course, an identity, subject to the electromagnetic equations
we started from, and is only one of the multitude of forms which may
be given to it, many being far simpler. But the particular importance
of this form arises from its being the only form apparently possible
which shall exhibit the principle of continuity of energy without out-
standing terms, and without loss of generality ; and this is only possible
by taking J0 as the proper flux for e0 to work upon.*
* In the original an erroneous estimate of the value of ('d/'dt)(tfc+ T^) was used
in some of the above equations. This is corrected. The following contains full
details of the calculation. We require the value of (9/90 Uc, or of £E0c/90E,
where 3e/'<3£ is the linear operator whose components are the time-variations (for
the same matter) of those of r. The calculation is very lengthy in terms of these
six components. But vectorially it is not difficult. In (27), (28) we have
D = cE = i.CE
if the vectors c1? c2, C3 are given by
Ci = ten+Jrja + lKjg, C,, = ira +Jr22 + kc23, c, =
We, therefore, have
The part played by the dots is to clearly separate the scalar products.
Now suppose that the eolotropic property symbolized by c is intrinsically
unchanged by the shift of the matter. The mere translation does not, therefore,
affect it, nor does the distortion ; but the rotation does. For if we turn round
an eolotropic portion of matter, keeping E unchanged, the value of U is altered
by the rotation of the principal axes of c along with the matter, so that a torque
is required.
In equation (132a), then, to produce (132&), we keep E constant, and let the six
548 ELECTRICAL PAPERS.
Derivation of the Electric and Magnetic Stresses and Forces from the
Flux of Energy.
§19. It will be observed that the convection of energy disappears by
occurring twice oppositely signed ; but as it comes necessarily into the
expression for the stress flux of energy, I have preserved the cancelling
terms in (132). A comparison of the stress flux with the Poynting
flux is interesting. Both are of the same form, viz., vector products of
the electric and magnetic forces with convection terms ; but whereas in
the latter the forces in the vector-product are those of the field (i.e., only
intrinsic forces deducted from E and H), in the former we have the
motional forces e and h combined with the complete E and H of the
fluxes. Thus the stress depends entirely on the fluxes, however they
be produced, in this respect resembling the electric and magnetic
energies.
To exhibit the stress, we have (131), or
(133)
Qi?i + Q2?2 + Q3?3 = VeH + VEh +
In this use the expressions for e and h, giving
2Q2 = VHVBq + VEVDq + q(tf+r)
= B.Hq - q .HB + D. Eq - q.ED + q( U+ T)
where observe the singularity that q( U+ T) has changed its sign. The
first set belongs to the magnetic, the second to the electric stress, since
we see that the complete stress is thus divisible.
vectors i, j, k, C1} C2, C3 rotate as a rigid body with the spin a = Jcurlq. But
when a vector magnitude i is turned round in this way, its rate of time-change
is Vai. Thus, for 'dfdt, we may put Va throughout. Therefore, by (1326),
E|-CE = Efvai.Cj + Vaj .c2 + Vak.c3 ^E + E^i .VaCj+j .Vac2+k . Vac3^E. (132c)
In this use the parallelepipedal transformation (12), and it becomes
by (132a), if D' is conjugate to D; that is, D/ = c/E = Ec. So, when c = c', as in
the electrical case, we have
£ = p^E = DVEa = aVDE,
and similarly
.(132e)
= BVHa = aVBH.
ot ot
Now the torque arising from the stress is (see (139) )
s = VDE+VBH,
sowehave ^-( Uc + TV) = Sa = torque x spin ........................ (132/)
ot
The variation allowed to i, j, k may seem to conflict with their constancy (as
reference vectors) in general. But they merely vary for a temporary purpose,
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 549
The divergence of 2 Qq being the activity of the stress-variation per
unit volume, its N-component is the activity of the stress per unit
surface, that is,
(NB.Hq - Nq. T) + (ND. Eq - Nq. U)
= q(H.BN + E.DN-NE7-NT) = P.vq .......... (135)
The stress itself is therefore
............... (136)
divided into electric and magnetic portions. This is with restriction
to symmetrical /x and c, and with persistence of their forms as a particle
moves, but is otherwise unrestricted.
Neither stress is of the symmetrical or irrotational type in case of
eolotropy, and there appears to be no getting an irrotational stress save
by arbitrary assumptions which destroy the validity of the stress as a
correct deduction from the electromagnetic equations. But, in case of
isotropy,' with consequent directional identity of E and D, and of H
and B, we see, by taking N in turns parallel to, or perpendicular to E
in the electric case, and to H in the magnetic case, that the electric
stress consists of a tension U parallel to E combined with an equal
lateral pressure, whilst the magnetic stress consists of a tension T
parallel to H combined with an equal lateral pressure. They are, in
fact, Maxwell's stresses in an isotropic medium homogeneous as regards
fj. and c. The difference from Maxwell arises when /A and c are variable
(including abrupt changes from one value to another of ft and c), and
being fixed in the matter instead of in space. But we may, perhaps better, discard
i, j, k altogether, and use any independent vectors, 1, m, n instead, making
D = (l.Cj + m.Cjj + n.CjJE, .............................. (1320)
wherein the c's are properly chosen to suit the new axes. The calculation then
proceeds as before, half the value of 'dUJ'dt arising from the variation of 1, m, n,
and the other half from the c's, provided c is irrotational.
Or we may choose the three principal axes of c in the body, when 1, m, n will
coincide with, and therefore move with them.
Lastly, we may proceed thus : —
(132A)
That is, replace 'd/'dt by Va when the operands are E and D. This is the
correct result, but it is not easy to justify the process directly and plainly ;
although the clue is given by observing that what we do is to take a difference,
from which the time-variation of E disappears.
If it is D that is kept constant, the result is 2aVED, the negative of the above.
It is also worth noticing that if we split up E into Ex + £3 we shall have
=a[~V(E1c)E2 - VE^cE,)] , }
b $ ......................... (132*)
= •[Y0M4 - VE2(cE1) J . J
These are only equal when c = c', or EC = cE ; so that, in the expansion of the
torque,
VDE =
the cross-torques are not VD^ and VDjEj, which are unequal, but are each equal
to half the sum of these vector-products.
550 ELECTRICAL PAPERS.
when there is intrinsic magnetization, Maxwell's stresses and forces
being then different.
The stress on the plane whose normal is VEH, is
V0EH V0EH
reducing simply to a pressure (U+ T), in lines parallel to V7EH, in case
of isotropy.
§ 20. To find the force F, we have
FN = div Q,v = div (D . EN - N CT+ B . HN - NT)
= N[E/> + V curl E.D-V*7C + etc.], ............................ (138)
where the unwritten terms are the similar magnetic terms. This being
the N-component of F, the force itself is given by (122), as is necessary.
It is Vcurlh0.B that expresses the translational force on intrinsically
magnetized matter, and this harmonizes with the fact that the flux B
due to any impressed force h0 depends solely upon curl h0.
Also, it is - V^ that explains the forcive on elastically magnetized
matter, e.g., Faraday's motion of matter to or away from the places of
greatest intensity of the field, independent of its direction.
If S be the torque, it is given by
therefore S = VDE+ VBH ........................... (139)
But the matter is put more plainly by considering the convergence
of the stress flux of energy and dividing it into translational and other
parts. Thus
), ...(140)
where the terms following Fq express the sum of the distortional and
rotational activities.
Shorter Way of going from the Circuital Equations to the Fliu1 of
Energy, Stresses, and Forces.
§21. I have given the investigation in ^ 17 to 19 in the form in
which it occurred to me before I knew the precise nature of the results,
being uncertain as regards the true measure of current, the proper form
of the Poynting flux, and how it worked in harmony with the stress
flux of energy. -But knowing the results, a short demonstration may
be easily drawn up, though the former course is the most instructive.
Thus, start now from
on the assumptioual understanding that J0 and G0 are the currents which
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 551
make e0J0 and h0G0 the activities of e0 and h0 the intrinsic forces. Then
e0J0 + h0G0 = EJ0 + HG0 + divW, .................. (142)
where W - V(E - e0)(H - h0) ; ...................... (143)
and we now assume this to be the proper form of the Poynting flux.
Now develop EJ0 and HG0 thus :—
EJ0 + HG0 = E(C + D + q/> + curl h) + H(K + B + qo- - curl e), by (93) ;
= Ql + U +U, + Eqp + E curl VDq
+ Q3 + T+ Tu + Hqo- + H curl VBq, by (88) and (91) ;
= C>i + U+ Uc + Eq/> + E(D div q + qy. D - q div D - Dv.q)
= Ql + U+ Uc + 2 U div q + E. qV. D - E . Dv. q
+ magnetic terms,
+ magnetic terms
Nowhere qy.Z7= JE.qV.D + JD.qV.E,
so that the terms in the third pair of brackets in (144) represent
with the generalized meaning before explained. So finally
EJ0 + HG0 = g+6* + r+divq(Z7+r) + ^(f7c + r/i)
+ (^divq-E.DV.q) + (rdivq-H.BV.q), ...(145)
which brings (142) to
ivq-H.BV.q), (146)
which has to be interpreted in accordance with the principle of con-
tinuity of energy.
Use the form (127), first, however, eliminating Fq by means of
which brings (127) to
e0J0 + hl)G0 = (t)+^+r+div{W + q(/:T + r)}-i:Qv^ + Sa; (147)
and now, by comparison of (147) with (146) we see that
-Sa + 2QV(7 = (E.DV.q-^divq)-35': + (H.BV.q-rdivq)-^;i; (148)
ot ot
from which, when /a and c do not change intrinsically, we conclude that
552 . ELECTRICAL PAPERS.
as before. In this method we lose sight altogether of the translational
force which formed so prominent an object in the former method as a
guide.
Some JRemarks on Hertz's Investigation relating to the Stresses.
§ 22. Variations of c and /*, in the same portion of matter may occur
in different ways, and altogether independently of the strain-variations.
Equation (146) shows how their influence affects the energy transforma-
tions ; but if we consider only such changes as depend on the strain,
i.e., the small changes of value which /x and c undergo as the strain
changes, we may express them by thirty -six new coefficients each (there
being six distortion elements, and six elements in //,, and six in c), and
so reduce the expressions for 'dUJ'dt and 'dT^/'dt in (148) to the form
suitable for exhibiting the corresponding change in QiV and in the stress
function P^. As is usual in such cases of secondary corrections, the
magnitude of the resulting formula is out of all proportion to the
importance of the correction-terms in relation to the primary formula
to which they are added.
Professor H. Hertz* has considered this question, and also refers to
von Helmholtz's previous investigation relating to a fluid. The c and /*
can then only depend on the density, or on the compression, so that a
single coefficient takes the place of the thirty -six. But I cannot quite
follow Hertz's stress investigation. First, I would remark that in
developing the expression for the distortional (plus rotational) activity,
he assumes that all the coefficients of the spin vanish identically ; this
is done in order to make the stress be of the irrotational type. But it
may easily be seen that the assumption is inadmissible by examining
its consequence, for which we need only take the case of c and //. intrin-
sically constant. By (139) we see that it makes S = 0, and therefore
(since the electric and magnetic stresses are separable), VHB = 0, and
VED = 0 ; that is, it produces directional identity of the force E and
the flux D, and of the force H and the flux B. This means isotropy,
and, therefore, breaks down the investigation so far as the eolotropic
application, with six /* and six c coefficients, goes. Abolish the assump-
tion made, and the stress will become that used by me above.
Another point deserving of close attention in Hertz's investigation,
relates to the principle to be followed in deducing the stress from the
electromagnetic equations. Translating into my notation it would
appear to amount to this, the a priori assumption that the quantity
-, l(r"> <150>
where v indicates the volume of a moving unit element undergoing
distortion, may be taken to represent the distortional (plus rotational)
activity of the magnetic stress. Similarly as regards the electric stress.
Expanding (150) we obtain
* Wiedemann's Annalen, v. 41, p. 369.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 553
Now the second circuital law (90) may be written
-e0) = K + + (Bdivq-BV.q) ........... (152)
Here ignore e0, K, and ignore the curl of the electric force, and we obtain,
by using (152) in (151),
H.BV.q-HBdivq + rdivq-^ = H.BV.q-rdivq-?^, (153)
ot ot
which represents the distortional activity (my form, not equating to
zero the coefficients of curl q in its development). We can, therefore,
derive the magnetic stress in the manner indicated, that is, from (150),
with the special meaning of 3B/3J later stated, and the ignorations or
nullifications.
In a similar manner, from the first circuital law (89), which may be
written
-DV.q), ........... (154)
we can, by ignoring the conduction-current and the curl of the mag-
netic force, obtain
, .............. (155)
which represents the distortional activity of the electric stress.
The difficulty here seems to me to make it evident a priori that (150),
with the special reckoning of 3B/d£, should represent the distortional
activity (plus rotational understood) ; this interesting property should,
perhaps, rather be derived from the magnetic stress when obtained by
a safe method. The same remark applies to the electric stress. Also,
in (150) to (155) we overlook the Poynting flux. I am not sure how
far this is intentional on Professor Hertz's part, but its neglect does
not seem to give a sufficiently comprehensive view of the subject.
The complete expansion of the magnetic distortional activity is, in
fact,
r-HG0; ...... (156)
and similarly, that of the electric stress is
tf-EJc, ...... (157)
It is the last term of (156) and the last term of (157), together,
which bring in the Poynting flux. Thus, adding these equations,
(158)
where (E J0 + HG0) = (e0J0 + h0G0) - div W ; .............. (159)
and so we come round to the equation of activity again, in the form
(146), by using (159) in (158).
554 ELECTRICAL PAPERS.
Modified Form of Stress-Vector, and Application to the Surface separating
two Regions.
§23. The electromagnetic stress, Pv of (149) and (136) may be put
into another interesting form. We may write it
NH.B) ...... (160)
Now, ND is the surface equivalent of div D and NB of div B ; whilst
VNE and VNH are the surface equivalents of curl E and curl H. We
may, therefore, write
P.v = £(Ep' + VDG') + £(Hcr/ + VJ/B), ............. (161)
and this is the force, reckoned as a pull, on unit area of the surface
whose normal is N. Here the accented letters are the surface equiva-
lents of the same quantities unaccented, which have reference to unit
volume.
Comparing with (122) we see that the type is preserved, except as
regards the terms in F due to variation of c and ^ in space. That is,
the stress is represented in (161) as the translational force, due to E
and H, on the fictitious electrification, magnetification, electric current,
and magnetic current produced by imagining E and H to terminate at
the surface across which' P v is the stress.
The coefficient J which occurs in (161) is understandable by sup-
posing the fictitious quantities ("matter" and "current") to be distri-
buted uniformly within a very thin layer, so that the forces E and H
which act upon them do not then terminate quite abruptly, but fall off
gradually through the layer from their full values on one side to zero
on the other. The mean values of E and H through the layer, that is,
JE and ^H, are thus the effective electric and magnetic forces on the
layer as a whole, per unit volume-density of matter or current ; or JE
and JH per unit surface-density when the layer is indefinitely reduced
in thickness.
Considering the electric field only, the quantities concerned are
electrification and magnetic current. In the magnetic field only they
are magnetification and electric current. Imagine the medium divided
into two regions A and B, of which A is internal, B external, and let N
be the unit normal from
the surface into the
external region. The
mechanical action be-
tween the two regions
is fully represented by
the stress P^v over their
interface, and the for-
cive of B upon A is
fully represented by the
E and H in B acting upon
the fictitious matter and
current produced on the boundary of B, on the assumption that E and
H terminate there. If the normal and PA- be drawn the other way,
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 555
thus negativing them both, as well as the fictitious matter and current
on the interface, then it is the forcive of A on B that is represented by
the action of E and H in A on the new interfacial matter and current.
That is, the E and H in the region A may be done away with alto-
gether, because their abolition will immediately introduce the fictitious
matter and current equivalent, so far as B is concerned, to the influence
of the region A. Similarly E and H in B may be abolished without
altering them in A. And, generally, any portion of the medium may
be taken by itself and regarded as being subjected to an equilibrating
system of forces, when treated as a rigid body.
§ 24. When c and /x do not vary in space, we do away with the forces
- %E'2Vc and - J-fl^V/*, and make the form of the surface and volume
translational forces agree. We may then regard every element of p or
of o- as a source sending out from itself displacement and induction
isotropically, and every element of J or Gr as causing induction or
displacement according to Ampere's rule for electric current and its
analogue for magnetic current. Thus
(163)
where rx is a unit vector drawn from the infinitesimal unit volume in
the summation to the point at distance r where E or H is reckoned.
Or, introducing potentials,
, .................. (165)
These apply to the whole medium, or to any portion of the same,
with, in the latter case, the surface matter and current included, there
being no E or H outside the region, whilst within it E and H are the
same as due to the matter and current in the whole region (" matter,"
p and cr; "current," J and G-). But there is no known general method
of finding the potentials when c and p vary.
We may also divide E and H into two parts each, say Ej and Hj due
to matter and current in the region A, and E.7, H.7 due to matter and
current in the region B surrounding it, determinable in the isotropic
homogeneous case by the above formulas. Then we may ignore Ej
and Hj in estimating the forcive on the matter and current in the region
A; thus,
^(H^ + VJ^ + ^E^ + VDA), .............. (166)
where o-1 = div Bx = div B, and Jl = curl Hj = curl H in region A, is the
resultant force on the region A, and
-(H^ + VJ.BJ + SCE^ + VDjG,,) ................ (167)
is the resultant force on the region B ; the resultant force on A due to
556 ELECTRICAL PAPERS.
its own E and H being zero, and similarly for B. These resultant forces
are equal and opposite, and so are the equivalent surface-integrals
2(HX+VJ{B2) + 2(E^ + VD2GO, ................ (168)
and SfHjoJ + VJ^B1) + 2(E^ + VD1GO, ................ (169)
taken over the interface. The quantity summed is that part of the
stress-vector, Pv, which depends upon products of the H of one region
and the B of the other, etc. Thus, for the magnetic stress only,
+ (H2.B2N - N. JH2B2) + (H^N - N.JH^), (170)
and it is the terms in the second and fourth brackets (which, be it
observed, are not equal) which together make up the magnetic part of
(168) and (169) or their negatives, according to the direction taken for
the normal; that is, since H1B2 = H2B1,
O = 2(HX + VJ{B2) = 2(H<r' + VJ'B)
= 2 F = 2(^0-2 + VJ^) = 2(H*Ji + VJA) = 2(Hcr + V JB), (17 1 )
where the first six expressions are interfacial summations, and the four
last summations throughout one or the other region, the last summation
applying to either region. No special reckoning of the sign to be
prefixed has been made. The notation is such that H = H1 + H2,
<r = 0^ + 0-2, etc., etc.
The comparison of the two aspects of electromagnetic theory is
exceedingly curious ; namely, the precise mathematical equivalence of
" explanation " by means of instantaneous action at a distance between
the different elements of matter and current, each according to its kind,
and by propagation through a medium in time at a finite velocity. But
the day has gone by for any serious consideration of the former view
other than as a mathematical curiosity.
Quaternionic Form of Stress-Vector.
§ 25. We may also notice the Quaternion form for the stress-function,
which is so vital a part of the mathematics of forces varying as the
inverse square of the distance, and of potential theory. Isotropy being
understood, the electric stress may be written
P^JctEN-iE], ........................... (172)
where the quantity in the square brackets is to be understood quater-
nionically. It is, however, a pure vector. Or,
ffil-S]
r-p —i
that is, not counting the factor Jc, the quaternion —^ is the same as
I-TO-I L •& J
the quaternion — ; or the same operation which turns N to E also
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 557
turns E to P^. Thus N, E, and P,v are in the same plane, and the
angle between N and E equals that between E and PA, ; and E and P^
are on the same side of N when E makes an acute angle with N. Also,
the tensor of P^ is U, so that its normal and tangential components are
U cos 20 and U sin 26, if 0 = NE.
Otherwise,
PJ,= -|C[ENE] (174)
since the quaternionic reciprocal of a vector has the reverse direction.
The corresponding volume translational force is
F= -cV[EVE], (175)
which is also to be understood quaternionically, and expanded, and
separated into parts to become physically significant. I only use the
square brackets in this paragraph to emphasize the difference in nota-
tion. It rarely occurs that any advantage is gained by the use of the
quaternion, in saying which I merely repeat what Professor Willard
Gibbs has been lately telling us ; and I further believe the disadvan-
tages usually far outweigh the advantages. Nevertheless, apart from
practical application, and looking at it from the purely quaternionic
point of view, I ought to also add that the invention of quaternions
must be regarded as a most remarkable feat of human ingenuity.
Vector analysis, without quaternions, could have been found by any
mathematician by carefully examining the mechanics of the Cartesian
mathematics ; but to find out quaternions required a genius.
Remarks on the Translational Force in Free Ether.
§ 26. The little vector Veh, which has an important influence in the
activity equation, where e and h are the motional forces
e = VqB, h = VDq,
has an interesting form, viz., by expansion,
Yeh = q.qVDB = ^.qVEH, (176)
if v be the speed of propagation of disturbances. We also have, in
connection therewith, the equivalence
eD = hB, (177)
always.
The translational force in a non-conducting dielectric, free from
electrification and intrinsic force, is
P = VJB + VDG + VjB + VDg,
or, approximately [vol. II., p. 509],
= VDB + VDB = ^VDB=I^VEH = ^ (178)
dt v2 dt v2
The vector VDB, or the flux of energy divided by the square of the
speed of propagation, is, therefore, the momentum (translational, not
558 ELECTRICAL PAPERS.
magnetic, which is quite a different thing), provided the force P is the
complete force from all causes acting, and we neglect the small terms
VjB and VDg.
But have we any right to safely write
where m is the density of the ether ? To do so is to assume that F is
the only force acting, and, therefore, equivalent to the time-variation of
the momentum of a moving particle.*
Now, if we say that there is a certain forcive upon a conductor
supporting electric current; or, equivalently, that there is a certain
distribution of stress, the magnetic stress, acting upon the same, we do
not at all mean that the accelerations of momentum of the different
parts are represented by the translational force, the " electromagnetic
force." It is, on the other hand, a dynamical problem in which the
electromagnetic force plays the part of an impressed force, and similarly
as regards the magnetic stress ; the actual forces and stresses being
only ^terminable from a knowledge of the mechanical conditions of
the conductor, as its density, elastic constants, and the way it is con-
strained. Now, if there is any dynamical meaning at all in the electro-
magnetic equations, we must treat the ether in precisely the same way.
But we do not know, and have not formularized, the equations of
motion of the ether, but only the way it propagates disturbance through
itself, with due allowance made for the effect thereon of given motions,
and with formularization of the reaction between the electromagnetic
effects and the motion. Thus the theory of the stresses and forces in
the ether and its motions is an unsolved problem, only a portion of it
being known so far, i.e., assuming that the Maxwellian equations do
express the known part.
When we assume the ether to be motionless, there is a partial
similarity to the theory of the propagation of vibrations of infinitely
small range in elastic bodies, when the effect thereon of the actual
translation of the matter is neglected.
But in ordinary electromagnetic phenomena, it does not seem that
the ignoration of q can make any sensible difference, because the speed
of propagation of disturbances through the ether is so enormous, that if
the ether were stirred about round a magnet, for example, there would
be an almost instantaneous adjustment of the magnetic induction to
what it would be were the ether at rest.
Static Consideration of the Stresses. — Indeterminateness.
§27. In the following the stresses are considered from the static point
of view, principally to examine the results produced by changing the
form of the stress-function. Either the electric or the magnetic stress
alone may be taken in hand. Start then, from a knowledge that the
* Professor J. J. Thomson has endeavoured to make practical use of the idea,
Phil. Mag., March, 1891. See also my article, The Electrician, January 15, 1886
[vol. i., pp. 547-8].
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 559
force on a magnetic pole of strength m is Rw, where R is the polar force
of any distribution of intrinsic magnetization in a medium, the whole of
which has unit inductivity, so that
div R = m = conv h0 (180)
measures the density of the fictitious " magnetic " matter ; h0 being the
intrinsic force, or, since here /x= 1, the intensity of magnetization. The
induction is B =h + R. This rudimentary theory locates the force on a
magnet at its poles, superficial or internal, by
F-RdivR (181)
The N-component of P is
FA'=RN.divR = div{R.RN-N.iR-'}, (182)
because curl R = 0. Therefore
P.V = R.RN-N.JH2 (183)
is the appropriate stress of irrotational type. Now, however uncertain
we may be about the stress in the interior of a magnet, there can be no
question as to the possible validity of this stress in the air outside our
magnet, for we know that the force R is then a polar force, and that is
all that is wanted, m and h being merely auxiliaries, derived from R.
Now consider a region A, containing magnets of this kind, enclosed
in B, the rest of space, also containing magnets. The mutual force
between the two regions is expressed by 2 P v over the interface, which
we may exchange for 2 Rm through either region A or B, still on the
assumption that R remains polar.
But if we remove this restriction upon the nature of R, and allow it
to be arbitrary, say in region B or in any portion thereof, we find
NF - div P,v = RN div R + N V(curl R) . R ;
or F = Rm + VJR,
if J = curl R. This gives us, from a knowledge of the external magnetic
field of polar magnets only, the mechanical force exerted by a magnet
on a region containing J, whatever that may be, provided it be measure-
able as above; and without any experimental knowledge of electric
currents, we could now predict their mechanical effects in every respect
by the principle of the equality of action and reaction, not merely as
regards the mutual influence of a magnet and a closed current, but as
regards the mutual influence of the closed currents themselves; the
magnetic force of a closed current, for instance, being the force on unit
of m, is equivalently the force exerted by m on the closed current, which,
by the above, we know. Also, we see that according to this magnetic
notion of electric current, it is necessarily circuital.
At the same time, it is to be remarked that our real knowledge must
cease at the boundary of the region containing electric current, a
metallic conductor for instance ; the surface over which P^ is reckoned,
on one side of which is the magnet, on the other side electric current,
can only be pushed up as far as the conductor. The stress PiV may
therefore cease altogether on reaching the conductor, where it forms a
560 ELECTRICAL PAPERS.
distribution of surface force fully representing the action of the magnet
on the conductor. Similarly, we need not continue the stress into the
interior of the magnet. Then, so far as the resultant force on the
magnet as a whole, in translating or rotating it, and, similarly, so far as
the action on the conductor is concerned, the simple stress P^v of
constant tensor JR2, varying from a tension parallel to R to an equal
pressure laterally, acting in the medium between the magnet and con-
ductor, accounts, by its terminal pulls or pushes, for the mechanical
forces on them. The lateral pressure is especially prominent in the
case of conductors, whilst the tension goes more or less out of sight, as
the immediate cause of motion. Thus, when parallel currents appear to
attract one another, the conductors are really pushed together by the
lateral pressure on each conductor being greater on the side remote
from the other than on the near side : whilst if the currents are
oppositely directed, the pressure on the near sides is greater than on
the remote sides, and they appear to repel one another.
The effect of continuing the stress into the interior of a conductor of
unit inductivity, according to the same law, instead of stopping it on
its boundary, is to distribute the translational force bodily, according to
the formula 2VJR, instead of superficially, according to 2P^. In
either case, of course, the conductor must be strained by the magnetic
stress, with the consequent production of a mechanical stress. But the
strain (and associated stress) will be different in the two cases, the
applied forces being differently localized. The effect of the stress on a
straight portion of a wire supporting current, due to its own field only,
is to compress it laterally, and to lengthen it. Besides this, there will
be resultant force on it arising from the different pressures on its
opposite sides due to the proximity of the return conductor or rest of
the circuit, tending to move it so as to increase the induction through
the circuit per unit current, that is, the inductance of the circuit.
§ 28. If, now, we bring an elastically magnetizable body into a
magnetic field, it modifies the field by its presence, causing more or less
induction to go through it than passed previously in the air it replaces,
according as its inductivity exceeds or is less than that of the air. The
forcive on it, considered as a rigid body, is completely accounted for by
the simple stress P^ in the air outside it, reckoned according to the
changed field, and supposed to terminate on the surface of the disturbing
body. This is true whether the body be isotropic or heterotropic in its
inductivity ; nor need the induction be a linear function of the magnetic
force. It is also true when the body is intrinsically magnetized ; or is
the seat of electric current. In short, since the external stress depends
upon the magnetic force outside the body, when we take the external
field as we may find it, that is, as modified by any known or unknown
causes within the body, the corresponding stress, terminated upon its
boundary, fully represents the forcive on the body, as a whole, due to
magnetic causes. This follows from the equality of action and reaction ;
the force on the body due to a unit pole is the opposite of that of the
body on the pole.
If we wish to continue the stress into the interior of the body,
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 561
surrounded on all sides by the unmaguetized medium of unit inductivity,
as we must do if we wish to arrive ultimately at the mutual actions of
its different parts, and how they are modified by variations of induc-
tivity, by intrinsic magnetization, and by electric current in the body,
we may, so far as the resultant force and torque on it are concerned, do
it in any way we please, provided we do not interfere with the stress
outside. For the internal stress, of any type, will have no resultant
force or torque on the body, and there is merely left the real external
stress.
Practically, however, we should be guided by the known relations of
magnetic force, induction, magnetization, and current, and not go to
work in a fanciful manner ; furthermore, we should always choose the
stress in such a way that if, in its expression, we take the inductivity
to be unity, and the intrinsic magnetization zero, it must reduce to the
simple Maxwellian stress in air (assumed to represent ether here). But
as we do not know definitely the forcive arising from the magnetic
stress in the interior of a magnet, there are several formulae that suggest
themselves as possible.
Special Kinds of Stress Formula statically suggested.
§ 29. Thus, first we have the stress (183) ; let this be quite general,
then
,V = R.RN-N.JR2, (184)
= RdivR + VJR (185)
Here R is the magnetic force of the field, not of the flux B. If
/x= 1, divR is the density of magnetic matter — the convergence of the
intrinsic magnetization — but riot otherwise. In general, it is the density
of the matter of the magnetic potential, calculated on the assumption
/* = !. The force on a magnet is located in this system at its poles,
whether the magnetization be intrinsic or induced. The second term
in (185) represents the force on matter bearing electric current
(J = curlR), but has to be supplemented by the first term, unless
div R = 0 at the place.
§ 30. Next, let the stress be /x times as great for the same magnetic
force, but be still of the same simple type, p being the inductivity,
which is unity outside the body, but having any positive value, which
may be variable, within it. Then we shall have
(186)
(187)
where m = conv ^h0 = div /*R is the density of magnetic matter, /xh0
being the intensity of intrinsic magnetization.
The electromagnetic force is made /* times as great for the same
magnetic force ; the force on an intrinsic magnet is at its poles ; and
there is, in addition, a force wherever //, varies, including the intrinsic
magnet, and not forgetting that a sudden change in /*, as at the
boundary of a magnet, has to count. This force, the third term in
H.E.P.— VOL, ii. 2N
562 ELECTRICAL PAPERS.
(187), explains the force on inductively magnetized matter. It is in
the direction of most rapid decrease of p.
§ 31. Thirdly, let the stress be of the same simple type, but taking H
instead of R, H being the force of the flux B = /*H = /*(R + h0), where h0
is as before. We now have
'P^=H.NB-N.JHB, .................. (188)
.P =VJB + Vj0B-iH2V/x, .................. (189)
where J0 = curl h0 is the distribution of fictitious electric current which
produces the same induction as the intrinsic magnetization /xh0, and
J is, as before, the real current.
It is now ^wasz-electromagnetic force that acts on an intrinsic magnet,
with, however, the force due to V/u, since a magnet has usually large \i
compared with air.
The above three stresses are all of the simple type (equal tension and
perpendicular pressure), and are irrotational, unless p be the eolotropic
operator. No change is, in the latter case, needed in (186), (188),
whilst in the force formulae (187), (189), the only ch^ige needed is to
give the generalized meaning to V/*. Thus, in (189), instead of H2V/A,
use 2V^, or V,t(H/xH), or
or Vfl-
or i(EV^B - BViH) + j(HV2B - BV2H) + k(HV3B - BV3H),
showing the i, j, k components.
Similarly in the other cases occurring later.
The following stresses are not of the simple type, though all consist
of a tension parallel to R or H combined with an isotropic pressure.
§ 32. Alter the stress so as to locate the force on an intrinsic magnet
bodily upon its magnetized elements. Add R./xh0N to the stress (186),
and therefore /*h0.RN to its conjugate; then the divergence of the
latter must be added to the N-component of the force (187). Thus we
get, if I = /xh0,
,4) JP^R.BN-N.iR/xR, .................. (190)
' \P = IV.R + VJ/*R-|R2V/*. .................. (191)
But here the sum of the first two terms in F may be put in a different
form. Thus,
Also IV^j = IViR + I(VJ?! - VXR) = IVXR + iVJI.
These bring (191) to
P = (i.IV1R+j.IV2R + k.IV3R) + VJB-JR2V/x, ......... (192)
where the first component (the bracketted part) is Maxwell's force on
intrinsic magnetization, and the second his electromagnetic force. The
third, as before, is required where /* varies.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 563
§ 33. To the stress (190) add - N. JRI, without altering the conjugate
stress, making
• (193)
= VJB-(V,-vl)JRB. ' ! .*. ! (194)
This we need not discuss, as it is merely a transition to the next form.
§ 34. To the stress (193) add h0.NB ; we then get
P^H.NB-N.JRB, (195)
- Jfi.fRVjB -B^B) + j .(RV2B - BV2R) + k.(RV3B - BV3R)}
where h^ liy hs are the components of h0.
Now if to this last stress (195) we add - N. Jh0B, we shall come back
to the third stress, (188), of the simple type.
Perhaps the most instructive order in which to take the six stresses
is (1), (2), (4), (5), (6), and (3) ; merely adding on to the force, in
passing from one stress to the next, the new part which the alteration
in the stress necessitates.
To the above we should add Maxwell's general stress, which is
R2, (197)
F =VJB+{i.lV1R+j.lV2R + k.:
{i.MV1R+j.MV2R + k.MV3R}, ............ (198)
where M = (//. - 1 )R = intensity of induced magnetization. There is a
good deal to be said against this stress ; some of which later.
Remarks on Maxwell's General Stress.
§ 35. All the above force-formulae refer to the unit volume ; when-
ever, therefore, a discontinuity in the stress occurs at a surface, the
corresponding expression per unit surface is needed ; i.e., in making a
special application, for it is wasted labour else. It might be thought
that as Maxwell gives the force (198), and in his treatise usually gives
surface-expressions separately, so none is required in the case of his
force-system (198). But this formula will give entirely erroneous
results if carried out literally. It forms no exception to the rule that
all the expressions require surface-additions.
Maxwell's general stress has the apparent advantage of simplicity.
It merely requires an alteration in the tension parallel to R, from R2 to
RB, whilst the lateral pressure remains |R2, when we pass from
unmagnetized to magnetized matter. The force to which it gives rise is
also apparently simple, being merely the sum of two forces, one the
electromagnetic, VJB, the other a force on magnetized matter whose i-
component is (I + M)VXR, both per unit volume, the latter being accom-
564 ELECTRICAL PAPERS.
panied (in case of eolotropy) by a torque. Now I is the intrinsic and
M the induced magnetization, so the force is made irrespective of the
proportion in which the magnetization exists as intrinsic or induced.
In fact, Maxwell's "magnetization" is the sum of the two without
reservation or distinction. But to unite them is against the whole
behaviour of induced and intrinsic magnetization in the electromagnetic
scheme of Maxwell, as I interpret it. Intrinsic magnetization (using
Sir W. Thomson's term) should be regarded as impressed (I = /xh0, where
ho is the equivalent impressed magnetic force); on the other hand,
"induced "magnetization depends on the force of the field {M = (/x- 1)R}.
Intrinsic magnetization keeps up a field of force. Induced magnetiza-
tion is kept up by the field. In the circuital law I and M therefore
behave differently. There may be absolutely no difference whatever
between the magnetization of a molecule of iron in the two cases of
being in a permanent or a temporary magnet. That, however, is not in
question. We have no concern with molecules in a theory which
ignores molecules, and whose element of volume must be large enough
to contain so many molecules as to swamp the characteristics of
individuals. It is the resultant magnetization of the whole assembly
that is in question, and there is a great difference between its nature
according as it disappears on removal of an external cause, or is intrinsic.
The complete amalgamation of the two in Maxwell's formula must
certainly, I think, be regarded as a false step.
We may also argue thus against the probability of the formula. If
we have a system of electric current in an unmagnetizable (/*=!-)
medium, and then change //, everywhere in the same ratio, we do not
change the magnetic force at all, the induction is made /x times as
great, and the magnetic energy p, times as great, and is similarly dis-
tributed. The mechanical forces are, therefore, /x times as great, and
are similarly distributed. That is, the translational force in the /t=l
medium, or VJR, becomes VJ/tR in the second case in which the in-
ductivity is /x, without other change. But there is no force brought in
on magnetized matter per se.
Similarly, if in the /x = 1 medium we have intrinsic magnetization I,
and then alter /* in any ratio everywhere alike, keeping I unchanged,
it is now the induction that remains unaltered, the magnetic force
becoming ft'1 times, and the energy /A-I times the former values,
without alteration in distribution (referring to permanent states, of
course). Again, therefore, we see that there is no translational force
brought in on magnetized matter merely because it is magnetized.
Whatever formula, therefore, we should select for the stress-function,
it would certainly not be Maxwell's, for cumulative reasons. When,
some six years ago, I had occasion to examine the subject of the stresses,
I was unable to arrive at any very definite results, except outside of
magnets or conductors. It was a perfectly indeterminate problem to
find the magnetic stress inside a body from the existence of a known,
or highly probable, stress outside it. All one could do was to examine
the consequences of assuming certain stresses, and to reject those which
did not work well. After going into considerable detail, the only two
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 565
which seemed possible were the second and third above (those of
equations (186) and (188) above). As regards the seventh (Maxwell's
stress, equation (198) above), the apparent simplicity produced by the
union of intrinsic and induced magnetization, turned out, when ex-
amined into its consequences, to lead to great complication and un-
naturalness. This will be illustrated in the following example, a simple
case in which we can readily and fully calculate all details by different
methods, so as to be quite sure of the results we ought to obtain.
A worked-out Example to exhibit the Fwcives contained in Different Stresses.
§ 36. Given a fluid medium of inductivity ^ in which is an intrinsic
magnet of the same inductivity. Calculate the attraction between the
magnet and a large solid mass of different inductivity //2. Here it is
only needful to calculate the force on a single pole, so let the magnet
be infinitely thin and long, with one pole of strength ra at distance a
from the medium /*2, which may have an infinitely extended plane
boundary. By placing a fictitious pole of suitable strength at the
optical image in the second medium of the real pole in the first, we
may readily obtain the solution.
Let PQ be the interface, and the real pole be at A, and its image at
B. We have first to calculate the distribution of R, magnetic force, in
both media due to the pole TTZ, as disturbed by the change of inductivity.
We have div f^Rj = m in the first medium, and div /*2R2 = 0 in the
second, therefore R has divergence only on the interface. Let a- be
the surface-density of the fictitious interfacial matter to correspond ;
its force goes symmetrically both ways ; the continuity of the normal
induction therefore gives, at distance r from A, the condition
/iaa\
.............. ( }
(
ma
566 ELECTRICAL PAPERS.
because m/47r/x1r2 is the tensor of the magnetic force due to m in the
ftj medium when of infinite extent. Therefore
_!^_. ...(200)
2W8
The magnetic potential ft, such that R = - Vfl is the polar force in
either region, is therefore the potential of m//Xj at A and of a- over the
interface.
But if we put matter n at the image B, of amount
.(201)
l2 i
normal component of El on the /^ side due to n and the pole m
.................. (202)
the
will be
ma na ma
the same value as before ; the force Ra on the /^ side is, therefore, the
same as that due to matter m/^ at A and matter n at B ; whilst on
the /*2 side the force R2 is that due to matter m//^ at A and matter n
also at A, that is, to matter — - — at A. Thus, in the /x2 medium the
force B2 is radial from A as if there were no change of inductivity,
though altered in intensity.
The repulsion between the pole m and the solid mass is not the
repulsion between the matters m/^ and n of the potential, but is
= m x magnetic force at A due to matter n at B,
= n x magnetic force at B due to matter m at A,
mn ^-»* m* (2Q3)
4ir(2a)2
becoming an attraction when ^ > ^ making n negative. When
ja2 = 0, the repulsion is
m
when /A2 = oo, it is turned into an attraction of equal amount.
Similarly, if we consider the attraction to be the resultant force
between m and the interfacial matter cr, we shall get the same result by
the quantity summed (over the interface) being o- x normal component
of magnetic force due to matter m in a medium of unit inductivity, or
the normal component of induction due to m in its own medium.
For this is
ma - m«
(203) again.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 567
Another way is to calculate the variation of energy made by displac-
ing either the pole m or the /x2 mass. The potential energy is expressed
by
J(P+^)m = JPm + |ZPo-/>t, ................. (205)
where P = m/lir^r and p = 2 o-/4?rr, the potentials of matter m/ft, and cr,
where r is the distance from m or from o- to the point where P and p
are reckoned.
The value of the second part in (205), depending upon o-, comes to
- m* 0
'
and its rate of decrease with respect to a expresses the repulsion
between the pole and the /x2 region. This gives (203) again.
A fourth way is by means of the gwwi-electromagnetic force on
fictitious interfacial electric current, instead of matter, the current
being circular about the axis of symmetry AB. The formula for the
attraction is
2 V curl B. B0, .......................... (207)
if R0 be the radial magnetic force from m in its own medium, tensor
m/47r/i1r2. Here the curl of B is represented by the interfacial discon-
tinuity in the tangential induction, or
zm
Also the tangential component of R0 is mx/fa^r3. Therefore the
repulsion is
(208)
as before, equation (203). This method (207) is analogous to (204).
§ 37. There are several other ways of representing the attraction,
employing fictitious matter and current; but now let us change the
method, and observe how the attraction between the magnetic pole and
the iron mass is accounted for by a stress-distribution, and its space-
variation. The best stress is the third, equation (188), § 31. Applying
this, we have simply a tension of magnitude J/*jAf"^i m tne nrst
medium and \p.2R% = Tz in the second, parallel to Bx and B2 respec-
tively, each combined with an equal lateral pressure, so that the tensor
of the stress-vector is constant.
But, so far as the attraction is concerned, we may ignore the stress
in the second medium altogether, and consider it as the 2 P^ of the
stress-vector in the first medium over the surface of the second medium.
The tangential component summed has zero resultant; the attraction
is therefore the sum of the normal components, or ST^cos 20P where
6l is the angle between Rx and the normal. This is the same as
568 ELECTRICAL PAPERS.
2 %p^(R$ - R%), if Rx and RT are the normal and tangential components
of Rxj or
which on evaluation gives the required result (203).
But this method does not give the true distribution of translational
force due to the stresses. In the first medium there is no translational
force, except on the magnet. Nor is there any translational force in
the second /*2 medium. But at the interface, where /x changes, there is
the force - J722V/* per unit volume, and this is represented by the
stress-difference at the interface. It is easily seen that the tangential
stress-difference is zero, because
(210)
and both the normal induction and the tangential magnetic force are
continuous. The real force is, therefore, the difference of the normal
components of the stress-vectors, and is, therefore, normal to the inter-
face. This we could conclude from the expression - ^R^Vp. But
since the resultant of the interfacial stress in the second medium is
zero, we need not reckon it, so far as the attraction of the pole is con-
cerned. The normal traction on the interface, due to both stresses, is
of amount
................. (211>
per unit area. Summed up, it gives (203) again.
That (211) properly represents the force - J722V/* when fi is discon-
tinuous, we may also verify by supposing ft to vary continuously in a
very thin layer, and then proceed to the limit.
The change from an attraction to a repulsion as p2 changes from
being greater to being less than /*j, depends upon the relative import-
ance of the tensions parallel to the magnetic force and the lateral
pressures operative at different parts of the interface. In the extreme
case of /x2 = 0, we have Rj tangential, with, therefore, a pressure every-
where. For the other extreme, RT is normal, and there is a pull on
the second medium everywhere. When /*2 is finite there is a certain
circular area on the interface within which the translational force due
to the stress in the medium containing the pole m is towards that
medium, whilst outside it the force is the other way. But when both
stresses are allowed for, we see that when /A2>/>t1 the pull is towards
the first medium in all parts of the interface, and that this becomes a
push in all parts when ^ > p2.
A Definite Stress only obtainable by Kinetic Consideration of the Circuital
Equations and Storage and Flux of Energy.
§ 38. We see that the stress considered in the last paragraph gives a
rationally intelligible interpretation of the attraction or repulsion. The
same may be said of other stresses than that chosen. But the use of
ON THE; FORCES IN THE ELECTROMAGNETIC FIELD. 569
Maxwell's stress, or any stress leading to a force on inductively mag-
netized matter as this stress does, leads us into great difficulties. By
(198) we see that there is first a bodily force on the whole of the /u,9
medium, because it is magnetized, unless ^2=^ When summed up,
the resultant does not give the required attraction. For, secondly, the
/*! medium is also magnetized, unless /^ = 1, and there is a bodily force
throughout the whole of it. When this is summed up (not counting
the force on the magnet), its resultant added on to the former resultant
still does not make up the attraction (i.e., equivalently, the force on the
magnet). For, thirdly, the stress is discontinuous at the interface
(though not in the same manner as in the last paragraph). The
resultant of this stress-discontinuity, added on to the former resultants,
makes up the required attraction. It is unnecessary to give the details
relating to so improbable a system of force.
Our preference must naturally be for a more simple system, such as
the previously considered stress. But there is really no decisive settle-
ment possible from the theoretical statical standpoint, and nothing
short of actual experimental determination of the strains produced and
their exhaustive analysis would be sufficient to determine the proper
stress-function. But when the subject is attacked from the dynamical
standpoint, the indeterminateness disappears. From the two circuital
laws of variable states of electric and magnetic force in a moving
medium, combined with certain distributions of stored energy, we are
led to just one stress-vector, viz. (136). It is, in the magnetic case, the
same as (188): that is, it reduces to the latter when the medium is
kept at rest, so that J0 and G-0 become J and G.
It is of the simple type in case of isotropy (constant tensor), but is a
rotational stress in general, as indeed are all the statically probable
stresses that suggest themselves. The translational force due to it
being divisible conveniently into (a), the electromagnetic force on
electric current, (6), the ditto on the fictitious electric current taking
the place of intrinsic magnetization, (c), force depending upon space-
variation of p ; we see that the really striking part is (b). Of all the
various ways of representing the forcive on an intrinsic magnet it is
the most extreme. The magnetic " matter " does not enter into it, nor
does the distribution of magnetization ; it is where the intrinsic force
h0 has curl that the translational force operates, usually on the sides of
a magnet. From actual experiments with bar-magnets, needles, etc.,
one would naturally prefer to regard the polar regions as the seat of
translational force. But the equivalent forcive 2j0B has one striking
recommendation (apart from the dynamical method of deducing it),
viz., that the induction of an intrinsic magnet is determined by curl h0,
not by h0 itself; and this, I have shown, is true when h0 is imagined to
vary, the whole varying states of the fluxes B, D, C due to impressed
force being determined by the curls of e0 and h0, which are the sources
of the disturbances (though not of the energy).
The rotational peculiarity in eolotropic substances does not seem to
be a very formidable objection. Are they not solid ?
As regards the assumed constancy of p, a more complete theory
570 ELECTRICAL PAPERS.
must, to be correct, reduce to one assuming constancy of /*, because, as
Lord Rayleigh* has shown, the assumed law has a limited range of
validity, and is therefore justifiable as a preparation for more complete
views. Theoretical requirements are not identical with those of the
practical engineer.
But, for quite other reasons, the dynamically determined stress might
be entirely wrong. Electric and magnetic "force" and their energies
are facts. But it is the total of the energies in concrete cases that
should be regarded as the facts, rather than their distribution ; for
example, that, as Sir W. Thomson proved, the " mechanical value " of
a simple closed current C is %LC'2, where L is the inductance of the
circuit (coefficient of electromagnetic capacity), rather than that its
distribution in space is given by JHB per unit volume. Other distri-
butions may give the same total amount of energy. For example, the
energy of distortion of an elastic solid may be expressed in terms of the
square of the rotation and the square of the expansion, if its boundary
be held at rest; but this does not correctly localize the energy. If,
then, we choose some other distribution of the energy for the same dis-
placement and induction, -we should find quite a different flux of energy.
But I have not succeeded in making any other arrangement than Max-
well's work practically, or without an immediate introduction of great
obscurities. Perhaps the least certain part of Maxwell's scheme, as
modified by myself, is the estimation of magnetic energy as ^HB in
intrinsic magnets, as well as outside them, that is, by JB/^~1B, however
B may be caused. Yet, only in this way are thoroughly consistent
results apparently obtainable when the electromagnetic field is con-
sidered comprehensively and dynamically.
APPENDIX.
Received June 27, 1891.
Extension of the Kinetic Method of arriving at the Stresses to cases of Non-
linear Connection between the Electric and Magnetic Forces and the
Fluxes. Preservation of Type of the Flux of Energy Formula.
§ 39. It may be worth while to give the results to which we
are led regarding the stress and flux of energy when the restriction
of simple proportionality between "forces" and "fluxes," electric
and magnetic respectively, is removed. The course to be followed,
to obtain an interpretable form of the equation of activity, is
sufficiently clear in the light of the experience gained in the case
of proportionality.
First assume that the two circuital laws (89) and (90), or the two in
(93), hold good generally, without any initially stated relation between
the electric force E and its associated fluxes C and D, or between the
* Phil. Mag., January, 1887.
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 571
magnetic force H and its associated fluxes K and B. When written in
the form most convenient for the present application, these laws are
~ + (Ddivq-DV.q), ......... (212)
q-Bv.q) .......... (213)
Now derive the equation of activity in the manner previously followed,
and arrange it in the particular form />^ ^££>
e0J0 + h0G0 + conv Y(E - e0)(H - h0) = (EC + HK) + ( E?? + H^) '
\ (jv (Jv J \ (~\
+ (E.DV.q-EDdivq) + (H.BV.q-HBdivq), (214)
which will best facilitate interpretation.
Although independent of the relation between E and D. etc., of course
the dimensions must be suitably chosen so that this equation may really
represent activity per unit volume in every term.
Now, guided by the previous investigation, we can assume that
(e0J0 + h0G0) represents the rate of supply of energy from intrinsic
sources, and also that V(E - e0)(H - h?), which is a flux of energy
independent of q, is the correct form in general. Also, if there be
no other intrinsic sources of energy than e0, h0, and no other fluxes of
energy besides that just mentioned except the convective flux and that
due to the stress, the equation of activity should be representable by
(e0J0 + h0G0) + conv [V(E - e0)(H - h0) + q(Z7+ T)]
U+ ) + Fq +
U+T) + 2Qvq, ........................... ............. (215)
where Q is the conjugate of the stress-vector, F the translational force,
and Q, U1 and T the rate of waste and the stored energies, whatever
they may be.
Comparing with the preceding equation (214), we see that we require
+ [E.DV.q-(ED- tf)divq] + [H.Bv.q-(HB -T)divq]. (216)
Now assume that there is no waste of energy except by conduction; then
(217a)
Also assume that =E, =H .................. .(217ft)
at ot ot ot
These imply that the relation between E and D is, for the same particle
of matter, an invariable one, and that the stored electric energy is
(218)
'0
where E is a function of D. Similarly,
(219)
= T
572 ELECTRICAL PAPERS.
expresses the stored magnetic energy, and H must be a definite function
of B.
On these assumptions, (216) reduces to
^QV^ = [E.DV.q-(ED- Z7)div q] + [H.BV.q- (HB - J) div q], (220)
from which the stress-vector follows, namely,
P^=[E.DN-N(ED- CT)] + [H.BN-N(HB-r)] (221)
Or, P,v=(VDVEN + NZ7) + (VBVHN + Nr) (222)
Thus, in case of isotropy, the stress is a tension U parallel to E com-
bined with a lateral pressure (ED - U] ; and a tension T parallel to H
combined with a lateral pressure (HB - T).
The corresponding translational force is
F = EdivD + DV.E-V(ED- £/) + HdivB + BV.H - V(HB-7), (223)
which it is unnecessary to put in terms of the currents.
Exchange E and D, and H and B, in (221) or (222) to obtain the
conjugate vector Q v ; from which we obtain the flux of energy due to
the stress,
- $Qg = D.Eq - q(ED - U) +B.Hq - q(HB - T)
= VEVDq + VHVBq + q(CT+T), (224)
or -^Q^VeH + VEh + q^+T7), (225)
where e and h, are the motional electric and magnetic forces, of the same
form as before, (88) and (91) ; so that the complete form of the equation
of activity, showing the fluxes of energy and their convergence, is
e0J0 + h0G0 + conv [ V(B - e0)(H - h0) + q( 17+ T)]
- conv [VeH + VEh + q( U+ T)] = Fq + (Q + U+ f), (226)
where F has the above meaning.
There is thus a remarkable preservation of form as compared with
the corresponding formulae when there is proportionality between force
and flux. For we produce harmony by means of a Poynting flux of
identical expression, and a flux due to the stress which is also of
identical expression, although U and T now have a more general
meaning, of course.*
* As the investigation in this Appendix has some pretensions to generality, we
should try to settle the amount it is fairly entitled to. No objection is likely to
be raised to the use of the circuital equations (212), (213), with the restriction of
strict proportionality between £ and H and the fluxes D and B, or C and K entirely
removed ; nor to the estimation of J0 and G0 as the " true " currents ; nor to the
use of the same form of flux of electromagnetic energy when the medium is
stationary. For these things are obviously suggested by the preceding investi-
gations, and their justification is in their being found to continue to work, which
is the case. But the use in the text of language appropriate to linear functions,
which arose from the notation, etc., being the same as before, is unjustifiable.
We may, however, remove this misuse of language, and make the equation (226),
showing the flux of energy, rest entirely upon the two circuital equations. In
fact, if we substitute in (226) the relations (217a), (2176), it becomes merely a
f writing (214).
to (21 la), (217&) that we should look for limitations. As regards
particular way of writing (214).
It is, therefore,
ON THE FORCES IN THE ELECTROMAGNETIC FIELD. 573
Example of the above, and Remarks on Intrinsic, Magnetization when
there is Hysteresis.
§ 40. In the stress-vector itself (for either the electric or the magnetic
stress) the relative magnitude of the tension and the lateral pressure
varies unless the curve connecting the force and the induction be a
straight line. Thus, if the curve be of the type shown in the first
figure, the shaded area will
represent the stored energy
and the tension, and the
remainder of the rectangle
will represent the lateral
pressure. They are equal
when H is small ; later on
the pressure preponderates,
and more and more so the
bigger H becomes.
But if the curve be of the
type shown in the second
figure, then, after initial
equality, the tension pre-
ponderates ; though, later
on, when H is very big, the
pressure preponderates.
To obtain an idea of the
effect, take the concrete
example of an infinitely
long rod, uniformly axially
inductized by a steady
current in an overlapping
solenoid, and consider the
forcive on the rod. Here
both H and B are axial or longitudinal ; and so, by equation (223), the
translational force would be a normal force on the surface of the rod,
acting outwards, of amount
per unit area ; this being the excess of the lateral pressure in the rod
over |#o^>o. the lateral pressure just outside it.
In case of proportionality of force to flux, the first pressure is \RB,
and, if there is no intrinsic magnetization, H and H0 are equal. The
(217a), there does not seem to be any limitation necessary. That is, there is no
kind of relation imposed between E and C, and H and K. This seems to arise
merely from Q meaning energy wasted for good, and having no further entry into
the system. But as regards (2176), the case is different. For it seems necessary,
in order to exclude terms corresponding to E(dcfdt)E and H(3/i/30H in the linear
theory, when there is rotation, that E and D should be parallel, and likewise H and
B. At any rate, if such terms be allowed, some modification may be required in
the subsequent reckoning of the mechanical force. In other respects, it is merely
implied by (2176) that E and D are definitely connected, likewise H and B, so that
there is no waste of energy other than that expressed by Q.
574 ELECTRICAL PAPERS.
outward force is therefore positive for paramagnetic, and negative for
diamagnetic substances, and the result would be lateral expansion or
contraction, since the infinite length would prevent elongation.
But if the curve in the rod be of the type of the first figure, and the
straight line ac be the air-curve to correspond, it is the area abc that now
represents the outward force per unit area when the magnetic force has the
value ad. If the straight line can cross the curve ab, we see that by suffi-
ciently increasing H we can make the external air-pressure preponderate,
so that the rod, after initially expanding, would end by contracting.
If the rod be a ring of large diameter compared with its thickness, the
forcive would be approximately the same, viz., an outward surface-force
equal to the difference of the lateral pressures in the rod and air. The
result would then be elongation, with final retraction when the external
pressure came to exceed the internal.
Bid well found a phenomenon of this kind in iron, but it does not seem
possible that the above supposititious case is capable of explaining it,
though of course the true explanation may be in some respects of a
similar nature. But the circumstances are not the same as those
supposed. The assumption of a definite connection between H and B,
and elastic storage of the energy T, is very inadequate to represent the
facts of magnetization of iron, save within a small range.
Magneticians usually plot the curve connecting H-h0 and B} not
between H and B, or which would be the same, between H-h0 and
B - B0, where B0 is the intrinsic magnetization. Now when an iron
ring is subjected to a given gaussage (or magnetomotive force), going
through a sequence of values, there is no definite curve connecting
H—h0 and J5, on account of the intrinsic magnetization. But, with
proper allowance for A0, it might be that the resulting curve connecting
H and B in a given specimen would be approximately definite, at any
rate, far more so than that connecting H-hQ and B. Granting perfect
definiteness, however, there is still insufficient information to make a
theory. The energy put into iron is not wholly stored ; that is, in
increasing the coil-current we increase B0 as well as B, and in doing so
dissipate energy ; but although we know, by Ewing's experiments, the
amount of waste in cyclical changes, it is not so clear what the rate of
waste is at a given moment. There is also the further peculiarity that
the energy of the intrinsic magnetization at a given moment, though
apparently locked up, and really locked up temporarily, however loosely
it may be secured, is not wholly irrecoverable, but comes into play
again when H is reversed. Now it may be that the energy of the
intrinsic magnetization plays, in relation to the stress, an entirely
different part from that of the elastic magnetization. It is easy to make
up formulae to express special phenomena, but very difficult to make a
comprehensive theory.
But in any case, apart from the obscurities connected with iron, it is
desirable to be apologetic in making any application of Maxwell's
stresses or similar ones to practice when the actual strains produced are
in question, bearing in mind the difficulty of interpreting and harmonizing
with Maxwell's theory the results of Kerr, Quincke, and others.
THE POSITION OF 4* IN ELECTROMAGNETIC UNITS. 575
LIII. THE POSITION OF 4?r IN ELECTROMAGNETIC UNITS.
[Mature, July 28, 1892, p. 292.]
THERE is, I believe, a growing body of opinion that the present system
of electric and magnetic units is inconvenient in practice, by reason of
the occurrence of 4?r as a factor in the specification of quantities which
have no obvious relation with circles or spheres.
It is felt that the number of lines from a pole should be ra rather
than the present 47rra, that "ampere turns" is better than 471-71(7, that
the electromotive intensity outside a charged body might be a- instead
of 4;r(r, and similar changes of that sort; see, for instance, Mr. Williams's
recent paper to the Physical Society.
Mr. Heaviside, in his articles in The Electrician and elsewhere, has
strongly emphasized the importance of the change and the simplifi-
cation that can thereby be made.
In theoretical investigations there seems some probability that the
simplified formulae may come to be adopted —
/A being written instead of 4^, and k instead of -^ ;
but the question is whether it is or is not too late to incorporate the
practical outcome of such a change into the units employed by electrical
engineers.
For myself I am impressed with the extreme difficulty of now
making any change in the ohm, the volt, etc., even though it be only a
numerical change ; but in order to find out what practical proposal the
supporters of the redistribution of 4?r had in their mind, I wrote to
Mr. Heaviside to inquire. His reply I enclose ; and would merely say
further that in all probability the general question of units will come
up at Edinburgh for discussion.
OLIVER J. LODGE.
My dear Lodge, — I am glad to hear that the question of rational
electrical units will be noticed at Edinburgh— if not thoroughly dis-
cussed. It is, in my opinion, a very important question, which must,
sooner or later, come to a head and lead to a thoroughgoing reform.
Electricity is becoming not only a master science, but also a very
practical science. Its units should therefore be settled upon a sound
and philosophical basis. I do not refer to practical details, which may
be varied from time to time (Acts of Parliament notwithstanding), but
to the fundamental principles concerned.
If we were to define the unit area to be the area of a circle of unit
diameter, or the unit volume to be the volume of a sphere of unit
diameter, we could, on such a basis, construct a consistent system of
units. But the area of a rectangle or the volume of a parallelepiped
would involve the quantity TT, and various derived formulae would
576 ELECTRICAL PAPERS.
possess the same peculiarity. No one would deny that such a system
was an absurdly irrational one.
I maintain that the system of electrical units in present use is founded
upon a similar irrationality, which pervades it from top to bottom.
How this has happened, and how to cure the evil, I have considered in
my papers — first in 1882-83, when, however, I thought it was hopeless
to expect a thorough reform; and again in 1891, when I have, in my
" Electromagnetic Theory," adopted rational units from the beginning,
pointing out their connection with the common irrational units sepa-
rately, after giving a general outline of electrical theory in terms of the
rational.
Now, presuming provisionally that the first and second stages to
Salvation (the Awakening and Repentance) have been safely passed
through, which is, however, not at all certain at the present time, the
question arises, How proceed to the third stage, Reformation 1 Theo-
retically this is quite easy, as it merely means working with rational
formulae instead of irrational ; and theoretical papers and treatises may,
with great advantage, be done in rational formulae at once, and irre-
spective of the reform of the practical units. But taking a far-sighted
view of the matter, it is, I think, very desirable that the practical units
themselves should be rationalized as speedily as may be. This must
involve some temporary inconvenience, the prospect of which, unfortu-
nately, is an encouragement to shirk a duty; as is, likewise, the
common feeling of respect for the labours of our predecessors. But
the duty we owe to our followers, to lighten their labours permanently,
should be paramount. This is the main reason why I attach so much
importance to the matter; it is not merely one of abstract scientific
interest, but of practical and enduring significance ; for the evils of the
present system will, if it continue, go on multiplying with every
advance in the science and its applications.
Apart from the size of the units of length, mass, and time, and of
the dimensions of the electrical quantities, we have the following
relations between the rational and irrati Dnal units of voltage V, electric
current (7, resistance R, inductance L, permittance S, electric charge Q,
electric force E, magnetic force JJ, induction B. Let #2 stand for 47r,
and let the suffixes r and t mean rational and irrational (or ordinary).
Also let the presence of square brackets signify that the "absolute"
unit is referred to. Then we have —
[ft]
The next question is, what multiples of these units we should take to
make the practical units. In accordance with your request I give my
ideas on the subject, premising, however, that I think there is no
finality in things of this sort.
First, if we let the rational practical units be the same multiples
THE POSITION OF 4ir IN ELECTROMAGNETIC UNITS. 577
of the "absolute" rational units as the present practical units are
of their absolute progenitors, then we would have (if we adopt the
centimetre, gramme, and second, and the convention that />t = l in
ether)
[Jtr] x 109 = new ohm =x2 times old.
[Lr~\ x 10° = new mac =x2 „
[Sr ] x 10~9 = new farad = ar2
[Cr] x 10~1 = new amp =or1 „
[KJxlO8 = new volt =x „
107 ergs = new joule =old joule.
10" ergs per sec. = new watt =old watt.
I do not, however, think it at all desirable that the new units should
follow on the same rules as the old, and consider that the following
system is preferable : —
y.2
[£r] x 108 = new ohm = ~~- x old ohm.
x2
[Lr] x 108 = new mac =-—xoldmac.
I £ '] x 10-s = new farad = 15 x old farad.
x2
[6V] x 1 = new amp = — x old amp.
[Tr] x 10s =new volt = x x old volt.
108 ergs = new joule = 10 x old joule.
108 ergs per sec. = new watt = 10 x old watt.
It will be observed that this set of practical units makes the ohm, mac,
amp, volt, and the unit of elastance, or reciprocal of permittance, all
larger than the old ones, but not greatly larger, the multiplier varying
roughly from 1J to 3J.
What, however, I attach particular importance to is the use of one
power of 10 only, viz., 108, in passing from the absolute to the practical
units • instead of, as in the common system, no less than four powers,
101, 107, 108, and 109. I regard this peculiarity of the common system
as a needless and (in my experience) very vexatious complication. In
the 108 system I have described, this is done away with, and still the
practical electrical units keep pace fairly with the old ones. The
multiplication of the old joule and watt by 10 is, of course, a necessary
accompaniment. I do not see any objection to the change. Though
not important, it seems rather an improvement. (But transformations
of units are so treacherous, that I should wish the whole of the above
to be narrowly scrutinized.)
H.E.P. — VOL. ii. 2o
578 ELECTRICAL PAPERS.
It is suggested to make 109 the multiplier throughout, and the
results are : —
x 109 = new ohm =x- x old ohm.
[Lr] x 10° = new mac =#- x old mac.
[Sr] x 10-9 = new farad = ar2 x old farad.
[Cr] x 1 = new amp = — x old amp.
[Vr] x 109 = new volt = IQx x old volt.
109 ergs = new joule = 102 x old joule.
10-' ergs p. sec. =new watt = 10'2 x old watt.
But I think this system makes the ohm inconveniently big, and has
some other objections. But I do not want to dogmatize in these
matters of detail. Two things I would emphasize : — First, rationalize
the units. Next, employ a single multiplier, as, for example, 10s.
OLIVER HEAVISIDE.
PAIGNTON, DEVON, July 18, 1892.
CORRECTIONS. VOL. II.
p. 69, equation (516), change sign of last term from - to +, as in (73), p. 192.
p. 69, equation (526), change sign of last term from + to - , as in (72), p. 192,
and for )[ read )-[, to agree with (72), p. 192.
p. 316, equation (400), the lower limit should be 20.
p. 355, last line, for 361 read 301.
p. 387, seventh line, for 153 read 393.
p. 400, second line, for fraction to read fraction of to.
INDEX.
Absorption, (1) 428, 432, 479, 480
Action at a distance, (2) 490
Activity, equations of, (1) 450, 521 ;
(2) 174, 535, 547, 572
mutual, (1) 522
Admittance, (2) 357
Ampere, theory of magnetism, (1) 181
electrodynamics, (1) 238, 282, 482,
559
Analogies, conduction, induction, and
displacement, (1) 472
magnetization and electrization, (1)
489
electric and magnetic (various), (1)
509-15
moving isotropic and stationary eolo-
tropic medium, (2) 499
induction in core and current in wire,
(2) 30, 57
waves along circuit and waves along
cord, (2) 349, 401
hydraulic, (1) 96
telegraph cable and inductized core,
(1)399
liquid in pipe and current in wire,
(2) 60, 182
Anglo-danish cable, unilateral effect,
(1), 61
speeds of working on, (1) 62
Arrival-curves on cables, (1) 50-1, 68,
72-4
calculation of, (1) 78-95, 125
in cores and wires, (1) 398 ; (2) 58
Atomic currents, (1) 490
Attenuation, (2) 120, 129, 166
tables of, (2) 346, 350
Ayrton and Perry, (1) 39, 337 ; (2) 245,
367, 486
Axioms of thermodynamics, (1) 487
Bain, (1) 138
Balances, true and false, (2) 100, 115
periodic, (2) 106
iron against copper, (2) 115
with the Christie, (2) 33-38, 256-292,
366
H.E.P.— VOL. II.
2o2
Berliner, (1) 183
Bessel functions, (1) 173, 360, 387 ; (2)
48, 176, 445
different forms of, (2) 445
of any order, (2) 467
complementary, (2) 445, 467
in plane waves, (2) 477
in spherical waves, (2) 428
Bidwell, retraction of iron, (2) 574
Blaserna, oscillations, (1) 61
Blyth, arc microphone, (1) 182
Bosscha's corollaries, (1) 21
Bottomley, (2) 42, 113
Boundary functions, connection with
electrical distributions, (1) 552-6
Bridge (see Christie)
system of telephony, (2) 251
across circuit, effect of, (2) 123
Budde, (1) 328
Capacity (see Permittance)
Cardinal formula, (2) 501
Carnot, (1) 316, 486
Cartesian expansions, (2) 16
Cayley, A., (2)389
Characteristic function, (1)412-15; (2)
261, 371
degree of, (1) 540
Chemical contact force, (1) 337-42,
472
Christie balance, (2) 102, 256
of exact copies, (2) 257
of reduced copies, (2) 104, 258
conjugate conditions of, (2) 263
of self-induction, (2) 263
practical use of, (2) 265
peculiarities of, (2) 270
simple-periodic, (2) 106, 270
disturbance of, by metal, (2) 273
of resistance, permittance, and induct-
ance, (2) 280
of self and mutual inductance, (2) 107,
291
miscellaneous arrangements of, (2) 286
of thick wires, (2) 116
applied to telegraph circuit, (2) 105
580
ELECTRICAL PAPERS.
Circuital, (1) 279, 344, 435, etc.
distributions, (2) 470
law, first, (1) 443
law, second, (1) 447
equations, (1) 449; (2) 8, 174, 468,
497, 540, 541, 543, 571.
Clark, Latimer, (1)2
Clausius, (1) 179, 296, 316, 327, 487 ;
(2) 501
Closure of electric current, (1) 559
Coils with cores, combinations of, (1)
402-416
in parallel, equivalent to one, (2) 292
combinations of, with S.H. voltage,
(1)114
Compliancy, (2) 542
Condensers, in sequence, (1) 425
theory of signalling with, (1) 47, 53
theory of combination of shunted, (1)
536-42
Condenser, electromagnetic wave on dis-
charge of, (2) 465
Conductance, (1) 399; (2) 24, 125
Conduction and displacement (simul-
taneous), (1) 494-509
Conductors, diffusion of current in
(nature of), (2) 385
Conjugacy of conductors (conditions of),
(2) 259
Conjugate property, of normal systems,
(1) 81, 128, 390, 396, 401 ; (2) 53,
178, 202
general, (1) 143, 523
in electrical arrangements, (2) 205
Conjugate vector functions, (2) 19
Conservation of energy, (1) 291-303
Contact layers, (1) 342, 350
Convection-current, (2) 490-518
produces plane wave, (2) 493, 511
equatorial concentration, (2) 493, 496,
511
energy of, (2) 493, 505, 514
mutual energy of two point-charges,
(2) 507
general theory of, (2) 508
at speed greater than light, (2) 494,
496, 515
at speed less than light, (2) 495
equilibrium surfaces, (2) 514
charged straight line, (2) 516
charged plane, (2) 517
bidimensional solution, (2) 517
Convergence, (1) 210, 215
Coulomb, (1)278
Culley, R. S., (1) 62
Cumming, (1) 311
Curl (of a vector), (1) 199, 443
at a surface, (1) 200
inverted, (1) 220
of impressed forcive (source of dis-
turbances), (2) 60, 361
Current, a function of magnetic force,
(1) 198
straight, magnetic force of, (1) 198
true (Maxwell's), (1) 433
sheet, (1) 205, 227
elements, (2) 310, 501
in wires, magnetic theory, (2) 58, 181
Cycles in a mesh of conductors, (2) 108
Daniell'o cell, (1) 2
Davies, (2) 41
Deflection of wave, (2) 519
Deprez, Marcel, (1)238
Determinantal equation, (1) 415
and differential equations, (2) 261
Determinateness of distributions, (1)
497-506
Determination of potential from surface
value, (1) 553
Dielectric, (1) 433
moving, (2) 492
Diffusion of current in wires, (2) 44-61
Diffusion effect, (2) 274
nature of, (2) 385
conductive, (1) 384
Differentiation of vectors, (2) 531
Displacement, (1) 432, 475
circuital, (1)466
instantaneous vanishing of, (1) 534
persistence of, (2) 481
Dissipativity, (1), 431
Distortion, (2) 120, 166
of plane waves, (2) 482
abolition of, (2), 512
in telephony, causes of, (2) 347
Distortionless circuit, (2) 123-155
short theory of, (2) 307
with terminal short-circuit, (2) 131,
312
with terminal resistance, (2) 130
with terminal complete absorption,
(2)127,311
with terminal partial absorption, (2)
133-5, 312
best arrangement of, (2) 136, 323
in parallel, (2) 137
with intermediate resistance, (2), 138,
315
of different types, (2) 152
with variable speed of current, (2)
153, 316
with intermediate bridges, (2) 315
approximate, (2) 345
establishment of current in, (2) 313
Divergence of a vector, (1) 209, 444
of coefficients in normal systems, (1)
90, 530
Divided core, (1) 374
Divided iron equivalent to self-induction,
(2) 275
INDEX.
581
Division of discharge, (1) 106
Duplex method (electromagnetic), (1)
449, 542 ; (2) 172
Duplex telegraphy, Gintl's method, (1)
18; Frischen's, (1) 19; Eden's, (1)
21; Stearns', (1)21
by balancing batteries, (1) 22
by Bridge system, theory of sensitive-
ness, (1) 24
by differential system, theory of
sensitiveness, (1) 30
variations of balance in, (1) 33
with balanced capacity, (1) 25
Earth, as a return conductor, (1) 190
magnetic force of current in, (1) 224
currents, (1) 389
Edison, T. A., problem, (1) 34
etheric force, (1) 61 ; (2) 85
Effective resistance and inductance, or
conductance and permittance, (2)
357
Elastance, (1)512; (2) 125
Elastivity, (2) 125
Elastic solid (generalized), (2) 535-9
Electret, (2) 488
Electric energy, (1) 432, 466
various expressions for, (1) 506
Electrification in a conductor, (1) 476
Electric impulse, (1) 517
Electric connexions (summary), (2) 375
Electrization, (1) 488
Electromagnets, (1) 95
Electromagnetic force, from stress, (1)
545
Electromotive forces, method of com-
paring, (1)1
Electromagnetic field, (2) 251
flux of energy in, (2) 525, 541-3
equations of the, (2) 539
stress in the, (2) 548
force in the, (2) 546, 558
Electrostatic time-constant of circuit,
(2) 128
induction, (1) 117
Energy, electric, (1) 432
magnetic, (2) 434
mutual, of magnetic shells, (1) 234
of linear currents, (1) 235
of current systems, (1) 240
self, of current system, (1) 248
magnetic, localization of, (1) 248
minimum property of, (1) 251
transfer of, (1) 282, 434-41, 450; (2)
541-3, 571
Equal roots (in normal systems), (1)
529
Equilibrium surf aces in movingmedium,
(2) 514
Eolotropic potential function, (2) 499
Eolotropy in Ohm's law, (I) 280-90, 430
Equilibrium of stressed medium, (1)
547
of stress, (2) 534
Ether, (1) 420, 430, 433 ; (2) 525
gravitational function of, (2) 528
force in free, (2) 557
Euler, (1) 381
Evaluation of constants in normal sys-
tems, (1) 523-5, 529
Everett, (1) 179, 327
Ewing, (1)365; (2)275, 574
Extra-current, (1) 53-61
integral, (1) 121
False electrification, (1) 506
electric current, (1) 506, 512
magnetic current, (1) 509, 512
Faraday, (1) 195, 298, 447, etc.
Faults (leakage), theory of effect on
signalling, (1) 71-95.
Felici's balance, (2) 110
disturbed, theory, (2) 112
Fictitious matter and current on bound-
aries, (1) 549 ; (2) 554
Fitzgerald, G. F., (1) 467 ; (2) 394, 489,
492, 508, 524
Fleming, J. A., (2) 108, 488.
Fluids (electric), (2) 80, 486.
Forbes, (2) 403
Flux of energy (see Transfer)
Flux (initial) due to impressed force,
cancelled later, (2) 412
Force, electromagnetic, (1) 545; (2) 560
magneto-electric, (1) 545
on intrinsic magnets, (2) 550, 559
on inductively magnetized matter, (2)
550
(general) in electromagnetic field, (2)
546, 550, 569, 572
other forms of, got statically, (2)
561-3
between two regions, (2) 554
Forced vibrations of electromagnetic
systems (examples), (2) 233
Foucault currents, (2) 111, 113
Fourier, (1) 201, 333 ; (2) 387
series, to suit terminal conditions, ( 1 )
92, 123, 151 ; (2) 391
integrals, (2) 474 ; evaluation of, (2)
478
Fourier's theorem, extension of, (1) 154
Freedom, degrees of, in electrical com-
binations, (1) 540
Fresnel, (2) 1, 2, 3, 11, 12, 392, .VJI
Friction and electrification, (1) 475
Functions, Fourier's, (1) 151
Bessel's, (1) 173
Murphy's, (1) 176
Legendre's, (1) 177
582
ELECTRICAL PAPERS.
Functions —
spherical zonal harmonic, (1) 229;
(2) 405
expansion in series, (1) 142-150; (2)
201, 233
Function of wires, (2) 486
of self-induction, (2) 489
Galvanometer, resistance of, for maxi-
mum magnetic force, (1) 12, 38
differential, for measuring small re-
sistances, (1) 13
differential, resistance of coils for
maximum effect, (1) 16
Generalization of resistance to pass from
characteristic function to differ-
ential equation, (1) 415
Gibbs, Willard, (1) 272 ; (2) 20, 528-9
Giltay, (2) 348
Glaisher, J. W. L., (2) 389
Glazebrook, (2) 521
Goethe, (1) 335
Granville, W. P., (2)496
Grassmann, (1) 272
Gravitation, (2) 527
Gray, Elisha, (2) 156
Green, (1) 555
Hamilton, Sir W. R., (1) 207; (2) 5,
528, 557
Hamilton's cubic, (2) 19
Hall effect, (1) 290
Heat, Joule's law, (1)490
developed in core, (1) 364
Heaviside, A. W., (2) 83, 145, 185, 251,
323
Hertz, H., (2) 444, 489, 490, 503, 523-4,
552-3
Helmholtz, von, (1) 282, 342, 344, 381 ;
(2) 552
Henry, Joseph, (1) 61
Hindrance, (2) 488
Hockin, C., (2) 246
Hughes, D. E., (1) 365-6 ; (2) 28-30, 35,
38, 101, 111, 169
Hydrokinetic analogy, (1) 275
Hysteresis, in telephone, (2) 158
outside mathematical theory, (2) 574
Identities, transcendental, (1) 88; (2)
245, 389, 445-6
Impedance, (1) 371 ; (2) 64, 125, 185
equality rule, (1) 99 ; (2) 143, 354
of a wire, (2) 165
of circuits, (2) 64
equivalent, of telegraph circuit, (2)
72, 341
reduced by inertia, (2) 65
Impedance-
reduced by compliancy, (2) 71
magnetic, of short lines, (2) 67
influence of displacement on, (2) 71-6
fluctuations with frequency, (2) 73,
345
ultimate form with great frequency,
(2)76
extended meaning of, (2) 371
Impressed forces, effect of, (1) 164; (2)
473
in dielectrics, (1) 471
Impulsive inductance and permittance,
(2) 359
inductance of telegraph circuit, (2)
368
E.M.F. generating spherical wave,
(2) 417
Inanity of ^, (2) 511
Index-surface, (2) 9
Inductance, (1) 354 ; (2) 28, 125
generalized, (2) 357
vanishing of, (2) 358
of straight wires, (1) 101 ; (2) 47
of cylinders, (2) 355
coils, (2) 37
of solenoid. (2) 277
(effective) of wires, (2) 64
(effective) of tubes, (2) 69, 192
ultimate form at great frequency, (2)
71
of iron and copper wires, (2) 261
of prisms, (2) 243
and permittance of lines, (2) 303
beneficial effect of, (2) 380, 393
increases amplitude, lessens distor-
tion, (2) 164, 308, 350
effect of increasing, (2) 121-3
of unclosed conductive circuit, (2) 502
of Hertz oscillator, (2) 503
Inductivity, (2) 28, 125
a constant with small forces, (2) 158
Induction, between parallel wires, (1)
116-141
in cores, (1) 353-416
balances with the Christie, (2) 33-38,
366
Inductize, (2) 40
Inductometer, (2) 110, 112, 167, 267
calibration of, (2) 110, 267
with equal coils, (2) 268
Inequalities between wires, (2) 305,
337
Inertia (magnetic), (1) 96; (2) 60
Influence between distant circuits,
telephony by, (2) 237
Intermitter, (2) 272
Intermittences, not S.H. variations,
(2) 270
Iron, divided, (2) 111, 113, 158
Ironic insulators, (2) 123
INDEX.
583
Intrinsic magnetic force, (1) 454
magnetization, (1) 451
electric force, (1)489
electrization, (1) 489
Inversion of vector operators, (2) 22
Irrational units, origin of, (1) 199
Jenkin, Fleeming, (1) 46, 125, 417
Joubert, (1) 116
Joule, (1) 283, 294
Joule's law, (1) 301
Kerr, (2) 574
Kirchhoff, laws, (1)4
theory of telegraph, (2) 81, 191, 395
Kohlrausch, (2) 271
Kundt, (2) 486-7
Lacoine, Emile, (I) 2, 23
Lamb, (1) 382
Leakage, effect on propagation, (1) 53,
71, 138, 535; (2) 71, 122
quickening effect of, (2) 252
Lenz, (1) 281, 482
Leroux, (1) 325
Light, (2)311
electromagnetic theory of, (2) 392
Lightning discharges, (2) 486
Limiting distance of telephony, (2) 121,
347
Linear network, property of, (2) 294
Lodge, 0. J., (1) 416-24; (2) 41, 438,
444, 483, 486, 503, 524, 527, 575
Long-distance telephony, (2) 119, 147,
349
Loop circuits, (2) 303
as induction balances, (2) 334
Mac, (2) 167
Magnetic induction, Faraday's idea of,
(1) 279
conductivity, (1) 441 ; effect of, (2)
480, 483
current, (1) 441, 442, 520
energy, (1) 445-8 ; due to current, (1)
517-19
impulse, (1) 504
retentiveness, (2) 41
force, example of independence of
permeability, (1) 517
disturbances from Sun, (2) 122
energy of moving charges, (1) 446
Magnetization, molecular, (2) 39
Magnetoelectric force, (1) 545 ; (2) 498
Magnus, (1) 313
Mance, (2) 294
Manganese steel, (2) 113
Maximum heat, (1) 499
energy, (1) 499
Maxwell, ;>aWw,
gravitational stress, (1) 544
magnetic stress, (2) 563
naturalness of his views, (1) 478
sketch of his theory, (1) 429-451
Mayer, (1) 294
Mechanical forces on magnets, (1) 457
action between two regions, (1) 548-
558
force between magnets and currents,
(1)556
Michelson, (2) 520
Microphone, theory of, (1) 181
Minimum heat, (1) 303-9, 497
Momentum, magnetic, (1) 59, 120, 480
persistence of, (2) 142, 145, 320, 481
Morse instrument, (1) 20, 23, 33
Motion of sphere through liquid, (1)
276
Motional electric force, (1) 448, 497
magnetic force, (1) 446, 497
Motion of medium, effect of, (2) 497
Mutual inductance, decrease by in-
creasing inductivity, (2) 112, 288
Neumann, J., formula, (1) 236, 281 ;
(2) 501, 503
Newton, (1) 291, 335, etc.
Nomenclature, (2)23-28, 165-8, 302, 327
Normal systems, size of, (2) 206
cylindrical, (1) 385, 393
in heterogeneous telegraph circuits,
(2) 223
general electromagnetic, (1) 521-531
of displacement in conductors, (1)
533
in shunted condensers, (1) 539
of current in wires, (2) 46, 51, 54
Oersted, (1)282
Ohm's law, (1) 282-6, 429
theory of propagation in wires, (1)
286 ; (2) 77, 191
O'Kinealy, (1) 94
Orthogonality of electric and magnetic
forces, (2) 221
Oscillations, condenser and coil, (1) 106 ;
(2)84
on long circuits, (I) 57, 132; (2) 85
got by reducing inductance, (1) 536
Oscillator, permittance and inductance
of, (2) 503
Oscillatory E.M.F. on a telegraph line,
(2) 61-76
subsidence of charge of condenser,
(1)532
subsidence in normal systems, (1) 526
584
ELECTRICAL PAPERS.
Peltier effect. (1) 310
Penetration of current into wires, ('2)
30,32
Permanent magnetic field of telephone,
(2) 156
Permeability, (1) 434
Permeance, (1) 512; (2) 24
Permittance of wires overground, (1)
42-46 ; (2) 159
of wires in loop, (2) 329
Poggendorff, (1)2, 23
Poisson, (1) 279
Pole, dimensions of magnetic, (1) 179
Polar distributions, subsidence of, (2)
469
Potential, of scalars, (1) 202
of vectors, (1) 203
characteristic equation of, (1) 218
in relation to curl, (1) 219
in relation to impressed force, (1) 349
not physical, (1) 502
metaphysical nature of propagation
of, (2) 483, 490
of circular magnetic shell, (1) 229
energy of magnets, (1), 457
Poynting, (2) 93-96, 172, 489, 490, 521,
522, 525, 527, 541
Preece, (2) 119, 160, 165, 305, 367, 380,
488-9
Pressural wave, (2) 485
Prescott, (2) 156
Prisms, magnetic induction in, (2) 240
Propagation along a wire, (2) 62, 82
general equations of, (2) 87-91
along a wire with variable constants,
(1)142; (2)222
along parallel wires, (1) 130, 136, 140
Pyroelectricity, (1) 493
Quaternions, (1) 207, 271 ; (2) 3, 376,
528, 556
Quincke, (2) 574
Rational units, (1) 199, 263 ; (2) 543
Rational current elements, (2) 500, 508
mutual energy of, (2) 501, 507
Rayleigh, Lord, (1) 299, 333, 365 ; (2)
63, 101, 274, 277, 367, 405, 445, 570
Ray, in direction of flux of energy,
(2) 16
Reaction of core currents on coil, (1) 370
Reciprocity, (1) 62, 128
Received current on telegraph cii*cuit,
(2)62
Reis, (1) 181
Reluctance, (2) 125, 168
Reluctivity, (2) 125, 168
Reciprocal relation of permittance and
inductance, (2) 221
Resistance of telegraphic lines, (1) 42
insulation, (1) 42
of carbon contacts, (1) 181
of earth, (1) 193
balances, true and false, (2) 37
increased, of wires, (2) 30, 37
effective, of wires, (2) 64
at great frequency, (2) 71
terminal, (1) 67, 155
negative (equivalent to), (1) 91, 167
• of tubes. (2) 69, 192
at great frequency, (2) 71
and inductance of wires, general
formulae, (2) 97, 278-9
ditto, induction longitudinal, (2) 99
table of increased, (2) 98
observation of increased, (2) 100
effective, of wires, balance, (2) 115
at front of a wave along a wire, (2) 436
Resistance operators, general, (2) 205,
355
elementary form of, (2) 356
S.H. form of, (2) 357
of telegraphic circuit, (2) 105
ditto, properties of, (2) 368
of infinitely long circuit, (2) 369
of distortionless circuit, (2), 370
in normal solutions, (2) 371
irrational, (2) 427
theorem relating to, (2) 373
spherical, (2) 439
cylindrical, (2) 447
Resistivity, (2) 24, 125
Resonance on telephone circuits, (2) 71,
73-76
Retardation, electrostatic, (1) 63
and permittance of looped wires, (2)
323
Roots, imaginary, (1) 89, 153, 159
Rotational property, (1) 289, 431, 451
Rowland, H. A., (1) 434; (2) 405
St. Venant, (2) 240
Salvation, (2) 576
Scalar product, (1) 431
Schwendler, (1)4
Seat of E.M.F., (1) 421
Seebeck, (1) 311, 314
Self-contained forced vibrations,
Plane, (2) 377
Spherical, (2) 365, 408, 419, 442
Cylindrical, (2) 365, 450, 454, 455,
458, 467
Self-induction, function of, (2) 396
Sensitiveness of Wheatstone's Bridge,
(1)4
table of, (1)11
Shunt, to differential galvanometer, (1)
17
to electromagnet, (1) 111
INDEX.
585
Siemens-Halske, duplex, (1) 19
Similar electrical systems, (2) 290
Slope of a scalar, (1) 212
Smith, Willoughby, (1) 47 ; (2) 28
Solutions, of electromagnetic equations,
(2) 469
distortionless, (2) 470
for plane waves in conducting di-
electric, (2) 473
Source of magnetic disturbances, (1)
425
Specific heat of electricity, (1) 313
Speculations, (1) 331-7
Specific capacity of conductors, (1) 495
Speed of current, (2) 121, 129
Spherical functions in plane waves, (2)
475
Stationary wave, (1) 548
Stokes, (2) 405, 538
formula for «/,„, (2) 467
Stresses (1) 542-558 ; (2) 533-574.
Stress vector, (1) 543 ; (2) 533, 572
force due to, (1) 544
torque due to, (1) 544 ; (2) 533
electric, (1) 545
Maxwellian, (1) 546; (2) 563
in plane waves, (1) 547
over surface, (1) 551, 554
rotational and irrotational, (2) 523
activity of, (2) 535
electromagnetic, (2) 549, 551
various kinds of, (2) 561-3
distortional and rotational activity,
(2) 535
statical indeterminateness of, (2) 558
Submarine cables, signalling on, (1) 47,
61, 71
Sumpner, (2) 367
Sun, long waves from, (2) 122, 392
Subsidence of induction in a core, (1)
398
of displacement in a conductor, (1) 533
of current in wires, (2) 49
of current in rectangular rods, (2) 243
Surface condition, (2) 170, 487
Surface conduction, (1) 440
Surface divergence, (1) 216
Sylvester, (2) 201
Tait, P. G., (1) 271, 324-5; (2) 3, 12,
91, 528
Tail of wave, (2) 124
growth of, (2) 318
positive, due to resistance, (2) 141,
318
negative, due to leakage, (2) 145, 320
general, due to both, (2) 150
Tangential continuity, (1) 505
Telegraphy, duplex, (1) 18-34
multiplex, (1)24
Telegraph lines, test for, (1) 41
circuits, classification of, (2) 340, 402
of low resistance, simplified theory,
(2) 343
nearly distortionless, (2) 345
periodic impressed force on, (2) 245
amplitude of received current on,
(2) 249, 400
with terminal apparatus, (2) 250,
401
Telephone, theory of, (2) 155
in induction balances, (2) 33
differential, (2) 33, 43
Telephony, conditions of good, (2) 121
improvement of, (2) 322
Temperature, absolute, (1) 317
Terminal conditions, theory of, (1), 144
conditions, treatment of, (2) 297
conditions, transcendental, (1) 169-72
arbitrary functions, (2) 208, 300
apparatus, effect of, (2) 353, 390, 400
condenser, (1) 85, 156
condenser and coil, (1) 157
induction coil and condenser, (1) 161
Thermodynamics, (1) 315-318, 481-488
Thermoelectric force, (1) 305-331, 441,
484
inversion, (1) 314
diagram, (1) 321
Theorem of divergence, (1) 209
of version, (1)211
of slope, (1)212
of normal systems, (2) 226
of electric and magnetic energy, (2)
360
of dependence of disturbances on
rotation, (2) 3(>1
Time-constants, (1) 57
Thompson, S. P., (1) 181 ; (2) 348, 492
Thomson, J. J., (2) 93, 396, 403, 405,
434, 443, 493, 495, 497, 505-7, 524,
558
Thomson, Sir W. (Lord Kelvin), passim
theory of telegraph, (1) 48, 74, 122,
286, 439 ; (2) 78, 191
thermodynamics, (1) 487
thermoelectricity, (1) 312, 319
magnetic energy, (1) 238
rotational effect, (1) 290
Volta force, (1) 417
sparking distance, (1) 298
Thomson effect, (1) 314
Transferability of impressed forces, (2)61
Transfer of energy, (1) 282, 378, 420;
(2) 174
in general, (2) 525-7
in stationary medium, (2) 541-2
in moving medium, (2) 546-7, 551, 572
along wires, (2) 95
circuital indeterminateness of, (2) 93
auxiliary inactive, (2) 94
586
ELECTRICAL PAPERS.
Transformer with conducting core, (2)
118
Transformation from ascending to
descending series, (2) 446
True current, Maxwell's, (1) 433
extended form, (2) 492, 497
criterion of, (2) 541, 547
expression for, in moving medium,
(2)561 m
Tube and wire coaxial, current longi-
tudinal, (2) 50-55
Tubes, coaxial, theory of, (2) 186, 208-15
Tumlirz, (2) 41
Tyndall, (1) 435
Units, rational and irrational, (1) 199,
262, 432 ; (2) 543, 576
names of, (2) 26
practical, multiplier for, (2) 577
Van Rysselberghe, (2) 250
Varley, C. F. , condenser patent, (1) 47
wave-bisector, (1) 63
gas resistance, (1) 286
Vectors, type for, (1) 199
scalar product of, (1) 431 ; (2) 5
circuital and polar, (1) 520
Vector, curl of a, (1) 199
potential of a, (1) 203
divergence of a, (1) 209, 215 ; (2) 5
function, division into circuital and
divergent parts, (1) 253
product, (1) 431 ; (2) 4
potential of magnetic current, (1)
467
Vector algebra, outline, (2) 4-8
fuller outline, (2) 528-33
to harmonize with Cartesian, (2) 3
Vector operators, (1) 430; (2) 6, 19,
532
conjugate property, (2) 533
differentiation of, (2) 544, 547-9, 562
Vector and scalar potential, insufficient
to specify state of field, (2) 173
Version, theorem of, (1) 211, 444 ; (2) 5
Velocity of electricity, (1) 435, 439 ; (2)
310, 393
of propagation of potential, (2) 484
of plane waves in eolo tropic medium,
(2) 1, 2, 3
Viscous fluid motion and conductive
diffusion, (1) 384
dissipation, (1) 382
Volta-force, (1) 337-42, 416-28
Voltage, transverse, (2) 189
Vortices (Maxwell's), (1) 333
Vorticity, (2) 363
Vortex line, circular, source of waves,
(2) 415
Waves of magnetic induction into cores,
(1) 361, 384
propagation of along wires, (1) 439 ;
(2)62
Wave-surface, duplex electromagnetic,
(2)15
features of, (2) 2
ellipsoidal, (2) 3
Fresnel's, (2) 1, 2
Waves, electromagnetic, (2) 375-520
generat-'on and propagation, (2) 377,
385
in conductors, with distortion re-
moved, (2) 378
in the P.O., (2)489
spherical, from moving charge, (2)
49
convective deflection of, (2) 519
infinite concentration of, (2) 465
reflected (solutions), (2) 387
Waves, plane, distorted, in conducting
medium, (2) 381
with distortion removed, (2) 379
general solution for, (2) 474
Fourier integrals for, (2) 474, 478
integration of differential equations
for, (2) 476
resulting from arbitrary initial states,
(2) 477
interpretation of distorted waves, (2)
479
Waves, spherical, in dielectric, (2) 402-
443
general, (2) 403
condensational, (2) 403
simplest type of, (2) 404
with conical boundaries, (2) 404-5
zonal harmonic, (2) 406
differential equation of, (2) 407
of first order ; generation of shell
wave, (2) 409
reflection at centre, (2) 410
magnetic energy constant, (2) 412
second order, (2) 413
from spherical sheet of radial force,
(2) 414
simply periodic, (2) 418, 443
Waves, spherical, in conductors, (2)
421
in conducting dielectrics, (2) 422
undistorted, (2) 425
general case, (2) 426
special solutions, (2) 427-436
effect of metal screens, (2) 440
effect of reflecting barriers, (2) 438
Waves, cylindrical, (2) 443-67
due to longitudinal impressed force
in thin tube, (2) 447
with two coaxial conducting tubes, (2)
449
effect of barrier on, (2) 451
INDEX.
587
Waves —
separate action of two surface sources
of, (2) 453
from a vortex filament, (2) 456
from a filament of impressed force
(2) 460
from a finite cylinder of impressed
force, (2) 461
Webb, F. H., (2) 83, 329
Weber's hypothesis, (1)296, 435; (2) 191
Weber, H., (2) 28
Wheatstone's bridge, (1)3; (2) 256
automatic, (1) 52, 62, 63
velocity of electricity, (2) 395
alphabetical indicator (oscillations),
(1)59
Williams, W., (2) 575
Winter, G. K., (1) 53
Wires, propagation along, (2), 190
approximate equations, (2), 333
Wire*—
S.H. waves along, (2) 195
resonance on, (2) 195
impedance fluctuations, (2) 196
practical working system of treating
propagation in terms of transverse
voltage and current, (2) 119
parallel, (2) 220
of varying resistance, etc., (2) 229
homogeneous, (2) 231
Wires and tubes, general equations, (2)
176
differential equations, (2) 179
normal systems, (2) 178, 180
magnetic theory of, (2) 181
S.H. voltage, solution, (2) 183
resistance operators of, (2) 188
Work done by impressed forces, (1)
462-5, 474
(double) of impressed force, (1) 456
END OF VOL. II.
ROBERT MACLKHOSE, PRINTER TO THE UNIYKRSITY, GLASGOW.
RETURN TO the circulation desk of any
University of California Library
or to the
NORTHERN REGIONAL LIBRARY FACILITY
Bldg. 400, Richmond Field Station
University of California
Richmond, CA 94804-4698
ALL BOOKS MAY BE RECALLED AFTER 7 DAYS
2-month loans may be renewed by calling
(415) 642-6753
1-year loans may be recharged by bringing books
to NRLF
Renewals and recharges may be made 4 days
prior to due date
DUE AS STAMPED BELOW
NOV ^ tnr
SENT ON ILL
OCT 2 7 1999
SEP 16
199?
I33J U. C. BERKELEY
flUfi I_8_2flni
1 n A lO*}9
ou^ £4 *jy
,,iRGU^
MAR 0 » ON*
JUL j3-»"
UNIVERSITY OF CALIFORNIA LIBRARY
Live Music Archive
Librivox Free Audio
Metropolitan Museum
Cleveland Museum of Art
Internet Arcade
Console Living Room
Books to Borrow
Open Library
TV News
Understanding 9/11